201102896 六、發明說明： 【發明所屬之技術領域】 胃 本發明係有關一種電容式觸控板，特別是關於一種電容式觸控 板的控制電路與方法及其應用。 【先前技術】 為實現電容式觸控板，一般以印刷電路板、玻璃或塑膠薄膜為 基底，在其上印刷金屬、銦錫氧化物導電薄膜或其他材質的圖 案做為感應器。依照應用的不同，感應器的形狀及大小亦不相 同。鐵筆或手指等導體接觸觸控板時’會在感應器上造成電容 變化，控制電路偵測感應器的電容變化量，以獲得使用者輸入 的資訊，據以進行觸控控制。因此，習知技術藉由增大因導體 接觸造成的電容變化量(AC)來提高觸控板的效能。例如美國專 利號5920309以互為反相的電流訊號對相鄰的感應器充放 電’藉由差動方式增加電容變化量，提升觸控板的效能。 然而’除了電容變化量之外，電容式觸控板的效能亦與其基本 電容(CBAse)相關。當基本電容較高時，電容變化量變得不明 顯，感應不易，因此效能降低。換言之，電容式觸控板的效能 正比於AC/Cbase。習知的差動偵測方式雖然提高了電容變化 量，卻同時增加了相鄰感應器之間的寄生電容’造成電容式觸 控板的基本電谷增大，因此效能改善的程度有限。 對此’發明人於中華民國專利申請案號第〇97142〇63號(美國 專利申凊破12/379,573)提出一種單端模式的電容侧電路及 方法，如圖1所示，電容式觸控板10上具有多個感應器12， 201102896 縱向的感應器12組成跡線(trace) XI、X2.....，橫向的 感應器12組成跡線Y卜Y2.....Ym，調變器16提供的電 流訊號Imodl和Imod2具有相同的相位，藉由類比多工器14 施加至選擇的跡線，調變成訊號muxl及mux2，解調器a以 直流電壓的參考訊號Mux_Vref解調訊號muxl，產生訊號 ppeak和npeak提供給電壓轉換電路20，在電壓轉換電路2〇 中’訊號減法器22將訊號ppeak和npeak調整成相同的準位， 再經增益電路24放大後提供給類比轉數位(A/D)轉換電路 26 ’以獲得電容式觸控板1〇上的電容變化資訊。增益電路％ 一般為電壓轉電流(Vto I)的訊號放大器。 為進一步改善電容式觸控板的效能，本發明提出一種單端彳貞測 電容式觸控板的控制電路與方法及其應用，以不同的調變及_ 調方法來減少電路複雜度，達到更廣的偵測範圍和更大的電容 介質厚度。 【發明内容】 本發明的目的之一，在於提出一種電容式觸控板的控制電路。 本發明的目的之一，在於提出一種電容式觸控板的控制方法。 本發明的目的之一，在於提出一種電容式觸控板模組。 根據本發明，一種電容式觸控板的控制電路與方法，在掃描訊 號對該電容式觸控板的第一跡線充放電的同時，提供與該掃描 訊號同相之訊號給該第一跡線鄰近的第二跡線，以及以與該掃 瞒訊號同相之參考訊號解調從該第一跡線取得的調變訊號。 根據本發明，一種電容式觸控板模組包括具有第一跡線及其鄰 201102896 近的第二跡線的電容式觸控板’調變器提供第一訊號以及與該 第一訊號具有相同相位的第二訊號，多工器耦接該電容式觸控 板及該調變器，將該第一訊號施加予該第一跡線而產生調變訊 號，以及將該第二訊號施加予該第二跡線，參考訊號調變器提 供與該調變訊號同相的參考訊號，以及解調器耦接該多工器以 及該參考訊號調變器，以該參考訊號解調該調變訊號，產生第 一解調訊號以及第二解調訊號。 根據本發明，對該第二跡線施加該第二訊號可降低該第一跡線 與該第二跡線之間的寄生電容，因而降低該電容式觸控板的基 本電容，增加感應量’並提供屏蔽效果，降低雜訊干擾’同時 達到簡化電路效果’提升該電容式觸控板的效能。 【實施方式】 圖2係根據本發明一實施例的示意圖，電容式觸控板一般 為玻璃材質、塑膠薄膜或印刷電路板，其上分佈有複數個以金 屬、銦錫氧化物導電薄膜或其他材質的圖案設置的感應器12， 這些感應器12組成X方向跡線XI〜xm和γ方向跡線 Y1〜Ym°調變器16提供的電流訊號Imodl和Imod2透過類比 多工器14施加至選擇的跡線，調變產生調變訊號muxl及 mux2，參考訊號調變器28調變產生參考訊號mux_ref，解調 器30以參考訊號mux_ref解調訊號⑺敗丨，輸出訊號卯從让和 npeak給電壓轉換電路32。 圖3繪示圖2中的調變/解調電路，解調器16包括電流源34、 36、38和40以及開關MO、Ml、M2和M3，開關MO、Ml、 201102896 M2和M3受控切換以供應電流Imodi和Imod2對電容ci和 C2充放電，因而產生調變訊號muxl和mux2。電容C1和C2 表示透過類比多工器14接受施加電流imodi和im〇(i2的第一 跡線和第二跡線的電容值。參考訊號調變器28由電流源42、 44和開關M4、M5組成，開關M4、M5受控切換以供應電流 Imod_ref對電容Crefl充放電而調變產生參考訊號mux_ref。 解調器30以參考訊號mux_ref解調訊號muxl，開關Ai、A2、 B1和B2受控切換產生解調訊號卯和叩，經低通濾波電路46 整流成電壓訊號ppeak和npeak。調節電流源34、36、38、40 和電"il源42、44可使產生的訊號ppeak和npeak等電位，因 此解調器30不再需要減法器，即可將訊號ppeak和叩eak提 供給增益電路24進行後續的訊號轉換，因此簡化了電路。 圖4係參考訊號調變器28的另一實施例，除了調變電流源42、 44、調變切換開關M4、M5及參考電容Crefl之外，還包括擺 動控制器48。本實施例藉由對參考電容Crefl同步充電/放電 • 產生與感應器端同相位的三角波，該三角波的擺動大小由數位 的擺動控制器48控制，經由調校(calibrati〇n)後，訊號muxl 的擺動可與參考訊號mux—ref相同。 圖5係習知差動模式解調器以全波解調產生之三角波訊號卯 和np的波形圖，訊號pp和np經過低通濾波器後產生電壓訊 就ppeak及npeak ’而ppeak及npeak之間會有壓差aV，因此 還為要讯號減法H 22將壓差減去Δν才能進人下—級的訊號 放大器24。 圖6係習知單端模式解調n以半波解魅生之半波訊號卯和 201102896 叩的波形圖，半波訊號pp和np經過低通濾波器後產生電壓 訊號ppeak及npeak ’而ppeak及npeak之間亦存在壓差av， 因此也需要訊號減法器22將壓差Δν減去.，才能進入丁一級 的訊號放大器24。 圖7係圖2之實施例的單端偵測調變的時序圖。參照圖3及圖 7，開關励、]VQ、M2和M3受控切換而供應電流Imodi和 Imod2分別對電容C1和C2充放電，調變產生三角波的電壓 訊號muxl和mux2。電流Imod_ref係藉由切換開關]vi4、M5 產生，對參考電容Crefl充放電而產生參考訊號mux_ref。在 本實施例中’調變訊號mux卜mux2和參考訊號muxj*ef為具 有相同相位的三角波。當有手指或導體接觸電容式觸控板1〇 時，訊號muxl的波形將出現變動，如虛線5〇所示。 圖8係圖2之實施例的單端偵測解調的時序圖。參照圖3及圖 8 ’脈波A和B控制開關Al、A2、B1和B2的切換，使解調 器30以訊號muxl和參考訊號muxjref解調出訊號pp與np。 訊號muxl的三角波經解調後分別成為訊號pp的上半波以及 Λ號np的下半波’一者加上參考訊號mux_ref形成一全波整 流。經調校後’訊號muxl與mux_ref的擺動可以十分接近甚 至相等，因此，經過低通濾波電路46產生之電壓訊號ppeak 及npeak的電位得以接近或相等，不需再經訊號減法器調整電 壓訊號ppeak及npeak之間的壓差，即可直接進入下一級的訊 號放大器24。當導體或手指接觸電容式觸控板1〇時，訊號 muxl會產生變化，由於訊號pp和叩都具有部份的訊號 muxl，其電壓也會隨之產生變化，如圖8中的虛線所示，濾 201102896 波產生之訊號ppeak和npeak亦因而改變，出現av2的電壓 差。 除了使用電壓轉電流的訊號放大器24之外，亦可如圖9所示， 透過可程式化增益放大器(Programmable Gain Amplifier; PGA) 52將電壓訊號ppeak、npeak放大，再解析出訊號。 本發明提出之調變/解調方式不再侷限於以三角波充電/放電。 例如在調變器中設置不同大小的電流源，以不同大小的電流對 跡線充放電而產生如圖10所示之多邊形訊號muxl和mux2， 再辅以同相的參考訊號mux_ref，解調出波形近似的訊號pp 和叩’訊號pp和np經過低通濾波器46濾波後，仍可呈現兩 個電位相等且近似直流電壓的訊號ppeak及npeak。以圖1〇所 不之波形進行偵測和解調時，取得的電容值為圖中斜線區域的 積分，因此其測得的電容變化值可以比三角波偵測的更為明 顯，提供更廣的偵測範圍或更大的電容介質厚度。 圖Π及圖12分別繪示其他型式調變/解調變的波形圖，產生 故些波形的技術為習知技術，因此不再詳述。當使用各種不同 的波形做為muxl和mux2，只要提供具有相同相位的參考訊 錢行解調，仍可獲得電位相等的直流電壓訊號ppeak及 npeak。 將本發明應用於電容式觸控板時，如圖13所示，可以將第一 讯號Imodl提供給第一跡線知調雙產生訊號mux卜同時將 與第一訊號Imodl同相的第二訊號Im〇d2提供給與第一跡線 处相鄰的第二跡線Xn+1和Xn-1。如圖14所示，由於使用同 相之調變時脈_變，產生的訊號讎i 、mux2為同相，其中 201102896 只有第-跡線Χη的訊號muxl是真正接受解調的訊號與第 一跡線Xn相鄰的第二跡線处+1和的訊號則有如 交流的屏蔽(shielding)訊號一般，不但避免訊號㈤受雜訊干 擾’同時減少跡線如、处和Xn+1之間的電位差，因此降 低第跡線Χη與第二跡線群处+1和处之間的寄生電容 Cpl和Cp2 ’換言之，降低了基本電容。 圖15係應用本發明之第三實施例的示意圖。參照圖2及圖n 當欲掃描麟Χη時，類比乡以電流ImQdl對跡線知 充放電而產生訊號卿u，同時以電流Im〇d2對跡線处兩側 的多條跡線Xn-j〜Xn_l以及Xn+1〜处+丨充放電而產生訊號 mux2，同樣改善相鄰跡線之間的寄生電容，並提供更好的屏 蔽效果。 圖16係應用本發明之第四實施例的示意圖，一次掃描多條跡 線Χη〜Xn+b ’在以電流imocji對跡線充放電而產生 §K號muxl的同時’將與電流同相之電流Im〇d2提供給 跡線Xn-j〜Χη-I及跡線Xj^+b+i〜Xjj+b+i，產生電壓訊號 mux2 ’以利偵測跡線x^xn+b的電容變化。 圖17係應用本發明於Y方向跡線的示意圖，跡線γη〜Yn+b 調變產生訊號muxl，同時，於跡線γη〜Yn+b兩側的跡線 Yn-j〜Yn-1以及跡線Υη+b+l〜Yn+b+i調變產生訊號mux2。 本發明提出之控制電路及方法不受感應器形狀及尺寸的限 制。圖18及圖19係常見的電容感應器。圖μ中，X方向感 應器54為多邊形’ Υ方向感應器56為菱形。圖19中，X方 向感應器58和Υ方向感應器60皆為菱形，其中，X方向感 201102896 應器58之間以橋接線(圖中未示)互相連接，而γ方向感應器 60則直接相連。在其他實施例中，單位電容感應器可以是圓 形或其他形狀’亦可針對面積做挖空調整。 - 圖2〇係本發明應用於一維感應器的示意圖。在以訊號muxi 偵測感應器64的電容變化的同時，對感應器64相鄰兩側之感 應器62及66充放電以調變產生同相訊號mux2，減低感應器 64與感應器62、66之間的寄生電容並降低雜訊干擾。 本發明提出之電容式觸控板的控制電路及方法，藉由提供同相 馨 訊號降低相鄰導體之間的寄生電容，減少觸控板的基本電容以 提升感應量，再配合調變/解調變波形，可以提供更廣的偵測 範圍和更大的電容介質厚度，進一步提升電容式觸控板的效 能。 以上對於本發明之較佳實施例所作的敘述係為卿之目的，而 無意限定本發明精確地為所揭露的形式，基於以上的教導或從 本發明的實施例學料作修改或變化是可能的，實施例係為解 • 說本發明的原理以及讓熟習該項技術者以各種實施例利用本 發明在實際應用上而麵及敘述，本發日_技術思想企圖由以 下的申請專利範圍及其均等來決定。 【圖式簡單說明】 圖1是習知單端伽，丨電容式觸控板模_示意圖； 圖2是根據本發明之單端_電容式觸控板模組一實施例的 示意圖； 圖3繪示圖2之實施例中的調變及解調變電路； 201102896 圖4係參考訊號調變器一實施例的示意圖； 圖5係習知差動模式解調器以全波解調產生之三角波訊號卯 和np的波形圖； 圖6為習知單端模式解調器以半波解調產生之半波訊號即和 np的波形圖； 圖7係圖2之實施例的單端偵測調變時序圖； 圖8係圖2之實施例的單端偵測解調變時序圖； 圖9係以PGA放大解調訊號的示意圖； _ 圖10是以多邊形波實現本發明之調變及解調的時序圖； 圖11是以方波實現本發明之調變及解調的時序圖； 圖12是以另一種不規則波形實現本發明之調變及解調的時序 圖； 圖13係應用本發明之第二實施例的示意圖； 圖14係圖13之實施例中寄生電容的示意圖： 圖15係應用本發明之第三實施例的示意圖； • 圖16係應用本發明之第四實施例的示意圖； 圖17係將本發明應用在γ方向感應器上的實施例示意圖； 圖18及圖19繪示常見的電容感應器；以及 圖20係本發明應用於一維感應器的示意圖。 【主要元件符號說明】 10 電容式觸控板 12 感應器 類比多工器 i S1 201102896201102896 VI. Description of the Invention: [Technical Field of the Invention] The present invention relates to a capacitive touch panel, and more particularly to a control circuit and method for a capacitive touch panel and an application thereof. [Prior Art] In order to realize a capacitive touch panel, a printed circuit board, a glass or a plastic film is generally used as a substrate, and a pattern of a metal, an indium tin oxide conductive film or the like is printed thereon as an inductor. The shape and size of the sensor are different depending on the application. When a conductor such as a stylus or a finger touches the touchpad, a capacitance change occurs on the sensor, and the control circuit detects the amount of capacitance change of the sensor to obtain information input by the user, thereby performing touch control. Therefore, the prior art improves the performance of the touch panel by increasing the amount of capacitance change (AC) caused by the conductor contact. For example, U.S. Patent No. 5920309 charges and discharges adjacent sensors with mutually inverted current signals. The differential capacitance increases the amount of capacitance change to improve the performance of the touch panel. However, in addition to the amount of capacitance change, the performance of a capacitive touch panel is also related to its basic capacitance (CBAse). When the basic capacitance is high, the amount of capacitance change becomes unnoticeable, and the inductance is not easy, so the performance is lowered. In other words, the performance of a capacitive touchpad is proportional to AC/Cbase. The conventional differential detection method increases the capacitance variation, but at the same time increases the parasitic capacitance between adjacent inductors, resulting in an increase in the basic electric valley of the capacitive touch panel, so the degree of performance improvement is limited. In this case, the inventor's patent application No. 97142〇63 (U.S. Patent Application Serial No. 12/379,573) proposes a single-ended mode capacitor side circuit and method, as shown in Fig. 1, capacitive touch The board 10 has a plurality of sensors 12, 201102896 The longitudinal sensors 12 form traces XI, X2....., and the lateral sensors 12 form the traces Yb.....Ym, tune The current signals Imodl and Imod2 provided by the transformer 16 have the same phase, are applied to the selected trace by the analog multiplexer 14, and are modulated into signals muxl and mux2, and the demodulator a demodulates the signal with the reference signal Mux_Vref of the direct current voltage. The mux1, the generated signals ppeak and npeak are supplied to the voltage conversion circuit 20, and in the voltage conversion circuit 2, the signal subtractor 22 adjusts the signals ppeak and npeak to the same level, and then the gain circuit 24 amplifies and supplies the analog to the digital digit. The (A/D) conversion circuit 26' obtains capacitance change information on the capacitive touch panel 1''. The gain circuit % is typically a voltage-to-current (Vto I) signal amplifier. In order to further improve the performance of the capacitive touch panel, the present invention provides a control circuit and method for a single-ended snubber capacitive touch panel and an application thereof, and reduces the circuit complexity by using different modulation and modulating methods. A wider detection range and a larger capacitive medium thickness. SUMMARY OF THE INVENTION One object of the present invention is to provide a control circuit for a capacitive touch panel. One of the objects of the present invention is to provide a method of controlling a capacitive touch panel. One of the objects of the present invention is to provide a capacitive touch panel module. According to the present invention, a control circuit and method for a capacitive touch panel provides a signal in phase with the scan signal to the first trace while the scan signal charges and discharges the first trace of the capacitive touch panel. An adjacent second trace, and a reference signal taken in phase with the broom signal, demodulates the modulated signal obtained from the first trace. According to the present invention, a capacitive touch panel module includes a capacitive touch panel having a first trace and a second trace adjacent to 201102896. The modulator provides a first signal and has the same signal as the first signal. a second signal of the phase, the multiplexer is coupled to the capacitive touch panel and the modulator, applying the first signal to the first trace to generate a modulation signal, and applying the second signal to the second signal a second trace, the reference signal modulator provides a reference signal in phase with the modulation signal, and the demodulator is coupled to the multiplexer and the reference signal modulator, and the modulation signal is demodulated by the reference signal. A first demodulation signal and a second demodulation signal are generated. According to the present invention, applying the second signal to the second trace can reduce the parasitic capacitance between the first trace and the second trace, thereby reducing the basic capacitance of the capacitive touch panel and increasing the sensing amount. And provide shielding effect, reduce noise interference 'at the same time to simplify the circuit effect' to improve the performance of the capacitive touch panel. 2 is a schematic view of a capacitive touch panel generally comprising a glass material, a plastic film or a printed circuit board, on which a plurality of conductive films of metal, indium tin oxide or the like are distributed. The patterns 12 of the material are arranged, and the inductors 12 constitute the X-direction traces XI to xm and the γ-direction traces Y1 to Ym. The current signals Imod1 and Imod2 provided by the modulator 16 are applied to the selection through the analog multiplexer 14. The traces are modulated to generate the modulation signals muxl and mux2, the reference signal modulator 28 is modulated to generate the reference signal mux_ref, the demodulator 30 is demodulated by the reference signal mux_ref (7), and the output signal is given from the sum and npeak. Voltage conversion circuit 32. 3 illustrates the modulation/demodulation circuit of FIG. 2, the demodulator 16 includes current sources 34, 36, 38, and 40 and switches MO, M1, M2, and M3, and the switches MO, M1, 201102896 M2, and M3 are controlled. Switching supplies the currents Imodi and Imod2 to charge and discharge the capacitors ci and C2, thus generating the modulation signals muxl and mux2. Capacitors C1 and C2 represent the application of currents imodi and im 透过 through the analog multiplexer 14 (the capacitance values of the first and second traces of i2. The reference signal modulator 28 is comprised of current sources 42, 44 and switch M4, M5 is composed, and switches M4 and M5 are controlled to switch to supply current Imod_ref to charge and discharge capacitor Cref1 to generate reference signal mux_ref. Demodulator 30 demodulates signal mux1 with reference signal mux_ref, and switches Ai, A2, B1 and B2 are controlled Switching generates demodulation signals 卯 and 叩, which are rectified into voltage signals ppeak and npeak by low-pass filter circuit 46. Adjusting current sources 34, 36, 38, 40 and electric "il sources 42, 44 can generate signals ppeak and npeak Equipotential, so demodulator 30 no longer needs a subtractor, and can provide signals ppeak and 叩eak to gain circuit 24 for subsequent signal conversion, thus simplifying the circuit. Figure 4 is another reference signal modulator 28 The embodiment includes a swing controller 48 in addition to the modulated current source 42 and 44, the modulation switching switch M4, M5 and the reference capacitor Cref1. In this embodiment, the charging/discharging is synchronously performed by the reference capacitor Cref1. Three in phase The amplitude of the wobble of the triangular wave is controlled by the digital wobble controller 48. After the calibration, the wobble of the signal mux1 can be the same as the reference signal mux-ref. Fig. 5 is a conventional differential mode demodulator The waveform of the triangular wave signal 卯 and np generated by full-wave demodulation, the signals pp and np pass through the low-pass filter to generate voltage signals on ppeak and npeak 'and there is a voltage difference aV between ppeak and npeak, so it is still necessary Signal subtraction H 22 subtracts Δν from the differential pressure to enter the lower-level signal amplifier 24. Figure 6 is a waveform diagram of a conventional single-ended mode demodulation n with a half-wave enchanted half-wave signal 201 and 201102896 叩The half-wave signals pp and np pass through the low-pass filter to generate voltage signals ppeak and npeak ', and there is also a voltage difference av between ppeak and npeak. Therefore, the signal subtractor 22 is also required to subtract the differential pressure Δν. Level 1 signal amplifier 24. Figure 7 is a timing diagram of single-ended detection modulation of the embodiment of Figure 2. Referring to Figures 3 and 7, switching excitation, ]VQ, M2, and M3 are controlled to switch currents to supply current Imodi and Imod2. Charge and discharge capacitors C1 and C2, respectively, to generate a triangular wave of electricity The signals mux1 and mux2. The current Imod_ref is generated by the switching switches vi4 and M5, and the reference capacitor Cref1 is charged and discharged to generate the reference signal mux_ref. In the present embodiment, the 'modulation signal mux mu and the reference signal muxj*ef have A triangular wave of the same phase. When a finger or conductor contacts the capacitive touch panel, the waveform of the signal mux1 will change, as indicated by the broken line 5〇. FIG. 8 is a timing diagram of single-ended detection and demodulation in the embodiment of FIG. Referring to Figs. 3 and 8 'pulse A and B control switches A1, A2, B1 and B2, the demodulator 30 demodulates the signals pp and np with the signal mux1 and the reference signal muxjref. The triangular wave of the signal muxl is demodulated and becomes the upper half of the signal pp and the lower half of the nick np, respectively, and the reference signal mux_ref forms a full-wave rectification. After the adjustment, the swings of the signals muxl and mux_ref can be very close or even equal. Therefore, the potentials of the voltage signals ppeak and npeak generated by the low-pass filter circuit 46 are close or equal, and the voltage signal is not required to be adjusted by the signal subtractor. And the voltage difference between npeak, you can directly enter the next level of the signal amplifier 24. When the conductor or finger touches the capacitive touch panel 1,, the signal muxl will change. Since the signals pp and 叩 have a partial signal muxl, the voltage will also change, as shown by the dotted line in FIG. The signal ppeak and npeak generated by the filter 201102896 wave are also changed, and the voltage difference of av2 appears. In addition to the voltage-to-current signal amplifier 24, as shown in FIG. 9, the voltage signals ppeak and npeak are amplified by a programmable gain amplifier (PGA) 52, and the signals are analyzed. The modulation/demodulation method proposed by the present invention is no longer limited to charging/discharging with a triangular wave. For example, in the modulator, different current sources are set, and the currents of different magnitudes are charged and discharged to generate the polygon signals muxl and mux2 as shown in FIG. 10, and then the in-phase reference signal mux_ref is used to demodulate the waveform. The approximate signals pp and 叩' signals pp and np are filtered by the low-pass filter 46 to still present two signals ppeak and npeak of equal potential and approximately DC voltage. When detecting and demodulating the waveforms in Figure 1, the obtained capacitance is the integral of the oblique line in the figure, so the measured capacitance change value can be more obvious than the triangular wave detection, providing a wider detection. Measure the range or larger capacitance medium thickness. FIG. 12 and FIG. 12 respectively show waveform diagrams of other types of modulation/demodulation, and the techniques for generating the waveforms are conventional techniques, and therefore will not be described in detail. When a variety of different waveforms are used as muxl and mux2, as long as the reference signal demodulation with the same phase is provided, DC voltage signals ppeak and npeak of equal potential can be obtained. When the present invention is applied to a capacitive touch panel, as shown in FIG. 13, the first signal Imod1 can be supplied to the first trace to determine the double generating signal mux and the second signal in phase with the first signal Imod1. Im〇d2 is supplied to the second traces Xn+1 and Xn-1 adjacent to the first trace. As shown in FIG. 14, the signals 雠i and mux2 are in phase due to the use of the in-phase modulation clock, wherein only the signal mux1 of the first-trace Χn is the signal that is actually demodulated and the first trace. The signal of +1 and the signal at the second trace adjacent to Xn is like the shielding signal of the alternating current, which not only avoids the interference of the signal (5) by noise, but also reduces the potential difference between the trace and the trace, such as Xn+1. Therefore, the parasitic capacitances Cpl and Cp2' between the first trace Χn and the +1 and the second trace group are lowered, in other words, the basic capacitance is lowered. Figure 15 is a schematic view showing a third embodiment to which the present invention is applied. Referring to Fig. 2 and Fig. n, when the Χn η is to be scanned, the analog township uses the current ImQdl to charge and discharge the trace to generate the signal u, while the current Im 〇d2 pairs the traces on both sides of the trace Xn-j ~Xn_l and Xn+1~where + charge and discharge generate signal mux2, which also improves the parasitic capacitance between adjacent traces and provides better shielding effect. Figure 16 is a schematic view showing a fourth embodiment of the present invention, in which a plurality of traces Χn to Xn+b' are scanned at a time to charge and discharge a trace with a current imocji to generate a §K muxl while a current which is in phase with the current Im〇d2 is supplied to the traces Xn-j~Χη-I and the traces Xj^+b+i~Xjj+b+i, and the voltage signal mux2' is generated to detect the change in capacitance of the trace x^xn+b. Figure 17 is a schematic view showing the application of the present invention in the Y-direction trace, the traces γη~Yn+b are modulated to produce the signal muxl, and the traces Yn-j~Yn-1 on both sides of the traces γn~Yn+b and The trace Υη+b+l~Yn+b+i is modulated to produce the signal mux2. The control circuit and method proposed by the present invention are not limited by the shape and size of the inductor. 18 and 19 are common capacitance sensors. In Fig. 51, the X-direction sensor 54 has a polygonal shape, and the Υ direction sensor 56 has a diamond shape. In FIG. 19, the X-direction sensor 58 and the Υ-direction sensor 60 are both diamond-shaped, wherein the X-direction sensor 201102896 is connected to each other by a bridge wire (not shown), and the γ-direction sensor 60 is directly connected. Connected. In other embodiments, the unit capacitance sensor can be circular or otherwise shaped to make a knockout adjustment for the area. - Figure 2 is a schematic view of the invention applied to a one-dimensional inductor. While detecting the change of the capacitance of the sensor 64 by the signal muxi, the inductors 62 and 66 on the adjacent sides of the inductor 64 are charged and discharged to be modulated to generate the in-phase signal mux2, and the inductor 64 and the inductor 62, 66 are reduced. Parasitic capacitance between them and reduces noise interference. The control circuit and method of the capacitive touch panel provided by the invention reduce the parasitic capacitance between adjacent conductors by providing the in-phase sinus signal, reduce the basic capacitance of the touch panel to increase the sensing amount, and cooperate with the modulation/demodulation Variable waveforms provide a wider detection range and a larger capacitive dielectric thickness, further enhancing the performance of capacitive touch panels. The above description of the preferred embodiments of the present invention is intended to be illustrative, and is not intended to limit the scope of the invention to the disclosed embodiments. It is possible to make modifications or variations based on the above teachings or from the embodiments of the present invention. The present invention is to explain the principles of the present invention and to enable those skilled in the art to use the present invention in various embodiments to practice and describe the present invention. It is equal to decide. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic diagram of a conventional single-ended gamma, tantalum capacitive touch panel module; FIG. 2 is a schematic diagram of an embodiment of a single-ended _capacitive touch panel module according to the present invention; The modulation and demodulation circuit in the embodiment of FIG. 2 is shown; 201102896 FIG. 4 is a schematic diagram of an embodiment of a reference signal modulator; FIG. 5 is a conventional differential mode demodulator generated by full-wave demodulation FIG. 6 is a waveform diagram of a half-wave signal and np generated by a conventional single-ended mode demodulator by half-wave demodulation; FIG. 7 is a single-ended detection of the embodiment of FIG. FIG. 8 is a schematic diagram of a single-ended detection and demodulation variable according to the embodiment of FIG. 2; FIG. 9 is a schematic diagram of a PGA amplification and demodulation signal; _ FIG. 10 is a modulation of the present invention by a polygon wave. And a timing chart for demodulation; FIG. 11 is a timing chart for realizing the modulation and demodulation of the present invention with a square wave; FIG. 12 is a timing chart for realizing the modulation and demodulation of the present invention with another irregular waveform; A schematic diagram of a second embodiment of the present invention is applied; FIG. 14 is a schematic diagram of a parasitic capacitance in the embodiment of FIG. 13: FIG. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 16 is a schematic view showing a fourth embodiment to which the present invention is applied; FIG. 17 is a view showing an embodiment in which the present invention is applied to a gamma direction sensor; FIG. 18 and FIG. A common capacitive sensor is shown; and Figure 20 is a schematic illustration of the application of the present invention to a one-dimensional inductor. [Main component symbol description] 10 Capacitive touch panel 12 Sensor Analog multiplexer i S1 201102896
16 調變器 18 解調器 20 電壓轉換電路 22 訊號減法器 24 訊號放大器 26 類比轉數位轉換電路 28 參考訊號調變器 30 解調器 32 電壓轉換電路 34 電流源 36 電流源 38 電流源 40 電流源 42 電流源 44 電流源 46 低通濾波電路 50 虛線 52 可程式化增益放大器 54 X方向感應器 56 Y方向感應器 58 X方向感應器 60 Y方向感應器 62 感應器 64 感應器 201102896 66 感應器16 Modulator 18 Demodulator 20 Voltage Conversion Circuit 22 Signal Subtractor 24 Signal Amplifier 26 Analog-to-Digital Converter Circuit 28 Reference Signal Modulator 30 Demodulator 32 Voltage Conversion Circuit 34 Current Source 36 Current Source 38 Current Source 40 Current Source 42 Current Source 44 Current Source 46 Low Pass Filter Circuit 50 Dotted Line 52 Programmable Gain Amplifier 54 X Direction Sensor 56 Y Direction Sensor 58 X Direction Sensor 60 Y Direction Sensor 62 Sensor 64 Sensor 201102896 66 Sensor
.[S] 13.[S] 13