TW201029306A - Power converter - Google Patents

Abstract

A power converter includes: a filtering unit, a first power factor correction unit, a second power factor correction unit, and a resonance conversion unit. The resonance conversion unit includes a full-bridge switch circuit and a resonance circuit. The full-bridge switch circuit includes a first switch, a second switch, a third switch, and a fourth switch. The four switches are switched between conduction and cut-off states, so as to generate an AC converted voltage shown as a square wave. The first power factor correction unit and the second power factor correction unit perform power factor corrections according to the switching of the first switch and the second switch, respectively. Because only one set of the switches is required to operate with the power factor correction units and the resonance conversion unit to perform circuit operation, it is able to achieve the purposes of reducing the number of electronic components and simplifying the control process.

Description

201029306 VI. Description of the Invention: [Technical Field] The present invention relates to a power conversion device, particularly to a single-stage high power factor power conversion device. [Prior Art] In order to avoid the waveform of the AC power supply voltage at the input end caused by the pulse current waveform generated by the power conversion device, and to improve the power factor of the external power supply at the input terminal, reduce the total harmonic distortion of the current, and improve the utilization rate of the power device. Some two-stage AC/DC power conversion devices have been proposed to 'add a power factor correction circuit between the external AC power supply and the DC/DC converter, perform AC/DC conversion, and make the input current sinusoidal and It is in phase with the voltage of the external power supply to reduce the total harmonic distortion of the current and improve the power factor, and then convert the output DC voltage of the power correction circuit into a voltage value corresponding to the load via the DC/DC converter. However, this two-stage circuit requires the use of two control circuits and more electronic components, which results in a higher product price, and requires two energy conversion processes to reduce the overall circuit conversion efficiency. In order to overcome the shortcomings of the two-stage power conversion device, a number of single-stage conversion devices incorporating a power correction circuit and a DC/DC converter have been proposed, such as the paper "MZYoussef, and PK Jain, "Analysis and Design of a Single-stage. AC-DC Front-end Resonant Converter with a New Active Control Technique, "Proceedings of the Power Electronics Specialists Conference, PESC, June 2007, pp. 17-21." The disclosed technology, although sharing switches to reduce electrons Component 201029306 'But' these single-stage architecture circuits have several shortcomings that need to be improved: (1) The circuit architecture is complex and requires many additional electronic components. (2) The control method that satisfies both the high power correction factor and the DC output voltage regulation is too complicated and not feasible. (3) The active switch cannot operate at zero voltage switching conduction.

(4) The current loop contains many power switches, increasing conduction losses and limiting the space for improved efficiency. SUMMARY OF THE INVENTION Accordingly, it is an object of the present invention to provide a power conversion apparatus which provides high conversion efficiency and which avoids the above-mentioned conventional drawbacks. The power conversion device includes: a filtering unit that receives an AC input voltage and an input current, and provides an AC filtered voltage and a pulse current; the first power factor correcting unit receives the filtered voltage and the pulse current And generating a first correction voltage of the continuous current; a first power factor correction unit receiving the filtered voltage and the pulse current ' and generating a second correction voltage of -DC, and causing the second correction voltage and the third The positive voltage is added to add a total voltage; and, the full bridge switch circuit includes a first switch ..... surgery: two or four switches 'the full bridge switch circuit receives the sum signal, 』 Μ - switch To the fourth switch between the on state and the wear state, the resonance conversion unit includes a full bridge switch circuit and a second switch of the resonance circuit, a 201029306 change, to generate an alternating current and a square wave conversion voltage, The resonant circuit receives the converted voltage, and filters the DC component and the high frequency harmonic component of the converted voltage by the series inductance and the series capacitance of the resonant circuit to generate an alternating current switching current; The first power factor correcting unit adjusts the pulse current during the positive half cycle of the filtered voltage according to the switching of the first switch to correct the input voltage and the power factor of the input current, and the filtering The voltage is converted into the first correction voltage, and the second power factor correcting unit adjusts the pulse current during the negative half cycle of the filtered voltage according to the switching of the fourth switch, to correct the input voltage and the input current. And converting the filtered voltage to the second modified voltage, the filtering unit filtering out the frequency harmonic component of the pulse current-to make the input current substantially sinusoidal. The above and other technical contents, features, and advantages of the present invention will be apparent from the following detailed description of the preferred embodiments. Referring to FIG. 1, a preferred embodiment of the power conversion device of the present invention is suitable for converting an input voltage I of an alternating current source into an output current sv〇' of a continuous stream and comprising: a filtering unit 2; The first power factor correction unit 21, a second power factor correction unit 22, and a resonance conversion unit are electrically connected to the external power source, and receive the input voltage Vin and the __ input current provided by the external power source. &, and provide - the AC wave voltage and the pulse current iP, and filter out the high frequency harmonic component of the pulse current ip 'so that the input current from the external power source ^ is sinusoidal, and the package 201029306 includes an input An inductor Lm, and an input capacitor Cm, the input inductor Lm includes a first end electrically connected to the external power source to receive the input voltage Vin and the input current iin and a second end of the output filter voltage and the pulse current ip. The input capacitor Cm includes a first end and a second end electrically connected to the second end of the input inductor Lm.

The first power factor correcting unit 21 is electrically connected to the filtering unit 2, and receives the filtered voltage and the pulse current ip, and generates a first correcting voltage vdel of a continuous current, and includes a first diode Di and a The first switch & a third diode D3, a first winding Li, and a first capacitor. The first diode D1 has an anode and a cathode electrically connected to the second end of the input inductor to receive the filtered voltage and the pulse current ip. The third diode D3 has a cathode electrically connected to the cathode of the first diode and an anode. The first winding Li has a first end (polar point end) and a second end (non-polar point end) electrically connected to the first diode body. The first valley cdcl is electrically connected between the polarity end of the first winding Li and the anode of the third diode D3, and the voltage across the first correction voltage Vdcl. The second power factor correcting unit 22 is electrically connected to the filtering unit 2 and the first power factor correction unit A 21 'and (4) filters the wave voltage and the pulse current ip, and generates a second correction of -DC ν & 2, and the second correction voltage vdc2 and the first correction voltage Vdci are summed into a total voltage, and includes a second diode D2, a fourth switch ~, - a fourth diode d4, a second winding L2 and a second capacitor Cdc2. The second diode d2 has a cathode and an anode electrically connected to the seventh end of the input inductor 7201029306 to receive the filtered voltage and the pulse current ip. The fourth diode 〇4 has an anode electrically connected to the anode of the second diode h and a cathode electrically connected to the anode of the third diode A. The second winding L2 has a first a terminal (polar point end) and a second end (non-polar point end) electrically connected to the anode of the second diode D2. The second capacitor Cdd is electrically connected to the polarity end of the second winding L2 and the The voltage between the cathodes of the fourth diode and the two ends thereof is the second correction voltage Vdc2. Because of the second capacitance Cdc2 The first capacitor Cdcl is connected in series, so the second correction voltage and the first correction voltage vdcl are summed into the total voltage. In this embodiment, the first winding q and the second winding L2 can be wound around the same shovel. (not shown), it can also be wound in two different iron cores (not shown). The resonance conversion unit 3 includes a full bridge switching circuit 31, a resonant circuit 32' and an alternating current to direct current conversion circuit. The full bridge switching circuit 31 receives the summed voltage and has a first switch Si, a first switch S2, a second switch S3, and a fourth switch S4, and the first switch S The fourth switch S4 is switched between an on state and an off state to generate an alternating current and a square wave switching voltage. The first switch Si has a first end electrically connected to a polarity end of the first winding Li2, A second end (labeled as point A) of the second end of the input capacitor Cm is coupled to a control terminal, and the control terminal is controlled to switch the first switch Si between an on state and an off state. The second switch S2 has an electrical connection to the first winding ^ The first end of the polarity end, the second end (labeled as point B in the figure) and the control end, the control terminal of the 201029306 is controlled to switch the second switch S2 between the on state and the off state. The voltage between the second end of a switch S1 and the second end of the second switch & (ie, the voltage between points A and B) is the converted voltage. The third switch S3 has an electrical connection to the a first end of the second end of the second switch core, a second end electrically connected to the polarity end of the second winding 12, and a control end, the control end being controlled to make the third switch S3 in an on state and Switching between the off-states. The fourth switch S4 has a first end electrically connected to the second end of the first switch core, a second end electrically connected to the polarity end of the second winding 12, and a control end. The control terminal is controlled to switch the fourth switch core between an on state and an off state. The resonant circuit 32 receives the converted voltage of the full bridge switching circuit 31, and filters the DC component and the high frequency harmonic component of the converted voltage by resonance to generate an alternating current converting current 'and has a transformer Τι, A series inductor Ls and a series capacitor cs. The transformer 包括1 includes two windings wound around a core (not shown), a second winding L3' and a fourth winding, a polarity point end and a non-polar point end. L4. And each winding has the series inductance Ls, the series capacitances cs and Cs, and the third winding L3 at the first

9 201029306

And electrically connected to the fourth winding 145, the diode A has an anode electrically connected to the fourth receiving the switching current and a cathode electrically connected to the anode of the anode of the fifth diode A a cathode of the non-polar point of the group L4, the eighth diode d8 having an anode electrically connected to the non-polar point end of the fourth winding u to receive the switching current and an electrical connection to the sixth diode The cathode of the cathode of the body. - the output capacitor c is electrically connected between the anode of the seventh diode d7 and the cathode of the eighth diode 〇8, and the voltage across the output voltage V is the first power factor correction The unit 21 operates the first winding L1 in the discontinuous conduction mode and the current ipi during the positive half cycle of the filtered voltage (also during the positive half cycle of the input voltage vin) according to the switching of the first switch S1. Presenting a two-wave waveform, and the peak value of the current ipi is proportional to the input voltage vin of the alternating current, thereby adjusting the pulse current ip 'to make the input voltage vin and the input current iin in phase, thereby improving the power factor of the external power source . The first power factor correcting unit 21 further converts the filtered voltage into the first correcting voltage Vdcl 10 201029306 and the second power factor correcting unit during the positive half cycle of the filtered voltage according to the switching of the first switch Si. According to the switching of the fourth switch, the second winding L2 is operated in the discontinuous conduction mode during the negative half cycle of the filtered voltage (also during the negative half cycle of the input voltage), and the current k exhibits a triangular waveform. And the peak value of the current ip2 is proportional to the input voltage Vin of the alternating current, thereby adjusting the pulse current ip such that the wheeling voltage and the input current lin are in phase, thereby improving the power factor of the external power source. The second power factor correcting unit 22 further converts the filtered voltage into the second modified electric food reading circle 2 and the image during the negative half cycle of the chopping voltage according to the switching of the fourth switch & The pattern enters _ ΤιηΜ with the electricity and low potential, the theoretical waveform in each mode in the positive half cycle. In the present embodiment, the 'I-th switch S, the second switch S2, the third switch S3 and the fourth switch % are respectively controlled by four control signals vgsl, Vgs2, Vgs々Vgs4, and the control signals ^, Vgs3 are group- Synchronous voltage square wave, control signal V, also

:, with = step: do not waste the square wave, these two sets of signals are complementary and very short-lived

Delay time. The hysteresis time is ignored right, and the duty cycle of the control signals Vgsi, V VSS4 is about 〇5. gS 883 ' where the Vab parameter represents „ between the second end of the first switch Si and the second end of the :s2 (four), the ir parameter represents the flow through the series

The resonant current of Cs at both ends, the Vti parameter represents the third winding J 5 ' lp 丨 parameter represents that the current flowing through the first winding L 2 represents the current flowing through the third diode 03, isl, = represent flow The current of the first MQ2 parameter is divided into 1, the second switch S2, the third switch core, and the 11th 201029306 four switch s4. For simplification circuit analysis, the filtering unit 2 ignores, and assuming that the load quality factor of the resonant circuit 32 is sufficiently high, the current flowing through the series inductance Ls and the series capacitance Cs is sinusoidal. The following is an explanation of the operation of inputting electricity $ I for a positive half cycle in six modes. In the negative half cycle of the input voltage Vin, the difference between the input voltage vin and the positive half cycle is the control of the second switch S2 and the fourth switch core in the first three modes (mode one, mode two, mode three, respectively). The terminal is pulled to a high potential, and the latter three modes (mode 4, mode 5, mode 6) are the control terminals of the first switch Si and the third switch S3 are pulled to a high potential, 10 due to the working principle and the input voltage Vin is positive The half-cycle operation is substantially symmetrical, so it will not be described here. Mode 1 (H: Refer to Figure 2, Figure 3 and Figure 4. In the mode, no switch is turned on. And in Figure 4, the current path is indicated in this mode. And the following is for convenience of explanation. The diodes and switches are shown in the figure, while the cut-off diodes and switches are not labeled. In this mode, only the first diode, the first diode S1 of the first switch S1, and the third switch core are © Essential diode SD3 is turned on. When the second switch S2 and the fourth switch S4 are turned off, mode - start, the external power supply provides input current iin to the first winding via the first diode D1 ^

Exciting, and the resonance current ir of the resonance conversion unit 3 is a negative value and flows through the intrinsic diode SDi of the first switch Si and the intrinsic diode SR of the third switching core, so that the voltage across the first switch S1 is vdsl, The voltage vds3 across the third switch S3 is clamped at -0.7V. 12 201029306

The control signals vgsl, vgS3 are raised to a high potential, but the resonant current ι is a negative value and flows through the essential diode SDi of the first switch S1 and the essential diode SD3 of the third switching center, the first switch Si, the third The switch h therefore continues to cut off. The voltage across the first winding L1 is almost equal to the input voltage Vin of the external power source. Since the first power factor correcting unit 21 operates in the discontinuous conduction mode, the current ipl of the first winding h linearly increases from zero and its rising slope is proportional to the input voltage vin. When the resonant current ir and the current of the first winding ^ add up to a positive value, the first switch Si is turned on' because the voltage before the first switching center is turned on is clamped at _〇.7V, and has a characteristic of zero voltage switching conduction. The power consumed by the switching can be reduced and the next mode is entered. Mode 2 (time π~: , see Fig. 2, Fig. 3 and Fig. 5, under mode 2, the first start is turned on. In Fig. 5, the direction of the current path is indicated in this mode 2, and in mode 2, Only the first diode Si, the first diode 匕 and the intrinsic diode SD3 of the third switch S3 are turned on. /, the oscillating current 1 is still negative, and continues to flow through the essence sd3 of the third switching core and External power supply. When the resonant current ir becomes positive, the third switch S3 is turned on 'to enter the next mode' because the voltage of the third switch and before being turned on is clamped at -0.7V' with zero voltage switching conduction, which can reduce the loss of switching. Power. Ceremony _ three (time t2 ~:

Referring to Fig. 2, "3 and Fig. 6, in mode three, the first switch and the third switch S3 are maintained in conduction. The direction of the three current paths in this mode is indicated in Fig. 6, and in mode three, only the first diode η 13 201029306 is turned on and the third switch s3 is turned on. In this mode, the resonant current L changes and the third switch s3, the first capacitor 1 32 provides energy, and the external power source continues to energize the first winding via the pair of resonant circuits to cause the second switch to rise. At time..., control signal v winding; 1 "continue, first switch S1 and third switch buckle drop to low potential toa between t3 ~ (4): enter the lower - mode. See Figure 2, Figure 3 and Figure 7, in the grip 々通. Figure 7 is marked as dry out in the second 'no switch guidance' can not mark the direction of the current circuit grip in this mode, and in the mode: 'only the third diode D3, the second switch & The essential diodes of the intrinsic diode 2 and the fourth switch S4 are called conduction. After a short period of hysteresis, the control signals vgs2 and Vgs4 are raised to a high potential, but the resonance current I - is positive and flows through the first The intrinsic diode SD2 of the second switch S2 and the intrinsic diode SD4 of the fourth switching core, the second switch 52 and the fourth _ & remain off, the two ends of the second switch s2 voltage Vds2, the fourth switch S4 The terminal voltage L is clamped at -0.7V. g cover_vibration current is applied to the first capacitor, and in this mode, the resonant current ir is via the second switch & the essential diode SD2 and the fourth The intrinsic diode Sd4 of the switch S4 charges the first capacitor Cdcl and the second capacitor Cdc2. The two power correction units 21 and 22 have the function of the step-down converter. Therefore, the first correction voltages Vdei and 14 201029306 of the first capacitor cdcl are designed to be the first correction voltage vd{; The peak value of the input voltage Vin of the external power source reverses the first diode D1, and the current ipl of the first winding Li flows through the third diode D3 to charge the first capacitor Cdcl. The voltage is changed from the input voltage Vin which is originally equal to the external power source to the first correction voltage 第一 of the first capacitor Cdcl which is negative, so that the current ipl of the first winding k starts to decrease linearly, and the peak of the current ipl of the first winding ^ and the external power source The input voltage Vin is proportional, so the time required for the current ipl of the first winding I to fall to zero is not fixed but varies in proportion to the input voltage vin. Therefore, the current h and the resonant current ir according to the first winding L] decrease. The sequence is different from zero to 'the mode can be divided into = action mode. Mode five-a (time t4~: see Figure 2 and Figure 8, in mode five, the second switch & and the fourth switch S4 start Turn on. And in mode five' In the &, the third diode a maintains conduction. When the input voltage Vin is at a higher potential, the peak value of the current 1P1 of the first winding ^ is also relatively high, and in this state, if the first winding U current Μ and resonance hunger are simultaneously decremented, and the resonance current ir drops first to zero: it enters mode five-a. In this mode, the resonance current “turns to a negative value, causing switch S2 and fourth switch S4 to conduct because the second switch ^ and the voltage before the fourth turn-on is boxed at _G.7V, with zero voltage switching conduction = characteristic 'can reduce the power consumed by the switching. Mode 6 is entered when the current 1P1 of the first winding L1 continues to drop to zero. Photograph U (time t4~t5,: 15 201029306 Refer to Figure 3 and Figure 9. In mode five-b, no switch is turned on. And in mode five-b, only the second switch & The body sD2 and the intrinsic diode SD4 of the fourth switch S4 are turned on. When the input voltage vin is at a lower potential, the peak value of the current ipl of the first winding Li is relatively *, and in this state τ, the first winding L1 The electrical method iPl and the resonant current are simultaneously decremented, and the current k of the first winding Li is first; when it is lowered to zero, the input mode is five_b. In this mode, the third diode is turned off, and the resonant current 1 is passed through the second switch. The essential diode of & and the essential diode of the fourth switch S4 are called the first capacitor Cdcl and the second capacitor Cd^, and the resonant current ir continues to decrease. When the resonant current ^ drops C, 2 enters the mode six Feeding (time t5~t6,: second: circle IFig. 3 and ^1〇' in mode six' second switch core and: four switch S4 switch on conduction with zero power. Figure 1〇 shows in This chess is six times, the direction of the current path, and in the mode, your style, in, all the diodes are cut off in mode six Between, the resonant current ir is a negative value, and the first capacitor C _capacitor Cdc2 provides energy via the second switch s dcl 32. When the control _ Vgs2, v4: 4 pairs the resonant circuit, "fourth switch, mode six potential, The working mode of the second cycle... bundle, enter the lower-high frequency as shown in Figure 11, assuming that the external power supply is ν·ω-ν. The input voltage of the source is ln()-vmsln(kfLt ), where the frequency of 4 and ν is the input voltage Vin frequency and amplitude. In the actual design, the frequency of the wheel voltage Vln is much smaller than the switching frequency fs per 16 201029306. 'In this embodiment, it is 6〇Hz and 40kHz respectively. Therefore, the input voltage Vin can be regarded as a fixed value during each high-frequency switching period of each switch. When the input voltage Vin is positive half cycle, the pulse The wave current ip is equal to the rising portion of the current ipi of the first winding L!, and when the input voltage vin is negative half cycle, the negative pulse current -iP is equal to the rising portion of the current ip2 of the second winding L2. The peak value of the current ip follows the input voltage vin waveform can be expressed as: p,peak (0 V,

Where Ts is the high frequency switching period of each switch, and Lp is the exciting inductance of the first winding and the second winding. The input current iin is the pulse current, and the high frequency harmonic component is removed, which is equivalent to the average of the pulse current ip. (10)=士)·_=do) (2) 's 〇Lp Equation (2) shows that if the switching frequency of the switch is greater than the frequency of the input voltage Κη, the input current iin exhibits a sine wave and is in phase with the input voltage Vin. 2 With a small input inductance Lm and input capacitance, the high-frequency harmonic components of the pulse current ip can be filtered out, so that a high power factor can be achieved. The input power can be obtained from the average value of one cycle. ) = (3) Calculated 17 (4)201029306 puin l^pfs where 7 represents the circuit efficiency. Actually completed: Figure 12 shows the waveform of the wheel voltage Vin, the input current iin and the output voltage v〇 'input current iin It is a sine wave and is in phase with the input voltage Vin, the measured power factor is higher than 0 99 and the total current distortion is 6 8%. Figure 13 shows the currents ipi, ip of the first and second windings q, La. The power factor correction unit 21, 22 is used for the entire input voltage I For each working period seine discontinuous conduction mode.

Fig. 14 shows the waveform of the voltage vds1 and current isisi of the first switch I and the voltage and current iS4 of the fourth switch S4 when the input voltage Vin is between positive half cycles.

Fig. 15 is a diagram showing the waveform 's of the voltage Vds1 and the current isisi of the first switch I and the voltage % of the fourth switch, when the input voltage Vin is between negative half cycles.

Waveform with current iS4. It can be seen from Figures 14 and 15 that the switches have the function of zero-switching conduction. In summary, the power conversion device of the present embodiment has the following advantages: (-) By correcting the power factor by the two-factor correction unit 21, 22, the power factor can be improved. (2) By sharing the switch by the two-factor correction unit 21, 22 and the resonance conversion unit 3, the number of electronic components can be effectively reduced and the simplified control mode can be reduced. (3) By switching all the switches at zero voltage Turn on, 18 201029306 Switch losses, which in turn increases conversion efficiency. The above is only the preferred embodiment of the present invention, and the scope of the invention is not limited thereto, that is, the simple equivalent changes and modifications made by the scope of the invention and the description of the invention are All remain within the scope of the invention patent. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a circuit diagram of a preferred embodiment of the present invention;

2 is a timing diagram of the preferred embodiment of the present invention at a high potential when inputting a positive half cycle; FIG. 3 is a preferred embodiment of the present invention at a positive half cycle of the input voltage and at a low potential 4 is a circuit diagram of the preferred embodiment of the present invention, illustrating a mode operation; FIG. 5 is a circuit diagram of the preferred embodiment of the present invention, illustrating operation in mode one, FIG. The circuit diagram of the preferred embodiment of the present invention illustrates the operation in mode three; Figure 7 is a circuit diagram of the preferred embodiment of the present invention illustrating the operation in mode four; 圜8疋 the preferred embodiment of the present invention The circuit diagram of the embodiment illustrates the operation in mode 5-1A; _9 is a circuit diagram of the preferred embodiment of the present invention, illustrating the operation in mode 5.4; 阖 is the circuit diagram of the preferred embodiment of the present invention Figure 11 is a schematic diagram of the current of the preferred embodiment of the present invention, illustrating the current waveform input to the secondary power modifying unit; Figure 12 is a preferred embodiment of the present invention. Experimental measurement chart The input voltage and the input current waveform from the external power source are in phase, and the waveform of the output voltage; FIG. 13 is an experimental measurement diagram of the preferred embodiment of the present invention, illustrating current waveforms of the first winding and the second winding; FIG. An experimental measurement diagram of the preferred embodiment of the present invention illustrates voltage and current waveforms of the first switch and the fourth switch when the input voltage is positive half cycle; and the figure is a preferred embodiment of the present invention The experimental measurement chart shows the voltage and current waveforms of the first switch and the fourth switch when the input voltage is negative half cycle.

20 201029306

[Description of main component symbols] 〇* · Filter unit D 8 ' "4' ... eighth diode 21 * • First power factor correction single L1 ... first winding element Τ, 2 * * ° ^ ...·· Second winding" second power factor correction single V fi V » 9 ..... third winding element L4 ' ... fourth winding * · resonance conversion unit 1 «««««? ... first switch 2 J •• full bridge switch Circuit S2... ••...Second switch•,Resonance circuit S3»»^ ^ *s ...*Third switch ν^ΛΨΨ9¥ν ...AC to DC conversion*...The fourth switch circuit SD!.... .. The essence of ....S1 - pole 1 ««**««»« ^m • 4 input inductor body « «·««♦«««« '-Μη - input capacitance SD2 .... ... the essence of S2 - Pole series inductor body ι_ -s «**<, "»*» ... series capacitor SD3 .... ... the essence of S3 - pole τ 1 1 ♦ do « « ♦ ♦ * • • transformer body wolf) 1 β ·The first diode sd4··........the essence of S4-pole 2 44-^444^« ••second diode body)^ af9ft#ptf ”third diode Cdcl ...* ..."first capacitor 〇4 - fourth diode Cdc2 .. second Capacitance]) 5 »»***».» "Fixth Diode Co. . Output Capacitor «»·>♦*** - Sixth Dipole « « 4 « « ύ 4 •• Seventh Diode 21

Claims (1)

201029306 VII. Patent application scope: 1. A power conversion device comprising: a clean wave unit 'receiving an AC input voltage and an input current, and providing an AC filtered voltage and a pulse current; a correction unit, receiving the filtered voltage and the pulse current, and generating a first correction voltage that is always flowing; a second power factor correcting unit 'receives the filtered voltage and the pulse current, and generates a second correcting voltage of the current, and adds the second modified voltage and the first modified voltage to a total voltage; and The resonant switching unit includes a full bridge switching circuit and a resonant circuit. The full bridge switching circuit includes a first switch, a second switch, a third switch and a fourth switch, and the full bridge switch circuit receives the total And switching between the on state and the off state by the first switch to the fourth switch to generate an alternating current and square wave switching voltage, the resonant circuit receives the converted voltage, and filters out the resonance by resonance Conversion voltage The DC component and the high frequency chopping into the > to generate an alternating current switching current; wherein the first power factor correcting unit adjusts during the positive half cycle of the filtered voltage according to the phase cut of the first switch The pulse current is to correct the input voltage and the power factor of the input current, and convert the filter pressure into the first correction voltage, and the second power correction unit is switched according to the fourth switch. During the negative half cycle of the wave, the pulse current is adjusted to correct the input voltage and the power of the input current, and the filtered voltage is converted into the second modified voltage. The filter is 5 22 201029306 The high frequency harmonic component of the pulse current is filtered to make the wheeled current substantially sinusoidal. 2. According to the patent scope of the request! The power conversion device of the present invention, wherein each of the first switch to the fourth switch is controlled by a control signal to synchronize the control signals of the first switch and the third switch The control signal of the second switch and the fourth switch are synchronized, and the control signals of the first switch and the second switch are complementary, and there is a time lag between the two. 3. According to the power conversion described in the middle item (4), the first switch to the fourth switch are switched at a frequency of 4〇k Hz and their duty cycle is substantially 50%. 4. The power conversion device according to the ninth aspect of the invention, wherein the resonance frequency of the s-resonance circuit is lower than the switching frequency of the four switches on the flat page of the sinusoidal/m. The power conversion device according to the above aspect of the invention, wherein the switching frequency of the four switches is greater than the frequency of the input voltage. 6. The power conversion device according to claim 1, wherein: the first power factor correction unit comprises a first two-pole body, a -first capacitor, and a first winding, the first two Upper: an anode and a cathode m body electrically connected to the filter unit to receive the filter, the wave current and the pulse current have a cathode electrically connected to a cathode of the first diode and an anode Having a first end connected to the first end of the first switch and a second end electrically connected to the cathode of the first diode The voltage between the anodes of the triodes and the voltages at both ends thereof is the first 23 201029306 correction voltage; the second power factor correction unit includes a second diode body, a fourth body, a first electricity valley, and a first a second winding having a cathode electrically connected to the filtering unit to receive the filtered voltage and the pulse current and an anode, the fourth diode having an anode electrically connected to the second diode An anode and a cathode, the second winding having an electrical connection to the fourth a first end of the body, and a second end electrically connected to the anode of the second diode, the second capacitor being electrically connected between the first end of the second winding and the cathode of the fourth diode And the voltage across the two is the second correction voltage. According to the power conversion device of claim 6, wherein the first winding and the second winding are wound in the same iron core. According to the power conversion device of claim 6, wherein the first winding and the second winding are respectively wound in two different cores, and the power conversion according to claim 6 of the patent scope is applied. The device, wherein the first end of the first winding is a polarity point end, and the 5th end of the first winding is a non-polar point end, and the first end of the second winding is a polarity point end, and the The second end of the two windings is a non-polar point end. The power conversion device of claim 6, wherein: the first switch has a first end, a second end, and a control end electrically connected to the first end of the first winding, the control The end is controlled to switch the first switch between a conducting state and a wearing state; the second switch has a first end, a second end, and a first end, 24, 29, 29, 306, electrically connected to the first end of the first winding a control terminal, the control terminal being controlled to switch the second switch between an on state and an off state, wherein a voltage between the second end of the first switch and the second end of the second switch is the conversion voltage The third switch has a first end electrically connected to the second end of the second switch, a second end electrically connected to the first end of the second winding, and a control end, the control end being controlled Switching the third switch between an on state and an off state; the fourth switch has a first end electrically connected to the second end of the first switch, and a second end electrically connected to the first end of the second winding End, and - control end, the control Controlled so that the fourth switching between a conducting state and a stop state of wear. The power conversion device of claim 2, wherein the resonance conversion unit further comprises an AC to DC conversion circuit, the AC to DC conversion circuit receives the conversion current, and performs a parent current to DC conversion of the conversion current. Convert to produce a constant output voltage. 25