RU2649897C1 - Automated radio receiving center of radio communication network of the shortwave band - Google Patents

Abstract

FIELD: radio engineering and communications.

SUBSTANCE: invention relates to the field of radio communication, in particular to radio receiving centers in the radio communication units of the short-wave range of stationary and mobile versions. Automated radio receiving center of the short-wave radio communication unit comprises an antenna-feeder system connected to the input of a corresponding multi-channel digital radio receiver, the voltage of the n-th sample of the received signal of the m-th radio subscriber is fed through the multiplexer to the corresponding inputs of the devices of the coherent addition of signals, representing a closed system of self-regulation with feedback, providing a geometric addition of the corresponding noise voltages and in-phase addition of samples of the signal of the m-th radio subscriber, which is fed to the workstation.

EFFECT: invention is intended to improve the noise immunity of receiving a signal from each of the M radio subscribers.

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Description

The invention relates to the field of radio communications and can be used in the development and modernization of radio reception centers as part of the short-wave (KB) radio communication nodes of the stationary and mobile versions.

Automated radio receiving centers are known as part of stationary geographically separated multichannel transceiving radio communication nodes (URS) of the KB range, each of which contains a set of receiving antennas that are switched to the inputs of the M receiving channels using antenna sharing equipment, in which the radio receiving center (RPMC) and the radio transmitting are controlled the center (RPdTs), which are part of the URS, is carried out via intra-node communication lines (HUS), as when using a separate station as part of the URS control and management station when combined with RPmTs [1] and [2].

The disadvantages of these RPMC in the composition of the URS KB range are:

- the need to use large areas to accommodate sets of KB receiving antennas of medium and high efficiency such as VGDSH, BS, BS-2, SRS, etc. [1], [3], providing in the operating frequency range the reception of signals from radio subscribers on radio paths of various azimuth directions and various lengths;

- reduction of noise immunity of signal reception due to the use of equipment for the collective use of receiving antennas with broadband antenna amplifiers, which serve to compensate for signal attenuation in multichannel distribution and switching devices [2];

- energy losses in KB radio lines due to the diverging processes of changing the elevation angle of the bisectors of the radiation patterns of most types of high-efficiency receiving antennas and the necessary elevation angle of the radio beam incident on the reflecting layer of the ionosphere, when changing the value of the optimal operating frequency (ORF) under changing geophysical conditions [four].

Known automated RPMC as part of a mobile geographically dispersed URS KB range, given in [5], containing N multi-channel receive paths, each of which contains a switch, the inputs and outputs of which are connected to the corresponding outputs and inputs of the driver of control signals, the outputs and inputs of the switch are connected to corresponding inputs - outputs of intra-node communication equipment (VUS), consisting of wireless access equipment and wired communication equipment.

RPMC control is carried out via WUS channel channels from the first control station, which can also control RPC through a second control station connected to the RPC via wired channel channels and connected to the first control station via a WUS wireless line.

The disadvantages of the above automated RPMC as part of the URS KB range are:

- all the disadvantages inherent in the above-described radio receiving centers of the radio communication nodes KB range [1], [2];

- the use of appropriate control stations in the RPMC and RPdTs complex as part of the URS complicates the RPMTs and URS as a whole, increases the cost of the RPMTs for its industrial production, in addition, the control station requires additional maintenance personnel - radio operators, as well as additional labor costs for routine works when servicing a complex of station equipment.

Of the well-known automated radio receiving centers of the KB range radio communication nodes, the closest in essence to the tasks to be solved and the majority of the essential features coinciding is the automated RPMC KB range given in [6], containing the antenna-feeder system (APS), consisting of N antenna elements with serial numbers from 1 to N, placed in a certain way on the ground in the form of an antenna array of the selected configuration (linear, annular, flat rectangular or hexagonal) [3], [7] with regular placement a ntenny elements.

The output voltage of each antenna element with serial number n (n = 1,2, ..., N) is the voltage of the sample with the same serial number n received from the air of high-frequency signals and interference.

The output of each antenna element with serial number n is connected to the input of the corresponding multi-channel receive path with the same serial number n, containing M independent receive channels with serial numbers from 1 to M. Currently, such a multi-channel receive path with the output voltage of the receive channels to digital form is called a multichannel digital radio receiver (ICRPU) ([3], p. 159), therefore, in the future we will use the modern name (abbreviation) of the multichannel receiving path - DRR.

Each of the N MCRPUs with serial numbers from 1 to N contains M independent receive channels with serial numbers from 1 to M, where M is the maximum number of radio subscribers interacting with an automated RPMC with serial numbers from 1 to M emitting signals at the corresponding carrier frequencies. Moreover, each receive channel with serial number m (m = 1,2, ..., M) as part of each MCRPU with serial number n is set to the reception mode of the radio subscriber signal with the same serial number m.

The outputs-inputs of each MCRPU with serial number n are connected to the corresponding inputs and outputs of the multiplexer, the outputs of which are connected to the corresponding inputs of the beam forming unit (BFDN), in which M beam patterns are generated with serial numbers from 1 to M.

The formation of each radiation pattern with serial number m in the BFDN is carried out by in-phase summation of the voltages N of the samples of the received signal of the radio subscriber with serial number m from the outputs of the respective receive channels, each with serial number m in each of the N ICRPUs with serial number n. In this case, the phasing of the voltages N of the samples of the received signal of the radio subscriber with serial number m is carried out by their time delay by the values calculated using the initial data on the location coordinates of each antenna element of the AFS and the values of the radio path parameters (length, azimuths), which determine the spatial direction of signal arrival ( beam), which is equivalent to the fact that the spatial direction of the maximum of each formed radiation pattern with serial number m with corresponds to the spatial direction of arrival of the radio subscriber signal with serial number m.

The BFDN outputs are connected to the corresponding inputs of the demodulation and decoding unit, in which each result of the formation of a radiation pattern with serial number m, which is the resulting voltage of the reception of the radio subscriber signal with serial number m, is demodulated by the corresponding demodulator of the radio subscriber signal with serial number m and decoded by the corresponding decoder with serial number number m.

The outputs and inputs of the demodulation and decoding unit are connected to the corresponding inputs and outputs of the switch, the outputs and inputs of which are connected respectively to the inputs and outputs of the BFDN, to the inputs and outputs of the multiplexer, to the inputs and outputs of the driver of the control signals, to the inputs and outputs of the equipment for determining location coordinates and time stamps, with inputs and outputs of each of L automated workstations (AWS) by means of corresponding communication lines, as well as inputs and outputs of intra-node communication equipment (VUS), effectiveness to two-way intrasite connection with RPmTs RPdTs while working as a part of URS kb range. Moreover, on the screens of the computer monitors of each of the L AWPs, the results of receiving signals of the corresponding radio subscribers are displayed.

However, it should be noted the following disadvantages of this automated RPMC radio range node KB range:

1. The noise immunity of receiving radio subscriber signals is insufficient when exposed to additive and multiplicative noise in the KB communication channel for several reasons:

1.1. Due to the inaccuracy of determining the values of the initial data input into the electronic memory of the RPMC for the formation of directional patterns in the BFD [3]:

a) the geographical coordinates of the location on the terrain of each antenna element as part of the selected configuration of the antenna array AFS;

b) the values of the parameters of the radio paths when working with the corresponding M radio subscribers (lengths, azimuths) that determine the spatial direction of arrival of signals (radio beams), each of which is characterized by the directivity of the corresponding vector r _m with serial number m (m = 1,2, ..., M) .

Obviously, with the mobile version of RPMC, inaccuracies are inevitable in determining the geographical coordinates of the location of the antenna elements according to paragraph a) above, each time the AFS antenna array is deployed after the mobile RPMC is moved to a new location, especially in adverse weather conditions (precipitation, work in winter conditions).

Accordingly, with some deviations, each m-th BP with serial number m (m = 1,2, ..., M) will be formed in the BFDN, since the summed voltages N of the samples of the received signal of the m-th radio subscriber with serial number m from the outputs of the mth the reception channels corresponding to N ICRPU will differ from each other in phase by the values determined by the error in measuring the coordinates of the location of each antenna element. Accordingly, the summation result in magnitude will be less than required. It follows that the resulting signal-to-noise ratio at the input of the corresponding signal demodulator of the m-th radio subscriber (as part of the demodulation and decoding unit) h _mp = U _{С pm} / U _{П pm} ( Uc _pm is the resulting signal voltage at the input of the signal demodulator m radio subscriber, U _{P pm} - the resulting interference voltage at the input of this demodulator, measured in the frequency band occupied by the signal) will be less than the potential achievable, which reduces the noise immunity of the reception.

Let us consider the effect on the noise immunity of receiving the signals of the initial data input into the electronic memory of the RPMC when performing the operations in the above item b).

To achieve the maximum possible value of the resulting relation h _pm = U _Cpm / U _{П pm} at the input of the signal demodulator of the m-th radio subscriber as part of the demodulation and decoding unit, it is required that the spatial direction of the maximum of the generated m-th beam coincides with the spatial direction of arrival of the radio beam from m -th radioabonenta characterized oriented corresponding vector r _m with sequence number m [3].

However, the exact value of the angle of arrival of the received signal (the spatial direction of the vector r _m ) cannot be determined a priori by calculating the radio path due to the temporal and spatial variability of the ionosphere region from which short waves are reflected [8]. In addition, the propagation paths of radio waves reflected from the region of the ionosphere F often have noticeable asymmetry due to the shift of the reflection region relative to the middle of the path ([8], p. 46), which also leads to a change in the angles of arrival of the signal relative to the calculated values for a symmetric radio path, and respectively, and to the energy loss of the radio link [4].

1.2. Due to short interruptions in communication due to deep fading of received signals.

It is known that when working on single-hop radio paths with a length of 1000-3000 km ([8], p. 80, 81) under conditions of deep fading of a signal received from any m-th radio subscriber, at the output of the corresponding demodulator and subsequent decoder during a communication session error packets may be logged repeatedly. The duration of each error packet is determined by the time the electromagnetic field (EMF) level of the received radio beam is below a certain threshold level, which leads to short-term communication losses.

When working on multi-hop routes with a length of 3000-4000 km or more (with the number of jumps more than one), on which there are several possible triangular propagation paths of radio waves ([8], p. 13, Fig. 1.1), several a radio beam at different angles of arrival with independent fading of the EMF intensity levels of each of the rays.

At time intervals when deep fading of the EMF intensity level occurs, for example, of the “main” radio beam, to which the maximum of the phased array antenna beam is oriented when receiving the signal of the m-th radio subscriber, corresponding error packets will be recorded at the RPMC, as described above. However, in this case, with deep fading of the "main" radio beam, the EMF intensities of other radio beams arriving at the receiving point at different angles of arrival can exceed the threshold level.

Since the known RPMC [6] does not provide for the operational restructuring of the spatial directivity of the maximum of the beam formed to receive the signal of the m-th radio subscriber, to another radio beam (carrying the same information as the "main" radio beam) in order to reduce the duration of the error packet, the duration of each error packet will be determined by the time the EMF intensity level of the “main” radio beam is below the threshold level. As a result, the reception of information from the m-th radio subscriber can be resumed only after the EMF intensity level of the “main” radio beam (after each of its deep fading) exceeds the threshold level, which does not allow to reduce the duration of the error packet.

1.3. Due to the insufficient signal-to-noise ratio of each of the M resulting reception voltages of the radio subscriber signals generated in a known manner at the outputs of the BFDN.

The area occupied by the AFS antenna array of a well-known automated RPMC is selected relatively small, for example, the antenna array of the FAR 5AR analog antenna receiving complex [7] consists of 40 antenna elements and occupies an area of 40 × 60 m, while the distances between adjacent antenna elements of the array do not exceed 10 m. From this it follows that the received samples (copies) of signal voltages and interference at the outputs of adjacent antenna elements are strongly correlated (with the value of the spatial correlation function or radius n ostranstvennoy correlation R _d [9] is close to the maximum, i.e., R _d ≈1).

, где λ - длина волны принимаемого сигнала ([10], с. 169).It should be noted that with this method of forming radiation patterns, a weak correlation of signals and interference at the outputs of adjacent antenna elements (at R _d → 0) of the antenna array is not permissible, since it will lead to an uncertainty in the phase difference of the voltage samples of the signal of the mth radio subscriber at the outputs of neighboring elements. A weak correlation is achieved with the spatial separation of adjacent antenna elements over a distance

where λ is the wavelength of the received signal ([10], p. 169).

As a result, when the voltage of a mixture of signal samples and interference is added to the BFDN, received, for example, by two adjacent antenna elements of the antenna array (filtered and amplified in the corresponding reception channels of neighboring MCRPUs), for example, with serial numbers 1 and 2 and with corresponding signal / noise ratios : h _{m 1} = U _{C 1 m} / U _{П1 m} and h _{m 2} = U _{C 2 m} / U _{П2 m} , there will be practically no increase in the resulting signal to noise ratio h _{pm (1 + 2)} with respect to the signal to noise ratio one of the terms, i.e. h _{pm (1 + 2)} ≈h _pm1 ≈h _m2.

It is known ([10], p. 183) that an increase in the resulting signal-to-noise ratio in the case under consideration can be achieved only when the samples of the signal of the m-th radio subscriber from the outputs of the m-th reception channels of the corresponding MCRPUs are added algebraically (common-mode signal addition) , and weakly correlated interference (noise) at the output of these reception channels are added geometrically. Accordingly, an increase in the resulting signal-to-noise ratio h _mp at the m-th output of the BFDN (during the demodulator of the signal of the m-th radio subscriber) during the formation of the m-th beam will be achieved mainly by adding the output voltages of the m-th reception channels of those MCRPUs that are connected to antenna elements spaced on the ground relative to each other for longer distances at which received interference is less correlated (R _d <1). However, the samples of the signal of the m-th radio subscriber received by these antenna elements will also be less correlated, which leads to an increase in the phasing error of the most distant antenna elements during the formation of the m-th beam.

Thus, in an automated RPMC that implements this method of multichannel signal reception, the potential capabilities of the equipment used (N antenna elements as part of the APS and M reception channels as part of each MCRPU) to increase the signal-to-noise ratio at the input of the signal demodulator of the m-th radio subscriber are not completely.

2. The relatively large deployment time of the mobile RPMC version, structurally executed, for example, in the form of a mobile equipment room mounted in a box body on a KamAZ-type car chassis. The deployment time of such an RPMC will be determined by the sequence of the following actions:

2.1. Before deploying the AFS antenna array in a wooded area, it is necessary to find a relatively flat horizontal area and perform the operations in paragraph a) above, i.e. using the equipment for determining the location and timestamps to determine the geographical coordinates of the geometric center of the antenna array. Relative to this center, it is required to determine the geographical coordinates of the location of each of the N antenna elements in accordance with the adopted configuration of the antenna array (linear, circular, flat rectangular or hexagonal) [3] and mark the terrain. After this, you can deploy each antenna element with its installation on the ground in accordance with the markup.

2.2. Next, you need to deploy a mobile hardware room, start an electric unit from its composition to power the RPMC technical equipment (electronic equipment and computers - computers) and perform operations according to paragraph b) above to programmatically generate directional patterns with the required orientation of the maximums in the space. After performing these operations, the deployment of the mobile RPMC can be considered completed.

3. The limited use of RPMC due to the complexity or inability to deploy the antenna array AFS with regular placement of antenna elements, for example, on:

- heavily rugged terrain or mountainous terrain;

- flat roofs of nearby buildings and structures;

- decks of bulky sea vessels;

- railway platforms, including on the roofs of special wagons, etc.

The tasks to which the invention is directed, the automated radio receiving center of the shortwave radio communication center, are:

1. Improving the noise immunity of signal reception from each of the M radio subscribers when operating on single hop and multi hop KB radio paths of various lengths under conditions of deep fading of received signals.

2. Reducing the deployment time of the N antenna elements of the AFS mobile version of the RPMC operating in parking lots.

3. Expanding the possibilities of using automated RPMC by ensuring the deployment of antenna elements of the AFS, for example:

- in severely rugged terrain or mountainous terrain;

- on the flat roofs of nearby buildings and structures;

- on bulky sea vessels;

- on railway platforms, including on the roofs of special wagons, etc.

The solution to these problems is achieved by the fact that in the automated radio receiving center of the shortwave range, containing the antenna-feeder system (APS), consisting of N antenna elements remote from each other with serial numbers from 1 to N, the output of each antenna element with serial number n connected to the input of the corresponding multichannel digital radio receiver (MCRPU) with the same serial number n, containing M independent receive channels with serial numbers from 1 to M, outputs-inputs each the second MCRPU with serial number n are connected to the corresponding inputs and outputs of the multiplexer, the outputs and inputs of which are connected to the corresponding inputs and outputs of the switch, the outputs and inputs of which are connected respectively to the inputs and outputs of the control signal generator, with the inputs and outputs of the demodulation and decoding unit, with the inputs and outputs of the equipment for determining the coordinates of the location and timestamps, with the inputs and outputs of the workstation through the communication line, as well as the inputs and outputs of the equipment in internal communications (CCS), M coherent signal addition (CCS) devices were introduced with serial numbers from 1 to M, the inputs and outputs of each of which with serial number m are connected to the corresponding additional outputs-inputs of the multiplexer, each CCS with serial number m contains a switch ACS, the inputs and outputs of which are inputs and outputs of the ACS with serial number m, an adder, a filter of the resulting oscillation, a normalizing amplifier of the resulting oscillation, and N phasing nodes with serial numbers from 1 to N, the first inputs s of each of which with serial number n are connected to the corresponding outputs of the UKS switch, the inputs of which are connected to the corresponding outputs of the filter of the resulting oscillation, combined with the corresponding inputs of the normalizing amplifier of the resulting oscillation, the outputs of which are combined with the corresponding second inputs of each phasing node with serial number n, the outputs of each phasing node with serial number n are connected to the corresponding inputs of the adder, the outputs of which are connected to the corresponding and the inputs of the filter of the resulting oscillation, each phasing node with serial number n contains a channel filter, the inputs of which are the first inputs of the phasing node with serial number n, the outputs of the channel filter are connected to the corresponding inputs of the normalizing amplifier, the outputs of which are connected to the corresponding first inputs of the first multiplier and the corresponding first inputs of the second multiplier, the outputs of which are the outputs of the phasing node with serial number n, the second inputs of the second multiply The firs are connected to the corresponding outputs of the measuring filter, the inputs of which are connected to the corresponding outputs of the first multiplier, the second inputs of which are the second inputs of the phasing unit with serial number n.

, где λ - максимальная длина волны принимаемого сигнала от любого из М радиоабонентов.As part of the AFS, the distance between any two adjacent antenna elements with any serial numbers from 1 to N is not less than

where λ is the maximum wavelength of the received signal from any of the M radio subscribers.

In addition, as part of the AFS, each of the N / 2 antenna elements with serial numbers from 1 to N / 2, identical in design, is designed to receive horizontal electromagnetic field (EMF), and each of the other N / 2 antenna elements with other serial numbers from N / 2 + 1 to N, identical in design, designed to receive EMF of vertical polarization, or each of the N / 2 antenna elements with serial numbers from 1 to N / 2 of a mixed type - both identical design and different to structural design, designed to receive EMF of horizontal polarization, and each of the other N / 2 antenna elements with different serial numbers from N / 2 + 1 to N of mixed type - both identical design and different design, is designed to receive EMF of vertical polarization.

In FIG. 1 and FIG. 2 shows electrical structural diagrams of the proposed automated radio receiving center of the KB band radio communication unit and coherent signal addition (UKS) device.

An automated radio receiving center of a shortwave radio communication center containing APS 1, consisting of N antenna elements 2 ₁ , ..., 2 _N remote from each other with serial numbers from 1 to N, the output of each antenna element 2 ₁ , ..., 2 _N with a serial number n is connected to the input of the corresponding ICMPU 3 ₁ , ..., 3 _N with the same serial number n, containing M independent receive channels with serial numbers from 1 to M, the outputs-inputs of each ICMPU 3 ₁ , ..., 3 _N with serial number n are connected with corresponding inputs and outputs of multiplexer 4, output - the inputs of which are connected to the corresponding inputs and outputs of the switch 5, the outputs and inputs of which are connected respectively to the inputs and outputs of the control signal generator 6, with the inputs and outputs of the demodulation and decoding unit 7, with the inputs and outputs of the apparatus for determining the location coordinates and timestamps 8 , to the inputs-outputs workstation 9 through the communication line 10 as well as with inputs - outputs VSL apparatus 11, MSC 12 introduced M _1, ..., 12 _M with numbers from 1 to M, inputs - outputs of each of the cat ryh with sequence number m are connected to corresponding additional output-input multiplexer 4, each MSC 12 _1, ..., 12 _M with sequence number m comprises switch MSC 13, inputs - outputs of which are inputs - outputs MSC 12 _1, ..., 12 _M with serial number m, adder 14, the filter of the resulting oscillation 15, the normalizing amplifier of the resulting oscillation 16 and N phasing nodes 17 ₁ , ..., 17 _N with serial numbers from 1 to N, the first inputs of each of which with serial number n are connected to the corresponding outputs of the switch UKS 13, cat inputs They are connected to the corresponding outputs of the filter of the resulting oscillation 15, combined with the corresponding inputs of the normalizing amplifier of the resulting oscillation 16, the outputs of which are combined with the corresponding second inputs of each phasing node 17 ₁ , ..., 17 _N with serial number n, the outputs of each phasing node 17 ₁ , ... , 17 _N with serial number n are connected to the corresponding inputs of the adder 14, the outputs of which are connected to the corresponding inputs of the filter of the resulting oscillation 15, each phasing node 17 ₁ , ..., 17 _N with order The current number n contains a channel filter 18, the inputs of which are the first inputs of the phasing unit 17 ₁ , ..., 17 _N with the serial number n, the outputs of the channel filter 18 are connected to the corresponding inputs of the normalizing amplifier 19, the outputs of which are connected to the corresponding first inputs of the first multiplier 20 and with the corresponding first inputs of the second multiplier 21, the outputs of which are the outputs of the phasing unit 17 ₁ , ..., 17 _N with serial number n, the second inputs of the second multiplier 21 are connected to the corresponding outputs a filter ceiling elements 22, whose inputs are connected to respective outputs of the first multiplier 20, second inputs of which are the second inputs of the phasing unit 17 _1, ..., 17 _N with a sequence number n.

, где λ - максимальная длина волны принимаемого сигнала от любого из М радиоабонентов.As part of APS 1, the distance between any two adjacent antenna elements 2 ₁ , ..., 2 _N with any serial numbers from 1 to N is not less than

where λ is the maximum wavelength of the received signal from any of the M radio subscribers.

In addition, as part of APS 1, each of the N / 2 antenna elements 2 ₁ , ..., 2 _{N / 2} with serial numbers from 1 to N / 2, identical in design, is designed to receive horizontal polarized electromagnetic fields, and each of the other N / 2 antenna elements 2 _{N / 2 + 1} , ..., 2 _N with other serial numbers from N / 2 + 1 to N, identical in design, designed to receive EMF of vertical polarization, or each of N / 2 antenna elements 2 ₁ , ..., 2 _{N / 2} with serial numbers from 1 to N / 2 of the mixed type - both identical design and different design, designed to receive EMF horizontal polarization, and each of the other N / 2 antenna elements 2 _{N / 2 + 1} , ..., 2 _N with other serial numbers from N / 2 + 1 to N mixed type - as an identical design, and various designs, designed to receive EMF vertical polarization.

To analyze the operation of the proposed automated RPMC node of the KB range, we first consider the distinctive features of the deployment of a mobile version of this RPMC.

In contrast to the well-known automated RPMTs [6] of the mobile version operating on parking lots, for the deployment of AFS 1 of the proposed automated RPMTs (Fig. 1 and Fig. 2) of the mobile embodiment, structurally executed, for example, in the form of a mobile hardware installed in LCV type KamAz car chassis is not required to select the conditions in a wooded area, relatively flat area and to determine the geographical coordinates of the location of each antenna element 2 _1, ..., 2 _N times for the location of the antenna elements in the form of an antenna array of one of the configurations (linear, circular, flat rectangular or hexagonal).

, где λ - максимальная длина волны принимаемого сигнала от любого из М радиоабонентов.The deployment of N antenna elements 2 ₁ , ..., 2 _N APS 1 of the proposed automated RPMC can be performed on virtually any terrain, for example, on very rough terrain or mountainous terrain, free from metal structures that impede the reception of signals from radio subscribers, and from dense thickets that impede attaching antenna elements to the ground. In this case, the antenna elements 2 ₁ , ..., 2 _N APS 1 can be installed on the selected area in any order, but subject to the condition: the distance between any two adjacent antenna elements 2 ₁ , ..., 2 _N with any serial numbers from 1 to N should be no less than

where λ is the maximum wavelength of the received signal from any of the M radio subscribers.

, при которых напряжения принимаемых сигналов и помех на выходах соседних антенных элементов с любыми порядковыми номерами от 1 до N будут слабо коррелированны [10] (при значении радиуса пространственной корреляции [9] R_d→0).It should be noted that the proposed structure of the automated RPMC and the principle of processing received signals, which is given below when describing the operation of the RPMC, provide the most noise-resistant reception of signals from each of the M radio components when the antenna elements 2 ₁ , ..., 2 _N are spaced apart at such distances

at which the voltages of the received signals and interference at the outputs of adjacent antenna elements with any serial numbers from 1 to N will be weakly correlated [10] (for the value of the spatial correlation radius [9] R _d → 0).

As the antenna elements 2 _1, ..., 2 _N 1 AFU may be used broadband antenna of vertical polarization [11], [12] and the horizontal polarization ([13], p. 264).

The above rather simple conditions deployment ASF 1 (without observing the condition of evenly spaced antenna elements 2 _1, ..., 2 _N in the composition of the antenna array defined configuration), allow the installation of the antenna elements 2 _1, ..., 2 _N and electronic RPmTs equipment generally at large-sized mobile facilities such as, for example, sufficiently large sea-going vessels or railway trains with RPMC “on the go” work. Moreover, the number N of antenna elements 2 ₁ , ..., 2 _N as part of the APS 1 of the proposed RPMC can be significantly less than in the known PRMC [6] (using the antenna array of the selected configuration) due to the possibility of using more efficient antenna elements 2 ₁ , ... , 2 _N and proposed methods for processing received signals from each of M radio subscribers.

As antenna elements 2 ₁ , ..., 2 _N RPMC deployed on such mobile objects, for example, small-sized low-profile broadband receiving antennas of the KB range, the code "Action" and "Action - KB-K" (SKZHG.464639.007 TU) can be used ) produced by NPP ROSMORSERVICE LLC, St. Petersburg. Antennas are designed for installation on ships, ships, coastal stationary and mobile communications, railway transport.

The above-mentioned deployment conditions of AFU 1 also allow the deployment of AFS 1 on the flat roof of one or several closely located buildings with a stationary version of the RPMTs design.

Each MCRPU 3 ₁ , ..., 3 _N with serial number n (n = 1,2, ..., N) has one high-frequency input, designed to connect the corresponding antenna element with serial number n to the output, and allows simultaneous reception of independent M reception channels. Processing of the received signals in the receiving channels is performed in digital form with direct analog-to-digital conversion of the radio signal without preliminary transformations of its frequency [3], [14]. The number of independent receive channels M of each MCPRC 3 ₁ , ..., 3 _N is determined by the maximum number of radio components interacting with the RPMC that emit signals at the respective carrier frequencies.

The multiplexing and switching of the generated digital streams coming from the outputs and inputs of the MCRPU 3 ₁ , ..., 3 _N to the inputs and outputs of the multiplexer 4 is organized on standard network protocols, which makes it possible to have the required number of MCRPU 3 ₁ , ..., 3 _N.

As switch 5 in the RPMC and switch UKS 13 in each UKS 12 ₁ , ..., 12 _M , an Ethernet switch of standard IEEE 802.3u 1000/100 Base - TX, for example, type EDS - 308 - T from MOXA, can be used. organization of a local information network (LIS) between devices connected to its corresponding outputs and inputs via the Ethernet interface.

The automated radio receiving center of the KB radio range is as follows.

In advance, before starting communication sessions with radio subscribers, control software 6, which is a computer, downloads special software (STR) and introduces a radio communication program to control the technical means of an automated RPMC and interacting (when operating as part of the URS KB range) RPdC (time of sessions; speed of data reception and transmission; classes of received and emitted signals; radiation power of signals in the direction of radio subscribers; texts are transmitted radiograms; etc.), e.g., for a day. In addition, in the driver of control signals 6 from the equipment for determining the coordinates of the location and timestamps 8 by LIS based on the switch 5, timestamps are entered to ensure the execution of the radio program in accordance with the planned time sequence of actions. At the same time, the time stamps are received via LIS on the basis of the switch 5 to the computer of the automated workstation (AWS) 9 via the communication line 10 to display the exact time for the radio operator operator RPmTs on the monitor screen. In addition to computers, a workstation may include, for example, a printer connected to a computer for documenting received information, and other peripheral devices [6].

The automatic functioning of the RPMC in accordance with the radio program is carried out under the control of open source software. In this case, the control signal generator 6 under the control of the STR generates the necessary control commands for RPMC hardware for communication sessions with radio subscribers along the following routes: the control signal generator 6 — LIS based on switch 5, through which control commands can be sent to the following RPMC hardware: МЦРПУ 3 ₁ , ..., 3 _N ; block demodulation and decoding 7; UKS 12 ₁ , ..., 12 _M (via multiplexer 4).

The necessary commands to control the technical means of the RPDC (when working as part of the URS) from the control signal generator 6 through the LIS based on the switch 5 are sent to the VUS 11 equipment, which provides interaction via a wired communication channel or via a radio channel (using wireless access equipment) with a similar VUS RPdTs equipment as part of the URS.

With automated control, the technical management teams of the RPMC and RPdTs (when working as part of the URS) follow in the same way through LIS based on the switch 5 from the computer AWP 9 through the communication line 10.

The output voltage of each n-th antenna element 2 ₁ , ..., 2 _N APS 1 with serial number n (n = 1,2, ..., N) is the voltage of the sample (copy) with the same serial number n received from the ether high-frequency signals and interference, which is fed to the input of the corresponding n-th MCRPU 3 ₁ , ..., 3 _N with the same serial number n, containing M independent receive channels.

In each n-th MCRPU 3 ₁ , ..., 3 _N, each m-th reception channel with serial number m (m = 1,2, ..., M) is set to the signal reception mode of the corresponding m-th radio subscriber to extract n from the output voltage of the nth voltage antenna element of the nth sample of the received signal of the mth radio subscriber. From the outputs of each n-th MCRPU 3 ₁ , ..., 3 _{N, the} voltage of the n-th sample of the received signal of the m-th radio subscriber is digitally supplied through multiplexer 4 to the corresponding inputs of the m-th UKS 12 ₁ , ..., 12 _M.

Thus, in each m-th UKS 12 ₁ , ..., 12 _M, through digital multiplexer 4, N digital signals are received, which represent in digital form the voltage N samples of the received signal of the m-th radio subscriber.

Moreover, in each m-th UKS 12 ₁ , ..., 12 _M voltage (in digital form) N signal samples of the m-th radio subscriber are fed to the inputs of the UKS 13 switch and, through the LIS based on the UKS 13 switch, the voltage of each n-th signal sample m -th radio subscriber is fed to the first inputs of the corresponding n-th phasing node 17 ₁ , ..., 17 _N with serial number n.

Since the bandwidth of each mth reception channel in each n-th MCRPU 3 ₁ , ..., 3 _N can be wider than the bandwidth occupied by the spectrum of the received signal of the m-th radio subscriber, then in each n-th phasing node 17 ₁ , ..., 17 _{N the} n-th sample of the received signal of the m-th radio subscriber is additionally filtered by a digital channel filter 18, the passband of which is consistent with the signal spectrum of the m-th radio subscriber.

The filtered mixture of the voltages of the nth sample of the received signal of the mth radio subscriber and the additive interference falling into the passband of the channel filter is leveled by a digital normalizing amplifier 19 and then goes to the first inputs of the first 20 and second 21 multipliers. After adjusting the phase (phasing) of the signal sample and its “weighting” in the second multiplier 21 (by multiplying the normalized total voltage of the n-th sample of the received signal and noise by the voltage from the output of the measuring filter 22, corresponding to the level (“weight”) of the voltage of the sample of the received signal in a normalized mixture of signal and interference), the voltage from the outputs of the second multiplier 21 (in digital form) is supplied to the corresponding inputs of the adder 14.

The result of summing the output voltages of the phasing nodes 17 ₁ , ..., 17 _N from the outputs of the adder 14 is filtered by the filter of the resulting oscillation 15 and fed to the inputs of the normalizing amplifier of the resulting oscillation 16, from the outputs of which this voltage is supplied to the second inputs of each of the phasing nodes 17 ₁ , ..., 17 _N with serial number n, in which this voltage is supplied to the second inputs of the first multiplier 20.

Thus, the structure of each m-th UKS 12 ₁ , ..., 12 _M (Fig. 2) is a closed loop self-regulation system with feedback, at the end of transient processes a mode is established in which in-phase (algebraic) addition at the output of the adder 14 is provided voltage N of the samples of the signal of the m-th radio subscriber and the geometric addition of the corresponding noise voltages with the corresponding "weight" coefficients proportional to the signal-to-noise voltage ratio at the output of the measuring filter 22 [10].

The voltage (in digital form) from the output of the filter of the resulting oscillation 15, which is the output voltage of the corresponding mth UKS 12 ₁ , ..., 12 _M or the resulting voltage of receiving the signal of the mth radio subscriber, is supplied to the inputs of the UKS 13 switch and through the LIS based on the switch UKS 13, as well as through LIS based on the switch 5, is fed to the inputs of the corresponding demodulator of the signal of the m-th radio subscriber of the demodulation and decoding unit 7. The demodulated and decoded signals of the m-th radio subscriber are received by LIS based on switch 5 in the computer AWP 9 through the communication line 10. The decoded signal of each m-th radio subscriber can be reflected on the screen of the computer AWP 9 and printed on a printer connected to the computer AWP 9. If necessary, transmit the received information, for example, to the control center via To the KB channel, the corresponding decoded signal of the m-th radio subscriber via LIS based on the switch 5 is fed to the VUS 11 equipment for further interaction with similar VUS RPdTs KB URS equipment.

If necessary, a demodulated signal of some mth radio subscriber can be transmitted via a standard interface to terminal equipment for special decoding, etc.

Let us analyze in more detail the work of any mth UKS 12 ₁ , ..., 12 _M with serial number m, which ensures optimal coherent summation of the voltages N of the samples of the signal of the mth radio subscriber from the outputs of the mth reception channels of the corresponding ICMPU 3 ₁ , ..., 3 _N.

To simplify the analysis, we will consider the operation of the mth UKS when receiving N samples of the signal of the mth radio subscriber on any stationarity interval of duration Δt, within which the voltage level of each nth sample of the signal of the mth radio subscriber does not change or changes slightly. Moreover, the duration of each interval Δt, selected within the duration of the conditional average “half-period” of fading of the samples of the signal of the mth radio subscriber T _P3 , should be greater than the time constant of the measuring filter 22 and more than the time constant of the AGC circuit of the normalizing amplifiers 16 and 19 of identical phasing nodes 17 ₁ , ..., 17 _N , but much less than the value of T _P3 .

We also assume that the transmission coefficient of any of the filters (15, 18, 22), as well as the adder 14, is equal to one. In addition, due to the fact that the structure of each UKS 12 ₁ , ..., 12 _M , as mentioned above, is a closed loop system with feedback, we will not take into account signal delays or changes in their initial phases when passing through these UKS filters.

In addition, for clarity, the principle of operation of any of the M UKS 12 ₁ , ..., 12 _M will be considered that the analyzed UKS (Fig. 2) is made in analog form and all operations performed by the components of the UKS will be described using analog signals, since the principle of operation of any ACS does not depend on the method of its implementation - in digital or analog form.

The main functional nodes of any m-th UKS 12 ₁ , ..., 12 _M are identical phasing nodes 17 ₁ , ..., 17 _N , the operation of any n-th phasing node with serial number n will be considered in more detail.

Let the first input (in the analysis we have in mind the analog input) of the nth phasing node 17 ₁ , ..., 17 _N , the voltage of the mth receiving channel of the nth ICMPU 3 ₁ , ..., 3 _N receiving the voltage of the nth the signal sample of the m-th radio subscriber, which can be represented on the stationarity interval Δt in the following analog form:

where U _Cnm and ϕ _Cnm are the amplitude and phase of the nth “sample” of the signal of the m-th radio subscriber;

ω _Cm is the carrier frequency of the signal of the m-th radio subscriber;

θ _{Cm (t)} is a function that determines the type of angular manipulation of the signal of the m-th radio subscriber.

It should be noted that in the proposed RPMC, the reception channels of the MCRPU 3 ₁ , ..., 3 _N should work in the off mode of their own automatic gain control systems (AGC), since the AGC of any m-th reception channel of any n-th MCRPU 3 ₁ , ..., 3 _N can adjust the signal level with a wider frequency band than the frequency band occupied by the signal of the m-th radio subscriber.

The AGC system of the normalizing amplifier 19 of each phasing node 17 ₁ , ..., 17 _{N of} any m-th UKS 12 ₁ , ..., 12 _M can be characterized by the control coefficient of the AGC system. The AGC control coefficient shows how many times the signal range at the output of the normalizing amplifier is less than at its input [10]:

where U _{BX MIN} and U _{OUT MIN} are the minimum input and minimum output voltages, which are limited by the value of the real sensitivity of the normalizing amplifier 19 of the phasing unit 17 ₁ , ..., 17 _N , and U _{BX MAX} and U _{OUT MAX} are limited by the maximum value of input oscillations, at which level of combinational components at the output of the normalizing amplifier 19 does not exceed the permissible.

For each of the normalizing amplifiers 16 and 19 of the phasing nodes 17 ₁ , ..., 17 _{N of} each m-th UKS 12 ₁ , ..., 12 _M, we will consider acceptable, for example, changing the signal at the input of the normalizing amplifier filtered by the corresponding filter 15 (18) by 100 dB when the signal at its output changes by no more than 3 dB. AGC systems with such parameters are implemented in modern radio receivers [3].

At the output of the normalizing amplifier 19 of the nth phasing node 17 ₁ , ..., 17 _{N, the} voltage of the filtered nth sample of the signal of the mth radio subscriber is normalized in level and fed to the input of the first multiplier 20, the other input of which comes from the normalizing amplifier of the resulting oscillation 16 the result of self-regulation of a closed system (UKS) is the resulting oscillation (“convolution”):

where U _Pnm , ω _Pm , ϕ _Pm are the amplitude, angular frequency, and phase of the resulting oscillation of the nth phasing node, which corrects the phase of the nth sample of the signal of the mth radio subscriber, respectively.

The output product of the first multiplier 20 of the n-th phasing node 17 ₁ , ..., 17 _N can be represented as:

where K _nm is the transmission coefficient of the normalizing amplifier 19 of the nth phasing node 17 ₁ , ..., 17 _{N of the} mth UKS 12 ₁ , ..., 12 _M , at which the nth sample of the input signal with the amplitude U _{Cnm is normalized} .

The first term in braces (4) is easily eliminated by the measuring filter 22, because its spectrum is much higher than the spectrum of the second term.

The second term in curly brackets (4) is harmonic oscillation (without manipulation) at the difference circular frequency ω _Фm = ω _{Cnm -ω Pm} , which coincides with the central frequency of the measuring filter 22. Since this oscillation is directly proportional to the amplitude of the received signal sample U _Cnm and the coefficient _Since K _nm (at U _Pnm ≈const and K _nm U _Cnm ≈const), then in the absence of interference at the input of the nth phasing node under consideration 17 ₁ , ..., 17 _N , at the output of measuring filter 22, the amplitude of this oscillation will be maximum and correspond to maximum " weight "voltage of the received i-th sample of the signal of the m-th radio subscriber in the normalized oscillation at the output of the normalizing amplifier 19.

The output voltage of the measuring filter 22 of the n-th phasing node 17 ₁ , ..., 17 _N , taking into account the foregoing, can be represented as:

For a more accurate evaluation of n-th node phasing 17 _1, ..., 17 _N m-th MSC 12 _1, ..., 12 _M-level or "weights» n-th signal sample of m-th radioabonenta a normalized signal mixture and interference at the output of the normalizing amplifier 19, the passband of the measuring filter 22 of each phasing unit 17 ₁ , ..., 17 _N , on the one hand, should be extremely small, and on the other hand, it is necessary that this band provides the ability to "track" the level of the nth "sample »The signal of the m-th radio subscriber during its fading and changes in the carrier frequency of the signal during its reception. In the practical implementation of the RPMC, this band can be selected on the order of (20-25) Hz.

The output product of the second multiplier 22 of the n-th phasing node 17 ₁ , ..., 17 _N will be:

The first term in curly brackets (6) is eliminated during further filtering of the output product of the adder 14 by the filter of the resulting oscillation 15 and can be ignored. Therefore, the phase-corrected voltage in the nth phasing node of the nth sample of the signal of the m-th radio subscriber at the output of the filter of the resulting signal 15 (excluding other N-1 summed output voltages of the phasing nodes) can be represented as:

In this case, the result of the algebraic addition of the output voltages of all phasing nodes 17 ₁ , ..., 17 _{N of the} mth UKS 12 ₁ , ..., 12 _M at the output of the filter of the resulting oscillation 15 or the resulting voltage of the reception of the signal of the mth radio subscriber at the input of the signal demodulator m the radio subscriber of the demodulation and decoding unit 7 taking into account (7) is written in the form:

.From (8) it follows that the voltage of each of the N received samples of the signal of the m-th radio subscriber in the corresponding m-th UKS 12 ₁ , ..., 12 _M using the corresponding phasing node 17 ₁ , ..., 17 _N with serial number n is reduced to a single the resulting frequency ω _Pm and phase ϕ _Pm is squared, after which the voltages of all N received samples of the signal of the m-th radio subscriber are in-phase (algebraically) summed (in power) in the adder 14 with the corresponding weight coefficients

.

With relatively large values of the signal-to-noise ratio h _nm = U _nm / U _{П nm} at the output of the m-th receiving channel of each n-th MCRPU 3 ₁ , ..., 3 _N (h _im > 1), at the phasing nodes 17 ₁ , ... , 17 _N, the voltage amplitudes of the corresponding samples of the signal of the mth radio subscriber are equalized by each of the normalizing amplifiers 19 to a certain value, the maximum range of which does not exceed 3 dB when the input voltage amplitude changes to 100 dB.

If, when operating in the KB channel with fading, the voltage amplitudes of the samples of the signal of the m-th radio subscriber can vary, for example, within 60 dB relative to their minimum values, at which the relation h _nm > 1 at the input of each n-th phasing node is still preserved 17 ₁ , ..., 17 _n, then the output value of the normalized amplitude of oscillation U _CH phasing each node 17 _1, ..., 17 _n with a sequence number n may assume approximately the same:

Since the phasing nodes 17 ₁ , ..., 17 _{N are} identical, the amplitude U _{Pm of the} resulting oscillation of the form (3) at the output of the normalizing amplifier 16 of each phasing node (under the above conditions) can also be considered the same:

In view of (9) and (10), expression (8) can be represented as:

From (11) it follows that each m-th UKS 12 ₁ , ..., 12 _M can provide an increase in the power of the received nth signal sample of the corresponding m-th radio component up to N times.

Using the normalizing amplifier 16, the resulting voltage, determined by the expression (8) or (11), is normalized by level and reduced to the form (3), which proves the correctness of the analysis of the operation of any UKS 12 ₁ , ..., 12 _M.

будет поступать преобразованное напряжение этого образца сосредоточенной по спектру помехи с выхода второго перемножителя 21 n-го узла фазирования на соответствующий вход сумматора 14.Using the above method for analyzing the operation of any UKS 12 ₁ , ..., 12 _M, it is not difficult to show that when exposed to the air with the signal of the mth radio subscriber, an additive spectrum-concentrated noise, for example, in the form of harmonic oscillations at a fixed frequency within the band frequency occupied by the signal of the m-th radio subscriber, then the received voltages N of the “samples” of this interference falling into the pass-band of the channel filters 18 of the corresponding phasing nodes 17 ₁ , ..., 17 _{N of the} m-th UKS 12 ₁ , ..., 12 _M will add up geometrically . Moreover, the larger the voltage amplitude of the sample concentrated along the interference spectrum at the input of the channel filter 18, for example, the nth phasing node 17 ₁ , ..., 17 _N with respect to the voltage amplitude of the nth "sample" signal of the mth radio subscriber at the input of this filter, the one with lower weight

the converted voltage of this sample will be concentrated in the interference spectrum from the output of the second multiplier 21 of the n-th phasing node to the corresponding input of the adder 14.

), пораженных сосредоточенными по спектру помехами.Since as part of the AFS 1 of the proposed RPMC, each of the N / 2 antenna elements 2 ₁ , ..., 2 _{N / 2 is} designed to receive the electromagnetic field (EMF) of horizontal polarization, and each of the N / 2 other antenna elements 2 _{N / 2 + 1} , ..., 2 _{N is} designed to receive vertical polarized EMF, then when operating on the air together with the signal of the mth radio subscriber concentrated on the interference spectrum, samples of which fall into the passband of the channel filter 18 phasing nodes 17 ₁ , ..., 17 _{N of the} mth UKS 12 _1, ..., 12 _M, it is possible to increase the value of the resulting Aspect of the signal / noise ratio at the output of the SMS (in the resulting oscillation output of filter 15) by summing at adder 14 the individual signal samples (reception channels) m-th radioabonenta free of interference, and to suppress other receiving channels (integrable with small weights

) affected by spectrum-centered interference.

In this case, the received samples of the signal of the m-th radio subscriber (or the m-th reception channels of the corresponding MCRPU 3 ₁ , ..., 3 _N ) will be affected by interference, the direction of polarization of the electromagnetic fields of which coincides with the direction of polarization of the electromagnetic fields of interference. Otherwise, these samples of the signal of the mth radio subscriber will be free from interference, or to some extent affected by interference, depending on the angle between the vectors corresponding to the polarization directions of the EMF of the signal and interference samples.

, корреляция уровней образцов сигнала и помех на выходах антенных элементов уменьшается (при

[9]), соответственно при работе в канале с замираниями эти уровни изменяются независимо друг от друга [10]. Из этого следует, что при уменьшении уровней, например, первых Q образцов сигнала m-го радиоабонента ниже порогового уровня (при глубоких замираниях сигналов), когда соотношение сигнал/помеха h _nm =U _Cnm / U _{П nm} (n=1,2,…,Q) на выходе m-го канала приема каждого из Q МЦРПУ 3₁,…,3_Q становится меньше единицы (h _nm <l), уровни напряжений других N-Q образцов этого сигнала обеспечат соотношение h _nm >1 (n=Q+1, Q+2,…,N) на выходе m-го канала приема каждого из N-Q МЦРПУ 3_Q+1,…,3_N.In addition, as noted above, when removing from each other any two adjacent antenna elements 2 ₁ , ..., 2 _N APS 1 at a distance

, the correlation of the levels of signal samples and interference at the outputs of the antenna elements decreases (at

[9]), respectively, when working in a channel with fading, these levels change independently of each other [10]. It follows that when the levels, for example, of the first Q samples of the signal of the mth radio subscriber are lower than the threshold level (with deep fading of the signals), when the signal-to-noise ratio h _nm = U _Cnm / U _{П nm} (n = 1,2, ..., Q) at the output of the mth channel for receiving each of the Q ICRCU 3 ₁ , ..., 3 _Q becomes less than unity (h _nm <l), the voltage levels of the other NQ samples of this signal will provide the relation h _nm > 1 (n = Q + 1, Q + 2, ..., N) at the output of the m-th receiving channel of each of the NQ MCPRC 3 _{Q + 1} , ..., 3 _N.

In accordance with (11), the resulting voltage at the filter output of the resulting oscillation 15, which is the output signal of the mth UKS 12 ₁ , ..., 12 _M, or the resulting voltage of the reception of the signal of the mth radio subscriber, which is then fed to the input of the signal demodulator of the mth radio subscriber block demodulation and decoding 7, can be written as:

. Таким образом, как при замираниях напряжений отдельных образцов сигнала m-го радиоабонента, так и при действии прицельных сосредоточенных по спектру помех [10], когда на выходе каждого m-го канала приема соответствующих Q МЦРПУ 3₁,…,3_Q соотношение сигнал/помеха h _nm <l, прием осуществляется за счет когерентного суммируемых напряжений других m-ых каналов приема соответствующих N-Q МЦРПУ 3_Q+1,…,3_N, на выходе каждого m-го канала приема которых соотношение сигнал/помеха h _nm >1.It is taken into account in expression (12) that Q terms are excluded from summation during the formation of the resulting oscillation, since the voltage amplitude of each of them at the output of the second multiplier 21 of the corresponding phasing nodes 17 ₁ , ..., 17 _Q is multiplied by the “weight” coefficient

. Thus, both during the fading of the voltages of individual samples of the signal of the mth radio subscriber, as well as under the action of interference-focused interference spectra [10], when at the output of each mth receiving channel the corresponding Q ICMP 3 ₁ , ..., 3 _Q signal / interference h _nm <l, reception is carried out due to the coherent summed voltages of the other m-th reception channels corresponding to the NQ MCRPU 3 _{Q + 1} , ..., 3 _N , at the output of each m-th reception channel whose signal-to-noise ratio is h _nm > 1.

When working on multi-hop routes, when a signal is transmitted by the m-th radio subscriber, several radio beams can arrive at the receiving point at different angles of arrival with independent fading of the EMF intensity levels of each of the beams, m-th UKS 12 ₁ , ..., 12 _M at the beginning of a communication session "Tuned" to receive samples of the signal of the m-th radio subscriber from a more powerful "main" radio beam. At the same time, if in the process of conducting a communication session there are simultaneous deep fading of most samples of the signal of the “main” radio beam, then the mth UKS can automatically adapt to receiving samples of the signal of the mth radio subscriber from another more powerful radio beam at a given time interval. The tuning time is determined by the time constant of the narrow-band measuring filter 22 phasing units 17 ₁ , ..., 17 _N.

The implementation of the present invention is an automated radio receiving center of the short-wave range radio communication node will allow to achieve the following advantages compared to known automated radio receiving centers [1], [2], [5], [6]:

1. To increase the noise immunity of signal reception from each of the M radio subscribers when operating on single hop and multi hop KB radio paths of various lengths under conditions of deep fading of received signals.

2. To reduce the deployment time of AFS 1 of the mobile version of the RPMC operating in parking lots by eliminating a number of preparatory work before the direct deployment of antenna elements from AFS 1.

3. To expand the possibilities of using RPMTs by ensuring the deployment of antenna elements of the ASF 1, for example:

- in severely rugged terrain or mountainous terrain;

- on the flat roofs of nearby buildings and structures;

- on bulky sea vessels;

- on railway platforms, including on the roofs of special wagons, etc.

Information sources

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Claims (4)

1. An automated radio receiving center of a shortwave radio communication center comprising an antenna-feeder system (APS) consisting of N antenna elements remote from each other with serial numbers from 1 to N, the output of each antenna element with serial number n is connected to the input of the corresponding multi-channel digital a radio receiving device (MCRPU) with the same serial number n, containing M independent receive channels with serial numbers from 1 to M, the outputs-inputs of each MCRPU with serial number n are connected to the corresponding the existing inputs and outputs of the multiplexer, the outputs and inputs of which are connected to the corresponding inputs and outputs of the switch, the outputs and inputs of which are connected respectively with the inputs and outputs of the driver of the control signals, with the inputs and outputs of the demodulation and decoding unit, with the inputs and outputs of the apparatus for determining location coordinates and time stamps, with inputs and outputs of an automated workstation through a communication line, as well as inputs and outputs of intra-node communication equipment, characterized in that M devices of coherent signal addition (UKS) with serial numbers from 1 to M, the inputs and outputs of each of which with serial number m are connected to the corresponding additional outputs-inputs of the multiplexer, each UKS with serial number m contains a switch of the UKS, whose inputs and outputs are inputs - ACS outputs with serial number m, an adder, a filter of the resulting oscillation, a normalizing amplifier of the resulting oscillation and N phasing nodes with serial numbers from 1 to N, the first inputs of each of which with serial number Measures n are connected to the corresponding outputs of the UKS switch, the inputs of which are connected to the corresponding outputs of the filter of the resulting oscillation, combined with the corresponding inputs of the normalizing amplifier of the resulting oscillation, the outputs of which are combined with the corresponding second inputs of each phasing node with serial number n, the outputs of each phasing node with serial number n are connected to the corresponding inputs of the adder, the outputs of which are connected to the corresponding inputs of the filter of the resulting oscillations, each phasing node with serial number n contains a channel filter, the inputs of which are the first inputs of the phasing node with serial number n, the outputs of the channel filter are connected to the corresponding inputs of the normalizing amplifier, the outputs of which are connected to the corresponding first inputs of the first multiplier and to the corresponding first inputs of the second multiplier, the outputs of which are the outputs of the phasing unit with serial number n, the second inputs of the second multiplier are connected to the corresponding outputs measurement filter rows having inputs connected to respective outputs of the first multiplier, the second inputs of which are the second inputs of phasing unit with sequence number n. 2. The automated radio receiving center of the shortwave radio communication center according to claim 1, characterized in that, as part of the AFS, the distance between any two adjacent antenna elements with any serial numbers from 1 to N must be at least

where λ is the maximum wavelength of the received signal from any of M radio subscribers. 3. The automated radio receiving center of the shortwave radio communication center according to claim 1, characterized in that, as part of the AFS, each of the N / 2 antenna elements with serial numbers from 1 to N / 2, identical in design, is designed to receive an electromagnetic field (EMF ) horizontal polarization, and each of the other N / 2 antenna elements with different serial numbers from N / 2 + 1 to N, identical in design, is designed to receive EMF of vertical polarization. 4. The automated radio receiving center of the shortwave radio communication center according to claim 1, characterized in that, as a part of the AFS, each of the N / 2 antenna elements with serial numbers from 1 to N / 2 is of a mixed type - both of identical design and various design , designed to receive horizontal polarized EMF, and each of the other N / 2 antenna elements with different serial numbers from N / 2 + 1 to N of mixed type - both identical design and different design Ia is designed for receiving vertical polarization EMF.

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