RU2614055C1 - Method for radio-electronic destruction of conflict-resistant radio-electronic equipment - Google Patents

Abstract

FIELD: radio electronics.

SUBSTANCE: invention relates to method for combating radio-electronic systems and can be used for active counteraction to conflict-resistant (CR) radio-electronic equipment (REE). Said result is achieved due to the fact, method for radio-electronic destruction of REE CR includes reception of signals by phased antenna array (PAA), emitted by destructed REE CR, detection of received signals, determination of their arrival direction, repetition period and range to destructed REE CR, PAA radiation of interfering ultra-high frequency signals (microwave signals) in the direction of destructed REE CR with delay of each interference microwave signal relative to the arrival of signal emitted by destructed REE CR, control over the process of signal emission from destructed REE CR, given that before radiation of interference microwave signals one performs probing of arrival direction for signals, emitted by destructed REE CR with the help of pilot signal on frequency of interfering microwave signal radiation, receives pilot signal, reflected by destructed REE CR and measures amplitude-phase distribution (APD), formed at PAA elements, further at the moments of time t_n equal to

, where T - period of receiving signals form destructed REE CR; R_n – distance from destructed REE CR to n-element of PAA; c – speed of light, each n-th element of PAA in the direction of destructed REE CR emitting interference microwave signals with initial phase, which is equal to complex-conjugated value of measured APD on n-th element of PAA.

EFFECT: achieved technical result – increased efficiency.

1 cl, 2 dwg

Description

The invention relates to techniques for dealing with electronic systems and is intended to actively counter conflict-resistant (KU) electronic means (RES).

A known method of counteracting air defense (air defense) and a device for its implementation [1]. The method includes passive direction finding of air defense systems in the radio and optical ranges, analysis of the data by a computing device, generation of location signals, emitting them through active jamming stations in the optical and radar ranges in the direction of air defense means. The reflected signals are received by passive direction finders, they determine the range, speed, coordinates and speed of convergence with air defense systems. They give commands to counteract active stations with interference in the direction of air defense systems, a device for ejecting expendable funds, and transmitting data for the use of standard weapons.

The disadvantage of this method is its low efficiency, which is manifested in the fact that upon termination of the counteraction by active stations of interference, the suppressed air defense system can immediately resume its work in normal mode.

A known method of functional damage to a radar station with a phased antenna array [2], selected as a prototype, including receiving signals emitted by RES, detecting received signals, determining the direction of their arrival, the repetition period and the distance to the affected RES, emitting high-power microwave signals (microwave signals) in the direction of the affected RES with a delay of each microwave signal relative to the arrival of the signal emitted from the affected RES, the monitoring of the process of emission of the RES signals.

, где L - пространственный размер ФАР; λ - длина волны излучения, много больше единицы, приводит к снижению эффективности радиоэлектронного поражения (РЭП) КУ РЭС.The disadvantage of the prototype method is that its use in devices with antenna systems, for example with phased array antennas (PAR) of arbitrary configuration and / or large-aperture PAR with relative electrical dimensions

where L is the spatial size of the PAR; λ is the radiation wavelength, much greater than unity, leads to a decrease in the efficiency of electronic destruction (RE) of KU RES.

.The problem to which the invention is directed, is to expand the field of practical application of the prototype method in the case of a REP radio electronic signal by an interfering microwave signal emitted by a HEADLAND of a random configuration and / or a large-aperture HEADLAND with a relative electric size much larger than unity

.

.The technical result of the invention is to increase the efficiency of the RE KU RES interfering microwave signal emitted by a HEADLAND of a random configuration and / or a large-aperture HEADLAND with a relative electric size much larger than unity

.

, где Т - период следования сигналов поражаемого КУ РЭС; R_n - расстояние от поражаемого КУ РЭС до n-го элемента ФАР; с - скорость света, каждым n-м элементом ФАР в направление поражаемого КУ РЭС излучают помеховые СВЧ-сигналы с начальной фазой, равной комплексно-сопряженному значению измеренного АФР на n-м элементе ФАР.The problem is solved, and the required technical result is achieved by the fact that in the known prototype method, which includes receiving the phased array signals emitted by the affected KU RES, detecting the received signals, determining the direction of their arrival, the repetition period and the distance to the affected KU RES, the radiation of the phased array microwave interference - signals in the direction of the affected KU RES; with a delay of each interfering microwave signal relative to the arrival of the signal emitted by the struck KU RES; monitoring the process of radiation of signals from the affected KU RES; the fact that, in addition, according to the invention, before the emission of interfering microwave signals, the direction of arrival of the signals emitted by the affected KU RES from the pilot signal at the frequency of emission of the interfering microwave signals is sensed, a pilot signal reflected by the struck KU RES is received, and the amplitude-phase distribution (AFR) is measured, formed by it on the PAR elements, then at times t _n equal

where T - the period of the signals of the affected KU RES; R _n is the distance from the affected KU RES to the n-th element of the PAR; c is the speed of light, each n-th element of the headlamp in the direction of the affected KU RES contains radiated microwave signals with an initial phase equal to the complex conjugate of the measured AFR on the n-th element of the headlamp.

, где Т - период следования сигналов поражаемого КУ РЭС; R_n - расстояние от поражаемого КУ РЭС до n-го элемента ФАР; c - скорость света, позволяет скомпенсировать различные фазовые набеги на трассе распространения "n-й элемент ФАР - поражаемое КУ РЭС" и повысить уровень помехового СВЧ-сигнала на входе приемного устройства поражаемого КУ РЭС. Следствием этого является расширение области практического применения изобретения и создание способа РЭП КУ РЭС помеховым СВЧ-сигналом, излучаемым ФАР произвольной конфигурации и/или крупноапертурной ФАР с относительным электрическим размером много больше единицы

.Introduction of additional procedures for sensing the angular direction in which the KE RES affected by the pilot signal at the frequency of the interference microwave signal is located, followed by the measurement of the AFR generated by it on the PAR elements and the emission of the interference microwave signal in the direction of the affected KES RES with the initial phase, equal to the complex conjugate value measured in the PRA instants t _n equal

where T - the period of the signals of the affected KU RES; R _n is the distance from the affected KU RES to the n-th element of the PAR; c - the speed of light, allows you to compensate for various phase incursions along the propagation path "n-th element of the PAR - affected KU RES" and increase the level of the microwave interference signal at the input of the receiving device of the affected KU RES. The consequence of this is the expansion of the field of practical application of the invention and the creation of a method for REP KU RES with an interfering microwave signal emitted by a HEADLAND of a random configuration and / or a large-aperture HEADLAND with a relative electric size much larger

.

The invention is illustrated by the example of a device having a phased array antenna (PAR) of arbitrary configuration with N blocks of transceiver elements (PES), N blocks of transceiver modules (PPM), interconnected by a highly stable coherent communication line, N blocks controlled phase shifters (UFV), a signal divider block, a radio intelligence unit (RTR), N analog-to-digital conversion (ADC) blocks, a digital adjustment factor calculator (SC) block, an interfering signal generator block , synchronization unit, power amplifier unit (PA). In this case, the input / outputs of the N blocks of the PPE FAR are connected to the input / output of the corresponding blocks of the PPM. The output of each PPM block is connected in parallel with the input of the corresponding ADC block and the corresponding input of the RTP block, which form the signal group of the inputs of the RTP block. The control output of the RTP block is connected to the second input of each PPM block, which is the control input of the PPM block. The output of each of the ADC block is connected to the corresponding input of the block of the digital computer SK. Each of the N outputs of the SC digital computer unit is connected to the second input of the corresponding UVB unit, which is the control input of the UVB unit. The output of each UVB block, which is the signal output of the UVB block, is connected to the input of the corresponding PPM block. The first input of each UVB block, which is the signal input of the UVB block, is connected to the corresponding output of the signal splitter block. The input of the signal divider block is connected to the output of the PA unit. The input of the PA unit is connected to the output of the interfering signal generator unit. The clock input of the jamming signal generator unit is connected to the first output of the synchronizer unit. The synchronizing input of the SC digital computer unit is connected to the second output of the synchronizer unit. The clock input of the RTP block is connected to the third output of the synchronizer block.

To state the essence of the proposed method of REP KU RES, we believe that in the far zone of the phased array of the device according to the claimed method is the affected KU RES, emitting pulsed signals, the parameters of which, including the direction to the affected KU RES, are determined by the RTR unit.

A separate value of the complex amplitude of the field R of the interfering microwave signal in the far zone of an arbitrary PAR, consisting of N PES blocks in the direction of the unit vector u, is determined by the relation [3, p. 273]

- волновое число; λ - длина волны излучения;

- комплексная амплитуда тока возбуждения n-го элемента ФАР; u - орт (единичный вектор), характеризующий направление наблюдения относительно нормали к апертуре ФАР; j - мнимая единица [4, стр. 26].where Г _n (u) is the complex transmission coefficient of the tropospheric propagation channel from the nth element of the PAR in the direction of the unit vector u; Y _n (u) = g _n (u) exp (jkur _n ) is the complex pattern of the n-th PAR element, the position of which in the general coordinate system is determined by the vector r _n ; g _n (u) is the vector pattern of the n-th PAR element;

- wave number; λ is the radiation wavelength;

- the complex amplitude of the excitation current of the nth element of the PAR; u is the unit vector (unit vector) characterizing the direction of observation relative to the normal to the PAR aperture; j is the imaginary unit [4, p. 26].

.Under the condition of a quasistationary model of the tropospheric microwave signal propagation channel, the phase value of the complex transmission coefficient of the tropospheric microwave signal propagation channel in the direction normal to the linear headlamp is the same for each of its elements and is

.

приводит к тому, что значение фазы коэффициента Г_n(u) для n-го,

блока ППЭ ФАР в направлении ее нормали (u=0), представляется в виде суммы среднего значения и случайной величины, отсчитанных относительно опорного блока ППЭ ФАР, произвольная геометрия расположения элементов ФАР в (1) учтена в коэффициентах Г_n(u),

) [5]The use of headlamps of arbitrary configuration and / or large-aperture headlamps with a relative electric size much larger than unity

leads to the fact that the phase value of the coefficient Г _n (u) for the nth,

block PES FAR in the direction of its normal (u = 0), is represented as the sum of the average value and a random value counted relative to the reference block PES FAR, the arbitrary geometry of the arrangement of elements of the PAR in (1) is taken into account in the coefficients Г _n (u),

) [5]

- среднее значение фазы комплексного коэффициента передачи тропосферного канала распространения в направлении нормали к ФАР; ϕ_n - пространственная случайная величина с нулевым математическим ожиданием и дисперсией

.Where

- the average phase value of the complex transmission coefficient of the tropospheric propagation channel in the direction normal to the headlamp; ϕ _n - spatial random variable with zero mathematical expectation and dispersion

.

Using (2), we write a separate normalized value of the complex amplitude of the field R in the far zone of the linear equidistant headlamp, up to an amplitude factor

where ψ = kd sin (θ) is the generalized angular coordinate; θ is the angle measured from the normal to the headlamp; d is the distance between the blocks of the PPE HEADLIGHT.

Assuming in (3) | I _n | = 1, the normalized value of the average power of the interfering microwave signal at the input of the receiving device of the affected KU RES, is written

, где ρ(n,m) - пространственный коэффициент корреляции случайной величины ϕ_n,

и полагая

, где μ - радиус пространственной корреляции случайной величины ϕ_n,

, выражение (4) примет видGiven that

, where ρ (n, m) is the spatial correlation coefficient of a random variable ϕ _n ,

and putting

, where μ is the radius of the spatial correlation of the random variable ϕ _n ,

, expression (4) takes the form

.Where

.

в выражении (2), характеризует величину отклонения (степень отличия) волнового фронта СВЧ-сигнала от линейного. Измерение ϕ_n,

и их учет в фазе тока возбуждения каждого блока ППЭ ФАР, позволит скомпенсировать влияния неопределенности в значениях коэффициентов Г_n(u),

на величину средней мощности помехового сигнала на входе приемного устройства подавляемой РЭС.For the far diffraction zone (Fraunhofer zone), the set of spatial random variables ϕ _n ,

in expression (2), characterizes the deviation (degree of difference) of the wavefront of the microwave signal from the linear one. Measurement ϕ _n ,

and taking them into account in the phase of the excitation current of each PPE FAR block will compensate for the effects of uncertainty in the values of the coefficients Г _n (u),

the value of the average power of the interfering signal at the input of the receiving device of the suppressed RES.

для каждого блока ППЭ ФАР постоянно на интервале времени T: ϕ_n(t)=ϕ_n, t∈T, где Т - интервал квазистационарности тропосферного канала. Это обстоятельство позволяет для измерения ϕ_n,

применить известные методы, например, [6]. Для этого перед излучением помехового СВЧ-сигнала в направлении поражаемого КУ РЭС, в этом же направлении на частоте помехового СВЧ-сигнала излучается пилот-сигнал (СВЧ-сигнал пониженной мощности), регистрируется отраженный от поражаемого КУ РЭС сигнал (эхо-сигнал) и измеряется АФР, создаваемое им на блоках ППЭ ФАР. Результатом измерения АФР являются значения величин ϕ_n,

, совокупность которых образует фазовое распределение (ФР) СВЧ-сигнала, прошедшего тропосферный канал распространения на блоках ППЭ ФАР относительно ее опорного блока ППЭ. Далее измеренные величины

, где "^" - знак измеренного значения величины, учитываются в фазе комплексных амплитуд токов возбуждения соответствующих блоков ППЭ ФАР. Учет измеренных значений

выполняется в соответствии с правилом, определяемым выражениемThe value of ϕ _n ,

for each PES block of the PAR, it is constant over the time interval T: ϕ _n (t) = ϕ _n , t∈T, where T is the quasistationary interval of the tropospheric channel. This circumstance allows for the measurement of ϕ _n ,

apply known methods, for example, [6]. To do this, before emitting the interference microwave signal in the direction of the affected KU RES, in the same direction, at the frequency of the interfering microwave signal, a pilot signal (microwave signal of reduced power) is emitted, the signal reflected from the affected KU RES (echo signal) is measured and measured AFR, created by him on the blocks of PPE FAR. The result of measuring AFR are the values of ϕ _n ,

, the combination of which forms the phase distribution (RF) of the microwave signal that has passed the tropospheric propagation channel on the PES blocks of the PHAR relative to its reference block PES. Further measured values

, where "^" is the sign of the measured value of the value, are taken into account in the phase of the complex amplitudes of the excitation currents of the corresponding blocks of the PES of the PAR. Measured value accounting

performed in accordance with the rule defined by the expression

- измеренное значение пространственной случайной величины ϕ_n на n-м блоке ППЭ ФАР.Where

- the measured value of the spatial random variable ϕ _n on the nth block of the PES of the PHAR.

независимыми и одинаковыми для каждого из блоков ППЭ ФАР, выражение для нормированного значения средней мощности помехового сигнала на входе приемного устройства поражаемого КУ РЭС по заявляемому способу примет видSubstituting (6) into (3) and assuming measurement errors

independent and identical for each of the PPE FAR blocks, the expression for the normalized value of the average power of the interfering signal at the input of the receiving device of the affected KU RES according to the claimed method will take the form

- дисперсия ошибки измерения величин

.Where

- variance of measurement error

.

Expression (5) characterizes the normalized value of the average power of the interfering signal at the input of the receiving device of the affected KU RES according to the prototype method.

Expression (7) characterizes the normalized value of the average power of the interfering signal at the input of the receiving device of the affected KU RES according to the claimed method.

, является величина средней мощности помехового СВЧ-сигнала на входе приемного устройства поражаемого КУ РЭС. Повышение эффективности заявляемого способа относительно способа-прототипа при использовании ФАР произвольной конфигурации и/или крупноапертурной ФАР с относительным электрическим размером много больше единицы

по показателю "величина нормированного значения средней мощности помехового СВЧ-сигнала на входе приемного устройства РЭС" вычисляется в соответствии с выражениемAn indicator that determines the effectiveness of the proposed method of REP KU RES when using a HEADLAND of arbitrary configuration and / or a large-aperture headlamp with a relative electric size is much larger than unity

is the value of the average power of the interfering microwave signal at the input of the receiving device of the affected KU RES. Improving the effectiveness of the proposed method relative to the prototype method when using a HEADLAND arbitrary configuration and / or large-aperture HEADLAND with a relative electric size is much larger than unity

according to the indicator "the value of the normalized value of the average power of the interfering microwave signal at the input of the receiver of the RES" is calculated in accordance with the expression

- нормированное значение средней мощности помехового СВЧ-сигнала на входе приемного устройства РЭС, вычисляемое по заявляемому способу и способу-прототипу соответственно.Where

- the normalized value of the average power of the interfering microwave signal at the input of the receiver of the RES, calculated by the present method and the prototype method, respectively.

, определяемые (5), (7), и полагая, что фазовое распределение эхо-сигнала на блоках ППЭ ФАР измеряется без ошибок

, имеемSubstituting in (8) the values

defined by (5), (7), and assuming that the phase distribution of the echo signal on the PES of the PHAR units is measured without errors

, we have

, по оси ординат - Δ. Представленные зависимости построены для числа блоков ППЭ в ФАР равное N=10, при значении μ радиуса пространственной корреляции величины ϕ_n,

μ=0 (непрерывная линия) и μ=0.7 (пунктирная линия). Как следует из представленных зависимостей, введение дополнительных процедур по зондированию углового направления, в котором находится поражаемое КУ РЭС пилот-сигналом на частоте излучения помехового СВЧ-сигнала, с последующим измерение АФР, создаваемого им на блоках ППЭ ФАР и излучением помехового СВЧ-сигнала в направлении поражаемого КУ РЭС с начальной фазой, равной комплексно-сопряженному значению измеренного АФР в моменты времени t_n равные

, где Т - период следования сигналов поражаемое КУ РЭС; R_n - расстояние от поражаемого КУ РЭС то n-го блока ППЭ ФАР; с - скорость света, позволяет на "Δ⋅100%" процентов (Δ⋅100%>1) повысить эффективность РЭП КУ РЭС устройством с ФАР произвольной конфигурации и/или крупноапертурной ФАР с относительным электрическим размером много больше единицы

. Так для условий N=10, μ=0,

заявляемый способ на ~35% эффективнее способа-прототипа по показателю "величина нормированного значения средней мощности помехового СВЧ-сигнала на входе приемного устройства РЭС".In FIG. Figure 1 shows plots of dependence (9). The abscissa represents the variance of ϕ _n ,

, along the ordinate axis - Δ. The presented dependences were constructed for the number of PES blocks in the PAR equal to N = 10, with the value of the radius of the spatial correlation radius ϕ _n ,

μ = 0 (continuous line) and μ = 0.7 (dashed line). As follows from the presented dependences, the introduction of additional procedures for sensing the angular direction in which the KU RES affected by the pilot signal at the radiation frequency of the interfering microwave signal is located, followed by measuring the AFR created by it on the PES of the PAR and the radiation of the interfering microwave signal in the direction affected KU RES with an initial phase equal to the complex conjugate value of the measured AFR at time t _n equal

where T - the period of the signals affected by KU RES; R _n is the distance from the affected KU RES then the n-th block of the PPE FAR; c is the speed of light, which makes it possible to increase the efficiency of RE KU RES by a device with a HEADLAND of a random configuration and / or a large-aperture headlamp with a relative electric size much larger than unity by "Δ⋅100%" percent (Δ⋅100%> 1)

. So for the conditions N = 10, μ = 0,

the claimed method is ~ 35% more efficient than the prototype method in terms of the indicator "value of the normalized value of the average power of the interfering microwave signal at the input of the receiver of the RES".

The inventive method of electronic destruction of KU RES is illustrated by the graph shown in Fig.1 and the drawing presented in Fig. 2.

In FIG. 1 presents the results of calculating the magnitude of the increase in the efficiency indicator of the proposed method of REP KU RES in relation to the prototype method.

In FIG. 2 presents an electrical block diagram of a device that implements the inventive method of REP KU RES. The numbers in figure 2 indicate:

1 - block transceiver element (PES) phased array antenna (PAR) of the device according to the claimed method;

2 - block transceiver module (PPM) PAR;

3 - block controlled phase shifter (UVB);

4 - signal divider block;

5 - block radio intelligence (RTR);

6 - block analog-to-digital Converter (ADC);

7 - block digital calculator quotation coefficients (UK);

8 - block generator interference signal;

9 - block synchronizer;

10 - power amplifier unit (PA).

The device (see Fig. 2) according to the claimed method includes a phased array (PAR) of arbitrary configuration with N blocks 1 of transceiver elements (PES), N blocks of 2 transceiver modules (PPM) interconnected by a line highly stable coherent communication, N blocks of 3 controlled phase shifters (UVB), block 4 of the signal divider, block 5 of radio intelligence (RTR), N blocks of 6 analog-to-digital conversion (ADC), block 7 of the digital calculator of quotation coefficients (SC), block 8 of the generator interfering signal unit 9 synchronization, block 10 power amplifier (PA).

In this case, the input / outputs of N blocks 1 of the PPE of the PHAR are connected to the input / output of the corresponding blocks of 2 PPM. The output of each PPM block 2 is connected in parallel with the input of the corresponding ADC block 6 and the corresponding input of the RTR block 5, which form the signal group of the inputs of the RTR block 5. The control output of the RTP block 5 is connected to the second input of each PPM block 2, which is the control input of the PPM block 2. The output of each of block 6 of the ADC is connected to the corresponding input of block 7 of the digital computer SK. Each of the N outputs of block 7 of the digital computer SK is connected to the second input of the corresponding block 3 of the UVB, which is the control input of the block 3 of the UVB. The output of each block 3 UVB, which is the signal output of block 3 UVB, is connected to the input of the corresponding block 2 PPM. The first input of each block 3 of the UVB, which is the signal input of the block 3 of the UVB, is connected to the corresponding output of the block 4 of the signal splitter. The input of block 4 of the signal splitter is connected to the output of block 10 of the PA. The input of unit 10 of the PA is connected to the output of unit 8 of the interfering signal generator. The clock input of block 8 of the jamming signal generator is connected to the first output of block 9 of the synchronizer. The clock input of block 7 of the digital computer SK is connected to the second output of block 9 of the synchronizer. The clock input of the RTP block 5 is connected to the third output of the synchronizer block 9.

Block 1 PES provides reception / transmission of a microwave signal, can be performed, for example, in the form of a mirror antenna [3, p. 371].

Block 2 PPM performs the formation of a given level of microwave power when emitting microwave signals, separate control of the amplitude and phase of the emitted and received microwave signals with the required adjustment depth, installation accuracy and stability over time, can be performed, for example, on the basis of the active PPM HEADLIGHTS [7, p. 18].

Block 3 UVB carries out a phase change of the transmitted signal (wave), can be performed on the basis of a phase shifter of a discrete type, for example [3, p. 176].

Block 4 of the signal divider distributes the signal from one source (master oscillator) along the "N" channels of the PAR, can be performed on the basis of a multi-channel power divider, for example [8].

Block 5 RTR detects signals reconnaissance RES, evaluates their parameters, the angular direction to reconnaissance RES, can be performed on the basis of electronic intelligence stations, for example, [9, p. 234].

Block 6 of the ADC converts the received microwave signal into digital form, can be performed, for example, on the basis of the ADM214 × 10M submodule [10].

Block 7 of the digital computer SK performs the calculation of the AFR signal of the received headlamp in accordance with the algorithm [6] according to the criterion of minimum error dispersion [11, p. 45-47], can be performed on the basis of a digital signal processing processor, for example, the TMS320C30 chip [12, p. 88].

Block 8 of the generator of the interfering signal implements the formation of the interfering signal emitted by the PAR, can be performed on the basis of a solid-state generator of low power [7, p. 22].

Block 9 synchronizer synchronizes the operation of the device according to the claimed method, can be performed on the basis of frequency dividers [13, p. 602-603].

Unit 10 power amplifier (PA) amplifies the input signal, can be performed, for example, on the basis of a solid-state power amplifier [7, p. 25].

The operation of the device according to the claimed method is illustrated by the drawing of FIG. 2.

, определяющие фазовое распределение пилот-сигнала на блоках 1 ППЭ ФАР.Let in the area of the claimed device is KU RES, emitting signals. The signals emitted by the affected KU RES are received by N blocks 1 of the PPE of the phased array and through N blocks of 2 PPM arrive at block 5 of the RTR. Based on the synchronizing signal of synchronizer unit 9, the RTR unit 5 evaluates the range, the repetition period, the direction to the affected KU RES, and also the delay of the received signal with respect to each of the 1st PPE FAR units. Further, before emitting an interfering microwave signal for REP KU RES, according to the synchronizing signal of the synchronizer unit 9, the interfering signal generator unit 8 generates a pilot signal at the frequency of the interfering microwave signal, arrives at the PA unit 10. The amplified pilot signal through block 4 of the signal divider is fed to the signal input of each of the N blocks 3 UVB and. From the signal output of each block 3 UFV pilot signal is supplied to the signal input of the corresponding block 2 PPM and then through the input / output of the corresponding block 1 PPE PHAR is radiated in the direction of the affected KU RES. After the delay time, determined by the range to the affected KU RES, the reflected pilot signal received by N blocks 1 of the PPE of the PAR through the corresponding blocks of 2 PPM, enters the corresponding blocks 6 of the ADC, where it is digitized. The digitized pilot signal from the outputs of blocks 6 of the ADC is supplied to block 7 of the digital computer SK. In block 7 of the digital computer SK calculate values ϕ _n ,

that determine the phase distribution of the pilot signal on blocks 1 PES FAR.

, с соответствующего выхода блока 4 делителя сигнала помеховый СВЧ-сигнал поступает на сигнальный вход соответствующего блока 3 УФВ. Одновременно с этим на управляющий вход каждого блока 3 УФВ с блока 7 цифрового вычислителя ЮК, по синхронизирующему сигналу блока 9 синхронизатора, поступает управляющий сигнал, устанавливающий в каждом из N блоков 3 УФВ соответствующий фазовый сдвиг, равный измеренному значению

, который устанавливает комплексную амплитуду I_n токов возбуждения блоков 1 ППЭ ФАР равную

, где φ₀ - начальное значение фазы тока возбуждения блока 1 ППЭ ФАР. С выхода блоков 3 УФВ помеховый СВЧ-сигнал поступает на сигнальный вход соответствующего блока 2 ППМ, далее на соответствующий блок 1 ППЭ ФАР и излучается в направлении поражаемого КУ РЭС.For REP KU RES, block 9 of the synchronizer generates a corresponding synchronization signal, which enters block 8 of the generator of the interfering signal. By the synchronizing signal of the synchronizer unit 9, the interfering signal generator unit 8 generates an interfering microwave signal, which enters the PA unit 10, where it is amplified. The amplified interfering microwave signal from the output of unit 10 of the amplifier enters the unit 4 of the signal splitter. According to the synchronizing signal of the block 9 synchronizer at time t _n equal to

, from the corresponding output of block 4 of the signal splitter, the interfering microwave signal is fed to the signal input of the corresponding block 3 of the UVB. At the same time, a control signal is supplied to the control input of each UHF unit 3 from block 7 of the UK digital computer by the synchronizing signal of the synchronizer unit 9, setting in each of the N UHF units 3 a corresponding phase shift equal to the measured value

, which sets the complex amplitude I _n of the excitation currents of the blocks 1 PES of the PAR equal to

where φ ₀ is the initial value of the phase of the excitation current of block 1 of the PES of the PHAR. From the output of the UVV blocks 3, the interfering microwave signal is fed to the signal input of the corresponding PPM block 2, then to the corresponding block 1 of the PPE of the PAR and is radiated in the direction of the affected KU RES.

, которые соответствуют фазовому распределению пилот-сигнала на блоках 1 ППЭ ФАР, обеспечивает РЭП КУ РЭС помеховым СВЧ-сигналом, излучаемым ФАР произвольной конфигурации и/или крупноапертурной ФАР с относительным электрическим размером много больше единицы

.Perform control in units 3 of UVB in accordance with the measured values

, which correspond to the phase distribution of the pilot signal on the PES block 1 of the PAR, provides the RE KU RES with an interfering microwave signal emitted by a PAR of arbitrary configuration and / or a large-aperture phased array with a relative electric size much larger than unity

.

. Следствием этого является расширение области применения изобретения и создание способа РЭП КУ РЭС помеховым сигналом, излучаемый ФАР произвольной конфигурации и/или крупноапертурной ФАР с относительным электрическим размером много больше единицы

.Thus, the claimed method, for the situation considered, allowed to increase by ~ 35% the efficiency of the RE KU RES by an interfering microwave signal emitted by a HEADLAND of arbitrary configuration and / or a large-aperture HEADLAND with a relative electric size much larger than unity

. The consequence of this is the expansion of the scope of the invention and the creation of a method of REP KU RES interfering signal emitted by a HEADLAND of a random configuration and / or a large-aperture HEADLAND with a relative electric size much larger than unity

.

Sources

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Claims (1)

The method of electronic defeat (REP) of a conflict-resistant (KU) electronic means (RES), including the reception of a phased array antenna (PAR) of the signals emitted by the affected KU RES, detection of received signals, determining the direction of their arrival, the period and range to the affected KU RES the radiation of the phased array of interfering microwave signals (UHF) signals in the direction of the affected KU RES with a delay of each interfering microwave signal relative to the arrival of the signal emitted by the struck KU RES, process control emitting signals to the affected KU RES, characterized in that, in addition, before emitting the interfering microwave signals, the direction of arrival of the signals emitted by the struck KU RES from the pilot signal at the radiation frequency of the interfering microwave signals is sensed, a pilot signal reflected by the affected KU RES is received, and measure the amplitude-phase distribution (AFR) formed by it on the elements of the PAR, then at times t _n equal

where T - the period of the signals of the affected KU RES; R _n is the distance from the affected KU RES to the n-th element of the PAR; c is the speed of light, each n-th element of the headlamp in the direction of the affected KU RES contains radiated microwave signals with an initial phase equal to the complex conjugate of the measured AFR on the n-th element of the headlamp.

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