RU2459342C1 - Resonant converter of dc voltage into dc and ac and method to control its output voltage - Google Patents

Abstract

FIELD: electricity.

SUBSTANCE: in an available resonant converter with a serial circuit L, C, there is a parallel circuit from an inductance L2 of a transformer and a series capacitor C2, besides, Q-factors of circuits make 1.5. To the upper (or lower) valves of the inverter pulses arrive with a duration equal to a half-cycle of resonant quality of circuits, and to the lower (or upper) valves - pulses, duration of which complies with adjustment, besides, the period of inverter switching is by 4-5% more than the period of circuit oscillations, and either fronts of pulses or their centres match.

EFFECT: converter has smaller dimensions, higher efficiency factor, wide range of adjustment, low multiplication factor of currents, harmonic current of valves, independence of an output voltage on a load, a simple control device and simplicity of tuning.

7 cl, 9 dwg

Description

The invention relates to the field of electrical and radio engineering and can be used as power sources of constant and alternating voltage in various fields of the national economy, for example, generators in radio systems, etc.

Known resonant DC-DC to DC converter (patent No. 235858 RU, HO 2M 3/338, publ. 10.10.08), containing a bridge inverter on valves with reverse conductivity, connected by one diagonal to a power source, a transformer, the primary winding of which is in series with the inductance L is connected to the second diagonal of the inverter, capacitance C, shunting the second winding of the transformer, a rectifier connected to the secondary winding of the transformer, a low-pass filter in the form of a capacitance connected in parallel with the load and Connecting to the rectifier and a control device comprising a series of measurement sensors, a computing device, and other elements. Inductance L, capacitance C with load resistance R form a L-shaped oscillatory circuit with a resonant frequency that is 2 times the inverter switching frequency.

The disadvantages of this converter are:

- small adjustment area (pulse duration within

- a strong dependence of the output voltage on the load resistance and resistance limitations ρ <R <3ρ, where ρ is the wave impedance of the LCR circuit;

- a very complex control system, since at high powers the current transition through zero is not defined and you have to calculate the turn-on time and the duration of the so-called "dead" time when the valves are turned off;

- low reliability and large dimensions;

- A great time tuning the converter.

Known resonant DC-DC to AC and DC converter (circuits for switching power supplies and their application. - M .: "Dodena - XXI" 2001 - 608 S.), selected as a prototype, containing a bridge inverter on valves with reverse conductivity, connected one diagonal to the power source, a transformer whose primary winding is connected in series with the inductance L and capacitance C, is connected to the second diagonal of the inverter, a rectifier connected to the secondary winding of the transformer, and G-arr a basic low-pass filter connected to the rectifier and containing an inductance connected in series with the capacitance and load resistance connected in parallel. The converter also contains a control device - a microcontroller UC 3875, specially designed to control resonant voltage converters. The resonant frequency of the series LCR circuit (where R is the total load resistance, reduced to the primary side of the transformer) is approximately equal to the inverter switching frequency, which can be adjusted. The "dead" time required during operation of the converter is also regulated by the selection of two RC chains. To obtain good harmonic oscillations and suppress parasitic Q-factors of the circuit should be sufficiently large (4-5). The transformer output is an AC voltage output.

The main disadvantage of this converter is the need to select the mentioned RC circuits with simultaneous adjustment of the switching frequency to obtain a good harmonic current shape, which requires a long setup time for each specific converter, unreliable and reduces the efficiency of the converter.

The disadvantage is also large reactive power on the elements L and C of the circuit due to the requirement of high quality factor, which increases their dimensions. The disadvantage is that when adjusting the voltage of the converter, “dead” time falls into the region of harmonic currents and can disrupt the current shape and the control process.

The microcontroller UC 3875 (microcircuits for switching power supplies and their application. - M .: Dodena-XXI 2001 - 608 p.) Implements a phase method for controlling the output voltage of a voltage converter, which consists in generating rectangular pulses of half the duration period of the resonant frequency, and with a repetition frequency slightly lower than the resonant (adjustable), and they are fed to the valves of one arm of the inverter with a half-period shift of this frequency, and between the pulses of the valves form an adjustable "dead" in remy. Similar pulses arrive at the valves of the other arm of the inverter. The voltage of the converter is controlled by changing the phase shift φ between the pulse signals of the inverter arms. In this case, the time for connecting the load circuit to the power source changes, and thereby the duration of the pulses supplied to the oscillating load circuit changes.

The disadvantage of this method is the need for three adjustments (switching frequency and two RC chains) at the same time when setting each converter, as well as the fact that the "dead" time crashes into the current area.

This requires a long setup time for each specific converter, reduces the reliability and efficiency of the converter.

A known method of controlling a resonant voltage converter (patent No. 235858 RU, HO 2M 3/338, publ. 10.10.08), selected as a prototype, which consists in the fact that they form rectangular pulses with a given repetition rate, feed them to the inputs of the inverter valves with reverse conductivity and thus switch the load circuit relative to the poles of the power source with the same frequency, and the duration of the pulses arriving at the first valves connected to one pole of the source is equal to half the period of the connection frequency inverter, and the duration of the pulses arriving at the gates connected to the other pole corresponds to a predetermined level converter output voltage. In this case, with the help of sensors, the shape of the output current is controlled, the moment of passage of the current through zero, the necessary amount of "dead" time and the moment of its inclusion or change in the switching period of the inverter are calculated.

The disadvantage of this method is its complexity and complexity of implementation, which reduces the efficiency, reliability of the converter, complicates setup, maintenance and increases the size.

The aim of the invention is:

- increase the efficiency of the Converter,

- increased reliability,

- reduction in size,

- reduction in cost and maintenance costs,

- reducing the setup time of the Converter,

- improving the quality of harmonic voltage,

- stimulating the development of microcontrollers that implement the proposed temporary method for controlling the output voltage of a resonant voltage converter due to

- setting the guaranteed minimum "dead" time and its location in the current nodes,

- minimum number of adjustments: inverter switching frequency and output voltage level,

- reducing the reactive power of the elements of the oscillatory circuit,

- use as a resonant circuit of a high-order filter (fourth),

- simplification of control devices and their use of standard microcircuits used in voltage converters.

In accordance with the object of the invention and the proposed technical solution, the resonant DC-DC to AC / DC converter, comprising a bridge inverter on valves with reverse conductivity, connected by a single diagonal to a power source, a transformer whose primary winding is connected in series with inductance L and capacitance C, is connected to the second diagonal of the inverter, a rectifier connected to the secondary winding of the transformer, and a low-pass filter, for example a L-shaped link connected to the rectifier, as well as the control device, according to the technical solution, the primary winding of the transformer is bridged with a capacitance C ₂ , which with an inductance L _{2 of the} transformer forms a parallel circuit L ₂ C ₂ R, where R is the total load resistance, reduced to the primary side of the transformer. Both circuits are tuned to a frequency greater than 4-5% of the inverter switching frequency.

In the voltage conversion, the AC voltage output in accordance with the proposed technical solution, the quality factor of the circuits is 1-1.5, and the control device contains a UC 3825 microcontroller with mounted RC elements corresponding to the inverter switching frequency and the converter output voltage stabilization mode, two D-flip-flops, D-inputs of which are grounded, S-inputs through logic elements are NOT connected to outputs 11, 14 of the microcontroller, respectively, C-inputs are connected to output 4 of the microcontroller, direct trigger outputs moat through drivers connected to the unregulated inverter gates (upper or lower), and outputs 11, 14 through microcontroller drivers are connected to the adjustable valves (upper or lower).

The converter has an AC voltage output from the third winding of the transformer, in accordance with the proposed technical solution, has a Q factor of 1.5-2, and the control device contains a UC 3825 microcontroller with mounted RC elements corresponding to the inverter switching frequency and pulse duration at outputs 11, 14 a microcontroller equal to a quarter of the period of the resonant frequency of the circuits (the duration is adjustable), two D-flip-flops, the S-inputs of which are not connected to the outputs 11, 14 of the microcontroller via logic elements and accordingly, the D-inputs of which are grounded, the C-inputs are connected to the output 4 of the microcontroller, an integrator, the input of which is connected through the 2OR element to the outputs 11, 14 of the microcontroller, an inverting amplifier, the input of which is connected to the output of the integrator, a comparator, the direct input of which is connected to the amplifier’s output, while the inverse is connected to an adjustable voltage divider, the direct outputs of the triggers through the drivers are connected to the unregulated valves of the inverter (top or bottom), two 2I elements, one of which inputs are connected to the compar output torus, and the other - to the direct outputs of flip-flops, respectively, the outputs 2I elements connected via controllable valves to the driver inverter (lower or upper).

In accordance with the goal in a method for controlling the output voltage of a resonant DC-DC to AC / DC converter, which consists in the fact that rectangular pulses are formed with a given repetition rate, they are fed to the valve inputs of the bridge inverter of the converter and thus the load circuit is switched relative to the poles of the power source with the same frequency, and the duration of the pulses arriving at the first valves connected to one pole corresponds to a given level nu output voltage, according to the proposed technical solution, the duration of the pulses arriving at the first valves equal to half the oscillation period of the inverter circuit and less than half the switching period of the inverter on the value of the minimum of "dead" time constituting the standard value (4-5% of the half cycle of the inverter switching).

In the method of controlling the output voltage of the resonant voltage converter, the leading edges of the pulses arriving at both valves coincide.

In the method of controlling the output voltage of the resonant voltage converter, the centers of both coincide.

The essence of the technical solution is illustrated by drawings, where:

Figure 1, 2 presents the electrical circuits (options) of the inventive resonant DC-DC to DC and AC.

Figure 3 presents the electrical diagram of the device for controlling the output voltage of the inventive Converter according to option 1.

Figure 4 presents a diagram of a device for controlling the output voltage of the inventive converter according to option 1 in the form of a microcontroller, similar to UC 3825.

Figure 5 presents a diagram of a device for controlling the output voltage of the inventive Converter according to option 2.

Figure 6 presents timing diagrams explaining the principle of operation of the inventive Converter according to option 1.

Figure 7 presents time charts explaining the principle of operation of the inventive Converter according to option 2.

On Fig presents time diagrams explaining the principle of operation of the Converter prototype with a control device UC 3875.

Figure 9 presents time charts explaining the principle of operation of the Converter according to patent No. 2335841 RU, the control method of which is a prototype of the proposed control method.

The resonant DC-DC to AC and DC converter, Figs. 1 and 2, contains a bridge inverter 1 on valves with reverse conductivity 2, 3, 4, 5, connected with a diagonal of 2.5-3.4 to a power supply Ep, an oscillating circuit 6, containing inductance 7 (L ₁ ), capacitance 8 (C ₁ ), capacitance 9 (C ₂ ), transformer 10 with inductance L ₂ , and capacitance 9 shunts the primary winding of transformer 10, and inductance 7, capacitance 8 and primary transformer winding are connected in series and connected to another diagonal 2.3-4.5 inverter, bridge you ryamitel 11 with diodes 12, 13, 14, 15, connected to the secondary winding of the transformer 10 and the lowpass filter 16 comprising the inductance 17 connected in series with a parallel connected capacitance 18 and the load 19 resistance.

The output of the alternating voltage to the load 20 in figure 1 is carried out directly from the secondary winding of the transformer 10, and in figure 2 from the third winding, which provides galvanic isolation of constant and alternating voltages.

Inductance 7 and capacitance 8 form a serial circuit, and the inductance of transformer L ₂ with capacitance 9 is a parallel circuit, and together it is a fourth-order bandpass filter with a given resonant frequency

)Such a filter provides good harmonic suppression regardless of the value of the load resistance at a low Q factor of the circuits (1-1.5), i.e. low reactive power on its elements. For example, the level 3 of the harmonic with respect to the first with a Q factor of 1.5 is (

)

We also have

The voltage at inductors L ₁ and capacitance C ₁ is 1.5 times higher than at the load (reduced to the primary side of the transformer), and the current in inductance L ₂ and at capacitance C ₂ is 1.5 times higher than at load.

The voltage control device of the inventive converter according to embodiment 1, figure 3, contains a UC 3825 microcontroller, the RC mounted parts of which provide a given inverter switching frequency, "dead" time (the RC chain is connected to the inputs of the microcontroller 5, 6, 7), soft start (capacity connected to input 8), stabilization and output voltage level (a divider connected to input 16 sets the reference voltage at input 2, an RC circuit connected to inputs 3, 2 works in an integrator circuit, a divider connected to input 1 sets uro voltage output voltage), outputs 11, 14 are connected via drivers to adjustable valves 3, 4 of the converter (Figs. 1, 2), 2 D-flip-flops T1, T2, D-inputs of which are grounded, 5 - inputs through logical elements NOT 3, 4 connected to the outputs 11, 14 of the microcontroller, and direct through the drivers are connected to unregulated valves 2, 5 of the Converter (figure 1, 2).

The operation of the inventive Converter according to option 1 is illustrated by timing diagrams, Fig.6.

The microcontroller UC 3825 generates pulses U ₃ , U ₄ (Fig.6c) at the outputs 11, 14 with the switching frequency of the inverter set by the RC circuit (inputs 5, 6, 7 UC) and a duration τ corresponding to the output voltage level of the converter, as well as short pulses (4 UC output), the duration of which determines the "dead" time (4-5% of the inverter switching period). The pulses U ₃ , U ₄ (Fig.6c) switch the triggers T1, T2 to the single state, the pulse from the output 4 of the UC switches them to zero, as a result, the pulses U ₂ , U ₅ (Fig.6a) are formed at the direct outputs of the triggers, equal to the period of the resonant frequency of the oscillatory circuit. By adjusting the switching frequency of the inverter, you can easily choose the duration of the trigger pulses for a given value of the resonant frequency, taking into account the hard "dead" time. The pulses from the outputs 11, 14 of the UC and from the outputs of the triggers through the drivers go to the inputs of the corresponding valves and as a result, the voltage U (FIG. 6c) of the meander type and duration corresponding to the adjustable output voltage of the converter is generated at the inverter output. As you know, only odd harmonics 1, 3, 5 ... etc. are present in a type of meander voltage. with relative amplitudes of 1, 1/3, 1/5 ...

фиг.6с). Как следует из изложенного, ток инвертора и выходное напряжение негармонические. Для получения постоянного напряжения это не имеет значения, а для переменного определим уровень третьей гармоники относительно первой, например при

то есть при максимальном напряжении питания. Применяя преобразование Фурье, имеемDue to the properties of the oscillatory circuit L ₁ C ₁ L ₂ C ₂ R, the voltage of the first harmonic (resonant frequency) is phased with the input current and the output voltage of the oscillatory circuit. The voltage pulse U at the inverter input can be represented as two infinite voltage surges. The response of the oscillating circuit to each jump will be a sinusoid of the input current and output voltage, the shift of these sinusoids is equal to the pulse duration τ. Thus, the inverter current and the voltage at the transformer output will be determined by the difference of two sinusoids with a shift of τ: the sinusoid from the beginning of the pulse to its end and then decline to zero, and zero in the middle of the segment

figs). As follows from the above, the inverter current and the output voltage are not harmonic. To obtain a constant voltage, this does not matter, but for the variable we determine the level of the third harmonic relative to the first, for example,

that is, at maximum supply voltage. Applying the Fourier transform, we have

I ₁ = 0.887 I _m , I ₃ = 0.056 I _m , I ₃ / I ₁ = 0.056 / 0.887 = 0.063

Q₁=Q₂=1,5, Ω=f/f₀=3It should also be noted that our oscillatory circuit is not ideal and the harmonic ratio at its output for

Q ₁ = Q ₂ = 1.5, Ω = f / f ₀ = 3

The total level of the third harmonic will be 0.08 = 8%. For many applications, this level is acceptable; otherwise, additional filtering must be applied. At minimum

зависит от τ и составляет при τ=Т/2-π/2=1,5 а при τ=Т/4-2,2. В силу свойств предложенной колебательной цепи уровень выходного напряжения не зависит от изменения сопротивления нагрузки от номинального до холостого хода и определяется средним уровнем напряжения на входе инвертора (если его выпрямить).Multiplicity of currents

depends on τ and is at τ = T / 2-π / 2 = 1.5 and at τ = T / 4-2.2. Due to the properties of the proposed oscillatory circuit, the level of the output voltage does not depend on the change in load resistance from nominal to idle and is determined by the average voltage level at the inverter input (if rectified).

Thus, the addition of a single capacitance C ₂ , the use of a transformer as an element of the oscillating circuit, the selection of the proposed values of the quality factor of the links of this circuit, the proposed control device is an essential sign and allows to achieve the purpose of the invention. The novelty lies in the fact that for the first time in voltage converters a high-order filter with the specified parameters was used, as well as a new control device, Figs. 3, 4.

(делитель напряжения на входах 2, 16 UC), 2 D-триггера T1, T2, D-входы которых заземлены, S-входы - через логические элементы НЕ 3, 4 подключены к выходам 11, 14 UC, интегратор 5, вход которого через элемент 2 ИЛИ 6 подключен к выходам 11, 14 UC, инвертирующий усилитель 7, вход которого подключен к интегратору 5, компаратор 8, прямой вход которого подключен к выходу усилителя 7, а инверсный - к делителю напряжения, регулирующему выходное напряжение преобразователя, две логические схемы 2И 9, 10, подключенные одними входами к выходу компаратора 8, а другие входы подключены к выходам триггеров T1, T2 соответственно, прямые выходы триггеров T1, T2 через драйверы подключены к входам нерегулируемых вентилей 2, 5 преобразователя, фиг.1, 2, а выходы элементов 9, 10 подключены к входам регулируемых вентилей 3, 4.The control device of the resonant DC-DC to AC and DC converter according to option 2 of figure 5 contains a UC 3825 microcontroller with attachments corresponding to a given inverter switching frequency and "dead time" (RC circuit connected to inputs 5, 6, 7 of UC), soft start (capacitance at input 8 UC), pulse duration at outputs 11, 14 UC equal to

(voltage divider at inputs 2, 16 UC), 2 D-flip-flops T1, T2, D-inputs of which are grounded, S-inputs - through logic elements NOT 3, 4 connected to outputs 11, 14 UC, integrator 5, whose input is through element 2 OR 6 is connected to the outputs 11, 14 of the UC, the inverting amplifier 7, the input of which is connected to the integrator 5, the comparator 8, the direct input of which is connected to the output of the amplifier 7, and the inverse to the voltage divider regulating the output voltage of the converter, two logic circuits 2and 9, 10, connected by one input to the output of comparator 8, and other inputs connected s to the outputs of the triggers T1, T2, respectively, the direct outputs of the triggers T1, T2 through the drivers are connected to the inputs of the unregulated gates 2, 5 of the converter, FIGS. 1, 2, and the outputs of the elements 9, 10 are connected to the inputs of the adjustable gates 3, 4.

,

фиг.7g), то есть ток не прерывается.The principle of operation of the resonant Converter according to option 2 is illustrated by the timing diagrams of Fig.7. The microcontroller generates at the output 4 UC pulses corresponding to "dead time", and at the outputs 11, 14 UC pulses, the duration of which is equal to a quarter of the period of the resonant frequency, with the switching frequency of the inverter. These pulses are fed to the inputs S and C of the triggers, as a result, the pulses of Figs.7a), b) of duration equal to half the period of the resonant frequency, which through the drivers control the unregulated valves 2, 5 of the inverter are generated at the outputs of the triggers T1, T2 (Fig. 1, 2). The pulses from the outputs 11, 14 of the UC start the integrator 5, as a result, a symmetrical gable sawtooth voltage is generated at the output of the integrator, which after inversion by the amplifier 7 has the form of FIG. 7c). This voltage on the comparator 8 is compared with the reference U _reg , and as a result, pulses of duration τ are formed at the output of the comparator, which, after logical multiplication with the output pulses of the triggers T1, T2, form the pulses of fig.7d), e), centered with the pulses of fig.7a) , b), and through the drivers controlling the adjustable valves 3, 4 of the inverter, Figs. 1, 2. As a result, an impulse voltage of the meander type is generated at the inverter output, Fig. 7g), the pulses of which are of duration τ are centered relative to the switching moments of the inverter and “dead” time. " The first harmonic of this voltage (cosine) is also centered relative to the same moments for any pulse duration. By properties oscillatory circuit current in the oscillating circuit at its input and output voltage are also a cosine wave form and the same location, 7G) -U _O, I. current flows either through the included valves (2-4, 3-5), or through the included unregulated valves 2, 5 and the reverse diodes of the same valves

,

Fig.7g), that is, the current is not interrupted.

«мертвое время» находится всегда в нуле тока, а содержание третьей гармоники (определено выше) составляет 1,6% относительно первой. Область регулировки - весь полупериод

.Thus, at the output of the converter we always have an alternating voltage of a harmonic shape, the amplitude of which does not depend on the load resistance (the transmission coefficient of the oscillating circuit at the resonant frequency is 1), the current through the inverters is also harmonic, the current ratio

“Dead time” is always at zero current, and the content of the third harmonic (as defined above) is 1.6% relative to the first. Adjustment area - the whole half-cycle

.

On Fig presents time diagrams explaining the principle of operation of the control device UC 3875, controlling, for example, the Converter, figure 1.

At the outputs UC, pulse signals of FIG. 8a) are generated that control the left arm 2, 3 of the inverter. The duration of the pulses is half the period of the resonant frequency, and the phase shift between the pulses of the valves in the end is half the period of the resonant frequency plus "dead time". Thus, the included states of the valves 2, 3 in the shoulder are separated by "dead time".

The same signals are applied to the valves of the right shoulder (Fig.8b).

The output voltage level is adjusted by changing the phase shift between the pulse signals of the shoulders. In this case, the connection time of the load circuit to the power source corresponding to the pulse signals of Fig. 8c) is changed. At the inverter output, we have a meander type voltage, Fig. 8f).

The features of this control system are that when the valves 2, 3 (Fig. 8c) are turned off, the current of the oscillatory circuit does not interrupt, since at this time its input is closed by valves 5-3 and 4-2, and the oscillatory circuit goes into free oscillation mode .

Fig. 8d) shows that the "dead time" crashes into the current region, and it is shown what can happen in this case: spurious oscillations and distortion of the pulse shape. The main disadvantage of this control device is that the indicated pulse duration is achieved by three adjustments: a change in the switching frequency and a change in the "dead time" of the two shoulders of the inverter (RC circuit).

Figure 6 presents the timing diagrams explaining the principle of operation of the Converter, patent No. 2355841 RU.

The case of low power supply voltage E _n ≈U _O and two modes of operation: low power, when the duration of pulses of regulated valves small mode and high power mode, when the duration of these pulses is large. According to the control method, valves 2, 5 are adjustable, and valves 3, 4 are unregulated, with a pulse duration equal to half the period of the switching frequency, the loop frequency is 2 times the switching frequency of the inverter.

периода, и при этом ток в нагрузку не поступает; t₂ - ток постоянный, поддерживается непосредственно источником питания и поступает в нагрузку; t₃ - разряд индуктивности на нагрузку; t₄ - отсутствие тока до начала следующих циклов.We have 4 cycles: the time t _{1 is the} recharge of the capacitance C of the circuit and the charge of inductance L. This cycle is

period, and while the current does not enter the load; t ₂ - constant current, supported directly by the power source and supplied to the load; t ₃ - inductance discharge to the load; t ₄ - no current until the next cycles.

In high power mode (at the same supply voltage), the t ₃ cycle enters the region of the next half-cycle, and the inclusion of "dead time" does not give anything, since the source voltage and output voltage are equal. It follows that it is necessary to increase the oscillation period, that is, to reduce the switching frequency.

The case of E _n > U _{o is} considered in (patent No. 2335841, figure 5), whence it follows that the converter must have a series of sensors and computing devices, that is, a very complex control system, which is its drawback. In addition, the load resistance has a limitation. This follows from the equality of the inductance charge energies and the capacitance overcharge:

откуда имеем

where do we have

By condition

t₄=0;

t ₄ = 0;

When R = R _max ; t ₂ = 0:

Resistance limit:

ρ <R <3ρ

This technical solution allows to increase the efficiency of the converter, increase reliability, reduce dimensions, reduce cost and maintenance costs, reduce the setup time of the converter, improve the quality of harmonic voltage,

Claims (7)

1. The resonant DC-DC to AC and DC converter, containing a bridge inverter on valves with reverse conductivity, connected by one diagonal to a power source, a transformer, the primary winding of which is connected in series with inductance L ₁ and capacitance C ₁ (forming a series oscillatory circuit), connected to the second diagonal of the inverter, a rectifier connected to the secondary winding of the transformer, and a low-pass filter (for example, L-shaped link) connected to the rectifier, and also a control device, characterized in that the primary winding of the transformer is shunted by a capacitance C ₂ , which, with the transformer inductance L _2, forms a parallel circuit tuned to the frequency of the series oscillatory circuit, which is 4-5% higher than the inverter switching frequency. 2. The resonant DC-DC to AC and DC converter according to claim 1, characterized in that the quality factor of the circuits is 1-1.5, and the control device contains a UC 3825 microcontroller with attachments. 3. The resonant DC-DC to AC and DC converter according to claim 1 or 2, characterized in that the hinged elements of the microcontroller correspond to the inverter switching frequency, "dead time" and the converter output voltage stabilization mode, two D-flip-flops, whose D-inputs are grounded , S-inputs via logic elements are NOT connected to outputs 11, 14 of the microcontroller, respectively, direct outputs of triggers through drivers are connected to unregulated inverter valves (lower or upper), and outputs 11, 14 of micro Through the drivers, the controller is connected to adjustable valves (top or bottom). 4. The resonant DC-DC to AC and DC converter according to claim 1 or 2, characterized in that the hinged elements of the microcontroller correspond to the inverter switching frequency, "dead time" and the pulse duration at the outputs 11, 14 of the microcontroller, equal to a quarter of the period of the resonant frequency of the circuits, two D-flip-flops, whose S-inputs through logic elements are NOT connected to the outputs 11, 14 of the microcontroller, the D-inputs are grounded, the C-inputs are connected to the output 4 of the microcontroller, an integrator whose input is through the element 2 OR connected to the outputs 11, 14 of the microcontroller, an inverting amplifier, the input of which is connected to the output of the integrator, a comparator, the direct input of which is connected to the output of the amplifier, and the inverse to the adjustable voltage divider, the direct outputs of the triggers through the drivers are connected to unregulated valves of the inverter (upper or lower ), two 2I elements, one of whose inputs are connected to the output of the comparator, and the other to the direct outputs of the triggers, respectively, the outputs of the 2I elements are connected via drivers to the adjustable inverter valves (neither him or upper). 5. The method of controlling the output voltage of the resonant DC-DC to AC and DC converter, which consists in the formation of rectangular pulses with a given repetition frequency, feed them to the valve inputs of the bridge inverter of the converter and thus switch the load circuit relative to the poles of the power source with the same frequency moreover, the duration of the pulses arriving at the first valves connected to one pole of the power source is constant, and the duration of the pulses arriving them to the valves connected to the second pole, corresponds to a given level of the output voltage of the Converter, characterized in that they form pulses arriving at the first valves with a duration equal to half the period of oscillation of the circuits of the Converter and less than half the period of switching the inverter by the value of the minimum "dead time", making up the standard value (4-5% of the inverter switching half-period). 6. The control method according to claim 5, characterized in that the leading edges of the pulses arriving at one or another valve coincide. 7. The control method according to claim 5, characterized in that the centers of the pulses arriving at one or another valve coincide.

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