RU2349926C1 - Digital active jammer - Google Patents

Abstract

FIELD: physics.

SUBSTANCE: active jammer applied for radioelectronic equipment (REE) comprises interconnected in a certain way receiving and transmitting antenna, designed as phased-array antenna with M radiators (M not less than two) and M send-receive channels, analysis and control block, jamming signal modulation calculating unit, reference frequency synthesizer. Besides, each channel includes: series emitter of receiving phased-array antenna, digital radio receiver, M digital memory units, amplitude-and-phase modulator, phase shifter, radio transmitter and emitter of transmitting phased-array antenna.

EFFECT: generation of adequate jamming signal used for REE rejection suppression at angular detection and tracking channels, generation of jamming for REE detection and tracking channels considering range, speed, bearing.

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Description

Application area

The invention relates to techniques for electronic suppression (REP) and can be used in radar and electronic reconnaissance (RTR), in devices designed to measure bearing.

Description of analogues

A digital storage device is known (Filippo Neri, Introduction to Electronic Defense Systems. Apteeh House, Inc. Boston, London, 1991. Translated by Filippo Neri, Introduction to Electronic Defense Systems, FSUE TsNIRTI, 2003, pp. 317-319), which contains step-up and step-up quadrature converters, two analog-to-digital (ADC) and digital-to-analog (DAC) converters, digital memory, local oscillator and clock. The step-down quadrature converter has a signal input, a local oscillator input and two outputs for a signal that coincides in phase (direct) with the input radio signal and a quadrature signal. The ADC and DAC of the direct signal have inputs of a synchronizing signal at one input and one output. The ADC and DAC of the quadrature signal have a signal input and an input of a synchronizing signal and one output of the converted input signal. Digital memory has inputs and outputs of direct and quadrature signals. The outputs of the step-down quadrature converter are connected to the inputs of the corresponding ADCs, the outputs of which are connected to the corresponding inputs of the digital memory. The outputs of the digital memory are connected to the inputs of the corresponding DACs, the outputs of which are connected to the corresponding inputs of the boosting quadrature converter. The inputs of the step-down and step-up quadrature converter are connected to the output of the local oscillator. The output of the clock generator is connected to the inputs of the synchronization signal of the ADC and DAC of the quadrature signal and the received signal, too.

The device operates as follows. The input of the step-down quadrature converter receives the radio signal to be converted. A step-down quadrature converter converts the input radio signal into two intermediate-frequency quadrature signals. The ADC quadrature signals are converted into digital signals, which are recorded in the memory of the storage device. To reproduce the radio signal, it is enough to extract two quadrature signals from the memory with the same clock frequency, duplicates of the stored signals. These signals at the output of the boosting quadrature converter allow you to generate a radio signal identical to the incoming radio signal, with some false components, caused by the choice of quantization.

The analogue works only as a signal repeater and is controlled by a computer, i.e. any transformations over a copy of the stored signal can be carried out only by a computer. And this leads to the impossibility of the formation of imitation interference in real time, due to a significant increase in the delay time from the moment the signal is recorded to the moment the noise is reproduced.

The closest technical solution is a system of electronic suppression (REP) digital radio frequency memory device (DRFM) (Fig. 1) (Perunov Yu.M., Fomichev K.I., Yudin L.M., Radio-electronic suppression of information channels of weapon control systems. - M .: Radio engineering, 2003). The structure of this device includes: a receiving and transmitting antenna, a radio receiver, a digital memory unit, an analysis and control unit, an amplitude-phase modulator, a unit for calculating the modulation parameters of interfering signals, and a radio transmitter.

The disadvantage of this device is the inability to interfere with electronic means (RES) in a given angular direction (such as "adaptive kotofot") and interfere with the angular channel for detecting and tracking RES with a monopulse method of direction finding (MIP) of electromagnetic radiation sources (EMP). To create such interference, including antipode type interference, an underlying surface (earth or a cloud of dipole reflectors) is required, and “negative interference” that adjusts the gain according to the inverse law of the amplitude of the received signal has limited efficiency [2].

The technical result of the invention

The technical result of the invention is the creation of an interfering signal for suppressing the radio electronic signal through the angular channel of detection and tracking by endowing the radio signal received from the radio electronic module with furry modulation and re-emitting the converted radio signal in any direction, including in the direction of the suppressed radio electronic signal — creating interference to the angular channel.

The invention is illustrated by drawings.

Figure 1 presents the block diagram of a digital device for creating active interference, in which the numbers of the twelfth font indicate the numbers of the blocks, and the numbers of the font 8 inputs and outputs of the individual blocks. In the text, the font numbers 8 are enclosed in parentheses.

Figure 2 shows the structural diagram of the PAR in cooperation with the suppressed radar station 12 (RES).

Figure 3 shows a diagram of the formation of a phase shift Δφ _i when the wave propagates from the i-th radiator PAR to i + 1 radiator.

Description of device design

The technical result of the invention is achieved due to the fact that the proposed digital device for creating active interference contains (Fig.1 and 2):

1 - receiving antenna - phased array antenna;

1.i - the i-th emitter of the receiving headlamp 1, i = 1, 2 ... M, M must be at least two;

2.i - i-th digital radio receiver (RPR);

3.i - i-th block of digital memory (BCP);

4 - analysis and control unit (BAU);

5 - synthesizer reference frequencies (MF);

6.i - i-th block of the amplitude-phase modulator (BAFM);

7 - block computing parameters of modulations of interfering signals (BPS);

8.i - i-th phase shifter;

9.i - i-th radio transmitter (RP);

10 - transmitting antenna - phased array antenna;

10.i - i-th transmitter emitting headlamp 10;

11.i - i-th transmit-receive channel;

12 - suppressed radar station (RES).

A digital device for creating active interference contains M identical transceiver channels (figure 1). Each i-th receiving-transmitting channel includes: emitter 1.i of the receiving headlight, digital radio 2.i (RPR), digital memory unit 3.i (BCP), analysis and control unit 4 (BAU), reference frequency synthesizer 5 (SOCH), the block of the amplitude-phase modulator 6.i (BAFM), the block for calculating the parameters of the modulation of the interference signals 7 (BPS), the phase shifter 8.i, the radio transmitter 9.i (RP), the emitter 10.i of the transmitting PAR. All devices and blocks in the channels are connected in series.

All M emitters of the receiving 1.i and transmitting 10.i HEADLIGHTS can be made, for example, in the form of horns, parabolic or helical antennas, have the same design, and are assembled in the receiving 1 and transmitting 10 flat HEADLIGHTS. When direction finding in the plane, all emitters are placed on one line, while the number of emitters must be at least two. When direction finding in three-dimensional space, at least one emitter must be located in space above or below the remaining emitters located on the same line (figure 2), while the number of emitters must be at least three. The electric axes of the emitters of the receiving 1 and transmitting 10 headlamps in space are parallel to each other and directed towards the suppressed RES.

The emitters are assembled either in the form of a linear phased antenna array and located along the horizontal X or vertical Y axes of the Cartesian coordinate system X, Y, Z associated with the horizon and the direction of their radiation Z, or in the form of a plane-equidistant phased array located in the X, Y plane ( figure 2). The electric axes of the HEADLIGHTS 1 and 10 relative to each other are linearly equidistant with a step d = kλ, where k≤1 / 2; λ is the minimum length of the operating range of radio wavelengths. The distances d between the electric axes of the adjacent HEADLIGHTER emitters are selected taking into account the requirements of electromagnetic compatibility (EMC) and the required isolation between them to exclude mutual influence along the side lobes of the radiation patterns of the HEADLIGHTS. Other configurations of the arrangement of the HEADLIGHT emitters in space are possible, while the HEADLIGHT diagrams and the algorithm for processing their signals will change.

All 2.i radios are digital and amplified by superheterodyne receivers and have one output (3) and three inputs: the first (1) for the radio signal, the second (2) for controlling the amplification of the intermediate frequency signal and the third (4) for the signals reference local oscillators SOCH 5.

All blocks of digital memory 3.i (BCP) have one output (3) and two inputs: the first (1) for a digitized radio signal and the second (2) for receiving a command signal for recording. Digital memory blocks are designed for storing digital copies of radio signals represented by the coordinate components Re (xi) and Im (xi).

Digital copies of radio signals, as material carriers of information about the coordinate position (along the bearing) and motion (Doppler frequency), undergo transformations that endow response - converted radio signals with appropriate interference modulations.

The analysis and control unit 4 has one input (2) and five outputs: the first (1) - for supplying a command signal to turn on the frequency conversion oscillators 5, the second (3) - for the gain control signal by radio receivers 2.i, the third (4) - to signal the command about the appointment of the type of interference modulation, and the fifth (5) - to signal the command for execution.

The reference frequency synthesizer 5 (MFB) has a control signal input (1) and, accordingly, two groups of outputs: the first (2) for radio receivers and the second (3) for radio transmitters and is made in the form of a reference frequency divider fo by a given division factor to form the required frequency ratings heterodyne signals for converting frequencies “to decrease” in RR 2.i and to “increase” in RP 9.i.

All amplitude-phase modulators 6.i (BAFM) have one output (3) and two inputs: the first (1) for the signal extracted from the 3.i BCP and the second (2) for the signal of the selected type of modulation.

The calculator of the parameters of the interference modulation signals 7 has one input (1) and two outputs: the first (3) for the signal of the modulating function in amplitude and phase (Doppler modulation) and range modulation and the second (2) for transmitting the signal of the modulating function in phase of the converted emitted radio signal (turning the front of its wave).

8.i phase shifters have one output (3) and two inputs: the first (1) for receiving a signal from a BAFM 6.i device and the second (2) for receiving a signal of a modulating function in amplitude and phase (Doppler modulation, modulation in amplitude, time delay).

9.i radio transmitters have one output (3) and three inputs: the first (1) for the converted radio signal, the second (2) for the signal of the formation of the radio signal and the third (4) for the signals of the local oscillators of frequency synthesizers 5.

The receiving headlight 1 has an air input for receiving radio signals RES and M outputs of the signals of the emitters 1.i.

The transmitting PAR 10 has an ether output and M inputs by the number of emitters 10.i

Description of electrical connections

The communications of the devices and units included in the transceiver channels 11.i are identical.

In each transceiver channel 11.i, the output of one emitter 1.i of the receiving headlight 1 is connected to the first (1) radio signal input of the radio receiver 2.i (Рпр), the second (2) control input of which is connected to the second output (3) of the control signal radio receiver of the analysis and control unit 4 (BAU), the third input (4) of the local oscillator signal of the radio receiver is connected to the first (2) output of the signal of the reference frequency synthesizer 5 (MFB) (Fig. 1).

The output (3) of the radio 2.i is connected to the input (1) of the radio signal of the digital memory unit 3.i (BCP) and the radio signal (2) of the analysis and control unit 4 (BAU). The input of the signal (2) control the BCP is connected to the output (6) of the control signal BAU 4.

The output (3) of the digital signal of the BPC 3.i is connected to the input (1) of the block of the amplitude-phase modulator 6.i (BAFM). The input (1) BAFM 6.i is connected to the output (3) of the block for calculating the modulation parameters of interfering signals 7 (BPS).

The output (3) BAFM 6.i of the signal, converted - endowed with interference of a digital signal, is connected to the input (1) of the phase shifter 8.i, the second input (2) of which is connected to the output (2) of the BPS control signal 7.

The output (3) of the phase shifter 8.i is connected to the input (1) of the converted radio signal of the radio transmitter 9.i. The input (2) of the radio transmitter 9.i is connected to the output (4) of the control signal BAU 4. The input (4) of the local oscillator of the radio transmitter 9.i. connected to the output (3) SOCH 5.

Output (3) of the 9.i radio transmitter connected to the input of the emitter 10.i transmitting HEADLIGHT 10.

Description of the device

The device operates as follows.

The radio signals from the RES through the M emitters of the receiving headlamp 1 arrive at the first (1) inputs of the 2.1-2.M radio receivers. Regardless of the law of intrapulse modulation of RES signals, the output of digital memory devices 3.1-3.M generates samples of RES signals whose phases correspond to samples of the spatial frequency signal Ωk = sinθ _m (2π / λ) of the k-th RES (Fig. 3).

The phase shift Δθi at point i + 1 with respect to the phase at point i with a uniform spatial quantization step d is constant and equal (for the direction Θ _{k of} the incident wave arrival) to Δθi = Δθ = Ωd = (2πd / λ) sinΘ _k .

Thus, external radio signals from several RES through the emitters 1.i of the receiving headlamp arrive at the inputs (1) of the radio receivers 2.i. In this case, regardless of the law of intrapulse modulation of the signal of the k-th RES, at the output of the digital receivers 2.i, signal samples are generated whose phases correspond to samples of the spatial frequency signal Ω _k = sinθ _k (2π / λ).

The spatial frequency Ωk is uniquely associated with the bearing θk of the k-th RES. For example, if we take two samples i and i + m, then formed respectively by receivers 2.i with numbers i and i + m will have a relative phase difference Δφ _{i, i + m} = kΩkd, which contains information about the bearing θ _k k-th RES

The combination of all phase differences Δφ _{i, i + m} , i = 1, 2 ... M, m> i allows us to clarify the estimate of Ω _k , and therefore to improve the accuracy of measuring the bearing θ _{k of the} k-th RES. In general, according to the set of M readings per root mean square error of bearing measurement, it is possible to reduce (RMS) √M times [4].

In each radio 2.i, filtering is carried out according to the usual (temporary) frequencies f, for example, using the N-point discrete Fourier transform (DFT) algorithm, as a result of which the sensitivity of the frequency resolution system of it can be increased N times [4] . These are ordinary spectral transformations.

The analysis and control unit 4 (BAU) for the second output (3) controls the necessary attenuation of the input signal in order to increase the input amplitude dynamic range Rpr 2.i in order to process the signals without limiting the amplitude (Fig. 1).

In radio receivers 2.i, analog-to-digital conversion is carried out using analog-to-digital converters (ADCs) included in digital radios, as well as output (3), these signals are fed to BAU 4, a spatial-temporal analysis of the signals is carried out, and the bearing г is measured Θ ₁ RES signals.

In radios, radio signals are divided into quadrature components. The signals of digital copies (CC) of the quadrature components of the radio signal from the output (3) of the radio receivers 2.i are recorded in the digital memory of the BTSP 3.i by the command of the BAU 4, received at the inputs 3.i from the fifth output (6). The signals from the outputs of the BTSP 3.i go to the inputs (1) BAFM 6.i, where they are endowed with the corresponding noise component of the amplitude-phase modulation according to Doppler features, amplitudes, delays and other parameters of the radio signal.

BAFM 6.i is controlled by BPS 7 at the output (3), the signals from which are fed to the control inputs of BAFM 6.i.

BAFM 6.i is intended for amplitude and phase modulation of signals in transceiver channels in order to introduce the required functional interference modulations in digital copies of radio signals.

First of all, such a need arises in connection with the organization of Doppler (high-speed) withdrawals in order to disrupt tracking, as well as to simulate false signal marks at the stage of detection and target designation.

The introduction of the Doppler frequency shift ΔFd into the radio signals x _i , i = 1, 2 ... M is carried out by the vector multiplication of the complex samples of the signal x _i by a factor

,

,

where Re (jΔFdt) = cos (ΔFdt), and Im (jΔFdt) = sin (ΔFdt).

The signal in the complex form x _i = a _i exp (jφ _i ), and in the Cartesian coordinate system in the form

,

,

where Re (jΔFdt) and Im (jΔFdt) are the real and imaginary quadrature components of the input signal x _i , we are talking about performing the product operation of formulas (1) and (2), which is carried out using the well-known trigonometric cosine and sine transforms of the sum ΔFdt and φ _i .

where y _i is the complex readout of the radio signal at the output of the BCM 3.i, which takes into account interference modulation of the type of velocity drift, the parameters of which are set by BPS 7 at the output (3). On the same circuit (bus) can be set to the program "consistent removal" in range and speed, as well as other types of modulation within the modulation capabilities of the amplitude a _i and phase φ _i signals BAFM 6.i.

In addition, the BAFM 6.i control algorithm may provide for the creation of simulation interference in which amplitude modulation and range delay are involved.

The parameters of the interference signals specified in BAFM 6.i are calculated by BPS 7, the input of which (1) is connected to the output (5) of BAU 4. At the command of BAU 4, which, in addition to performing spatio-temporal analysis of radio signals, reveals the degree of danger of each 1 of the 1st RES, carries out their ranking, determines the order of service, assigns an adequate interference effect for each of them, i.e. BPS 7 is made in the form of a signal processor.

Amplitude modulation of the output interfering signal can be carried out both at the “low” power level in BAFM 6.i, and at the “high” power level in 9.i radio transmitters at inputs (1), which is reflected by the connection of output (4) with input (2 ) 9.i radio transmitters, which is a bus.

In a special way, the proposed device solves the problem of creating interference to the angular channel, for which phase shifters 8.i are introduced into the interference generating device, which provide for each RES a “complex twist” of the interference vector y _i on the value of the frequency of the spatial-frequency bias ΔΩ1 = (2π / λ) sin (Δθi).

The technical effect of the invention is due to the introduction of phase shifters 8.i, which change the direction of re-emission of radio signals by a given angle (additive rotation) or distort the front of the re-emitted signal to form angular tracking errors in RES with single-pulse direction finders.

The rotation algorithm of the vector radiation by the angle Δθ _k implements operations (1) - (3) only for the spatial frequency Ω.

Taking into account the angular direction of each k-th RES in the formation of the “address” response is taken into account by performing the complex conjugation operation “*” on the sample yi, which allows you to “align” the phases φ _i and thereby send the response signal to where it came from, or, where necessary (by type, multi-beam lens “R-2R” [4], “adaptive catfot” or Van-Watt grating [5]).

The spatial frequency Ω is stored from a given direction by implementing the principle of “coordinated filtering” of signals by spatial frequencies (angular directions), which is ensured by converting the real and imaginary components in the BAFM 6.i and M 8.i passage blocks and BAU 4 and BPS 7 in the well-known “convolution” and “conjugation” relations [3, 7].

The reference frequency synthesizer 5, which is controlled by the BAU 4 through the input (6), performs the functions of the reference local oscillators when implementing the principle of multi-stage superheterodyne.

The passage of the signal and their conversion is carried out using conventional mixers in a standard way by filtering the "difference" or "total" frequencies.

The formation of quadrature components is carried out with the aim of performing the operation of vector multiplication of complex numbers to organize the drifts ΔFd in speed, or turning the angle of the radiation direction by a given angle ΔΘ _{1 of} the "adaptive catfot" mode, which is ensured by the use of "quadrature schemes". The rotation of the radiation vector of the interfering signal is carried out using phase shifters 8.i, which provide a phase rotation of the wave front of the converted radio signal by the value ΔФ _1i = ΔΩ _1i d, i = 1, 2 ... M, where d is the spatial step of the PAR 14 in the X coordinate (for azimuth) or Y (for elevation).

The implementation of the frequency conversion components in the 9.i radio transmitters is similar to the corresponding components of the 2.i radio receivers, with the exception of the filter settings (to “increase the frequency” for RP 9.i and “lower the frequency” for RPR 2.i).

The signals from the outputs of the RP 9.i are fed to the emitters 10.i of the transmitting PAR, which, taking into account the programmed phase relations, are emitted in the direction Θ ₁ of the 1st RES.

Features of the invention common to the prototype

Receiving and transmitting antennas, a radio receiver, a digital memory unit, an analysis and control unit, an amplitude-phase modulator, a unit for calculating the modulation parameters of interfering signals and a radio transmitter.

An example of a specific implementation of a digital device for creating active interference

The device is made according to the block diagram in figure 1, operates in the frequency range 2.5-4.5 GHz, and has the same receiving 1 and transmitting 10 HEADLIGHTS (figure 2). Each headlamp has two flat helical emitters (M = 2) in the form of flat helical antennas. The distance between the emitters is d = 0.707 of the average working wavelength, which ensures the working sector of the bearing angles Θ ₁ ± 45 °.

Radios 2.1 and 2.2 are made according to the scheme of a digital superheterodyne receiver with double conversion of the radio frequency in the range 1 ± 0.25 GHz. Radio receivers include typical elements: low-noise high-frequency (RF) input amplifiers, mixers, band-pass filters, intermediate-frequency amplifiers (IF), phase detectors that provide the necessary amplification, filtering, and lowering the frequency to IF, including the formation of quadrature components. Radio amplifiers are made with a logarithmic gain characteristic on ERA type microcircuits and QBA12 dividers [6].

The digital memory blocks 3.1 and 3.2 are made on standard memory microcircuits of the type of a trigger cell with write and read addressing upon request.

Channel devices BCP 3.i, BAFM 6.i and phase shifters 8.i are made on 1879 VMZ, BAU 4.i and BPS 7.i microcircuits and on a signal processor of the TMS-320 type [5]. BAU 4.i is made in the form of a signal processor.

The reference frequency synthesizer 5 is made quartz with frequency multipliers of quartz.

Amplitude-phase modulators 6.1 and 6.2. made according to the scheme of inertialess trigonometric signal converters proportional to sin (ω ± Δω) and cos (ω ± Δω), where ω is the intermediate frequency (1 GHz), Δω is the deviation of the intermediate frequency ± 0.25 GHz. In the manufacture of such converters were used multipliers, adders and subtractors on microcircuits [5, 6].

The calculator of the parameters of the BPS 7.i interference modulation is designed as a signal processor [5].

Phase shifters 8.i are made similarly to amplitude-phase modulators 6.1 and 6.2, but in this case for the frequency space Ω ± ΔΩ, ΔΩ = ± 6 GHz.

Radio transmitters 9.1 and 9.2 are designed as step-up quadrature converters with amplification and double conversion of the frequency “to increase” in quadrature channels [5, 6].

Testing a prototype device showed that the technical result of the invention has been achieved. The device generates an adequate (coherent-synchronous, consistent with the angular direction and Doppler frequency) interfering signal to suppress the radio electron path along the angular detection and tracking channel.

A prototype of the device interferes with the channels of detection and tracking of RES in range, speed, bearing (azimuth and elevation).

Information sources

1. Perunov Yu.M., Fomichev K.I. Yudin L.M. Radio-electronic suppression of information channels of weapon control systems. - M.: Radio Engineering, 2003.

2. Gorbunov Yu.N. DRFM-S digital spatial spatial storage technology and the prospects for its implementation in new generation avionics. Radio Engineering, 2003, No. 1.

3. Gorbunov Yu.N., Galashin M.E., Melnikov M.Yu. Evaluation of the possibilities of taking into account the angular directions of signal reception and emission using digital frequency memory technology (DRFM). Questions of Radio Electronics, 2004, issue 1. Systems and means of automated information processing of special equipment (SOIU).

4. Van Brunt L.V.B. Applied ECM. E.W. Engineering, USA. 1978, V 1.

5. Texas Instrument. Website on the Internet: www.tms.com.

6. Web site: www.hittitt, www.agilent.com.

7. Gorbunov Yu.N. Digital systems SDS. Tutorial. - Chelyabinsk Polytechnic Institute. 1985.

Claims (1)

A digital device for generating active interference, comprising a receiving and transmitting antenna, an analysis and control unit, a block for calculating modulation parameters of interfering signals, characterized in that M radio transmitters, M radio receivers, M digital memory units, M amplitude-phase modulators, M phase shifters are inserted , a reference frequency synthesizer having a control signal input and accordingly two groups of local oscillator signal outputs - the first for M radio receivers and the second for M radio transmitters, while the receiving and transmitting antennas The antennas are made in the form of flat linear phased antenna arrays with M emitters each, M radio receivers are made digital, the i-th emitter of the receiving phased antenna array, where i = 1, 2, ..., M, is connected to the first input of the i-th radio receiver, output the i-th radio receiver is connected to the corresponding input of the analysis and control unit for conducting spatio-temporal analysis from the outputs of the M radio receivers and measuring bearings of the signals of the radio-suppressed means, and is also connected to the first input of the i-th digital memory block, the output which is connected to the first input of the i-th amplitude-phase modulator, the output of which is connected to the first input of the i-th phase shifter, the output of which is connected to the first input of the i-th radio transmitter, the output of which is connected to the i-th emitter of the transmitting phased array antenna, in addition , the first output of the analysis and control unit is connected to the input of the control signal of the reference frequency synthesizer for issuing commands to turn on the frequency conversion local oscillators, the second output of the analysis and control unit is connected to the second inputs M of the radio Ik for controlling the amplification of intermediate frequency signals, the third output of the analysis and control unit is connected to the second inputs of the M radio transmitters to signal the formation of the radio signal and the designation of the type of interference modulation, the fourth output of the analysis and control unit is connected to the input of the unit for calculating the parameters of the modulation of interference signals for signal of the execution command, the fifth output of the analysis and control unit is connected to the input of the command signal to record the i-th block of digital memory, in addition, the first group and the outputs of the reference frequency synthesizer are connected to the third inputs of the M radio receivers, the second group of the outputs of the reference frequency synthesizer is connected to the third inputs of the M radio transmitters, the first output of the block for calculating the parameters of the modulation of interference signals, which is the signal output of the selected modulating function in amplitude and phase and range modulation in range with the second input of the i-th amplitude-phase modulator, the second output of the block for calculating the modulation parameters of interfering signals is connected to the second input of the i-th phase shifter To transmit a modulating function signal through the phase of the converted emitted radio signal.

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