RU2281520C1 - Method for correction of frequency characteristics in range of 2n discrete frequency values and device for its realization - Google Patents

Abstract

FIELD: radio communication and microwave engineering, applicable in designing of correctors of amplitude-frequency characteristics of receiving and transmitting communication channels at a preset quantity of fixed frequencies.

SUBSTANCE: the method consists in connection of permanent reactive elements between the matched element on the side of the input and the matched element on the side of the output. The common input of the divider for N frequency channels is connected to the matched element on the side of the input, and the common input of the adder for N frequency channels is connected to the matched element on the side of the output. Each channel of the adder is connected to the divider channel corresponding to one and the same frequency by means of a matching device. The input impedances of each m-th channel matching device are formed proceeding from the conditions of matching of the matched element on the side of the input at its m-th frequency with the input normalized impedances of each m-th matching device on the side of the divider. Mathematic formulas for calculation of these values are given in the claim. The device for correction of frequency characteristics in range of 2N discrete frequency values for matching, for example, of the signal source and antenna has matching devices in the form of an L-shaped connection of two two-terminal networks of reactive elements. The common input of the divider for N channels is connected to the signal source, and the common input of the adder for N channels is connected to the antenna. The divider and adder channels corresponding to one and the same adjacent pair of discrete frequency values are connected by channel matching devices. All the channel matching devices are made in the form of an L-shaped connection of two two-terminal networks. The formulas for calculation of conductance of these two-terminal networks are given in the claim. Each two-terminal network is made in the form of two series-connected parallel circuits.

EFFECT: expanded functional opportunities, with the matching at all 2N discrete frequencies remaining unchanged.

2 cl, 7 dwg

Description

The invention relates to radio communications and microwave technology and can be used in the design of correctors for amplitude-frequency characteristics (AFC) (matching devices) and controlled correctors for phase-frequency characteristics (PFC) of receiving and transmitting communication channels at a given number of fixed frequencies, as well as for forming phase-shifted signals.

It is known that for the transmission and reception of undistorted information, constant frequency response and linearity of the phase response are necessary (Beletsky AF Fundamentals of the theory of linear electrical circuits. M: Communication, 1967, p. 344-345). The constancy of the frequency response is provided by matching devices, and the linearity of the frequency response by phase circuits.

There is a method of sequentially matching impedances (frequency response correction method) (Designing radio transmitting devices using a computer / Ed. By OV Alekseev, M .: Radio and communications, 1987, p. 82-113), which consists in the fact that between the input side element and the output side matching element include constant reactive elements, select the number and values of elements of type L, C of the matching device from the condition of perfect matching of impedances at a fixed frequency and manually change the values of these elements in with frequency. The transmission coefficient modulus at this frequency is equal to one.

A device for implementing this method is known (Design of radio transmitting devices using computers / Edited by O.V. Alekseev, M .: Radio and communications, 1987, p. 82-113), consisting of a L-shaped connection of two reactants (inductive or capacitive elements) whose parameters (L, C) are selected from the matching condition at a fixed frequency. The principle of operation of the device is to replace the elements with other elements with other nominal parameters, ensuring coordination at a different fixed frequency.

The disadvantages of the method and device are the low switching speed (long time) associated with manual switching, and a narrow class of matched impedances due to the method of selecting the number and values of elements, as well as the inability to adjust the phase response and phase shift of the carrier signal.

There is a method of correcting phase-frequency characteristics (Beletsky AF Fundamentals of the theory of linear electrical circuits. M: Communication, 1967, s.563-564), consisting in the fact that between the signal source and the load (antenna) or between the antenna and the receiver in the communication channel includes a phase correction circuit having a phase dependence on frequency in a certain frequency band, the inverse of the corresponding characteristics of the communication channel. As a result, the total phase response is close to linear. Distortion of information is reduced.

A device for implementing this method is known (Beletsky AF Fundamentals of the theory of linear electric circuits. M .: Communication, 1967, p.549-554), made in the form of a phase circuit, in which the amplitude-frequency characteristic is constant, and the phase when the frequency changes increases from zero (ω = 2πf = 0) to π (ω = ∞) for the first-order loop and from zero to 2π for the second-order loop. In this case, you can always find some frequency band in which the phase response of the circuit is inverse to the phase response of the communication channel without correction.

The disadvantages of the method and device are the limited frequency band within which the correction of the phase response is implemented, and the conditions of use. The method and device are feasible only for the case when the resistance of the signal source and antenna are real and equal to each other. The third disadvantage is the lack of the ability to change the frequency response of the communication channel, which existed before the correction. Since the frequency response of the phase circuit is constant, the frequency response of the channel after switching on the circuit remains unchanged. This means that there is no possibility of matching arbitrary complex resistances (conductivities) of the signal source and load in a given frequency band and phase manipulation of the carrier signal.

A known method is that between the matched element on the input side and the matched element on the output side, they include constant reactive elements, select the number and values of elements of type L, C from the condition for matching impedances, one of which is purely active and does not depend on frequency, at a fixed frequency and automatically change the values of these elements if necessary, matching at any of the working frequencies of coordination (Design of radio transmitting devices / Ed. by V.V. Shahgildyan. - M .: Radio and communication s, 1984, p.90, 216-217).

A device for implementing this method is known (Design of radio transmitting devices / Edited by V.V. Shahgildyan. - M.: Radio and Communications, 1984, p.90, 216-217), consisting of N pin diodes connected in parallel to a matched impedance on the input side, with each diode connected to a matching device in the form of an L-shaped connection of two reactants, the parameters of which are selected from the matching conditions of the coordinated element on the input side and the matched element on the output side, to which all matching devices are connected in parallel, corresponding discrete frequency. The principle of operation of this device is that in each individual period of time only one of the N diodes is open, while matching occurs at one of the N discrete frequencies. The remaining N-1 diodes are closed and their corresponding channels are disabled. Consistent matching of coordinated impedances at N discrete frequencies is carried out by sequentially switching the diodes from a closed state to an open state.

Despite the automatic change of elements, this method and device for its implementation also has a low switching speed, because as variable elements, elements of type L, C are selected, which suggests the presence of an electromechanical or electrical relay in the circuit, and their switching time is fractions and units of seconds. When using high-speed switches (for example, on p-i-n-diodes), the switching time is significantly reduced. However, in this case (when using p-i-n-diodes), their number should be no less than the number N of frequencies, since it becomes necessary to connect the matching devices in series, which leads to a more complicated method. In addition, due to the insufficiently developed methodology for choosing the number and values of elements, the method allows you to coordinate impedances, one of which is purely active and does not depend on frequency, and there is also no possibility of correcting the phase response and phase manipulation of the carrier signal.

The closest in technical essence and the achieved result (prototype) is a method of sequentially matching impedances in the range of N discrete frequencies (method for correcting frequency characteristics) (Auth. No. 1778827 dated August 1, 1992, application for invention No. 4766552 dated December 4 1989), namely, that between the matched element on the input side and the matched element on the output side include constant reactive elements in an amount of 2N, between the third and fourth independent permanent reactive elements from of the matched element on the input side include a variable impedance element, while the input impedance of 2N independent constant reactive elements, the variable impedance element and the matched element on the output side is determined by linear-linear transformation of the input impedance of 2N-3 independent constant reactive elements, starting from 4- from the matched element on the input side of an independent reactive element, an element with variable impedance and the matched element on the input side, real and imaginary components of the input impedance of 2N-3 independent elements and coefficients of linear fractional transformation is determined from the conditions negotiated matching element on the input side and conformable member from the output member, adjusting the impedance of the variable impedance.

The closest in technical essence and the achieved result (prototype) is a device for implementing this method for the case of two discrete frequencies, consisting in the fact that a matching device in the form of a L-shaped connection of two two-terminal devices is connected to the coordinated impedance on the input side, and the two-terminal device included in the transverse circuit is a capacitor, and the two-terminal circuit included in the longitudinal circuit is a series oscillatory circuit, a pin diode is connected to the circuit, in parallel with to the declared impedance, an inductance is connected on the output side, a source of control two-level signals is connected in parallel with the diode (Aut. St. No. 1778827 of August 1, 1992, application for invention No. 4766552 of December 4, 1989). The principle of operation of this device consists in sequentially switching the impedance of the p-i-n-diode, as a result of which the conditions for matching the coordinated impedances at two discrete frequencies are sequentially provided.

The disadvantage of this method and device for its implementation is the need to switch the impedance of an element with a variable impedance and the lack of correction of the phase response. The switching speed of modern p-i-n-diodes is a few microseconds (see M.S. Gusyatiner, A. I. Gorbachev. Semiconductor microwave diodes. - M.: Radio and communication, 1983, p. 141-142). With the number of discrete frequencies equal to N, the period of time during which there is no matching at each frequency increases by N-1 times. There is also no manipulation of the phase of the carrier signal.

The technical result of the invention is the expansion of functionality by providing the correction of the phase response and phase manipulation of the carrier signal while maintaining constant in time matching at all 2N discrete frequencies in both states of the controlled element.

This result is achieved by the fact that in the method of correcting the frequency characteristics in the range of 2 N discrete frequencies, consisting in connecting between the matched element on the input side and the matched element on the output side of the constant reactive elements, to the matched element on the input side connect the common input of the divider to N frequency channels, an adder on N frequency channels is connected to the matched element on the output side, each adder channel is connected to the corresponding matching channel According to the channel of the divider corresponding to the same frequency, the input impedances of each channel matching device are formed from the matching conditions of the matching element on the input side at its mth frequency with the input normalized impedances of each mth matching device from the side of the divider:

m=1,2,...N,

m = 1,2, ... N,

conditions for matching the matched element on the output side at its mth frequency with the input impedances of each mth channel matching device on the adder side:

m=1,2,...N,

m = 1,2, ... N,

physical feasibility conditions

m≠n; m, n=1,2,...N,

m ≠ n; m, n = 1,2, ... N,

b _mn · b _{N + 1n} >0; b ' _mn b' _{N + 1n} > 0,

- действительные и

- мнимые составляющие импедансов согласуемого элемента со стороны входа, подключенного к N+1-му каналу делителя, и параллельно соединенных управляемого и согласуемого элементов в первом и втором состояниях со стороны выхода, подключенного к N+1-му каналу сумматора, в m-м канале на n-й частоте, причем структуру и параметры реактивных элементов канальных согласующих устройств определяют из условий обеспечения требуемых разностей фаз (φ_ml) коэффициентов передачи (S₂₁ ^(ml)) на 2N частотах:where a _mn , a ' _mn are real and b _mn , b' _mn are the imaginary components of the normalized input impedances of the channel matching devices included in the frequency channels from the divider and from the adder of the m-th channel at the n-th frequency;

- valid and

- imaginary components of the impedances of the matched element from the input side connected to the N + 1-th channel of the divider, and parallel connected controlled and matched elements from the output side connected to the N + 1-m channel of the adder, in the m-th channel at the nth frequency, and the structure and parameters of the reactive elements of the channel matching devices are determined from the conditions for ensuring the required phase differences (φ _ml ) transmission coefficients (S ₂₁ ^(ml) ) at 2N frequencies:

where l are frequency numbers two in each channel; S ₂₁ ^ml1 , S ₂₁ ^ml2 - transmission coefficients of the corrector of the frequency characteristics in two states of the controlled element; g _Ym1,2 , b _Ym1,2 - real and imaginary components of the complex conductivities of the controlled elements in each of the m-channels in two states; g ' _{N + 1 n} , ν' _{N + 1 n} are the real and imaginary components of the complex conductivities of the matched element on the output side at the nth frequency.

This result is achieved by the fact that in the device for the correction of frequency characteristics in the range of 2N discrete frequencies, made in the form of a signal connected to the source by a common input of the divider to N frequency channels, and to the antenna by the common input of the adder N frequency channels, connecting the divider and adder channels, corresponding to the same discrete frequency values, channel matching devices, made in the form of a L-shaped connection of two two-terminal devices (Fig. 1), the conductivity of which is selected from the conditions:

each two-terminal device is made in the form of two series-connected parallel circuits (figure 2). The values of the parameters of the elements of the two-terminal circuits are defined by the expressions:

where b _mνl is the conductivity of the l-th two-terminal network (l = 1, 2) in the m-th channel at the ν-th frequency (ν = 1, 2); ω ₁ = 2πf ₁ ω ₂ = 2πf ₂ ; f ₁ , f ₂ - given frequencies in the m-th channel;

Y ₀ = g _0mν + jb _0mν ; Y _n = g _nmm + jb _nmm ;

m=1,2,...N,

m = 1,2, ... N,

m=1,2,...N,

m = 1,2, ... N,

- действительные и

- мнимые составляющие нормированных входных импедансов канальных согласующих устройств, включаемых в частотные каналы со стороны делителя и со стороны сумматора m-го канала на ν-й частоте; a=_N+1ν,

- действительные и b_N+1ν,

- мнимые составляющие импедансов согласуемого элемента со стороны входа, подключенного к N+1-му каналу делителя, и параллельно соединенных согласуемого элемента и управляемого элемента в первом или втором состояниях со стороны выхода, подключенного к N+1-му каналу сумматора, на ν-й частоте; k, m, i - текущие номера каналов; n - текущий номер частоты; ν - номера частот по две в каждом канале, одна из которых соответствует n-й частоте; φ_mν - разность фаз коэффициентов передачи в двух состояниях управляемого элемента в m-м канале на ν-й частоте; значения параметров L₂, С₂ второго контура выбраны произвольно.

- valid and

- imaginary components of the normalized input impedances of the channel matching devices included in the frequency channels from the divider and from the adder of the m-th channel at the ν-th frequency; a = _{N + 1ν} ,

are real and b _{N + 1ν} ,

- the imaginary components of the impedances of the matched element on the input side connected to the N + 1th channel of the divider, and the paired matched element and the controlled element in the first or second states on the output side connected to the N + 1th channel of the adder, on ν- th frequency; k, m, i - current channel numbers; n is the current frequency number; ν - frequency numbers two in each channel, one of which corresponds to the nth frequency; φ _mν is the phase difference of the transmission coefficients in two states of the controlled element in the mth channel at the νth frequency; the values of the parameters L ₂ , C _{2 of the} second circuit are selected arbitrarily.

-образного соединения двух двухполюсников (фиг.6), проводимости которых выбраны из условий:The specified result is also achieved by the fact that in the previous device for the correction of frequency characteristics channel matching devices are made in the form

-shaped connection of two two-terminal networks (Fig.6), the conductivity of which is selected from the conditions:

, каждый двухполюсник выполнен в виде двух параллельно соединенных последовательных контуров (фиг.7). Значения параметров элементов двухполюсников схемы определены выражениями:Where

, each bipolar is made in the form of two parallel connected serial circuits (Fig.7). The values of the parameters of the elements of the two-terminal circuit are defined by the expressions:

the values of the parameters L ₂ , C _{2 of the} second circuit are chosen arbitrarily; ν = 1, 2 is the number of the two-terminal network.

Figure 1 shows the first embodiment of a structural diagram of a device for implementing the prototype method.

Figure 2 shows a second variant of the structural diagram of a device for implementing the prototype method (channel matching device).

Figure 3 shows a structural diagram of a device for implementing the proposed method for correcting frequency characteristics.

-образного соединения двух проводимостей.Figure 4 shows the first variant of the structural diagram of the channel matching device for implementing the proposed method in the form

-shaped connection of two conductivities.

Figure 5 shows the implementation of the two-terminal network of the first embodiment of the structural diagram of the channel matching device for implementing the proposed method.

-образного соединения двух проводимостей.Figure 6 shows a second variant of the structural diagram of the channel matching device for implementing the proposed method in the form

-shaped connection of two conductivities.

Figure 7 shows the implementation of the two-terminal network of the second variant of the structural diagram of the channel matching device for implementing the proposed method.

The structural diagram of a device for implementing the prototype method (Fig. 1) (a method of correcting frequency characteristics by sequentially matching impedances in a range of N discrete frequencies) is made in such a way that constant reactive components are included between the matched element on the input side 1 and the matched element on the output side 2 elements 3 in the amount of 2N, between the third and fourth independent constant reactive elements from the matched element from the input side include an element with variable impedance 4, while the input the impedance of 2N independent constant reactive elements, a variable impedance element and a matched element on the output side is determined by linear-linear transformation of the input impedance of 2N-3 independent constant reactive elements, starting from the 4th from the matched element on the input side of an independent reactive element, element with variable impedance and a matched element on the input side, the real and imaginary components of the input impedance of 2N-3 independent elements and linear fractional coefficients formation is determined from the conditions negotiated matching element on the input side and conformable member from the output member, adjusting the impedance of the variable impedance.

The device operates as follows.

When applying one level of control voltage or current of the control device 5, determined by the computing device 6, to the element with variable impedance 4, due to the special choice of parameters of the reactive elements 3, matched elements with arbitrary impedances from the input 1 and output 2 side are matched at the first frequency. When a second level of control action is applied to an element with variable impedance 4, the matched elements 1 and 2 with the same parameters of the reactive elements 3 will be matched at the second frequency and so on.

The structural diagram of a device for implementing the prototype method (FIG. 2) (a method for correcting frequency characteristics by sequentially matching impedances in a range of 2 discrete frequencies) is made in such a way that a matching device in the form of a L-shaped connection is connected to the matched impedance from the input side two two-terminal, moreover, the two-terminal included in the transverse circuit is a capacitor, and the two-terminal included in the longitudinal circuit is a sequential oscillatory circuit, to a p-i-n-diode is connected to the circuit, inductance is connected in parallel to the impedance to be matched from the output side, and a source of control two-level signals is connected in parallel to the diode. The principle of operation of this device consists in sequentially switching the impedance of the p-i-n-diode, as a result of which the conditions for matching the coordinated impedances at two discrete frequencies are sequentially provided.

-образного соединения двух реактивных двухполюсников и включенного в поперечную цепь с переменным импедансом 4 (управляемым элементом) (фиг.4). Каждый двухполюсник, входящий в схему канального согласующего устройства (фиг.4) выполнен в виде 2-х последовательно соединенных параллельных колебательных контуров (фиг.5), параметры которых выбраны из условий одновременного согласования каждого канала с источником сигнала и нагрузкой на своей частоте и развязки с другими каналами и обеспечения требуемой разности фаз коэффициентов передачи корректора (фиг.3) в двух состояниях управляемого элемента.The structural diagram of the device for implementing the proposed method (Fig. 3) consists of a matched element on the input side 1 (complex conductivity of the signal source), a matched element on the output side 2 (complex conductivity of the antenna or other load) connected to the matched element 1 by the common input of the divider 7 on N-channels connected to the matched element 2 by the common input of the adder 8 N-channels, and each channel of the divider is connected to the adder channel corresponding to the same frequency by N channel of connecting devices 9, 10 ... N + 8. Each channel matching device can be made either as

-shaped connection of two reactive two-pole and included in the transverse circuit with a variable impedance 4 (controlled element) (figure 4). Each two-terminal device included in the circuit of the channel matching device (Fig. 4) is made in the form of 2 series-connected parallel oscillatory circuits (Fig. 5), the parameters of which are selected from the conditions of simultaneous matching of each channel with the signal source and the load at its frequency and isolation with other channels and providing the required phase difference of the transmission coefficients of the corrector (Fig.3) in two states of the controlled element.

-образного соединения двух реактивных двухполюсников и включенного в поперечную цепь управляемого элемента (фиг.6). Каждый двухполюсник, входящий в схему канального согласующего устройства (фиг.6), выполнен в виде 2-х параллельно соединенных последовательных колебательных контуров (фиг.7), параметры которых выбраны из условий одновременного согласования каждого канала с источником сигнала и нагрузкой на своей частоте и развязки с другими каналами и обеспечения требуемой разности фаз коэффициентов передачи корректора (фиг.3) в двух состояниях управляемого элемента. В качестве управляемых элементов могут быть использованы выпускаемые промышленностью полупроводниковые диоды: варикапы, p-i-n диоды и т.д.Each channel matching device can also be made either as

-shaped connection of two reactive bipolar and included in the transverse circuit of the controlled element (Fig.6). Each two-terminal device included in the circuit of the channel matching device (Fig.6) is made in the form of 2 parallel-connected sequential oscillatory circuits (Fig.7), the parameters of which are selected from the conditions of simultaneous matching of each channel with the signal source and the load at its frequency and decoupling with other channels and providing the required phase difference of the transmission coefficients of the corrector (figure 3) in two states of the controlled element. As controlled elements, semiconductor diodes manufactured by the industry can be used: varicaps, pin diodes, etc.

The principle of operation of both devices implementing the proposed method for correcting the frequency characteristics is that, thanks to a special selection of parameters L, C of the oscillatory circuits in each channel at 2 specified frequencies, a given phase difference of the transmission coefficients in two states of the controlled element is maintained while maintaining at these frequencies harmonization of elements that are close to complete. At frequencies other than these preset frequencies, a phase difference close to the preset ones will be provided in each channel, as well as matching with some matching tolerance. In each channel, a pair of predetermined frequencies differs from a pair of frequencies of other channels. At the same time, each channel is decoupled from all other channels. Thus, the proposed method and both devices of its implementation provide N working frequency bands within which coordination and a given phase difference of the transmission coefficients in two states of the controlled element are maintained. It must be emphasized that coordination at 2N frequencies is provided continuously, regardless of the switching of a controlled element from one state to another. The change of states leads to a change in the phase of the transmission coefficient by a given value, but does not affect the value of its modules.

We show the possibility of fulfilling these conditions. We will divide the proof of these possibilities into three stages. At the first stage, for arbitrary conductivities (not yet known) of the signal source and load, which upon matching should be respectively equal to the input conductivities of the channel matching devices, respectively, from the input and output sides, we determine the conductivities of the two-terminal devices included in each channel matching device, and parameters of reactive elements of type L, C from which these two-terminal devices are formed. At the second stage, we determine the values of the input conductivities of all channel matching devices from the input side and from the output side at each frequency from the known conductivities of the matched elements from the input and output side. At the third stage, we sew the obtained solutions at the previous two stages.

To solve the problem in the first stage, we will develop an algorithm for synthesizing a passage-type phase manipulator connected between the complex conductivities of the signal source (Y ₀ = g ₀ + jb ₀ ) (input conductivity of the channel matching device from the input side) and the load (Y _n = g _n + jb _n ) (input conductivity of the channel matching device from the output side), by finding the optimal ratios between the elements of the transmission wave matrix and determining, based on these ratios, the uncontrollable parameter s filter.

Let the equivalent circuit of the phase manipulator be presented in the form of four cascade-connected four-terminal devices. The first four-terminal network characterizes a jump in the normalized conductivity Y ₀ to "1". The second four-terminal device is a phase manipulator filter formed only of reactive elements. The third four-terminal network is a parallel-connected controlled element with given complex conductivities Y ₁ = g ₁ + jb ₁ and Y ₂ = g ₂ + jb ₂ in two states determined by the levels of the control low-frequency effect (current or voltage). The fourth quadrupole is a jump in wave conductivity from "1" to Y _n . These four-terminal circuits are described by the corresponding wave transmission matrices:

where X = a / d, Y = b / d, Z = c / d; T ₁₁ = a + jb, T ₂₂ = a-jb, T ₁₂ = d + jc, T ₂₁ = d-jc - elements of the wave matrix T2.

It should be noted that the introduction of the quadripoles T1 and T4 is a necessary technique, the use of which ensures the normalization of the total wave transmission matrix obtained by multiplying the matrices (1):

Using the known relations between the elements of the wave matrix and the elements of the scattering matrix [6], we obtain the expression for the transmission coefficient from one input to another:

It is required to determine the minimum number of uncontrolled filter elements and the values of their parameters at which a change in the conductivity of the controlled element from Y ₁ to Y ₂ leads to a change in the phase of the transmission coefficient with the module constant according to the following law:

where φ is the given value of the phase difference of the transmission coefficients in the first and second states at a fixed frequency.

Substituting (3) into (4) and separating the real and imaginary parts from each other, we obtain a system of two equations equivalent to (4):

where A ₁ = cos (φ) · (b ₀ + b ₂ + b _H ) -sin (φ) · (g ₀ + g ₂ + g _H ) - (b ₀ + b ₁ + b _H );

B ₁ = cos (φ) · (b ₂ g ₀ + b ₀ g ₂ + b ₀ g _H + b _H g ₀ ) + sin (φ) · (b ₀ b ₂ -g ₀ g ₂ + b ₀ b _H -g ₀ g _H +1) - (b ₁ g ₀ + b ₀ g ₁ + b ₀ g _H + b _H g ₀ );

C ₁ = cos (φ) · (b ₂ g ₀ + b ₀ g ₂ + b ₀ g _H + b _H g ₀ ) + sin (φ) · (b ₀ b ₂ -g ₀ g ₂ + b ₀ b _H -g ₀ g _H -1) - (b ₁ g ₀ + b ₀ g ₁ + b ₀ g _H + b _H g ₀ );

D ₁ = cos (φ) · (b ₂ -b ₀ + b _H ) -sin (φ) · (g ₂ -g ₀ + g _H ) - (b ₁ -b ₀ + b _H );

A ₂ = cos (φ) · (g ₀ + g ₂ + g _H ) + sin (φ) · (b ₀ + b ₂ + b _H ) - (g ₀ + g ₁ + g _H );

B ₂ = cos (φ) · (g ₀ g ₂ -b ₀ b ₂ + g ₀ g _H -b ₀ b _H -1) + sin (φ) · (b ₂ g ₀ + b ₀ g ₂ + b ₀ g _H + b _H g ₀ ) + (b ₀ b ₁ -g ₀ g ₁ + b ₀ b _H -g ₀ g _H +1);

C ₂ = cos (φ) · (g ₀ g ₂ -b ₀ b ₂ + g ₀ g _H -b ₀ b _H +1) + sin (φ) · (b ₂ g ₀ + b ₀ g ₂ + b ₀ g _H + b _H g ₀ ) + (b ₀ b ₁ -g ₀ g ₁ + b ₀ b _H -g ₀ g _H -1);

D ₂ = cos (φ) · (g ₂ -g ₀ + g _H ) + sin (φ) · (b ₂ -b ₀ + b _H ) - (g ₁ -g ₀ + g _H ).

Solution (5) has the form:

Where

The resulting system of two relations between the elements of the transmission wave matrix (6) means that, to ensure phase manipulation of the transmitted signal with the required value φ, the filter must contain at least two independent independent elements, the parameters of which must be determined from the solution of the system of two equations formed from the indicated relations as follows . For the selected connection scheme of 2 elements, the wave transmission matrix is determined, which is reduced to the form T2 (1). The expressions obtained in this way for X, Y, Z, determined through specific parameters of the circuit, must be substituted into (6) and the resulting system of equations relative to two parameters must be solved. If there are M> 2 elements in the circuit, then M-2 elements should be assigned to the third four-terminal network and converted to the conductivity of the controlled part of the manipulator.

The parameters of the M-2 elements can be selected arbitrarily or based on any other physical conditions, for example, from conditions for ensuring the required phase differences of the transmission coefficients at a certain number of discrete frequencies, a frequency band, in N states of a controlled element at a single frequency, and so on.

In accordance with the described algorithm, the simplest circuits of the channel matching device, shown in Figures 4, 6, were synthesized. The optimal values of the parameters of the device shown in Figure 4 are determined by the following formulas:

,Where

,

and for the device depicted in Fig.6:

Where

To solve the problem in the second stage, we use the results of the work (Golovkov A.A., Kovalev S.V. Synthesis and analysis of quasi-dissipative mutual single-frequency and two-frequency adders and power dividers with controlled characteristics, part 1. Impedance and energy relations. Antennas, issue 2 (69), 2003, pp. 61-71 and Golovkov AA, Chaplygin AA Admittance and energy relations of quasi-dissipative reciprocal adders and power dividers. Telecommunications, No. 7, 2003, pp. 13-20) in which it is shown that, in order to ensure the agreement conditions, each After the channel with both matched elements, the following relationships must be fulfilled:

and in order to fulfill the conditions of physical realizability and the conditions of isolation between the channels, the implementation of the following relations is necessary:

b _mn · b _{N + 1n} >0; b ' _mn b' _{N + 1n} >0; m ≠ n; m, n = 1,2, ... N,

Expressions (9) - (11) for quasi-dissipative reciprocal adders and dividers into N channels must be compared with the solutions to the synthesis problem of channel matching devices for which the input impedances of channel matching devices from the input and output side obtained in (9) - (11), are the source for determining the parameters of bipolar and reactive elements L, C.

The results can be used to synthesize channel matching devices with a given phase φ _mn at a given number of frequencies and frequency in each channel. For example, for N = 2, it is necessary at both frequencies to use formulas (7), (8) for the circuits shown in Figs. 5, 7. Then, each bipolar should be formed from the elements L, C so that they provide at each frequency would be the calculated conductivity values.

In accordance with the described algorithm, two two-terminal circuits were synthesized (Figs. 5, 7). For two series-connected parallel circuits (figure 5):

For two parallel connected serial circuits (Fig.7):

where B _l1 , B _l2 - calculated according to formulas (7), (8), the values of reactive conductivities at the first and second frequencies for two-terminal channel matching device; l = 1, 2 is the number of the corresponding two-terminal network in figure 4, 6.

In principle, to realize the two required conductivity values at two frequencies, respectively, one circuit is sufficient. However, the presence in the circuits (Figs. 5, 7) of a second circuit with arbitrarily selected values of L ₂ , C ₂ allows, by varying them, to provide the required frequency response and phase response in the frequency band.

The positivity of the radical expressions in (7), (8) determines the areas of variation in the values of the load conductivity and the conductivity of the signal source at which the required phase values of the transmission coefficients are realized. Moreover, part of these values can be set parametrically. It is known (Smith F. Pie Charts in Radio Electronics / Translated from English by M.N. Berger, B.Yu. Kapilevich. - M.: Communication, 1976, p. 88-98) that the circuit shown in figure 4 , 6, complement each other in the areas of variation in the conductivity of the signal source and the load, within which the physical realizability of these circuits is ensured. This means that if one of these circuits does not physically realize the given phase difference of the transmission coefficients at given conductivities of the signal source and load, then the second circuit is necessarily physically feasible, and vice versa.

In the third stage, it is necessary to compare the results of the decisions obtained in the first and second stages. To do this, we give the expressions explaining the correspondence of the notation adopted at these stages:

Y _1.2 = g _1.2 + jb _1.2 = g _Ym1.2 + jb _Ym1.2 ; r ₀ = a _mn ; x ₀ = b _mn ;

- действительные и мнимые составляющие импедансов согласуемого элемента со стороны входа и параллельно соединенных согласуемого элемента и управляемого элемента в первом или втором состояниях со стороны выхода на n-й частоте в m-м канале; a_mn, а'_mn - действительные и b_mn, b'_mn - мнимые составляющие нормированных входных импедансов канальных согласующих устройств, включаемых в m-й канал, со стороны делителя и со стороны сумматора на n-й частоте.

- the real and imaginary components of the impedances of the matched element from the input side and parallel to the matched element and the controlled element in the first or second states from the output side at the nth frequency in the m-th channel; a _mn , a ' _mn are real and b _mn , b' _mn are the imaginary components of the normalized input impedances of the channel matching devices included in the m-th channel, from the divider and from the adder at the nth frequency.

Thus, the obtained results can be used for practical design of SFU with given phase differences of the transmitted signal. The new interconnections between the elements of the transmission wave matrix complement the well-known interconnections of the parameter matrices arising from the conditions of reciprocity, symmetry, antimetry and non-dissipativity of the four-terminal networks, and expand the possibilities of their synthesis.

The technical and economic efficiency of the method and devices for its implementation lies in the ability to provide the required phase differences of the transmission coefficients at a theoretically unlimited number of specified frequencies with transmission coefficient modules equal to unity. This means that the function of full coordination is preserved at a given number of frequencies, implemented by the prototype, and a new function arises to provide the required phase differences of the transmission coefficients. Together, the conditions for transmitting information without distortion, the formation of phase-shifted signals, matching at 2N frequencies, as well as providing a predetermined dependence of the phase on frequency and time, for example, the quadratic dependence necessary for the formation of the LFM signal, are provided.

The proposed technical solution - the method is new, since the method of correcting the frequency characteristics is not known from publicly available information, ensuring the equality of the transmission coefficient modules to the unity and the phase difference of the transmission coefficients in two states of the controlled elements to the required values at an arbitrarily specified number of frequencies, including connecting the divider to N channels with a common input to the coordinated element on the left and connection of the adder N channels with a common input to the coordinated element on the right, the connection is medium channel matching devices containing uncontrolled reactive elements and a controlled element, adder and divider channels corresponding to the same values of discrete frequencies, as well as a special selection of input impedances of matching devices on the left and right on each channel and each frequency and reactive parameters L, С .

-образного соединения двух двухполюсников, причем каждый двухполюсник сформирован из двух последовательно соединенных параллельных колебательных контуров, а все параметры согласующих устройств выбраны по специальным формулам, обеспечивающим согласование и заданные разности фаз коэффициентов передачи на 2N дискретных значениях частот в некоторой определенной области изменения проводимости нагрузки.The proposed device for implementing this method is new, because from publicly available information, a device consisting of a divider and adder N channels connected by common inputs to the elements to be matched to the left and right is unknown, and the divider and adder channels corresponding to the same frequency pair are interconnected by means of channel matching devices containing uncontrolled reactive elements and a controlled element, and channel matching devices are made in the form

-shaped connection of two two-terminal networks, each two-terminal network formed of two series-connected parallel oscillatory circuits, and all parameters of matching devices are selected according to special formulas that ensure matching and given phase differences of transmission coefficients at 2N discrete frequency values in a certain defined range of load conductivity changes.

-образного соединения двух двухполюсников, причем каждый двухполюсник, сформирован из двух параллельно соединенных последовательных колебательных контуров, а все параметры согласующих устройств выбраны по специальным формулам, обеспечивающим согласование и заданные разности фаз коэффициентов передачи на 2N дискретных значениях частот в некоторой определенной области изменения проводимости нагрузки.The proposed device for implementing this method is new, because from publicly available information, a device consisting of a divider and adder N channels connected by common inputs to the elements to be matched to the left and right is unknown, and the divider and adder channels corresponding to the same frequency pair are interconnected by means of channel matching devices containing uncontrolled reactive elements and a controlled element, and channel matching devices are made in the form

-shaped connection of two two-terminal networks, each two-terminal network formed from two parallel-connected sequential oscillatory circuits, and all parameters of matching devices are selected according to special formulas that ensure matching and given phase differences of the transmission coefficients at 2N discrete frequency values in a certain defined range of load conductivity changes.

The proposed technical solutions have an inventive step, since it does not explicitly follow from the published scientific data and the known technical solutions that the claimed sequence of operations is connecting the divider with a common input to a coordinated element on the left, connecting an adder with a common input to a coordinated element on the right, connecting all the channels of the divider and adder corresponding to the same frequency values, by N channel matching devices, the choice of input impedances of these devices in each channel At each frequency and according to special formulas, the choice of parameters of reactive elements - leads to full coordination and provision of the given phase differences of the transmission coefficients at 2N frequencies in two states of the controlled element, corresponding to two levels of control, which is necessary when building antennas, radio communications and multiplexers to transmit information without distortion, the formation of phase-shifted signals and predetermined phase dependencies in two states.

The proposed technical solution is industrially applicable, since known serial and parallel oscillatory circuits and transmission lines with parameters determined by the proposed mathematical expressions, and controlled elements in the form of semiconductor diodes: varicaps, p-i-n-diodes, etc. can be used for its implementation.

Claims (2)

1. A method of correcting frequency characteristics in the range of 2N discrete frequency values, comprising switching on between the matched element on the input side and the matched element on the output side of the constant reactive elements, characterized in that the common input of the divider to N frequency channels is connected to the matched element on the input side , the common input of the adder on N frequency channels is connected to the matched element on the output side, each channel of the adder is connected via a channel matching device to the corresponding With the channel of the divider sharing the same frequency, the input impedances of each m-th channel matching device are formed from the conditions of matching the matching element from the input side at its m-th frequency with the normalized input impedances of each m-th matching device from the side of the divider:

m = 1,2, ... N, conditions for matching the matched element on the output side at its mth frequency with the input impedances of each mth channel matching device on the adder side:

m = 1,2, ... N, and conditions of physical feasibility

b _mn · b _{N + 1n} >0; b ' _mn b' _{N + 1n} >0; m ≠ n; m, n = 1,2, ... N, where a _mn , a ' _mn and a _mm , a' _mm are real, b _mn , b ' _mn and b _mm , b' _mm are the imaginary components of the normalized input impedances of the channel matching devices included in the frequency channels, from the divider and side of the adder of the m-th channel at the n-th and m-th frequencies; a _{N + 1n} ;

- real and b _{N + 1n} ;

- imaginary components of the impedances of the matched element from the input side connected to the N + 1-th channel of the divider, and parallel to the matched element from the output side and the controlled element in the first and second states at the nth frequency, connected to the N + 1-th channel the adder, and the structure and parameters of the reactive elements of the channel matching devices are determined from the conditions for ensuring the required phase differences (φ _ml ) transmission coefficients (S ₂₁ ^(ml) ) at 2N frequencies: S ₂₁ ^ml1 = (cosφ _ml + jsinφ _ml ) S ₂₁ ^ml2 , l = 1,2 ... 2N, where l are frequency numbers two in each channel; S ₂₁ ^ml1 , S ₂₁ ^ml2 - transmission coefficients of the corrector of the frequency characteristics in two states of the controlled element; g _Ym1,2 , b _Ym1,2 - real and imaginary components of the complex conductivities of the controlled elements in each of the m-channels in two states; g ' _{N + 1n} , ν' _{N + 1n} are the real and imaginary components of the complex conductivities of the matched element on the output side at the nth frequency; k, m, i - current channel numbers; n is the current frequency number. 2. A device for correcting frequency characteristics in a range of 2N discrete frequency values for matching, for example, a signal source and an antenna, containing matching devices in the form of an L-shaped connection of two two-terminal reactive elements, characterized in that the common input of the divider is connected to the signal source by N channels, and to the antenna - the total input of the adder of N channels, and the divider and adder channels corresponding to the same adjacent pair of discrete frequency values are connected by channel matching devices, while all channel matching devices are made in the form of a L-shaped connection of two two-terminal devices, the conductivity of two-terminal devices is selected from the conditions:

each two-terminal network is made in the form of two series-connected parallel circuits, the values of the parameters of the elements of the first circuit are determined by the expressions:

where b _mνl is the conductivity of the l-th two-terminal network (l = 1, 2) in the m-th channel at the ν-th frequency (ν = 1, 2); ω ₁ = 2πf ₁ ; ω ₂ = 2πf ₂ ; f ₁ , f ₂ - given frequencies in the m-th channel;

m = 1, 2, ... N;

m = 1, 2, ... N;

b _mn · b _{N + 1n} >0; b ' _mn b' _{N + 1n} >0; m ≠ n; m, n = 1, 2, ... N, where a _mn , a ' _mn , a _mν , a' _mν and a _kν , a ' _kν are real and b _mn , b' _mn , b _mν , b ' _mν , b _kν , b ' _kν and b _iν , b' _iν are the imaginary components of the normalized input impedances of the channel matching devices included in the mth, kth and i-th channels, from the divider and from the adder to the nth and νth frequencies; a _{N + 1n} ,

a _{N + 1ν} ,

are real and b _{N + 1n} ,

b _{N + 1ν} ,

- imaginary components of the impedances of the matched element from the input side, for example, a signal source, and parallel connected matched element, for example, an antenna, and a controlled element in the first or second states from the output side at the nth and νth frequencies; g _0mν , b _0mν - real and imaginary components of the input conductivity of the channel matching device from the divider in the m-th channel of the ν-th frequency; g _нmν , b _нmν - real and imaginary components of the input conductivity of the channel matching device from the adder in the m-th channel at the ν-th frequency; g _Ym1 , g _Ym2 are real and b _Ym1 , b _Ym2 are imaginary components of the complex conductivities of the controlled elements in each of the m-channels in the first and second states, k, m, i are the current channel numbers; n is the current frequency number; ν - frequency numbers two in each channel, one of which corresponds to the nth frequency; φ _{m ν} is the phase difference of the transmission coefficients in two states of the controlled element in the mth channel at the νth frequency; the values of the parameters L ₂ , C _{2 of the} second circuit are selected arbitrarily.

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