RU1841316C - Hydroacoustic transmission path power supply system - Google Patents

Abstract

FIELD: hydroacoustic engineering.

SUBSTANCE: invention relates to the field of hydroacoustic engineering and electrical engineering and is intended for use as a power supply system for high-power devices in pulsed operation. The power supply device of the hydroacoustic transmission path contains a rectifier and a capacitive storage device connected in series, the input terminals of the rectifier through a thyristor key are connected to the terminals for connecting an alternating voltage source, a control pulse generator, the output of which is connected to the control input of the thyristor key. At the same time, a control circuit for the turn-on delay of the thyristor key is introduced, containing a zero organ, two prohibition circuits, two R-S counters, a trigger and a high-frequency pulse generator.

EFFECT: increased reliability in the pulse mode.

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Description

The present invention relates to the field of hydroacoustic engineering and electrical engineering and is intended for use as a power supply system for high power devices in a pulsed mode of operation.

Power supply systems are known, for example, those described in the book by Yu.S. Rusina "Power supply of hydroacoustic equipment", L .: Shipbuilding, 1986, containing a power transformer, the primary winding of which is connected to the AC voltage buses (220 V, 50 Hz) of the primary power supply, and the secondary winding through a rectifier and a capacitive storage device with hydroacoustic power supply buses transmitting path (GAPT). The disadvantage of the known devices are large dimensions and weight due to the use of a low-frequency transformer (the frequency of change of the voltage of the primary power supply is 50 Hz). In addition, the use of known devices in high-power GAPT (up to 2 ... 4 kW during signal emission) with a duty cycle of more than 20 ... 50 leads to a deterioration in the energy characteristics of the equipment due to the flow through the primary winding of the idle current transformer ) in the pause between messages.

These shortcomings limit the scope of such devices in autonomous hydroacoustic systems with limited energy resources and stringent requirements for heat dissipation of the transmitting equipment.

Known power supply systems, for example, described in US Pat. US No. 4217632, 4251857, containing the first rectifier, the inputs of which are connected to the primary power supply buses, and the outputs - through the first capacitive storage to the power supply buses of a push-pull transistor amplifier, the inputs of which are connected to the pulse shaper, and the outputs through a pulse transformer, the second rectifier and the second capacitive drive - with power supply buses GAPT. In such devices, the transistor amplifier operates at a high switching frequency (about 5 ... 20 kHz), which can significantly reduce the size of the output pulse transformer. However, the use of known solutions is associated with a greater complexity of the power supply system (the presence of two rectifiers and two capacitive storage), a decrease in efficiency and reliability. In particular, the use of transistors to control the flow of energy from the primary power supply requires a complex scheme for the formation and pre-amplification of the pulsed voltage. In a push-pull terminal stage, through currents can flow transistor-transistor, which is also associated with a decrease in the reliability of the device. The use of transistors to form a pulsed voltage in the primary winding of the transformer limits the output power of the power supply system, which, as a rule, does not exceed 0.5 ... 1 kW. Thus, low reliability limits the use of transistor converters in the GAPT power supply system with an output power of up to 2…4 kW during sending.

Closest to the proposed power supply system is the system described in US Pat. W080/01023 MKI H03F 3/21, H02M 5/44 (international patent).

The prototype device (Fig. 1) contains a power transformer 2, the primary winding of which is connected through the thyristor key 1 to the primary power buses, and the secondary winding through the rectifier 3 and capacitive storage 4 is connected to the power supply buses of the transmission path 5, and the control input of the thyristor key 1 connected to the output of the phase-shifting circuit 6, the input of which is connected to the corresponding primary power bus, and the control input is connected to the reference voltage bus U _ET.

. Величина Δϕ определяется уровнем эталонного напряжения U_ЭТ, поступающего на вход управления фазосдвигающей цепи 6, чем обеспечивается требуемый уровень выходного напряжения системы электропитанияThe prototype device works as follows. The phase-shifting circuit 6 ensures the inclusion of the thyristor key 1, made on two back-to-back thyristors (Fig. 1), at times t _k with a phase shift relative to zero-crossings of the primary power supply voltage

. The value of Δϕ is determined by the level of the reference voltage U _ET supplied to the control input of the phase-shifting circuit 6, which ensures the required level of the output voltage of the power supply system

where K _T is the transformation ratio of the power transformer 2,

E _M - the amplitude of the voltage of the primary electrical network (E ₀ ≈310 V).

(при Δϕ=0). При этом вольт-секундная площадь напряжения, поступающего в первичную обмотку трансформатора 2, в два раза меньше вольт-секундной площади полуволны первичной электросети. Указанное обстоятельство позволяет в устройстве-прототипе использовать силовой трансформатор 2 с меньшей индуктивностью первичной обмотки и тем самым уменьшить габарит силового трансформатора 2. Наличие тиристорного ключа 1 позволяет использовать устройство-прототип в качестве системы электропитания передающего тракта в импульсном режиме работы. Обеспечив выключение тиристорного ключа 1 в паузе между посылками, можно устранить потери, вызванные протеканием тока холостого хода и повысить эксплуатационный КПД системы.Starting from the moment t _k , the thyristor key 1 is open, which ensures the connection to the primary winding of the transformer 2 of the primary voltage and, accordingly, the charge of the capacitive storage to U _out (1). When the voltage of the primary power grid passes through zero, the thyristor key turns off. As a rule, for a large output power, the phase shift is chosen from the condition

(for Δϕ=0). In this case, the volt-second area of the voltage supplied to the primary winding of the transformer 2 is two times less than the volt-second area of the half-wave of the primary power grid. This circumstance allows the prototype device to use a power transformer 2 with a lower inductance of the primary winding and thereby reduce the size of the power transformer 2. The presence of a thyristor key 1 allows the use of the prototype device as a power supply system for the transmission path in a pulsed mode of operation. By ensuring that the thyristor switch 1 is turned off in a pause between bursts, it is possible to eliminate the losses caused by the flow of no-load current and increase the operational efficiency of the system.

However, the prototype device compares favorably with known devices (US Pat. US No. 4217632, No. 4251857), using transistor key elements. The use of a thyristor key in the prototype makes it possible to control the flow of energy at a high power level (up to 2...4 kW) with a relatively simple device circuit.

The main disadvantage of the prototype device is the large amplitude of the currents when the device is turned on, the value of which can be more than 5...10 times the amplitude of the rated operating current. The noted drawback is due to the connection of a voltage of a given value through a thyristor key 1, a transformer 2 and a rectifier 3 to a capacitive storage, the voltage of which at the initial moment of switching on is zero. This circumstance, especially in the pulsed mode of operation of the transmission path 5, leads to periodic operation of the prototype device in the current overload mode, which is associated with a significant decrease in the reliability of the prototype device and limits its use for powering the HAPT of a high power level.

The aim of the present invention is to improve the reliability in the pulsed mode of operation. This goal is achieved in a known device containing a power transformer, the primary winding of which is connected through a thyristor key to the primary power buses, and the secondary winding through a rectifier and a capacitive storage device is connected to the power supply buses of the transmitting path, by introducing into its composition a controlled delay circuit, a reference oscillator, an accumulator, a limiter, a differentiating device and an additional transformer, the primary winding of which is connected to the primary power supply buses, and the secondary winding, through a limiter and a differentiating device connected in series, is connected to the synchronization input of the accumulator and to the input of a controlled delay circuit, the synchronization input of which is connected to the output of the reference oscillator, the output is connected to the control input of the thyristor switch, and the bit control inputs are connected to the bit outputs of the accumulator, the installation input of which is connected to the control signal bus.

The introduction of new blocks and connections in the composition of the known device made it possible in the proposed power supply system to ensure the charge of the capacitive storage in the direct current mode, thereby reducing the switching current, the value of which exceeds the value of the rated operating current by more than 20 ... 30%. Thus, in the proposed device, current overloads are eliminated in the pulsed mode of operation, thereby increasing the reliability of its operation. The set of newly introduced blocks and links was not previously used in devices of this class, therefore, the proposed device has new features, the use of which leads to a positive effect.

In FIG. 1 and FIG. 2 shows block diagrams of the prototype device and the proposed device, and Fig. 3 illustrates voltage diagrams that explain the operation of the inventive power supply system.

The proposed device (Fig. 2) contains a thyristor key 1, a transformer 2, a rectifier 3, a capacitive storage 4, the outputs of which are connected to the power supply buses of the transmitting path 5, an additional transformer 6, a limiter 7, a differentiating device 8, a controlled delay circuit 10, a storage 9 and reference oscillator 11.

Functional diagrams of the differentiating device 8, the accumulator 9 and the controlled delay circuit 10 are shown in FIG. 4. Thyristor key 1 is designed to control the flow of energy from the primary power network through transformer 2 and rectifier 3 to capacitive storage 4. Thyristor key 1 connects the primary winding of transformer 2 to the primary power supply voltage U _n from the moment t _k of thyristor key 1 control input pulse voltage U ₁₀ (t _u ≈20...50 μs) from the output of the controlled delay circuit (Fig. 3). Turning off the thyristor key 1 occurs when the primary power supply voltage passes through zero. Thyristor key 1 is performed on two back-to-back thyristors, the control electrodes of which are connected to galvanically isolated outputs of the delay circuit 10.

Power transformer 2 is used to transform the voltage of the primary power supply, supplied to its primary winding through the thyristor key 1, into a voltage of a given value, which through the rectifier 3 enters the capacitive storage 4. Transformer 2 is performed at the required output power from the sieve of the volt-second area of the half-wave of the primary voltage U _n .

The additional transformer 6 serves to provide the voltage of the secondary power supply to the driving part of the system and is performed at a power level of about 10...20 W, and, therefore, leads to an increase in the dimensions of the device by no more than 5...10%. The secondary winding of the transformer 6, connected to the inputs of the limiter 7, is used to highlight the zero crossings of the primary power supply voltage.

The limiter 7 serves to convert the voltage supplied to its inputs into a pulse signal U ₇ of the meander type, the front and slope of which is determined by the moments of zero crossing of the voltage U _n . The limiter 7 can be made on the amplifier-limiter with a sufficiently large gain (more than 10).

The differentiating device 8 is designed to generate short pulses U ₈ whose time position coincides with the rise and fall of the pulse voltage U ₇ generated by the limiter 7. The differentiating device 8 can be made, for example, in accordance with the functional diagram shown in FIG. 4, where short pulses corresponding to the rise and fall of the input voltage are fed to the input through a logical adder made on the "OR" circuit (8.3). Accumulator 9 is used to form a linearly increasing binary code S ₉ (Fig. 3) supplied to the bit inputs of the delay circuit 10. Accumulator 9 (Fig. 4) is performed on an n-bit binary counter 9.2, the installation input "R" of which is connected to control signal bus, and the synchronization input is connected to the output of the "AND" circuit (9.1), the inputs of which are connected to the output of the differentiating device 8 and the output of the high-order bit of the binary counter. The capacity n of a binary counter is determined from the condition:

where T _about - the period of the output pulse voltage of the reference generator 11,

T _p - the period of the primary voltage of the power supply (T _p ≈20 ms).

после предшествующего перехода через ноль

первичного напряжения электропитания. Длительность интервала τ₃ определяется величиной S₉ двоичного кода, поступающего с разрядных выходов накопителя 9, который определяет коэффициент деления счетчика 10.1:The fulfillment of condition (2) is necessary for the normal operation of the controlled delay circuit 10, the bit inputs of which are connected to the bit outputs of the drive. The controlled delay circuit 10 is performed on a controlled n-bit binary counter 10.1, an "RS" trigger 10.2, an "AND" circuit 10.3, a single vibrator 10.4 and a single-cycle preamplifier 10.5 with a transformer output, the secondary windings of which are connected to the control inputs of the thyristors that are part of the thyristor key 1. The delay circuit 10 is designed to generate pulses U ₁₀ (Fig. 3) turn on (t _k ) thyristors with a duration t _u =20...50 μs, determined by a single vibrator 10.4, through a time interval

after previous zero crossing

primary supply voltage. The duration of the interval τ ₃ is determined by the value S _{9 of} the binary code coming from the bit outputs of the drive 9, which determines the division ratio of the counter 10.1:

The value S ₉ of the output binary code of the drive 9 varies by zero-crossing of the primary voltage of the power supply from the maximum value

to the minimum value:

Accordingly, the duration of the delay τ also varies within:

τ _max =S _max ⋅T _o ; τ _min \u003d S _min ⋅T _o

or taking into account (2):

Moreover, in the absence of a control signal (U _y =0 Fig. 4), the counter 9.2 of the drive 9 is reset, which corresponds to the maximum value of the binary code on its inverse outputs S ₉ =S _max and, therefore, the maximum delay τ ₃ =T _p /2- T _o . When a control signal arrives (U _y =1, Fig. 4) with each half-wave of the primary voltage U _n supply, the value of S ₉ discretely (by one) decreases, which corresponds to a decrease in the delay time by the value

Reducing the code S ₉ to the minimum value (5) leads to zeroing the output of the most significant bit 2 ⁿ of the code, which prohibits the passage of pulses U ₈ through the "AND" circuit 9.1 to the synchronization input of the counter 9.2 and provides a constant value of the code S ₉ =S _min and the delay time τ ₃ \u003d τ _min . The described algorithm of operation of the drive 9 and the controlled delay circuit 10 makes it possible to charge the capacitive storage 4 without significant current overloads.

The proposed power supply system works as follows. The load of the device is the transmission path, which corresponds to a pulsed change in power consumption. The main modes of operation of the hydroacoustic complex are characterized by high power consumption (2 ... 4 kW) during the sending, the duration of which reaches 10 ... 20 s, with a duty cycle of more than 20 ... 50. During the pause between bursts, the control signal is absent (U _y =0), the drive 9 is reset, which corresponds to the maximum delay (6) of turning on the thyristor switch 1. In this case, a voltage is applied to the primary winding of the transformer 2, the amplitude of which does not exceed:

where Ω=2π⋅50 rad/s,

τ ₃ \u003d τ _max .

In particular, for the bit depth of the binary code n=4, taking into account (6) and (2)

where

Accordingly, the volt-second voltage area in the primary winding of the transformer 2 does not exceed 1% of a quarter of the half-wave of the primary voltage U _n , which makes it possible to practically eliminate losses in the transformer 2 during the pause between messages.

When a control signal (U _y =1) is received, the pulses U ₈ from the output of the differentiating device 8 to the synchronization input of the drive 9 lead to a decrease in its output code, which corresponds to a decrease in the delay time. For each transition through zero of the primary voltage of the power supply, the code value decreases by 1 and, therefore, the voltage amplitude on the primary winding of the transformer U ₁ increases with each half-wave by ΔU:

Moreover, the value of ΔU, for example, for a 4-bit system, does not exceed 10% of the amplitude E _M of the voltage U _P of the primary power grid.

The noted circumstance makes it possible to significantly reduce the amplitude of the current i ₄ (Fig. 3) of the charge of the capacitive storage 4. In particular, with the permissible amplitude of the output voltage ripples of the storage 4 in the operating mode up to 5%, the amplitude of the charge current exceeds the amplitude of the rated current by no more than 20 ... thirty%. In this case, the charge of the capacitive storage is carried out for no more than 8 periods of the primary voltage of the power supply.

For a smaller amplitude of output voltage ripples U ₄ , which is ensured by an increase in the capacitance of the capacitive storage 4, equalization of the amplitudes of the charging and operating current can be achieved by increasing the capacity of the storage 9 and the controlled delay circuit 10. For example, with voltage ripples up to 1%, the capacity of the system should be provided on the order of n=6, and the charge time in this case does not exceed 32 periods of the primary supply voltage. Thus, the proposed device provides for the elimination of losses in the pauses between messages and the condition for the smooth charging of the capacitive storage 4. These advantages distinguish the claimed technical solution from the known solutions and the prototype device. In particular, when ensuring that the primary power supply is turned off during the pause between bursts, the periodic charge of the capacitive storage before the start of the working cycle in the prototype device is associated with connecting the maximum voltage to the primary winding of the transformer, which leads to current overloads, in which the magnitude of the charging current is more than 5…10 times the rated current. Such current overloads do not allow switching off the primary power grid during the pause between transmissions, which is associated with an increase in losses and a decrease in the operational efficiency of the prototype device to 50 ... 70%.

In the proposed device, the noted shortcomings are eliminated. The introduction of a set of new blocks and links into the composition of the known device made it possible to significantly improve the energy characteristics and increase the reliability of the proposed device and thereby ensure its efficient use for power supply of the HA transmission paths in the pulsed mode of operation.

So, if a known device with an output power during sending up to 4 kW and a duty cycle of more than 20 has an operational efficiency of less than 60% at current overloads of more than 5 times the rated current, then the proposed device under the same conditions has an operational efficiency of up to 90% at exceeding the charging current by no more than 20 ... 30% of the rated current in the operating mode.

A prototype was made at the enterprise and experimental tests of the proposed device were carried out, the results of which confirmed its advantages in comparison with known technical solutions.

The proposed technical solution can significantly improve the energy performance of the power supply equipment of the GA transmission paths, eliminate current overloads caused by the pulse mode of its operation, and can be effectively used in hydroacoustic systems of high and medium power levels.

Claims (1)

The power supply device of the hydroacoustic transmission path, containing a rectifier and a capacitive storage connected in series, the input terminals of the rectifier through a thyristor key are connected to the terminals for connecting an alternating voltage source, a control pulse shaper, the output of which is connected to the control input of the thyristor key, characterized in that, in order to increase reliability in the pulsed mode, a thyristor key turn-on delay control circuit has been introduced, containing a null organ, two inhibition circuits, two counters R-S trigger and a high-frequency pulse generator, while the input of the null organ is connected to the terminals for connecting an AC voltage source, and its output through the first prohibition circuit is connected to the synchronization input of the first counter, the output of the most significant digit of which is connected to another input of the first prohibition circuit, and its setting input is connected to the outputs for connecting the start signal, the outputs of the first counter are connected to the information inputs the second counter, the synchronization input of which is connected to the output of the second prohibition circuit, one input of which is connected to the output of the high-frequency pulse generator, and the other input to the output of the R-S flip-flop, connected by the S input to the output of the null organ, and R by the input to the output of the second counter and the input of the control pulse shaper.

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