NO121681B - - Google Patents
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- Publication number
- NO121681B NO121681B NO139970A NO139970A NO121681B NO 121681 B NO121681 B NO 121681B NO 139970 A NO139970 A NO 139970A NO 139970 A NO139970 A NO 139970A NO 121681 B NO121681 B NO 121681B
- Authority
- NO
- Norway
- Prior art keywords
- transistor
- transformer
- oscillator
- secondary winding
- base
- Prior art date
Links
- 239000003990 capacitor Substances 0.000 claims description 15
- 238000004804 winding Methods 0.000 claims description 11
- 230000000903 blocking effect Effects 0.000 claims description 8
- 229920006395 saturated elastomer Polymers 0.000 claims description 4
- 230000003247 decreasing effect Effects 0.000 claims description 3
- 238000010586 diagram Methods 0.000 description 4
- 230000010355 oscillation Effects 0.000 description 4
- 230000008878 coupling Effects 0.000 description 2
- 238000010168 coupling process Methods 0.000 description 2
- 238000005859 coupling reaction Methods 0.000 description 2
- 230000004913 activation Effects 0.000 description 1
- 238000004146 energy storage Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 230000001172 regenerating effect Effects 0.000 description 1
- 230000005417 remagnetization Effects 0.000 description 1
- 230000007306 turnover Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3385—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement with automatic control of output voltage or current
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Description
Likespenningsomformer i særdeleshet for ladning av kondensatorer. DC voltage converter in particular for charging capacitors.
ladning av kondensatorer, omfattende en transistoroscillator med en transformator hos hvilken det til en sekundærvikling over en likeretter som er vendt på slik måte at strom flyter i en i oscillatoren inngående transistors sperretid, er koblet en kondensator som skal opplades, hvorved en annen sekundærvikling inngår i en tilbakekoblingskrets som er koblet til transistorens base. charging of capacitors, comprising a transistor oscillator with a transformer in which a capacitor to be charged is connected to a secondary winding above a rectifier which is reversed in such a way that current flows during the blocking time of a transistor included in the oscillator, whereby another secondary winding is included in a feedback circuit which is connected to the base of the transistor.
Ved en likespenningsomformer av nevnte type skjer energiover-føringen fra transformatoren til kondensatoren hurtigere jo hoyere kondensatorspenningen er, hvilket innebårer at kondensatorens oppladningstid er kortest mulig. Virkningsgraden i en slik selvsvingende kobling er imidlertid lav eftersom primærstrommen av-brytes av at transformatorkjernen mettes, hvorved induktansen i primærviklingen synker kraftig og strommen vokser hurtig til en hoy verdi innen primærstrommen gjennom den minskende tilbake-koblingen brytes. In the case of a direct voltage converter of the aforementioned type, the energy transfer from the transformer to the capacitor occurs faster the higher the capacitor voltage is, which means that the capacitor's charging time is as short as possible. The efficiency in such a self-oscillating coupling is, however, low because the primary current is interrupted by the transformer core being saturated, whereby the inductance in the primary winding drops sharply and the current rapidly increases to a high value before the primary current through the decreasing feedback circuit is broken.
I en likespenningsomformer av nevnte type vil transistoren i oscillatoren ikke sperre for transformatoren er mettet, hvilket medfbrer ommagnetiseringstap. In a direct voltage converter of the aforementioned type, the transistor in the oscillator will not block because the transformer is saturated, which entails remagnetization losses.
%Den lave virkningsgraden kan forbedres ved at styrepulsenes lengde tilpasses slik at kjernen ikke mettes. Anordningen gjores folgelig ikke selvsvingende. Repetisjonsfrekvensen for styre-pulsene må i dette tilfelle være så lav at transformatorkretsen rekker å omsette sin energi til kondensatoren også i begynnelsen av oppladningsforlopet, dvs. når kondensatorens spenning ennå er. lav og omsetningstiden lengre enn når kondensatoren er oppladet. Den totale oppladningstiden blir således lengre hos en slik oscillator enn hos en selvsvingende oscillator, slik at samtidig som virkningsgraden forbedres, forlenges oppladningstiden. %The low efficiency can be improved by adapting the length of the control pulses so that the core does not saturate. The device is therefore not made self-oscillating. The repetition frequency for the control pulses must in this case be so low that the transformer circuit manages to transfer its energy to the capacitor also at the beginning of the charging process, i.e. when the capacitor's voltage is still there. low and the turnover time longer than when the capacitor is charged. The total charging time is thus longer with such an oscillator than with a self-oscillating oscillator, so that while the efficiency is improved, the charging time is extended.
Formålet med oppfinnelsen er å eliminere ulempene hos disse to kjente anordninger og å tilveiebringe en kobling som har god virkningsgrad samt arbeider med en kortere oppladningstid. The purpose of the invention is to eliminate the disadvantages of these two known devices and to provide a coupling which has a good degree of efficiency and works with a shorter charging time.
Anordningen ifolge oppfinnelsen kjennetegnes slik det fremgår av patentkravets karakteriserende del. The device according to the invention is characterized as it appears from the characterizing part of the patent claim.
Oppfinnelsen skal nærmere beskrives nedenfor ved hjelp av et ut-fbrelseseksempel under henvisning til tegningen der The invention will be described in more detail below with the help of an exemplary embodiment with reference to the drawing therein
fig. 1 viser et koblingsskjema over en anordning ifolge oppfinnelsen, og fig. 1 shows a connection diagram of a device according to the invention, and
fig. 2 viser den i oscillatoren inngående transistorens kollektor-emitter-spenning som en funksjon av tiden. fig. 2 shows the collector-emitter voltage of the transistor included in the oscillator as a function of time.
I fig. 1 betegner T en transformator og V en transistor, hvilke inngår i en oscillator. Transistoren V er over transformatorens primærvikling T. koblet til en spenningskilde E. En forste sekundær vikl ing TJ, hos transformatoren er koblet over en diode D til en kondensator C som skal opplades. Oscillatorens tilbakekoblingskrets dannes av en forbindelse mellom transistorens V base og en andre sekundær vikl ing TJJ hos transformatoren. I denne tilbakekoblingskrets er det ifolge oppfinnelsen innkoblet en monostabil vippekrets MV. Med A betegnes en vilkårlig start-anordning, f.eks. en monostabil vippekrets som ved sin aktivering mater en puls til transistorens base for å starte svingningsforlopet. Svingningsforlopet skiller seg imidlertid fra svingningsforlopet hos en vanlig likespenningsomformer som arbeider som en regenerativ forsterker eller blocking-oscillator ved at mens transistoren hos en vanlig oscillator sperres når transformatorkjernen er mettet og transistoren aktiveres igjen efter transformatorens utladning, styres transistorens sperring i dette tilfelle ved hjelp av den monostabile vippekretsen MV. In fig. 1 denotes T a transformer and V a transistor, which are part of an oscillator. The transistor V is connected above the transformer's primary winding T to a voltage source E. A first secondary winding TJ of the transformer is connected via a diode D to a capacitor C which is to be charged. The oscillator's feedback circuit is formed by a connection between the transistor's V base and a second secondary winding TJJ of the transformer. In this feedback circuit, according to the invention, a monostable flip-flop circuit MV is connected. A denotes an arbitrary starting device, e.g. a monostable flip-flop circuit which, on its activation, feeds a pulse to the base of the transistor to start the oscillation cycle. However, the oscillation sequence differs from the oscillation sequence of a normal DC voltage converter that works as a regenerative amplifier or blocking oscillator in that, while the transistor of a normal oscillator is blocked when the transformer core is saturated and the transistor is activated again after the transformer discharges, the transistor's blocking in this case is controlled using the monostable flip-flop circuit MV.
Når transistoren V går over fra ledende til sperrende tilstand, forefinnes energi lagret i transformatoren T. Denne energi overfores til kondensatoren C via dioden D, og når diodestrommen har avtatt til null, sperrer dioden. Transformatoren inneholder nå ikke noe energi, og spenningen over transformatorens andre sekundærvikling TJJ er minsket til null. Hittil skiller funksjonen seg ikke fra en konvensjonell likespenningsomformers. Ved at den monostabile vippen er innkoblet i oscillatorens tilbakekoblingskrets, vil imidlertid transistorens tilbakeføring til ledende tilstand i dette tilfelle skje ved hjelp av den monostabile vippekretsens medvirkning. Den monostabile vippekretsen er innstilt på slik måte at den aktiveres når spenningen i trans-formatorviklingen T'^ har sunket til en bestemt verdi, f.eks. null. Ved aktivering av den monostabile vippekretsen åpnes transistoren V slik at svingningsforlopet kan påbegynnes, og holdes åpen i så lang tid som transistorens base mottar et signal fra vippen MV. Lengden av dette åpningssignal fra vippekretsen MV er valgt på slik måte at transistoren holdes ledende i en kortere tid enn den tid som skulle være nodvendig for å sperre transistoren ved metning av transformatoren, slik at transforma-tortapene unngås. Når således strommen opphorer på grunn av transistorens sperring, overfores den i transformatoren lagrede energi til kondensatoren C. When the transistor V goes from conducting to blocking state, energy is stored in the transformer T. This energy is transferred to the capacitor C via the diode D, and when the diode current has decreased to zero, the diode blocks. The transformer now contains no energy, and the voltage across the transformer's second secondary winding TJJ is reduced to zero. So far, the function does not differ from that of a conventional DC voltage converter. As the monostable flip-flop is connected in the oscillator's feedback circuit, however, the transistor's return to the conducting state will in this case take place with the aid of the monostable flip-flop circuit's involvement. The monostable flip-flop circuit is set in such a way that it is activated when the voltage in the transformer winding T'^ has dropped to a certain value, e.g. zero. When the monostable flip-flop circuit is activated, the transistor V is opened so that the oscillation sequence can begin, and is kept open for as long as the base of the transistor receives a signal from the flip-flop MV. The length of this opening signal from the flip-flop circuit MV is chosen in such a way that the transistor is kept conducting for a shorter time than the time that would be necessary to block the transistor when the transformer saturates, so that the transformer losses are avoided. Thus, when the current ceases due to the blocking of the transistor, the energy stored in the transformer is transferred to the capacitor C.
1 fig. 2 som er et diagram over transistorens V kollektor-emitter-spenning som funksjon av tiden, betegner t sden tid ilopet av hvilken den monostabile vippekretsen MV avgir åpningssignal til transistoren V. Med t betegnes den tid ilopet av hvilken transistoren V er sperret og som ifolge eksemplet tilsvarer transformatorens utladningstid ilopet av hvilken energi overfores til -kondensatoren C. Spenningen E i diagrammet er oscillatorens matningsspenning, og spenningstidsflåtene A og B som er et mål på energiinnholdet i transformatoren, må være like store under lagring av energi i transformatoren T som under overfbring av energi. I diagrammet er også med strekede linjer antydet den tidsperiode t' efter hvilken transistoren skulle sperres hvis.. 1 fig. 2 which is a diagram of the collector-emitter voltage of the transistor V as a function of time, t denotes the time ilope during which the monostable flip-flop circuit MV emits an opening signal to the transistor V. By t is denoted the time ilope during which the transistor V is blocked and which the example corresponds to the transformer's discharge time during which energy is transferred to the -capacitor C. The voltage E in the diagram is the oscillator's supply voltage, and the voltage time floats A and B, which are a measure of the energy content in the transformer, must be as large during energy storage in the transformer T as during transfer of energy. In the diagram, dashed lines also indicate the time period t' after which the transistor should be blocked if..
det var transformatorens metning som bestemte sperringen. Tids-periodene t er like i begge tilfelle. it was the transformer's saturation that determined the blocking. The time periods t are the same in both cases.
Claims (1)
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
SE527769A SE330209B (en) | 1969-04-15 | 1969-04-15 |
Publications (1)
Publication Number | Publication Date |
---|---|
NO121681B true NO121681B (en) | 1971-03-29 |
Family
ID=20266123
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
NO139970A NO121681B (en) | 1969-04-15 | 1970-04-14 |
Country Status (10)
Country | Link |
---|---|
JP (1) | JPS498576B1 (en) |
AT (1) | AT300125B (en) |
CH (1) | CH521050A (en) |
DE (1) | DE2016002C3 (en) |
DK (1) | DK122048B (en) |
FR (1) | FR2041174B1 (en) |
GB (1) | GB1298520A (en) |
NL (1) | NL163387C (en) |
NO (1) | NO121681B (en) |
SE (1) | SE330209B (en) |
Family Cites Families (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
NL104941C (en) * | 1957-02-26 |
-
1969
- 1969-04-15 SE SE527769A patent/SE330209B/xx unknown
-
1970
- 1970-03-31 DE DE19702016002 patent/DE2016002C3/en not_active Expired
- 1970-04-01 NL NL7004619A patent/NL163387C/en not_active IP Right Cessation
- 1970-04-07 AT AT317770A patent/AT300125B/en not_active IP Right Cessation
- 1970-04-09 JP JP2981570A patent/JPS498576B1/ja active Pending
- 1970-04-09 DK DK178470A patent/DK122048B/en not_active IP Right Cessation
- 1970-04-10 GB GB1728070A patent/GB1298520A/en not_active Expired
- 1970-04-13 CH CH543070A patent/CH521050A/en not_active IP Right Cessation
- 1970-04-14 NO NO139970A patent/NO121681B/no unknown
- 1970-04-14 FR FR7013480A patent/FR2041174B1/fr not_active Expired
Also Published As
Publication number | Publication date |
---|---|
GB1298520A (en) | 1972-12-06 |
DE2016002A1 (en) | 1971-01-07 |
JPS498576B1 (en) | 1974-02-27 |
FR2041174B1 (en) | 1974-05-03 |
NL7004619A (en) | 1970-10-19 |
DE2016002C3 (en) | 1975-05-22 |
AT300125B (en) | 1972-07-10 |
FR2041174A1 (en) | 1971-01-29 |
DE2016002B2 (en) | 1973-04-26 |
NL163387C (en) | 1980-08-15 |
CH521050A (en) | 1972-03-31 |
NL163387B (en) | 1980-03-17 |
SE330209B (en) | 1970-11-09 |
DK122048B (en) | 1972-01-10 |
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