DEVICE FOR THE INDUCTIVE TRANSMISSION OF THE ELECTRICAL ENERGY The invention relates to a device for the inductive transmission of electric power, in accordance with the main concept of claim 1. A device of this type serves to transmit electrical energy to a mobile consumer without mechanical or electrical contact. It includes a primary part and a secondary part, which similarly to the transformer principle are electromagnetically connected. The primary part consists of an electronic power supply and a driver. One or several sockets and the corresponding electronic attachment devices make up the secondary part. Unlike a transformer where the primary part and the secondary part are connected as closely as possible, in this case it is a loose connection system. This can be achieved through a relatively high operating frequency of the order of kilohertz. In this way, relatively large air spaces of up to a few centimeters can be bypassed. In this way the operating frequency of the secondary side is established as the resonance frequency of a parallel oscillating circuit, which is formed through the parallel connection of a capacitor with the pick-up coil. Among the advantages of this type of power transmission, we can mention in particular the absence of welding and maintenance, as well as contact safety and greater availability. Typical uses are automatic material transport systems in assembly stations, as well as systems for transporting people such as electric buses and elevators. A tap-side connection principle is described in WO 92/17929 and is shown in simplified form in Figure 1. The pick-up inductor Ll and the capacitor Cl connected in parallel to form an oscillating circuit is connected downstream to a rectifier 1, which is connected to a switch regulator of known type consisting of an inductor L2, a diode DI, a capacitor C2 and an electronic switch S as well as a regulator 2. The regulator 2 has essentially a voltage reference and a comparator that closes the electronic switch S through the control conductor 3 when the voltage on the capacitor C2 exceeds a first predetermined value and opens said electronic regulator S when the voltage is below a second value slightly lower than the first value so that the voltage UL on capacitor C2 and load 4 connected to it in parallel through terminals A and B assumes a value close to a predetermined value ado. In the case of load 4, it is typically an electric motor. In the case of numerous uses, in addition to the main load 4, in the form of an electric motor, an electronic control must also be supplied, so that the voltage levels required are very different. While a typical voltage value to power a motor is approximately 560 V, the voltages in the field of the electronic control are lower by more than one order of magnitude, for example are 24 V. A possible solution to provide a second voltage very low output is the connection of a direct voltage transformer in terminals A and B in parallel to the main load 4. However, the direct voltage transformers of which we are talking here with transformation reasons for example 560 V at 24 V are expensive and this increases the price of the installation. Another solution is proposed in DE 100 14 954 A1, which forms the basis of the main concept of claim 1. To achieve a much lower direct voltage, a second secondary winding is connected to the second rectifier at the outlet. Although it is not mentioned in the document of which we are speaking, the second rectifier to stabilize the voltage must also be connected to a second regulator, so it effectively doubles the electronic add-ons at the lowest voltage level. The need to use a second secondary winding in the socket therefore limits the design freedom of the socket construction. From US Pat. No. 6,005,435 a high voltage generator for the production of a high voltage of the order of kilovolts for the anode of a cathode ray tube is known, wherein a parallel member of RC is formed on the side of the outlet for divide the output voltage as a size with the necessary high flank slope through the series connection of two parallel RC distributors. In this way there are fewer requirements regarding the resistance to the voltage of the capacitors used and also a more compact construction of the connection is obtained. DE 38 32 442 A1 teaches a power supply device for a passenger train car, where the alternating current taken from the rail is regulated and transformed through a reducing converter at a direct voltage of 600 V. Starting from from this, two identical three-phase current inverters and an LC filter connected downstream are obtained, three sinusoidal alternating currents of 380 V. In this case, the reduction converter has two GTO thyristors connected in series that are connected both on the input side as on the output side through two equal capacitors connected in series whose junction points are in turn connected to each other. This connection configuration of the reduction converter serves to double its resistance to the input voltage. From this state of the art, the object of the present invention is to present the simplest possible form of such a device only with a limited intervention in the socket, providing the secondary side with at least a second output voltage. This object is achieved through a device according to the features of claim 1. Useful embodiments of the present invention are derived from the dependent claims. An essential advantage of the present invention relates to the fact that only a few additional construction elements are required and no major modifications to the topology of the connection are required to obtain an additional output voltage. The intervention in the socket itself is minimal, since it is limited to a socket on the secondary winding. Likewise, the degree of effectiveness of the transmission of energy is not significantly affected by the modification of the electronic fittings. The necessary division according to the present invention of the capacitors connected in series has the positive side effect of the application of a lower voltage in each individual capacitor, which means a lower requirement in terms of the resistance to the voltage of the capacitors. used. A further advantage of the present invention is that it allows the use of a direct current transformer ^ with an input voltage value less than 300 V to power the electronic control. These direct voltage transformers are used in large quantities in devices driven by the mains current and therefore are obtained at an economical price. An economical and especially preferred compact solution is the realization of the device according to the present invention together with a converter for controlling a motor in a common unit, whereby the concept of said mode can be used in common devices of this type. Next, examples of embodiments of the present invention will be described with reference to the drawings, in which Figure 1 shows a circuit diagram of an electronic take-off device in accordance with the state of the art, Figure 2 shows a diagram of circuit of an electronic take-off fitting in accordance with the present invention with a second output voltage, Figure 3 shows a connection of an electronic take-off fitting according to the present invention with a load in the form of a motor controlled by a converter. The embodiment illustrated in Figure 2 of the present invention is for the purpose of providing a second output voltage UL2 which is about half of the voltage UL necessary for the main load 4, which is supplied as before to the electronic take-off fitting in a value without change of for example 560 V between terminals A and B. For this purpose, the intake inductor Ll is divided into two equal inductors Lll and L12 connected in series between them, whose sum corresponds to the inductor Ll. This division of the inductor Ll is performed through a mean derivation C of the winding without other modifications to the winding or to the core. Similarly the capacitors Cl and C2, each connected in series, are also divided between two capacitors Cll and C12 or C21 and C22, respectively, of equal size, so that the partial capacitors must present in a known manner each double value of the global capacitor. The connection point of the capacitors Cll and C12 is connected to the mean derivation C of the tap winding, that is, to the point of union of the inductors Lll and L12, that is, these two connection points form a point of connection C. In relation to the behavior of the oscillating tap circuit with respect to its external connections with rectifier 1, nothing has been modified. The four diodes Dll to D14 connected downstream in the tapped oscillating circuit in FIG. 2 form in a manner known per se the rectifier 1 shown only schematically in FIG. 1. This part of the connection has no modifications. Likewise the DI diode remains unchanged, as well as the electronic switch S and the regulator 2, which takes the voltage UL on the load 4 through the terminals A and B and this voltage UL maintains a predetermined constant value through the drive of the switch S on the conductor 3. The regulator 2 is no longer illustrated in Figure 2 for reasons of simplification. As additional elements, two resistors R21 and R22 of high relative ohmic power, of the same size, are introduced in parallel with the capacitors C21 and C22. In addition, the middle derivation C is connected to the combined tap inductor Lll and L12 through a diode D2 with the connection point D of the capacitors C21 and C22 as well as with the resistors R21 and R22, so the diode is connected in such a way that only a current flow from C to D, that is to say, from the oscillation circuit to the RC members on the output side, is allowed. The partial voltage! ½ through the parallel connection of C22 and R22 is approximately to the partial voltage UL2 over the parallel connection of C21 and R21 and thus is equivalent to half of the UL output voltage directed to the main load 4 and is fed to the input of a direct voltage transformer 5, thereby obtaining an output voltage Us. The additional output terminal for this connection of the transformer 5 is shown in Figure 2 with the letter E. Typical values for the voltages mentioned are ULi = UL2 = 280 V and Us = 24 V. The operating mode of the breaker is released first of the decrease to half of the UL general output voltage through a division of the original output capacitor C2 into two capacitors C21 and C22 of the same size connected in series between them. However, in order to obtain a low voltage Us additional to UL, it is not possible to connect a direct voltage transformer with a corresponding lower nominal direct voltage on capacitors C21 or C22 since the asymmetry of the load caused by this reason would cause the interruption of the current on the capacitor in question. In order to avoid this problem, the present invention also contemplates the division of the intake inductor Ll and the intake capacitor connected in parallel Cl correspondingly in the partial inductors Lll and L12 or Cll and C12, respectively, and the connection of the splices C, in which the partial oscillating circuits created in this way are connected to the connection splices D of both output capacitors. Through this measure, it is possible to avoid the interruption of the current in capacitor C22 contemplated for the additional CD / DC transformer provided in the previous case for partial voltage tap, but is nevertheless provided in the closed state of the switch S for the direct voltage a short circuit through C22 in the path over the partial inductor L12, the rectifier diode D13, the inductor L2 and the switch S. The object of the additional diode D2 is to prevent the discharge of capacitor C22 through this path of short circuit. With the measures described above, the switch works satisfactorily, that is to say, a voltage that is half the voltage between terminals A and B and fed to a CD / CD transformer can be controlled through C22. 5. However, when for some reason the main load 4 is separated from the electronic take-off fitting, the constancy of the voltage OL2 can no longer be ensured since in this case the only ohmic load that remains in parallel with C22 is closed, while that the regulator 2, as shown in Figure 1, contemplates the complete voltage UL = ULi + UL2-In order to obtain a partial voltage OL2 stable also in the case of a division of the main load 4, the two are connected resistors R21 and R22 of the same size also in parallel with capacitors C21 and C22, so that the existence of an ohmic load between terminals A and B is always ensured. This load is not symmetrical overall or that the magnitude of the asymmetry depends in the first instance on the importance of the power taken from terminals F and G of the CD / CD 5 transformer. This means that the power that can be taken from these terminals, especially in the case of motor electronic attachment of tap without connected main load 4, is limited. As already mentioned, the additional voltage Us is only necessary to drive an electronic control which, in comparison with the main load 4, only requires a low power. The additional resistors R21 and R22 can have a relatively high ohmic dimension, that is, of the order of 10 to 100 kQ. Although the modalities described above have a symmetrical division of the oscillating tap circuit and the RC side of the output side, it is also possible to select an asymmetric division, in order to obtain an additional voltage tap which is greater or less than half of the output voltage UL. A subdivision could also be contemplated in more than two voltages in the case in which additional voltages were necessary. Said modification or extension is within the scope of knowledge of a person skilled in the art based on the examples described above and are within the scope of the present invention. A specific connection technique of the electronic tap attachment described above with the main load 4 in the form of an asynchronous motor 6, controlled by a three-phase converter 7 is shown in Figure 3. The electronic tap attachment in Figure 3 is represented as the block 8 containing all the components of the connection shown in Figure 2 to the tap inductor L11 + L12, the direct voltage transformer 7, and the main load 4. The configuration shown in Figure 3 with a controlled motor 6 per converter 7 is a classic type of main load 4 that is contemplated for connection to terminals A and B of an electronic jack 8 in accordance with the present invention. In this case the problem arises that, in the case of the activation of the motor 6 as well as in the case of braking, the power can flow through the converter 7 back in the direction of the electronic attachment 8., in the case of an electronic take-off device in accordance with the state of the art, as shown in Figure 1, would cause a voltage rise in the output capacitor 2, which would cause the regulator 2 to close the switch S so the intake side would not contribute to an additional lift of the UL output voltage. The rise in tension would not be problematic insofar as the regulator 2 can handle it. In the case of a connection in accordance with the present invention, as shown in Figure 2, however, no such elevation of the output voltage UL = ULi + UL2 can be allowed in the case of the motor drive 6 , since this would destroy the stability of the input voltage UL2 of the direct voltage transformer 5. A significant increase in the output voltage could cause a corresponding overshoot of the partial voltage UL2 and damage to the input of the direct voltage transformer 5. For this reason, as shown in Figure 3, the intermediate connection has an additional diode D3 between the output terminal A of the electronic socket 8 and the converter 7 as well as a parallel connection of an additional capacitor, which consists of two capacitors C31 and C32 connected in series, in parallel with the input of the converter 7, A rise in voltage at the input of the converter 7 as a result of the fr In this case, the motor 6 only carries a discharge of the capacitors C31 and C32, while a reverse current is prevented by the diode D3 towards the outlet of the electronic input 8, which would increase the voltage there with the discharge of the capacitors. capacitors on the output side C21 and C22. The capacitors C31 and C32 are necessary to absorb the energy that returns from the converter 7, so the division of the capacitor into two capacitors connected in series is not forced, but it is convenient for the realization with capacitors of lower resistance to the voltage . It is particularly advantageous if the electronic socket 8, the converter 7 and the elements connected to each other, in the example of FIG. 3, diode 3 and capacitors C31 and C32 are integrated. This means at least that they are together in a rack. They can advantageously be placed on a common sheet. In this way a more compact and economical solution can be achieved than in the case of the state of the art where the electronic control 8 and the converter 8 are separate units each with a frame, which are connected to each other through a cable and plug, and therefore the present invention allows to save space, weight and component parts. This is valid not only in the case in which the electronic socket 8 allows the derivation of a second output voltage, but also in the case of the combination of a conventional electronic socket, in accordance with what is illustrated in FIG. Figure 1, equipped with a converter 7 contemplated to control an engine. The combination of the mentioned system components in a single common unit provides a saving of space, weight and cost, as compared to the formation of separate individual units. A special advantage is provided in the case of an electronic socket 8 according to Figure 2 with two output voltages to the extent that the necessary additional elements D3, C31 and C32 can be integrated in this case for the disconnection of the electronic attachment of socket 8 of the converter 7 in the case of a reverse current without greater cost in terms of the common structure.