MXPA01005371A

MXPA01005371A - Method and software for user interface device in "last mile" telecommunications cabling.

Info

Publication number: MXPA01005371A
Application number: MXPA01005371A
Authority: MX
Inventors: John A Taylor
Original assignee: Khamsin Technologies Llc
Priority date: 1998-11-30
Filing date: 1999-11-30
Publication date: 2002-03-14
Also published as: WO2000033494A1; IL143357A0; CA2352895A1; AU2034700A; EP1135879A1; ID30068A; HK1041128A1; JP2002531998A; KR20010112222A; CN1346556A; BR9916150A

Abstract

A communications system is provided which includes a regional ring with a plurality of local nodes (51), each node including at least one fiber interface device (53) and at least one Local Node interface device (59) for connection to a global electrical and fiber network. The Local Node interface device (59) connects to a user interface device (65) through a cable (67). The Local Node (51), the Local Node interface device (59) and the user interface device (65) may each accept and process signals transmitted from a wireless network.

Description

METHOD AND SOFTWARE FOR USER INTERFACE DEVICE IN TELECOMMUNICATIONS WIRING OF THE "LAST MILE" • Technical Field The invention relates to telecommunications cabling, and more particularly to the cabling used for the so-called "last mile" connection of users with external networks. The invention relates especially to improvements in the • software to route information within these networks. Background v Compendium of the Invention An examination of the existing inherited landline communications networks 5, in light of the communications technology solution, leads to some interesting perspectives. On the one hand, the newer long-range communications and information infrastructures that are currently being built are based on fiber optic and coding technologies that are capable of immense capacity. On the other hand, the local entrance of the "last mile" for the end user, is usually still the legacy copper line installed decades ago for telephone service. Because the legacy copper lines were designed for operation that did not contemplate the fiber optic capabilities of today, end users of the copper line can not use the high bit rates that long-haul infrastructure can provide. modern reach. The user is limited by their local connection with the service provider. Seeing the architectures of the communications systems that are currently being sought by service providers, almost all suffer from implicit assumptions that retain the notion of service based on the connection. These aspects of the background are discussed immediately. The "Last Mile" The use of telecommunication resources has moved well beyond mere telephone calls. Voice communications messages are no longer the dominant class of information that flows through the world's communication networks. Today's telecommunication users use these resources for many other forms of information. Data and computer video are just examples of the future. Users are requiring that their communication link with global networks have a high bandwidth, that is, digital data rate capability. The legacy links, as well as the architecture of the central office (ie the telephone exchange) and its cable to the user, can not provide the desired information capacity for all of these data, video, and other information. There is a need for a new network architecture that provides a wide bandwidth path to the user, which can satisfy both present and future requirements. For any of these new systems • of cable, an adequate bandwidth must be provided for the current end user, with an electrical signal interface - not an optical one -, while at a small additional cost, allowing the capacity for the transfer of optical signals for the moment in which both the equipment and the bandwidth utilization of the end user need to evolve. For the present, and the near future, the largest user bandwidth generally required (including for two-way communications), can still be contained within an interface that provides a total channel capacity of less than one Gigabit per second. . Stretches are required 15 relatively costs to connect from any local distribution nodes of a new network. Certainly, most of these cable runs are well under the mile distance of the "Last Mile" appeal that has been applied to this kind of > cable system, and most of these sections (or "local connections") will be well below half a mile. These new "base structure" link nodes for distribution of the networks may well be served by two-way fiber optic channels that connect many nodes provided for this regional network. With the advent of digital signal transmission technology 5, the operating requirements for these local connections, or branches of the "last mile" of the cable system, present very different new objectives that have been solved by the prior art. • It is also possible that, with a 5-watt electrical design, this last mile-inclusive cable may be suitable for some short-range inter-nodes links. The cost of installing any cable system to individual users - not the cable itself - is substantial, and is by far the majority of the network investment required by the service providers. It is highly desirable, if not essential, that any new installation of these connection cables will provide future growth in capacity. A Paradigm Shift in Network Architecture The communication networks of the past have been based almost 1: 5 entirely in a "call" or "message" type of traffic, where users only connect in a transient way to the network while "calling" or being "called". This connection-based architecture established a temporary connection path between the caller and the receiver. In the future, the 0 communications will be based on the "packet" switching principle. A packet message carries address information, so that the sender obtains the message for the receiver and vice versa. All users can connect continuously to this network. Users will actively choose to participate 5 and produce information "messages" only when they wish. Most of the activity in this network will exist with the flow of data, if only in an intermittent manner, albeit with a high frequency to and from the user, in a way that does not require the presence or active participation. user. This kind of function is more similar to the supply of electric power to users than the present communication function based on call connection, except that these messages also originate from the user's installation, as well as come to the user from various foreign sources to the I user's location. This represents new uses of communication processes to accommodate functions such as those exemplified by network "agents" or "avatars" that operate independently, supplying the information whenever their function requires it. In a similar way, the system of 1. The user may originate information as a result of similar programming. In the very near future, "passive" functions (that is, not demanding user attention) may become the dominant volume of information traffic carried by the network. 0 This future requires significant increases in data speeds. For example, in 1997, the entire volume of information flow in all long lines was presented with a rate of something just below 1 x 1014 bits per second. It is possible that in only a few years, a thousand .5 million users can be connected by networks at which time the global information speed can approach 1 x 1019 to 1 x 1020 bits per second. Although much of the fiber now placed in the world is dark, the growth of data speed eventually presents challenges. The use of wavelength division multiplexing ("WDM") in optical carriers used for fiber, as well as optical amplifiers and scatter correction, can increase their capacity by several hundred times. Even so, large quantities of new fiber will be required to support even larger and more ambitious applications.

This will simply further aggravate the need for a substantial bandwidth at the user end of the network systems. Improvements to meet this need should provide hundreds of megabits per second, in the send and receive modes, and preferably in duplex, that is, simultaneous sending and receiving. Many needs, unique to the last mile cable system, significantly affect the feasibility of the last mile designs, and influence their cost, durability, and reliability. The present communication systems are capable of providing only a limited bandwidth to the user, even when their long-distance base structures, and most local inter-exchange paths are fiber-based systems. Existing fiber trajectories have generally used only a very small portion of the information bandwidth potential of these fiber paths. The 1997 technology, for example, as mentioned above, provides the • opportunity to send many signals on a single fiber, and 5 to make each of these signals carry 10 to 20 Gigabits per second. The optical fiber is currently installed; only the terminal connection is required to achieve this result. Currently, some "Common Carriers" have been installing U these bandwidth enhancing means in the long range portions of their networks only to handle their current and projected loads. There is still a considerable latent bandwidth capability in these lines; however, currently there is little or no feasible technology 15 to provide a substantial two-way bandwidth at the user's terminal end of the existing communication networks. In addition, the current state of fiber use is significant: most of the fibers installed now are dark. That is, they are installed, but they do not carry signals. The present limitations of the bandwidth are simply in the means of supplying the existing and latent long range bandwidth locally to the entire audience at the same time. The United States patent application No. of Series 09 / 124,958, entitled "Electrically Optimized Hybrid Last 5 Mile Telecommunications Cable System" by Cotter and Taylor, incorporated by reference above, discloses a cable system that can be conveniently used to meet many of the needs described above.

• In addition, recent attention has focused on the: 5 combination of wireless technologies and computer systems. For example, wireless data communications for unlinked workers are being proposed from their desktops. These combinations can be expected to be provided with an appropriate architecture at least m because, for example, PCS networks were originally built with a fully digital infrastructure. For these reasons, PCS architectures can evolve to create wireless local cycles by building on existing copper or fiber infrastructures up to 1: 5 restriction. However, these proposed systems, for example, do not provide wireless communications from a user to the local cycle. They are proposed rather to provide a wireless local cycle. There remains a need for a wireless communication link from a user to the local cycle or to some other type of communication infrastructure. The present invention resolves the fabrication and design of novel cable systems and related system equipment to provide the last stretch of a cable system that links users with a wired communication network capable of providing any user with a capacity and versatility. greatly increased over those currently available from common carriers. The issues resolved here refer to the actual physical link that must be used to connect: 5 to a user with a network system. The present invention allows future growth. As noted above, the cost of installing any last mile cable system to individual users is also so substantial that any new installation should provide future growth. The incorporation of optical fibers in these local connection cables is essential to provide a real option for future growth. Again, the cost of the optical fiber itself is relatively low, adding little to the overall initial cost. 1: 5 Accordingly, a well-designed cable system design capable of combining both the broadband amplitude power line and the optical signal line in a hybrid configuration, becomes of exceptional value in the field of communications that It is evolving rapidly. If all local connections could be 0 constructed in this way, the present needs would be met and easy future expansion to optical use would be available when necessary. With the advances provided by the invention, it is feasible to see this kind of new network construction as an investment in .5 infrastructure of a long-term value.

The invention solves the physical and functional telecommunications supply requirements by achieving a hybrid electric / optical signal transmission cable system having a broad electrical bandwidth suitable for the current and foreseeable short-term communications needs, together with a capacity to accommodate optical fibers for the future. In the design of the cable system of this invention, there may be a number of optical fibers present in the connection of each user to the system. Anywhere can be easily accommodated from a few to possibly sixteen or more fibers without altering the performance of the electrical signals of the cable system. The contemplated frequency range of electrical signals from direct current to approximately one Gigahertz (GHz) or even more. 1: 5 This new cable system has two independent power lines, one to send and the other to receive. Both signal lines to send and receive have the same performance, and perform their performance of equivalent signals without interfering with each other. The conceptual architecture of this new system emphasizes the maintenance of a "four wire" connection, that is, the separation of the sending and receiving lines. These architectures eliminate many problems of echo, loss of return, and "singing" that complicate the present distribution systems. This new cable system 5 is intended to service the full range of current and future needs. For example, the invention can accommodate users of the Internet, digital TV, high-definition television ("HDTV"), multi-channel demand video, high-capacity digital information exchange, communication of work in the home and telecommuting, myriads of home and office services through "agents" and "avatars", automated manufacturing control, "telephony" with video, commercial and private conference with video, transfer and search of library files of high volume, and llfe channels of "telephone" service of multiple voice frequencies. The portability of the number (as in a transportable individual "telephone number" that goes with the user wherever it goes), now so highly sought, becomes a simple derivative of the nature of the Hierarchy signaling base 15 Digital Synchronous / Synchronous Optical Network (SDH / SONET) used by the system disclosed. Many of these applications require a very wide bandwidth in both directions. The design of the hybrid cable system can serve all kinds of users from the few that demand optical broadband amplitudes here and now, to the vast majority of users who are currently much less demanding. For the latter, a line of high-quality electrical signals with a bandwidth of one Gigahertz or less will be adequate, far exceeding the capacity of the 5 pairs of existing telephone wires, until they cover, in the future, the most plaintiffs An exemplary configuration that can conveniently be employed f the present invention is shown in Figure 1, which shows a schematic form of an interface of the local node .5 to the user. A local node 51 with inputs from two-way fiber optic lines 53 is shown. The nature of this local node is described in more detail below. These can be conveniently optical line links using the SDH / SONET format, the ATM format, or other formats. Additionally, through the use of WDM, a single fiber line can serve hundreds and even thousands of connections. Another entry 55 is shown for a possible plain Old Telephone Service ("POTS") line. In addition, a power source 57 is connected to the local node. This can be a battery backup source 1: 5 within the node, or you can have a source in another location in the system. Inside the local node 51, a Local Node interface ("NID") device 59 couples the sending and receiving channels with the fibers. The basic channel of an NID includes an optical receiver connected to the receiver fiber line, and an optical transmitter 0 connected to the transmitting fiber line. Each of these opto-electric elements provides a number of user channels (normally from 16 to 32). The NID can accommodate both an electrical mode 61 and an optical mode 63. A similar user interface device 65 ("UID") is connected at the user's end. A hybrid cable according to one embodiment of the present invention is connected between the NID 63 and the UID 65, and is denoted here with the numeral 67. The UID may have outputs to a computer, a telephone, a television, telephones, entrances of data, etcetera. Numerous other connections can also be provided, these being schematically represented by the numeral 69. Figure 2 shows a regional ring architecture that can employ the present invention. Starting from a global network or base structure 411, the initial connection is made with a switching and transfer point ("STP") 401. The base structure 411 is usually optical, but may also employ electrical wiring. The base structure can be provided by a company, such as QWEST or WINSTAR. STP 401 is connected to a plurality of local nodes 51. An example local node is 51 A In Figure 2, local node 51 'connects to a plurality of networks. One network serves a business district 403. Another network serves a shopping plaza 405. Another network serves an industrial park 409. It still serves a plurality of neighborhoods 407. Each of these networks can connect to the node 51 'via of cables 413. The cables 413 can employ the cable of the present invention. In the local node 51 ', an NID 415 is shown. In the network, such as that of the industrial park, the UID 417 is shown. These interface devices are described above and in more detail below. However, it should be noted that the regional ring architecture according to Figure 2 can take many forms. For example, if a cable 413 serves a single house, there may be a switch point and transfer at the house entrance that distributes the signals from the cable 5 to a plurality of rooms or devices. In this case, each room can be equipped with a local mini-node that serves the devices or devices inside. Moving one device from one room to another may only require the resetting of the switches, or the moving of jump cables. As seen in more detail below, the nodes or mono-nodes can be located by addresses inserted into the signal headers by the UID. In particular, for use in homes, cables of the type described below can be used, but with fewer materials 1: 5 protection and reinforcement, such as stainless steel braid. In this way, the cables can be made more compact, which is desirable for applications within the home. A typical distance from a node to a user will generally be less than 609 meters, and in urban or dense areas, it will usually be less than 304.5 meters. The design of the hybrid cable system of the present invention can even be operated to allow its two pairs of electrical conductors to be used for two POTS lines, which can be used in a manner concurrent with the wideband electrical operation. 5 Of course, the fiber channels remain independent in the manner used for any electrical mode. These power lines can also serve to carry the very modest amounts of energy needed to operate different regenerators of last-mile line signals, and possible network devices for the terminal equipment of the user, and yet still can operate without interfering with the "battery" voltage and bell functions in a POTS operation. POTS functions can be better served using digital lines to provide one or even a multiple number of "telephone" lines by means of a "line card" of digital-to-speech interface in the UID. The earlier node system would possibly better employ the signal format of the SONET and SDH standards now widely used by the existing inter-office and long-range optical networks. This new cable system, therefore, is highly compatible forward and backward. This again solves an important issue of cost / investment. The existing copper wire telephone network ("external plant") comprises more than three quarters of the present or total investment in the existing local telephone network systems. The node, sometimes referred to herein as a Local Node, has access to a multiplicity of broadband SDH frames, and makes it possible for them to address a plurality of users distant from the node. 5 The review of the previous technical analysis of the objectives and principles concerning the last mile cable system, has led the inventors to a new form of protected quadruple electrical conductor configuration and system elements, as well as architecture for use it 5 This new cable also easily accommodates a number and variety of optical fibers in novel ways. The quadruple principle, fully realized, provides the lines of electrical signals of sending and receiving without double independent interference (two) so essential for the local connection of the last ll mile. A four-wire cable concept is not new by itself, but this disclosure resolves many other factors that, by improving the realization of its potentials and by extending the flexibility of the configuration, allows to achieve all the other characteristics required of cable systems. the last 15 miles, including fiber optic lines. The present invention also discloses a new structure, particularly suitable for achieving the required precision in a quadruple geometry selected for low noise ("XTLK") across the wide-band 0-band electrical performance spectrum. The structure of the cable system of the invention provides novel methods for the inclusion of various optical fibers. The present invention also discloses new techniques for improving the protection effectiveness of electromagnetic interference within the cable systems of the invention. The unique performance advantages arise from the novel balanced power source and the load termination devices disclosed, which can be easily incorporated into the online digital signal regeneration modules. A novel annular conductor construction that improves the performance of electrical signals and improves the performance of EMIR is also disclosed. In addition, novel and economical manufacturing methods for the new quadruple configuration are disclosed, which also achieve exceptional precision and stability of the mechanical structure. Also disclosed is a wireless room that can be interconnected in one of several locations in the last mile system of the invention. For example, this port can be part of the node, the NID, or the UID. The port can be incorporated into a module that can translate the wireless protocol, for example CDMA or GSM, into a form usable by the UID, for example LINUX. F Software is provided to operate the devices 20 of the invention. In particular, the software works particularly to operate the STP and the UID and their mutual operations. These operations may include billing or signaling depletion, and so on. The details of one or more embodiments of the invention 25 are stipulated in the accompanying drawings and in the following description. Other features, objects, and advantages of the invention will be apparent from the description and drawings, and from the claims. Description of Drawings 5 Figure 1 is a block diagram of an organization of a local node that serves multiple users by designing novel cable with electric or optical lines of full two-way bandwidth. The possible use with the POTS service is also shown. Figure 2 is a diagram of the organization of a regional communications ring that uses the novel cable design for the last mile connection with the end users. Figure 3 is a schematic block diagram of a fiber interface device and a Local Node interface device. Figure 3a is a flow chart of a process according to one embodiment of the invention. Figure 4 is a schematic block diagram of a user interface device. Figure 4a is a schematic drawing showing the flow of signals within a user interface device. Figure 5 is a diagrammatic view showing a central support of a quadruple annular conductor that maintains the precision in the location of the conductor inside a cable and in relation to the external protector. Figure 6 is a diagrammatic view of a form of a composite cable that includes fiber optic members. Figure 7 is a schematic cross-section of a section of the cable wall as located in Figure 6. Figure 8 is a perspective section of a cable in accordance with the present invention, employing a housing. External coupling of impedance Figure 9 shows a schematic form of a possible drive and termination element to achieve a balanced operating condition for a quadruple cable Figure 10 shows a schematic form of an alternative mode of a possible drive and termination element to achieve a balanced operating condition for a quadruple cable Figure 11 is a diagrammatic cross-sectional view of a form of the interlock or novel positioner Figure 12 is a view of the shape of the unsecured extrusion of Figure 11. Figure 13 is an additional schematic detail of the positioner 5 Figure 14 is a schematic view separated in part is of a mode of the positioner, illustrating the separated interseguro elements. Figure 15 is an enlarged diagrammatic cross section of a form of instantaneous insurance portions of a positioner, which may be employed with the present invention. Figure 16 is a schematic cross-section of a complete circular shape of the four-section extruded positioner. Figure 17 shows a cross section of a novel annular conductor shape, showing the novel waveguide wires, and the central core available for the optical fibers. Figure 18 shows a cross section of a wire inside the annular conductor of Figure 17. 1: 5 Figure 19 shows a shape of a unitary tubular annular conductor ("UTAC") having a surface waveguide function, and with a central core available to contain the optical fibers and a protector. FIG. 20 shows a schematic cross section of the unitary tubular annular conductor of FIG. 19. FIG. 21 shows a schematic cross section of an individual conductor inside the annular conductor assembly shown in FIG. 18. FIG. Figure 22 is a schematic cross-sectional view of an extruder die head and a body, which can be used to form a positioner in accordance with one embodiment of the present invention. Figure 23 shows a profile of the pressure against the time that can be followed in the extruder of Figure 22 to form the positioner. Figure 24 shows a schematic configuration of the extrudate treatment baths that can be used immediately following the extrusion step. Figure 25 shows a schematic diagram of an alternative die li that can be used to form the positioner of the present invention. Figure 26 shows a profile of the pressure against time that can be used in the device of Figure 25 to form the positioner in accordance with an embodiment of the present invention. Figure 27 shows a process flow diagram that can be used to form the positioner in accordance with an embodiment of the present invention. FIG. 28 shows a schematic form of the basic time frame of the SONET or SDH transport time division multiplex. Figure 29 shows a twin axial cable employing one embodiment of the present invention. Figure 30 shows a double coaxial cable employing one embodiment of the present invention.

Equal reference numbers and designations in the different drawings indicate the same elements. Detailed Description System and Interfaces Referring to Figure 2, where a Local Node system is shown schematically, the fiber optic ring contains the many fibers of the regional system. Each fiber line can follow a ring topology in such a way that it physically goes in two directions from each node, ^ finally connecting with the regional STP (Switch Transfer Point) 401 shown schematically in Figure 2. The STP links to the regional ring with the fiber or electric base structure, and is a blockless multiple transmission device that connects multiple users with global networks, and that can also connect the wireless input transmissions and the incoming wire line signals from the global network wired to and from multiple users. The STP can also provide operational energy for the regional ring and for each of its Local Nodes, as well as for the UIDs connected to them. In addition, standby power can be provided for the case in which the system is going to be subjected to an energy depletion. The system can use a duplex line design, in such a way that there are separate transmitting and receiving lines throughout it. At least two of the fibers in the fiber bundle shown schematically, would interconnect with any particular node 51. As shown in greater detail in Figure 3, a Fiber Interface Device ("FID") 60 couples its optical receiver 61. and its optical transmitter 62 with its respective optical receiving and transmitting fibers 53. As mentioned herein, a local node includes at least one "FID" and at least one NID per FID. Typically, several NIDs are provided per FID, such as approximately 16 to 64 NIDs. The demultiplexer ("DEMUX") 301 converts the multiple channel signal of the fiber into the plurality of outputs. The manner in which demultiplexing occurs depends on the coding of the data, for example, if the data is encoded by TMD, WDM, and so on. The elements of an FID are a shared resource for channels fed by an FID 15 within a node. Any of the FIDs in a node can serve 16 to 32 or even more than 64 double data lines, and therefore, 16 to 64 or more NIDs. The node can contain both FIDs as needed for the number of users that are F go serve. The number of users per FID depends on the level 20 multiplexing of the SDH transport carrier used. For example, STS-384 (10 Gbs) provides 32 channels of STS-12 (622 Mbs). A single Local Node could serve 3,200 users within its economic range, if its last mile stretches were economically short. If desired, the 622 Mbs lines are 25 can divide into a number of IT or T3 lines to serve, for example, multi-owner buildings. The FID elements 60 and NID 63 can be of a modular physical character f, and a node housing can be designed to accommodate additions of substantial capacity where this seems advisable. The stretches of the regional fiber bundle ring can also be specified to contain additional unencumbered fiber for additional expansion of the users served by the system. In this way, a single node site may be accommodating user expansion by connecting more luf of the fiber bundles of the ring with the added FID and NID elements. Figure 3, of course, is a non-limiting case, showing only a possible FID with only one NID connected. The serial optical / electrical receiving interface 61 may be an optical fiber broadband SDH optical receiver, 15 of only a limited sensitivity, because the fiber cable runs in general will be very short - just around the regional ring. The demultiplexer and the multiplexer circuits ("MUX") can use one of the varieties of chips or chipsets now generally available for 0 SDH. For example, the chipset from Vitesse Semiconductor Corp. VS8021 / 8022, is an example of the chip set class that can be used for fiber data rates up to OC-48, and the Triquint Semiconductor can supply a game package of chips that operates at a speed of 10 Gbs. : 5 The FID can provide any number of additional functions. For example, the FID can provide decoding functions, or other functions that would otherwise be left, for example, to the NID. The NID contains the elements of the system that are responsible for the coupling of the physical cable with the FID, and therefore, with the global network system. The two separate lines are shown in Figure 3. The NID 63 includes the portions that couple the serial reception line from a demultiplexer output, with the cable 67 receiving pair, and also couples the transmission torque of the cable 67 with one of the serial transmission inputs of a multiplexer circuit. The impulse lift circuit of the receiving portion of the NID, and the opening elevation circuit of the 15 receiver of the transmission line, are adjusted by the installer to give the clearest pattern and the optimum BER (bit error rate) when the system is installed. The termination resistors on the terminals of the transmission torque and F reception are impedance coupling devices for 20 minimize Reflections in those points. The unit of the current source appears for the system as an infinite impedance in all impulse states (ie, high bit, low bit, and transitions). The HPF and LFP elements help to isolate the direct current energy from the active signals. The perfection of The cable balance is complemented by making the current source unit balance in the phase with the impellers, and by having the balanced input amplifier reject t ^ fc highly any common mode signals in the respective pairs, as it is explained in detail later. The fibers t > Optics contained in the Ultima Mile cable are not used in any of these schemes in Figures 3 or 4. They are shown in both figures as fiber ends available for future applications. In some applications, the user may wish to affect the data before or after the data passes through the quad cable 67. For example, the user may wish to use a wireless link to affect the data passed to the quad cable. An "affectation" of the type referred to herein may be an application to switch on or off. 15 turn off a device in the user's house using a cell phone. To accomplish this, the invention also provides a method and apparatus for affecting the data in one of several locations, this apparatus being connected to a cellular communications module. 0 To do this, and referring to the Figure 3, a DEMUX 303 / MUX 305 chipset is provided immediately following cable termination. This location is, therefore, before the signal that enters the quadruple cable 67. An input is provided from a wireless module 307, described further forward, to the DEMUX / MUX. This entry is used to alter the demultiplexed data. The wireless module 307 in turn connects to a wireless antenna 309. f The DEMUX / MUX does not need to be presented at the prescribed location. For example, an optical, non-electrical DEMUX / MUX 5 may be provided on the regional ring itself, for example at the node location, in the FID, or in the NID. This system is shown in Figure 3 by the corresponding elements 303 'to 309'. Although these elements are different from elements 303 to 309, in that they act in the optical domain, their functions are analogous in another way. Of course, in the event that the fiber extends to the user's domain, an all-optical system would be necessary. In this case, the DEMUX / MUX operates optically at the UID level. Also in this case, the SONET / SDH frame can be sent all the way current 15 down to the UID. Then an optical demultiplexer can operate on the frame therein. This can be particularly convenient for star / bus-type architectures. In yet another embodiment, a wireless input 0 acts on the signal at the UID level. This can be in the electrical domain or in the optical domain. In particular, in an all-optical system, the DEMUX / MUX would operate in the optical domain. In several ways, the action on the signal at the UID level may be more convenient to implement. 5 In this modality, the basic structure can be as follows. As is known, a user's mobile unit can connect wirelessly to a cell site, which in turn connects to a telephone switching office ^ Be 'mobile. The mobile telephone switching office is connected by means of a terrestrial telephone network with another mobile telephone switching office, which in turn connects to a cellular site serving a node, a NID, or a UID. Accordingly, a user of a cell phone can send information through the land-based telephone lines llfc to his UID. A user may wish to have a land-based telephone line dedicated to their UID for this purpose. The user's call can be routed through the POTS input 55. In an alternative mode, the user's call can be routed from the mobile telephone switching office 15 directly to a fiber base structure. However, this last modality may involve a significant capital investment. For some special situations, the user may use a radio device to affect the data in F the UID or in the NID. However the signal is received, the call of the user may initiate a change in the data in a demultiplexed data frame, for example the SONET / SDH frame. For example, a basic SONET / SDH framework is shown in Figure 28. The basic frame has 8 bits per cell. By changing the data in this In the frame, the user can send a message to his UID, causing a desired action to occur. The data in the frame can be changed in different ways. For the placement of the f elements 303-309 of Figure 3, the frame is already unique for a specific UID, and therefore, the header information related to the intended NID / UID can be omitted. This would also be true for the next mode, where the signal is affected immediately after demultiplexing by the UID. However, for the DEMUX / MUX placement of elements 303 '-309', the frame is still not specific to an Ifc NID / UID, and therefore, the related header information for which the NID is intended is required. / UID. In this latter mode, the header information would be used to route the optical signal to the appropriate FID, from where it is sent to the specific intended UID. The rest of the operation would be the same as in the previous modalities. This alteration operation would involve decoding the data in the SONET framework, and determining if the new data is redundant or contrary to the data of the present SONET framework. A protocol can be determined; for example, data 0 originated the last time in time prevail. In this protocol, user data would take precedence over contrary data already present in the SONET framework. In most situations, the new data can simply be in addition to the data already present in the 5 SONET framework. Therefore, the new data is simply appended to the last data entry in the SONET framework. If required, a new framework could be created to handle the additional data. It should be noted that the modality shown in Figure 5 3 shows the wireless link connected to the FID 60. Of course, other modalities may also be employed as described herein, or as would be known to one skilled in the art. For example, the wireless link can be incorporated by itself at a point within the regional ring not Life connected with some particular node. This link can serve the entire regional ring. If a wireless signal arrives at the regional ring, then part of the demultiplexing process would involve adding the additional header information in order to send the altered SONET frame to the node 15 appropriate. An advantage of this mode is that the wireless link can be placed at some distance, including at some height, from the nearest node. In another mode, the wireless link could service additional regional rings by sending an appropriate signal to another regional ring or through the STP. In a variation of the previous modality, a number of wireless links capable of communicating with each other can be employed by means of a separate implementation of the wireless architecture for standard wireless mobile telephone switching office 5. For example, a wireless transmitter / receiver can be located in each of several buildings. Each building can service a local node, which can include a number of adjacent buildings. You can use wireless signals to transfer information between the 5 buildings that have wireless links. Alternatively, the buildings can be linked together, for example, with a fiber optic connection cable or by a separate regional ring. The buildings can also be placed in mutual communication, for example, through microwave ll or radio frequency links. When a building receives information, that information may be inherently specific to a UID or NID within the regional ring served by that same building. The information, which may be, for example, in the form of CDMA, TDMA, or GSM, is converted into a protocol language that can be 15 understood by the architecture of the ring (for example, SONET), and can be routed along the regional ring. Other systems that may be employed include ATM, IP V6, W-CDMA, and so on. A return line is available through the STP. The pose¬ F has the advantage of being economical and of providing a 20 return line of very high bandwidth. It will be appreciated that a similar architecture can be employed in the modalities where buildings are linked not by wireless links but by broadband microwave communications, fiber cables, or a regional ring. It can also be used 25 wide symmetric band.

In yet another embodiment, a central antenna with a satellite downlink can be provided. This central antenna can serve several communities. Each communication has a sub-antenna that receives a signal from the central antenna 5. The communication link between the central antenna and the sub-antennas can be, for example, by means of a microwave link, a radio frequency link, or another similar link. Then you can connect each sub-antenna with an STP or another part of a regional ring, which then gives service. This may be especially economically feasible, because the current wireless companies are not restricted in the number of towers they can build. Then the regional ring can connect a number of Local Nodes, which are connected to the users by means of the cables that are an aspect of the 1: 5 present invention. This configuration is referred to herein as "converged wireless cable". This system is analogous to a star / busbar architecture, which is common in cable companies. In an architecture or star topology / busbar. The 0 end points of a network are connected to a common central switch through point-to-point links. From the end points, a busbar is provided to extend the cable service, for example, to several houses one block away. In the present invention, a difference is that the collecting bar 5 is a regional ring. Of course, many other advantages and differences in the invention are also present. A particularly powerful implementation of the converged wireless cable is the provision of HDTV. Current cable companies can not supply HDTV. The central antenna and the sub-antennas disclosed above, however, can be conveniently provided with sufficient bandwidth, in combination with the cable of the invention, to easily provide HDTV from satellites or other wireless sources. One way of distributing HDTV or other cable system is by using the microwave multi-point distribution system ("MMDS"), which is also known as multipoint multi-channel distribution service. This system uses microwave transmissions to distribute the cable from a single transmission point to 15 multiple reception points. These systems can operate, for example, at 2.3 GHz. Using this and the cable provided, HDTV can be supplied without compression. Other techniques can also be used, such as LMDS (with speeds up to 28 F GHz), as it will be recognized, although it has been recognized that MMDS is 20 stronger with respect to the weather, and so on. In the case of LDMS, the frequency is conveniently shifted down to the frequency-modulated rate, in order to avoid the line of vision requirements implicit in a signal at 28 GHz. This change is even more important with respect to the 25 higher frequencies that are currently being considered, for example 38 GHz. In these systems, all supported channels would circulate around the regional ring, but f only one can be sent down one cable to the user at a time. Periodically, the appropriate billing information will be sent upstream through the cable, in such a way that the user can be charged his HDTV if desired by the billing structure. Of course, the cable system of the invention allows to have complete two-way communications upstream and downstream. The recent FCC regulations have opened the way for these two-way communications, and the cable system of the present invention can conveniently utilize these permits to provide a high bandwidth return line. With regard to billing, it is observed that the The invention can provide an excellent billing function, which is currently lacking significantly in the industry. Two-way communications allow to route in a convenient way the related information, for example, F with the use of electricity, wireless rights, use of TV by 20 payment, downloading files, such as music or games, and so on. In particular, the user interface device can be used to keep track of the use of each device connected thereto by means of the different interfaces and interface cards. The billing or accounting database can be located at the STP, the Local Node, and so on. For example, the billing database can be located in the UID in the same way that an electric meter is located in a house. Alternatively, the billing database can be located upstream of the STP, at a regional or central location. In addition to billing, other important information may be passed upstream, including exhaustion or service requirements, viewer and subscriber marketing data, advertisements seen, and so on. You can encode marketing data related to more personal information. It is further noted that these sub-antennas may be suitable for mounting and connecting in the STPs for each regional ring. Of course, cell sites can be physically located in a separate tower, and can be connected to the regional or direct ring 5 up to the STP. Wherever the sub-antennas are mounted, the received signal can then be converted to a SONET / SDH frame (or other protocol) in the STP by means of hardware, software, or firmware. That is, an IP protocol can be provided to convert the wireless signal 0 to optical or electrical. For some content, the manufacturer or the distributor can provide a code necessary to make decoding possible. This type of distribution can be particularly powerful for, for example, moving images, in order to make possible a uniform distribution throughout the nation.

Figure 3a shows an example flow chart of the conversion process. Step 302 shows a signal that is being received from a satellite. This signal can be an HDTV signal, for example. Alternatively, a signal can be received from some other upstream antenna (step 304). The signal ee receives at the central antenna (step 306). Then the signal is retransmitted to the sub-antennas by means of a system such as MMDS or LMDS (step 308). The sub-antennas receive the retransmitted signal (step 310), and the signal lajf is demultiplexed (step 312). Then the signal is converted to a suitable frame for transmission around the regional ring (step 314). In Figure 3a, a SONET / SDH format is shown, although it will be recognized that other formats can also be used. This data format can be, for example, optical or electrical. 15 The frame is then thrown around the regional ring (step 316). This mode can be conveniently used for residential as well as commercial applications. For example, a residential application can use the same F format with a centralized transmission point towards a 20 plurality of local regional rings. Each regional ring can have its own dish to receive signals. Returning to the architecture of Figure 3, the altered SONET frame can be multiplexed before being launched into the data stream. In the following modality, the data is 25 subsequently alter their demultiplexing by the UID, and no further multiplexing is required. In this mode, the data is altered in or near the UID. The UID is shown schematically in Figure 4. The cable 67, in this figure, represents the same cable 67 (the opposite end) shown in Figure 3. The example signal provided for each of the double lines is a current of 622 bits of type SDH. Of course, other types of signals can be used as they are known in this field. The reception and transmission lines, processed as pairs of wire wires, operate F in a manner similar to the function of the circuit of Figure 3. These elements operate in a similar manner up to the buffer zones 71, 72 of the elements DEMUX and MUX 171 and 172, respectively. These DEMUX / MUX elements operate in a manner similar to the higher-speed circuit shown in Figure 3, but at the lowest speed of the individual user's bitstream-622 Mbs. They work to distribute the appropriate cells of the SDH framework to the functions assigned by the system design. Of the many possible assignments, a typical selection is shown in Figure 4, which involves a video interface, an Internet interface, and numerous optional interfaces, including interfaces for wireless or wired communications. The UID controller 173 may be a microprocessor or a computer. The UID controller 173 may also place software headers on the signals routed to the different devices connected to the node or the mini-node. In a similar way, headers can be placed by the UID over the signals sent upstream to the NID and the FID, to indicate where the signals should be sent, as well as the nature of the signals. 5 There are two video lines for the user. Each of the two is available as a baseband video or as a radio frequency signal suitable for existing TV receivers. These outputs can be connected using plugs or the RG-59 TV cable connectors commonly used in TVs. \ m TV sets. Of course, in order to connect a digital UID to an analog television, a video interface 81 (Figure 4) is required, which can employ a digital-to-analog converter 82. The converter 82 can convert the digital television signals into a form appropriate for analog TVs. 15 This allows users who have analog TV sets to use the UID. The converter 82 can be, for example, a separate line card. The allocation of the digital data rate for this function can be any desired level of F use of channel capacity; however, they can be optimal 20 approximately 100 Mbs for each one in the system, allowing a very high resolution video to be transferred. A multi-purpose tuner can also be used as an additional module, since it allows tuning a variety of different digital television formats. The The choice of program in this system is made by transmitting to the network the instructions for the desired source and program. Additionally, the sources can also allow the user f to specify the desired duration. These instructions would be sent over one of the sending interfaces by means of a simple 5 keyboard input system. If desired, it will only receive one type of video transmission, the user would simply enter the channel number of the desired program. This operates as what has been called video on demand. The STP of Figure 12 is a point in the system where these switching and selection functions can be executed. The system allows many service providers to deliver their offers through the system. The number of possible selections is as large as the number of possible addresses. At least two lines of information can be provided 15 Internet, each with a broadband capacity, which can be 10 Mbs, 45 Mbs, or even more, depending on the user's requirements and the ability of the ISP to provide the data rate, although this choice is arbitrary . This bandwidth would use only a small percentage of the available capacity of a dual system of 622 Mbs, and typically has 400 times more capacity than the best current telephone modems. The mechanical connection of the interface can be one of the standard computer formats, such as a 1394 serial bus bar. The digital lines can be routed to any Internet Service Provider that connects to the system. The scope of these sources is considerably extended by the format based on SDH, which makes it possible to communicate with the sources at any point of the global network, 5 regardless of the distance, because the digital format does not deteriorate with distance to no significant degree. The system is shown with six telephone lines that connect to the digital network through the SDH signal lines. The elements of the "line card" supply the cycle The 48-volt DC current common to the standard telephone, and also provide the 20 Hz ring function, and the lines of reception and transmission of voice digitization. The outputs of the line card can be a standard telephone hardware type RJ-11. A wireless line is also provided as shown in Figure 4. In this line, a wireless transmitter / receiver 405 coupled with the UID controller 173 is shown by means of an optional wireless electronic system 407. Then the transmitter / is coupled. 405 wireless receiver to an appropriate type 0 of antenna 409. The wireless transmitter / receiver 405 can be placed, it is recognized, in other locations of the system as well. For example, wireless transmitter / receiver 405 can be located at the location denoted as location 411 or 411 '. 5 I mean, the position requirement for the 405 wireless transmitter / receiver is that it be placed where it may affect a portion of the data in the circuit. (^ Using the wireless transmitter / receiver 405, the user can affect the UID by means of a 5-wire wireless connection, such as a cell phone.For example, the user can switch on a household appliance by means of his cell phone In the location shown in Figure 4 of the wireless transmitter / receiver 405, the user would affect or llfc alter the data at a point in the circuit downstream of the demultiplexer 171, but before the signals that are physically divided into different signal lines Depending on the type of signal used, the alteration of the data may then be similar to that described in relation to Figure 3.

The alteration may occur at any point following the demultiplexion. In certain situations, a separate DEMUX / MUX step may be presented before the signal reaches the demultiplexer 171. F At location 411, the wireless link only 20 would affect the video interface, and therefore, this location may have limited application. At location 411 ', the wireless link could affect the optional interfaces, the internet interface, and telephone lines. In addition, the data from the alteration conveniently could easily be rerouted to the transmission circuit. The wireless electronics 407 serves for further processing of the signal from the wireless transmitter / receiver 405. For example, many current cellular systems employ a form of digital cellular telephone service called code division multiple access ("CDMA"). The CDMA is an extended-spectrum technology that assigns a code to all voice bits, sends a mixed transmission of the coded voice over the air, and reassembles the voice to its original format. This technique provides a very effective and efficient use of the spectrum. Accordingly, the 407 wireless electronics could be a dedicated wireless port employing an algorithm, implemented in the software, in the hardware, in the firmware, or a combination of the three, to accommodate the signals sent in the CDMA protocol, and can allow these signals have been translated into the software language of the UID. For example, a possible software language for the UID is LINUX, and the 407 wireless electronics could translate, for example, the CDMA into LINUX. Of course, the software could then also translate the signals to the standard for transmission, for example back to CDMA, for different purposes, such as verification that the signal was received by the UID. In addition, the plug module could be replaced to accommodate different types of wireless standards or improvements.

It is observed, in the wireless modalities of Figures 3 and 4, that it can also be accommodated wirelessly by satellite. In other words, the same procedures and methods would apply, except that the transmissions would arrive from, and be sent to, the satellites. It is further noted that, in each of these modalities, an "open industrial standard port" could be provided. For example, a standard interface of sockets or protocols can be used to connect to the controller 173. The structure structure of this standard port can vary depending on the consensus of user requirements. However, once a standard port is defined, any level of control can be used. For example, the level of control can vary from a simple electrical control of an interface device 15 optional, up to a fully automated control of each device connected to the UID. A possible open industrial standard port can conveniently employ the Firewire, for example the Firewire 125_sec standard, which conveniently F has the same time base as SONET. This feature 20 allows the activation of dirigible video in the UID, that is, it allows the interactivity between the user and the UID. It is also observed in each of these modalities, that the wiring from a UID to, for example, the appliances inside a home, can be realized in a way 25 wireless. However, it is possible that wireless communications are not efficient for these purposes, and that a direct radio link, a computer analogue of which is available (for computer network) in Diamond Multimedia, would be preferable. In an alternative way, 5 telephone plugs within a house can also provide a convenient way to connect devices to each other and to the UID. Software Considerations The software can be resident in each one of the li components of the system to operate the different functions. Of course, the software can be implemented in the hardware, in the firmware, in microcode, or in other different media as they are known. The functions of the software include at least the following 15. Conversion of Wireless Signals to SONET / SDH This aspect is discussed in more detail below under the functions of the STP, because it is in the STP where F can conveniently present this functionality. However, it is further noted that UID software can employ these features as well. For example, if a dedicated wireless port is located in the UID, then the software can provide some or all of the conversion from the wireless mode to the UID language, for example C ++, or another language, depending on the processor that controls the UID. .

Routing of Signals Within the Local Node Routing of Signals Within the Interface Device, ^ fc of the User The user interface device requires the 5 software to route the signals as they are received from the cable to the different input / output devices. The software of the user interface device also routes the signals as they are received from the different input / output devices upstream to the cable, and further to the Li Local Node. An important advantage of the present invention is this high-bandwidth two-way communications line. Therefore, the software must include a set of controllers to control the different interface cards that serve the different input / output devices. 15 These controllers must be replaceable and updatable. Figure 4 shows a flow diagram of the signals made by the UID software. An analogous system is that carried out by the STP. In Figure 4a, a wire 602 is shown F with an output to a receiver 604 and a transmitter 606. A communication processor 608 controls the receiver 604 and the transmitter 606. The communication processor 608 maintains the active line, performs some frame error correction, and performs synchronization . A memory 610 serves the communication processor 608, and allows modifications of its protocols. The data from the receiver 604 is fed into a buffer zone 612. To clean the data immediately from the interface, a detector 614 and a derived clock 616 are provided. The derived clock can be controlled by the network line. The clean data is then demultiplexed by the DEMUX 618, and distributed by the distribution processor 620. The distribution processor controls the distribution of the signals subject to instructions from the general interface 622. This general interface 622 may be comparable to the port open industrial standard mentioned above in relation to the UID controller 173. Generalized single user instructions can be stored in a memory 624, which service the distribution processor 620. Then the bus driver 626 can route the signals up to the interface cards 628, 630, 632, et cetera. On the transmission side, a buffer zone 634 and a multiplexer 636 are provided to prepare the data before it is launched on the cable 602. An error correction circuit 638 may also be provided. A number of controllers may be provided. generic 0 for each of the different interface cards. Quality Control through Communications with the STP The STP can periodically interrogate the UIDs to make sure they are functioning properly. If they are not, a service alert may occur. In an alternative way, communications between the STP and the UID may allow the transmission of data between the two, such as to carry the record or for the bookkeeping functions. Attaching Addresses to Output Packages 5 Software within the UID essentially eliminates the functions of today's ISPs. The software adds headers to the output packets, that is, all the routing information necessary for a packet of data, for example, over the internet, to be sent to a receiver. In other words, the UID prepares the message, in such a way that the message is able to be processed by a router to the intended recipient without requiring additional processing. The address does not have to be added or modified or subtracted in order to deliver the message. The headers 15 may also include, for example, a time stamp and the address of the sender. In this way, the concepts used in SDH are taken all the way down to the user. In In particular, the entire framework is always available to the user. Therefore, the system is similar to the service 20 current newspaper. It is not necessary to make rows. The user sees the distribution network directly from the UID, as opposed to being separated, for example, by an ISP. First, a packet of data is described. A data packet is much more than just a payload, although that can 25 be the bulk of the package. Before the payload, a number of headers are placed. The first header can be the TCP / IP header, followed by the UID header, followed by 1 ^ the payload of the UID. The TCP / IP payload is identically the combination of the UID header and the UID payload. 5 The UID can work to place these headers in the payload, for example the SONET header, the TCP / IP header, and the UID header, so that no further modification of the packet is necessary to enable it to be transmitted to your intended receiver. For sub-UID functions, such as to switch on devices within a home, the headers to cause these commands are located within the payload, and are called "sub-headers". The UID can place headers in the payload starting at the interface cards. This aspect of the header describes from which device the data came from. At a point upstream of this, such as in the distribution processor or in the multiplexer, another header can be set if necessary, denoting the UID from which the data came. An additional TCP / IP header can be placed, as given to know, for example, in Cisco TCP / IP Routing Professional Reference, by Chris Lewis (McGraw Hill 1998), pages 29-40, which is incorporated herein by reference. reference. Billing / Account Functions The billing and account functions performed by the software have already been mentioned previously. These include monitoring any and all devices connected to the UID to determine a variety of parameters, including the use of f energy, the time used, and so on. For example, in a pay-per-view TV situation, the software can allow a 5-minute user to preview a selected feature. If the viewer keeps that channel activated for more than 5 minutes, or returns to the channel after the conclusion of the preview period, the software can be directed to debit the viewer's account for the amount of money prescribed. These billing and account functions do not need to occur in the UID, however. They can be presented in the STP, in the Local Node, or any combination thereof. The billing and account functions can be used to track the data for commercialization, as described above. You can maintain information regarding consumer demographics and purchasing trends. Then directed marketing can be used to sell to previously selected consumers. 0 STP Software Functions Many of the functions provided by the software at the Local Node or UID levels can also be incorporated into the software located in the STP. For example, the software can be used in the STP to place the 5-direction headers in the output data packets or frames to identify the regional ring from which they arose. In this sense, the STP acts as an ISP of the current day. f For the data to travel in the opposite direction, the routing software can be used to launch the 5 data frames around the regional ring. For redundancy, duplicate frames can be thrown around the regional ring in opposite directions. A frame arrives at the desired Local Node. The other can go back to the STP. Then the STP software can separate this duplicate message and prevent it from being sent to any other party. In the case where duplicate messages are received in the Local Node, and allow them to travel to the UID, the UID software can separate one of the two input messages. It is also observed that redundant duplicate frames sent by the STP are monitored by software 5 to detect a break or cut in a fiber line. If such a break or cut is detected, a service alert can be automatically sent to the service provider. In the case where the STP is coupled with a central antenna or a sub-antenna, as those terms are used previously, the STP software can also be used to convert the wireless or satellite input signals to frames or other formats , for example through IP protocols. For example, frames can be SONET / SDH frames, or they can use the ATM format. The STP software can also perform a reverse conversion when sending frames from the regional ring back to the wireless domain. In this case, the STP software may place a wireless header over the wireless data, or another header as required by the wireless communication protocol 5 employed. In an alternative mode, a variety of wireless signal types can be transmitted through an STP, instead of just one. These may include CDPD, wireless IP, or other protocols, as enumerated elsewhere in this disclosure, or other similar protocols. ] F It was previously observed that the STP provides multiple transmission. This possibility of multiple transmission allows the connection of any two users within a regional ring without the need to send a message or packet of data from the users outside the regional ring. 15 Signal Considerations and Performance Requirements Several higher performance requirements are important for a local network connection cable system in accordance with one embodiment of the present invention. The F losses of optical line transmission will be very small 20 inclusive for the longest of these local connections. Little else can affect the optical signals, short of a physical damage by the weather, water, or squirrels always present that seem to favor the cables to gnaw. However, in the electric cable mode - for broad band use - the most significant performance limitations depend primarily on how well a cable system works with respect to these three main signal corruption factors: 1 ) Loss of cable system transmission and delay time properties, particularly at higher frequencies (HFTL). 2) Rejection of electromagnetic interference from the cable system protector of the signal lines (EMIR). 3) Noise between the sending and receiving lines (XTLK). In the engineering efforts of the prior art, the main thrust with the electric communication cable systems was dedicated to obtaining low transmission losses over as wide a bandwidth as possible. The need for a very low transmission loss was presented by 15 the analogous modality that dominated the methods of transmitting information from the past. Because the analog signals were repeatedly amplified after losing energy in each branch of a few miles of their journey, the F ratio of signal to noise. The longer the 20 sections and more traveled the equipment, the greater the possibility of having cross talk and interference noises entering the signals. With the development of modern information theory, the advantages of digital signal transmission became clear. This new understanding, together with the 25 digital error correction coding that became possible, revolutionized the design ideas of communication systems. As a result, the hardware techniques used changed radically and quickly. For example, in 1997, virtually all communication channels used digital techniques, at least in the inter-office and long-range portions of their lines. On similar days, the main concerns were the deterioration of the signal to noise and the increase in other noises (distortion and cross talk), with the distance traveled by the signals. Modern digital lffe systems essentially do not deteriorate in that way, even when challenged by the distance of going around the world. Once in the digital domain, the rules for the definition of the transmission requirements of the cable systems changed radically. 15 The loss of signal transmission and high frequency unwinding (HFTL) are not judged by themselves, but rather in relation to two other factors: ^^ 1) the amount of internal noise energy in the system, and 2) the proportion of the signal energy to the other two corrupting energies, EMIR and XTLK. It is relatively easy to correct even substantial loss or high frequency unwinding and delay dispersion, which is reasonably stable or changes only slowly over time. A portion of these problems can be overcome by the adaptive matching of the system response. As such, even a large bandwidth can be sent over a very loose cable system. Adaptive equalizers or other "matched filter" signal correctors 5 are part of most modern signal terminal equipment, such as ubiquitous personal computer modems that enable telephone data communication. Because virtually all of the information that will be communicated in any new system will be in a digital form, the process will be the same. Reliable communication of signal information is reduced to the ability of the equipment to reasonably differentiate between a "one" and a "zero" by means of a detector or signal discriminator. The signal loss level or the high frequency response defects are further exceeded whenever the signal 15 is only moderately corrupted by noise, agitation, interference, and / or cross talk. The binary digital signal can be regenerated completely with this signal detector, A thus resetting the energy of the peak signal well above the noise and the cross talk at the position of the line in 20 where this is done. Therefore, the ratio of signal to noise (S / N) becomes a first and most important part of any new "last mile" cable system specification. This behavior of the signal-to-noise ratio is dominantly a result of the system's capabilities. 25 cable to reject interference (EMIR), and to minimize cross-talk (XTLK) between the sending and receiving links within the cable system. The novel quadruple configuration | A of this disclosure resolves the needs in these factors, allowing lengths of substantial stretches before the action of the regenerator is required. Modern integrated circuit technology allows these devices to become sufficiently small and inexpensive, so that they can be incorporated into the cable of a small channel hardly larger than the diameter of the cable. The system disclosed m employs these techniques to provide a substantial margin in performance over the variable noise environment that today's networks face. Signal Energy It is unlikely that a practical amount of energy 15 of the signal, be a serious barrier, as demonstrated by the following. To estimate the amount of signal energy required in the electrical or analog aspect of the signaling system for a good communication function, the first factor that must be considered is the minimum internal noise that a system can have. 20 The internal noise energy in excess of the irreducible thermal noise at the input terminals of the receiver, sets the lower limit on any noise level of the system. This measure can be expressed in a way that is independent of the working bandwidth of the system by means of a "Figure 25 Equivalent Input Noise Temperature. "As a good way to quantify this parameter, first measure the noise energy output of the system when it is fed into the input f from a known hot temperature source resistor, then into a second Measurement connects that input with a much known cooler temperature resistor (electrically equivalent) by comparing the resulting ratio of the two output power levels with the known ratio of the noise energy at the sources of the hot and cold resistors , it is allowed to properly account for the contribution made by the internal noise of the system.The thermal noise energy in each of the two test resistors is in direct proportion to its absolute temperatures, being the thermal noise energy of 4 kT, in where k is the Boltzmann constant, and T is the absolute temperature in Kelvin degrees.

The difference between the energy ratio of the known hot / cold source and the measured output of the system is an excellent and accurate measure of how much noise the system adds to the input signal. When viewed in this way, a typical broadband electrical system will have a "noise floor," which 20 is well below a value that is 10 dB more than that of a room temperature source resistor. In real-world work systems, the design of the local connection cable system should only allow the corrupting energy level from EMIR and XTLK to be 25 add relatively little to the noise floor of the system. For example, a very good performance of the cable system in EMIR and XTLK can contain this signal corruption up to a value no ^ fc greater than 10 dB more than the noise floor of the proposed system of +10 dB. The energy required for the signals can be calculated 5 then defining the working bandwidth and the ratio of the signal to the minimum noise of the system: 10 A proportion of the signal to the desired noise can be, for example, of 50 dB, which would provide a very low bit error rate for even the most demanding applications. íJF 20 The bandwidth can be 1 Gigahertz. Then the required energy can be calculated as follows: the total noise energy is the sum of the Noise Cipher, EMIR power, and XTLK. The example value assumed was 20 dB over thermal noise. The environmental thermal noise (4kT) is approximately 1.65 x 10"20 watts per hertz of bandwidth, which is increased 100 times by the assumption of noise. +20 dB, and it is also increased by the bandwidth of the system, so that the total equivalent input energy of the system becomes 1.65 x 10 ~ 20 x 102 x 109 = 1.65 x 0 10 ~ 9 watts . For a signal to noise ratio of 50 dB, the energy of the signal must be raised above this value by 50 dB (105 times = 1.65 10 ~ 4 watts of signal energy). Therefore, the necessary energy of the signal is only 0. 165 milliwatts very moderate (-7.8 dBm). 5 Even assuming that the EMIR and the XTLK have a much higher level of, say, +30 dB (instead of only +10 dB) above the practical noise floor described, the system still f would need only a small energy level of signal, just +12 dBm or approximately 16 milliwatts. This more large but still very modest energy level would require just a 1.3 volt signal through the nominal electrical transmission impedance of the example of the cable of the invention (approximately 100 ohms). These numbers represent a lower energy per unit of bandwidth than the classes of energy levels \ áF signal used in the older analog voice frequency connection circuits, which as a class, have a much poorer system energy efficiency. Older analog systems often used an operating standard of -8 dBm of signal energy (approximately 0.16 milliwatts) in 15 a bandwidth of 10 kilohertz. If this energy efficiency were used so low for the bandwidth of a Gigahertz from the previous example, then the needs of ». Signal energy would jump up to +42 dBm or approximately 16 watts (an energy density of 16 nanowatts per hertz of 0 bandwidth). Even the noisiest digital system example (+30 dB interference) operates with a use thousands of times more effective than the signal power (only 16 picowatts per Hertz). These examples of cable systems did not take into account the losses in the cable system, or any high-frequency response rejection. Some of these unwinding losses will occur and can be easily compensated by raising both the level and the frequency response in the signal transmitter, and correcting the balance of the deficits with a similar rise in the response of the receiver system. As is generally the case, if most of the flat loss and the high frequency unwinding also operate on the corrupting EMIR and XTLK, then these factors will not affect the ratio of the signal to the noise as much. This approach has worked reasonably well in practical systems. In the previous example, a very conservative 50 dB signal-to-noise ratio was used, and the extremely important role that error correction coding would have in producing an adequately low level of signal corruption was not considered. The correction coding of 15 error of the SONET or SDH systems used by most of the world's digital communication systems, would not require a good signal to noise ratio, 30 ^ dB for trivial errors in most applications. Adding to this repertoire of improvements the use of regeneration 20 of digital signals, you can design a performance for a really high level with only a modest use of regenerators. In any good system design, noise immunity will be the greatest limitation. In these examples, there is a lot of room to adjust to any demands of the real system. The question The greatest for the "last mile" cable system is that of the effects of EMIR and XTLK that must effectively solve good designs. It is from these kinds of corruption of signals that the existing external telephone plants ("copper wire pair" cable) develop their 5 fatal limitations, resulting in the obsolescence mentioned above. These older cable systems can not provide enough multilayer broadband signals to the multitude of users, due to excessive problems with XTLK and EMIR. LJF Losses d &; Energy and HFTL If the insulation material used in a cable design is selected from the best modern plastic materials for the frequency range below 1 GHz, the HFTL of small diameter cables is primarily controlled by 15 losses of the cable conductor, which at high frequencies are dominantly the result of the "skin effect" on the drivers. g ^ The skin effect has been known for a long time in the art. The apparent resistance seen by the current 20 alternating that flows over (or inside) a conductor rises substantially above the direct current resistance of the conductor. The description equations show that, for frequencies above a value inversely related to the diameter of this conductor, the effect becomes significant. 25 To cause the current to flow more and more only within a slight depth on the surface of the conductor as the frequency used increases. For drivers of very large size, these effects are apparent even at energy frequencies (50 Hz). The first investigations, 5 that began in the 19th century, were presented due to the unexpectedly high losses found in the large systems of AC power cables. In smaller drivers, the skin effect becomes very significant in the megahertz range. In normal conductive material (eg, copper), most of the current flows only in a thin layer ("skin") of less than a few thousandths of an inch. This approximate thickness is proportional to the reciprocal of the square root of the frequency of the current, thus reducing in depth 15 relative of the skin to one tenth for an increase of 100 in the frequency used. The "depth of the skin" is considered as the depth at which the current has become 1 / e * (approximately 37 percent) of the total current value. For non-magnetic copper conductive material (relative permeability = 1), an engineering formula commonly used to calculate the depth of the skin is: d = 2.6 * f 0.5, where d is 1/1000 inch (thousandth) , and f is the frequency in megahertz (MHz). F d 5 @ 1 MHz 2.6 thousandths; @ 10 MHz, 0.822 thousandths; @ 100 MHz 0.26 thousandths; g @ 1 GHz 0.082 mils The skin effect has been analyzed in 5 different ways, but the analyzes of the prior art share an important fundamental defect. They lack a causal basis, failing to consider an alternating current that starts rapidly from a zero current condition. A different approach, on which some aspects of this invention can be supported, begins by considering the skin effect that is presented to. Starting from a process of propagation of electromagnetic energy into the highly conductive medium of the conductor. An initial current must be propagated to the driver to be able to drive. 15 Therefore, it is necessary to consider the skin effect as a process that is presented by the need for wave propagation, instead of the concepts of almost continuous state that become difficult to rationalize for high frequency phenomena, and especially for the propagation 0 of signals in the cables. (A study reference of the skin effect is: H. B. G. Casimir and J. Ubbink, a three-part document in The Philips Technical Review, 1967, Volume 28, numbers 9, 10, and 12). In an electrical communication cable system, the energy flows through the space in the cable as well, working only with the conductors in the spatial limits of the cable. Seen in this way, drivers operate much more like mirrors than power conductors. This perspective will be described more fully as the construction of the cable system of the invention is detailed below. For mechanical reasons, it is necessary that the space inside the cable is filled with some insulating substance. This substance must also not have a dissipative resistance or switch effect to the flow of electromagnetic energy, or it will produce energy losses or extension of energy over time. These insulating materials (for example, dielectrics) can have high frequency losses, and many materials have them. For example, microwave ovens rely on these losses to heat and cook. There are modern plastic materials available that do not 15 shows a significant loss in the range of interest here (below 1 GHz). The class of available thermoplastics allows for inexpensive manufacturing methods, and they have low dielectric losses to allow the loss image to remain largely the result of 2C resistive losses in the conductor elements of the line. In efforts to minimize the resistance of the skin effect, a technique has been used for the redistribution of the current to many small conductors. By using a large total surface area, it is possible to maintain 25 a practical level of losses when driving high current IjMitfi ^ ditt ----------- frequency. Efforts to do this are exemplified by the development of "Litz" wire, and other similar attempts in the wiring, along with many small strands isolated from each other to form a wire or composite conductor wire. Although at the beginning it is not fully appreciated during the development of these wires, the proximity of one strand to another makes the magnetic field of alternating current of each wire induces a "parasitic current" on the adjacent wires, thus diverting the current of each wire from the regions á! adjacent adjacent of the strands. This "Proximity Effect" greatly increases the apparent resistance of alternating current, so that, at a sufficiently high frequency, the advantages of the Litz construction are finally reversed, becoming poorer than a solid conductor of a diameter 15 comparable total. In other words, a given "Litz" construction can show an improvement over some frequency section, but at a frequency just a few times the center of its range of ^ Improvement, the standard Litz cable will become worse than a single solid wire of the same direct current resistance of the 20 driver. The annular (tubular) conductors made of separate insulated wires minimize the loss of conductive material at high frequencies, but the adjacent conductors that compose them still show some proximity effect. To further combat these problems of proximity, it has been 25 used the transposition of the wires, in such a way that the wires follow a reentrant or spinning pattern that breaks the proximity of each other. These schemes have some value 1 ^ over a limited frequency range. Something better is required for a wide wavelength range. The proximity of one conductor to another becomes a limiting problem as the frequency reaches the range of tens or hundreds of megahertz. Provide Low XTLK - on a Single Cable Two separate cables could be used to reduce the XTLK between the sending and receiving lines, if the lfc protector each line could be sufficient to avoid interaction. Then this puts the XTLK load back on the protector. The protector can never be perfect, and practical limitations will still require a rather heavy and rigid structure, if the objective is a high attenuation of protection. With 15 two cables, this need should be confronted with each of a pair. The overall cost and weight then increase dramatically, and mechanical flexibility is reduced. The present invention avoids the problem by its approach of putting both electric lines within the same cable system (inside the same protector). This new approach unifies the provision of the protection function of the cable system (EMIR), and XTLK, by perfecting the symmetry of the novel quadruple configuration of the invention, and by the novel role of the surrounding "protective type" structure. Then the role of the protector is to maintain the EMIR income to a satisfactory level, benefiting the system disclosed by the exceptional rejection of the income energy due to the balance with which the true orthogonality of the two lines in the quadruple configuration is developed. . The novel cable jacket provides uniformity of the penetrating fields. Proportion of Signal to Noise and Regeneration for Digital Signals The foregoing has shown that S / N can be managed, XTLK, and EMIR in a manner particularly well by the novel features of the cable of this disclosure, as explained in detail below. For digital signals, yet another parameter known in the art improves the operation of the system. With digital signals, it becomes possible to regenerate the signal at some distance down the transmission cable, where the corrupting influences have not been significantly altered for the reliability of the data. This is particularly convenient with simple binary data or no return to zero (NRZ). As discussions have shown with respect to signal energy, for only modest amounts of energy, the ratio of signal to noise can be very substantial. The binary or NRZ tolerate modest amounts of noise, producing trivial data errors. Accordingly, a signal regenerator can be placed in such a way that its threshold accurately reads the center of the so-called "eye" signal. By avoiding long stretches of zeros or ones, the line codes used by SDH / SONET systems, such as B3ZS, easily allow a clock signal to be recovered within this detector system, which also improves the reliability of the detection of the digital signs The placement of this regenerative system at a point at some distance down the length of a cable, completely regenerates the weakened signal, restoring a large proportion of the signal to noise. Having this "fresh start", with much more energy than the attenuated signal at that point, raises the level of the signal well above both the system noise and cross talk (XTLK). This regeneration scheme can be used because, for a proportion of the signal to noise greater than only 20 to 30 dB, error rates can become negligible in practical systems. This capability can be used in both directions of transmission, effectively overriding a large portion of any signal deterioration in cable runs where the corruption is manageably small, because the moderate amount of power is readily available for the new regenerated signal "clean". Designers can choose the point where this restoration is made. Integrated circuits are known in the art, and are available in a suitable operation for the signal rates considered. These devices contain the differential mode threshold trigger detectors (which have some useful hysteresis), and the clock positioning of the decision threshold to synchronize it with the so-called "eye center". A double regenerative system can be manufactured that serves. each of the two lines in a very small package, 5 even considering the need to protect it from static and electrical discharges. This package can be incorporated into the Last Mile cable in a small channel hardly bigger than the cable itself. The conductors in the cable that allow this regeneration operation to be performed Repeatly, even in a long cable run, they can easily transmit the direct current energy required for these regenerative system modules. The use of the electrical conductors of the cable to transmit the energy of the system for other needs of the system, such as maintaining 15 the operational UID, is considered as part of the design function of the last mile cable system. This approach allows the application of this novel A cable to be extended to lengths easily capable of servicing the typical requirements of the last mile, and to provide a 20 system that works without relying on any other source of energy that may not be as reliable as that provided by the network. This requirement of reliability is seen as essential for the high level of continuous use that the system provides to the users of the network. Structure The invention provides the "last mile" connection cable system, equipping users of network communication systems with independent two-way power lines with an equivalent 5 bandwidth performance, as well as providing fiber optics for current and future needs. The quadruple configuration was chosen, because, fundamentally, the two electrical lines can be completely non-interacting. What this demands is simply a very good symmetry. The symmetry is the llfe attribute that has a very important role both in the orthogonality of the two lines (rejection of XTLK), and in the capacity of each of the lines to reject electromagnetic interference. Figures 5 and 6 show, in cross section, a 15 general form that this quad four-conductor configuration could take. In Figure 5, substantially exact electrical positions must be reached for each of four conductors 71, 73, 75, 77, and if a conductor is F "protective" surrounding 79, and is uniform in its properties 20 electromagnetic around the circumference (on the frequencies of interest), then the two pairs will be precisely in a nullity of induction from one to the other. Because it is the electromagnetic fields of each of the pairs that are of interest, the degree of balance or symmetry achieved can 25 to be evaluated by measuring the capacitance from each conductor to the protector and to each of the other conductors. The degree of coupling is a measure of the "balance" or inductive symmetry f as well as capacitive of this set. Then the cross talk is sufficiently small, and each of the two pairs can be operated in a manner substantially independent of the other. This aspect is what attracts our attention for the broadband system of two tracks and two lines. The method by which this symmetry is achieved includes a specially molded positioner as disclosed below. FIG. 6 shows in greater detail a cross-sectional view of a quadruple annular hybrid cable. The four conductors 71, 73, 75, and 77 are shown as in Figure 5. The surrounding protective conductor 79 is also shown, symmetrical with the four conductors. Figure 6 shows the 15 damper channels 81, 83, 85, and 87 that can support one or more optical fibers. An annular conductor support locator or insulator 89 provides the structure through which conductors 71, 73, 75, and 77 pass. The construction of the F positioner 89 is described below. A filler gel 91 surrounding each buffer channel 81 may be employed. Types of filler gels that may be suitable include superabsorbent compounds, such as petroleum-based gels. These compounds serve at least two purposes. One is to keep the glass fibers 25 contained in them so they are not corroded by air.

Another purpose is to provide lubrication to pull the wires through the cable. (A Other advantages are accumulated with the addition of a twist to the quadruple internal structure of the conductor, such that the lines along the insulation and central positioning structure and the conductors form a helix going down the length of the cable , say, one to two turns per foot of cable length.This configuration has the useful property that when properly fed from {? a balanced source, and ends in a balanced receiver, any fields that penetrate uniformly to the internal conductors will not cause a net current flow in any pair The use of twisted pairs is known, however, the advantage for the helical configuration of the invention is that the EMIR of the invention is improved to the same extent as Therefore, in the cable system of the invention, the reduction of XTLK also reduces the unwanted noise input of the pollution. The electromagnetic phenomenon is ubiquitous in modern environments. The function of the "protector" in the configuration of the invention is not only to attenuate the interference energy, but also to symmetrize the electromagnetic transmission of the input fields by distributing the energy leaked symmetrically towards the well-balanced interior quad structure. 5 The balance of the quadruple rejects a lot the energy that it crosses. The term "protector", as used herein, refers to the behavior of the circumferential structure, and not to the common use that simply implies an energy barrier. These barriers are always imperfect, and some energy is always permeated. This approach to symmetrising the shield to improve EMIR is a novel method to end the currently increasing levels of EMI that are difficult to handle otherwise. The degree of this rejection made possible by the precision structure of the present invention, has not been achieved by the prior art known to the inventors, which sought a substantial rejection of interference, even after making extensive use of rather heavy protectors. in your cable designs. Internal Symmetrizer Design 5 The invention uses an internal symmetrizer that surrounds the quad cable. Of course, one skilled in the art recognizes that the quad cable is not required by itself. The structures disclosed as surrounding the cables can be used for dual quad cables, coaxial cables, or the like. The structure of the internal symmetrizer is shown in cross section in Figure 7 in a modality for a local connection cable system, and can be used in a similar manner in all other example drawings. The design of Figure 7 creates a high degree of symmetry in attenuated electromagnetic fields that manage to penetrate into the cable, thereby developing a substantially increased rejection over what would previously be done by a brute force protector, and without the symmetry of the drivers. Example 1 Figure 7 shows a schematic cross-section of an internal symmetrizer seen through a section of the cable wall, as it is located in the dotted section shown in Figure 6. The layers are described starting from the layer closest to conductors 71, 73, 75, and 77. The function of each of these layers is described by following this short reference list. Of course, the following list is merely an example. In fact, it is highly specific, and variations of these materials can be employed without departing from the spirit and scope of the invention.

F The composite sleeve can add approximately 0.210 inches to the diameter of the basic quad DO (without the optional external corrugated vapor barrier). This produces an overall diameter of approximately 5/8 inch for a quadruple using a quadruple tubular annular conductor with a finished diameter of 0.042", that does not require the vapor barrier to protect the optical fibers that the conductors may contain. The constituent layers are described further below. The aluminum foil material 101 can be backed by a suitable plastic carrier which can be 5"Mylar" or some other durable material known in the art, suitable for the temperature range, and preferably substantially non-hygroscopic. The sheet wraps in pairs would wrap in opposite directions, each shell wrapping completely metal with metal for about half a turn, and bending once upon itself. Each of the two different layers in pairs (101 and 105) may require a slightly different spiral of the shell to realize the proper bending properties. Layers 101 and 105, of course, can be replaced with alternative forms of conductive materials. The colloidal carbon or secondary artificial carbon powder material 102 is available from Asbury Graphite 5 Mills, Asbury, New Jersey, United States, in a particle size less than 325 mesh or finer, which is sufficiently small to allow a complete mixing of the materials with the selected binder before processing it as a cover for the cable. The direct current resistivity l (| P surface of the mixture in the solidified binder must be less than 500 ohms per square.) Other materials that can be used for this layer include materials with similar conductive properties. appropriate 15 103 is available from OMG America, Research Triangle Park, North Carolina, United States. The purest and finest particle size currently offered is K291A, and is suitable for F this use. In all cases, a uniform and complete mixture with the binder is essential. Flexible urethane materials 20 are available in a variety of sources, for example, a wide variety that is offered by B.F Goodrich Company. Other materials that can be used for this layer include materials with similar magnetic properties. The High Frequency Ni-Zn Ferrite Material 104 25 is produced by crushing "ball mi11ing" and then milling in a ball mill of the material in several steps to produce an average particle such that 98 percent by weight of the resulting particles are classified in a size smaller than 5 microns. Suitable materials can have adequate complex permeability for the frequency range of 100 MHz to 1000 MHz. Materials manufactured by Milled Philips Ferroxcube type 4 can be satisfactory for this purpose. It is important to consider the anisotropy in the permissiveness of the high frequency material that results from the strong magnetizing field in the range of 0.25 to 0.60 Tesla. Other materials that can be used for this purpose include materials with similar magnetic properties, for example remanence, permissiveness, and permeability. The stainless steel braid 106 can be selected from the materials in the thread thickness of 4 to 6 thousandths which exhibit a high tensile strength and low drag for the typical stress levels in the use of the suspended cable outdoors. Other materials that can be used for this purpose include materials with a high tensile strength. The outer sleeve 108 may be of extruded hard polyurethane material in a typical thickness of 32 to 40 thousandths. Other materials that can be used for this purpose include materials with similar strength properties.

The layers of Figure 7 distribute the penetrating fields inside the cable, in such a way that they produce a balanced effect on the signal lines. Layer 101 of this non-limiting example of the art is present for several reasons. First, it acts as a field mirror for the internal fields of the quadruple signal pairs. The layer 101 also operates on the external penetrating fields, by presenting a short circuit of the conductive field to the penetrating fields, from the layer 102, in such a way that the surface current Im becomes more evenly distributed as it leaves the layer 102. The layer 102 has a relatively high strength compared to the aluminum metal surface of the layer 101, which creates a large extension effect on the next field from the relatively loose and resistive material of the 15 layer 102. The EM wave velocity is relatively high in the material of layer 102, and is made to a thickness that allows significant redistribution of the field. The layer 102 is attached to F a layer region 103 above which it has a relatively high permeability (from 5 to 50 within the frequency range of 20 interest), and an average conductivity that has a rather low EM wave velocity. The connection with the layer 102 creates an additional extension effect. The previous layer, layer 104, is selected to have a relatively high permeability in the high frequency region (50-500 MHz), where its EM speed will be 25 very low. As a consequence, the layer 104 is a little thicker than the layer 103. The layer 104 has a significant difference in EM velocity at the boundary with the layer 103, and therefore, the extent of the field is improved. The layer 105 is a thin layer of high conductivity that produces the typical field current short 5 as a "protector", but its primary value is in the magnetic coupling with the sublayers for the benefits described, because it will only have a small protective effect against external fields. The traction layer 106 is for the strength, while at the same time providing \ mf some capture of electrical current in the braid. The layer 107 (not shown) can also be used instead. The vapor barrier properties of stainless steel also provide a protective effect and some traction benefits. The outer jacket 108 is for protection from the weather and 15 other environmental protection and management. Each of the above layers can be varied, or another combination of layers can be used. The principles of ^ variation of EM properties in abrupt junctions with different EM propagation, effect a symmetry effect Significant that is a desired characteristic. Attenuation by itself is not a primary objective of the constructions described. To evaluate the possible constructions, a relatively refined quadruple helical line of the type described above can be constructed and, using it as a test device, to compare the contributions to balanced signal transmission through the cable with and without a possible f symmetrizing coating of the type described. The differences reflect the relative advantages of the properties of 5"collimation" or of symmetry. External Impedance Coupling Housing A second form of external covering develops some rather different properties of the classical protective element for the purpose of reducing type collection. \ áF effective electromagnetic energy antenna that will exhibit any conductive line established in a typical outdoor environment. Because it is impossible to make a physically "protective" workable that is not penetrable by electromagnetic fields, the inventors found another way 15 to achieve the reduction in vulnerability to this electromagnetic interference. The symmetry and balance characteristics of the present cable system design have already been discussed. He ^ Second approach allows a different factor to be used. The space itself has a characteristic impedance 2C that characterizes the propagation of the electromagnetic field. The resistive component of this radiation impedance is approximately 377 ohms, a value derived from the ratio of space permissiveness to space permeability (or space inductance and capacitance). If the The surface of a cable to exhibit a resistance to an electromagnetic field in propagation that had the same value as that of the same space when it was not occupied, then the cable would produce an antenna effect of a much smaller area, and in this way it would absorb much less energy than a good uncoupled conductor of the same length as this cable. The action of the cable as an antenna would be substantially smaller, collecting only due to the energy flowing through little more than its optically apparent projected area. In fact, it would appear almost invisible to a radiant electromagnetic field. For whatever you can design the internal layers of the system, shirt, if this effect is present, the protective effect of other of these internal layers will be greatly improved. This design for an apparent superficial or external resistance that is coupled with the radiation of the space is made using a 15 external impedance coupling housing according to the invention, and is shown in Figure 8. Referring to Figure 8, a cable 301 with a quadruple conductor configuration 303 is shown. An external impedance coupling housing is incorporated. 305 surrounding quadruple conductor 0 303. This external housing has an apparent radiation resistance that couples with the radiation characteristics of the space, and can be realized for a reasonably wide range of frequencies using dissipative loads in a polyurethane jacket material. The loading with a mixture of particles of 5 carbon of artificial graphite, such as the Asbury Graphite Mills A99 material (cited above) (or finer size grades), and the metal poles such as the atomized pure nickel f powder from OMG Americas (cited above) AN325 (or finer grades) of ASTM class NO2200, can provide 5 the required radiation dissipation properties. In the selection of the materials and combinations for the desired effects in the dissipative resistive coupling with the space of the surface properties of the external housing of impedance coupling, two aspects must be considered. First, there is a method by which the performance of the material and the construction can be evaluated to minimize the impact of the radiant electromagnetic field found by the material. This is a way in which you can choose the appropriate materials. By using an anechoic room 5 for radiofrequency fields in the frequency range of interest, relatively flat wave radio frequency fields can be launched towards a non-reflecting wall. Then a directional radio frequency receiver can be configured to observe the amount of reflected energy returning from this wall. Pulse emission and detection can be used to minimize the energy returned as a parasite. By placing a metallic conductor object of the same profile as the cable to be evaluated on the same wall, its reflection can be recorded. This test part is removed, and the cable with the material covering to be evaluated is placed where the test piece was. Then the measurement is repeated. The values thus obtained give a relative measure of the degree to which the test material approaches a good coupling with the space. Using this method or another, you can try other 5 forms of carbon materials or similar that can be used. For example, some of the natural flake or mine flake graphite may be appropriate, and / or in combination with other conductive particles or fibers of different metals, for example with or without very small particles or stainless steel fibers. There is a wide range of materials that can be effective in this way, in particular, materials that closely approximate a coupling with space properties, to minimize the "gathering" of radiant EM fields for the range of frequencies of interest . 15 A well-known test method for evaluating the ability of a cable not to transfer energy from external fields to its signal line is the established "surface transfer impedance" measurement defined in the United States military specification. MIL- 0 C-85485A, heading 4.7, and collaborators. However, this test does not carry out its objective (to define the effects of income) when confronted with the balanced quadruple configuration. The test is not even completely adequate in its primary domain of coaxial systems. The concept, if applied appropriately to the structures of the present invention, would possibly show extraordinarily low values of energy transfer as a result of the contribution f made by the rejection of balance that is well beyond the energy attenuation of the protector itself. For a reference to 5 the test problems of this MIL specification, and other test problems and issues of cable design and measurement, see the following two references: "Introduction to Electromagnetic Compatibility" by Clayton R. Paul (1992, John Wiley &Sons, Inc., New York) chapters 10, 11, pages 491-666; "Cable ] É¡f Shielding for Electromagnetic Compatibility "by Anatoly Tsaliovich, (1995, by Van Nostrand Reinhold), in particular chapter 3"The internal layers of the protector surrounding the quadruple configuration serve still another purpose 15 act as an electromagnetic mirror to confine the internal fields of the quad conductors, thus preventing the loss of signal energy. As an additional benefit, • the conductor structure also reduces the loss of energy I of the signal by virtue of its more confined propagation. Referring back to Figure 7, the conductive layer 101 near the outer surface of the quadruple dielectric positioner 89 is designed to minimize this loss. This surface is better proportioned, in such a way that the space between it and the quadruple conductors is substantial in relation to the separation of the conductor pairs, helping to preserve the precision symmetry, and minimizing the influence of the protector ("mirror"). "). This would be such a diameter f f times much greater ttwice the space between a conductor pair. (See Bell System Technical Journal, volume 15, number 2, pages 5 248-283, Estel I. Green, F.A. Leibe and H.E. Curtis). To preserve the inherent value of the quad, the source and termination devices are also important. Any significant alteration of the intrinsic balance of the cable at these ends produces increases in the input of undesired energy JJ, and additionally adds to the internal crossover between the pairs. Some examples of novel balanced to unbalanced couplers ("baluns") and baluns of cable impulse circuits, are shown in Figures 9 and 10, and form an important part of the regenerators, the NIDs, and 15 the UIDs, as shown in the diagrams of the systems of Figures 1 to 4. They are also discussed in the section on Impulse and Termination for a Good Balance. Another contribution of the invention to the achievement of F the precision in electromagnetic structural geometry is 20 presents the conductor positioning structure as shown in Figure 11. Efforts to extrude a quad with the four conductors in place have shown that they suffer from significant variability, even when exerting extreme effort to control the process. The Canadian patent No. 788,603, issued on June 25, 1968 to Eyraud and Delorme de Compagnie General d'Electricite, Paris, France, endeavored to create good symmetry by meccally grinding four helical grooves into a continuous cylindrical "stem", which included a thermoplastic dielectric (presumably extruded), 5 centrally reinforced by a fiberglass cable, and subsequently placing the conductors in the four ground grooves. This patent shows the spiral of the slots to provide the desired helical rotation of the quadruple orientation. This assembly was then covered with a suitable additional insulating dielectric lamp, protected, and externally sheathed. The material of the plastic "stem" and its processing, probably by extrusion to a form suitable for machining, were not discussed. It has been well known in the field that normally 15 considerable stresses are present in the material formed in this way. The machination releases these tensions, resulting in a significant relaxation traction. This affects the precision of the resulting machined "stem", both initially F as increasingly through time, both for the release 20 for aging in the field, as per the daily temperature cycle experienced by outdoor cable systems. Eyraud's patent approach, apart from any limitations of its method to create the "stem", simply precedes a different group of problems of 25 precision that come from the placement of your wire "stem" in some dielectric and surrounding protector, because any errors in doing this, will also result in an imbalance in the resulting system. The patent did not disclose the way to carry out this last phase of manufacturing. The present invention eliminates these problems by providing a precision positioning and isolation structure, as shown in Figure 11, which ensures the arrangement of conductor 71, 73, 75, and 77 at a precise position within a final electromagnetic shape. locked In one form, the positioner 89 is fabricated as four linked longitudinal sections using an especially high stability extrusion process disclosed below under Extrusion Methods. This process ensures that the already manufactured forms of the four parts remain identical and stable, 5 not only during manufacture, but subsequently during prolonged use and during aging in the field. The method of the invention releases the stresses normally associated with the pressure and temperature gradients present in conventional extrusion methods (even when a mixture is used, as with the screw plasticizing elements). The lifetime performance of the cable system of the present invention can be, either indoors or outdoors, still greater than 100 years. The selected modern materials, together with the manufacturing methods of the invention, make this desirable objective economically achievable. In several preferred forms, these novel insulating and positioning parts are inter-secured around precise annular signal conductors also in a special way disclosed further below. Figures 11 to 16 further illustrate some examples of the general form of these four locating parts. These figures illustrate the way in which a typical inter-assurance set of projections and recesses can be configured to capture \ áF and maintain the relative locations of the elements of a positioning structure of the four quad conductors. Referring to Figure 11, the positioner 89 is shown in four separate sections. These sections are numbered 305, 307, 309, and 311. Each of the sections has 15 generally forms an L shape, and includes a male member 313 that fits into the slot 315. These elements are further shown in Figure 12. Figure 12 further shows a number of points of A 317 articulation, which allows the sections to be extruded in a convenient manner. Once the extrusion is formed as in 20 Figure 12, each section can be rotated with respect to its attached sections in order to form the complete positioner 8 '. Figure 13 shows a more detailed view of the molded joint 317. As can be seen, a 25 extrusion of four sections, usually three joints or joints 317b. The sections can be rotated in order to form the complete positioner 89 ', or they can be separated at the articulation points before this formation. Figure 14 shows the mode where they are separated. Figure 14 also shows the male member 313 of each positioner in a position to enter the slot 315. This situation is shown in greater detail in Figure 15. In particular, Figure 15 shows an example of a possible safety configuration lamp. instant. An annular ring around the male member 313 fits into a corresponding section of the slot 315 to more securely hold the sections of the positioner 89 'together. The perimeter can be in any convenient way 15 as in Figure 16, where it is circular. Figure 16 also shows the optional perimeter grooves 319 for containing fibers or other conductors. In an alternative form of this structure, the slots 319 may not be present, the F perimeter only some circularly symmetric surface. In this example of structure, any fibers or conductors different from the four quad conductors, may be entirely inside the interiors of the four quad conductors. Returning to Figure 6, sufficient space 25 is shown to install fiber optic lines in the interstices or buffer channels 81, 83, 85, and 87 of the positioner. In addition, the shape of the positioner 89 'can be formed to accommodate f any desired cable shape. The positioning and the dielectric properties of these four regions, however, must preserve the internal electrical symmetry of the quadruple. The four regions must be uniform in their electrical behavior, even when that aspect has nothing to do with their function as fiber optic fasteners. The inventors have also found yet another \ á way to include optical fiber in the new quad structure. As indicated in Figure 11, the cores 90 of the four annular conductors 71 ', 73', 75 ', and 77' can be used to contain the fibers 321 in each or any combination without altering the electrical balance. For example, you can Provide 1 to 16 or more fibers inside each of the four annular conductors, allowing electrical performance to be independent of the dielectric properties of the A fiber. This advantage is considerable, because the desired helical twisting of the quad arrangement (a non-limiting example) 20 uses approximately two turns up to the foot) will also provide a significant margin for the elastic release of the fiber, freeing it from thermal expansion, movement or mechanical stress from the movements of the cable. The helix suggested in the examples requires a length of approximately 110 percent of the conductor and fiber inside the cable in relation to its total length of the outer cable. Figure 17 shows, in cross-section, a possible type of annular conductor of the invention, exemplified herein as 71 ', whose central region 92 allows the fibers to be installed during manufacture, or even to be blown in place subsequently, after a cable is installed. One way in which the fibers can be installed after the cable is extended, includes the fiber blowing technique. In this technique, a mushroom-shaped device is attached to the end \ á of the fiber, and the tip of the fiber is placed inside a cable. A so of high-pressure air is coupled to the mushroom-shaped device, pulling the fiber through the cable. Other techniques, which are known in the art, can also be employed. Figure 17 shows a section Cross section of an example of this annular conductor of innovative design. The central annular support sleeve 49 only needs to be of a thickness such that it adequately supports the special electric conductor braided and spun 110. The surface F of the inner conduit of the fiber 94 may be of a material of 20 low friction, such as one of the fluoropolymers. This allows a wide range of possible choices to accommodate the optical fibers. The structure of each of the, for example, 36 individual wires that can be used in this example, is derived from a new approach to minimize the effect of 25 skin, and of the proximity losses found in the configurations of multiple stranded wire conductors. The discussion of the skin effect was previously introduced in the section entitled Energy Losses and HFTL. In the consideration of the behavior of the electromagnetic waves that propagate towards a conductive medium, the group velocity of the real physical energy moving into the material becomes notoriously small, considering that it is an effect of the electric field. This speed is only a very tiny fraction of the speed of light that propagates in free space. For example, for the conditions that describe the skin effect data for copper, given above, this group speed is 47 meters / second at 1 MHz, and it rises to only 470 meters / second at 100 MHz. space and shape of the annular conductor can be selected to suit the requirements 15 of the fibers without compromising the qualities of the annular conductor. Over time, optical fibers may be susceptible to damage by water vapor corrosion. HE A can use super-absorbent compounds to fill the space around the plastic-coated optical fibers 20 inside the central region 92 that carries them. These materials absorb and immobilize the little water that enters the cable structure relatively resistant to otherwise well-enclosed water. The outer sheath 94 of this cable must also be relatively impermeable to water. Figure 18 shows an annular conductor using one embodiment of the structure of the invention to improve the performance of the 36 strands (shown as ends in the figure)? F of the wire of magnetic material size 39, with 50 percent of copper coated conduit as described below in relation to Figure 12. Each wire of the 36 strands, as shown in Figure 18, has a first conducting layer of copper material 353 overlying a steel tensile core 351 This is followed by a matrix of high frequency magnetic material 355 that has a high degree of anisotropy of lj | permissiveness, as described below, and furthermore it is coated with a fluoropolymer 357 insulation. To form the annular conductor, these wires are spun into a 2 x 18 spun trough by filling the surrounding portion of the 0.042 inch OD hollow sheath. , which is adequate to contain the fibers 15 optics or other drivers. The braid is a tight yarn to tightly contain the external design diameter up to the value necessary to maintain the design impedance value ^ fe, nominal. Still another form of annular conductor, shown in Figure 19 is inherently water vapor proof by virtue of a solid metallic tube 102, which still gives better protection for its enclosed optical fibers. In Figure 19, a central region 96 for the fibers is shown. The wall surrounding this region should be thick enough to 25 to withstand the bending and resistance found in the magnetic field. Surrounding this region is the layer 98, formed of a tubular magnetic material, this layer providing an annular support for the optical fibers Finally, a coating 102 is placed on the layer 98. The coating 102 may have three layers, As shown in Figure 20. The first coating 104 is formed of a conductive layer In this example, the first coating 104 can be copper about 28 microns thick A second layer 106 of a magnetic matrix is provided, which has In this example, the second layer 106 is about 10 to 20 microns thick.A third layer 108 of a dielectric coating can be formed, in this example being 4 to 8 microns thick. A schematic description of these layers is shown .. 5 Annular Conductors The annular conductors of this disclosure have elements and structure that complement the different functions that these four conductors in the invention. Annular conductors can be chosen according to 0 specific criteria. Suitable annular conductors can perform at least some of these six functions: 1. Bring the two signal lines with an acceptable high-frequency spread. 2. Bring power to online regenerators, UID peripherals, and related devices, and optionally allow the flow of POTS signals. 3. Maintain accuracy and balance in the broadband characteristic propagation impedance of each pair. 4. Maintain signal losses up to a manageable level 5, particularly at high frequencies. 5. Act as a protective conduit for the optical fibers necessary for present and future applications. 6. Provide additional strength and stability for the quadruple assembly, in order to help preserve the geometry for low XTLK and high EMIR. Figure 21 shows a cross-section of this individual wire class as discussed above with respect to Figure 18. Its design differs from the prior art in a number of significant ways that the 15 less well-known properties of wave propagation effects in and on conductive media. These aspects of the invention have the objective of improving the performance of the ^ h. elements that carry signals, and assist in the rejection of unwanted external electromagnetic energy, by altering both of: a) the skin effect properties of individual conductors; and b) substantially modifying the interactions of the proximity effect of a conductor on an adjacent conductor.

A modification of the propagation of the energy of the electromagnetic signal in the structure of the conductor f is made in an asymmetric manner which encourages propagation along the length of the conductor, and improves penetration into the conductive elements. These conductors have at least some of the following main characteristics: 1. They employ a core wire of ferromagnetic material 351 of a very high strength which has been selected from among materials which also have a significant magnetic remanence when magnetized axially. 2. A high conductivity metal coating 353 is applied to the surface of a wire core. In the illustrated case of Figure 21, the current resistance 15 direct selected for the finished wire coated with copper is 50 percent of the conductance of an equal diameter (coated) made entirely of copper. With the copper used as the conductive material, only a thin layer of copper is required over the ferromagnetic material. 3. This conductive layer is further covered with a thin coating of a high frequency magnetic material 355, which has a moderate permeability, which also exhibits the following other properties. This coating material 355 is selected from among materials and methods for forming such So that when they are in place on the coating wire, both their permeability (μr) and their permissiveness (er) are substantially altered by the resistance and by the direction of a practical value of a polarizing magnetic field. When the wire is magnetized, the spatial anisotropy results in 5 values of μr as of er. For a given application and for the frequency range of interest, the magnetic material is further selected to have a desired appropriate variation of permeability with the frequency over that range, and a desired limited amount of energy dissipation losses. 1. 4. The magnetic coating 355 can be a mixture of very fine particulate material (eg, including a nano-phase) with a matrix binder that is selected to allow the permeability and permeability to be oriented substantially permanent and remain 15 aligned by a magnetic field during the manufacture of the composite wire, in such a way that a substantial and desired spatial anisotropy is produced in both parameters (μ ^ and e). This provides magnetic permeability in the circumferential region around the conductor, which is substantially 20 different from the axial direction, and in the same way, a related anisotropy in the circumferential and axial permisivities. This can be done by making the mixture of magnetic materials and a binder in an almost fluid or semi-solid form that solidifies during the manufacturing process, 25 while still under the influence of an applied magnetic field of adequate proportions. The magnetic material can be one of the high-frequency ferrite class, such as one of the Philips Ferroxcube type 4 nickel-zinc materials, crushed after 5 ignites, and then finely ground, to a particle size of 98. percent in weight, and that are less than 5 microns. It has further been found that it is desirable for the polarizing magnetic field to be applied in such a way that the polarity of the field is inverted in a manner that causes the anisotropy to be continuously present down the length of the wire, but reversing the remaining magnetization of the core. of ferromagnetic material wire and the related polarization of the magnetic molecules in a spatial manner periodically 15 going down the length of the wire. The spatial periodicity is selected in relation to the demagnetizing effects in the wire core of ferromagnetic material, and also g ^ with the wavelength of the highest frequency spectrum to be transmitted in the cable system, and the properties of 20 propagation desired for that spectrum. The structure and functioning of this anisotropic system differs fundamentally from previous systems. There are numerous examples where magnetic materials have been used to simply "charge" the conductive lines of 25 signals as in the efforts of the past to increase the inductance of the line, thus raising its propagation impedance, and to thereby reduce the signal loss, and to correct the frequency response drop. A few examples of United States patents thereof are: U.S. Patent No. 1,586,887, to Elmen, "Inductive Loading Signaling Conductors," U.S. Patent No. 1,672,979, to Fondiller, " Loaded Driver "; U.S. Patent No. 2,669,603, to Prache, "Transmission Line With Magnetic Loading"; United States Patent No.

IÉF 2,787, 656, to Raisbeck; U.S. Patent No. 4,079,192, to Josse, "Driver For Reducing Leakage At High Frequencies", and in a different class of effects are: U.S. Patent No. 3,668,574, to Barlow, "Hybrid Mode Electric Transmission Line Using Accentuated Asymmetrical 15 Dual Surface Waves; "U.S. Patent No. 4,017,344, to Lorber et al," Magnetically Enhanced Coaxial Cable With Improved Time Delay Characteristics "; ^^ U.S. Patent No. 5,574,260, to Broomall et al, "Composite Conductor Having Improved High 20 Frequeney Signal Transmission Characteristics. "Elmen and Prache are examples of inductive load equivalent to the inductor effects in groups on the line.Prache was one of the first to develop the analysis of the dielectric effects of the magnetic material on the impedance of the charged cable. 25 Raisbeck '656, issued on April 2, 1957, performed this analysis by incorporating all losses, including dielectric losses overlooked by Prache. Raisbeck's analysis was further expounded in his article in the Bell System Technical Journal in the March 1958 edition 5 (pages 361-374). The emphasis of these workers was to minimize the transmission losses for a given size (mainly in the types of coaxial lines). They did not try to directly alter the effects, such as skin or proximity. Fondiller '979, issued on June 12, 1928, ) EF describes the coating of a wire with a magnetic material in an extrusion method, which also magnetizes by sending a "strong direct current" down the wire. The coating material described was iron powder in a binder. The patent explains that the magnetization of direct current is 15 performed to raise the permeability of the coating, and in this way increase the inductance per unit length following the established approach of the losses that were ^^ reduced by raising the impedance level of a transmission line. No asymmetry properties were reported 20 other magnetic or dielectric effects. Josse discloses the coating of the wire with a magnetic material mainly to reduce the losses by the eddy currents in the adjacent wires, applying this principle to the applications of the Litz wire. As well 25 applies the process to superconducting cables and frequency line applications of high current power, apparently being the focus there on the effects of parasitic f currents. The last group of three patents (Barlow, Lorber and 5 collaborators, and Broomall et al.) is different. All describe the experimental results that are not easily explained by the classical theory of transmission line and driver. All cite the experimental data that shows non-classical behavior. Only Barlow develops a theory of surface wave properties that affect the propagation of the wave. Lorber observes an abnormally low time delay in its structure, but proposes an elevation in the effective inductance, in series with the cable derivation capacitance, to explain it. In other portions of its disclosure, it is suggested 15 a "waveguide" effect, which contributes to the observed behavior. Lorber also cites the Kehler and Coren document 1970 (See Kehler et al., Susceptibility &Ripple Studies ^ in Cylindrical Films, J. of Appl. Phy., Volume 41, number 3 (March 1, 1970) pages 1346, 1347), which shows evidence 20 of a non-classical 110 MHz propagation effect in a short section of a magnetically coated thin wire used as a central conductor in a coaxial structure. Broomall and collaborators develop their explanations of the anomalous propagation effects purely in terms of the 25 behavior of the skin effect. Their structures differ from Lorber in that a magnetic substrate is used for their basic structure, although they also give suggestions of three-layer structures that place the magnetic material in the middle layer. The example they give shows only a moderate improvement in the 5 behavior of loss and delay, and no suggestion is made of having a process dominated by propagation. It is not clear from his teaching how to optimize his method for other materials and dimensions. Consequently, Barlow remains the only one of these l | examples that propose a direct effect on the process of wave propagation. As described above, the skin effect can be treated more effectively as a propagation effect within the highly conductive and / or permeable medium of the kinds of elements employed by these patents. Barlow 15 recognizes the lack of an analytical mathematical treatment in its description. It relates a family of experiments that it finds as demonstrations in a novel way of propagation that ^ fc names modes that are not TEM. It uses a dielectric layer to develop novel modes, and gives a wide range of 20 thicknesses to be deployed covering the frequency range from 1 MHz to 10 GHz. These documents and the curve given in the patent show a substantial alteration in the attenuation as a function of the added thin dielectric layer. It is possible that the three patents are better understood in 25 terms of energy trapping behavior that alters the propagation of energy. None of this prior art cited solves the effects of propagation that the invention solves, nor teach the development and influence of the anisotropies of union in the permissiveness and in the permeability. The ferrite type materials described above are only one example of the possible materials that have micro-structural properties, so that, under the influence of a magnetic field of a moderate value (less than 1 Tesla), their lflft electromagnetic properties (dielectric and magnetic) with respect to the intensity and direction of the magnetic field. Other crystalline, semi-crystalline, or even slightly amorphous substances may exhibit properties of internal ordering that develop comparable anisotropies. The invention uses in 15 part these effects to achieve the improvement of the propagation properties resulting from the unusual spatial distribution of these properties. A 5. The composite wire can be further coated with an insulating outer layer 357. Then the insulated construction 20 completes the separation of the component composite wires into a spun or spirally wrapped annular conductor configured on a support core, as shown in Figure 17. An Alternative Modality of the Annular Conductor Figure 19 illustrates still another embodiment not 25 limiting an annular conductor that can be used for the quad cable. Referring first to Figure 20, this hollow core annular conductor can be formed as a single tube of magnetic material 98, coated with a conductive (metallic) layer 104, followed by a layer of thin magnetic matrix 5 106, and coated with a very thin insulating layer 108. This structure resembles the layered structure of the individual wires described above. For many applications, this unitized tubular magnetic core shape is convenient. For example, it allows each of the four annular mF conductors to enclose the optical fibers in a vapor barrier barrier tube without requiring the entire cable to be completely vapor proof. This tube also provides the opportunity to increase the diameter of the available central void space for the optical fibers and the super-absorbent protective filler.

The remanence in the magnetizable tube, the scale of the conductive layer, and the anisotropic properties of the matrix layer, can be adjusted to provide low effective loss and uniform propagation behavior, resulting in substantially the same or a potentially better performance 0 than the spun wire form described above. This simplifies cable construction and reduces costs, producing a lighter and slightly smaller cable. This exemplary tensile strength member of the cable would possibly be a corrosion resistant high strength braid incorporated in the cable just below the outer jacket covering. The outer cover layers must employ the EMI symmetrizer and the outer impedance coupling layer must have a resistive spatial impedance design, both as described above. These annular conductors have at least the following unique and novel properties, and differ in many fundamental ways from the prior art known to the inventors. The magnetically "loaded" structures and prior art systems have generally focused on F simply raising the impedance level of a transmission line that propagates electromagnetic energy in relation to the loose behavior of the conductor systems used to launch and transmit energy. In this strategy, the magnitude of the resistance of these losses of the driver arrives 15 to be a smaller part of the impedance of the transmission system, thereby reducing the portion of energy lost for that cause. These efforts do not materially affect ^^ the propagation properties, nor reduce the resistance of the skin effect that dominates the AC resistance of the 20 driver - especially at a high frequency. These approaches have the disadvantage that they reduce the bandwidth available as the price paid for this loss reduction. A few exceptions have dealt with the parasitic currents and the proximity effects discussed above. 25 Most of this technique has been in power transmission applications with narrow or fixed band frequency strategies that are neither applicable nor suitable for the transmission of broadband signal energy. (See U.S. Patent Nos. 3,160,702, Lapsley, and 5 3,594,492, Bader). On the other hand, the present invention modifies the skin effect on the conductor, and alters the manner of propagation of energy along the path of the transmission line. This approach does not need to raise the impedance of the structure to perform the improvement, and the bandwidth is not compromised. A prudent choice of driver configuration requires that other objectives be served along with maintaining the transmission energy losses appropriate for the needs of any given application. This balance of choices is exemplified by the objectives of the advanced quadruple structure system that weigh the ratio of signal to noise well, thus emphasizing high performance in the behavior of XTLK and EMIR. These features together make possible the necessary network performance to meet the needs of the last mile cable system. Propagation Soliton Under some conditions, the propagation within the object cable exhibits very low energy dispersion properties of a type related to the Soliton propagation properties that were first observed in the mid-nineteenth century (1834 by Russell JS) as a notorious class of k wave of water that goes far created by a boat towed in a scotland canal. Others, after Russell, explored the 5 phenomena mathematically, developing Korteweg and deVries an important basic descriptive equation (1895). Fermi and others explored the mathematics of these wave systems in 1955, but the biggest step came when Zabusky and Kruskal took the deeper analysis, coining the term "Soliton" to describe the EF properties of coherent group type of these wave phenomena. Most of the mathematical and practical work on the matter has come to approximately 30+ years since then. Soliton propagation has been applied to fiber optic systems with desirable improvements obtained in their optical modality. The 5 optical fibers that are currently used employ soliton techniques. The novel anisotropic nature of the electromagnetic propagation conditions according to the invention allows the use of spatial propagation non-linearities (that is, by varying μ and e in a relatively abrupt manner and also in a spatially periodic manner) to launch and receive energy in the soliton type mode, which has very low dispersion, and therefore, very good fidelity of the waveform at high speed. The soliton propagation presents 5 advantages of lower energy loss, longer stretches, and larger effective signal bandwidth due to the character of the velocity of the soliton group to carry the energy of f signals over a considerable distance, while it conserves both its energy and its form in space and time. The source of signals and the charge coupling element to do this can be a bit more complex and expensive, but it can possibly be justified when necessary. The inventors have not found any prior FF technique that would employ such methods for the propagation of soliton electromagnetic waves in the suboptimal wavelength range for substantially all electric power transmission mode. The three patents cited above (Barlow, Lorber, and Broomall) all suggest a non-classical propagation, 5 but they do not explain or teach a method to achieve an optimum like this. This embodiment of the invention, which contemplates such anisotropy configurations as described, will facilitate the modes of low loss of signal transmission in addition to exhibiting a low dispersion of the higher-speed elements of the digital signals. Other effects of anisotropic wave propagation, described in the previous section on the structure of the special annular conductor, can be varied by choosing the magnetic field, observing the optimum for any given signals. 5 Examples of Fabrication of the Positioner For the precision in the symmetry necessary for the quadruple cable, it is desirable that the positioner maintain a substantially invariant electromagnetic functionality, in spite of the changes induced by the expected (or typical) variations of its environmental conditions. . Typical extruded thermoplastic shapes contain significant internal stresses resulting in changes in shape and dimension that occur after forming, and especially during aging, when used for outdoor service. To substantially overcome these problems, the inventors have developed techniques to reduce the production of these stresses during the forming process. The vibration of the thermoplastic melt, the mold walls, and the extruder can be used to improve the 15 flow rate, and to improve the quality of the finished product. Vibration frequencies of between 0.7 and 20,000 Hz have been used in the prior art to realize a variety of goals in the production of a variety of thermoplastic products. The inventors introduce a novel technique in the processing of thermoplastic materials. The inventors have found that abrupt pressure reduction and a return to pressure, often repeated during the extrusion process, results in a substantially smoother flow and stresses 25 internal substantially lower in the form of the resulting extrudate. This high-low-high pressure cycle shown in Figures 23 and 26 is fast enough to be adiabatic. The cycle, in effect, is a kind of process against the slab by which the induced expansion waves 5 encourage the fastened and inter-secured chains of the polymers to be released and saved. A key feature of the invention is the relaxation of the pressure, during the final formation, up to substantially atmospheric pressure, and the maintenance of this low pressure during cooling from F just above the glass transition temperature to the essentially solidified state . Due to the small variability of the material and the process on a moment by moment basis, all segments of the positioner can be formed in a simultaneous process using a common flow of molding material. For thermoplastic materials whose glass transition temperatures are sufficiently low to provide sufficient plasticity at melting temperatures below 315. 5 ° C, a process such as that shown in Example A is preferred. For other thermoplastic materials, such as polytetrafluoroethylene (PFTE), which does not really melt completely but rather requires a sintering process, the embodiment of Example B may be more appropriate. These examples are observed as described below, and are illustrated in Figures 22 to 27.

Example A An important factor in this process is the rapid and frequent release of pressure by impulses during the formation of the fusion and the extrusion process. These thermoplastic polymers have a molecular form of both a variable molecular weight and a variable polymer chain length that encourage the inter-assurance of the chains, which leads to non-Newtonian flow properties, producing the stresses assured to from typical continuous high pressure formation methods. Figure 22 shows an extrusion die head 201 connected to an extruder body 203. An extrusion screw 205 is located inside the body of the extruder 203. One or more hydraulic piston assemblies 207 are used, with the pistons 209, to adjust the volume change, and consequently, the pressure. The amount of volume change required for the pressure to drop substantially can be very small. Therefore, the small hydraulic pistons, which surround the final mixing chamber just before the extrusion die, need to be moved only by a very short stroke, or one that is sufficient to allow the rapid change of pressure to occur with much less inertia than could be presented from the efforts to move the screw plasticizer or the main pressure piston. The inventors have found that the extrusion die must have a small thinning along the hole 5 in order to avoid turbulent mixing on the approach to the opening of the final shape. For this process, appropriate pressures may be from about 0 kg / cm2 to about 140 kg / cm2, and this pressure may cycle approximately every 10 milliseconds. 5 Cycling pressure can act on the hot extrudate while cooling, for example, up to the glass transition temperature of -50 ° C to + 50 ° C. The pulse extrusion step is followed by a controlled slow cooling tempering in the baths 211, whose purpose is to prevent significant cooling gradients from developing in the extrudate, which would induce stresses. This tempering flow diagram with cooling is shown in Figure 24. Figure 24 indicates a schematic configuration of the extruded treatment baths (approximately 15 100 ° C to 300 ° C) immediately following the extrusion. In step 213, the hot extrudate emerges from the head of the die. In step 215, the hot extrudate is exposed to the first bath that ^ is maintained at a temperature of about 20 ° C to 50 ° C below the temperature of the extrudate. In the next step, the 20 step 217, the hot extruded, slightly cooled, is exposed to the second bath, which is maintained at a temperature of about 20 ° C to 50 ° C below that of step 215. In the next step, 219, the extruded exposes to the third bath, which is maintained at a temperature between 20 ° C and 70 ° C below that of the passage 25 217. Finally, in step 221, the extrudate is exposed to a cleaner bath maintained at approximately 63-65.5 ° C. Following the cleaner bath, a warm rinse is provided (step 223) and to clean the extruded, which is then dried with warm air. The duration of each step is set to provide a temperature equilibrium through the extrudate before entering the next stage of tempering. The time for each step will vary with the cross-sectional shape and the size of the extrudate. In the examination of the production results of this pulse pressure release method, extruded sections of completely cooled and aged samples were immersed in a uniformly heated bath to determine if deformations could be observed. When comparing the extruded materials, produced with and without the process illustrated in Example A, the difference becomes very apparent in the substantial deformation of the non-processed parts by these techniques. The processed parts show little or no change of shape or dimension. It is believed that the observed improvements result from the interlocked and tensioned molecular chains that unwind and relax during the brief portions of low impulse pressure. The final forming phase of the extrusion can be carried out during a low pressure condition, under which the flow properties are substantially improved. The solidification phase must be at such a low pressure that it provides contact with the die shape, typically about 1 bar. The impulse release process improves the fluidity of the extrudate. The thinning used depends on the shape and size of the cross section that is being produced. Ife slimming from 2 to 15 degrees can include the optimum range for most relatively small shapes and for the 5 materials such as polyethylene, polypropylene, high molecular weight polyethylene, and some copolymer mixtures. An important parameter that controls the thinning, is the proportion of reduction of the sectional volume that produces an increase of pressure to expel the extrusion along with an elevation of k adiabatic temperature. The amount of thinning needed will vary with the properties of the melt (viscosity and non-Newtonian behavior). The choice of angle can be directly related to the sectional volume, and in the ideal case, it will vary with the sectional thickness in the complex shapes. For many fusion behaviors, effective volume reduction can be in the range of about 1 to 7 percent. The initial exit of the extrudate has a cooling section with very short air before entering the first tempering bath. The choice of temperature of this first bath is selected by experiment to fairly stabilize the particulate material with minimal stress with respect to properties such as shape, section thickness, and volumetric exit velocity. This can be anywhere from 6.6 ° C to 37.7 ° C below the exit temperature of the extrudate, taking into account that there is always some adiabatic cooling from the pressure drop when the die shape comes out. Three stages of successive bath temperature drops may be sufficient to release tension and stabilize most of the 5 forms. The length of the extrudate that fits in each bath, and therefore, the time spent in it, is determined by the temperature stability of the extrudate as it arises from the bath. After the final tempering bath, a cleaning bath removes any residues from the materials of the tempering bath. For thermoplastic materials of higher temperature, the initial bath (or baths) may be one of the acid-reduced purified mineral oils suitable for the operating temperatures. The cleaning bath removes these residues and any other significant surface contaminants. Example B Fluoropolymers, which are highly desirable because of their low dielectric constant and their very low loss properties in the range of 10 MHz to 1 GHz, have more difficult forming properties. These materials do not really melt like the thermoplastics discussed in Example A. The fluoropolymer material, which starts in a particulate form, is processed in a manner that is somewhat akin to powder metallurgy. It is compressed into a shape, possibly with a binder, as a "green" shape, and then sintered into a final solid shape and configuration. During the pressure formation of these green forms, pressure releases in similar impulses have a beneficial effect on the uniformity and the results from the post-formation sintering process. Figures 25 to 27 describe a method applied to these materials and shapes. After fully sintering and curing the PTFE, for example, after the formation of the material heated in an inert atmosphere and in a pressure pulser die producing rapid changes in high-low-high volume of 1 to 3 percent, stability is improved and EF the precision of the final shape. This sequence of process steps that vary the pressure constitutes Example B for these materials. Referring to Figure 25, an inert atmospheric chamber 251 is shown where a continuous feed of sintered material in the form of a ribbon is entering. 253. A slat warming chamber 255 is shown inside the inert atmospheric chamber 251 to heat the slat 253. A thinned forming die assembly 257 accepts the slat 253. A pulsed pressure piston 259 applies a tempering pressure 0 wave to the heated sinter strip 253, thereby reducing internal stress, and improving shape stability. The pulse pressure piston 259 may employ pulses having a time pattern similar to that shown in Figure 26. The compression ratio is established by 5 die stops.

These steps are shown in the flow diagram of Figure 27. In particular, step 261 shows the hot compressed FTPE strip before it enters the inert atmospheric chamber 251. Step 263 shows the entry of the strip in a sintering chamber. under pressure. Step 265 shows the feeding of the hot sintered strip into the pulsed atmospheric insert die, as shown in Figure 25. Step 267 is the final step, where the hot strip is sent to a low pressure cooling chamber. Helicoidal Twist Eli final forming step for one embodiment of the present invention of quad cord involves imparting proper twisting to the positioner. The desired helical twisting occurs in a process that only resembles the 15 central positioner without conductors, and then in a heated phase imparts, in the form of a die-forming system that is maintained at a temperature below the transition temperature A glass (Tg), the desired helical twist to the assembly. The cooled assembly subsequently partially opens 20 during the next stage, where the conductors are installed in their notches. Next, the assembly is compressed to close, and enters the next stage, where the materials of the internal protector (or mirror) are assembled to the cable preform. After this assembly is ready for the final coverage 25 with the protective section, the traction member, and the outer jacket. Following the extrusion process, the positioner can be ready to be installed. The thermoplastic materials suitable for the positioner can be such that the resistivity of the material of the positioner is between approximately 105 and 1018 ohm-seconds, its dielectric constant is between approximately 1.05 and 4.0, and its low dielectric losses have a loss tangent. less than 0.1 over the target frequency range, generally up to or more than 1 GHz. F Other material properties are that the material of the positioner must have aging properties and weather resistance such that, for a temperature range of - 50 ° C to + 50 ° C and a humidity range of 0 to 100 percent, result less variation of 1 percent of the electromagnetic functionality. The flexural modules of the plastic materials acceptable for the positioner are in a range of approximately a minimum of 0.07 x 109 pascals (0.01 x 106 psi, typical of soft polyethylene, and probably of PTFE) up to a maximum of 6.89 x 109 pascals ( 1.00 x 106 psi, typical of PAEK). These types of materials are variably moldable or need to be "sintered" to extend in the range of types. A polypropylene filled with glass can also be a candidate material. Various mixtures of these materials can also be used. Impulse and Termination for a Good Balance There are three frequency domains of a particular interest for the network operation contemplated by this disclosure: 1) the direct current or low frequency range for energy or for very low frequency signaling 5 as with the POTS ring voltage at around 20 Hz; 2) the low frequency or voice frequency range from about 375 Hz to about 3,400 Hz; 3) the wide band high frequency range so that the digital data reaches around 1 GHz. The contemplated element and the terminator element can separate these three ranges in an effective way to isolate any interaction between them. The type of digital data format that seems most desirable in light of existing standards in the world is the SONET or SDH format, which 15 are the current accepted standards, through which most fiber optic communications around the world operate. A basic framework or "car-time box" of this scheme The time division multiplexing was established in a duration of 125 microseconds, that is, a group every 1 / 8,000 of 20 1 second. The structure of the time slots of either of these two formats is shown in Figure 28. The organization of each frame is represented by 810 time slots or "pigeon holes", which are shown configured in a 283 matrix of 9 rows for 90 columns. Each slot 281 contains a 25 word of 8 bits or 1 byte. The bytes flow row by row in sequence starting at 1 and ending at 810 for each frame of 125 microseconds. Then there are 6,480 bits per frame at 8,000 f times per second given the basic bit rate of 51.84 megabits per second. This is only the basic or minimum bit rate 5 or the STS-1 format when it is in electrical form. When it is used to produce an optical signal for, say, a fiber optic line, then this format is called an OC-1 (optical carrier). The SONET and SDH standards include the use of an 8-bit encoding scheme, known J as B3ZS, which operates to prevent the extended stretches of ones or zeros, by modifying the digital word in a way that allows the decoding or retrieval of the true data from the source. This scheme was developed to prevent significant low frequency energy from changing 15 the baseline of the signal, which in turn would alter the precise recovery of the digital signal. Accordingly, this format avoids the substantial low frequency components in the signal of A 51.84 MHz. The basic framework STS-1 is used as the structure 20 for the division of additional time by placing up to 192 times the data in this fundamental format. That is, each frame of 125 microseconds subdivides each of the 810 cells into as many as 192 words, each only 8 bits long. This multiplies the bit rate also by up 25 192 times, resulting in a maximum bit rate data rate of 9.9456 GHz. Current standards commonly use multiples of 3, 12, 24, 48, 96, and 192 times the base rate f in the communication systems of work used throughout the world. The electrical signal mode 5 contemplated for some of the last mile types of cable systems disclosed herein is typically STS-3 (155.52 MHz) or STS-12 (622.08 MHz). In these cases, only a very limited low frequency response in the portion of the balanced impulse or termination element F employed by the present invention needs to be hailed. Most signal processing circuit topologies, especially those using integrated circuit techniques, are single-ended or unbalanced designs. Elements must be used to couple these unbalanced single-ended circuits in and out of the quad-balanced design, while preserving the EMIR and XTLK performance of the cable. Balun devices that have properties that look like transformers have been used previously for this purpose. C.L. Ruthroff published a classic document related to this subject in the August 1959 issue of Proceedings of IRE, pages 1337-42. These designs have a limited common mode rejection (CMR), and some relevant bandwidth limitations. Almost transmission line devices that use multiple aperture ferrite cores have also been used to make Baluns, but they have difficulty achieving a CMR better than 25 to 30 dB over a wide bandwidth. Two example United States Patents are Nos .: 5,220,297, to Crowhurst, "Transmission Line Transformer 5 Device"; and 5,379,006, to McCorkle, "Wideband (DC To GHz) Balun". Figures 9 and 10 detail the pulse and termination devices that can be employed in the present invention. In the novel balanced impeller and receiver system, termination impedances are controlled essentially by EF resistors configured in "delta". In both cases, these small arrays of film resistors isolate the direct current and low frequency components on the lines by means of high-pass filters 501 shown, and the physically small capacitors integrated in each 5-delta resistor array. The balanced impeller, shown in Figure 9, includes the positive-negative polarization signal current sources 503 and 505, which drive the cable, plus the source and termination resistor arrangements, minimizing 0 in this manner. impedance changes in transitions or in "one" or "zero" states. In particular, Figure 9 shows a data stream in STS format that enters a high frequency pulse lift circuit 507. The high frequency lift circuit 507 compensates for losses. The high frequency lifting circuit 507 is adjusted with the opening lift circuit of the receiver 509 (Figure 10) to meet the BER specifications. The output of the high frequency rise circuit f is sent to a phase splitter 508. The output of the phase splitter 508 is two signals at 180 ° 5 out of phase. The first signal shown by the line 511 enters an impeller of the wide-band current source 503. The other signal, shown by the line 513, enters the impeller of the wide-band current source 505. A high-pass filter balanced 501 receives both signals. These pass through the F arrangement of the resistor 515 to the quad cable 517. Also shown in Figure 9 is a low pass filter 519 that accepts the inputs from the auxiliary low frequency services as well as the direct current power sources. . These low frequency signals are also sent to cable 517, to provide, for example, lines 55 and 57 of Figure 2. The receiving end of the balanced line, shown in Figure 10, ends in the arrangement of the passive resistor 515 'coupled with the long tail input amplifier in a positive-negative polarization. This stage couples the signal with the system and with a digital clock comparator with very good CMR over the whole bandwidth. Figure 10 shows in more detail the balanced cable receiver system. The receiving end of the cable 517 is received in a passive resistor array 515 '. The low frequency components of the signal pass through the low pass filter 519 'up, the auxiliary low frequency services, and provide the direct current power. The high-frequency components pass through the high-pass filter 501 '. The high frequency components pass up to a balanced input 521 amplifier. The balanced input amplifier 521 may have a long differential cascade pair architecture in differential cascade. The CMR of the balanced input amplifier can be greater than 40 dB across the amplitude of the band. The output of the balanced input amplifier can be passed through j a direct current resetting synchronous clamping system 523. The output of the clamping system is sent to an opening lift circuit of the receiver 509. The opening lift circuit of the 509 receiver can be used to trim the so-called "eye pattern", to meet the 15 BER specifications. The output of the opening elevation circuit of the receiver 509 is the data stream. These stages of the impeller and the receiver have shown g ^ a better performance of 50 dB CMR. In a fully integrated design, this level of operation should approximate 20 at a relatively low cost. The types of input and output stages discussed herein are easily incorporated into the regenerator modules for use in the cable system as disclosed above. Also in the Figures, as described above, transient voltage clamping devices are shown to avoid high voltage pulses from a variety of possible sources (e.g., electrostatic discharges, f near lightning or EMP, or transient connection or service). 5 Use of This Quadruple for Applications of "Wire of Fire" Recently, a new standard of data bus in series for use with computer peripherals has begun to reach a widespread use. This new standard is the IEEE 1394 or its near equivalent in the IEC jÉÉ international 1883. The appeal "FIRE WIRE" has been widely used to name this new wire and busbar system. The physical interconnecting cable of these systems uses two twisted pairs and two power supply wires inside of global shields. THE FIRE WIRE 15 was originally intended for relatively short stretches, to interconnect a variety of accessories to a personal computer. These standards have grown in their range and in the ^ Data operational speeds, so that the original limit of 100 Megabits / second now goes up to 400 Megabits / second, and 20 proposes that it still reaches one as high as 1,200 Mega-bits / second. These cables, modified by the invention, can be very suitable for connecting many types of current and future devices, information devices, and accessories through a home or office. The shape of the cable of the present invention lends itself easily to this objective. The cable can be easily modified to include two power conductors inside it. f You can certainly design a smaller version for indoor environments. The unique advantages of this cable form 5 can be exploited for these uses and with substantial savings for this more limited application. It is interesting that the root bar cycle arbitration selected by the standard uses the same range as the SDH and SONET protocols - 125 microseconds. In EP view of the always connected active user interface of the global communication system disclosed, and of the high-speed data objectives of the FIRE WIRE, these systems would seem to be well coupled, with the data functions easily interconnected for the medium local environment This 5 FIRE WIRE forms the novel cable structure, and these applications are absolutely contemplated by this disclosure. Example of a Manufacturing Process This example uses a positioner of the shape of the Figure 16, but where the radial 0 locator spaces for the fibers are omitted. The material selected for this example is PTFE. The diameter of the assembled core is 1,066 centimeters. It is formed by "green" extrusion, sintering, and final forging operation, as described above. It is previously assembled, and then formed in a tunnel heated with inert atmosphere to give a helical twist of 1.8 turns per foot. Annular drivers Tubular Units (UTAc) are separated at 0.508 centimeters above the centers, and the quadruple orthogonal arrangement centers on the diameter of 1066 centimeters of the core support. 5 The UTAc 's are made of 0.975 mm OD, mild hardened pipe, and formed from one of the high alloys in nickel-iron (18-30 percent Ni), which are axially magnetizable to more 0.6 Tesla. The ID of the tube is approximately 0.66 millimeters. This tube is manufactured F? as a continuous stretch of formed, laminated, and cast material, producing a "seamless" construction, with a smooth internal surface. It is plated with copper, and electroplated to a smooth gloss finish, and to a thickness of 28 microns. This surface is then coated by extruding the magnetic matrix from 15 urethane enamel containing the Ni-Zn ferrite powder as described above, to an additional finished thickness of 11 to 14 microns after solidification in the field ^ axial magnetizing. This can be done as a continuous operation after the plated pipe is formed. Then he The finished assembly is coated with a soft urethane enamel material to a thickness of 4 to 6 microns in a multi-stage dip and dry process similar to that used to coat the insulation of a magnetic wire. It is convenient to color code this layer to identify each one of the 25 four UTAc 's in a finished cable. This ends the formation of the Tubular Unitary Annular conductor that, in this stage, must be stored in reels with a minimum diameter of 1.22 meters. AJF The next step of the process for the conductors is to direct into the selected tube or tubes the required number of optical fibers, using appropriate sections selected for the lengths of sections of the intended finished cable (from, say, 1,219.2 meters to the shorter lengths to be used, typically 121.92 meters). The optical fibers are of a single mode, covered with plastic, n and color coded for identification. A conductor of thin steel wire directs them into the tube, in a generally straight path, together with the superabsorbent compound, which also then acts as a lubricant for the fiber steering operation. Depending on the application, 5 the fibers can be inserted into only one of a few of the UTAc 's. A suggested minimum fiber content is one per UTAc in each of the two pairs of electrical signals. Four of the appropriately selected sections of tubes are then assembled in a continuous section, and the PTFE positioner is re-assembled. At this point, the previously selected core cable runs are ready for the shield assembly following the program illustrated above under Protector Design. The outer covering layers must use the first protective layer of "EMI symmetrization (if etrizadora), and the second protective layer (more external) that has the resistive partial impedance design described above (external housing of impedance coupling). Protection steps complete the assembly of the finished cable The finished cable must be stored in reels of a minimum diameter of 1.22 meters Subsequent to the manufacture of the cable, the termination of the ends is carried out in a different environment, where The ends of the cables are cut back to an appropriate length to allow the optical fibers to be tailored to an appropriate length of service fiber, cushioned by a supporting plastic cushion tube. in this state for future use, or can be terminated in the selected connectors. bulbs are electrically connected 15 by means of a shrink sleeve splice to provide very short electrical connections with the source drive and receiver terminator devices. ^ This cable example can be used in the Node system in, for example, STS-3 or 155 Megabits / second, or for 20 data at 622 Megabits / second (STS-12). A number of embodiments of the present invention have been described. However, it will be understood that many modifications can be made without departing from the spirit and scope of the invention. For example, symmetry and external hosting of 25 impedance coupling can be conveniently employed in coaxial cables. In addition, it can be used in twin axial cables (Figure 29), where two coaxial cables f 1.601 and 1.603 are located inside a single jacket 1.609. Double concentric annular conductors 1605 and 1607 5 are provided in this embodiment. In a similar manner, referring to Figure 30, some cable formats, such as Super VHS or Y / C, employ two coaxial cables, where the returns are not coaxial. These can similarly benefit from an external housing 1707 having impedance coupling.

F Of course, any of the cables can additionally benefit from a symmetry layer as well. It should also be noted that each cable, for example 1701 and 1703, can also be a quad cable, for example. The invention also contemplates tri-axial cables. In accordance with the foregoing, other embodiments are within the scope of the following claims.

Claims

REIVI DICATIONS 1. A system for communicating data in two directions, comprising: a local node interface device for connection 5 to a network, including: a low frequency circuit to communicate signals of low frequency, energy or direct current signals; and a high frequency circuit for communicating data; a cable connected to the F / local node interface device; a user interface device for connecting the cable to a plurality of data devices, including: a low frequency circuit for communicating low frequency signals, energy or continuous current signals; a high frequency circuit to communicate data; and ^ a plurality of interfaces for communicating signals to and from a plurality of input devices, such that at least one of the local node interface and user interface devices further comprises a port configured for wireless communications. The system of claim 1, wherein said user interface device further comprises a port 25, and further comprising a POTS line coupled to said wireless leek. The system of claim 2, wherein the user interface device further comprises a radio port for communications with a peripheral device, the 5 radio port to communicate with the peripheral device through either radio waves, RF waves, or microwaves. The system of claim 1, wherein the user interface device further comprises an industry standard open port for a user interface device f control, where a level of control can be given as input to the device. user interface via the industry standard open port. The system of claim 1, wherein the local node interface device, the cable and the device 15 user interface operate in the optical domain. The system of claim 1, wherein the local node interface device, the cable and the device ^ of user interface operate in the electrical domain. The system of claim 1, further comprising a fiber interface device connected to the local node interface device. The system of claim 7, further comprising a local node, and wherein the local node includes a plurality of fiber interface devices and devices. 25 local node interface. 9. The system of claim 7 further comprises a port configured for wireless communications coupled to the local node. The system of claim 1, wherein the port 5 configured for wireless communications is arranged in the local node interface device. The system of claim 10, wherein the port configured for wireless communications is coupled to a circuit. iFk 12. The system of claim 1, wherein the port configured for wireless communications further comprises a plug-in module having a translator for translating signals in a cellular protocol to signals in a different protocol. 13. The system of claim 12, wherein the different protocol is the language of Linux computers. The system of claim 12, wherein the cellular protocol is CDMA. ^ 15. The system of claim 12, wherein the cellular protocol is CDPD. 16. The system of claim 12, wherein the cellular protocol is WAP. The system of claim 12, wherein the cellular protocol is TDMA. 18. The system of claim 12, wherein the cellular protocol is GSM. 19. A system for communicating data, comprising: a local node interface device for connection f to a network, which includes: a low frequency circuit for communicating low frequency signals, energy or DC signals; and a high frequency circuit to communicate data; a cable connected to the local node interface device; a user interface device for connecting the Mk cable to a plurality of data devices, including: a low frequency cit for communicating low frequency signals, energy or DC signals; a high frequency cit to communicate 15 data; and a plurality of interfaces for communicating signals to and from a plurality of input devices, at least one of the local node interface and user interface devices further comprising a stop port, a satellite communications cit. 20. A communication system, comprising: a plurality of regional rings, each regional ring including: a switch transfer point; and a plurality of nodes coupled in a ring structure to the switch transfer point, each node including: at least one fiber interface device; And 5 an interface device; a bridging cit between each of the two rings to allow data transfer between the regional rings; and a plurality of user interface devices, each user interface device connected to a respective local node interface device by means of a cable, wherein at least one of either the switch transfer points, the regional rings, the nodes, the bridging cit, or the user interface device further comprises a port for wireless communications. 21. The system of claim 20, wherein the bridging cit includes a microwave communication link. 22. The system of claim 20, wherein there are 20 between 16 and 64 local node interface devices per node. The system of claim 20, further comprising a port coupled to the user interface device for a user interface controller. 24. A method for altering data in a communications system, comprising: accepting data in a predetermined data format box; de-multiplexing the default data format box; receive a transmission from a wireless network; alter the data in the default data format box based on the transmission of the wireless network; and multiplexing the default data format box. 25. A method for altering data in a communication system, comprising: accepting data in a predetermined data format box; 15 de-multiplexing the default data format box; receive a transmission from a wireless network; ^ alter the de-multiplexed data based on the transmission of the wireless network; and transmit the altered data. 26. The method of claim 25, wherein the predetermined data format frame is one of either a SONET / SDH frame or an ATM frame. 27. A method for altering data in a communications system, comprising: accepting data in a SONET / SDH box; de-multiplexing the predefined data format box; receive a transmission from a wireless network in a 5 CDMA format; translate the transmission of the CDMA format to a different format; alter the de-multiplexed data based on the transmission of the wireless network; f transmit altered data; send a status signal in the different format; translate the status signal to the CDMA format; and transmit the status signal. 28. A method for altering data in a communications system, comprising: accepting data in a SONET / SDH box; de-multiplexing the predefined data format box; receive a transmission from a wireless network over a 20 POTS line; translate the transmission of the POTS format to a different format; alter the de-multiplexed data based on the transmission of the wireless network; 25 transmit altered data; generate a status signal in the different format; translate the status signal to the POTS format; and transmit the status signal. 29. A method for altering data in a communication system, comprising: accepting data in the default data format box; de-multiplexing the default data format box; f receiving a transmission from a satellite network; alter the data in the default data format box based on the transmission of the satellite network; and multiplexing the default data format box. 30. A method for altering data in a communication system, comprising: ^ accepting data in a predetermined data format box; 20 de-multiplexing the default data format box; receive a transmission from a satellite network; alter the de-multiplexed data based on the transmission of the satellite network; and 25 transmit the altered data. 31. The method of claim 30, wherein the alteration occurs in a user interface device. 32. The method of claim 31, further comprising transmitting a signal to a base interface device 5 in the altered data. 33. The method of claim 32, wherein the interface device controls the operation of a household appliance. 34. A communications system, comprising: i a central antenna; a plurality of sub-antennas in communication with the central antenna; a regional ring in communication with each sub-antenna of the plurality of sub-antennas, each regional ring including: a switch point of switches; and a plurality of nodes coupled in a ring structure to the switch transfer point, each node including: at least one fiber interface device; and 0 at least one local node interface device coupled to each fiber interface device; and a plurality of user interface devices, each user interface device connected to a respective local node interface device by a cable. 35. The system of claim 34, further comprising a microwave communication link, and wherein the M ± center antenna communicates with each sub-antenna of the plurality of sub-antennas via the microwave communication link. F