KR810001101Y1 - Lighting device of fluorescent lamp - Google Patents

Abstract

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Description

Discharge lamp lighting device

1 is an electric circuit diagram showing an example of a conventional discharge lamp lighting apparatus.

2 is a voltage, current and energy waveform diagram of each part of the apparatus shown in FIG.

3 is a drooping characteristic diagram of a discharge lamp in the apparatus shown in FIG.

4 is an electric circuit diagram showing an example of a fluorescent lamp lighting apparatus of each cycle start lighting method which is the background of the present invention.

5 is a voltage and current waveform diagram of each part of the apparatus shown in FIG.

6 is a voltage, current and energy waveform diagram of the main portion of the apparatus shown in FIG.

7 is a relationship between the duration of the tube current and the tube current.

8 to 10 are each an electric circuit diagram of another embodiment of the present invention.

The present invention relates to a discharge lamp lighting apparatus, and more particularly, to a discharge lamp lighting apparatus simplified by reducing the number of parts in every cycle lighting system.

In the recent energy crisis, the importance of saving resources and energy is emphasized, making it a technical proposition. Every cycle start lighting method which is the background of the present invention is intended to solve this proposition in the field of lighting. In other words, according to the inventor's proposal separately, in every cycle start lighting method (described later), the power loss of the discharge lamp lighting apparatus is reduced to less than one quarter of the conventional lighting method, for example, and the shape and weight ratio are also reduced. It can be miniaturized to less than sixths.

Thus, every cycle start lighting method has a significant advantage.

In the present invention, in order to further supplement these advantages, it is intended that the luminous flux is not mainly affected by voltage fluctuations of a commercial power supply.

In order to explain the reason why the current-limit choke can be miniaturized in every cycle start lighting method that is the background of the present invention, the mechanism of the conventional lighting method will be described first.

In other words, as the charging lamp lighting device for fluorescent lamps, a circuit structure such as that shown in Fig. 1 has been used conventionally. This configuration connects the discharge lamp FL to the AC power supply AC through the current-limit choke CH as a current-limiting device, while simultaneously connecting the discharge lamp FL to the oscillator circuit R 'in parallel. According to this configuration, the oscillation circuit R 'starts the oscillation operation at the same time as the power supply AC is connected, and the oscillation current heats the filaments f and f' of the discharge lamp FL, and oscillates higher than the required voltage Est between the terminals. The output voltage is applied. When the filaments f and f 'of the discharge lamp FL are sufficiently heated, and the start-up voltage of the discharge lamp FL decreases to Est, it is started by the above-mentioned oscillation output and lights up on the ground. Once lit, the terminal voltage of the discharge lamp FL drops to the tube voltage VT, so that the oscillator circuit R 'cannot maintain oscillation and stops operation, and the discharge lamp FL lights up by the voltage supplied to the power supply AC through the current-limit choke CH. maintain. When the waveforms of the tube voltage VT and the tube current iT are observed during lighting, the waveforms are the same as those in the second and second degrees. From the waveforms of the tube voltage VT, the tube current iT, and the power source voltage e, the energy change of the current-limiting choke CH at each instant is obtained as the waveform shown in FIG. 2C. As can be understood from the waveform, in the period (t _{1 to} t ₂ ) where the power supply voltage e is higher than the tube voltage VT, Energy increases unilaterally and accumulates in the Hallyu choke CH. When the power source voltage e falls below the tube voltage VT, the stored energy is switched to the discharged state. The period of emitting energy is a period (t ₁ -t ₂ ) in which the power supply voltage e is lower than the tube voltage VT, and in this period (t ₂ -t ₃ ) Energy is released. The magnitude of the current-limit choke CH is determined by the maximum value of the accumulated energy. In other words, the current-limit choke CH must select its capacity to withstand the maximum amplitude of the stored energy S ₁ . Basically, restart voltage ERst of discharge lamp FL must be less than power supply voltage e at the time of re-ignition. This means that the peak value VTP of the tube voltage VT cannot be increased in comparison with the power supply voltage e.

Actually, in the case of conventional discharge lamps, the effective value VT of the tube voltage VT is set to about one half of the effective value E of the power supply voltage e, and therefore, the effective value VCH of the terminal voltage VCH of the current-limit choke CH is equal to two minutes of the effective value e of the power supply voltage. It is set to 1 or more.

The above faults of the current-limiting device are shown again as the drop characteristic curve a of the discharge lamp FL shown in FIG. 3 and the impedance load line b of the current-limit choke CH (in this case, for simplicity, as the resistance load line assuming the impedance as resistance). ) Can be explained. In other words, the tube voltage V _T and the tube current iT of the discharge lamp FL during lighting are shifted to the right as indicated by the arrow according to the droop characteristic curve a, and are stabilized at the intersection point with the load line b. The slope of the load line b (impedance of the Korean wave choke CH), which determines the position of), is extremely important. For example, if the impedance is lowered in order to downsize the Hallyu choke CH, and the load line is set to a smooth slope like the broken line C, the intersection point (I) will move to the right side greatly, and the tube current iT will be excessive, resulting in the Hallyu choke CH. Is rather large.

Therefore, also in this structure, it is not possible to miniaturize the current-flow choke CH with the said structure.

The present inventors have provided a cycle start lighting method for solving the above-mentioned defects prior to the present invention. As described above, the present invention is intended to provide a discharge lamp lighting apparatus using the every cycle start lighting method, and therefore, the operation and features of every cycle start lighting method, which is the background of the present invention, will be described.

4 shows an example of the configuration of one circuit of the discharge lamp lighting apparatus for fluorescent lamps configured in this cycle start lighting system.

In Fig. 4, AC is an AC power supply, and a series circuit of a Hall current choke CH, which is an example of a current limiting device, and a discharge lamp FL are connected. The secondary choke CH is wound with a secondary winding W20, which is a high frequency transmission means for superimposing the oscillation output of the booster circuit to be described later, on the power supply voltage, and one end of the secondary winding W20 is one end of the filament f of the discharge lamp FL. The other end is connected to a booster circuit R which is a high frequency high voltage generating means. The step-up circuit R is a circuit in which the intermittent oscillation capacitor C ₁ is connected in series to the oscillation circuit R 'formed by connecting the series circuits of the thyristors S and the step-up inductor L and the capacitor C in parallel. It is connected to one end of one secondary winding W20, and the other end is connected to one end (b) of filament f 'of the discharge lamp FL. PRH is an electronic filament preheating circuit which is electrically conductively driven by the oscillation output of the boosting circuit R to preheat the filament f, f 'of the discharge lamp FL. The PRH is a high frequency convex inductor NL which convexes the oscillation output. A series circuit is connected in series between the filaments f and f 'of the discharge lamp FL.

As long as the boosting circuit R performs the oscillation operation intermittently, the booster circuit R may be replaced with a high-voltage generator circuit using a thyristor with a gate such as a triac, or an inverter or a pulse generator.

Next, the operation of the above configuration will be described. First, when the power supply AC is connected, the power supply voltage e is applied to the discharge lamp FL through the current choke CH, and the power supply voltage e is also applied to the boosting circuit R via the secondary winding W20 of the current flow choke CH. In the boosting circuit R, the power supply voltage e is applied to the thyristor S via the intermittent oscillation capacitor C ₂ , and the oscillation circuit R 'starts the oscillation operation in order to brake over the die Lister S. The oscillation operation is continued, but if there is no capacitor C ₁ for the intermittent oscillation, a power supply voltage e is an intermittent oscillation in each half cycle at a portion that rises because the capacitor C ₁ for the intermittent oscillation.

Now, considering the half cycle of the power supply voltage e, as described above, when the oscillation circuit R 'starts the oscillation operation, the intermittent oscillation capacitor C ₁ is charged with the polarity in the direction of canceling the power supply voltage e. Therefore, when the terminal voltage VC ₁ rises and the voltage difference from the power supply voltage e does not reach the brake overvoltage voltage V _BO of the die thruster S, the die thruster S remains off, and the oscillation circuit R 'is not oscillated. Is stopped. For this reason, in this half cycle, the oscillation circuit R 'is stopped in the oscillation circuit R' while the terminal voltage VC ₁ of the intermittent oscillation capacitor C ₁ is kept constant. However, when the power supply voltage e is switched to the next half cycle, the power supply voltage e becomes a voltage of opposite polarity to the voltage of the first half cycle. Therefore, the terminal charged in this voltage and the intermittent oscillation capacitor C ₁ in the first half cycle A voltage in agreement with the unloading voltage VC ₁ is applied to the oscillation circuit R ', and the thyristor S starts to start the oscillation by the brake overload due to this sum voltage.

However, the oscillation and at the same time is charged in a manner to compensate for again a power supply voltage e by the terminal voltage VC ₁ of the capacitor C ₁ for the intermittent oscillation rapidly inverting the polarity, before long to stop the oscillation of the oscillation circuit R '. Therefore, the oscillation circuit R 'oscillates only during the rapid inversion period of the intermittent oscillation capacitor C ₁ , and only during that period, current flows through the oscillation circuit R' through the intermittent oscillation capacitor C ₁ from the power supply AC. This operation is similarly carried out for each subsequent half cycle.

The 5a turns and also a voltage or current waveform of each part showing the state, e is the power supply voltage, VC ₁ will display the terminal voltage of the capacitor C ₁ for the intermittent oscillation only in the rapid reversal of the voltage condenser for intermittent oscillation C ₁ As shown in Fig. 2, the oscillation current iC ₁ flows, and only during this period, oscillation output VR of high frequency high voltage is generated at both ends of the booster circuit R.

The oscillation output VR is induced in the primary winding W10 from the secondary winding W20 of the Korean wave choke CH, and is superposed in the opposite polarity to the power supply voltage e and applied to the discharge lamp Fl and the filament preheating circuit PRH. Then, the above-described voltage is applied to the filament preheating circuit PRH through the high frequency convex inductor NL, and the die Lister SP is electrically driven by the sudden change effect of the voltage (that is, the dv / dt effect). Therefore, at the rear end of the intermittent oscillation phase, the current of the power source AC flows through the filament f, the die Lister SP, the inductor NL, and the filament f ', and the filaments f and f' start to preheat. When the oscillation output VR of the booster circuit R is applied to the preheating circuit PRH, the above-described die thruster SP is electrically driven, and preheated by a current flowing from the power supply AC to f and f 'during the period in which the thyristor SP is conducted.

In this manner, when the filament f, f 'is sufficiently preheated and the start-up voltage of the discharge lamp FL is lowered to Est, the booster circuit R triggers the oscillation output VR to start the discharge lamp FL.

When the discharge lamp FL is turned on, the intermittent oscillation force flows into the almost discharged discharge lamp FL, and the remaining force is absorbed by the high frequency convex inductor NL, and the brake overvoltage VBU of the thyristor SP is larger than the peak value VTP of the tube voltage. By setting it high enough, the thyristor SP will not conduct. In addition, if the brake overvoltage of the thyristor SP is very high, the high frequency block inductor NL may be omitted in some cases. However, such a thyristor is not common and expensive at present. Therefore, after the preheating of the filaments f and f 'is stopped, the discharge lamp FL is started by the oscillation output VR for each half cycle of the power supply AC and is kept on by the power supply voltage e (see also FIG. 5b).

In FIG. 4, the preheating circuit PRH may be replaced with an electrode preheating circuit by a filament transformer.

During the lighting, the tube voltage VT becomes a square wave having a rest period due to the intermittent oscillation period as shown in FIG. 6A. Therefore, the effective value VT of the tube voltage VT shows a value of about 90-95% of the conventional lighting system. The loading lamp FL is restarted by the oscillation output VR at the rising part of each half cycle. That is, the high-voltage oscillation output VR is applied to the discharge lamp FL at each start-up to prevent the disappearance of ions, and the intermittent current ic flowing in the boost circuit R flows through the secondary winding W20 and corresponds to the terminal of the secondary winding W20 corresponding thereto. The voltage is applied to the discharge lamp FL by a low frequency voltage which is rapidly increased through the coupling with the primary winding W10. The preceding phase of the tube current iT maintains a constant phase in spite of the fluctuation of the power supply voltage e. Therefore, the rate of change of the tube current in every cycle start lighting method is good despite the decrease in the stable impedance.

Next, the tube current iT flowing into the discharge lamp FL from the power source AC flows mainly in the period t _{2 to} t ₄ other than the oscillation period as shown in FIG. 6B. In the oscillation periods t _{1 to} t ₂ and (t _{4 to} t ₅ ), the current iC ₁ flows from the power supply AC to the boosting circuit R. 6C shows the current waveform of the two current iC ₁ .

The energy change of the current-limit choke CH is calculated from the waveforms of the tube voltage V _T , the tube current iT, the current iC ₁ of the booster circuit R, and the power supply voltage e to obtain the waveforms shown in FIGS. 6 d and e. The figure (D) shows the energy accumulated in the current-limit choke CH by the oscillation output V _R. The total S of this energy Is given by K is a constant determined by the turn ratio of the primary winding W10 and the secondary winding W20. The figure (E) shows the energy accumulated in the current-limit choke CH and emitted from the current-limit choke CH during the period in which the lighting is maintained by the power supply voltage e. Energy is accumulated during the period (t _{2 to} t ₂ ) where the power supply voltage e is higher than the tube voltage V _T , and the total energy S ₂ is Is given by

On the contrary, in the period (t _{3 to} t ₄ ) where the tube voltage V _T is higher than the power supply voltage e, the above-mentioned accumulated energy is released, and the total emission energy S ₃ is Is given by

In the case of the waveform shown in FIG. 6, the relationship S ₁ + S ₂ = S ₃ is established.

Next, based on the waveform shown in FIG. 6, the reason for miniaturization in every cycle start lighting system is as follows. For the sake of simplicity, however, the initial value of the tube current iT is set to 0 and the accumulated portion of energy due to the intermittent anticondensing capacitor C ₁ is ignored.

In such a case, the tube current iT is calculated as follows.

Where L is the inductance of the current-limit choke CH, the power supply voltage e = EmSi, θ = ω t, and the amplitude of the tube voltage VT is VTm. Is a period of θ = π + c2. The above formula this, And Calculation for the case is shown in FIG. In FIG. 7, it can be seen that iT increases when the ratio of VTm and float is small. For example, for VTm / Em = 1/2, VTm / Em = Compared to the case, the ratio of the maximum current is 7 times. Inductance L of the required Korean wave choke CH It becomes. This means that the terminal voltage V _CH of the current-limit choke CH can be greatly reduced, and the impedance of the current-limit choke CH can be reduced by that amount, and the size thereof can be reduced. In addition, the smaller impedance means that the slope of the impedance load line (see FIG. 3) is not a problem, and this means that the intersection with the droop characteristic curve of the discharge lamp FL is as large as indicated in FIG. It means not to move to the right. In other words, in the case of the cycle start lighting method, the drop characteristic curve of the discharge lamp FL is inclined approximately horizontally or rightly and is substantially straight.

The greatest advantage of this lighting method is that the terminal voltage V _CH of the Hall current choke _CH , i. It can be reduced to a degree. This leads to power loss It is expected to decrease to a degree, and the overall efficiency of the circuit system can also be expected to be improved by about 25%. In addition, since the phase difference between the power supply voltage e and the tube current iT is smaller than that of the conventional lighting method, the power factor improving capacitor can be made unnecessary or extremely small by the lighting method. In addition, since the discharge lamp FL is re-burned at the high-voltage power generation output of the booster circuit R as compared to the re-ignition of the discharge lamp FL by the power supply voltage as in the conventional apparatus of FIG. 1, the luminous flux fluctuation due to the change in the power supply voltage is relatively small.

In the above detailed description, it will be understood that every cycle start lighting method is extremely superior to the conventional lighting method.

However, if the miniaturization rate of the current-limit choke is reduced dramatically, the rate of change of the tube current is weakened. In the cycle start lighting method, the intermittent oscillation phase basically does not change due to fluctuations in the power supply voltage, but an induced voltage is generated in the current-limit choke CH by the input current of the booster circuit H. Compared to the method, the rate of change is reduced. Nevertheless, the rate of change is also a problem in the extreme miniaturization of the Korean wave choke CH. In other words, in each cycle start lighting method, the rate of change of the ground lighting circuit is generally possible, but in this type of every cycle lighting device, the rate of change is improved to the same or higher than that of the conventional fast lighting circuit. It would be advantageous if you could. Therefore, the main objective of this invention is to provide the discharge lamp lighting device which will improve a fluctuation rate again in every cycle start lighting device. Another object of the present invention is to eliminate the resonant inductor for resonantly boosting the oscillation output of the high frequency high voltage generating means in each cycle start lighting device.

Another object of the present invention is to eliminate the noise suppression inductor as a noise filter that prevents line noise from leaking into the power supply.

Another object of the present invention is to provide a high frequency transmission means in a leakage transformer.

Summary of the Invention In summary, in a cycle start lighting device, a leakage transformer is connected to a power supply, and the power supply voltage is appropriately stepped down by a combination of the primary winding and the secondary winding of the leakage transformer. The leakage impedance between the winding and the secondary winding acts as a low frequency current current impedance, a resonance boosting impedance, or an anti-noise impedance, or the combination of the secondary winding and the tertiary winding of the leakage transformer serves as a high frequency transmission means. Further, even the means for controlling low frequency components for the tertiary winding output terminal is provided in the above-mentioned leakage transformer transformer.

The above and other objects and features of the present invention will become more apparent from the following detailed description of the embodiments with reference to the drawings.

8 shows an electric circuit diagram of Embodiment 1 of the discharge lamp lighting apparatus of the present invention. This embodiment is a case where every cycle start lighting method is applied to a two-light series of high-power fluorescent lamp FLRIIOH. The difference from FIG. 4 is that the power supply AC is connected to the primary winding N ₁ of the leakage transformer LTR. A series circuit of the discharge lamps FL ₁ and FL ₂ is connected between the winding N ₁ and the series terminal of the secondary winding N ₂ through the current-limit choke CH, and the filaments f ₁ , f ₁ ′ and f ₂ , f ₂ of each discharge lamp are connected. 'Is configured to be preheated by the filament winding H. In addition, the capacitor C ₂ is connected in parallel with the series circuit of the discharge lamp FL _1, FL _2, will also that one discharge lamp, in the example shown is a capacitor C ₂ for sequential starting connected in parallel to the FL _2. Here, the secondary voltage of the leakage transformer LTR is set to about 300V.

Next, the operation will be described. When the power source AC is connected, the filaments f, f ₁ ′ and f ₂ , f ₂ ′ of the respective discharge lamps FL1 and FL2 are preheated by the filament winding H. At the same time, the booster circuit intermittently generates the high frequency high voltage as in FIG. This oscillation output V _R is transmitted from the secondary winding W20 of the Korean wave choke CH to the primary winding W10, and is superimposed on low-frequency alternating current and is provided at both ends of the series circuits of the discharge lamps FL ₁ and FL ₂ . Here, the oscillation frequency of the booster circuit R is set to a low frequency as much as possible from the viewpoint of noise generation suppression, and therefore the value of the oscillation output V _R is made slightly lower. By the way, in the two ends of the series circuit of the discharge lamp FL _1, FL _2, is the resonance step-up by the leakage impedance and the capacitor C ₂ between the leakage transformer primary winding N ₁ and the secondary winding of N ₂ LTR. Therefore, in the present invention, a resonant inductor made of ferrite, which is conventionally provided separately for resonance boosting, may be omitted.

In this way, the oscillation output boosted by resonance is given to one discharge lamp FL ₁ through the sequential start-up capacitor C ₃ . Accordingly, when the filaments f ₁ and f ₁ ′ of the discharge lamp FL ₁ are sufficiently heated, the discharge lamp FL ₁ is _first started by the oscillation output V _{R described} above. Then, the resonant boosted oscillation output is given to the other discharge lamp FL through the discharge lamp FL ₁ in which the internal impedance is reduced, so that the discharge lamp FL ₂ is continuously started.

During the lighting of the discharge lamps FL ₁ and FL ₂ , as is apparent from FIG. 5B, the high-frequency noise becomes a problem because the booster circuit R intermittently oscillates. In addition, noise generated by the discharge lamps FL ₁ and FL ₂ itself is also a problem. If these noises leak to the power supply AC side, they adversely affect other electrical equipment connected to the same power supply. Therefore, conventionally, in order to prevent leakage of generated noise to the power supply, a noise preventing inductor made of a light is provided between the power supply AC and the booster circuit R. In the present invention, even this function can be omitted because the leakage impedance of the leakage transformer LTR substitutes. In addition, during the lighting of the discharge lamps FL ₁ and FL ₂ , the change rate of the lamp current is improved by half to 10% when there is no leakage transformer LTR, which is sufficiently practical to be used even in a large power discharge lamp.

9 shows an electrical circuit diagram of another embodiment of the present invention. The upper part of this embodiment of the eighth help is, the leakage transformer LTR and the tertiary winding N ₃ reinstall the primary winding N ₁ and the secondary winding N _2, the high-frequency transmission means, i.e., in Figure 4, or claim 8, Fig. Corresponds to the combination of primary winding W10 and secondary winding W20 of the Korean wave choke CH in the same time, while setting the secondary voltage to an appropriate value, and between the primary winding N ₁ and the secondary winding N ₂ of the leakage transformer LTR. The leakage impedance of the circuit is increased so that the Hallyu choke CH is omitted.

10 is an electric circuit diagram of a discharge lamp lighting apparatus of another embodiment of the present invention. In this embodiment, the discharge lamp is the FLR110H 1 lamp and the power supply voltage is 200V, so that the secondary voltage of the leakage transformer LTR is reduced to 150V. In addition, in order to offset the induced voltage by coupling from the tertiary winding N ₃ of the leakage transformer LTR to the primary winding N ₁ , in other words, the induced voltage by the primary winding N ₁ mixed in the tertiary winding N ₃ is reduced. The voltage V _K is taken as shown, by connecting the other end of the booster circuit R to any intermediate point of the primary winding of the leakage transformer LTR for adjustment.

As described above, according to the present invention, at least a transformer, a low frequency inductance, a resonant inductor, and a high frequency low frequency transmission means are used as one leakage transformer, so that the variation rate is extremely improved and the number of parts is greatly reduced. , Shape, weight and the like can be reduced, and the practical effect is very high.

Claims (1)

A leakage transformer having a low-frequency AC power supply, a primary winding connected to the low-frequency AC power supply, and a secondary winding leak-coupled to the primary winding; a discharge lamp connected to the secondary winding of the leakage transformer; and the low frequency AC power supply. A high frequency high voltage generating means for generating arc discharge to the discharge lamp at every cycle of the circuit, a high frequency transmitting means for delivering a high frequency high voltage generated by the high frequency high voltage generating means, and between the primary winding and the secondary winding of the leakage transformer. A discharge lamp lighting device comprising: a means for improving the variation due to leakage impedance.