KR20240013301A - Substrate integrated waveguide type sum and difference comparator using diagonal iris coupling and dielectric resonator antenna - Google Patents

Abstract

A substrate integrated waveguide (SIW) type sum-mode comparator using diagonal iris coupling includes a substrate; a transmission line for a sum mode formed by a first via arrangement formed to extend from the first side of the substrate; a transmission line for the primary mode formed by a second via arrangement formed to extend from the second side of the substrate; a comparator connected to the first via arrangement and the second via arrangement and formed by the third via arrangement; a first SIW filter connected to one side of the third via arrangement and formed by the fourth via arrangement; a second SIW filter connected to the other side of the third via arrangement and formed by the fifth via arrangement; a first output transmission line connected to the fourth via arrangement and formed by the sixth via arrangement; and a second output transmission line connected to the fifth via arrangement and formed by the seventh via arrangement, wherein the first SIW filter is connected to the upper left side of the comparator, and the second SIW filter is connected to the upper right side of the comparator. You can.

Description

SIW (Substrate Integrated Waveguide) type summation mode comparator and dielectric resonator antenna using diagonal iris coupling

The present invention relates to a substrate-integrated waveguide type sum-mode comparator and dielectric resonator antenna using diagonal iris coupling.

Monopulse antenna arrays are used to track targets within radar systems through precise radio wave angle of arrival (DoA) estimation capabilities.

Conventional horn, lens or Cassegrain parabolic antenna systems are heavy and very large. The monopulse antenna array with a microstrip line structure introduced to solve this problem has the advantages of small antenna size and low production cost, but has large loss and severe spurious radiation in the millimeter-wave band. There is a downside.

Meanwhile, Reference Paper 1 [Venanzoni, Giuseppe & Mencarelli, D. & Morini, Antonio & Farina, Marco & Losito, Onofrio & Prudenzano, F.. (2016). Compact double-layer substrate integrated waveguide magic Tee for X-band applications. Microwave and Optical Technology Letters. 58. 932-936. 10.1002/mop.29707.], Reference Paper 2 [H. Chu, J.-X. Chen, S. Luo and Y.-X. Guo, “A Millimeter-Wave Filtering Monopulse Antenna Array Based on Substrate Integrated Waveguide Technology,” in IEEE Transactions on Antennas and Propagation, vol. 64, no. 1, pp. 316-321, Jan. 2016, doi: 10.1109/TAP.2015.2497351.], each sum-mode antenna is presented.

Reference paper 1 above [Venanzoni, Giuseppe & Mencarelli, D. & Morini, Antonio & Farina, Marco & Losito, Onofrio & Prudenzano, F.. (2016). Compact double-layer substrate integrated waveguide magic Tee for X-band applications. Microwave and Optical Technology Letters. 58. 932-936. 10.1002/mop.29707.], a Substrate Integrated Waveguide (SIW) type Magic-T structure was applied to implement the summation mode. SIW Magic T structure is implemented by utilizing the bond between SIW and aperture, resulting in a layered structure.

Reference paper 2 [H. Chu, J.-X. Chen, S. Luo and Y.-X. Guo, “A Millimeter-Wave Filtering Monopulse Antenna Array Based on Substrate Integrated Waveguide Technology,” in IEEE Transactions on Antennas and Propagation, vol. 64, no. 1, pp. 316-321, Jan. 2016, doi: 10.1109/TAP.2015.2497351.], a structure combining a dual-mode SIW resonator (TE102/TE201) and a single-mode SIW resonator through a slot was applied to implement a sum-mode filtering antenna. Because this structure utilizes slots, a stacked structure is required.

Existing methods that use a magic T structure as in reference paper 1 or slot combination as in reference paper 2 have the disadvantage of increasing production costs because they require a laminated structure.

Korean Patent Publication No. 2021-0028709 (published on March 12, 2021)

The present invention is intended to solve the problems of the prior art described above, and seeks to design a substrate-integrated waveguide-type sum-mode comparator using diagonal iris coupling.

However, the technical challenges that this embodiment aims to achieve are not limited to the technical challenges described above, and other technical challenges may exist.

As a technical means for achieving the above-described technical problem, a Substrate Integrated Waveguide (SIW) type sum-mode comparator using diagonal iris combination according to the first aspect of the present invention includes a substrate; a sum mode transmission line formed by a first via arrangement extending from the first surface of the substrate; a second mode transmission line formed by a second via arrangement extending from the second surface of the substrate; a comparator connected to the first via arrangement and the second via arrangement and formed by a third via arrangement; a first SIW filter connected to one side of the third via array and formed by a fourth via array; a second SIW filter connected to the other side of the third via array and formed by a fifth via array; a first output transmission line connected to the fourth via arrangement and formed by a sixth via arrangement; and a second output transmission line connected to the fifth via arrangement and formed by the seventh via arrangement, wherein the first SIW filter is connected to the upper left side of the comparator, and the second SIW filter is connected to the comparator. It can be connected to the upper right side of .

The dielectric resonator antenna including the substrate-integrated waveguide type sum-mode comparator according to the second aspect of the present invention has the sum-mode comparator of claim 1 disposed on one side and the sum-mode comparator disposed on the other side, and serves as a radiator of a higher order mode. It may include a dielectric resonator (DR).

The above-described means for solving the problem are merely illustrative and should not be construed as limiting the present invention. In addition to the exemplary embodiments described above, there may be additional embodiments described in the drawings and detailed description of the invention.

According to one of the above-described means for solving the problems of the present invention, the present invention can design a substrate-integrated waveguide type sum-mode comparator using diagonal iris coupling. In addition, the present invention can form an electric field of the same size while having the same coupling coefficient in the summation mode through diagonal iris coupling.

FIG. 1A is a diagram for explaining a sum mode comparator according to an embodiment of the present invention.
FIG. 1B is a diagram for explaining a dielectric resonant antenna including a sum-mode comparator and a dielectric resonator according to an embodiment of the present invention.
2A to 2B are exemplary diagrams showing low-pass filter g-parameters and band-pass filter parameters according to an embodiment of the present invention.
3A to 3B are diagrams showing a first SIW filter (or second SIW filter) and a third SIW filter (or fourth SIW filter) according to an embodiment of the present invention.
4A to 4B are diagrams between the first SIW filter and the third SIW filter (or the second SIW filter and the fourth SIW filter) and the third SIW filter (or the fourth SIW filter), according to an embodiment of the present invention. This is a diagram showing the frequency response characteristics and coupling coefficient of the transmission coefficient according to the width of the iris and the diameter of the circular opening between the dielectric resonators.
Figures 5a and 5b are diagrams showing reflection coefficient characteristics and external quality coefficient according to the slot length or aperture diameter of the GCPW-SIW converter according to an embodiment of the present invention.
Figure 6 is a diagram showing the electric field distribution of a comparator combined with a filter according to an embodiment of the present invention.
Figure 7 is a diagram showing the frequency response characteristics and coupling coefficient of the transmission coefficient according to the width of the iris in a sum-mode comparator according to another embodiment of the present invention.

Below, with reference to the attached drawings, embodiments of the present invention will be described in detail so that those skilled in the art can easily implement the present invention. However, the present invention may be implemented in many different forms and is not limited to the embodiments described herein. In order to clearly explain the present invention in the drawings, parts that are not related to the description are omitted, and similar parts are given similar reference numerals throughout the specification.

Throughout the specification, when a part is said to be "connected" to another part, this includes not only the case where it is "directly connected," but also the case where it is "electrically connected" with another element in between. . Additionally, when a part "includes" a certain component, this means that it may further include other components rather than excluding other components, unless specifically stated to the contrary.

Hereinafter, specific details for implementing the present invention will be described with reference to the attached configuration diagram or processing flow diagram. Figure 1a is a diagram for explaining a sum mode comparator.

Referring to FIG. 1A, the sum mode comparator 100 includes a sum mode transmission line 108 formed by a first via arrangement extending from the first side of the substrate 106 and the second side of the substrate 106. It may include a transmission line 110 for the difference mode formed by a second via arrangement formed to extend from.

The sum mode comparator 100 may include a comparator 112 connected to the first via array and the second via array and formed by the third via array. Here, the comparator 112 may be a SIW dual-mode resonator operating in TE102 mode (sum mode) and TE201 mode (difference mode).

The sum-mode comparator 100 may include a first SIW filter 114 connected to one side of the third via array and formed by the fourth via array. Here, the first SIW filter 114 may be a SIW resonator operated in TE101 mode.

The sum mode comparator 100 may include a second SIW filter 116 connected to the other side of the third via array and formed by the fifth via array. Here, the second SIW filter 116 may be a SIW resonator operated in TE101 mode.

The first SIW filter 114 may be connected to the upper left side of the comparator 112, and the second SIW filter 116 may be connected to the upper right side of the comparator 112.

The coupling structure between the comparator 112 and the first SIW filter 114 (or the second SIW filter 116) has an inductive coupling structure through a diagonal iris made of a via hole. You can.

The first SIW filter 114 may be connected to the upper left side of the comparator 112, and the second SIW filter 116 may be connected to the upper right side of the comparator 112. That is, the first SIW filter 114 may be coupled to the comparator 112 through a diagonal iris, and the second SIW filter 116 may be coupled to the comparator 112 through a diagonal iris.

The sum mode comparator 100 is connected to the fourth via array, the first output transmission line 118 formed by the sixth via array, and the second output transmission line 118 formed by the seventh via array and connected to the fifth via array. It may include an output transmission line 120.

FIG. 1B is a diagram for explaining a dielectric resonant antenna including a sum-mode comparator and a dielectric resonator. Hereinafter, FIG. 1B will be described with reference to FIGS. 1A to 7.

Referring to FIG. 1B, the dielectric resonant antenna 200 may include a sum-mode comparator 104 and a dielectric resonator 102 according to another embodiment of the present invention.

The dielectric resonant antenna 200 to which the sum mode comparator 104 is applied can be used to track a target within a radar system through sophisticated Direction of Arrival (DoA) estimation capability.

The dielectric resonator 102 may function as a radiator of a higher order mode.

The sum-mode comparator 104 may be a comparator having a substrate-integrated waveguide-type structure.

The sum mode comparator 104 may include a Substrate Integrated Waveguide (SIW) power supply circuit.

The dielectric resonator 102 and the SIW power supply circuit have a preset first dielectric constant (e.g., ) and a preset first loss tangent (e.g., ) can be configured to have characteristics.

The substrate 106 used in the SIW power supply circuit has a preset second dielectric constant (e.g., ) and a preset second loss tangent (e.g., ) can be configured to have characteristics.

The SIW power supply circuit may be composed of an aperture for feeding power to the dielectric resonator 102 and a grounded coplanar waveguide (GCPW).

The dielectric resonator 102 uses a higher order mode (e.g., ) can be operated.

Approximate values for the height and diameter parameters of the dielectric resonator 102 operating in a high-order mode can be found by applying the magnetic wall method.

The diameter parameters and height parameters of the dielectric resonator 102, the size parameters of the opening surface, and the distance parameters between the opening surface and the dielectric resonator 102 may be designed to be optimized in a direction that maximizes the directionality of the dielectric resonator antenna 100.

After each parameter is optimized, the return loss and realized gain values of the optimized dielectric resonator antenna 100 are adjusted by adjusting the GCPW-SIW transition through the optimization function of the CST tool. It can be obtained. For example, the dielectric resonator antenna 100 may have a 10 dB return loss band of 3.3% at 27.65 GHz, a gain of 10.6 dBi in the E-plane, and a gain of 10.2 dBi in the H-plane.

On the other hand, if you want to design a dielectric resonant antenna 200 with a center frequency of 27.65 GHz, a reflection loss value in the pass band of the band pass filter of 15 dB, and a pass bandwidth of 700 MHz, first, a prototype of the low pass filter is used. ) We need to find the constants. The low-pass circular coefficient can be calculated through [Equation 1].

[Equation 1]

When this is implemented in the fourth order, the low-pass filter g-parameters can be derived as shown in Figure 2a. Conversion from the low-pass filter g-parameter to the band-pass filter parameter can be performed through [Equation 2].

[Equation 2]

The sum mode comparator 104 is a transmission line for the sum mode formed by a first via array formed to extend from the first side of the substrate and a transmission line for the difference mode formed by a second via array formed to extend from the second side of the substrate. May include transmission lines.

The sum mode comparator 104 may include a comparator 112 connected to the first via arrangement and the second via arrangement and formed by the third via arrangement.

Here, the comparator 112 may be a SIW dual-mode resonator operating in TE102 mode (sum mode) and TE201 mode (difference mode). The width and length of the comparator 112 can be derived through [Equation 3].

[Equation 3]

Referring to FIG. 6, at 27.65 GHz, the comparator 112 may have an electric field (a) distribution corresponding to the sum mode and an electric field distribution (b) corresponding to the difference mode. Due to the orthogonality of the sum mode and difference mode electric fields in the comparator 112 within the same frequency, excellent isolation performance is achieved between the sum mode port and the difference mode port.

The sum mode comparator 104 may include a first SIW filter 114 connected to one side of the third via array and formed by the fourth via array. Here, the first SIW filter 114 may be a SIW resonator operated in TE101 mode. For example, the resonance frequency of the first SIW filter 114 may be designed to have 27.65 GHz, which is the center frequency of the passband of the filter. The first SIW filter 114 can be designed through [Equation 4]. Figure 3a shows the design parameters (a) of the first SIW filter 114, the electric field distribution in the resonance mode of the first SIW filter 114 (b), and the frequency response characteristics of the transmission coefficient of the first SIW filter 114 (c). ) This is a drawing showing.

[Equation 4]

here, is the phase velocity of propagation in free space, is the dielectric constant of the substrate, is the width of the first SIW filter 114, is the length of the first SIW filter 114, is the diameter of the via hole, is the distance between the centers of two adjacent via holes.

The sum mode comparator 104 may include a second SIW filter 116 connected to the other side of the third via array and formed by the fifth via array. Here, the second SIW filter 116 may be a SIW resonator operated in TE101 mode. For example, the resonance frequency of the second SIW filter 116 may be designed to have 27.65 GHz, which is the center frequency of the filter's passband.

The coupling coefficient and external quality factor (external Q-factor) between the third SIW filter 122 (or fourth SIW filter 124) and the dielectric resonator 102 are the size of the opening that feeds the dielectric resonant antenna 200. It can be determined through the distance between and SIW shorted end. Figure 3b shows the design parameters (a) of the third SIW filter 122 (or fourth SIW filter 124), the electric field distribution (b) in resonance mode of the second SIW filter 116, and the frequency response characteristics of the transmission coefficient. This is a drawing showing (c).

The first SIW filter 114 may be connected to the upper left side of the comparator 112, and the second SIW filter 116 may be connected to the upper right side of the comparator 112. That is, the first SIW filter 114 may be coupled to the comparator 112 through a diagonal iris, and the second SIW filter 116 may be coupled to the comparator 112 through a diagonal iris. Figure 7 is a diagram showing the frequency response characteristics and coupling coefficient of the transmission coefficient according to the width of the iris in a state in which the comparator 112 is coupled to the first SIW filter 114 and the second SIW filter 116 through a diagonal iris. .

Through a symmetrically configured diagonal iris, electric field distributions of the same size can be formed in the sum mode and difference mode of the comparator 112 (see FIG. 6).

For example, taking the combination between the comparator 112 and the first SIW filter 114 as an example, when the TE102 mode corresponding to the sum mode is performed in the comparator 112, the first SIW filter 114 is connected through diagonal iris combination. ) is formed, and when the TE201 mode corresponding to the difference mode is performed in the comparator 112, the TE101 mode of the first SIW filter 114 can be formed through diagonal iris combination.

Through this, the coupling coefficient between the comparator 112 and the first SIW filter 114 and the coupling coefficient between the comparator 112 and the second SIW filter 116 can be substantially the same in the summation mode. Through this, the same filter characteristics required in summation mode can be implemented within a single substrate.

The coupling coefficient between the comparator 112 and the first SIW filter 114 can be derived through [Equation 5] since the resonance frequencies are the same.

[Equation 5]

The coupling structure between the comparator 112 and the first SIW filter 114 (or the second SIW filter 116) has an inductive coupling structure through a diagonal iris made of a via hole. You can.

The sum mode comparator 104 according to another embodiment of the present invention may include a third SIW filter 122 and a fourth SIW filter 124.

The third SIW filter 122 may be connected to the top of the first SIW filter 114, and the fourth SIW filter 124 may be connected to the top of the second SIW filter 116.

The third SIW filter 122 and the fourth SIW filter 124 may be SIW resonators operating in TE102 mode.

Figure 4a shows the frequency response characteristics (b) of the transmission coefficient according to the first width (a) of the iris and between the first SIW filter 114 and the third SIW filter 122 or the second SIW filter 116 and the fourth This is a diagram showing the coupling coefficient (c) of the SIW filter 124.

The coupling structure between the first SIW filter 114 and the third SIW filter 122 (or the second SIW filter 116 and the fourth SIW filter 124) may have an inductive coupling structure through an iris made of a via hole. there is.

When the resonance frequency of the first SIW filter 114 and the resonance frequency of the third SIW filter 122 (or the resonance frequency of the second SIW filter 116 and the resonance frequency of the fourth SIW filter 124) are the same, [ The coupling coefficient between the first SIW filter 114 and the third SIW filter 122 (or the second SIW filter 116 and the fourth SIW filter 124) can be derived through Equation 6.

[Equation 6]

The coupling coefficient between the third SIW filter 122 (or fourth SIW filter 124) and the dielectric resonator 102 may be determined by the diameter of the circular opening surface. Figure 4b shows the frequency response characteristic (b) of the transmission coefficient according to the diameter (a) of the circular opening surface and the coupling coefficient between the third SIW filter 122 (or fourth SIW filter 124) and the dielectric resonator 102. This is the drawing shown.

A plurality of design parameters for the sum-mode comparator 104 and the dielectric resonator 102 may be set so that the directionality of the dielectric resonator antenna 100 exceeds the threshold of the basic mode antenna directionality. Here, the plurality of design parameters may include a diameter parameter of the dielectric resonator 102, a height parameter, a size parameter of the aperture feeding the dielectric resonator 102, and a distance parameter between the aperture and the dielectric resonator 102. You can.

The external quality factor of the SIW filter applying GCPW can be determined by the tapering width and length of the GCPW transition unit and the slot length of the GCPW-SIW conversion unit. Figure 5a is a diagram showing the phase characteristics (b) and external quality coefficient (c) of the reflection coefficient according to the slot length (a) of the GCPW-SIW converter.

The coupling coefficient and external quality factor between the third SIW filter 122 (or fourth SIW filter 124) of the sum mode comparator 104 and the dielectric resonator 102 are circular openings for feeding power to the dielectric resonator 102. It can be determined by the diameter of . At this time, in order to simultaneously satisfy the coupling coefficient and external quality factor between the third SIW filter 122 (or fourth SIW filter 124) of the sum mode comparator 104 and the dielectric resonator 102, the opening surface and SIW short circuit termination The distance between the shortened ends must be adjusted additionally. Figure 5b shows the frequency response of the input impedance according to the opening surface diameter and the SIW resonator length (a) when the dielectric resonator 102 and the third SIW filter 122 (or fourth SIW filter 124) are coupled through the opening surface. This is a diagram showing (b) and external quality factor (c).

The description of the present invention described above is for illustrative purposes, and those skilled in the art will understand that the present invention can be easily modified into other specific forms without changing the technical idea or essential features of the present invention. will be. Therefore, the embodiments described above should be understood in all respects as illustrative and not restrictive. For example, each component described as single may be implemented in a distributed manner, and similarly, components described as distributed may also be implemented in a combined form.

The scope of the present invention is indicated by the claims described later rather than the detailed description, and all changes or modified forms derived from the meaning and scope of the claims and their equivalent concepts should be construed as being included in the scope of the present invention. .

100: sum mode comparator
200: dielectric resonant antenna
102: dielectric resonator
104: Addition mode comparator

Claims (9)

In the substrate integrated waveguide (SIW) type sum-mode comparator using diagonal iris coupling,
Board;
a sum mode transmission line formed by a first via arrangement extending from the first surface of the substrate;
a second mode transmission line formed by a second via arrangement extending from the second surface of the substrate;
a comparator connected to the first via arrangement and the second via arrangement and formed by a third via arrangement;
a first SIW filter connected to one side of the third via array and formed by a fourth via array;
a second SIW filter connected to the other side of the third via array and formed by a fifth via array;
a first output transmission line connected to the fourth via arrangement and formed by a sixth via arrangement; and
a second output transmission line connected to the fifth via arrangement and formed by the seventh via arrangement
Including,
The sum mode comparator wherein the first SIW filter is connected to the upper left side of the comparator, and the second SIW filter is connected to the upper right side of the comparator.
According to claim 1,
A sum-mode comparator wherein the comparator is an SIW dual-mode resonator operating in TE102 mode and TE201 mode.
According to claim 1,
The first SIW filter is a SIW resonator operated in TE101 mode,
The summation mode comparator wherein the second SIW filter is a SIW resonator operated in TE101 mode.
According to claim 1,
A sum-mode comparator wherein the coupling structure between the comparator and the first SIW filter or the second SIW filter has an inductive coupling structure through a diagonal iris made of a via hole.
In the dielectric resonator antenna including a substrate integrated waveguide (SIW) type sum-mode comparator,
The sum mode comparator of claim 1 disposed on one side, and
A dielectric resonator (DR) is placed on the other side and acts as a radiator for higher order modes.
A dielectric resonator antenna comprising a.
According to claim 5,
The plurality of design parameters for the dielectric resonator are such that the direction of the dielectric resonator antenna is set in a direction that exceeds a threshold of basic mode antenna directionality,
The plurality of design parameters include a diameter parameter of the dielectric resonator, a height parameter, a size parameter of an aperture that feeds the dielectric resonator, and a distance parameter between the aperture and the dielectric resonator. .
According to claim 5,
A sum-mode comparator wherein the coupling coefficient between the sum-mode comparator and the dielectric resonator is determined by the diameter of a circular opening for feeding power to the dielectric resonator.
According to claim 5,
The external quality factor of the SIW filter to which the GCPW (Grounded coplanar waveguide) is applied is determined by the tapering width and length of the GCPW transition unit and the slot length of the GCPW-SIW conversion unit. A sum-mode comparator.
According to claim 5,
A sum-mode comparator in which the coupling coefficient and external quality coefficient between the third SIW filter or the fourth SIW filter and the dielectric resonator are determined by the diameter of the circular opening surface and the distance between the opening surface and the SIW shorted end. .

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