KR20160088792A - Communication method and apparatus based on a filter bank multi-carrier modulation - Google Patents

Abstract

The present disclosure relates to a 5G or pre-5G communication system which will be provided to support a higher data transmission rate after a 4G communication system, such as an LTE system. According to the present disclosure, provided are a method for transmitting a signal based on filter bank multi-carrier (FBMC) modulation, a method for receiving a signal based on FBMC modulation, a corresponding transmission device, and a corresponding reception device. The method for transmitting a signal based on FBMC modulation comprises the steps of: preprocessing predetermined symbols in a data block including at least one symbol; modulating the preprocessed data block by using FBMC modulation; removing a part or all of tailing data by truncating the modulated data block; and transmitting the truncated modulated data block. In this case, the part or all of tailing data has been removed from the data block, and the predetermined symbols are symbols that are influenced by the truncation.

Description

Field of the Invention [0001] The present invention relates to a communication method and apparatus based on a filter bank multi-carrier modulation,

This disclosure relates to the field of mobile communications, and more particularly to filter bank multiple carrier modulation based communications.

All. A typical FBMC utilizes a technique called offset quadrature amplitude modulation (OQAM) to maximize spectral efficiency. Thus, this technique is referred to as the FBMC / OQAM system and is also referred to as the OFDM / OQAM system. The use of FBMC in digital communications was discussed earlier in an article entitled "Analysis and design of OFDM / OQAM systems based on filter bank theory (IEEE Transactions on Signal Processing, Vol. 50, No. 5, 2002)".

Since FBMC has some beneficial properties that OFDM does not have, FBMC is noticed in 5G research, but some inherent problems are a problem in the use of mobile communications, and these problems need to be resolved urgently, do. One of these problems is that the filters employed in the FBMC cause a long tail effect, also known as a transition period problem. During uplink multi-user transmission based on short data blocks (data frames), if the length of the data blocks includes a tail effect to avoid overlapping between the tail and other data blocks, The number of symbols to be processed is reduced, and the spectral efficiency is reduced. On the other hand, if the length of the data block does not include a tail effect, the portion of the tail will overlap with other data blocks (in particular, data blocks from other users) and, if not resolved appropriately, Block interference, and further reduces spectrum utilization efficiency. In addition to multi-user interference, in a time division duplexing (TDD) system, to avoid unnecessary uplink / downlink crosstalk caused by the tail effect, the uplink / And the increased conversion period reduces the spectral efficiency of the system. Presently, the existing method is to truncate portions of the tail to avoid overlapping with other data blocks. However, truncation of the waveform causes distortion of the signal, and distortion of the signal affects the efficiency of the spectrum. Further, the spectrum of the truncated signals is extended to produce inter-carrier interference (ICI). Accordingly, such direct cutting is not effective.

In conclusion, in order to improve the competitiveness of FBMC among the candidate technologies, it is required to solve inherent problems in addition to developing beneficial characteristics. It is important to use efficient methods to solve the problems caused by the tail effect of the FBMC in the mobile communication system, especially for the IoT scenarios, for the service modes for sporadic connection in various scenarios of 5G.

For the tailing problem in FBMC systems where data blocks are transmitted, there is not yet an efficient way to reduce the impact on the system by the smearing effect.

In one embodiment of the present disclosure, a method of signal transmission based on a Filter Bank Multiple Carrier (FBMC) is provided.

According to a first aspect of the disclosure, there is provided a method of signal transmission based on a filter bank multi-carrier (FBMC) modulation. The signal transmission method includes the steps of preprocessing predetermined symbols in a data block including one or more symbols, modulating a data block using FMBC modulation, truncating the modulated data block, Removing some or all of the tailing data of the modulated data block; and transmitting a modulated data block wherein some or all of the tailing data is removed, These are the affected symbols.

In one embodiment, the step of preprocessing the predetermined symbols comprises pre-coding predetermined symbols.

In one embodiment, the precoding matrix used for precoding is determined according to the parameters used for FBMC modulation and the parameters used for truncation.

In one embodiment, the parameter used for cutting comprises a predetermined cut length.

In one embodiment, the precoding matrix has a dimension of N x N or N ₀ x N ₀ , where N is the number of scheduling sub-carriers, N ₀ is a fixed value and less than N, and N ₀ x N ₀ The precoding matrix with dimensions is repeatedly used to precode N ₀ sub-carrier signals in predetermined symbols to precode all N sub-carrier signals.

In one embodiment, the precoding matrix may be an inverse of an intercarrier interference matrix generated by the modulated data block after truncation, or an estimated inter-carrier interference matrix based on a minimum mean square error (MMSE) criterion Pseudo-inverse-matrix.

In one embodiment, the precoding process includes adjusting the precoding dynamically based on the modulation order used for the predetermined symbols.

In one embodiment, the process of adjusting precoding includes disabling precoding when the predetermined symbols are modulated with low order modulation, enabling the precoding to be enabled when the predetermined symbols are modulated with high order modulation (enabling) the process.

In one embodiment, the process of pre-processing the predetermined symbols comprises assigning reference signals in the data block to predetermined symbols.

In one embodiment, the step of assigning reference signals in the data block to predetermined symbols comprises allocating interference cancellation symbols or guard symbols in the reference symbols to the predetermined symbols.

In one embodiment, pre-processing the predetermined symbols comprises allocating the predetermined symbols to the channels required for the low order modulation mode in the data block.

In one embodiment, the channels required for low order modulation include control channels.

In one embodiment, the process of pre-processing the predetermined symbols comprises allocating the data contained in the symbols other than the predetermined symbols in the initially transmitted data block to the predetermined symbols.

In one embodiment, the process of truncating the modulated data block includes selecting a truncation length such that the length of the truncated data block is an integer unit.

In one embodiment, the process of truncating the modulated data block includes at least one of setting a part or all of the tailing data to zero, and windowing some or all of the tailing data .

In one embodiment, the process of truncating the modulated data block is performed such that the adjacent frequency leakage of the truncated data block is less than a predetermined threshold, and the number of blocks in time zones of the plurality of data blocks from one or more users And the interferences do not exceed a predetermined level.

According to a second aspect of the present invention, there is provided a method of receiving a signal based on a filter bank multi-carrier (FBMC) modulation. The signal receiving method includes receiving one or more symbols in a data block according to a predetermined cut length, and demodulating each of the symbols based on the FBMC demodulation mode.

In one embodiment, the receiving of the symbols comprises receiving the uncorrupted portion of the symbols when transmitted, wherein predetermined symbols affected by the truncation are received.

In one embodiment, the process of demodulating each of the symbols comprises padding the un-truncated portion of the symbols to zero according to a predetermined truncation length, for predetermined symbols affected by truncation so that the original length of the symbols , And demodulating symbols having the original symbol length based on the FBMC.

According to a third aspect of the present disclosure, a transmitting apparatus is provided. The transmitting apparatus includes a preprocessing unit for preprocessing predetermined symbols in a data block including one or more symbols, a modulating unit for modulating the preprocessed data block using filter bank multi-carrier modulation, A truncating unit for truncating the modulated data block to remove some or all of the tailing data of the data block; and a truncating unit for truncating the modulated data block to remove some or all of the tailing data, Wherein the predetermined symbols are affected by the truncation.

According to a fourth aspect of the present disclosure, a receiving apparatus is provided. The receiving apparatus includes a receiving unit that receives one or more symbols in a data block according to a predetermined cut length, and a demodulating unit that demodulates each of the symbols based on a filter bank multi-carrier demodulation mode.

The present disclosure provides a method for suppressing tailing which ensures high signal reception performance and frequency spectrum leakage effects to maximize frequency spectrum efficiency of a filter bank multi-carrier (FBMC) system, Thereby preventing additional consumption due to the effect.

Further features, objects, and advantages of the present disclosure will become more apparent in light of the detailed description of the following non-limiting examples with reference to the accompanying drawings.
Figure 1 shows a block diagram for the generation of FBMC / OQAM signals.
FIG. 2 illustrates an exemplary flowchart 200 of a method for signal transmission based on Filter Bank Multi Carrier Modulation according to an exemplary embodiment of the present disclosure.
Figure 3 shows a schematic diagram for a cut data block and signal.
Figure 4 shows the performance simulation results of a precoding method according to an exemplary embodiment of the present disclosure.
5 shows a schematic diagram for reference signal allocation in a data block.
Figure 6 shows a schematic diagram for reference signal allocation including zero value protection symbols.
Fig. 7 shows a schematic diagram of the allocation of the first transmission data block and the retransmission data block.
Figure 8 shows a schematic view of two cutting methods.
Figure 9 shows a schematic for a frequency domain response for two cutting methods.
Figure 10 shows a schematic diagram of the overlap between data blocks using a truncation method involving windowing.
11 illustrates an exemplary application in a multi-user uplink scenario according to an embodiment of the present disclosure.
12 illustrates an exemplary application in a time division duplexing (TDD) system according to an embodiment of the present disclosure.
FIG. 13 shows a flowchart 1300 of a receive method based on a Filter Bank Multi Carrier Modulation according to embodiments of the present disclosure.
Figure 14 shows a schematic transmitting apparatus according to an exemplary embodiment of the present disclosure.
15 shows a schematic receiving apparatus according to an exemplary embodiment of the present disclosure.

The operation principle of various embodiments will be described in detail with reference to the accompanying drawings. In the following description, well-known functions or constructions are not described in detail since they would obscure the invention in unnecessary detail. The following terms are defined in consideration of functions in various embodiments and may vary depending on the intention of a user, an operator, or the like. Therefore, the definition should be based on the contents throughout this specification.

The present disclosure is described below for a technique for transmitting and receiving a filter bank multi-carrier based signal in a wireless communication system.

The term referring to the control information used in the following description, the term (for example, a mode) indicating a state change, the term referring to a component of the apparatus, and the like are illustrated for convenience of explanation. Accordingly, the present invention is not limited to the following terms, and other terms having equivalent technical meanings can be used.

Without conflict, embodiments and features of the embodiments of the present disclosure may be combined. Hereinafter, the present disclosure will be described in detail with reference to the accompanying drawings which are connected to the embodiments.

Signal waveforms with improved time / frequency localization (TFL) can be obtained through modulation based on a filter bank multi-carrier (FBMC), and the FBMC can be obtained using an isotropic orthogonal transformation algorithm may be based on prototype filter functions such as an isotropic orthogonal transform algorithm (IOTA), an extended Gaussian function (EGA), and a European PHYDYAS. The FBMC can implement pulse shaping for each subcarrier signal by using a shaping filter with an improved TFL. Thus, 1) FBMC can greatly suppress inter-symbol interference (ISI) from multipaths without cyclic prefix (CP) and obtain higher frequency spectrum efficiency and energy efficiency than OFDM Also, by allowing asynchronous transmission, high reception reliability can be obtained even with an increased timing synchronization error. 2) Using the improved TFL, the FBMC can transmit signals in a very narrow frequency band and can suppress ICI from Doppler and phase noise to maintain low out-of-band leakage. Thus, the FBMC has great potential for fragmented band access and asynchronous transmission.

Offset quadrature amplitude modulation (OQAM) is required to obtain the maximum frequency spectral efficiency of the FBMC, and OQAM may be referred to as FBMC / OQAM or OFDM / OQAM (hereinafter referred to as OQAM). In OQAM, one OQAM symbol is divided into two signals, and the two divided signals are alternately modulated to the real or imaginary part of the subcarriers, respectively, and the modulated signals are transmitted with the time offset. At the receiving end, if there is no influence from the channel, the transmitted signal can be recovered by alternately extracting the real or imaginary part for each subcarrier.

Figure 1 shows an exemplary block diagram for generating an FBMC / OQAM signal.

As shown in FIG. 1, M parallel data is obtained after complex-modulated input data such as a complex QAM (Quadrature Amplitude Modulation) symbol is serial-to-parallel converted through a serial-to-parallel conversion module 101, ≪ / RTI > Each of the signals is divided into two signals, and the real part and the imaginary part of the two signals are extracted through the real part extraction module 102 and the imaginary part extraction property 103, respectively. Then, the real and imaginary parts of the signals are respectively modulated through the inverse fast Fourier transform module 104, respectively. The modulated signals are sent to a synthesis filter bank module 105 that performs pulse shaping. Finally, the real and imaginary parts of the signals are combined and the combined signals are output to the OQAM signal via the parallel / serial conversion module 106.

The functions of each module shown in Figure 1 can be easily understood from mathematical signal modeling of OQAM signals. The equivalent form of the baseband of the continuous-time multi-carrier FBMC / OQAM signal can be expressed as Equation 1 below.

는 주파수-시간 포인트이고,

는 n번째 심볼의 m번째 서브-캐리어에 대한 실수 변조된 신호를 나타낸다. 즉, 펄스 진폭 변조(pulse amplitude modulation, PAM) 심볼

는 심볼 주기

인 복소수 QAM 심볼

의 실수부 또는 허수부의 값을 나타내며 아래의 수학식2와 같다.here

Is a frequency-time point,

Represents a real-modulated signal for the m-th sub-carrier of the n-th symbol. That is, a pulse amplitude modulation (PAM) symbol

Symbol period

Complex QAM symbol

And is expressed by Equation 2 below. &Quot; (2) "

및

는 각각 추출한 실수부 및 추출한 허수부를 나타낸다.

는 허수를 나타내며,

는 실수-허수 교대를 나타내며, 이는 도 1의

를 통해 나타난다. M은 서브-캐리어의 개수를 나타내는 짝수이다. Z는 전송된 심볼의 집합이다.

는 서브-캐리어 간의 스페이싱을 나타낸다.

는 OQAM의 심볼 주기를 나타내며

이다.

는 프로토타입(prototype) 필터 함수로, 시간 영역 임펄스 응답 길이는 일반적으로

곱하기

이며, 인접한

심볼들의 시간 영역 파형의 오버래핑을 발생시키고, 그리하여

는 일반적으로 필터의 오버래핑 인자로 지칭된다.

는

를 변조하기 위한 완전한 합성 필터 함수이다. OQAM의 심볼 레이트(symbol rate)는 종래의 순환 전치(cyclic prefix, CP)의 더함 없는 OFDM 의 심볼 레이트의 2배임을 알 수 있다. OQAM의 변조가 실수에 기반하기 때문에, 각각의 OQAM 심볼의 정보량은 종래의 OFDM의 그것의 절반이다. 즉, OQAM 시스템의 신호 전송 레이트는 CP없는 OFDM 시스템의 그것과 같다.

And

Represent the extracted real part and the extracted imaginary part, respectively.

Lt; / RTI > represents an imaginary number,

Represents a real-to-imaginary alternation,

Lt; / RTI > M is an even number indicating the number of sub-carriers. Z is a set of transmitted symbols.

Represents spacing between sub-carriers.

Represents the symbol period of OQAM

to be.

Is a prototype filter function, and the time domain impulse response length is generally

multiply

Lt; / RTI >

Overlapping of the time domain waveforms of the symbols,

Is generally referred to as the overlapping factor of the filter.

The

Lt; / RTI > is a complete synthesis filter function for modulating a signal. It can be seen that the symbol rate of the OQAM is twice the symbol rate of the OFDM without the addition of the conventional cyclic prefix (CP). Since the modulation of OQAM is based on a real number, the amount of information in each OQAM symbol is half that of conventional OFDM. That is, the signal transmission rate of the OQAM system is the same as that of the OFDM system without the CP.

를 설계함으로써 획득된다. 전송단에서의 합성 필터 함수 및 수신단에서의 분석 필터 함수의 내적(inner product)은 수학식 3 또는 수학식 3과 근사하게 만족시킬 필요가 있으며, 이는 프로토타입 필터가 이하의 수학식을 만족할 필요가 있다는 것이다.The real field orthogonality of OQAM is the prototype filter function

. The inner product of the synthesis filter function at the transmission end and the analysis filter function at the reception end needs to be approximated to Equation 3 or Equation 3 because the prototype filter needs to satisfy the following equation It is.

는 실수부를 추출하는 연산자,

는 내적, 만약

및

이면 각각

，

이고 다른 경우에는 0이다. 즉, 만약

또는

이면, 내적은 순 허수이다. 설명의 편의를 위해서,

는 내적을 나타내기 위해 이용된다. 다른 서브-캐리어들 및 다른 심볼들 사이의 신호들에 의해 생성된 간섭은 순 허수부 간섭임이 명백하다. 따라서, FBMC/OQAM에 의해 변조된 신호

가 왜곡으로부터 자유로운 채널(distortion-free channel)을 통과할 때, 송신 합성 필터(synthesis filter, SF)와 매칭되는

수신 분석 필터 (analysis filter, AF)

를 통하여 수신된 신호를 수학식 4에 따라 간단하게 처리함으로써 원래의 전송된 실수 신호

의 완벽한 복원(perfect reconstruction, PR)이 획득될 수 있다.Where * denotes a complex conjugate,

An operator for extracting a real part,

Is inner, if

And

Respectively.

,

And 0 otherwise. That is,

or

The inner product is the net imaginary. For convenience of explanation,

Is used to denote the inner product. It is clear that the interference generated by the signals between different sub-carriers and other symbols is pure imaginary interference. Therefore, the signal modulated by the FBMC / OQAM

When it passes through a distortion-free channel, it is matched with a synthesis filter (SF)

Analysis filter (AF)

Lt; RTI ID = 0.0 > (4) < / RTI > by simply <

A perfect reconstruction (PR) can be obtained.

는 잡음 성분으로서 복소 QAM 신호

를 합성함으로써 원래의 데이터가 변조될 수 있다.here,

As a noise component, a complex QAM signal

The original data can be modulated.

As noted above, an important problem of the FBMC is that the applied filter can cause a long tailing effect of the time domain waveform. If the tailing portion is truncated, signal distortion will occur and will affect the frequency spectral efficiency.

FIG. 2 illustrates an exemplary flowchart 200 of a method for signal transmission based on Filter Bank Multi Carrier Modulation according to an exemplary embodiment of the present disclosure.

As shown in FIG. 2, in step 201, predetermined symbols in a data block including one or more symbols are preprocessed.

Then, in step 202, the preprocessed data block is modulated with filter bank multi-carrier modulation.

Thereafter, in step 203, the modulated data block is truncated to remove some or all of the tailing data.

Finally, in step 204, the modulated data block (a data block from which some or all of the tailing data has been removed) is transmitted.

In preprocessing step 201, the predetermined symbols are the symbols to be affected by the truncation. For example, the predetermined symbols are symbols near the cutting location, such as the first and last symbols, which are symbols that can be distorted due to cutting.

In order to maintain high signal reception performance and frequency spectral leakage performance and to maximize the frequency spectral efficiency of the filter bank multi-carrier system, by pretreating the symbols to be affected by truncation prior to truncation, the tailing effect due to truncation is effectively suppressed .

There are many ways to preprocess predetermined symbols. Hereinafter, methods of transmitting signals according to embodiments of the present disclosure will be described with reference to specific examples.

Example 1

In this embodiment, the preprocessing process comprises pre-coding predetermined symbols, i. E. Precoding the frequency domain multi-carrier signals, which is then for countering the interference from the truncation .

For the sake of clarity, if the predetermined symbols are not preprocessed, the interference from the truncation must be analyzed.

개의 서브-캐리어들을 이용하는 것을 가정하면, 데이터 블록은 28개의 OQAM 심볼들(

)을 포함하고, 오버래핑 인자

및 PHYDYAS 필터는 필터 파라미터로서 이용된다. 시간 영역 응답은 이하의 수학식으로 표현될 수 있다.For example,

Assuming that there are a total of 28 sub-carriers, the data block contains 28 OQAM symbols (

), And the overlapping factor

And the PHYDYAS filter are used as filter parameters. The time domain response can be expressed by the following equation.

이다.here,

to be.

이다. 상대적으로, 동일한 레이트를 가지나 CP가 제외된 OFDM 데이터 블록 (14개의 OFDM 심볼들)은

개의 시간 영역 샘플링 포인트들을 포함한다. 이 둘을 비교함으로써, OQAM의 변조 방법은

개의 시간 영역 샘플링 포인트들을 더 가지며,

개의 샘플링 포인트들은

개의 샘플링 포인트들을 이용한 정형 필터들의 파형들의 적용으로부터 발생한 것이며, 다른

개의 샘플링 포인트들은 OQAM 변조의 IQ(in-phase/quadrature) 채널들의 딜레이로부터 발생한 것이다. 일반적으로, 이러한 샘플링 포인트들은 테일링 효과처럼 보여질 수 있다. 만약

개의 샘플링 포인트들이 OQAM 데이터 블록의 2개의 측면에서 각각 절단된다면, OQAM 변조의 테일링 효과는 완전히 제거될 것이다. 그러나, 이러한 절단과정은 파형, 특히 앞과 끝 OQAM 심볼들에 큰 영향을 미치고, 그리하여 데이터 블록의 수신 성능의 저하를 유발한다.At this time, the number of time-domain sampling points of the data block is

to be. Relatively, an OFDM data block (14 OFDM symbols) having the same rate but excluding the CP is

Lt; / RTI > time-domain sampling points. By comparing the two, the modulation method of OQAM is

Further having time-domain sampling points,

The number of sampling points

Lt; RTI ID = 0.0 > of the waveforms of the shaping filters using < / RTI >

The number of sampling points is derived from the delay of the in-phase / quadrature (IQ) channels of the OQAM modulation. In general, these sampling points can be seen as a tailing effect. if

If the two sampling points are each cut off at two sides of the OQAM data block, the tailing effect of the OQAM modulation will be completely eliminated. However, such a truncation process greatly affects the waveform, especially the leading and trailing OQAM symbols, thus causing a deterioration of the reception performance of the data block.

Fig. 3 (a) shows a diagram schematically illustrating the cutting of data blocks for 400 sampling points on each of two sides. The left panel of Fig. 3 (a) shows the signal waveform of the complete data block, and the right panel shows the signal waveform of the data block after the cut.

FIG. 3 (b) shows the truncation of the first OQAM symbol of the data block shown in FIG. 3 (a), where 400 sampling points are truncated at the beginning of the symbol. The left panel of Fig. 3 (a) shows the complete waveform of the OQAM symbol and the right panel shows the waveform of the truncated OQAM. The cutting process as shown in Fig. 3 sets the signals in the cut region directly to zero.

는 심볼상에 허수부-실수부가 교대로 있는 신호를 변조하는 것과 같이 정의되며,

는 순 실수 신호이고,

는 허수 부호이다. 채널 및 잡음의 영향을 제외하면, 수신된 신호는

이며,

는 복소 신호이다. 전송된 신호 및 수신된 신호의 관계는 이하의 수학식과 같이 나타낼 수 있다.

Is defined as modulating a signal with imaginary-real numbers alternating on the symbol,

Is a net real number signal,

Is an imaginary sign. Except for the effects of channel and noise, the received signal is

Lt;

Is a complex signal. The relation between the transmitted signal and the received signal can be expressed by the following equation.

는 간섭 행렬이다.here,

Is an interference matrix.

는 인접한 캐리어들에 대한 캐리어의 간섭 인자이며, 순 실수이다. 심볼간 간섭(inter-symbol interference, ISI)보다는, 오직 캐리어간 간섭(inter-carrier interference, ICI)만이 고려된다는 것이 주목되어야 하는데 이는 이후의 분석에서 설명되는 것과 같이 ICI가 절단에 따른 지배적인 효과를 가져오기 때문이다. 수학식 6에 따르면, 간섭 행렬의 대각 성분들이 1이고 간섭 인자(interference factor)

는 실수이기 때문에, 수신기에 의해 수신된 간섭은 실수부 및 허수부를 추출함으로써 제거될 수 있다. 도 3에서 도시된 것과 같은 절단 과정을 수행할 때, 수신된 신호는 ICI에 의해 영향을 받을 것이고 ICI는 실수부 및 허수부를 추출함으로써 제거될 수 없다. 이 때, 신호의 모델은 이하의 수학식 7과 같이 표현될 수 있다.

Is the interference factor of the carrier for adjacent carriers, and is the net real number. It should be noted that only inter-carrier interference (ICI) is considered, rather than inter-symbol interference (ISI), which is the dominant effect of ICI It is because of import. According to Equation (6), when the diagonal elements of the interference matrix are 1 and the interference factor is 1,

Is a real number, the interference received by the receiver can be removed by extracting the real and imaginary parts. 3, the received signal will be affected by the ICI and the ICI can not be removed by extracting the real and imaginary parts. At this time, the model of the signal can be expressed by the following Equation (7).

,

,

는 복소수이고, 전송된 신호

는

로부터 실수부 및 허수부를 추출함으로써 회복될 수 없다.

로 신호를 정의함으로써 이하의 수학식 8이 획득될 수 있다.According to Equation (7)

,

,

Is a complex number, and the transmitted signal

The

Can not be recovered by extracting the real part and the imaginary part.

The following equation (8) can be obtained.

는 등가 간섭 행렬이다.here

Is an equivalent interference matrix.

,

,

는 순 실수들이다. 여기서, 등가 간섭 행렬은 순 실수들로 구성된다. 즉, 실수부 및 허수부가 수신단에서 추출되는 PAM 신호는 원래의 PAM 신호에 순 실수들로 구성된 등가 간섭 행렬을 곱한 것과 같다.

,

,

Are net errors. Here, the equivalent interference matrix is composed of net real numbers. That is, the PAM signal whose real part and imaginary part are extracted from the receiving end is equal to the original PAM signal multiplied by the equivalent interference matrix composed of pure real numbers.

Thus, in the present disclosure, a precoding matrix may be used at the transmitting end to precode the transmitted signals to overcome interference due to disruption.

For example, the precoding of transmitted signals may be expressed as: < EMI ID = 9.0 >

는

의 차원을 갖는 프리코딩 행렬이다. 그러면, 실수-허수가 반복된

가 OQAM 변조를 이용함으로써 전송단에서 전송된다. 그리하여, 적절한 프리코딩 행렬

를 선택하는 것은 절단 과정으로부터의 ICI 를 효과적으로 극복할 수 있다. 등가 간섭 행렬 및 필터 뱅크 멀티-캐리어 변조에서 이용되는 필터 파라미터들은 절단 과정에서 이용되는 파라미터들과 관련되기 때문에, 절단 과정으로부터의 간섭에 대응하기 위한 프리코딩에 이용되는 프리코딩 행렬은 필터 뱅크 멀티-캐리어 변조에서 이용되는 파라미터들 및 절단 과정에서 이용되는 파라미터들에 기반하여 결정될 수 있다.here

The

≪ / RTI > Then, the real-imaginary is repeated

Is transmitted at the transmitting end by using OQAM modulation. Thus, a suitable precoding matrix

Can effectively overcome the ICI from the cutting process. Since the filter parameters used in the equivalent interference matrix and filterbank multi-carrier modulation are related to the parameters used in the truncation process, the precoding matrix used for precoding to correspond to the interference from the truncation process is the filter bank multi- The parameters used in the carrier modulation and the parameters used in the truncation process.

는 절단 이후 생성된 캐리어간 간섭 행렬의 역행렬이다. 미리 결정된 절단 길이 및 필터 파라미터가 결정된 경우, 등가 간섭 행렬

는 오프라인(off-line) 계산 및 시뮬레이션을 통해 획득될 수 있다. 그리하여,

에 기반하여 계산된 프리코딩 행렬이 적용될 수 있고(예를 들면,

) 절단 과정에 의해 영향을 받는 특정 심볼들은 전송단에서 프리코딩될 수 있다.In one embodiment, the precoding matrix may be determined using a zero forcing method, which is a simple and effective method. The precoding matrix in this example is as follows.

Is the inverse of the intercarrier interference matrix generated after truncation. If the predetermined cut length and filter parameters are determined, the equivalent interference matrix

Can be obtained through off-line calculation and simulation. therefore,

May be applied (e. G., ≪ RTI ID = 0.0 >

) The specific symbols affected by the truncation process may be precoded at the transmitting end.

In another example, an estimation method may be used, e.g., the precoding matrix may be estimated based on a minimum mean square error (MMSE) criterion. The precoding matrix estimated by the MMSE criterion is a pseudo-inverse-matrix of the intercarrier interference matrix generated after the truncation process.

From the above analysis it can be seen that the precoding matrix is only related to the filter parameters and the cut length. Thus, the calculation of the precoding matrix can be performed off-line, greatly reducing the implementation complexity of the algorithm.

의 차원을 가지며,

은 스케줄된 서브-캐리어들의 개수이다.

이 상대적으로 클 때, 프리코딩(수학식 9와 같은 프리코딩)은 여전히 높은 계산 복잡도를 갖는다.In some embodiments, the precoding matrix < RTI ID = 0.0 >

And,

Is the number of scheduled sub-carriers.

Is relatively large, precoding (precoding like Equation 9) still has a high computational complexity.

Optionally, in some embodiments, the precoding matrix used for precoding may have a fixed dimension. This matrix may be used to precode a sub-carrier block with a fixed length, and precoding may be repeated to precode all N sub-carrier signals. Since OQAM has improved frequency localization, most of the interference is concentrated near adjacent carriers, i. E. The interference matrix has a nonzero value only near the diagonal components. Thus, a method with low complexity is to use a precoding matrix with only a relatively small fixed dimension. For example, a precoding matrix having a fixed dimension can be expressed by the following equation.

는

의 차원을 갖는 프리코딩 행렬이며,

이고,

는 프리코딩 고정된 최소의 프리코딩 단위 차원이다.here

The

, ≪ / RTI >

ego,

Is the smallest precoding unit dimension precoded.

가 적절한 값으로 이용될 수 있다.

는

의 차원을 갖는 행렬이며,

의 성분은

의 행 1 내지

및 열 1 내지

의 성분과 각각 같다. 이는 아래의 수학식 11과 같다.For example, in a long term evolution (LTE) system, a physical resource block (PRB) comprising 12 sub-carriers is the smallest scheduling unit. therefore,

Can be used as an appropriate value.

The

, ≪ / RTI >

≪ / RTI &

≪ / RTI >

And columns 1 -

Respectively. This is shown in Equation (11) below.

를 통해

개의 서브-캐리어들을 프리코딩할 수 있으며, 모든 N개의 서브-캐리어들이 프리코딩될 때까지 프리코딩과정을 반복할 수 있으며, 그리하여 행렬 계산의 복잡도는 크게 감소될 수 있고, 특히 많은 캐리어가 있을 때 복잡도가 크게 감소될 수 있다.Thus,

Through the

The number of sub-carriers can be precoded and the precoding process can be repeated until all N sub-carriers are precoded, so that the complexity of matrix computation can be greatly reduced, especially when there are many carriers The complexity can be greatly reduced.

In a transmission system, the transmitting end generally dynamically adjusts the modulation and coding scheme (MCS) according to the state of the channel. When low order modulation, such as BPSK or QPSK modulation, is used for the data block, the effect on demodulation of the signal from the truncation can be ignored. Thus, in some examples, precoding can be dynamically adjusted based on the modulation and coding scheme used by the symbols in the data block. For example, when symbols are modulated with low order modulation, precoding is not essential, so the precoding module can be terminated, deactivated, or omitted. When the symbols are modulated by a high order modulation, for example, precoding can be performed by activating or activating the precoding module.

개의 서브-캐리어들을 이용하고, 반복 인자는

이며, 데이터 블록은 28개의 OQAM 심볼들을 포함하고, 필터는 PHYDYAS 필터이고, 채널은 ETU(Extended Typical Urban) 채널이고, 변조 방식은 64QAM이다. 도 4는 프리코딩 없는 절단 과정의 성능 시뮬레이션 결과 및 본 실시 예의 프리코딩을 포함한 절단뿐만 아니라, 절단 과정없는 시스템 성능 시뮬레이션 결과를 각각 도시한다. 도 4에서 도시된 것과 같이, 시스템이 절단 과정을 수행할 때(예를 들면 본 시뮬레이션에서, 2개의 측면 각각에 대해

개의 샘플링 포인트들을 절단), 신호대 잡음 비(signal-noise ratio, SNR)이 높을 때의 시스템의 비트 에러 레이트(bit error rate, BER)의 성능은 저하된다. 프리코딩의 방법을 이용할 때, 본 실시 예의 시뮬레이션에서, 상술된 것과 같은 낮은 복잡도의 프리코딩은 오직 첫번째 심볼 및 마지막 심볼에 대해서만 수행된다. 절단으로 인한 성능 저하가 사라진다는 것을 알 수 있다. 그 결과로서, 본 개시의 실시 예에 의해 제공되는 프리코딩의 방법은 데이터 블록의 절단으로부터의 성능의 영향을 효과적으로 제거할 수 있다.Figure 4 shows the performance simulation results of a precoding method according to an exemplary embodiment of the present disclosure. In the illustrated simulation,

Lt; / RTI > sub-carriers, and the repetition factor is

, The data block includes 28 OQAM symbols, the filter is a PHYDYAS filter, the channel is an ETU (Extended Typical Urban) channel, and the modulation scheme is 64QAM. Fig. 4 shows a simulation result of performance of a precoding-free cutting process and a result of simulation of a system performance without a cutting process as well as cutting including precoding of the present embodiment, respectively. As shown in Fig. 4, when the system performs a cutting process (e.g., in this simulation, for each of the two sides

The performance of the system's bit error rate (BER) when the signal-to-noise ratio (SNR) is high is degraded. When using the method of precoding, in the simulation of the present embodiment, precoding of low complexity as described above is performed only for the first symbol and the last symbol. It can be seen that the performance deterioration due to cutting disappears. As a result, the method of precoding provided by embodiments of the present disclosure can effectively remove the effect of performance from the cutting of the data block.

Example 2

In this embodiment, the predetermined symbol preprocessing process includes selecting a signal assigned to a predetermined symbol according to another condition for a data block to be transmitted.

In one implementation, the preprocessing process includes assigning a required reference signal in a data block to a predetermined symbol that is affected by the truncation process.

In general, in a data block, in addition to payload data, certain resources must be preserved to transmit a reference signal, so that the receiver can perform channel estimation. Since the reference signals are known signals and the influence from the cutting process mainly relates to the known ICI, assigning the reference signals to the symbols affected by the truncation process allows the receiver to perform a complete channel estimation.

5 shows a schematic diagram for reference signal allocation in a data block. As shown in FIG. 5, the reference signal is allocated to the two symbols of the outermost. The reference signal may be interference by ICI after the truncation process. For example, the interference can be expressed by the following equation (12).

는 원래의 기준 신호 벡터이다.here

Is the original reference signal vector.

는 수신단에서 계산될 수 있고, 기준 신호 벡터에 따라 채널 추정이 수행되는데, 즉,

이며, 여기서

은 주파수 영역에서 n 번째 서브-캐리어에 수신된 복소 신호이고

은 주파수 영역 채널 추정치이다.Since both the interference matrix and the original reference signal are known, the reference signal vector

Can be calculated at the receiving end, and channel estimation is performed according to the reference signal vector, that is,

, Where

Is the complex signal received on the nth sub-carrier in the frequency domain

Is a frequency domain channel estimate.

Further, in an OQAM system, ISI interference in an OQAM system is always considered in the design of the reference signal. Thus, the use of special protection symbols is proposed in some reference signal designs. The protection symbols may be zero-value protection symbols or other interference cancellation symbols that are generated to remove interference to the reference signal.

Thus, in some embodiments, assigning an intended reference signal in a data block to a predetermined symbol affected by the truncation procedure includes assigning a guard symbol or interference cancellation symbols in the reference signal to a predetermined symbol. Thus, within the truncated data block, the zero value protection symbol may be assigned to the truncated symbol. The truncation procedure has no effect on the system, since the receiver does not use zero value symbols.

Figure 6 shows a schematic diagram for reference signal allocation including zero value protection symbols. As shown in FIG. 6, the zero value protection symbols are affected by the truncation, while the reference signal is unaffected. Other reference signal designs using interference cancellation methods can be applied to similar assignments, so that only symbols for interference cancellation can be affected by truncation.

In another implementation, the preprocessing process may include assigning a channel requiring a lower order of modulation in the data block to a predetermined symbol affected by the truncation process.

As described above, in the transmission system, the transmission end can dynamically adjust the modulation and coding scheme according to the channel state. When the data block employs a low order modulation mode, for example BPSK or QPSK modulation, the effect of the truncation procedure on signal demodulation is negligible. As a result, a channel that requires modulation of a lower order in a data block, such as, but not limited to, a control channel, may be assigned to a predetermined symbol that is affected by truncation. Since the control channel always utilizes low order modulation, the system performance will not be significantly affected despite the disconnection process.

In another implementation, the preprocessing process includes allocating data in un-predetermined symbols in an initial transmission data block to predetermined symbols that are affected by interference when transmitting a retransmitted data block .

In a system using an automatic retransmission query (ARQ), the retransmission signal may apply soft combining to the original signal. The truncation process affects particular symbols, and thus the data loaded on these symbols are likely to be subject to strong interference. Thus, an interleaving method may be used in the retransmission data block in the system, so that other data may be loaded into specific symbols of the retransmission data block.

Fig. 7 shows a schematic diagram of the allocation of the first transmission data block and the retransmission data block. As shown in Fig. 7, # 1 and # N in the original transmission data block are assigned to predetermined symbols affected by truncation. In the retransmission data block, # 2 and # N-1 are allocated to predetermined symbols affected by truncation. Thus, some data will not be affected by two consecutive truncations during the soft combination of the two transmissions.

It is noted that the pretreatment methods in Examples 1 and 2 can be implemented individually or in combination. For example, in one implementation, the reference signal and the predetermined symbol in the data block assigned to the predetermined symbols to be affected by the truncation can be precoded simultaneously. In this way, interference due to disruption can be eliminated or offset to the reference signal. It is noteworthy that various combinations are possible without collision by an ordinary technician. Such combinations are not enumerated herein.

Example 3

The truncation used in Embodiment 1 and Embodiment 2 is to set the signals in the cutout section directly to 0, that is, to set some or all of the tailing data to zero. This method has the advantage that the length of the data block can be effectively reduced. The problem with this method, however, is that the frequency domain localization of the signal degrades due to corruption of the waveform, and this degradation causes strong out-of-band leakage. In this embodiment, truncation may include windowing for some or all of the tailing data. In one implementation, some of the sampling points in the cut region may be set to zero and windowing may be performed on the remaining sampling points. For example, assuming the data block in Example 1, 448 sample points on both sides of the data block are truncated, 200 sample points are set to 0, and the remaining 248 sample points are windowed.

Fig. 8 shows a schematic diagram of two cutting methods, the left drawing shows a direct zero setting cutting method, and the right drawing shows a zero setting and windowing method. 8, 200 sample points are set to zero, and the remaining 248 sample points can be windowed using a Hamming window.

To compare the effects or functions of the two cutting methods, Fig. 9 shows a schematic diagram of the frequency-domain response of the two methods. As shown in FIG. 9, the windowing for a portion of the sample points can cause the frequency-domain response of the waveform to quickly roll off, thereby obtaining improved frequency domain localization and reducing out-of-band leakage .

When the windowing method is used for truncation, it is important that a guard period (GP) between two data blocks for avoiding inter-block interference (IBI) needs to be set. When not considering sampling errors and channel delays, the minimum guard interval between two data blocks may be the number of windowed sample points and the windowing area where two data blocks overlap.

Figure 10 shows a schematic diagram of the overlap between a plurality of data blocks when using a windowing cut method. As shown in FIG. 10, two data blocks (data block 1 and data block 2) have an overlap of 248 sample points which is equal to the number of windowed sample points. Since the windowed sample points belong to the cutout area, the windowed sample points will not be received at the receiving end, so the receiving method is the same as the receiving method of the?

In certain systems, zero-setting cutting and windowing cutting can be considered together based on the channel's delay characteristics, out-of-band leakage requirements, and data block design requirements and other factors. Thus, in some embodiments, the zero set length and / or windowing length may be selected to satisfy the following conditions. (1) The adjacent channel leakage of a data block after disconnection does not exceed a predetermined threshold value. (2) the interference between the plurality of data blocks from one or more users does not exceed a predetermined level.

For example, based on Embodiment 1, a data block may be configured as follows. One data block of 1 ms contains 28 valid QAM symbols and uses 200 sample points for windowing. The guard interval between blocks is 256 sample points, and the windowed sample points effectively suppress out-of-band leakage. The data block configuration has 56 sample points used to avoid interference between blocks due to channel delay and synchronization errors. The sampling rate may be 3.84 MHz, which is the same as LTE.

In some embodiments, the truncation length may be selected such that the length of the truncated data block is an integer unit. For example, the integer unit may be 1 ms, 5 ms, 10 ms, and so on.

Based on the design described above, the data block can reduce the length of the data block, and the length of the data block can reduce the limited spectral overhead and maintain improved frequency domain localization. This data block design significantly improves the performance of a wireless communication system, especially in the case of an uplink multi-user or TDD system.

11 illustrates an exemplary application in a multi-user uplink scenario according to an embodiment of the present disclosure. The upper diagram of FIG. 11 is a non-truncated data block, and the lower diagram is a data block truncated through windowing according to the embodiment of the present disclosure. When multiple users transmit signals alternately, the guard interval set on both sides of the data block must be more than smearing on both sides to avoid inter-block interference. The guard interval between blocks is significantly reduced for the data block using the truncation method, and the spectral efficiency is greatly improved. Thus, the truncation method can significantly improve spectrum utilization when used for uplink multi-user cross-transmission. An inter-block guard region is not needed if a plurality of data blocks of a user are consequently scheduled, i.e., the improvement of the truncated data block in spectral efficiency is small for a single transmission of a single user.

12 illustrates an exemplary application in a time division duplexing (TDD) system according to an embodiment of the present disclosure. The upper diagram in Fig. 12 is a non-truncated data block, and the lower diagram is a data block truncated through windowing according to the embodiment of the present disclosure. In the TDD system, a guard interval for switching slots of the downlink and the uplink needs to be set in order to avoid crosstalk between the downlink and the uplink. Due to the blurring phenomenon, un-truncated data blocks increase the need for guard intervals or extension of the guard interval, thus reducing spectral efficiency. If the truncation method is used for the last symbol of the downlink data block and the preceding symbol of the uplink data block, the length of the guard interval of the uplink and the downlink will be shortened and thus the spectral efficiency can be improved.

A method for signal transmission based on filter bank multi-carrier modulation provided in various embodiments according to the present disclosure has been described above with reference to the accompanying drawings. According to the embodiments provided herein, blurring due to truncation can be effectively suppressed by preprocessing the symbols affected by truncation prior to cutting, thereby protecting the high signal reception performance and spectral leakage characteristics and improving the spectral efficiency of the FBMC system Can be maximized. Accordingly, this disclosure provides a corresponding method of signal reception.

FIG. 13 shows a flow diagram 1300 of a receive method based on a Filter Bank Multi-Carrier Modulation according to embodiments of the present disclosure.

As shown in FIG. 13, in step 1310, one or more symbols in a data block are received according to a predetermined cut length.

Since the disconnection of the data block transmitted at the transmitting end has been performed, the receiving process at the receiving end can only be reception of valid data only to avoid interference. Since the cut length is already determined, the receiving end can receive only the truncated data block within the correct time synchronization. That is, when receiving or sampling predetermined symbols that are affected by truncation, only symbols that are not truncated at the transmitting end are received or sampled. For example, the transmitting end in Example 1 cuts 448 sample points in each of the sides, so that the receiving needs to receive only 14 x M = 3584 sample points.

Then, in step 1320, each symbol may be demodulated through a demodulation mode based on a filter bank multi-carrier.

In some implementations, when precoding is performed at the transmitting end, the process of demodulating each symbol through the demodulation mode based on the filter bank multi-carrier is performed on the predetermined symbols affected by the truncation of step 1321, A step of demodulating the symbols having the original symbol length based on the filter bank multi-carrier of step 1322, a step of demodulating the symbols having the original symbol length, , I.e., a conventional OQAM demodulation.

Because precoding is performed at the transmitting end, the receiving end does not require additional processing and the signal can be demodulated by conventional OQAM demodulation after zero padding.

When a zero setting truncation is used at the transmitting end, the part of the received non-truncated symbols is padded with zeros and demodulated by the method described above. When the windowing cut is used in the transmitting end, the windowed sample points are not received because they are included in the cutout area, and the receiving method is the same as the receiving method when the zero setting cutting method is used.

In some other implementations, a pre-processing procedure for a predetermined symbol at a transmitting end includes selecting a signal assigned to a predetermined symbol for different conditions of data blocks to be transmitted, A corresponding receiving method can be used.

Wherein the pre-processing for the predetermined symbol comprises assigning the intended reference signal in the data block to a predetermined symbol affected by the truncation, the receiving end can calculate the truncated reference signal vector, and based on the reference signal vector, To perform channel estimation because the original canonical signal is a known signal and the ICI due to truncation is also known, i.e., the interference matrix is known.

When the preprocessing process for a predetermined symbol is the process of assigning a channel requiring a low order modulation mode in a data block to a predetermined symbol affected by truncation, the signal can be demodulated and received in a conventional manner, This is due to the effect of disconnection on the demodulation of the signal of the low order modulated data block.

The process for the predetermined symbol comprises transmitting the retransmitted data block and allocating the data contained in the non-predetermined symbols in the initially transmitted data block to predetermined symbols affected by the truncation , The retransmitted signal and the original signal are soft-combined so that no data is affected by the truncation in the data block. Thus, the receiving and demodulating processes can be performed in a conventional manner.

Figure 14 shows a schematic block diagram of a transmitting device configured to implement an exemplary embodiment in accordance with an exemplary embodiment of the present disclosure.

As shown in FIG. 14, the transmission apparatus 1400 may include a preprocessing section 1410, a modulating section 1420, a cutting section 1430, and a transmitting section 1440.

The preprocessing unit 1410 is configured to preprocess predetermined symbols in a data block including one or more symbols, and the predetermined symbols are the symbols affected by the truncation.

In some embodiments, preprocessor 1410 is configured to precode predetermined symbols. The precoding matrix used for precoding is determined according to the filter parameters used for filterbank multi-carrier modulation and the parameters used for truncation.

In some embodiments, preprocessor 1410 is configured to assign the required reference signals in the data block to predetermined symbols.

In some other embodiments, the preprocessor 1410 is configured to allocate the predetermined symbol (s) to a channel that requires low order modulation in the data block.

In some other embodiments, preprocessor 1410 is configured to allocate data for predetermined symbols in a data block that is initially transmitted when the data block is a retransmitted data block, to predetermined symbols.

A demodulator 1420 is configured to modulate the preprocessed data block using filter bank multi-carrier modulation.

Cutting section 1430 is configured to cut modulated data blocks to remove some or all of the tailing data.

In some embodiments, cuts 1430 are further configured to select a cut length such that the cut data block is an integer multiple.

In some embodiments, the cutter 1430 is configured to perform the cutting process through at least one of the following procedures: setting all or a portion of the tailing data to zero, and windowing some or all of the tailing data . The zero set length and / or windowing length may be selected such that at least one of the following conditions is satisfied: the adjacent channel leakage of the data block after truncation does not exceed a predetermined threshold, The interference between the blocks of the plurality of data blocks of the data block does not exceed a predetermined level.

Transmitter 1440 is configured to transmit demodulated data blocks after truncation.

The various units and sub-units included in the transmission apparatus 1400 are configured to implement the exemplary embodiments of the present disclosure. Thus, the above-described operations and features described in conjunction with FIGS. 2 to 12 can be applied to the units / sub-units of the transmission apparatus 1400 and the transmission apparatus 1400, and a detailed description of the apparatus is omitted.

Figure 15 shows a schematic block diagram of a receiving device that is configured to implement the exemplary embodiments of the present disclosure.

As shown in FIG. 15, the receiving apparatus 1500 includes a receiving section 1510 and a demodulating section 1520.

Receiver 1510 is configured to receive one or more symbols in a data block. Receiving unit 1510 is further configured to receive or sample only a portion of the truncated symbol at the transmitting end when a predetermined symbol affected by truncation is received or sampled.

The demodulator 1520 is configured to demodulate the respective symbols based on the filterbank multi-carrier demodulation mode.

In some embodiments, when precoding is performed at the transmitting end, the demodulator 1520 may be configured to perform, for predetermined symbols affected by the truncation, a portion of the symbols that have not been truncated according to a predetermined truncation length padding to obtain symbols with the original length of the symbols and demodulate the symbols with the original symbol length based on the filterbank multi-carriers after zero padding, i.e., perform conventional OQAM demodulation.

The units and sub-units included in the receiving apparatus 1500 are configured to implement the exemplary embodiments of the present disclosure. Thus, the above-described operations and features described in connection with Fig. 13 can be applied to the units / sub-units of the receiving apparatus 1500 and the receiving apparatus 1500, and a detailed description thereof will be omitted below.

Modules in the embodiments according to the present disclosure may be implemented using hardware, software, or a combination of hardware and software. Additionally, the modules described in this disclosure may be implemented within a processor. For example, it can be described as follows: A processor including a request receiving module, an information reading module, a view building module, and a function enabling module. (processor). The names of the modules in some cases are not intended to impose any restriction on the modules themselves. For example, the request receiving module may be described as a " module receiving a request submitted by the user to call widgets ".

Methods according to the claims of the present disclosure or the embodiments described in the specification may be implemented in hardware, software, or a combination of hardware and software.

Such software may be stored on a computer readable storage medium. The computer-readable storage medium includes at least one program (software module), at least one program that when executed by the at least one processor in an electronic device includes instructions that cause the electronic device to perform the method of the present disclosure .

Such software may be in the form of non-volatile storage such as volatile or read only memory (ROM), or in the form of random access memory (RAM), memory chips, For example, in the form of a memory such as an integrated circuit or in the form of a compact disc-ROM (CD-ROM), a digital versatile disc (DVDs), a magnetic disc, tape, or the like. < / RTI >

The storage and storage media are embodiments of machine-readable storage means suitable for storing programs or programs, including instructions that, when executed, implement the embodiments. Embodiments provide a program including code for implementing an apparatus or method as claimed in any one of the claims herein, and a machine-readable storage medium storing such a program. Furthermore, such programs may be electronically delivered by any medium, such as a communication signal carried over a wired or wireless connection, and the embodiments suitably include equivalents.

In the above-described specific embodiments, elements included in the invention have been expressed singular or plural in accordance with the specific embodiments shown. It should be understood, however, that the singular or plural representations are selected appropriately for the sake of convenience in describing the present invention. It is to be understood that the above-described embodiments are not limited to the singular or plural constituent elements, , And may be composed of a plurality of elements even if they are represented by a single number.

While the invention has been shown and described with reference to certain exemplary embodiments thereof, it will be understood by those skilled in the art that various changes and modifications may be made without departing from the spirit and scope of the invention as defined by the appended claims. Therefore, the scope of the present invention should not be limited by the illustrated embodiments, but should be determined by the scope of the appended claims, as well as the appended claims.

Claims (21)

A method for signal transmission based on a filter bank multi-carrier (FBMC) modulation,
Comprising the steps of: preprocessing a predefined symbol in a data block including at least one symbol;
Modulating the pre-processed data block using the FBMC modulation;
Truncating the modulated data block to remove some or all of the tailing data of the modulated data block;
And transmitting the truncated data block,
Wherein the predetermined symbol is a symbol affected by a truncation.
The method according to claim 1,
Wherein the step of pre-processing the predetermined symbol comprises:
And pre-coding the predetermined symbol.
3. The method of claim 2,
Wherein the precoding matrix used for precoding is determined according to a parameter used for FBMC modulation and a parameter used for truncation.
The method of claim 3,
Wherein the parameter used for the cutting comprises a predetermined cutting length.
The method of claim 3,
Wherein the precoding matrix has a dimension of N x N or N0 x N0 where N is the number of scheduling sub-carriers, N0 is a fixed value and less than N,
Wherein the precoding matrix having the dimension of N0 x N0 is repeatedly used to precode N0 sub-carrier signals in the predetermined symbol to precode all N sub-carrier signals.
The method of claim 3,
The precoding matrix may be calculated by using an inverse of an intercarrier interference matrix generated by the modulated data block after truncation or a pseudo inverse matrix of an intercarrier interference matrix estimated based on a minimum mean square error (MMSE) pseudo-inverse-matrix.
3. The method of claim 2,
And adjusting the precoding dynamically based on a modulation order used for the predetermined symbol.
8. The method of claim 7,
The process of adjusting the precoding includes:
Disabling precoding when the predetermined symbol is modulated with low order modulation;
And enabling precoding when the predetermined symbol is modulated with high order modulation.
The method according to claim 1,
Wherein the step of pre-processing the predetermined symbols comprises:
And allocating the required reference signals in the data block to the predetermined symbol.
10. The method of claim 9,
Wherein the step of allocating the reference signals in the data block to the predetermined symbol comprises:
And allocating an interference cancellation symbol or a guard symbol in the reference symbol to the predetermined symbol.
The method according to claim 1,
Wherein the step of pre-processing the predetermined symbol comprises:
And assigning to the predetermined symbols the channels needed for the low order modulation mode in the data block.
12. The method of claim 11,
Wherein the channels required for the low order modulation include control channels.
The method according to claim 1,
Wherein the step of pre-processing the predetermined symbols comprises:
Allocating data included in an un-predetermined symbol in a first transmitted data block to the predetermined symbol.
The method according to claim 1,
Wherein the step of cutting the modulated data block comprises:
And selecting a cut length such that the length of the truncated data block is an integer unit.
The method according to claim 1,
Wherein the step of cutting the modulated data block comprises:
Setting a part or all of the tailing data to 0;
And windowing a part or all of the tailing data.
16. The method of claim 15,
Wherein the step of cutting the modulated data block comprises:
Wherein adjacent frequency leakage of the truncated data block is less than a predetermined threshold and interblock interference in time zones of a plurality of data blocks from one or more users does not exceed a predetermined level ≪ / RTI >
A method of receiving a signal based on a filter bank multi-carrier (FBMC) modulation,
Receiving at least one symbol in a data block according to a predetermined cut length;
And demodulating the symbol based on an FBMC demodulation mode.
18. The method of claim 17,
Wherein the step of receiving the symbol comprises:
And receiving a predetermined symbol affected by the truncation when receiving the truncated portion of the symbol when transmitted.
19. The method of claim 18,
The process of demodulating the symbol includes:
Obtaining a symbol having an original length of the symbol by padding an uncut portion of the symbol to zero according to the predetermined cut length for the predetermined symbol affected by the truncation;
And demodulating the symbol having the original symbol length based on the FBMC.
In the transmitting apparatus,
A preprocessing unit for preprocessing a predetermined symbol in a data block including at least one symbol,
A modulator for modulating the pre-processed data block using filter bank multi-carrier modulation;
A truncating unit for truncating the modulated data block to remove some or all of the tailing data from the data block;
And a transmitter for transmitting the truncated data block,
Wherein the predetermined symbol is a symbol affected by a truncation.
In the receiving apparatus,
A receiver for receiving at least one symbol in a data block according to a predetermined cut length;
And a demodulator for demodulating the symbol based on a filter bank multi-carrier demodulation mode.

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