KR20150022579A - Power supply device - Google Patents

Abstract

According to the embodiment of the present invention, the voltage stress of a semiconductor device can be reduced by using a power device which has a first and a second amplification part which shares an energy storage device. A output voltage outputted to the first and the second amplification part can be constantly controlled while independently controlling the amplification rate of the first and the second amplification part. An inrush current applied to the first and the second amplification part in an initial driving process can be prevented.

Description

POWER SUPPLY DEVICE

The present invention relates to a power supply device.

Generally, a capacitor input type rectifier circuit is used as a switching power source used as a power source for an electronic device. These capacitors cause pulse-like input currents, and pulse-type input currents occur simultaneously at the inputs of each electronic, information, and communication device, so they are added in phase to the power distribution line to produce harmonics in the power system and power factor .

In order to solve this problem, a study on a control circuit of a boost type PFC (Power Factor Correction) having a power factor correction function is actively studied.

1 is a diagram of a conventional boost converter type power supply.

1, an input power source is connected to both ends of a rectifier 2, and an inductor 3, which is an energy storage element, is connected between the rectifier 2 and the switching device 4 , And a diode is connected between the switching element (4) and the capacitor.

The power supply device 1 amplifies the voltage on the input side by a predetermined ratio and outputs the amplified voltage to the output stage 5.

When a high voltage such as a line-to-line voltage in the three-phase system is applied to the power supply device 1, a very large high voltage is applied to the output stage 5. Therefore, the voltage stress of the semiconductor element at the output stage is increased, and an IGBT (Insulated Gate Bipolar Transistor) element is used as a switching element rather than a FET (Field Effect Transistor) element. Therefore, there is a disadvantage that a low switching frequency must be used as the IGBT element is used. In addition, there is a limitation in the design of the power supply device, such as an increase in the size of a passive element and an increase in cost.

The embodiment provides a power supply device for reducing voltage stress of a semiconductor device in a power supply device.

Embodiments provide a power supply that constantly controls the output voltage of the first and second output units within the power supply.

The embodiment provides a power supply device that forms a path of an inrush current formed at the time of initial operation of the power supply device.

The power supply unit according to the embodiment includes a rectifying unit for rectifying an AC voltage to a first voltage, a boosting unit for boosting the voltage by receiving the first voltage from the rectifying unit, and outputting the boosted voltage as a second voltage and a third voltage, And an inrush current path portion providing a path of an inrush current via the amplifying portion.

In the power supply apparatus according to the embodiment, the amplifying unit may include a first amplifying unit receiving the first voltage and outputting the second voltage, a second amplifying unit amplifying the first voltage and outputting the third voltage, And an inrush current path portion connected between the first and second amplifying portions and an inductor.

In the power supply apparatus according to the embodiment, the first amplifying unit includes the first switching unit and the first output unit connected between the first and second nodes, and the second amplifying unit includes the first switching unit and the second output unit, 2 switching element and a second output.

In a power supply apparatus according to an embodiment, the first output unit includes a first diode and a first capacitor-resistor unit, and the second output unit includes a second diode and a second capacitor-resistor unit.

In the power supply device according to the embodiment, the capacitors and the resistors included in the first and second capacitor-resistor portions are connected in parallel to each other, the first diode is connected between the second node and the fifth node, A diode is connected between the third node and the sixth node, the first capacitor-resistor portion is connected between the first and fifth nodes, and the second capacitor-resistor portion is connected between the fourth and sixth nodes And the inductor is connected between the second and third nodes.

In the power supply apparatus according to the embodiment, the inrush current path unit has one end connected to the first diode and the other end connected to the second diode.

In a power supply apparatus according to an embodiment, the inrush current path portion is a third diode.

Wherein the third diode in the power supply device according to the embodiment is connected between the fifth and sixth nodes.

In the power supply apparatus according to the embodiment, the third diode has an anode terminal connected to the anode terminal of the first diode, and a cathode terminal connected to the cathode terminal of the second diode.

In a power supply apparatus according to an embodiment, the inrush current path portion includes an inrush current control diode and an inrush current control resistor.

In the power supply apparatus according to the embodiment, the rush current path portion is connected between the fifth and sixth nodes, and the rush current control diode and the inrush current control resistor are connected in series with each other.

In the power supply apparatus according to the embodiment, when the power supply apparatus is initially driven, an inrush current flows through the first capacitor, the inrush current preventing unit, and the second capacitor.

In the power supply apparatus according to the embodiment, the second and third voltages are equal to each other.

In the power supply apparatus according to the embodiment, the first and second switching elements are simultaneously turned on and turned off.

In the power supply apparatus according to the embodiment, the first switching element is turned off at a first time point,

The second switching element is turned off at a second time point and the first time point arrives after a second time point when the first voltage has a value larger than the second voltage.

Wherein the first and second switching elements are simultaneously turned on in the power supply apparatus according to the embodiment.

The voltage stress of the semiconductor device can be reduced by using the power supply device including the first and second amplifying units sharing the energy storage device. The first and second amplifying units may individually adjust amplification ratios to maintain the output voltages of the first and second amplifying units constant. In addition, it is possible to prevent breakage of various circuit elements such as a switching element by forming an inrush current path formed in the first and second amplifying units when the power source apparatus is initially driven.

1 is a diagram of a conventional boost converter type power supply device
2 is a block diagram of a power supply apparatus 1000 according to an embodiment of the present invention.
Figures 3a and 3b show a power supply device according to an embodiment of the present invention;
4 is a diagram illustrating an operation method when the first and second switching elements Qs and Qm of the power supply device according to the first embodiment of the present invention are turned on
5 is a view showing an operation method when the first and second switching elements Qs and Qm of the power supply device according to the first embodiment of the present invention are turned off
6 is a diagram illustrating an operation method when the first switching device Qs of the power supply device according to the first embodiment of the present invention is turned off and the second switching device Qm is turned on
7 is a diagram illustrating an operation method when the first switching device Qs of the power supply device according to the first embodiment of the present invention is turned on and the second switching device Qm is turned off
8 is a view showing a power supply device according to a second embodiment of the present invention
9 is a view showing a control unit of a power supply apparatus according to a second embodiment of the present invention
10 is a diagram showing an analog control unit of a power supply device according to a second embodiment of the present invention;
11 is a circuit diagram of the first and second dual feedback units.
12 and 13 are circuit diagrams of a power supply device according to an embodiment of the present invention and a control section for driving the power supply device
14 is a diagram showing a simulation result of a power supply device according to an embodiment of the present invention

Hereinafter, a power supply device according to an embodiment of the present invention will be described in detail with reference to the drawings. The following embodiments are provided by way of example so that those skilled in the art can fully understand the spirit of the present invention. Therefore, the present invention is not limited to the embodiments described below, but may be embodied in other forms.

FIG. 2 is a block diagram of a power supply apparatus 1000 according to an embodiment of the present invention, and FIGS. 3A and 3B illustrate a power supply apparatus 1000 according to an embodiment of the present invention.

The power supply apparatus 1000 according to the embodiment of the present invention can be used in a system that requires an output voltage higher than the input voltage, that is, a power boost.

For example, it can be used in a battery, a solar panel, a rectifier and a direct current generating device, and can be used as a voltage supply device for an LED panel or as an apparatus for boosting a gate drive voltage of an LCD panel .

2, 3A and 3B, a power supply apparatus 1000 according to an embodiment of the present invention includes a power supply unit 11 including a rectifying unit 10, first and second amplifying units 20 and 30, An inductor 40 and an inrush current path portion 60, which are elements.

The rectifier (10) receives the input AC power and rectifies it and outputs it. The rectifying unit 10 may be a bridge rectifier and may include first to fourth diodes D1 to D4.

The rectifying unit 10 may rectify the input AC power to the first and second nodes and output the rectified current to the third node and the fourth node.

The connection relationship of the first to fourth diodes D1 to D4 of the rectifying unit 10 will be described.

And an anode connected to the P region of the first through fourth diodes D1 through D4 and a cathode connected to the N region.

The anode terminal of the first diode D1 is connected to the first node N1, and the cathode terminal is connected to the third node N3.

The anode terminal of the second diode D2 is connected to the fourth node N4, and the cathode terminal is connected to the second node N2.

The anode terminal of the third diode D3 is connected to the second node N2, and the cathode terminal is connected to the third node N3.

The anode terminal of the fourth diode D4 is connected to the fourth node N4, and the cathode terminal is connected to the second node N2.

The inductor 40, which is an energy storage element synchronized with the operation of the first and second switching elements Qs and Qm, accumulates energy and supplies the accumulated energy to the first and second amplifying units 20 and 30 Can be repeated.

The first and second amplifying units 20 and 30 are synchronized with the inductor 40 and can amplify and output the input voltage.

The first amplifier 20, the second amplifier 30, and the inductor 40 may be connected in series with each other. The inductor 40 is disposed between the first amplifying unit 20 and the second amplifying unit 30, but the present invention is not limited thereto.

The inductor 40, the first amplifying unit 20 and the second amplifying unit 30 are arranged in series in this order or the first amplifying unit 20, the second amplifying unit 30 and the inductor 40 are arranged in series .

The inrush current path unit 60 provides a path through which an inrush current that may be generated at the time of initial operation of the power supply apparatus 1000 flows so that the current flowing through the inrush current path unit 60 It is possible to solve the problem that the device must be applied.

The inrush current path unit 60 may be connected between the first amplifying unit 20 and the second amplifying unit 30.

The first and second amplifying units 20 and 30 may have a circuit configuration as shown in FIG. 3A.

Hereinafter, the fifth node N5 is defined as a super node of the sixth node N6 and seventh node N7.

The first amplifying unit 20 may be connected between the third node N3 and the fifth node N5.

The second amplifying unit 30 may be connected between the fifth node N5 and the fourth node N4. Therefore, the first and second amplifying units 20 and 30 may be connected in series with each other.

An inductor 40 may be connected between the sixth node N6 and the seventh node N7.

The position of the inductor 40 is not limited to that described above.

Can be connected on the third node N3 between the rectifier 10 and the first amplifying part 20 and connected on the fourth node N4 between the rectifier 10 and the second amplifying part 30 It is possible. Therefore, the rectifier 10, the first and second amplifying units 20 and 30, and the inductor 40 may be connected in series with each other.

The first amplification unit 20 may include a first switching device Qs and a first output unit 21 connected in parallel with the first switching device Qs.

The second amplifying unit 30 may include a second switching unit Qm and a second output unit 31 connected in parallel with the second switching unit Qm.

The first output portion 21 may include a first capacitor 22, a first resistor 23, and a first output portion diode 24.

The first capacitor 22 and the first resistor 23 may be connected in parallel to each other, and the first output sub-diode 24 may be connected to the first capacitor 22 and the first resistor 23 in series.

3A, the first output sub-diode 24 is connected between the fifth node N5 and the eighth node N8, but the present invention is not limited thereto. The first output sub-diode 24 may be connected to the first switching sub- Qs and the first capacitor 22 on the third node N3 in the forward direction.

 The second output portion 31 may include a second capacitor 32, a second resistor 33, and a second output portion diode 34.

The second capacitor 32 and the second resistor 33 may be connected in parallel with each other, and the second output sub-diode 34 may be connected in series with the second capacitor 32 and the second resistor 33.

In the drawing, the second output unit diode 34 is connected between the fifth node N5 and the ninth node N9, but is not limited thereto.

The second output sub-diode 34 may be connected on the fourth node N4 between the second switching device Qm and the second capacitor 32 in the forward direction.

3A, the inrush current path unit 60 includes a tenth node N10, a second capacitor 32, and a second output node N10 to which the first capacitor 22 and the first output sub- And an eleventh node N11 to which the subdiode 34 is connected.

The inrush current path portion 60 may be composed of a diode and the anode terminal of the inrush current path portion 60 is connected to the anode terminal of the first output side diode 24 and the inrush current path portion 60 May be connected to the cathode terminal of the second output-side diode 34. The cathode terminal of the second output-

The voltage across the first and second capacitors 22 and 32 becomes 0 V when the power supply apparatus 1000 is initially driven. Therefore, the first and second capacitors 22 and 32 instantaneously operate as a short circuit.

A large charge current can flow through the first capacitor 22 and the second capacitor 32, which act like an instantaneous short circuit when the initial input power Vi is applied to the power supply 1000. [ In particular, when the voltage of the input power source Vi is the maximum and the phase is 90 degrees, the inrush current may have the maximum value.

The inrush current can flow through the first capacitor 22 to the second capacitor 32 via the inrush current path portion 60 having a relatively small impedance rather than the inductor 40 have. The first and second capacitors 22 and 32 are charged by the inrush current and the terminal voltages of the first and second capacitors 22 and 32 are raised to charge the first and second capacitors 22 and 32 The inrush current, which is the current, falls to a steady state.

For example, when the input power source is an AC power source having a peak value of 460 V, the effective value of the AC power passing through the rectifying unit 10 may be about 650 V, and in a steady state, the first and second output units 21 and 31 In the case of outputting a voltage of 400V, the anode terminal of the inrush current path portion 60 takes 250V and the cathode terminal takes 400V. That is, since a reverse voltage is applied to the diode of the inrush current path unit 60, the diode of the inrush current path unit 60 can operate in the open state.

Referring to FIG. 3B, the inrush current path portion 60 may include an inrush current control diode 61 and an inrush current control resistor 62.

The inrush current control diode 61 and the inrush current control resistor 62 may be connected in series with each other.

The anode terminal of the inrush current control diode 61 may be connected to the tenth node N10 and the cathode terminal of the inrush current control diode 61 may be connected to one terminal of the inrush current control resistor 62. [

The other terminal of the inrush current control resistor 62 may be connected on the eleventh node N11.

An inrush current generated in the initial operation of the power supply apparatus 1000 may flow through the first capacitor 22, the inrush current path unit 60, and the second capacitor 32.

The rush current control resistor 62 on the rush current path portion 60 can limit the magnitude of the rush current.

The first and second capacitors 22 and 32 can stabilize the current supplied to the first and second resistors 23 and 33 and the first and second output diodes 24 and 34 A reverse current can be prevented from flowing through the rectifying diode function.

The first and second switching elements Qs and Qm control the current supplied from the inductor 40 to the first and second output sections 21 and 31.

That is, the first and second switching devices Qs and Qm repeatedly turn on or off by the pulse width modulation signal PWM to thereby output the first and second output portions 21 and 31 Can be controlled.

Although the first and second switching elements Qs and Qm are shown as power MOSFETs for convenience, the present invention is not limited thereto. Therefore, the first and second switching elements Qs and Qm can be turned on and off according to the power capacity.

The power supply apparatus 1000 receives an input voltage. The first output unit 21 can generate a first output voltage according to the operation of the first switching device Qs. And the second output unit 31 can generate a second output voltage according to the operation of the second switching device Qm.

In other words, the first amplification unit 20 and the second amplification unit 30 can amplify the input voltage from the input power supply unit 11 by n times.

Unlike the Buck converter whose output voltage is lower than the input voltage, the power supply 1000 according to the embodiment may have an output voltage greater than the input voltage. Thus, n may have a real value greater than one. And can have a voltage transfer ratio as shown in Equation (1).

는 입력 전압을 의미하고

는 증폭부(50)의 출력 전압을 의미한다. In Equation (1)

Means the input voltage

Means an output voltage of the amplifying unit 50.

와 듀티비

의 관계는

에 반비례한다. Voltage transfer ratio

And duty ratio

The relationship

.

는 듀티비

가 0일 때 최소인 1이되며, 듀티비

가 1일 때 최대인 무한대의 값이 된다. Voltage transfer ratio

The duty ratio

1 ", and the duty ratio

Is a maximum value of infinity when it is 1.

를 0에서 1까지 변경시켜 증폭부(50)의 출력 전압을 제어할 수 있다.Duty ratio

The output voltage of the amplifier 50 can be controlled.

The first amplification unit 20 may output a first output voltage corresponding to n1 times the input voltage to the first output unit 21. The second amplifying unit 30 may output a second output voltage corresponding to n2 times the input voltage to the second output unit 31.

The amplification ratio of the first amplifying part 20 can be controlled according to the switching frequency of the first switching device Qs and the amplification ratio of the second amplifying part 20 can be controlled by the operation of the second switching device Qm . ≪ / RTI >

The amplification ratio of the amplification unit 50 and the amplification ratio of the first and second amplification units 20 and 30 constituting the amplification unit 50 satisfy the relationship shown in Equation (2).

That is, the amplifier 50 can amplify the input voltage n times. The amplification voltage is equal to the sum of the input voltage amplified n1 times by the first amplifier 20 and the input voltage amplified n2 times by the second amplifier 30.

N1 and n2 may have the same value or may have different values.

If n1 and n2 have the same value, the degree of amplification of the input voltage in each of the first and second amplifying units 20 and 30 is the same. Therefore, the same output voltage can be obtained from the first and second output sections 21 and 31.

When n1 and n2 are different from each other, the degree of amplification of the input voltage in the first and second amplifying units 20 and 30 is different. Therefore, output voltages different from each other can be obtained from the first and second output sections 21 and 31. [

Hereinafter, an operation method of the power supply apparatus 1000 according to the first embodiment of the present invention will be described with reference to FIGS. However, for convenience of explanation, it is assumed that each device is close to an ideal characteristic.

 And may have four operation modes depending on the operation mode of the first and second switching elements Qs and Qm.

The output voltages of the first and second output sections 21 and 31 can be controlled by turning on and off the first and second switching elements Qs and Qm.

4 is a diagram illustrating an operation method when the first and second switching elements Qs and Qm of the power supply apparatus 1000 according to the first embodiment of the present invention are turned on.

Referring to FIG. 4, in the first operation mode, the first and second switching elements Qs and Qm are simultaneously turned on. In this case, the voltage applied to the first and second switching elements Qs and Qm may be 0V. The current flowing in the first and second switching elements Qs and Qm may be a current flowing in the inductor 40. [

The currents flowing through the first and second output side diodes 24 and 34 become 0A. A divided voltage of the input voltage is applied to the first and second output diodes 24 and 34, respectively.

The rectified input voltage is applied to the inductor 40 and the current flowing in the inductor 40 increases.

5 is a diagram illustrating an operation method when the first and second switching elements Qs and Qm of the power supply apparatus 1000 according to the first embodiment of the present invention are turned off.

Referring to FIG. 5, in the second operation mode, the first and second switching elements Qs and Qm are simultaneously turned off. In this case, the first and second switching devices Qs and Qm are divided into the input voltages. The current flowing through the first and second switching elements Qs and Qm is 0 A.

Since the first and second output diodes 24 and 34 are turned on, the voltage applied to the first and second output diodes 24 and 34 becomes 0V. The current flowing in the first and second output diodes 24 and 34 becomes a current flowing in the inductor 40.

The voltage applied to the inductor 40 becomes a voltage obtained by subtracting the voltage of the first output unit 21 and the voltage of the second output unit 31 from the input voltage, so that a negative voltage is applied. Therefore, the current flowing in the inductor 40 is reduced.

Hereinafter, a case where the first and second operation modes alternate will be described.

The current flowing in the inductor 40 increases in the first operation mode. At this time, when the power supply apparatus 1000 enters the second operation mode, the voltage across the inductor 40 is increased to maintain the current flowing through the inductor 40. Then, a current flows on the first and second output portions 21 and 31. When the current in the inductor 40 is gradually reduced, the first and second switching elements Qs and Qm are turned on when the mode is switched to the first operation mode, so that the current flowing in the inductor 40 increases.

When the first and second operation modes are repeated, that is, the on / off states of the first and second switching elements Qs and Qm are turned on and off as the first and second switching elements are simultaneously turned on and off as described above, Off ratio is determined by sensing the output voltage of the first and second output units 21 and 31. [ Therefore, constant first and second output voltages can be obtained. Also, the input voltage is amplified, and the amplified voltage can be equally divided in voltage to the first and second output portions 21 and 31.

The equation relating to the voltage transfer ratio at which the input voltage is transmitted to the first and second output sections 21 and 31 satisfies the following equation (3).

At this time, the voltages of the first and second output sections 21 and 31 can be adjusted by changing the duty ratio D within the range from 0 to 1. [

As described above, according to the power supply apparatus 1000 of the present invention, the amplified voltage is amplified and distributed to the first and second output units 21 and 31 and applied. Thus, the voltage stress of the circuit element is reduced. Therefore, an FET device as well as an IGBT can be used as a switching device.

That is, restrictions on selection of parts to be applied to the present invention are alleviated, thereby enhancing the design possibility so as to avoid the size and cost increase of various devices.

Not only the effect of lowering the voltage stress of the various devices but also the power can be transmitted to the circuit side having different functions for each output part by dividing the output part into two parts. Thus, the power supply apparatus 1000 according to the embodiment of the present invention has an advantage that it can provide a plurality of power supply sources using one power supply source, thereby reducing the size of the entire circuit and reducing the cost thereof .

According to the above description, the first and second switching elements Qs and Qm are simultaneously turned on and turned off simultaneously, but the present invention is not limited thereto.

Depending on the product in which the power supply apparatus 1000 is used, two output units having different voltages may be required. Therefore, in this case, the first and second switching elements Qs and Qm can be driven individually. That is, the PWM signals applied to the first and second switching devices Qs and Qm may be individually supplied to individually control the first and second switching devices Qs and Qm. Thus, voltages different from each other can be output to the first and second output units 21 and 31.

6 is a diagram illustrating an operation method when the first switching device Qs of the power supply apparatus 1000 according to the first embodiment of the present invention is turned off and the second switching device Qm is turned on to be.

Referring to FIG. 6, the first switching device Qs may be turned off by the third operation mode, and the second switching device Qm may be turned on at the same time.

When the first switching device Qs is turned off and the second switching device Qm is turned on, the voltage applied to the first switching device Qs becomes 0 V and the current flowing in the inductor 40 Current. The input voltage is amplified in the second switching device Qm, and the current is 0A. Also, the difference voltage between the input voltage and the voltage applied to the second switching device Qm is applied to the inductor 40, and the difference voltage becomes a negative voltage, so that the current flowing in the inductor 40 decreases.

7 is a diagram illustrating an operation method when the first switching device Qs of the power supply apparatus 1000 according to the first embodiment of the present invention is turned on and the second switching device Qm is turned off to be.

Referring to FIG. 7, the first switching device Qs may be turned on by the fourth operation mode, and the second switching device Qm may be turned off at the same time.

When the first switching device Qs is turned on and the second switching device Qm is turned off, the input voltage is amplified in the first switching device Qs, and the current is 0A. The voltage across the second switching device Qm becomes 0 V, and the current flowing through the second switching device Qm becomes the current flowing through the inductor 40. Further, the difference voltage between the input voltage and the voltage applied to the first switching element Qs is applied to the inductor 40, and the difference voltage becomes negative voltage, so that the current flowing in the inductor 40 decreases.

The amplification degree of the voltage applied to the first and second output sections 21 and 31 can be adjusted according to the duty ratio even in the third and fourth operation modes.

In summary, the power supply apparatus 1000 according to the first embodiment of the present invention can operate in various ways according to the combination of the first to fourth operation mode schemes. For example, when the first and second operation mode schemes are set to the main operation mode schemes, the voltage stress of the semiconductor device can be reduced by distributing the amplified voltage to the first and second output portions 21 and 31, 1 and the second output units 21 and 31 may be used for one application or for different purposes. When the voltages output to the first and second output units 21 and 31 are intermittently different from each other, the duty ratios of the PWM signals applied to the first and second switching devices Qs and Qm are set to be different from each other The purpose can be accomplished by doing otherwise. When the first and second operation mode schemes are used in the main operation mode scheme, amplification voltages having the same value will be applied to the first and second output sections 21 and 31, respectively. However, amplification voltages having the same magnitude may not be maintained in the first and second output portions 21 and 31 due to non-ideal characteristics of the circuit elements or external factors. In this case, amplification voltages having the same magnitude can be maintained in the first and second output sections 21 and 31 while adding the third and fourth operation mode schemes.

Hereinafter, a power supply apparatus 3000 according to a second embodiment of the present invention will be described.

According to the power supply apparatus 1000 of the first embodiment described above, the input voltage is divided and provided to the two output sections, and the input voltages can be evenly distributed through the first to fourth operation modes to be applied to the two output sections .

Alternatively, the amplified input voltages may be distributed to the two output units differently from each other. In addition, the amplified input voltage is uniformly distributed to the two output units for a predetermined time, and the amplified input voltages are distributed to the two output units at different values for a predetermined time.

In the second embodiment, a description will be given of a power supply apparatus 1000 that equally distributes an input voltage to the output stages of two stages, and corrects a voltage imbalance at the output stages of the two stages.

When the power supply apparatus 1000 described in the first embodiment operates alternately in the first and second operation modes, the amount of current flowing in the load side of the first and second output sections 21 and 31 can be different. In this case, the energy to be charged to the capacitors of the current-carrying output portion may be relatively small compared with the energy to be charged to the capacitors of the other output portion. Thus, the output voltage of the output section including the capacitor charged with relatively little energy can be lowered. In this case, the equal distribution of the input voltage will not occur and the balanced output will not appear. And a relatively high voltage is applied to one of the semiconductor elements, so that the voltage stress of the semiconductor element in the circuit in which a high voltage is applied can be increased.

According to the second embodiment of the present invention, if the currents flowing through the first and second output units 21 and 31 are different from each other and the output voltage becomes unbalanced, it can be corrected.

Hereinafter, an operation method of the power supply apparatus 3000 according to the second embodiment of the present invention will be described with reference to the drawings.

FIG. 8 shows a power supply device according to a second embodiment of the present invention, and FIG. 9 is a circuit diagram showing a detailed configuration of the control unit of FIG.

Referring to FIGS. 8 and 9, the power supply apparatus 1000 may include a power supply unit 1000 and a control unit 2000.

2 to 7, and the controller 2000 generates a control signal for turning on and off the switching elements Qs and Qm of the power supply apparatus 1000 do.

8 and 9, a power supply apparatus 3000 according to a second embodiment of the present invention includes a voltage controller 100, a power factor correction circuit 200, a triangle wave generator circuit 400, a first comparator 310, A second comparator 320, a first fine displacement controller 610, and a second fine displacement controller 620. And may additionally include first through third adders 510, 520, and 530.

The first adder 510 may be connected between the input terminal of the voltage controller 100 and the first and second output output terminals of the controller 2000, The power factor correction circuit 200 may be connected between the first reference voltage terminal and the output terminal of the first adder 510 and the input terminal of the power factor correction circuit 200, An output terminal, a terminal to which the sensed input voltage is applied, a terminal to which the sensed output current is applied, and an input terminal of the second and third adders 520 and 530. The second adder 520 may be connected between an output terminal of the first fine displacement controller 610 and an input terminal of the first comparator 310 and the third adder 530 may be connected to the second fine displacement controller 610. [ And the first micro displacement controller 610 may be connected between the output terminal of the first comparator 620 and the input terminal of the second comparator 320. The first micro displacement controller 610 may include a terminal to which the second output voltage is applied, And the second fine displacement controller 610 may be connected between the terminal to which the first output voltage is applied and the terminal to which the third reference voltage is applied to output the signal to the third adder 530 have. The first comparator 310 may be connected between the output signal terminal of the triangle wave generating circuit 400 and the output terminal of the second adder 520 and the control terminal of the first switching device Qs, The comparator 320 may be connected between the output signal terminal of the triangular wave generating circuit 400 and the output signal terminal of the third adder 530 and the control terminal of the second switching device Qm.

Hereinafter, an operation method of the power supply apparatus 3000 according to the second embodiment of the present invention will be described. In this case, for example, a case where the peak value of the input AC voltage is 400 V, and the peak value of the input AC voltage is amplified twice and output by 400 V at the first and second output units 21 and 31, respectively. The presented numerical values are for convenience of description of the invention, but are not limited thereto.

The voltage controller 100 receives the sum signal of the output voltages of the first and second output units 21 and 31 and compares the sum signal with the first reference voltage Vref1.

That is, the voltage controller 100 amplifies the difference between the first reference voltage Vref1 applied to the non-inverting terminal and the output voltage of the first and second output sections 21 and 31 applied to the inverting terminal, And an operational amplifier for outputting one control signal.

The first reference voltage Vref1 may be 800V, which is obtained by doubling the peak value 400V of the input AC voltage. The first reference voltage Vref1 is compared with the sum signal of the output voltages of the first and second output sections 21 and 31 and the first control signal obtained by amplifying the difference is output to the power factor improving circuit 200 have.

Meanwhile, the output voltages of the first and second output units 21 and 31 may be summed by the first adder 510.

The power factor correction circuit 200 receives the first control signal output from the voltage controller 100 and the sensed input voltage Vi and the sensed output current to output the second control signal.

That is, the power factor correction circuit 200 amplifies the difference between the sensed input voltage signal applied to the non-inverting terminal and the sensing current signal applied to the inverting terminal, and outputs the amplified difference as a second control signal Lt; / RTI >

The sensed output current may be defined as the current flowing through the inductor 40. Alternatively, the sensed output current may be an average current flowing in the inductor 40, and may be a current flowing in the first switching device Qs or the second switching device Qm.

The first fine displacement controller 610 compares the output voltage of the first output section 21 with the second reference voltage Vref2 to output a first fine displacement signal and the second fine displacement controller 620 outputs the first fine displacement signal The second fine displacement signal can be outputted by comparing the output voltage of the output unit 31 with the third reference voltage Vref2.

Meanwhile, the first fine displacement controller 610 receives the output of the second output unit with the non-inverting terminal, applies the second reference voltage Vref2 to the inverting terminal, amplifies the difference, and outputs the first fine displacement signal And an operational amplifier. The second fine displacement controller 620 receives the output of the first output unit with the non-inverting terminal, applies the third reference voltage Vref2 to the inverting terminal, amplifies the difference, and outputs the second fine displacement signal And an operational amplifier.

The second and third reference voltages Vref2 and Vref3 may have the same value.

On the other hand, the second and third reference voltages Vref2 and Vref3 are generated when the input voltage is amplified and the amplified voltage is uniformly applied to the first and second output portions 21 and 31, 21, and 31, and the 400V voltage may be used as the second and third reference voltages Vref2 and Vref3.

The second control signal output from the power factor correction circuit 200 and the first fine displacement signal may be converted to a first comparison signal which is a sum signal by the second adder 520 and supplied to the first comparator 310 The second control signal output from the power factor correction circuit 200 and the second fine displacement signal are converted into a second comparison signal by the third adder 530 and supplied to the second comparator 320 .

The first and second comparators 310 and 320 are circuits for comparing an analog signal with a reference signal and outputting the analog signal as a binary signal, and are used in a process of converting an analog signal to a digital signal. The first and second comparators 310 and 320 have substantially the same characteristics as a general operational amplifier having a high gain.

The first comparator 310 compares the triangle wave signal output from the triangle wave generating circuit 400 with the first comparison signal and supplies a first PWM signal to the first switching device Qs to output the first switching device Qs, And the second comparator 320 compares the triangular wave signal output from the triangular wave generating circuit 400 with the second comparison signal to control the second PWM signal to the second switching device Qm And turn on / off of the second switching device Qm.

Specifically, a first fine displacement signal and a second control signal are applied to a non-inverting terminal of the operational amplifier of the first comparator 310, a triangular wave signal is applied to an inverting terminal, and the two signals are compared to output a first PWM signal A second fine displacement signal and a second control signal are applied to the non-inverting terminal of the operational amplifier of the second comparator 320 and the triangular wave signal is applied to the inverting terminal to compare the two signals, Can be output.

The first and second PWM signals are signals for controlling the on / off times of the first and second switching elements. That is, within the range of 1% to 100% of the duty ratio of the first and second PWM signals.

On the other hand, the triangular wave generated in the triangular wave generating circuit 400 may be set to a proper period and magnitude to adjust the duty ratio of the pulse width modulation according to the second control signal and the first and second micro displacement signals.

The first to eighth impedances Z1 to Z8 included in the voltage controller 100, the power factor correction circuit 200, the first fine displacement controller 610, and the second fine displacement controller 620 shown in FIG. A resistive element and a capacitive element. In particular, the first, third, fifth and seventh impedances Z1, Z3, Z5 and Z7 can be resistances, and particularly the second, fourth, sixth and eighth impedances Z2, Z4, Z6 and Z8 ) May comprise a resistor as a negative feedback of the operational amplifier and a capacitor connected in series with the resistor.

Referring to FIGS. 4 to 7, an operation method for balancing the output when the output is unbalanced will be described.

For example, the case where the amplifying unit 50 amplifies the input voltage from the input power supply unit 11 by n (n is a positive real number) will be described.

The first amplifying unit 20 included in the amplifying unit 50 outputs a first output voltage corresponding to n1 (n1 is a positive real number) of the input voltage, and the second amplifying unit 30 And outputs a second output voltage corresponding to n2 (n2 is a positive real number) of the input voltage.

At this time, when the output voltage of the second output unit 31 included in the second amplifying unit 30 decreases and a value of n1 is greater than n2, that is, n1> n2, the first output unit By setting the turn-on time of the first switching device Qs to be later than the turn-off time of the second switching device Qm by increasing the on time of the first switching device Qs of the first switching device Qs, The output voltages of the two output units 21 and 31 can be adjusted to be balanced.

That is, as shown in FIGS. 4 and 5, when the power supply apparatus 1000 alternates between the first and second operation modes, the output voltage of the second output section 31 decreases due to the non-ideal characteristics of the internal elements of the circuit and external factors The output voltage of the first and second output units 21 and 31 can be adjusted through a method of temporarily switching to a third operation mode as shown in FIG.

Hereinafter, the operation of the control unit will be described when the output voltages of the first and second output units 21 and 31 are uneven.

For example, when the output voltage of the second output section 31 decreases, the voltage applied to the inverting terminal of the first micro displacement control section 610 decreases. Accordingly, the voltage of the first fine displacement signal which is the output voltage of the first fine displacement control unit 610 can be increased (high signal) and output. When the output voltage of the second output unit 31 decreases, the output voltage of the first output unit 21 increases and the voltage applied to the inverted terminal of the second micro displacement control unit 620 increases. Therefore, the second fine displacement signal, which is the output voltage of the second fine displacement control unit 620, can increase (low signal).

The first fine displacement signal with increased voltage and the second fine displacement signal with decreased voltage are respectively converted into first and second comparison signals which are the sum of the first fine displacement signal and the second control signal, 310, and 320, respectively.

The first and second comparators 310 and 320, receiving the first and second comparison signals, compare the applied first and second comparison signals with the triangular wave signal to generate a PWM output signal having a changed pulse width, can do.

The duty ratio of the first PWM output signal can be increased by increasing the magnitude of the signal applied to the inverting terminal of the first comparator 310 by the first fine displacement signal which is a high signal, The magnitude of the signal applied to the inverting terminal of the second comparator 320 may be reduced by the displacement signal and accordingly the duty ratio of the second PWM output signal may be reduced.

The turn-on time of the first switching device Qs becomes longer and the turn-on time of the second switching device Qm becomes shorter due to the first PWM output signal having the increased duty ratio. That is, the turn-on points of the first and second switching elements Qs and Qm are the same while the turn-off points of the first and second switching elements Qs and Qm are the same, Respectively.

Meanwhile, when the first and second comparison signals are applied to the inverting terminal by reversing the signals applied to the first and second comparators 310 and 320 and the triangular wave signal becomes the non-inverting terminal, The first comparator 310 generates a first PWM output signal whose duty ratio is decreased while the second comparator 320 generates a second PWM output signal whose duty ratio is increased while the first comparator 310 and the second comparator 320 perform the opposite operation .

When the bandwidths of the voltage controller 100, the power factor correction circuit 200 and the first and second micro displacement controllers 610 and 620 are selected, the bandwidth of the power factor improving circuit 200 is the largest, It is desirable to increase the bandwidth of the signal transmission path.

The controller 2000 of the power supply apparatus 1000 according to the second embodiment of the present invention has been described as a digital controller. Alternatively, the controller 2000 may be implemented using an analog PFC IC (Power Factor Controller Integrated Circuit).

10 is a diagram showing an analog control unit 2000 of the power supply apparatus 3000 according to the second embodiment of the present invention.

10, the controller 2000 of the power supply 3000 according to the second embodiment of the present invention includes first and second PFC ICs 1100 and 1200, first and second adders 1300 and 1400, . ≪ / RTI >

The first and second PFC ICs 1100 and 1200 receive the sensed AC input voltage, the sensed current, and the triangular wave, receive feedback signals from the first and second adders 1300 and 1400, respectively, It is possible to output first and second PWM signals for controlling the second switching elements Qs and Qm, respectively.

The first adder 1300 may add the output voltage of the second output unit 31 and the input voltages of the first and second output units 21 and 31 to the first PFC IC 1100. The second adder 1400 may add the output voltage of the first output unit 21 and the input voltages of the first and second output units 21 and 31 to the second PFC IC 1200 .

The first and second dual feedback units 1500 and 1600 may be implemented by using a 431 series element capable of feeding back the output voltage instead of the first and second adders 1300 and 1400 .

11 is a circuit diagram of the first and second dual feedback units.

A detailed circuit configuration of the first and second dual feedback units 1500, 1600 will be described with reference to FIG.

Since the circuit structure of any one of the first and second dual feedback units 1500 and 1600 having the output voltage feedback structure may be the same as the other, the first dual feedback unit 1500 will be mainly described.

The first dual feedback unit 1500 may include first through fourth resistors R1 through R4, a capacitor C, and a Zener diode ZD.

The first resistor R1 is connected between the eighth node N8 and a terminal to which an output voltage of the first and second output sections 21 and 31 is applied.

The second resistor R2 is connected between the eighth node N8 and the terminal to which the output voltage of the second output unit 31 is applied.

A third resistor R3 and a capacitor C connected in series to each other are connected between the eighth node N8 and the ninth node N9.

The Zener diode ZD is connected between the eighth node N8, the ninth node N9, and the ground. The feedback output to the first PFC IC 1100 is applied on the ninth node N9.

The magnitude of the first resistor R1 may be weighted by selecting the magnitude of the resistance smaller than the magnitude of the resistance of the second resistor R2.

12 and 13 show circuits for simulating the power supply device 3000 according to the second embodiment of the present invention.

The operation method and effect of the power supply apparatus 2000 according to the second embodiment of the present invention will be described with reference to FIG. 14, which shows the simulation results of the power supply apparatus 3000 of FIGS. 12 and 13.

Referring to FIG. 14, when the current flowing through the first output unit 21 increases at the time T1 and the currents flowing through the first and second output units 21 and 31 become unbalanced, It can be seen that the voltage V02 increases and the voltage V01 of the first output section 21 decreases. In this case, the first fine displacement signal, which is a high signal from the first fine displacement control unit 610, is output, and accordingly, the magnitude of the signal applied to the inverting terminal of the first comparator 310 becomes large, The duty ratio can be increased and the magnitude of the signal applied to the inverting terminal of the second comparator 320 is reduced by the second fine displacement signal which is the low signal from the second fine displacement control unit 620, It can be confirmed that the output voltages V01 and V02 of the first and second output units 21 and 31 become equal to each other after the time point T2 as the duty ratio of the output signal decreases.

In contrast, when the current flowing through the second output unit 31 increases at time T3 and the currents flowing through the first and second output units 21 and 31 become unbalanced, the voltage V01 of the first output unit 21 becomes And the voltage V02 of the second output section 31 decreases. In this case, the first fine displacement signal, which is a low signal from the first fine displacement control unit 610, is output, and accordingly, the magnitude of the signal applied to the inverting terminal of the first comparator 310 becomes small, The duty ratio of the second fine displacement control unit 620 can be reduced and the magnitude of the signal applied to the inverting terminal of the second comparator 320 is increased by the second fine displacement signal which is a high signal from the second fine displacement control unit 620, The output voltages V01 and V02 of the first and second output units 21 and 31 become equal to each other after the time T4 as the duty ratio of the second PWM output signal increases.

As described above, in the power supply apparatus 1000 according to the present invention, when the output voltages of the first and second output sections 21 and 31 become uneven, the first and second micro displacement sections 610 and 620 and the first and second The duty ratio of the first and second PWM signals is adjusted according to the operation of the comparators 310 and 320 so that the output voltages of the first and second output units 21 and 31 are controlled evenly.

While the present invention has been particularly shown and described with reference to exemplary embodiments thereof, it is clearly understood that the same is by way of illustration and example only and is not to be taken by way of limitation, It will be understood by those skilled in the art that various changes in form and details may be made therein without departing from the spirit and scope of the invention. Therefore, the technical scope of the present invention should not be limited to the contents described in the detailed description of the specification, but should be defined by the claims.

1. Conventional power supply
2. Rectifier
3. Inductor
4. Switching element
5. Output
10. Rectifier
11. Input power section
20. The first amplifying unit
21. First output section
22. A capacitor
23. The first resistor
24. The first output sub-
30. The second amplifying unit
31. Second output section
32. Second capacitor
33. Second resistance
34. Second output section diode
40. Inductor
50. Amplification unit
60. Inrush current path portion
61. Inrush current control diode
62. Inrush current control resistor
100. Voltage control section
200. Power factor improvement society
310. A first comparator
320. Second comparator
400. Triangular wave generator
510. The first adder
520. Second adder
530. The third adder
610. First fine displacement controller
620. Second fine displacement controller
1000. Power supply unit, power supply unit
1100. First PFC IC
1200. Second PFC IC
1300. First adder
1400. Second adder
1500. The first dual feedback section
1600. The second dual feedback section
2000. Control section
3000. Power supply.

Claims (16)

A rectifying section for rectifying the AC voltage to a first voltage, an amplifying section for receiving the first voltage from the rectifying section to step up, dividing the stepped up voltage and outputting it as a second voltage and a third voltage, And an inrush current path portion providing a path of current. The method according to claim 1,
The amplifying unit
A first amplifying unit receiving the first voltage and outputting the amplified second voltage,
A second amplifier for receiving and amplifying the first voltage to output the third voltage,
And an inrush current path part connected between the first and second amplifying parts and an inductor. 3. The method of claim 2,
Wherein the first amplifying part includes the first switching element and the first output part connected between the first and second nodes,
And the second amplifying part includes the second switching element and the second output part connected between the third and fourth nodes. The method of claim 3,
Wherein the first output comprises a first diode and a first capacitor-resistor portion,
And the second output portion includes a second diode and a second capacitor-resistor portion. 6. The method of claim 5,
The capacitors and resistors included in the first and second capacitor-resistor portions are connected in parallel with each other,
The first diode being connected between the second node and the fifth node,
The second diode being connected between the third node and the sixth node,
Wherein the first capacitor-resistor portion is connected between the first and fifth nodes,
The second capacitor-resistor portion being connected between the fourth and sixth nodes,
And the inductor is connected between the second and third nodes. 5. The method of claim 4,
Wherein the inrush current path unit comprises:
One end is connected to the first diode,
And the other end is connected to the second diode. 6. The method of claim 5,
And the inrush current path portion is a third diode. 8. The method of claim 7,
And the third diode is connected between the fifth and sixth nodes. 9. The method of claim 8,
The third diode
An anode terminal is connected to an anode terminal of the first diode,
And a cathode terminal is connected to the cathode terminal of the second diode. 6. The method of claim 5,
Wherein the inrush current path portion includes an inrush current control diode and an inrush current control resistor. 11. The method of claim 10,
The inrush current path portion is connected between the fifth and sixth nodes,
Wherein the inrush current control diode and the inrush current control resistor are connected in series with each other. The method according to claim 6,
During the initial operation of the power supply,
And an inrush current flows via the first capacitor, the inrush current preventing portion, and the second capacitor. The method according to claim 1,
And the second and third voltages are equal to each other. The method of claim 3,
Wherein the first and second switching elements are simultaneously turned on and turned off. The method of claim 3,
The first switching element is turned off at a first time point,
The second switching element is turned off at a second time point,
Wherein the first point of time arrives after the second point of time if the first voltage has a value greater than the second voltage. 16. The method of claim 15,
Wherein the first and second switching elements are simultaneously turned on.

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