KR20080063265A

KR20080063265A - Cancellation of anti-resonance in resonators

Info

Publication number: KR20080063265A
Application number: KR1020087003017A
Authority: KR
Inventors: 용 핑 수; 루이 유
Original assignee: 내셔날유니버서티오브싱가폴
Priority date: 2008-02-04
Filing date: 2005-07-20
Publication date: 2008-07-03

Abstract

The present invention is directed to removing network 112 to reduce and / or eliminate the anti-resonance effect of resonator 110, which may be due to, for example, electrostatic capacitance 210, inherent to the resonator. It relates to a resonator 110, such as an electromechanical resonator that can be connected with. Elimination of the anti-resonant effect from the resonator response causes the resonant effect of the resonator 110 to become a dominant effect, for example in a band pass sigma-delta modulator 526 that can be utilized in the digital RF receiver 800. As such, the resonator 110 can be utilized as a band pass filter with a relatively high Q.

Description

CANCELLATION OF ANTI-RESONANCE IN RESONATORS

FIELD OF THE INVENTION The present invention relates to digital communications, and more particularly, to the reduction and / or elimination of anti-resonance in resonators that can be utilized in sigma-deltasigma-delta modulators, but the scope of the invention Is not limited to this. According to one or more specific embodiments, the invention disclosed herein may relate to a delta modulator, but the scope of the invention is not limited thereto.

Communication systems have widely used surface acoustic wave (SAW) resonators because of their higher quality (Q) factor, which is generally difficult to achieve with active filters. With the recent development of micro-mechanical resonators, micromechanical resonators have replaced SAW resonators because such micromechanical resonators tend to be smaller in volume than SAW resonators. However, micromechanical resonators have often limited their resonant frequencies to the order of hundreds of megahertz (MHz). Advances in bulk acoustic wave (BAW) resonator technology have allowed these BAW resonators to utilize conventional CMOS technology, and furthermore, such BAW resonators generally have high resonant frequencies in the gigahertz (GHz) range, allowing for BAW resonators. Resonators are being utilized in cellular and wireless local area network (WLAN) applications. Such a resonator may exhibit both resonance and anti-resonance characteristics, where the resonance characteristics may provide a bandpass filter type function, and the anti-resonance characteristics provide a notch filter type function. can do.

In the following detailed description, numerous specific embodiments will be shown to provide a thorough understanding of the present invention. However, it will be understood by those skilled in the art that the present invention may be practiced without these specific embodiments. On the other hand, well-known methods, procedures, components and / or circuits are not described in detail.

In the following description and / or claims, the terms coupled and / or connected may be used with their derivatives. In certain embodiments, being connected may be used to indicate that two or more components are in direct physical and / or electrical contact with each other. Connecting may mean that two or more components are in direct physical and / or electrical contact. However, being connected may also mean that two or more components do not have direct contact with each other but may cooperate and / or interact with each other.

It will be appreciated that certain embodiments may be used for a variety of applications. Although the invention is not so limited, the circuitry disclosed herein may be used in many devices, such as transmitters and / or receivers in a radio system. Wireless systems intended to be included within the scope of the present invention include wireless personal area networks (WPAN), wireless local area networks (WLAN) devices, and / or wireless, such as networks in accordance with the WiMedia Alliance. Network interface devices and / or network interface cards (NICs), base stations, access points (APs), gateways, bridges, hubs, cellular radiotelephones Cellular radiotelephone communication systems, satellite communication systems, two-way radio communication systems, one-way pagers, two-way pagers, individuals Personal communication systems (PCS), personal computers (PCs), personal digital assistants (PDAs), And / or a wireless wide area network (WWAN) device, including the like, as an example only, but the scope of the present invention is not limited thereto.

Types of wireless communication systems intended to be included within the scope of the present invention include, but are not limited to, Wireless Local Area Networks (WLANs), Wireless Wide Area Networks (WWANs), Code Division Multiple Access, CDMA) cellular radiotelephony system, Global System for Mobile Communications (GSM) cellular radiotelephone system, North American Digital Cellular (NADC) cellular radiotelephone system, time division multiple access TDMA system, Extended-TDMA (E-TDMA) cellular radiotelephone system, Wideband CDMA (WCDMA), CDMA-2000, Universal Mobile Telecommunications System (UMTS), and / or And third generation systems such as, but not limited to.

The invention is specifically pointed out and specifically claimed in the ending section of this specification. However, the configuration and / or method of operation together with the objects, features and / or advantages thereof may be best understood with reference to the following detailed description of the invention in conjunction with the accompanying drawings.

1 is a circuit diagram of a resonator and cancellation network operable to implement band pass filter type functionality, in accordance with one or more embodiments.

2 is an equivalent circuit diagram for a resonator and cancellation network, in accordance with one or more embodiments.

3 is a response diagram of a resonator showing resonance and anti resonance, in accordance with one or more embodiments.

4 is a response diagram of a resonator and a removal circuit showing at least partially elimination of anti-resonance in accordance with one or more embodiments.

FIG. 5 is a block of an intermediate-frequency (IF) digitization receiver, including a narrowband band pass sigma-delta modulator capable of utilizing resonators and cancellation networks in accordance with one or more embodiments. It is also.

6 is a block diagram of a second band pass sigma-delta modulator that may utilize resonators and cancellation networks in accordance with one or more embodiments.

7 is a circuit level structural diagram of a band pass sigma-delta modulator in accordance with one or more embodiments.

8 is a block diagram of an intermediate frequency (IF) digitizing receiver for intermediate frequency (IF) digitization, including a wideband band pass sigma-delta modulator that may utilize resonators and cancellation networks in accordance with one or more embodiments. .

9 is a block diagram of a radio frequency (RF) digitizing receiver including a radio-frequency (RF) wideband band pass sigma-delta modulator that may utilize resonators and cancellation networks in accordance with one or more embodiments. .

It is to be appreciated that the components shown in the figures are for simplicity and / or clarity of description and are not intended to be drawn to scale in nature. For example, some dimensions of a component may be exaggerated relative to other components for clarity. Moreover, if deemed appropriate, reference numerals are repeated among the figures to indicate corresponding similar elements.

Referring now to FIG. 1, a diagram of a resonator and cancellation network according to one or more embodiments will be described. As shown in FIG. 1, the circuit 100 may include a combination of a resonator 110 and a removal network 112. The resonant frequency function of the resonator 110 allows the circuit 100 to function as a band pass filter circuit with a relatively high Q factor. In general, resonator 110 exhibits two resonance modes: resonance in series mode and resonance in parallel mode. In series mode resonance, the impedance of the resonator 110 may be at the minimum value and / or the admiadmit may be at the maximum value, which may occur at a frequency referred to as the resonance frequency. Similarly, in parallel mode resonance, the impedance of resonator 110 may be at the maximum value and / or the admittance may be at the minimum value, which may occur at a frequency referred to as an anti-resonant frequency. An example of the response of the resonator 110 showing the resonance characteristics and the anti-resonance characteristics is shown in FIG. 3. For the operation of circuit 100 as a band pass filter, the resonant frequency characteristic can provide such functionality. However, in some applications, the anti-resonant frequency characteristic may be such that, for example, when the resonator 110 is utilized in a sigma-delta modulator such as the sigma-delta modulator 526 shown in FIG. 6. Can be harmful to the operation of Here, the circuit 100 may function as a band pass filter, but the scope of the present invention is not limited thereto.

According to one or more embodiments, the resonator 110 may be realized as an electromechanical resonator. For example, the resonator 110 may include a micro-electromechanical system (MEMS) type resonator, a crystal type resonator, a ceramic type resonator, a surface acoustic wave (SAW) type resonator, and a bulk acoustic wave (BAW) type resonator. And a film bulk acoustic resonator (FBAR) type resonator. Such electromechanical type resonators may generally provide higher Q factors, higher resonant frequency accuracy, and greater temperature stability. According to one or more embodiments, the resonator 110 may be realized on a silicon substrate, for example, through a micromachining process. According to one particular embodiment, the resonator 110 may be realized on an integrated complementary metal oxide semiconductor (CMOS) type circuit, and / or a bipolar CMOS (BiCMOS) type circuit, but the scope of the present invention. Is not limited thereto.

The cancellation network 112 may be utilized in the circuit 100 to eliminate anti-resonance of the resonator 110, for example to provide a more ideal band pass filter response. According to one or more embodiments, the amplifier 114 may receive an input 116 at a non-inverting input 118, and an inverting input 120 of the amplifier 114. ) May be grounded. The non-inverting output 122 of the amplifier 114 may be connected to the resonator 110, and the inverting output 124 of the amplifier 114 may be connected to the cancellation network 112. The output and rejection network 112 of the resonator 110 may be connected to the node 126, where the resonator 110 and the rejection network 112 may have the same load Z _L 128, and / or the same effective load ( effective load) and share a common output V ₀ across the load 128 at node 126. It should be noted that the various connections shown in FIG. 1 are only one configuration of the circuit 100 and other configurations of the connection may be utilized. For example, the resonator 110 may be connected to the inverting output 124, the removal network may be connected to the non-inverting output 122, the scope of the present invention is not limited thereto.

Referring now to FIG. 2, an equivalent circuit diagram of a resonator and cancellation network according to one or more embodiments will be described. FIG. 2 shows the circuit 100 of FIG. 2, where the resonator 110 may be represented by equivalent circuit elements. The series mode resonance characteristic can be represented by a series RLC circuit comprising a resistor R _m 212, a capacitor C _m 214, and an inductor L _m 216, which is ideal or somewhat ideal resonator 110. You can provide a transfer function for. The parallel mode resonance characteristic can be represented by electrostatic capacitances C _p 210 and C _m 214. The electrostatic capacitance 210 may be an intrinsic characteristic of the resonator 110, which is modeled as a capacitance connected in parallel to an RLC circuit including, for example, a resistor 212, a capacitor 214, and an inductor 216. Can be. The electrostatic capacitance 210 can change the ideal transfer function of the resonator 110 by, for example, introducing two transmission zeros into the transfer function of the resonator 110. Removing capacitor C _C (218) of removing the network 112, it may be utilized to reduce and / or eliminate the effect of the electrostatic capacitor 210 of resonator 210, for example where resonator 110 may also 5 and 6 may be utilized to provide a band pass filter function to a sigma-delta modulator, such as sigma-delta modulator 526, but the scope of the present invention is not so limited. For example, this configuration of the circuit 100 using the resonator 110 and the cancellation network 112 may enhance the resonance characteristics of the resonator 112 and reduce the anti-resonance characteristics of the resonator 112. Although utilized, the scope of the present invention is not limited thereto.

When the input signal 116 is applied to the amplifier 114, the current flowing through the electrostatic capacitance 210 can flow in one direction, and the current flowing through the removal capacitance is the non-inverting output 122 of the amplifier 114. And the reverse phase polarity of the inverting output 124 may flow through the elimination capacitor 218 in the opposite direction. This current is coupled at node 126 and removed at load 128. As a result, the anti-resonance characteristic provided by the electrostatic capacitance 210 may be reduced and / or eliminated, which may be the dominant characteristic of the RLC circuit as a response in the circuit 100, for example, as shown in FIG. This can result in a series resonance effect. The removal of this anti-resonance characteristic may occur, for example, where the value of the removal capacitor 218 matches or at least nearly matches the value of the electrostatic capacitance 210, but the scope of the present invention is not limited thereto. Do not. In such a configuration, the elimination capacitor 218 can provide negative capacitance with respect to the capacitance of the electrostatic capacitance 210, where the elimination capacitor 218 effectively reduces and reduces the response provided by the electrostatic capacitance 210. And / or can be removed. While the removal network 112 may be realized by the removal capacitor 218 in one embodiment, any device and / or circuit element that may exhibit negative capacitance with respect to the electrostatic capacitance 218 may be a removal network ( It should be noted that it can be used to realize 112). For example, the removal network 112 may be a diode having a capacitance matched or nearly matched to the electrostatic capacitance 210 to remove, or at least partially eliminate, the anti-resonance characteristic provided by the electrostatic capacitance 210. It may include, but the scope of the present invention is not limited thereto. Therefore, by matching the elimination capacitor 218 to the electrostatic capacitance 210, elimination of anti-resonance from the response of the resonator 110 can be achieved, but the scope of the present invention is not limited thereto.

In accordance with one or more embodiments, eliminating the anti-resonant response of the resonator 110 with the elimination network 112 is characterized by the elimination of the resonator 110 and the elimination network 112 connected to the node 126 connected to the resistor 128. As a result of the output may occur in the current domain of node 126. As a result, no load matching is necessary in the output circuit 100 because the elimination of anti-resonance can occur in a single resistor. The elimination of anti-resonance may be provided by matching or nearly matching the impedance of the elimination network with the impedance, which is an intrinsic component of the resonator 110, which causes the anti-resonant effect in the response of the resonator 110. As shown in FIG. 2, the removal network 112 may include a removal capacitor 218 having a value that matches or nearly matches the capacitance value of the electrostatic capacitance 210, wherein the removal capacitor 218 is provided. The current flowing through has the same magnitude or approximately the same magnitude as the current flowing through the electrostatic capacitance 210, but with the opposite polarity, so that both currents are removed or nearly eliminated when coupled at node 126. However, the scope of the present invention is not limited thereto.

Referring now to FIG. 3, a diagram of the resonator's response showing resonance and anti resonance in accordance with one or more embodiments will be described. As shown in FIG. 3, the transfer function 310 of the resonator 110 may be plotted as, for example, frequency f in hertz versus admittance Y in Siemens. The peak 312 of the admittance may appear at the resonance frequency f _r , which may correspond to the series resonance characteristic of the resonator 110. The minimum admittance 314 may appear at the anti resonance frequency f _a , which may correspond to the parallel resonance characteristics of the resonator 110, which may be referred to as anti resonance.

Referring now to FIG. 4, a diagram of the response of a resonator in accordance with one or more embodiments and a removal circuit showing at least partial cancellation of anti-resonance will be described. As shown in FIG. 4, the transfer function 410 of the combined resonator 112 and the cancellation network 112 is plotted as, for example, frequency f in hertz versus admittance Y in eg Siemens. Can be set. The peak 412 of the admittance may appear at the resonant frequency f _r , where the cancellation network 112 may at least partially reduce and / or eliminate the anti-resonant effect as shown in FIG. 4. Elimination of anti-resonance through the cancellation network 112 results in the circuit 100 having a more ideal band pass filter response with a relatively high Q factor and center frequency near the frequency f _r as shown in FIG. Can result in

Referring now to FIG. 5, a block diagram of an intermediate frequency (IF) digitizing receiver including a band pass sigma-delta modulator that can utilize resonators and cancellation networks in accordance with one or more embodiments will be described. Receiver 500 may be, for example, a radio frequency (RF) receiver utilized in a cellular telephone type device, a wireless local area network (WLAN) type device, and / or the like. The RF signal may be received via the antenna 510, filtered by the RF filter 512, and amplified by a low-noise amplifier (LNA) 514. The signal may then pass through an image-rejection (IR) filter (IR FILTER) 516, and the signal may be demodulated using a demodulator 518 and an oscillator (f _LO1 ) 520. The channel may be selected by passing the signal through a channel filter 522 and then amplified via a variable gain amplifier (VGA) 524. The signal may be digitized via a band pass sigma-delta modulator (BP SDM) 526, where the digitized form of the signal is a digital signal processor (DSP) 528 for band pass processing of the signal. Is provided. DSP 528 may control the gain of VGA 524 via control line 530 and may provide an output 532 in response to the received signal, for example, the received signal. The data may be included therein, but the scope of the present invention is not limited thereto. A band pass sigma-delta modulator 526 for digitization of an IF signal is realized using circuit 100, for example using an electromechanical resonator type device as resonator 110 to provide a band pass filter function. Wherein the anti-resonance characteristics of the resonator may be reduced and / or eliminated via the cancellation network 112. However, the scope of the present invention is not limited thereto.

According to one or more embodiments, the receiver 500 may be part of a transceiver of a wireless local area or personal area network (WLAN or WPAN) communication system. For example, the receiver 500 may be utilized in a portable or remote unit, such as a portable computer and / or information processing system, a desktop computer, and / or a cellular telephone, and the digital signal processor 528 may be a baseband and / Alternatively, a media access control (MAC) processing function may be provided. According to one embodiment, the DSP 528 may include a single processor that includes filtering, or alternatively may also include a baseband processor and / or an application processor, the scope of the present invention being limited thereto. no. DSP 528 may be coupled to volatile memory such as DRAM, non-volatile memory such as flash memory (not shown), and / or may alternatively include other storage types such as hard disk drives. It is possible, but the scope of the present invention is not limited thereto. Any part or all of the memory may be included in the same integrated circuit DSP 528, and / or alternatively any part and / or all of the memory may be an integrated circuit and / or a DSP, such as, for example, a hard disk drive. And other media external to the integrated circuit of 528, but the scope of the present invention is not limited thereto.

Receiver 500 may receive via antenna 510, for example, a signal received from a remote access point and / or a base station (not shown) via a wireless communication link. According to another embodiment, the receiver 500 comprises two or more antennas to provide a spatial division multiple access (SDMA) system and / or a multiple input multiple output (MIMO) system. 510 may be included, but the scope of the present invention is not limited thereto. The remote access point may be connected to the network by communicating over a wireless communication link such that a receiver may receive information from the network, including devices connected to the network. Such a network may include a public network, such as a telephone network and / or the Internet, or alternatively, the network may include a private network, such as an intranet, and / or a combination of public and / or private networks. The range of is not limited to this. The communication between the receiver 500 and the remote access point may be a wireless personal area network (WPAN), such as a network according to the WiMedia Alliance, for example IEEE 802.11a, IEEE 802.11b, IEEE 802.11n, IEEE 802.16, HiperLAN-II, It can be implemented via a wireless local area network (WLAN), such as a network according to the Institute of Electrical and Electronics Engineers (IEEE) standard, such as HiperMAN, Ultra-Wideband (UWB), but the scope of the present invention is not limited thereto. According to another embodiment, such communication may be implemented at least in part via a cellular communications network in accordance with a Third Generation Partnership Project (3GPP or 3G) standard, Wideband CDMA (WCDMA) standard, or the like, wherein the present invention The range of is not limited to this.

Referring now to FIG. 6, a block diagram of a second band pass sigma-delta modulator that may utilize resonators and cancellation networks in accordance with one or more embodiments will be described. The band pass sigma-delta modulator 526 as shown in FIG. 6 may be a secondary band pass sigma-delta modulator, for example, utilized as the band pass sigma-delta modulator 526 of the receiver 500 of FIG. 5. However, the scope of the present invention is not limited thereto. Although the band pass sigma-delta modulator 526 of FIG. 6 is shown as a secondary modulator, other orders, for example, primary, tertiary, and quaternary, may be included within the scope of the present invention. The range of is not limited to this. Continuous time signal such as IF signal of receiver 500

May be applied to adder 612, the output of which is applied to band pass filter 614, which may be provided by circuit 100 via resonator 110 in combination with cancellation network 112. Can be. The output of circuit 100 may be applied to quantizer 616 to provide a discrete time version y (n) of the continuous time signal at output 618. Output 618 may be fed back through delay 620 to provide a delayed output 622 to digital-to-analog converter (DAC) 624 and DAC 626. DAC 624 may provide a return-to-zero (RZ) signal and may provide a DAC 626 half-delayed return-to-zero (HRZ) signal. Delay for one sampling period may be provided by, for example, discrete time delay 620 to avoid metastability and provide sufficient time for quantizer 616 to stabilize. Although FIG. 6 only describes a secondary sigma-delta modulator with a single bit quantizer, higher order multi-bit sigma modulators can also be realized with similar configurations.

Referring now to FIG. 7, a circuit level schematic of a band pass sigma-delta modulator, in accordance with one or more embodiments, will be described. The band pass sigma-delta modulator 700 may be substantially similar to the band pass sigma-delta modulator 526 of FIGS. 5 and 6 with functional blocks implemented in circuit blocks and / or elements. At least some circuit elements of the band pass sigma-delta modulator 700 may be realized on a semiconductor chip 710 fabricated using, for example, a standard CMOS process. Input transconductor (G _m ) 712 is utilized to convert the input signal from voltage to current, for example, feedback received from DAC 730 and / or DAC 732 at nodes 734 and 736. Allow the signal to be added in the current domain. After addition, the current signal is converted back to a voltage by current voltage converter (I / V) 714, for example resonator 110 and / or cancellation network, which may be separate or on chip 710. 112 can be driven. The outputs of resonator 110 and rejection network 112 can be coupled at node 126 and applied to ground through resistor R _L 718 to provide an input signal to variable gain amplifier (VGA) 716. have. As an alternative, resistor R _L 718 and variable gain amplifier (VGA) 716 may be replaced with a transimpedance amplifier. VGA 716 may also be utilized, for example, to provide phase adjustment or compensation of the signal prior to quantization. Phase adjustment or compensation may also be realized by a separate phase adjuster after the variable gain amplifier (VGA) or transimpedance amplifier and before quantization. Since VGA 716 may exhibit a relatively high input impedance, resistor 718 may be an effective load seen at node 126, and may be similar to load 128 of FIG. 1, but the scope of the present invention. Is not limited thereto.

Quantization by the quantizer 616 and the delayer 620 of FIG. 6 includes a latch (LATCH 1) 720, a latch (LATCH 2) 722, a latch (LATCH 3) 724, and a latch (LATCH 4). Four series connected dynamic latches of 726 can be realized. Latch 720 may function as quantizer 616 to provide 1-bit quantization, for example. Latch 722 may function as delay 620 with latch 720 to provide one sampling period delay. In other configurations, latch 720 and latch 722 may be replaced with a comparator or one bit quantizer with one sampling period delay. Latch 724 and latch 726 may generate an RZ and control a signal for DAC 730, and latch 724 may generate an HRZ and control a signal for DAC 732. DAC 730 and / or DAC 732 may provide current additions at nodes 734 and 736 as current-switched digital-to-audio converters. According to one or more embodiments, the circuitry of latch 720 may be configured to reduce kickback noise. Band pass sigma-delta modulator 700 may provide a digital output via a latch (output latch) 728, which may be, for example, a D flip-flop, the scope of the invention being limited thereto. It is not.

Referring now to FIG. 8, a block diagram of an intermediate frequency (IF) digitizing receiver, including a wideband band pass sigma-delta modulator that may utilize resonators and cancellation networks, in accordance with one or more embodiments, will be described. Receiver 800 employs a band pass sigma-delta modulator 526 that utilizes resonator 110 and cancellation network 112 to remove anti-resonance from the response of resonator 110 in accordance with one or more embodiments. One possible embodiment of a system that can be utilized is shown. The receiver 800 of FIG. 8 includes the receiver of FIG. 5 except that it includes a wideband band pass sigma-delta modulator 526 to digitize a wider signal band than a single channel, e.g., the entire signal band. Substantially similar to 500). The block of FIG. 8, similar to the block of FIG. 5, may perform a similar function in some embodiments. Antenna 810 may receive an RF signal that may be filtered by RF filter 812 and then amplified by LNA 814. The amplified RF signal may then be filtered via IF filter 816 and demodulated using demodulator 818 and oscillator 820. The wideband demodulated output may be provided to a band pass sigma-delta modulator 526 for an analog to digital converter of the wideband signal. The digitized wideband signal may be provided to the DSP 822 for subsequent digital signal processing and output 824, such as filtering and band pass signal processing, although the scope of the present invention is not limited in this respect.

Referring now to FIG. 9, a block diagram of a radio frequency (RF) digitizing receiver including an RF wideband band pass sigma-delta modulator that may utilize resonators and cancellation networks, in accordance with one or more embodiments, will be described. Utilize band pass sigma-delta modulator 526 utilizing resonator 110 and cancellation network 112 to remove anti-resonance from the response of receiver 900, resonator 110 in accordance with one or more embodiments. One possible embodiment of the system is shown. The block of FIG. 9, which is similar to the block of FIG. 5, may perform a similar function in some embodiments. According to one or more embodiments, the receiver 900 of FIG. 9 may implement RF digitization of the received RF signal. The RF signal may be received via antenna 910, filtered through RF filter 912, and amplified via LNA 914. The amplified RF signal may be directly digitized via a band pass sigma-delta modulator 526 for analog-to-digital conversion of the RF signal. According to this embodiment, the resonator 110 may have a resonant frequency tuned to the RF signal, where the resonant frequency of the resonator 110 may correspond to the frequency or frequency band of the RF signal. The digitized RF signal may then be provided to the DSP 916 for subsequent digital signal processing and output 918, such as filtering and band pass signal processing, although the scope of the present invention is not so limited. The narrowband IF digitization receiver 500 of FIG. 5, the wideband IF digitization receiver 800 of FIG. 8, and / or the RF digitization receiver 900 of FIG. 9 may include circuitry 100 including a resonator 110 and a cancellation network. Shows an exemplary system that can be utilized to eliminate anti-resonance from resonator 110. However, these are merely examples of applications for circuit 100. It will be appreciated that other applications for the circuit 100 may be included within the scope of the present invention, but the scope of the present invention is not limited thereto.

Although the present invention has been described with some specific examples, it will be appreciated that the elements may be modified by one of ordinary skill in the art without departing from the spirit and scope of the invention. It is contemplated that the elimination of anti-resonance of the resonator and / or many additional benefits will be understood by the above description, and the forms described herein are merely exemplary embodiments and are not intended to bring about substantial changes, and the nature of the invention and It will be apparent that various changes may be made in the form, structure and / or arrangement of the component parts thereof without departing from the scope, or at the expense of all substantial benefit. It is the intention of the claims to include and / or incorporate such changes.

Claims

A resonator comprising an output connected to the node; And

A removal network comprising an output connected to said node,

And said cancellation network reduces the anti-resonance characteristic of said resonator response at said node by removing current flowing through the electrostatic capacitance of said resonator with current flowing through said removal network at said node.

The method of claim 1,

And the removal network comprises a capacitor having a value that at least substantially matches the electrostatic capacitance of the resonator.

The method of claim 1,

Further comprising an amplifier including a non-inverting output and an inverting output,

The resonator is coupled to one of the non-inverted output and the inverted output, and the removal network is coupled to the other of the non-inverted output and the inverted output.

The method of claim 1,

The resonator may include a surface acoustic wave type resonator, a bulk acoustic wave type resonator, a film bulk acoustic resonator type resonator, a crystal type resonator, a ceramic type resonator, and a micro-resonator. An apparatus comprising at least one of a micro-electromechanical system type resonator, and an electromechanical type resonator.

The method of claim 1,

The anti-resonance characteristic is removed from the response of the resonator.

Band pass filter;

A quantizer receiving the output of the band pass filter; And

Two digital-to-analog converters for feeding back the output of the quantizer to the input of the band pass filter,

The band pass filter comprises a resonator comprising an output connected to the node and a cancellation network comprising an output connected to the node,

The cancellation network having current flowing through the removal network at the node and removing current flowing through the electrostatic capacitance of the resonator to reduce the anti-resonance characteristic of the resonator response at the node.

The method of claim 6,

And the resonator comprises at least one of a surface acoustic wave type resonator, a bulk acoustic wave type resonator, a thin film volume elastic resonator type resonator, a crystal type resonator, a ceramic type resonator, a micro-electromechanical system type resonator, and an electromechanical type resonator.

The method of claim 6,

A delay circuit coupled between the output of the quantizer and the input of the digital-analog converter, and an additional digital-to-analog converter for feeding back the output of the quantizer received via the delay circuit to the input of the band pass filter. Containing device.

A radio frequency circuit for demodulating the received radio frequency; And

A band pass sigma-delta modulator for converting the demodulated signal into a digital signal,

The band pass sigma-delta modulator comprises a band pass filter, a quantizer for receiving the output of the band pass filter, and a digital-to-analog converter for feeding back the output of the quantizer to the input of the band pass filter,

The cancellation network having current flowing through the removal network at the node and removing current flowing through the resonator to reduce the anti-resonance characteristic of the response of the resonator at the node.

The method of claim 12,

And said band pass sigma-delta modulator having a narrow band response.

The method of claim 12,

And said band pass sigma-delta modulator having a wideband response.

Means for providing a resonance response comprising an output connected to the node; And

Anti-resonance removing means, including an output connected to said node,

The anti-resonance removing means has a current flowing through the anti-resonance removing means at the node and removes a current flowing through the electrostatic capacitance of the resonant response providing means to thereby cause the anti-resonance characteristic of the response of the resonance providing means at the node Reduce device.

The method of claim 20,

And said anti-resonance removing means comprises charge storage means, said charge storage means having an impedance value that at least substantially matches the electrostatic impedance of said resonance response providing means.

The method of claim 20,

Further comprising signal amplification means,

The amplifying means includes a non-inverting output and an inverting output, the resonance response providing means is connected to one of the non-inverting output and the inverting output, and the anti-resonance removing means is the remaining of the non-inverting output and the inverting output. Device connected to one.

The method of claim 20,

The means for providing a resonance response includes at least one of a surface acoustic wave type resonator, a bulk acoustic wave type resonator, a thin film volume elastic resonator type resonator, a crystal type resonator, a ceramic type resonator, a micro-electromechanical system type resonator, and an electromechanical type resonator. Device.

The method of claim 20,

The anti-resonance characteristic is removed from the response of the resonance response providing means.

Means for providing a band pass filter response;

Signal quantization means for receiving an output of the band pass filter response providing means; And

Digital analog conversion means for feeding back an output of said quantization means to an input of said band pass filter providing means,

The band pass filter providing means includes resonant response providing means including an output connected to the node and anti-resonance removing means including an output connected to the node,

The anti-resonance removing means has a current flowing through the anti-resonance removing means at the node and removes a current flowing through the electrostatic capacitance of the resonant response providing means to thereby cause the anti-resonance characteristic of the response of the resonant response providing means at the node. Device to reduce.

The method of claim 25,

And said anti-resonance removing means comprises a capacitor having a value at least substantially matching said electrostatic capacitance of said resonant response providing means.

The method of claim 25,

Signal amplification means further comprising a non-inverting output and an inverting output,

And the resonance response providing means is connected to one of the non-inverting output and the inverting output, and the anti-resonance removing means is connected to the other of the non-inverting output and the inverting output.

The method of claim 25,

A delay providing means connected between the output of the quantization means and an input of the digital-analog conversion means, and an additional feedback of the output of the quantization means received via the delay providing means to the input of the band pass filter response providing means. Further comprising digital-to-analog conversion means.

Means for demodulating a received radio frequency signal; And

Means for converting the demodulated signal from an analog signal to a digital signal,

The analog to digital conversion means,

Means for providing a band pass filter response;

Digital analog conversion means for feeding back an output of said quantization means to an input of said band pass filter response providing means,

The band pass filter response providing means includes resonant response providing means comprising an output connected to a node and anti-resonance removing means comprising an output connected to the node,

The anti-resonance removing means has a current flowing through the anti-resonance removing means at the node and removes a current flowing through the electrostatic capacitance of the resonant response providing means to thereby cause the anti-resonance characteristic of the response of the resonance providing means at the node Device to reduce.

The method of claim 31, wherein

And said analog-to-digital conversion means has a narrowband response.

The method of claim 31, wherein

The analog-to-digital conversion means has a wideband response.

Driving the resonator with a first current;

Driving a removal network with a second current having a polarity opposite to the first current; And

Coupling the first current and the second current at a node, wherein the coupling results in a decrease in the anti-resonance characteristic of the response of the resonator.

The method of claim 39,

Wherein the first current and the second current are applied to a load coupled to the node to reduce the anti-resonance characteristic from the voltage of the node.

The method of claim 39,

The coupling results in the removal of the anti-resonance characteristic of the response of the resonator.

The method of claim 39,

Reducing the anti-resonance characteristic of the response of the resonator makes the resonant characteristic of the resonator a dominant characteristic of the transfer function of the resonator.

Radio frequency circuitry for receiving radio frequency signals; And

A band pass sigma-delta modulator for directly converting the radio frequency signal into a digital signal,

The band pass sigma-delta modulator comprises a band pass filter, a quantizer receiving the output of the band pass filter, and a digital-to-analog converter feeding back the output of the quantizer to the input of the band pass filter,

The method of claim 43,

The band pass sigma-delta modulator is configured to directly convert the radio frequency signal into a digital signal prior to subsequent digital signal processing including at least one or more of filtering, demodulation of the radio frequency signal, or baseband signal processing. Device.

Means for receiving a received radio frequency signal; And

Means for directly converting the radio frequency signal from an analog signal to a digital signal,

The analog to digital conversion means,

Means for providing a band pass filter response;

Quantization means for receiving an output of said band pass filter response providing means; And

The method of claim 45,

And said analog-to-digital converting means converts said radio frequency signal directly into a digital signal prior to subsequent digital signal processing comprising at least one or more of filtering, demodulation of said radio frequency signal, or baseband signal processing.