KR20010073986A - Narrowband Interference Canceller System and its Method in CDMA System - Google Patents

Abstract

PURPOSE: An apparatus and a method for controlling a narrow-band interference noise in a CDMA system is provided to improve the efficiency of a system and smoothly transmit a CDMA information signal by being simply and directly connected with the system and removing and restraining a narrow-band interference noise signal component inputted to a receiving device of a CDMA base station. CONSTITUTION: An RF(Radio Frequency) down converter(100) converts a received RF analog signal into an IF(Intermediate Frequency) analog signal. A digital adaptive signal processor(102) converts the converted IF analog signal into a digital baseband signal, removes interference noise using an auto-regressive and LMS(Least Mean Square) algorithm, and converts the digital baseband signal into an IF analog signal. An RF up converter(104) converts the converted IF analog signal into an RF analog signal.

Description

Narrowband Interference Canceler System and Its Method in Code Division Multiple Access System

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a narrowband interference noise control apparatus and method thereof in a code division multiple access system, and more particularly, to convert a received radio frequency (RF) analog signal including interference noise into an intermediate frequency band (IF) signal. After that, by eliminating / suppressing narrowband interference noise introduced digitally using an autoregressive and least squares average (LMS) algorithm, the interference noise can be efficiently removed / suppressed and code division multiplexed. An apparatus for controlling narrowband interference noise in a code division multiple access system and a computer readable recording medium having recorded thereon a program for realizing the method can be provided.

The spread spectrum communication method, which is a feature of the conventional code division multiple access (CDMA) technology, communicates with a transmission bandwidth (broadband signal) much wider than the bandwidth of the information signal to be transmitted. Is transmitted after spreading. If the receiver side despreads using the same spreading signal, the original information signal is extracted.

That is, the transmitter transmits information and arrives at the receiver by receiving the noise signal or interference signal in the spread spectrum transmitted by the transmitter through the wireless transmission channel to reach the receiver. Extract.

In a system using CDMA technology, a low data rate code is spread over a wide bandwidth, and thus the same performance is achieved by using an error correction code having a much lower code rate than that of a frequency division multiple access (FDMA) or time division multiple access (TDMA) scheme. A lower ratio of signal energy to noise energy is required to maintain.

In fact, the signal-to-noise ratio (Eb / No) is changed by various propagation environment conditions such as multipath fading, moving speed, and changes in interference signals received from other systems, and it is also a major variable that determines subscriber capacity. To increase capacity, this value should be minimized and the noise energy ratio should be reduced.

In other words, the CDMA technology using the spread spectrum communication method is very robust against interference noise signals, but if the interference noise signal becomes stronger than the spread signal, it is difficult to transmit information, thus avoiding noise and interference in the wireless environment. There is a method for performing a strong power control (Power Control), but there was a problem that can not effectively control the interference noise for the unexpected interference noise signal.

The present invention has been made to solve the above problems, and converts the received radio frequency (RF) analog signal including interference noise into a signal of the intermediate frequency band, and then digitally autoregressive and An apparatus and method for controlling narrowband interference noise in a code division multiple access system for removing / suppressing narrowband interference noise (including jamming signals) using a least square average (LMS) algorithm Its purpose is to provide a computer readable recording medium having recorded thereon a program.

1 is a block diagram of an embodiment of a narrowband interference noise control apparatus in a code division multiple access system according to the present invention.

2 is a block diagram of an embodiment of the digital adaptive signal processing apparatus of FIG. 1 according to the present invention;

3 is a block diagram of an embodiment of the digital adaptive interference noise control unit of FIG. 2 according to the present invention;

4 is a diagram illustrating an embodiment of a down converter of FIG. 1 according to the present invention;

5 is a diagram illustrating an embodiment of an upconversion unit of FIG. 1 according to the present invention;

Figure 6 is an embodiment configuration of the first comparative analysis of Figure 3 according to the present invention.

7 is a diagram illustrating an embodiment of a second comparative analysis unit of FIG. 3 according to the present invention;

8 is a block diagram of a first embodiment of the interference noise controller of FIG. 3 according to the present invention;

9 is an explanatory diagram of an output level adjusting function compared to a reference level applied to the present invention.

10 is a block diagram of an embodiment of the adaptive interference cancellation filter of FIG. 8 in accordance with the present invention.

11 is a block diagram of a second embodiment of the interference noise controller of FIG. 3 according to the present invention;

12 is a block diagram of an embodiment of the adaptive compensation filter of FIG. 11 according to the present invention;

13 is a flowchart of a first embodiment of a narrowband interference noise control method in a code division multiple access system according to the present invention;

14 is a flowchart of a second embodiment of a narrowband interference noise control method in a code division multiple access system according to the present invention;

Explanation of symbols on the main parts of the drawings

100: RF down converter 102: digital adaptive signal processing device

104: RF up converter 106: RF input unit

108: IF converter 110: RF output

112: RF converter 202: A / D converter

204: digital down converter 206: digital adaptive interference noise control unit

208: digital upconverter 210: D / A converter

302: first comparison analysis unit 304: interference noise controller

306: second comparative analysis unit

The present invention for achieving the above object, in the interference noise control apparatus applied to the code division multiple access system, frequency downconversion for converting the received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal Way; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting to an intermediate frequency (IF) analog signal Digital adaptive signal processing means for; And frequency upconverting means for converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

On the other hand, the present invention provides an interference noise control apparatus applied to a code division multiple access system, comprising: frequency downconverting means for converting a received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise by using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) Digital adaptive signal processing means for converting into an analog signal; And frequency upconverting means for converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

On the other hand, the present invention is an interference noise control method applied to a narrowband interference noise control apparatus in a code division multiple access system, the method comprising: converting a received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; Stage 1; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting the converted intermediate frequency (IF) analog signal to an intermediate frequency (IF) analog signal. Second step; And a third step of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

On the other hand, the present invention is an interference noise control method applied to a narrowband interference noise control apparatus in a code division multiple access system, the method comprising: converting a received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; Stage 1; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) Converting to an analog signal; And a third step of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

Meanwhile, the present invention relates to a narrowband interference noise control device having a processor for controlling narrowband interference noise in a code division multiple access system, wherein the received radiofrequency (RF) analog signal is converted into an intermediate frequency (IF) analog signal. A first function to convert to; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting the converted intermediate frequency (IF) analog signal to an intermediate frequency (IF) analog signal. Second function; And a computer readable recording medium having recorded thereon a program for realizing a third function of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

Meanwhile, the present invention provides a narrowband interference noise control device including a processor for narrowband interference noise control using adaptive compensation in a code division multiple access system. IF) a first function of converting to an analog signal; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise by using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) A second function of converting to an analog signal; And a computer readable recording medium having recorded thereon a program for realizing a third function of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal.

Hereinafter, exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings.

1 is a block diagram of an embodiment of a narrowband interference noise control apparatus in a code division multiple access system according to the present invention.

The narrowband interference noise control device is a radio frequency (RF) (hereinafter simply referred to as RF) down converter (RF) 100, a digital for removing / suppressing the received narrowband interference noise signal components It is composed of an adaptive signal processing device 102, and an RF Up Converter 104.

The digital adaptive signal processing apparatus 102 includes an analog-to-digital (A / D) converter 202, a digital down converter (DDC) 204, a digital adaptive interference noise control unit 206, and a digital up converter (DUC). Digital up converter (208), and a digital-to-analog (D / A) converter 210 (see FIG. 2). Here, the digital adaptive interference noise control unit 206 is composed of a first comparison analyzer 302, an interference noise controller 304, and a second comparison analyzer 306.

The RF down converter 100 includes an RF input unit 106 and an IF converter 108 (see FIG. 5), and the RF up converter 104 also includes an RF converter ( 112 and RF output 110 (see FIG. 6).

An RF down converter 100, a digital adaptive signal processor 102, and an RF up converter 104, which are components of a narrowband interference noise control device, will be described in general. Is as follows.

First, the RF down converter 100 will be described.

The RF information signal received by the receiving antenna of the receiver is an RF / high frequency analog signal including a CDMA information signal and a narrowband interference noise signal component and cannot be directly converted into a digital signal. Accordingly, the received RF / high frequency analog signal should be down-converted to a frequency band capable of digital signal processing. Such conversion is commonly referred to as IF / middle frequency band conversion / chunk.

As described above, in order to perform digital signal processing to remove / suppress narrowband interference noise signal components from the signals received at the RF receiver, the RF / high frequency analog signal received at the receiving antenna is a frequency band capable of digital signal processing IF / Mid frequency band converts high frequency analog signals to low frequency band.

Next, the digital adaptive signal processing apparatus 102 converts an analog signal converted to IF / low frequency band into a digital signal by an A / D converter to remove narrowband interference noise signal components from the received signal for digital signal processing. And a suppression function, and converts the digital signal from which the narrowband interference noise signal component is removed / suppressed into an analog signal by a D / A converter.

Lastly, the RF up converter 104 converts the digital signal from which the narrowband interference noise signal component is removed / suppressed by the digital adaptive signal processing apparatus 102 to the RF input unit of the RF down converter 100. In order to convert the frequency into the same frequency band as the analog RF signal band of the input frequency band, the IF input signal input to the RF up-converter 104 is converted into an RF band and an RF output function.

2 is a block diagram of an embodiment of the digital adaptive signal processing apparatus of FIG. 1 according to the present invention.

The A / D converter 202 assigns the frequency of the IF band converted by the IF frequency converter 108 of the RF down converter 100 as an input to the frequency of the CDMA system. A digital signal is obtained by dividing an analog signal at a frequency of an IF band inputted to all bands or divided unit FAs according to the (FA: Frequency Allocation) (hereinafter simply referred to as FA) criterion. Convert to

That is, the analog IF signal converted to the low frequency band is sampled using a sample-and-hold amplifier according to a constant sampling rate, and the sampled data is quantized to a constant bit.

The power level of the analog IF signal input to the A / D converter 202 is a signal of a certain level or more in the RF / IF portion so that the A / D converter 202 does not leave the dynamic range (A / D converter) Adjusted to a reference level within the dynamic range of 202, it should be delivered to the input of the A / D converter 202, if the input signal level exceeds the set reference level of the dynamic range of the A / D converter 202. In this case, overflow (over-flow) or saturation (saturation) occurs, it is recognized that the A / D conversion can not be made or at a constant maximum level.

On the other hand, the digital down converter (DDC) 204 frequency shifts the data of the IF band digitized by the A / D converter 202 into a band capable of signal processing.

That is, it converts data into baseband frequencies that can be processed by a standard digital signal processor (DSP), decimation, narrowband lowpass filtering, gain reduction, resampling, And a polar coordinate conversion function, and if necessary, a gain control function is performed.

In other words, IF input data sampled with 12 bits of resolution is converted to baseband by a digital mixer and a numerically controlled oscillator (NCO), and decimation is performed by CIC ( Cascaded Integrator Comb) filter (4 to 32: 5th order), which can be decimated up to 5 times by the inverse filter and programmable 255 finite impulse response filter (FIR Filter) Impulse Response Filter (hereinafter, simply referred to as FIR filter) follows. Output data from the FIR filter is scaled by Digital Automatic Gain Control before being resampled in a polyphase FIR filter.

3 is a configuration diagram of an embodiment of the interference noise control unit of FIG. 2 according to the present invention.

The digital adaptive interference noise controller 206 in FIG. 2 includes a first comparison analyzer 302 (see FIG. 6), an interference noise controller 304 (see FIGS. 8 to 12), and a second comparison analyzer 306. (See FIG. 7), the interference noise controller 304 may be configured as a digital adaptive interference noise control filter, or may be configured by adding a digital adaptive compensation filter as necessary.

The first comparison analyzer 302 performs various functions for calculating absolute value / average value of the signal output from the digital down converter (DDC) 208, detecting a threshold value, and gain control. Functions can be performed in the Central Processing Unit (CPU) (hereafter referred to as CPU), Micro Processing Unit (MPU) (hereinafter referred to as MPU), or Digital Signal Processor (DSP). Some of the functionality may be centralized or, if necessary, designed to be performed in the digital down converter (DDC) 204.

The absolute value of the digitally converted signal is calculated from the digital output signals of the A / D converter 202 and the digital down converter (DDC) 204, and a predetermined window is set to obtain a peak value among the samples existing in each window. The average of the peak values obtained in each window is obtained for a predetermined number of windows. Here, the reason for obtaining the peak value is to ensure a stable output operating within a constant amplitude level, and for the overall information processing for adjustment of the final output level. The size of the window is adjustable and the average of the peaks is intended to be insensitive to noise.

The final output value of the system is set based on the most appropriate reference level required by the system connection standard by using the output of the absolute value and the average value calculation result. The upper limit value, the lower limit value, the maximum value and the minimum value are outputted. As necessary, it is necessary to detect each threshold value, and the output value can be adjusted by outputting a control value for gain adjustment for an output that deviates from the upper and lower thresholds based on the most appropriate reference level.

The interference noise controller 304 is a core block for the present invention and is composed of a central processing unit (CPU), a micro processing unit (MPU) or a digital signal processor (DSP), and various peripheral circuits, and received narrowband. The interference signal is included in the CDMA information signal according to the digital signal processing technique using the autoregressive and least mean square (LMS) algorithm (hereinafter simply referred to as LMS algorithm) and the adaptive compensation circuit algorithm. It performs the function of eliminating and suppressing band interference noise, and the main components are a combiner, a divider, a digital adaptive interference cancellation filter, a digital adaptive compensation filter / digital adaptive compensation circuit, and the like.

The adaptive algorithm applied for the digital adaptive interference noise control uses a generalized and well-proven LMS algorithm. By minimizing the output estimation error signal of the adaptive interference noise control filter and the adaptive compensation filter by the LMS algorithm, the interference noise signal component Then, only the desired information signal is output and the output estimation error signal converges to the desired information signal.

The digital adaptive interference noise control filter for the control of digital adaptive interference noise is a finite shock response filter (FIR filter) in which the adaptive weighting factor is multiplied by the time-delayed signal of the filter by a time delay of a constant size, and an infinite impact response filter. (IIR Filter), and various other digital filters in the form of adaptive digital filters.

In other words, the adaptive weighting factor function is corrected and supplemented at the sampling moment, and the adaptive weighting factor satisfies the LMS algorithm by reducing the difference between the received signal and the output value. That is, the purpose of the weight function is to minimize the final output error value and to minimize the mean square value of the error.

As described above, the output signal via the digital adaptive interference noise control unit 206 including the digital adaptive interference noise control filter and the digital adaptive compensation filter / digital adaptive compensation circuit is the narrowband interference received by the LMS algorithm and the above process. The noise signal component is removed and suppressed to output only the required CDMA information signal.

The second comparison analyzer 306 performs gain analysis and gain control functions, and the main functions and functions are centralized in the central processing unit (CPU), the micro processing unit (MPU), or the digital signal processor (DSP), and are necessary. Accordingly, the digital up converter (DUC) 208 may be designed to perform some of the functions.

The gain analysis function and the gain control function and operation are not clearly separated, and mutual functions and operations are performed by mixing, and the main functions are control signals and interference noise controllers for gain adjustment of the first comparison analyzer 302. Gain adjustment is made to output an output value in accordance with the final output level set using the output of 304. In other words, for the signal level between the upper and lower thresholds, the gain is lowered below the upper threshold, and the signal level between the lower and minimum thresholds is adjusted above the lower threshold and the upper limit is adjusted so that the output level is centered on the reference level. Adjust the gain appropriately so that it is within the upper and lower thresholds.

In addition, depending on the needs of design convenience, the functions of the digital up-converter 208 and the D / A converter 210 perform the inverse functions of the digital down-converter 204 and the A / D converter 202, and the D / A The sampling rate of the converter 210 is set higher than the sampling rate of the A / D converter 202 in order to improve conversion efficiency. At this time, the analog signal at the intermediate frequency of the IF band received for the divided unit FA by dividing a series of FAs divided / assigned into a constant frequency band according to the frequency allocation rule of the CDMA system in the A / D converter 202. In case of converting into digital signal, ADD or MUX function should be added and rearranged in FA order according to frequency allocation rule in order to synthesize the signal processed in each FA unit.

4 is a diagram illustrating an embodiment of a down converter of FIG. 1 according to the present invention.

The RF down converter 100 includes an RF input unit 106 and an input RF analog for receiving an RF analog signal received from a receiving antenna that receives an RF analog signal including a CDMA information signal. In order to convert the signal into a digital signal is composed of an IF converter 108 for converting the RF signal into IF signal components in a low frequency band (intermediate frequency: IF).

The RF information signal received by the receiving antenna of the receiver is an RF / high frequency analog signal containing a CDMA information signal and a narrowband interference noise signal component and cannot be directly converted into a digital signal.

Therefore, the received RF / high frequency analog signal is converted into a frequency band capable of digital signal processing, and the received RF / high frequency analog signal must be down converted into an appropriate frequency band. Such a conversion is converted into an IF / middle frequency band. It is called cloth.

As described above, the RF down converter 100 receives the RF received by the receiving antenna to perform digital signal processing to remove / suppress the narrowband interference noise signal component from the signal received at the RF receiving end. The analog signal of high frequency is converted into IF / middle frequency band, that is, a frequency band capable of digital signal processing, that is, a high frequency analog signal is converted into a low frequency band, and each detailed configuration and function thereof are as follows.

The band pass filter (BPF) 402 is located at the very beginning of the RF down converter 100 and is one of the key components constituting the RF input unit 106. It passes only the frequencies of the band and does not pass the upper and lower band frequencies other than the bandwidth of the BPF.

The band pass filter 402 is typically located at the input of a mixer 408 that modulates at an intermediate frequency, in order to determine the bandwidth of the intermediate frequency modulation. When designing a receiver circuit, one of the most important basic factors is to determine the bandwidth of the signal. Usually, the bandwidth is determined in the BPF, and the selection criteria for the components used in the BPF are, among other things, bandwidth, self-loss, and VSWR. Since the selected BPF has its own loss while filtering the RF signal, it is necessary to select a component that has low self-loss of components, low VSWR, and is suitable for the bandwidth and frequency band used in the circuit configuration. .

The automatic gain controller (AGC) 404 operates in conjunction with the attenuator and performs the function of appropriately adjusting the range of gain when the change in the input gain is extreme. That is, since the A / D converter 202 of the digital adaptive signal processing apparatus 102 has a dynamic range capable of A / D conversion, an input signal beyond the limit of the dynamic range becomes impossible to A / D conversion and overflows. (Over Flow) or saturation. In order to prevent the overflow and saturation of the A / D converter 202, an excessive gain change of the RF input signal should be prevented. For this purpose, an automatic gain controller 404 is required, and an automatic gain controller 404 is combined with an attenuator to perform an attenuation operation of the required value.

Since the input value of each element and circuit constituting the circuit has a marginal gain, if the maximum power over the desired input is transmitted to the circuit based on this marginal gain, the circuit may be severely damaged. A device is needed to perform this function in the automatic gain controller 404 and the attenuator. That is, based on a predetermined reference value, when power of a predetermined power or more is transmitted, the transmission power is attenuated and transmitted to the next circuit.

In addition, the attenuator used mainly is determined based on the maximum input power of the circuit of the rear end of the attenuator, and in consideration of the attenuation ratio, to predict the power that can be transferred to the maximum power in the circuit to select the appropriate device. In order to keep the IF output level of the AGC 404 constant, the attenuator compares the output level of the IF in the AGC, feeds it back to the attenuator, and adjusts the RF input power. The comparison voltage to be compared is transmitted to the attenuator, compared with the reference voltage, and the RF transmission power is adjusted.

After the amplifier (AMP) 406 adjusts the deviation of the gain by the automatic gain controller (AGC) 404 when the deviation of the gain in the signal bandpassed by the band pass filter (BPF) 402 is large, Raise the low level signal to a constant level.

Mixer 408 is a frequency signal of 1.75 GHz to 1.76 GHz and 1.685 of first local oscillator 410 inputted from amplifier AMP using the frequency generated by first local oscillator 410. The frequencies of GHz are mixed to produce a first intermediate frequency of 65 MHz to 75 MHz. That is, the mixer 408 converts two signal frequencies into a first intermediate frequency by using the frequency of the first local oscillator 410 and the signal output from the amplifier AMP 406 as input signals. The functions are as follows.

The frequency filtered by the band pass filter (BPF) 402 is one band and several channels exist therein. However, in order to secure each channel, the number of channels and the number of filters must be the same. Therefore, if a frequency of all bandwidths is received through one filter and converted into one frequency, one filter is actually required.

In addition, since a mixer converts a high frequency signal, a low frequency carrier signal loaded at a high frequency does not change even if a local oscillator frequency is added to or subtracted from the converted frequency. A mixer that performs a function has its own loss, just like a filter, which is a loss that occurs when operating to mix and add a local oscillator frequency signal and an input signal.

Therefore, the mixer should be used with low self-loss (ie, low conversion loss, noise loss, etc.), and the precautions when designing the mixer should be the local oscillator of the mixer (Mixer). Local Oscillator) Be sure to place PAD resistors at the output and RF inputs, and if there is a large difference in the power level of the local oscillator output and the RF input, the PAD resistance is increased because of the large self-loss that occurs in the mixer. Use it to adjust it properly.

The bandpass filter 412 filters out only the signals of the IF signal frequency band (65 MHz to 75 MHz) among various intermodulation signals generated by the mixer 408, and the other intermodulation signal frequencies This eliminates the effect on the IF signal frequency.

Since the amplifier (AMP) 414 acts as a second amplifier and cannot obtain a certain level of gain by the first amplifier 406, the gain is adjusted using a second amplifier, and if necessary, a third amplifier. 422 is used to adjust the gain of the final output to the desired level of gain.

The second mixer 416 performs a similar function as the first mixer 408, but has a different input / output frequency band. That is, the frequency band input to the second mixer 416 is an IF frequency converted / output by the first mixer 408 and is a frequency of 65 MHz to 75 MHz band. Thus, the oscillation frequency (64 MHz) of the second local oscillator 418 is used to generate the final output IF frequency (6 MHz).

Since the band pass filter 420 filters only signals of a required frequency band among intermodulation signals generated by the second mixer 416, the frequency band passed through the band pass filter 420 has a center frequency of 6 MHz. Only in the frequency band of 1.0 MHz to 11 MHz.

The amplifier 422 located at the last stage is an amplifier for providing a signal level suitable for the input signal level required by the digital adaptive signal processing apparatus 102 with an IF signal level having a center frequency of 6 MHz.

The basics of the frequency conversion are made in the mixers 408 and 416, using the oscillation frequencies of the first local oscillator 410 and the second local oscillator 418, respectively, to convert the input RF analog carrier frequency to the first order transform and the first. Perform secondary transformation.

The first local oscillator 410 and the second local oscillator 418 coupled directly with the first mixer 408 and the second mixer 416 are signal sources for converting an RF input analog signal into an IF medium frequency band. It is called PLL (Phase Lock Loop).

PLL VCO module is a module used as Local Oscillator Frequency (VCO) that supplies the frequency and power level required for the up / down converter of cellular or PCS band. It is a voltage controlled oscillator (VCO). ), Loop Filter and Phase Detector. The basic operation is as follows.

The output of the voltage controlled oscillator (VCO) is divided by a frequency divider, and then compared at a reference frequency / phase detector (Reference Frequency and Phase Detector) to adjust the tuning point of the VCO so that the two signals are the same frequency. In this case, the output of the phase detector includes DC and various other unnecessary frequency components, so it is removed through a loop filter, and the loop filter has a response speed, stability, and phase noise. (Phase Noise) is determined.

In order to improve the phase noise of the PLL module, a VCO is fabricated using a high Q coaxial resonator, and all Lumped devices use a small sized device to produce a frequency synthesizer. Synthesizer).

Also, the final stage amplifier 410 of the IF converter 108 is an amplifier for providing a signal suitable for the input signal level required for the digital adaptive signal processing apparatus 102.

5 is a diagram illustrating an embodiment of an upconversion unit of FIG. 1 according to the present invention.

RF Up Converter 104 is a digital signal received by the digital adaptive signal processing device 102, the narrowband interference noise signal component is removed and suppressed by the D / A converter 210, An RF converter 112 for receiving a signal converted into an analog signal and converting the signal into an RF frequency band of the same frequency band as that input to the RF input unit 106 of the RF down converter 104, and interference And an RF output unit 110 for outputting the noise canceled and suppressed signal.

That is, the functions of the RF up converter 104 generally perform functions opposite to those of the RF down converter 100, and the RF converter 112 and the RF output unit. A low frequency band analog signal converted by the D / A converter 210 of the digital adaptive signal processing apparatus 102 as an input signal, and inputs an analog signal of the low frequency band to the RF input unit 106. Convert to an RF frequency band of the same frequency band.

The band pass filter (BPF) 502 is located in the RF converter 112, which is the first stage of the RF up-converter 104, and is one of the core elements constituting the RF up-converter 104. Only the frequency of the band is passed and the upper band frequency and the lower band frequency other than the bandwidth of the band pass filter 502 are not passed.

That is, the information signal that has completed the digital signal processing is a signal of 10 MHz bandwidth having a center frequency of 6 MHz, and when input to the RF up-conversion unit 104, it can be input including a frequency that is close to the band. have. At this time, the band pass filter 502 has a function of removing frequencies other than unnecessary bands, and the band pass filter 508 filters only the frequency bands necessary among the frequencies generated by the mixer 504, The bandpass filter 516 filters the frequency band for the final output to transmit only the frequency band of the desired output.

In general, the bandpass filter 516 located at the final output stage filters only the final output frequency band among the frequencies generated by the mixer of " 510 ".

In the RF up converter 104, a first local oscillator 512 and a second local oscillator 506 are present, and the frequencies of the first local oscillator 512 and the second local oscillator 506 are As a local oscillator having the same frequency characteristics used in the RF down-conversion unit 110, the main function is to convert the input IF frequency to the final output RF analog carrier frequency using the oscillation frequency of the local oscillator. Since the "410" local oscillator and the "512" local oscillator are local oscillators having the same frequency characteristics, both of them are referred to as first local oscillators. Also, the "418" local oscillator and the "506" local oscillator also have the same frequency characteristics. Both of them are called second local oscillators.

As described above, converting a frequency by a combination device and a combination of frequencies for converting a predetermined frequency into another frequency band is called a mixer, and is composed of a mixer of "504" and a mixer of "510". The basic function is similar to that of the mixer of the RF down converter 110.

In addition, the mixer of the RF up-converter 104 includes two mixers 504 and 510, like the RF down converter 100, and one mixer as necessary. It is also possible.

The second local oscillator 506 and the mixer 504 located at the input end of the IF input signal of the RF Up Converter 104 are the second local oscillator 418 located at the IF converter 108 of the RF down converter. ) And the function of the mixer 416, using the IF input signal of the center frequency 6 MHz input from the digital adaptive signal processing apparatus 102 and the frequency generated by the second local oscillator 506. Generates an intermediate frequency of 65 MHz to 75 MHz.

In addition, the mixer of "510" mixes the frequency of 65 MHz to 75 MHz generated by the mixer of "504" with the frequency of 1.685 GHz of the oscillation frequency of the first local oscillator 512, and thus the frequency of 1750 MHz to 1760 MHz. Generate.

The SAW filter 508 has the narrowest bandwidth and the best filtering effect among various types of filters, and detects only a carrier frequency band in which a signal is carried. The SAW filter 508 has a loss of about -23 ~ -24 dB of its own loss, requires a great deal of design due to the large time delay, and matching and RF across the SAW filter It should have the lowest self-loss, as it can have the greatest impact on front-end losses. Therefore, in consideration of the SAW filter's own characteristics, it is necessary to select a component having the most suitable characteristics for the system.

The attenuator 514 functions as a gain attenuator. When the circuit design is designed with a gain greater than or equal to a set gain value, or when a power level larger than a reference value set by the power level input to the system is input, In order to output the required output gain value, the overall gain is adjusted to the set gain value.

In other words, if the maximum power of the output of the RF output circuit 110 is connected to the maximum value of the required value is transmitted, the damage to the circuit can be enormously damaged, the device for preventing this is attenuator, the power of more than the predetermined power in such attenuator When transmitted, the transmission power is attenuated by a certain reference value and transmitted to the next circuit.

The matching circuit 518 of the RF up-converter 104 is a matching (matching) circuit for most efficiently delivering the output of the RF up-converter 104 to the next stage, and typically uses a resistor of 50 ohms or 80 ohms. The impedance is matched, and the transfer efficiency is maximum when the impedance is completely matched.

FIG. 6 is a diagram illustrating an embodiment of a first comparative analysis unit of FIG. 3 according to the present invention. FIG.

The first comparison analyzer 302 includes an absolute value and average value calculator 600, a signal detection and control signal generator 602, and main functions and functions are performed by a CPU, a micro processing unit (MPU), or a digital signal processor (DSP). : Digital Signaling Processor), the detailed operation is as follows.

In the digital output signals of the A / D converter 202 and the DDC 204, the absolute value calculator 600 obtains the absolute value of the digitally converted signal. The reason for obtaining the absolute value is that the output values of the A / D converter 202 and the DDC 204 should be within a constant amplitude level rather than having a constant power level. For example, if the square value is used to have a constant power level, it is advantageous to use an absolute value since a value greater than 1 becomes larger and a value smaller than 1 becomes smaller.

The average calculator 600 is located at the rear of the absolute calculator 600, sets a predetermined window for the output of the absolute calculator, obtains a peak value from the samples in each window, and then obtains a predetermined number of windows in each window. Average the peaks. The reason for obtaining the peak value is to ensure a stable output that operates within a constant amplitude level, and is for general information processing for adjusting the final output level of the narrowband interference noise control device. The size of the window is adjustable and the average of the peaks is intended to be insensitive to noise.

The signal detection and control signal generator 602 detects the level of the output of the average calculator 600 in order to adjust the final output level of the narrowband interference noise control device, and stores the reference level, the upper limit threshold, and the lower limit threshold in advance. After analyzing the predicted value which needs to adjust the current gain and the final output level in comparison with the maximum value and the minimum value, the output of the average calculator 600 sensed through the first output is sent to the interference noise controller 304, and The output terminal generates a control signal for adjusting the final output level of the narrowband interference noise control device according to the comparison / analysis result and outputs it to the second comparison analyzer 306.

7 is a configuration diagram of an embodiment of a second comparative analysis unit of FIG. 3 according to the present invention.

The second comparison analyzer 306 includes a gain analyzer 700 and a gain adjuster 702, and main functions and functions thereof are performed by a central processing unit (CPU), a micro processing unit (MPU), or a digital signal processor (DSP). In the following, the detailed operation of the second comparison analyzer 306 is as follows.

The input of the gain analyzer 700 is composed of the output of the interference noise controller 304 and the output of the signal sensing and control signal generator 602 of the first comparison analyzer 302.

The functions and operations of the gain analyzer 700 and the gain regulator 702 are not clearly separated, but mutual functions and operations are mixed, and main functions are controls for gain adjustment of the first comparison analyzer 302. Gain is adjusted to output an output value according to the final output level set in FIG. 9 by using the signal and the output of the interference noise controller 304.

In other words, the signal level between the upper limit threshold and the maximum value is lowered below the upper limit threshold, and the signal level between the lower limit threshold and the minimum value is adjusted to the upper limit of the gain above the lower limit threshold, and the final output level is shown in FIG. Adjust the gain appropriately so that it exists within the upper and lower thresholds with respect to the reference level.

8 is a block diagram of a first embodiment of the interference noise controller of FIG. 3 according to the present invention, in which the interference noise controller 304 includes a combiner 806, 808, a divider 810, 812, and an adaptive interference cancellation filter 802. , And LMS algorithm 804.

The adaptive algorithm applied to the interference noise controller 304 is an adaptive weighting factor function as an algorithm for real-time adapting the adaptive interference cancellation filter 802.

The adaptive weighting coefficient function uses a generalized and well-established least mean square (LMS) algorithm, which minimizes the estimated error signal of the output, eliminating interference noise signals and outputting only the desired information signal.

The main functions of the first combiner 806 are the input signal Zk of the interference noise controller 304 (ie, the output signal of the first comparison analyzer) and the estimated output value of the adaptive interference cancellation filter 802 ( ) Combines the backward feedback signal and generates an output error value εk generated by the combination.

The output error value of the first combiner 806 is adapted to be the minimum mean square value by the LMS algorithm. Further, the second coupler 808 is an estimate of the output error value εk of the first coupler 806 ( ) And the output estimate of the adaptive interference cancellation filter ( Of the feedback feedback signal of the ).

In addition, the output error value [epsilon] k of the first combiner 806 serves as a component of the adaptive transfer function of the LMS algorithm 804, and induces an adaptive weighting coefficient of the adaptive interference cancellation filter to generate an adaptive interference cancellation filter 802. ) Is adapted for each sampling instant.

Accordingly, the output of the adaptive interference cancellation filter is adaptively changed and output at each sampling moment, and the output value is backward feedback coupled to the first combiner 806 to operate adaptively to minimize the value of the minimum mean square.

The detailed design of the adaptive interference cancellation filter 802 in the interference noise controller 802 can be seen in detail in the design method of the adaptive interference cancellation filter (see FIG. 10), and the input signal of the adaptive interference cancellation filter is The digitally adaptive filter in the form of a finite impulse response (FIR filter) or an infinite impulse response filter (IIR) multiplied by the adaptive weighting factor (ai, k) Then, the total modeled output is added and outputted, and the adaptive weighting coefficient algorithm is shown in Equation 1 below.

Where ak is an adaptive weighting factor function, μ is an adaptive weighting factor, γk is an input power estimation function of the adaptive interference cancellation filter, ρ (εk) is an adaptive transfer function, and Xk is an estimated input function of the adaptive interference cancellation filter.

The adaptive weighting coefficient function of Equation 1 is corrected and supplemented at the instant of sampling, and the adaptive weighting coefficient is added to reduce the difference (error) between the received signal and the output value. To satisfy the LMS algorithm. That is, the purpose of the weight function is to minimize the final output error value and minimize the mean square value of the error.

In addition, the input signal of the adaptive interference cancellation filter 802 has a time delay of Tc and is multiplied by the adaptive weighting factor of the adaptive interference cancellation filter (FIR Filter: Finite Impulse Response) or infinite impulse response filter (IIR). Filter: This is modeled through digital adaptive filter in the form of Infinite Impulse Response. As such, the output signal via the interference noise controller 304 including the adaptive interference cancellation filter 802 and the LMS algorithm is removed and suppressed by the narrowband interference noise signal component received by the above process. Output only the signal.

9 is an explanatory diagram of an output level adjustment function compared to a reference level applied to the present invention, and shows a final output model of a narrowband interference noise control device.

The final output of the narrowband interference noise control device is gain adjusted to output the output value according to the final output level set in the CDMA system to which it is mounted. In other words, for the signal level between the upper and lower thresholds, the gain is lowered below the upper threshold.The signal level between the lower and minimum thresholds adjusts the upper and lower gains above the lower threshold and adjusts the final output level to the reference level. Adjust the gain appropriately so that it is centered and within the upper and lower thresholds.

A / D converter when an input signal level is input that exceeds the maximum value (A / D conversion dynamic range of the A / D converter) set by the CDMA system in which the adaptive narrowband interference noise control device is mounted. This causes saturation errors, which tends to degrade the performance of the entire system.

Therefore, in order to stabilize the system, the overflow level of the input signal needs to be adjusted so that the level of the signal may exist within the dynamic range of the A / D converter.

In general, the signal level in the CDMA system can be set to the system output level or system connection level in each connection point, module unit, unit unit, and also can be variously adjusted according to the mounting position of the present invention.

As an example, the output signal level based on the connection point of the LNA module of the CDMA receiving system can be modeled as follows. That is, the value of +/- 40 dBm is set as the upper limit maximum value and the lower limit minimum value based on the reference level 0 dBm, and the value exceeding this range is processed by the overflow (Over Flow) to perform the gain control.

In addition, the output threshold level of the system is set to +/- 20 dBm based on the reference level (0 dBm) to have a dynamic output range of 40 dBm with each value as the upper and lower thresholds. Therefore, when the signal output level exists between the maximum value and the upper limit threshold and between the minimum value and the lower limit threshold, gain control is performed so that the level of the output signal is within the dynamic output range.

FIG. 10 is a block diagram of an adaptive interference cancellation filter of FIG. 8 according to the present invention, and shows a detailed design of an adaptive interference filter (ANF) 802 of the interference noise controller 304. The description has already been made with reference to FIG. 8, but will be described again as follows.

Adaptive Noise Filter (ANF) 802 is comprised of combiners 1000, 1002, time delayer 1004 and multiple multipliers 1006.

The third combiner 1000 is a combiner that performs the same function as the second combiner 808 of FIG. 8, and estimates the output error value εk ( ) And Output Estimation of Adaptive Interference Cancellation Filter The feedback feedback of the ).

Input signal of adaptive interference cancellation filter ) Is a finite impulse response (FIR filter) or infinite finite impulse response (FIR) that is produced by multiplying the time-delayed signal by the Tc-sized time delay with the adaptive weighting factor (ai, k) produced by the adaptive transfer function of the LMS algorithm. It can be modeled as a digital adaptive filter composed of an Infinite Impulse Response Filter (IIR), and the fourth combiner 1002 adds the entirety of the output modeled by the digital adaptive filter to the third combiner 1000. It is backward feedback output and the adaptive weighting coefficient algorithm is shown in Equation (1).

11 is a configuration diagram of a second embodiment of the interference noise controller of FIG. 3 according to the present invention.

The interference noise controller 304 differs from the configuration in FIG. 8 by the combiner 1106, 1108, the dividers 1110, 1112, the adaptive interference cancellation filter 1104, the adaptive compensation filter 1100, and the adaptive compensation algorithm 1102. In this case, the adaptive compensation filter 1100 is added to the interference noise controller 304 illustrated in FIG. 8.

In the application of an algorithm for minimizing the error signal that asymptotically converges to the information signal, it is the most ideal system when the error signal is gradually approached to "0" and "0" is achieved. However, errors exist in all systems, and system stability is a problem due to errors. Therefore, adding a compensation circuit in order to reduce the output error of the system due to the received narrowband interference noise signal component can give an output error and improve the convergence function.

The interference noise controller 304 may be composed of a central processing unit (CPU), a micro processing unit (MPU), or a digital signal processor (DSP) and various peripheral circuits. The interference noise signal component is autoregressive. Digital signal processing and adaptive compensation algorithms using the LMS algorithm and elimination and suppression of narrowband interference noise included in CDMA information signals.

The main function of the fifth combiner 1106 is the output signal Zk of the first comparison analyzer 302 and the estimated output value of the adaptive interference cancellation filter 1104 ( ) Combines the backward feedback signal and generates an output error value εk generated by the combination.

The output error value of the fifth combiner 1106 is adapted to be the minimum mean square value by the CLMS algorithm and the sixth combiner 1108 is an estimate of the output error value? K of the fifth combiner 1106 ( ) And the output estimate of adaptive interference cancellation filter 1104 ( Of the feedback feedback signal of the ), And the output error value [epsilon] k of the fifth coupler 1106 serves as an input of the adaptive compensation filter 1100.

In addition, the output Vk of the adaptive compensation filter 1100 acts on the adaptive compensation least square averaging algorithm (CLMS Algorithm) 1102 to generate a weighting coefficient function of the adaptive interference cancellation filter and the adaptive compensation filter. And adapt the value of the adaptive compensation filter every sampling instant.

Accordingly, the output of the adaptive interference cancellation filter 1104 is adaptively changed and output at each sampling moment, and the output value is backward feedback coupled to the fifth combiner 1106 so that the square mean value of the output error of the fifth combiner is minimized. Adaptive operation

The adaptive algorithm applied to the interference noise controller 304 is applied in two separate ways, the first algorithm is the least square average (LMS) algorithm applied to the adaptive interference cancellation filter 1104, and the second algorithm is the adaptive compensation of FIG. An adaptive compensation algorithm applied to the filter 1100, and the two algorithms are collectively referred to as a Compensated Adaptive LMS Algorithm (CLMS algorithm) 1102.

Here, the adaptive compensation algorithm is called the adaptive compensation algorithm because it is related to the adaptive compensation filter, and the basic structure and function of the algorithm is generally similar to the verified least square average (LMS) algorithm.

The two algorithms have similar characteristics and shapes, and adjust the adaptive weighting coefficient of the adaptive interference cancellation filter 1104 and the adaptive weighting coefficient of the adaptive compensation filter 1100 by applying the output of the adaptive compensation filter 1100. do.

In addition, the adaptive compensation least square averaging algorithm (CLMS Algorithm) algorithm 1102 eliminates the interference noise signal by minimizing the output estimation error signal of the adaptive compensation filter 1100 and outputs only the desired information signal. In other words, the output estimation error signal converges to the desired information signal.

A detailed configuration diagram of the adaptive noise canceling filter (ANF) 1104 is shown in FIG. 10, and the input signal of the adaptive interference canceling filter is adaptive weighting coefficient function (ai) to a time delayed signal due to a time delay of Tc size. can be modeled through a finite impulse response filter (FIR filter), an infinite impulse response filter (IIR filter), and an adaptive filter in the form of various other digital filters. ((Equation 1) in the description of FIG. 8).

The detailed configuration diagram of the adaptive compensation filter 1100 is shown in FIG. 10, and an input signal of the adaptive compensation filter is primarily an output signal processed by the adaptive interference cancellation filter 1104 and an output of the first comparison analyzer. The signal Zk is an error signal outputted by combining (1106), and is processed by being time-delayed by a time delay of a size Tc in the adaptive compensation filter. The input signal of the adaptive compensation filter 208 is a finite impulse response filter (FIR filter) in which the time delay of Tc magnitude is multiplied by the adaptive weighting factor function (ci, k) of the adaptive compensation filter, and the infinite shock response. Filter (IIR Filter: Infinite Impulse Response Filter) and other digital adaptive filters (see Equation 2 in FIG. 12).

The adaptive compensation filter 1100 mainly aims at eliminating the vibration convergence and the interference noise cancellation function of the adaptive interference cancellation filter. The adaptive compensation filter 1100 is added to the output of the adaptive interference cancellation filter.

As described above, the output signal of the interference noise controller 304 including the adaptive interference cancellation filter 1104 and the adaptive compensation filter 1100 is signal-processed according to the CLMS algorithm 1102 and received by the above process. The narrowband interference noise signal component is removed and suppressed to output only necessary CDMA information signals.

12 is a block diagram of an embodiment of the adaptive compensation filter of FIG. 11 according to the present invention.

Adaptive Compensated Filter 1100 is comprised of combiners 1202, 1204, time delay 1200, and multiple multipliers 1206.

The seventh coupler 1202 has an output error value? K of the fifth coupler 1106 of FIG. 11 and an output value of the eighth coupler 1204 in the adaptive compensation filter ( In combination with the backward feedback of < RTI ID = 0.0 >

The adaptive compensation filter 1100 estimates the error output of the seventh combiner 1202 ( ) Is time-delayed by the Tc-sized time delay unit 1200 and multiplied by the adaptive weighting factor function Ci, k produced by the adaptive transfer function of the CLMS algorithm 1102 (1206). It is a digital adaptive filter composed of a finite impulse response filter (FIR filter) or an infinite impulse response filter (IIR filter) that compensates for interference noise.

The eighth combiner 1204 adds the entirety of the output modeled by the digital adaptive filter and outputs the backward feedback to the seventh combiner. The adaptive weighting coefficient algorithm is represented by Equation 2 below.

That is, FIG. 12 is a detailed configuration diagram of the adaptive compensation filter 1100 applied to the output terminal. The input signal of the adaptive compensation filter is primarily an output signal (processed by the adaptive interference cancellation filter 1104). ) And the input signal Zk (output signal of the first comparison analyzer) of FIG. 11 are combined (1106) and outputted as an error signal [epsilon] k.

Where ck is an adaptive weighting coefficient function, μc is an adaptive weighting coefficient, γk, c is an input power estimation function of the adaptive compensation filter, νk is an output estimation function of the adaptive compensation filter, and Ek is an estimated input vector function of the adaptive compensation filter.

The adaptive weighting coefficient function of the adaptive compensation filter of Equation (2) is corrected and supplemented at the sampling instant in the same manner as the adaptive weighting coefficient function of the adaptive interference cancellation filter of Equation (1), and the adaptive compensation filter is adaptive. The weighting factor satisfies the LMS algorithm by acting to reduce the difference between the received signal and the added value.

That is, the purpose of the weight function of the adaptive compensation filter is to minimize the error value of the output signal through the adaptive compensation filter and minimize the mean square value of the error.

The adaptive compensation filter 1100 has a main purpose of improving the vibration convergence and the interference noise canceling function of the adaptive interference cancellation filter 1104, and is added to the output of the adaptive interference cancellation filter 1104.

13 is a flowchart of a first embodiment of a method for controlling narrowband interference noise in a code division multiple access system according to the present invention.

Since the detailed description has already been made in the relevant part, the overall method will be described here (see FIGS. 1 to 10).

Receives an RF analog signal containing CDMA information and converts it into an IF analog signal (1300), and then converts the IF analog signal into an IF digital signal (1302) and then converts it into an appropriate sampling rate in the IF band. 1/4 to 1 to select a desired FA from the quantized A / D converted signals, convert the digital signal of the selected IF band to the baseband, and facilitate the digital processing of the oversampled signal. Decimation is performed at / 8 (1304).

Subsequently, autoregressive and least squares average (LMS) algorithms are used to remove and suppress narrowband interference noise and control the final output within a predetermined reference range (1306).

The digital output signal is then converted to baseband and decimated from 1/4 to 1/8 to restore the original IF band signal where the narrowband interference noise has been removed or suppressed to the original IF band signal (1308). The converted IF digital signal is converted into an IF analog signal (1310).

Thereafter, the IF analog signal is converted into an RF analog signal and output (1312).

FIG. 14 is a flowchart of a second embodiment of a narrowband interference noise control method in a code division multiple access system according to the present invention, and is a narrowband interference noise control method using adaptive compensation.

Since the detailed description has already been made in the relevant section, the overall method will be described here (see FIGS. 1 to 7, 9 to 12).

Receives an RF analog signal containing CDMA information, converts it to an IF analog signal (1400), and then converts the IF analog signal to an IF digital signal (1402), and then converts it to an appropriate sampling rate in the IF band. 1/4 to 1 to select a desired FA from the quantized A / D converted signals, convert the digital signal of the selected IF band to the baseband, and facilitate the digital processing of the oversampled signal. Decimation is performed at / 8 (1404).

Subsequently, autoregressive, least square mean (LMS) algorithms, and adaptive compensation algorithms are applied to remove and suppress narrowband interference noise, and control the final output within a predetermined reference range (1406).

Then, after the digital output signal converted to baseband and decimated from 1/4 to 1/8 to remove or suppress narrowband interference noise is restored to the original IF band signal (1408), The converted IF digital signal is converted into an IF analog signal (1410).

Thereafter, the IF analog signal is converted into an RF analog signal and output (1412).

The present invention described above is capable of various substitutions, modifications, and changes without departing from the spirit of the present invention for those skilled in the art to which the present invention pertains. It is not limited by the drawings.

The present invention as described above has the following excellent effects.

First, by simply connecting directly to a system using the CDMA technology, the narrowband interference noise signal component flowing into the CDMA base station receiver is removed and suppressed, thereby improving the efficiency of the system and smoothly transmitting the CDMA information signal.

Second, it minimizes the output error and maintains the output signal at a constant level, thereby increasing the stability and efficiency of the system.

Third, in order to prevent the difficulty of baseband signal processing, by directly converting and using the received RF analog signal, it is easy to develop and further change the system by removing the interference noise signal component before despreading the received signal. It is possible to simply remove the narrowband interference noise signal component without modification.

Fourth, in the CDMA system equipped with the present invention, it is possible to prevent an error due to a change in power level due to a large level of sudden interference noise input, and to prevent a system failure due to a large power signal input.

Fifth, by incorporating the present invention in a CDMA system, it is possible to prevent call disconnection of subscribers caused by narrowband interference noise signals.

Sixth, proper gain control for stabilization of the output level is possible for irregularly changing received signals, the adaptive coefficient value can be adjusted, and the steady state convergence time can be adjusted and the output error signal can be minimized.

Seventh, the present invention can be flexibly changed according to the frequency allocation regulation, the deployment / operation of the base station system, and the frequency usage.

Eighth, widening and integrating a specific band and a specific frequency band can be performed to facilitate frequency change.

Ninth, by applying the RF / IF frequency signal processing and digital signal processing technology can be applied to SDR (Software Defined Radio) technology that will be the basis of the future information and wireless communication system technology.

Tenth, it can be applied to various fields (ie, base station system, repeater system, terminal field, etc.) by light and small size reduction.

Eleventh, it is possible to use a wideband CDMA frequency by overlaying a frequency band that is already in use and to improve frequency utilization efficiency.

Twelfth, a simple modification is applicable to cellular, PCS systems, IMT-2000 systems, and CDMA technologies that are currently commercially available.

Claims (22)

An interference noise control apparatus applied to a code division multiple access system, Frequency downconverting means for converting the received radiofrequency (RF) analog signal into an intermediate frequency (IF) analog signal; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting to an intermediate frequency (IF) analog signal Digital adaptive signal processing means for; And Frequency up-converting means for converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal Narrowband interference noise control device comprising a. The method of claim 1, The digital adaptive signal processing means, Analog-to-digital (A / D) conversion means for converting the intermediate frequency (IF) analog signal into a digital signal; Digital downconversion means (DDC) for converting the converted digital signal into a baseband signal; Digital adaptive interference noise control means for removing narrowband interference noise signal components from the converted baseband signal using autoregressive and least squares average (LMS) algorithms and controlling the final output within a predetermined reference range ; Digital upconverting means (DUC) for converting the digital signal from which the narrowband interference noise is removed into a digital upconverting frequency band signal; And Digital-to-analog (D / A) converting means for converting the converted digital upconverted frequency band signal into an intermediate frequency (IF) analog signal Narrowband interference noise control device comprising a. The method of claim 2, The digital adaptive interference noise control means, First comparing and analyzing means for generating a control signal by obtaining an average value of the digital output signal of the digital down-converting means and comparing the predetermined reference values with respect to the output of the digital-to-analog (D / A) converting means; Interference noise control means for controlling narrowband interference noise signal components from the transformed baseband signal using an autoregressive and least squares average (LMS) algorithm; And Second comparative analysis means for adjusting the output of the interference noise removing means according to the control signal of the first comparative analysis means Narrowband interference noise control device comprising a. The method of claim 3, wherein The first comparative analysis means, An absolute value and an average value calculating means for obtaining an absolute value of the digital output signal of the digital downconverting means, setting a predetermined window to obtain a peak value among sampling values, and calculating an average of the peak values obtained in each window; And After sensing the output of the absolute value and the average value calculating means, comparing the predetermined reference values with respect to the output of the digital-to-analog (D / A) converting means, the output of the detected absolute value and average value calculating means A signal sensing and control signal generating means for transmitting to the interference noise control means and generating and transmitting the control signal to the second comparison analysis means according to the comparison result. Narrowband interference noise control device comprising a. The method according to claim 3 or 4, The interference noise control means, First combining means for obtaining an error signal between an output signal of the first comparison analysis means and an estimated output value of the adaptive interference cancellation filtering means; Second combining means for combining the estimated value of the error signal of the first combining means with the estimated output value of the adaptive interference cancellation filtering means to generate an input value of the adaptive interference cancellation filtering means; Adaptive weighting coefficient generating means for generating an adaptive weighting coefficient function by square-averaging the estimated value of the error signal of the first combining means; And The adaptive interference elimination filtering means for eliminating interference noise by combining the generated adaptive weighting factor after delaying the output of the second combining means Narrowband interference noise control device comprising a. An interference noise control apparatus applied to a code division multiple access system, Frequency downconverting means for converting the received radiofrequency (RF) analog signal into an intermediate frequency (IF) analog signal; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise by using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) Digital adaptive signal processing means for converting into an analog signal; And Frequency up-converting means for converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal Narrowband interference noise control device using adaptive compensation comprising a. The method of claim 6, The digital adaptive signal processing means, Analog-to-digital (A / D) conversion means for converting the intermediate frequency (IF) analog signal into a digital signal; Digital downconversion means (DDC) for converting the converted digital signal into a baseband signal; Digital to remove narrowband interference noise signal components from the transformed baseband signal using autoregressive, least squares average (LMS) algorithms, and adaptive compensation algorithms, and to control the final output within a predetermined reference range. Adaptive interference noise control means; Digital upconverting means (DUC) for converting the digital signal from which the narrowband interference noise is removed into a digital upconverting frequency band signal; And Digital-to-analog (D / A) converting means for converting the converted digital upconverted frequency band signal into an intermediate frequency (IF) analog signal Narrowband interference noise control device using adaptive compensation comprising a. The method of claim 7, wherein The digital adaptive interference noise control means, First comparing and analyzing means for generating a control signal by obtaining an average value of the digital output signal of the digital down-converting means and comparing the predetermined reference values with respect to the output of the digital-to-analog (D / A) converting means; Interference noise control means for controlling narrowband interference noise signal components from the transformed baseband signal using an autoregressive, least square average (LMS) algorithm, and an adaptive compensation algorithm; And Second comparative analysis means for adjusting the output of the interference noise control means in accordance with a control signal of the first comparative analysis means Narrowband interference noise control device using adaptive compensation comprising a. The method of claim 8, The first comparative analysis means, An absolute value and an average value calculating means for obtaining an absolute value of the digital output signal of the digital downconverting means, setting a predetermined window to obtain a peak value among sampling values, and calculating an average of the peak values obtained in each window; And After sensing the output of the absolute value and the average value calculating means, comparing the predetermined reference values with respect to the output of the digital-to-analog (D / A) converting means, the output of the detected absolute value and average value calculating means Signal detection and control signal generating means for transmitting to the interference noise control means and for generating the control signal according to the comparison result and transmitting it to the second comparison analysis means Narrowband interference noise control device using adaptive compensation comprising a. The method according to claim 8 or 9, The interference noise control means, First combining means for obtaining an error signal between an output signal of the first comparison analysis means and an estimated output value of the adaptive interference cancellation filtering means; The output value of the adaptive compensation means is fed back to obtain an error output with the output of the first coupling means, and then time-delayed. The adaptive compensation means for removing the; Second combining means for feeding back an estimated output value of the adaptive interference cancellation filtering means and combining it with an estimated value of an error signal of the first combining means to generate an input value of the adaptive interference cancellation filtering means; The adaptive weighting coefficient generating means for generating a first adaptive weighting coefficient function for the adaptive compensation means and a second adaptive weighting coefficient function for the adaptive interference cancellation filtering means by square-averaging the output value of the adaptive compensation means; ; And The adaptive interference elimination filtering means for eliminating interference noise in combination with the generated adaptive weighting factor function after delaying the output of the second combining means Narrowband interference noise control device using adaptive compensation comprising a. An interference noise control method applied to a narrowband interference noise control apparatus in a code division multiple access system, Converting the received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting the converted intermediate frequency (IF) analog signal to an intermediate frequency (IF) analog signal. Second step; And A third step of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal Narrowband interference noise control method comprising a. The method of claim 11, The second step, A fourth step of converting the intermediate frequency (IF) analog signal into a digital signal; A fifth step of converting the converted digital signal into a baseband signal; A sixth step of removing narrowband interference noise signal components from the transformed baseband signal using an autoregressive and least squares average (LMS) algorithm and controlling a final output within a predetermined reference range; A seventh step of converting the digital signal from which the narrowband interference noise has been removed in the sixth step into a digital upconverted frequency band signal; And An eighth step of converting the converted digital up-converted frequency band signal into an intermediate frequency (IF) analog signal; Narrowband interference noise control method comprising a. The method of claim 12, The sixth step, A ninth step of obtaining an average value for the baseband digital signal of the fifth step and generating a control signal by comparing the predetermined reference values with respect to a final output; A tenth step of controlling narrowband interference noise signal components from the converted baseband digital signal using an autoregressive and least squares average (LMS) algorithm; An eleventh step of adjusting the output of the tenth step according to the control signal of the ninth step Narrowband interference noise control method comprising a. The method of claim 13, The ninth step, A twelfth step of obtaining an absolute value of the baseband digital signal, setting a predetermined window to obtain a peak value among sampling values, and obtaining an average of peak values obtained from each window; And A thirteenth step of sensing the output of the twelfth step and generating the control signal according to a comparison result with predetermined reference values for the final output stored Narrowband interference noise control method comprising a. The method according to claim 13 or 14, The tenth step is An adaptive weighting coefficient function is generated by averaging the error signal between the output signal of the ninth step and the estimated value of the final output, and combining the time-delayed error signal with the estimated value of the final output to time delay the adaptive weighting coefficient function. Narrow band interference noise control method characterized in that by repeatedly performing the process of multiplying to remove / suppress the narrow band interference noise. An interference noise control method applied to a narrowband interference noise control apparatus in a code division multiple access system, Converting the received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise by using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) Converting to an analog signal; And A third step of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal Narrowband interference noise control method using adaptive compensation comprising a. The method of claim 16, The second step, A fourth step of converting the intermediate frequency (IF) analog signal into a digital signal; A fifth step of converting the converted digital signal into a baseband signal; A sixth step of removing narrowband interference noise signal components from the transformed baseband signal using autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, and controlling the final output within a predetermined reference range; step; A seventh step of converting the digital signal from which the narrowband interference noise has been removed in the sixth step into a digital upconverted frequency band signal; And An eighth step of converting the converted digital up-converted frequency band signal into an intermediate frequency (IF) analog signal; Narrowband interference noise control method using adaptive compensation comprising a. The method of claim 17, The sixth step, A ninth step of obtaining an average value for the baseband digital signal of the fifth step and generating a control signal by comparing the predetermined reference values with respect to a final output; A tenth step of optimally controlling narrowband interference noise signal components from the converted baseband digital signal using an autoregressive, least square average (LMS) algorithm, and an adaptive compensation algorithm; And An eleventh step of adjusting the output of the tenth step according to the control signal of the ninth step Narrowband interference noise control method using adaptive compensation comprising a. The method of claim 18, The ninth step, A twelfth step of obtaining an absolute value of the baseband digital signal, setting a predetermined window to obtain a peak value among sampling values, and obtaining an average of peak values obtained from each window; And A thirteenth step of sensing the average value output of the twelfth step and generating the control signal according to a comparison result with predetermined reference values for the final output stored Narrowband interference noise control method using adaptive compensation comprising a. The method of claim 18 or 19, The tenth step is A fourteenth step of obtaining an error signal between the average value output of the twelfth step and the estimated output value of the adaptive interference cancellation filtering means; A fifteenth step of generating a first adaptive weighting coefficient function for the adaptive compensation means and a second adaptive weighting coefficient function for the adaptive interference cancellation filtering means by square-averaging the output value of the adaptive compensation means; A sixteenth step of feeding back the estimated output value of the adaptive interference elimination filtering means to obtain a combined signal with the estimated value of the error signal of the fourteenth step and then delaying the combined signal with the second adaptive weighting coefficient function to remove the interference noise ; And A seventeenth step of feeding back the output value of the adaptive compensation means to obtain an error signal from the error signal of the fourteenth step and delaying it, and then combining the first adaptive weighting coefficient function to compensate for interference noise Narrowband interference noise control method using adaptive compensation comprising a. In a narrowband interference noise control device having a processor for controlling narrowband interference noise in a code division multiple access system, A first function of converting the received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; Converting the converted intermediate frequency (IF) analog signal to a digital baseband signal to remove interference noise using an autoregressive and least squares average (LMS) algorithm, and then converting the converted intermediate frequency (IF) analog signal to an intermediate frequency (IF) analog signal. Second function; And A third function of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal A computer-readable recording medium having recorded thereon a program for realizing this. In a narrowband interference noise control device having a processor for narrowband interference noise control using adaptive compensation in a code division multiple access system, A first function of converting the received radio frequency (RF) analog signal into an intermediate frequency (IF) analog signal; After converting the converted intermediate frequency (IF) analog signal into a digital baseband signal to remove the interference noise by using an autoregressive, least square average (LMS) algorithm, and adaptive compensation algorithm, the intermediate frequency (IF) A second function of converting to an analog signal; And A third function of converting the converted intermediate frequency (IF) analog signal into a radio frequency (RF) analog signal A computer-readable recording medium having recorded thereon a program for realizing this.