KR102456368B1 - Data processing, precoding method and communication device - Google Patents

Abstract

The encoder outputs an N-bit first bit string. The mapping unit uses the number of bits (X + Y) bit string obtained from the first number of bits X for generating the first complex signal s1 and the second number of bits Y for generating the second complex signal s2 among the input second bit strings. A first complex signal S1 and a second complex signal S2 are generated. By including a bit length adjusting unit that adjusts and outputs the first bit string so that the length of the second bit string becomes a multiple of the value of X+Y at the rear end of the encoding unit, the codeword length of the block code and the new modulation method set are necessary for mapping Adjust the number of bits.

Description

Data processing method, precoding method, communication device {DATA PROCESSING, PRECODING METHOD AND COMMUNICATION DEVICE}

(Reference to related applications) Japanese Patent Application No. 2013-003905 filed on January 11, 2013, Japanese Patent Application No. 2013-033353 filed on February 22, 2013 and September 20, 2013 All the disclosure contents of the claims, specifications, drawings, and abstracts included in the filed Japanese Patent Application No. 2013-195166 are incorporated herein by reference.

The present invention relates to a data processing method, a precoding method and a communication device.

Conventionally, as a communication method using a multi-antenna, for example, there is a communication method called MIMO (Multiple-Input Multiple-Output).

In multi-antenna communication typified by MIMO, one or more series of transmission data is modulated and each modulated signal is simultaneously transmitted from different antennas using the same frequency (common frequency) to improve data reception quality and/or (per unit time). )) You can increase the data communication speed.

72 is a diagram for explaining an outline of a spatial multiplexing MIMO scheme. The MIMO method in the figure shows an example of the configuration of a transceiver device when the number of transmit antennas is 2 (TX1, TX2), the number of receive antennas is 2 (RX1, RX2), and the number of transmit modulated signals (transmission streams) is 2.

The transmitting apparatus has a signal generating unit and a radio processing unit.

The signal generator encodes data into a communication path, executes MIMO precoding processing, and generates two transmission signals z1(t) and z2(t) that can be simultaneously transmitted using the same frequency (common frequency). The radio processing unit multiplexes individual transmission signals in the frequency direction as needed, that is, multi-carrier (for example, OFDM method), and the receiving device estimates transmission path distortion, frequency offset, phase distortion, etc. (However, the pilot signal may estimate other distortion, etc., and the pilot signal may be used by the receiving device for signal detection. Also, the usage form of the pilot signal in the receiving device is as follows: but not limited to this). The transmit antenna transmits z1(t) and z2(t) using two antennas TX1 and TX2.

The reception apparatus includes reception antennas RX1 and RX2, a radio processing unit, a channel change estimation unit, and a signal processing unit. The receiving antenna RX1 receives signals transmitted from the two transmitting antennas TX1 and TX2 of the transmitting device. The channel variation estimator estimates the channel variation using the pilot signal, and supplies the estimated channel variation to the signal processing unit. The signal processing unit recovers data included in z1(t) and z2(t) based on the signals received from the two reception antennas and the estimated channel values, and obtains this as one reception data. However, the received data may be a hard decision value of "0" or "1", or a soft decision value such as log likelihood or log likelihood ratio.

In addition, various coding methods such as turbo coding and LDPC (Low-Density Parity-Check) coding are used as coding methods (Non-Patent Document 1 and Non-Patent Document 2).

R. G. Gallager, “Low-densityparity-check codes,” IRE Trans. Inform. Theory, IT-8, pp-21-28, 1962. “Performance analysis and design optimization of LDPC-coded MIMO OFDM systems” IEEE Trans. Signal Processing. , vol. 52, no. 2, pp. 348-361, Feb. 2004. C. Douillard, and C. Berrou, “Turbo codes with rate-m/(m+1) constituent convolutional codes,” IEEE Trans. Commun., vol. 53, no. 10, pp. 1630-1638, Oct. 2005. C. Berrou, “The ten-year-old turbo codes are entering into service,” IEEE Communication Magazine, vol. 41, no. 8, pp. 110-116, Aug. 2003. DVB Document A122, Framing structure, channel coding and modulation for a second generation digital terrestrial television broadcasting system, m (DVB-T2), June 2008. D. J. C. Mackay, “Good error-correcting codes based on very sparse matrices,” IEEE Trans. Inform. Theory, vol. 45, no. 2, pp399-431, March 1999. S.M.Alamouti, “A simple transmit diversity technique for wireless communications,” IEEE J. Select. Areas Commun., vol. 16, no. 8, pp. 1451-1458, Oct 1998. V. Tarokh, H. Jafrkhani, and A.R. Calderbank, “Space-time block coding for wireless communications: Performance results,” IEEE J. Select. Areas Commun., vol. 17, no. 3, no. 3, pp. 451-460, March 1999.

SUMMARY OF THE INVENTION An object of the present invention is to solve a problem in implementation in a state in which an encoding method such as an LDPC code is applied when a MIMO method is used, and more specifically, to provide a transmission/reception method and apparatus for data communication.

The data processing method according to the present invention comprises an encoding step of outputting a first bit string 503 that is an N-bit codeword from a K-bit information bit string, and generating a first complex signal s1 from an input second bit string. A mapping step of generating a first complex signal s1 and a second complex signal s2 using a bit number (X+Y) bit string obtained from the first number of bits X and a second number of bits Y for generating a second complex signal s2; and a bit length adjustment step of adjusting and outputting the first bit string so that the length of the second bit string is a multiple of the number of bits (X+Y) after the encoding step and before the mapping step.

In processing data, the preferred transmission method for data communication of the present invention encodes first information using a first encoding rate and a first code length to generate a first encoded data sequence, and includes the first encoding rate and The second information is encoded using a second code length different from the first code length to generate a second encoded data sequence, and the first information is generated at 16 signal points determined by the first 16 QAM (Quadrature Amplitude Modulation) method. A first modulated symbol sequence is generated by mapping the coded data sequence, the second coded data sequence is mapped to 16 signal points determined by a second 16QAM scheme to generate a second modulated symbol sequence, and a transmitter and a receiver A pilot symbol group, which is a known symbol group, is generated between and, and a first OFDM (Orthogonal Frequency Division Multiplexing) symbol is generated based on the first modulation symbol sequence and the pilot symbol group. , generates a second OFDM symbol based on the second modulation symbol sequence and the pilot symbol group, and transmits a signal generated based on the first OFDM symbol and the second OFDM symbol, in the first 16QAM scheme The 16 signal points determined by the second 16QAM method and the 16 signal points determined by the second 16QAM method have non-uniform distances between adjacent signal points in the I/Q plane having real and imaginary axes. , The 16 signal points determined by the first 16QAM scheme have a first arrangement pattern in the I/Q plane, and the 16 signal points determined by the second 16QAM scheme have the first arrangement pattern in the I/Q plane. It has a 2nd arrangement|positioning pattern different from the 1st arrangement|positioning pattern.

In processing data, the preferred reception method for data communication of the present invention receives a signal including a first OFDM symbol and a second OFDM symbol, and the first OFDM symbol and the second OFDM symbol. A pilot symbol group is extracted from the symbol, a first modulated symbol sequence is extracted from the first OFDM symbol, and a second modulated symbol sequence is extracted from the second OFDM symbol, and the pilot symbol group is transmitted between a transmitter and a receiver. It is a known symbol group, and demodulates the first modulation symbol sequence mapped to 16 signal points determined by the first 16 QAM (Quadrature Amplitude Modulation) method based on the pilot symbol group to demodulate the first encoded data sequence. generates a second coded data sequence by demodulating the second modulation symbol sequence mapped to 16 signal points determined by a second 16QAM scheme based on the pilot symbol group to generate a second coded data sequence, a first coding rate and a first The first encoded data series is decoded using the code length to generate first information, and the second encoded data series is decoded using the first encoding rate and a second code length different from the first code length. to generate second information, and the 16 signal points determined by the first 16QAM method and the 16 signal points determined by the second 16QAM method are between adjacent signal points in an I/Q plane having a real axis and an imaginary axis. is non-uniform, the 16 signal points determined by the first 16QAM method have a first arrangement pattern in the I/Q plane, and the 16 signal points determined by the second 16QAM method are the I/Q points. It has a 2nd arrangement|positioning pattern different from the said 1st arrangement|positioning pattern in a Q plane.

In processing data, a preferred data communication receiving apparatus of the present invention includes a receiving circuit for receiving a signal including a first OFDM symbol and a second OFDM symbol, the first OFDM symbol and the A pilot symbol group is extracted from a second OFDM symbol, a first modulated symbol sequence is extracted from the first OFDM symbol, and a second modulated symbol sequence is extracted from the second OFDM symbol, and the pilot symbol group includes a transmitter and a receiver. The first modulation symbol sequence mapped to 16 signal points determined by the first 16QAM (Quadrature Amplitude Modulation) method based on the OFDM symbol processing circuit and the pilot symbol group a demapping circuit that demodulates a first coded data sequence and demodulates the second modulated symbol sequence mapped to 16 signal points determined by a second 16QAM scheme to generate a second coded data sequence; and decoding the first encoded data sequence using a first code length to generate first information, and using a second code length different from the first encoding rate and the first code length to generate the second encoded data and a decoding circuit for decoding a sequence to generate second information, wherein 16 signal points determined by the first 16QAM method and 16 signal points determined by the second 16QAM method are I/Q having real and imaginary axes The distance between adjacent signal points in a plane is non-uniform, and the 16 signal points determined by the first 16QAM scheme have a first arrangement pattern in the I/Q plane, and are determined by the second 16QAM scheme. The 16 signal points have a second arrangement pattern different from the first arrangement pattern in the I/Q plane.

According to the data processing method according to the present invention, when the MIMO method is used, it is possible to contribute to the problem of implementation in a state in which an encoding method such as an LDPC code is applied.

1 is an example of the arrangement of the signal points of QPSK in the IQ plane;
2 is an example of a signal point arrangement of 16QAM in the IQ plane;
3 is an example of a signal point arrangement of 64QAM in the IQ plane;
4 is an example of 256QAM signal point arrangement in the IQ plane;
5 is an example of the configuration of the transmitter;
6 is an example of the configuration of the transmitter;
7 is an example of the configuration of the transmitter;
8 is an example of the configuration of a signal processing unit;
9 is an example of a frame configuration;
10 is an example of a signal point arrangement of 16QAM in the IQ plane;
11 is an example of a signal point arrangement of 64QAM in the IQ plane;
12 is an example of signal point arrangement in the IQ plane;
13 is an example of signal point arrangement in the IQ plane;
14 is an example of signal point arrangement in the IQ plane;
15 is an example of signal point arrangement in the IQ plane;
16 is an example of signal point arrangement in the IQ plane;
17 is an example of signal point arrangement in the IQ plane;
18 is an example of signal point arrangement in the IQ plane;
19 is an example of signal point arrangement in the IQ plane;
20 is an example of signal point arrangement in the IQ plane;
21 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
22 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
23 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
24 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
25 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
26 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
27 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
28 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
29 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
30 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
31 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
32 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
33 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
34 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
35 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
36 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
37 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
38 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
39 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
40 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
41 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
42 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
43 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
44 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
45 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
46 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
47 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
48 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
49 is an example of the arrangement of signal points in the first upper limit of the IQ plane;
50 is an example of the arrangement of signal points in the second upper limit of the IQ plane;
51 is an example of the arrangement of signal points in the third upper limit of the IQ plane;
52 is an example of the arrangement of signal points in the fourth upper limit of the IQ plane;
53 is a diagram showing a relationship between a transmitting antenna and a receiving antenna;
54 is an example of the configuration of the receiving device;
55 is an example of signal point arrangement in the IQ plane;
56 is an example of signal point arrangement in the IQ plane;
Fig. 57 is a block diagram of a part for generating a modulated signal of the transmitting apparatus according to the first embodiment;
58 is a flowchart of a method for generating a modulated signal;
59 is a flowchart of bit length adjustment processing according to the first embodiment;
60 is a configuration of a modulation unit according to the second embodiment;
61 is an example of a parity check matrix;
62 is a configuration example of a sub-matrix;
63 is a flowchart of the LDPC encoding process executed by the encoding unit 502LA;
Fig. 64 is a diagram of an example of a configuration for realizing the accumulate processing;
Fig. 65 is a flowchart of bit length adjustment processing according to the second embodiment;
66 is an example of a method of generating a bit string for adjustment;
67 is an example of a method of generating a bit string for adjustment;
68 is an example of a method of generating a bit string for adjustment;
69 is a modified example of the adjustment bit string generated by the bit length adjustment unit;
70 is a modified example of the adjustment bit string generated by the bit length adjustment unit;
71 is a view for explaining one of the ideas of the invention according to the second embodiment;
72 is a schematic diagram of a MIMO system;
73 is a block diagram of a modulation unit according to the third embodiment;
74 is a diagram for explaining the operation of the bit interleaver 502BI in the output bit string;
75 is an example of mounting the bit interleaver 502;
76 is an example of bit length adjustment processing;
77 is a diagram showing an example of a bit string to be added;
78 is an example of insertion of a bit string adjustment unit;
79 is a modified example of the configuration of the modulator;
80 is a block diagram of a modulation unit according to the fourth embodiment;
81 is a flowchart showing processing;
82 is a diagram showing the relationship between the length of K bits of BBFRAME and the length of the secured TmpPadNum;
83 is a configuration diagram of a modulation unit different from that of FIG. 80;
84 is a view for explaining the bit length of bit strings 501 to 8003;
85 is an example of a bit string decoding unit of the receiving device;
86 is a diagram for explaining input and output of the bit string adjustment unit;
87 is an example of a bit string decoding unit of the receiving device;
88 is an example of a bit string decoding unit of the receiving device;
89 is a diagram conceptually explaining the processing of the sixth embodiment;
90 is a diagram showing a relationship between a transmitter and a receiver;
91 is an example of the configuration of a modulator on the transmission side;
92 is a diagram showing the bit length of each bit string;
93 is a block diagram of a modulator on the transmitting side different from that of FIG. 91;
94 is a diagram showing the bit length of each bit string;
95 is a diagram showing the bit length of each bit string;
96 is an example of a bit string decoding unit of the receiving device;
97 is a diagram of a part for executing precoding-related processing;
Fig. 98 is a diagram of a part for executing precoding-related processing;
99 is an example of the configuration of the signal processing unit;
100 is an example of a frame configuration in time-frequency in the case of transmitting two streams;
101 (A) is a diagram showing a state of an output first bit string 503, (B) a diagram showing a state of an outputting second bit string 5703;
102 is (A) a diagram showing a state of an outputted first bit string 503, (B) a diagram showing a state of an outputting second bit string 5703;
Fig. 103 is (A) a diagram showing the state of the outputted first bit string 503Λ, (B) is a diagram showing the state of the output bit string 7303 after adjusting the bit length;
104 (A) is a view showing the state of the output first bit stream 503' (or 503Λ), (B) is a view showing the state of the output bit stream 8003 after adjusting the bit length;
105 (A) is a diagram showing the state of the output N-bit codeword 503, (B) is a diagram showing the state of the output N-PunNum-bit data string 9102;
106 is an overview of the frame configuration;
107 is an example in which two or more types of signals exist at the same time;
108 is an example of the configuration of the transmitter;
109 is an example of a frame configuration;
110 is an example of the configuration of the receiving device;
111 is an example of signal point arrangement of 16QAM in the IQ plane;
112 is an example of the signal point arrangement of 64QAM in the IQ plane;
113 is an example of 256QAM signal point arrangement in the IQ plane;
114 is an example of signal point arrangement of 16QAM in the IQ plane;
115 is an example of a signal point arrangement of 64QAM in the IQ plane;
116 is an example of 256QAM signal point arrangement in the IQ plane;
117 is an example of the configuration of the transmitter;
118 is an example of the configuration of the receiving device;
119 is an example of signal point arrangement of 16QAM in the IQ plane;
120 is an example of a signal point arrangement of 64QAM in the IQ plane;
121 is an example of 256QAM signal point arrangement in the IQ plane;
122 is an example of the configuration of the transmitter;
123 is an example of a frame configuration;
124 is an example of the configuration of the receiving device;
125 is an example of the configuration of the transmitter;
126 is an example of a frame configuration;
127 is an example of the configuration of a receiving device;
128 is a view for explaining a transmission method using space-time block codes (Space-Time Block Codes);
129 is an example of the configuration of the transmitter;
130 is an example of the configuration of the transmitter;
131 is an example of the configuration of the transmitter;
132 is an example of the configuration of the transmitter;
133 is a view for explaining a transmission method using space-time block codes.

Hereinafter, prior to the description of each embodiment of the present invention, an example of a configuration of a transmission method and a reception method to which the invention described in each of the following embodiments can be applied and a transmission apparatus and a reception apparatus using the same will be described.

(Configuration Example R1)

Fig. 5 shows an example of the configuration of a portion for generating a modulated signal when a transmission method can be switched in a transmitting apparatus of a base station (broadcasting station, access point, etc.).

In this configuration example, it is assumed that there is a transmission method in which two streams are transmitted (Multiple Input Multiple Output (MIMO) method) as one of the switchable transmission methods.

A transmission method in the case where a transmission apparatus of a base station (broadcasting station, access point, etc.) transmits two streams will be described with reference to FIG. 5 .

The encoding unit 502 of FIG. 5 receives the information 501 and the control signal 512 as inputs, and performs encoding based on the information on the encoding rate and the code length (block length) included in the control signal 512. The encoded data 503 is output.

The mapping unit 504 receives the encoded data 503 and the control signal 512 as inputs. And, it is assumed that the control signal 512 specifies that two streams are transmitted as a transmission method. In addition, it is assumed that the control signal 512 designates the modulation method α and the modulation method β as the respective modulation methods of the two streams. In addition, modulation method α is a modulation method that modulates x-bit data, and modulation method β is a modulation method that modulates y-bit data (for example, in the case of 16 QAM (16 Quadrature Amplitude Modulation), 4-bit data is modulated. This is a modulation method that modulates 6-bit data in the case of 64QAM (64 Quadrature amplitude modulation).

Then, the mapping unit 504 modulates the x-bit data of the x+y-bit data by the modulation method α to generate and output the baseband signal s ₁ (t) 505A, and also converts the remaining y-bit data The data is modulated by the modulation method β and _a baseband signal s ₂ (t) 505B is output. A mapping unit for generating s 2 (t) and s ₂ (t) may exist separately, in this case, the encoded data 503 is a mapping unit for generating s ₁ (t) and a mapping unit for generating s ₂ (t). to be distinguished).

Further, s ₁ (t) and s ₂ (t) are expressed by complex numbers (however, either a complex number or a real number may be used). Also, t is time. In addition, when a transmission method using a multi-carrier such as OFDM (Orthogonal Frequency Division Multiplexing) is used, s ₁ and s ₂ are functions of frequency f as in s ₁ (f) and s ₂ (f), or s It can also be thought of as a function of time t, frequency f, such as ₁ (t, f) and s ₂ (t, f).

Hereinafter, the baseband signal, the precoding matrix, the phase change, etc. are described as a function of time t, but it may be considered as a function of frequency f, time t and frequency f.

Therefore, there are cases where the baseband signal, the precoding matrix, and the phase change are explained as a function of the symbol number i, but in this case, it is considered as a function of time t, a function of frequency f, and a function of time t and frequency f good to do

That is, the symbol and the baseband signal may be generated and disposed in the time axis direction or may be generated and disposed in the frequency axis direction. Further, the symbol and the baseband signal may be generated and arranged in the direction of the time axis and the direction of the frequency axis.

The power change unit 506A (power adjuster 506A) receives the baseband signal s ₁ (t) 505A and the control signal 512 as inputs, and sets a real number P ₁ based on the control signal 512, P ₁ x s ₁ (t) is output as the signal 507A after power change (note that P ₁ is a real number, but may be a complex number).

Similarly, the power change unit 506B (power adjuster 506B) receives the baseband signal s ₂ (t) 505B and the control signal 512 as inputs to set a real number P ₂ , and P ₂ ×s ₂ (t) is output as the signal 507B after power change (note that P ₂ is a real number, but may be a complex number).

The weighted synthesis unit 508 receives the signal after power change 507A, the signal after power change 507B, and the control signal 512 as inputs, and based on the control signal 512, the precoding matrix F (or F(i) )) is set. When the slot number (symbol number) is i, the weighted synthesis unit 508 performs the following operation.

Here, a(i), b(i), c(i), and d(i) can be expressed as complex numbers (which may be real numbers), and a(i), b(i), c(i), d( 3 or more of i) must not be 0 (zero). Further, the precoding matrix may be a function of i or may not be a function of i. And when the precoding matrix is a function of i, the precoding matrix is changed by the slot number (symbol number).

Then, the weighted synthesis unit 508 outputs u1(i) in the formula (R1) as the signal 509A after weight synthesis, and outputs u2(i) in the equation (R1) as the signal 509B after weight synthesis. do.

The power change unit 510A receives the weighted synthesis signal 509A (u ₁ (i)) and the control signal 512 as inputs, and sets a real number Q ₁ based on the control signal 512, Q ₁ × u ₁ (t) is output as the signal 511A (z ₁ (i)) after power change (although Q ₁ is a real number, it may be a complex number).

Similarly, the power change unit 510B receives the weighted synthesis signal 509B (u ₂ (i)) and the control signal 512 as inputs, and sets a real number Q ₂ based on the control signal 512, Q ₂ xu ₂ (t) is output as the signal 511A (z ₂ (i)) after power change (note that Q ₂ is a real number, but may be a complex number).

Therefore, the following expression holds.

Next, a transmission method in the case of transmitting two streams different from that of FIG. 5 will be described with reference to FIG. Incidentally, in Fig. 6, the same reference numerals are assigned to those operating in the same manner as in Fig. 5 .

The phase change unit 501 receives the signal 509B and the control signal 512 after weight synthesis of u ₂ (i) in the equation (R1), and based on the control signal 512, Change the phase of the signal 509B after weighting u ₂ (i). Therefore, the signal after changing the phase of the signal 509B after weighting u ₂ (i) in the formula (R1) is expressed as ejθ(i)×u ₂ (i), and ejθ(i)×u ₂ (i) is a signal 602 after the phase change, which is output by the phase change unit 601 (j is an imaginary number unit). In addition, a characteristic part is that the value of the phase to be changed is a function of i as in θ(i).

In addition, the power changing units 510A and 510B of FIG. 6 change the power of the input signal, respectively. Accordingly, the respective outputs z ₁ (i) and z ₂ (i) of the power changing units 510A and 510B in FIG. 6 are expressed as follows.

In addition, as a method of realizing the formula (R3), there is a configuration in FIG. 7 different from that in FIG. 6 . The difference between FIG. 6 and FIG. 7 is that the order of the power change unit and the phase change unit is reversed (the function itself of executing power change and phase change does not change). In this case, z ₁ (i) and z ₂ (i) are expressed as follows.

In addition, z 1 (i) of formula (R3) and z ₁ (i) of formula (R4) are the same, _and z ₂ (i) of formula (R3) and z ₂ (i) of formula (R4) is also the same

The changing phase value θ(i) in equations (R3) and (R4) is, for example, set so that θ(i+1)-θ(i) is a fixed value, in the propagation environment of radio waves dominated by direct waves. Therefore, there is a high possibility that the receiving device can obtain good data reception quality. However, the method of applying the value θ(i) of the phase to be changed is not limited to this example.

FIG. 8 shows an example of the configuration of a signal processing unit that is executed for the signals z ₁ (i) and z ₂ (i) obtained in FIGS. 5 to 7 .

The inserting unit 804A receives the signal z ₁ (i) 801A, the pilot symbol 802A, the control information symbol 803A, and the control signal 512 as inputs, so as to construct a frame included in the control signal 512. Accordingly, the pilot symbol 802A and the control information symbol 803A are inserted into the signal (symbol) z ₁ (i) 801A to output the modulated signal 805A according to the frame configuration.

In addition, the pilot symbol 802A and the control information symbol 803A are symbols modulated by BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), or the like (other modulation schemes may be used).

The radio unit 806A receives the modulated signal 805A and the control signal 512 as inputs, and based on the control signal 512, performs frequency conversion, amplification, etc. processing on the modulated signal 805A (OFDM). When the method is used, processing such as an inverse Fourier transform is performed) and a transmission signal 807A is output, and the transmission signal 807A is output as a radio wave from the antenna 808A.

The inserting unit 804B receives the signal z ₂ (i) 801B, the pilot symbol 802B, the control information symbol 803B, and the control signal 512 as inputs, so as to construct a frame included in the control signal 512. Accordingly, a pilot symbol 802B and a control information symbol 803B are inserted into the signal (symbol) z ₂ (i) 801B to output a modulated signal 805B according to the frame configuration.

In addition, the pilot symbol 802B and the control information symbol 803B are symbols modulated by BPSK (Binary Phase Shift Keying) or QPSK (Quadrature Phase Shift Keying) or the like (other modulation schemes may be used).

The radio unit 806B receives the modulated signal 805B and the control signal 512 as inputs, and based on the control signal 512, performs processing such as frequency conversion and amplification on the modulated signal 805B (OFDM method). is used, processing such as an inverse Fourier transform is performed) A transmission signal 807B is output, and the transmission signal 807B is output as a radio wave from the antenna 808B.

Here, in the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B), the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B) of which i is the same number are the same ( A common) frequency is transmitted from different antennas at the same time (that is, a transmission method using the MIMO method).

In addition, the pilot symbol 802A and the pilot symbol 802B are symbols for performing signal detection, frequency offset estimation, gain control, channel estimation, etc. in the receiving apparatus, and are called pilot symbols here, but reference symbols It is also possible to use other names such as

In addition, the control information symbol 803A and the control information symbol 803B include information on the modulation method used by the transmitter, information on the transmission method, information on the precoding method, information on the error correction coding method, information on the coding rate of the error correction code, It is a symbol for transmitting information on the block length (code length) of the error correction code to the receiving device. Alternatively, the control information symbol may be transmitted using only one of the control information symbol 803A and the control information symbol 803B.

9 shows an example of a frame configuration in time-frequency in the case of transmitting two streams. In FIG. 9 , the horizontal axis represents frequency and the vertical axis represents time. For example, the configuration of a symbol from carrier 1 to carrier 38 and from time $1 to time $11 is shown.

9 shows the frame structure of the transmission signal transmitted from the antenna 806A in FIG. 8 and the frame of the transmission signal transmitted from the antenna 808B at the same time.

In Fig. 9, in the case of a frame of a transmission signal transmitted from the antenna 806A in Fig. 8, a data symbol corresponds to a signal (symbol) z ₁ (i). And the pilot symbol corresponds to the pilot symbol 802A.

In Fig. 9, in the case of a frame of a transmission signal transmitted from the antenna 806B in Fig. 8, the data symbol corresponds to the signal (symbol) z ₂ (i). And the pilot symbol corresponds to the pilot symbol 802B.

(Therefore, as described above, in the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B), i is the same number of the signal z ₁ (i) (801A) and the signal z ₂ (i) ) 801B transmits the same (common) frequency from different antennas at the same time, the configuration of the pilot symbol is not limited to Fig. 9. For example, the time interval and frequency interval of pilot symbols are It is not limited to Fig. 9. And, in Fig. 9, the pilot symbol is transmitted from the antenna 806A of Fig. 8 and the antenna 806B of Fig. 8 at the same time and on the same frequency (same (sub-carrier)). However, the present invention is not limited thereto, and for example, a pilot symbol is disposed in the antenna 806A of FIG. 8 at time A and frequency a ((sub) carrier a), and at time A, frequency a ((sub) carrier a) In a), it is assumed that no symbols are arranged on the antenna 806B of Fig. 8, and that no symbols are arranged on the antenna 806A of Fig. 8 at time B and frequency b ((sub)carrier b), It is also possible to have a configuration in which pilot symbols are arranged on the antenna 806B of FIG. 8 at time B and frequency b ((sub)carrier b).

In addition, although only data symbols and pilot symbols are described in FIG. 9, other symbols, for example, symbols such as control information symbols, may be included in the frame.

In FIGS. 5 to 7 , a case in which a part (or all) of the power change unit is present has been described as an example, but a case in which a part of the power change unit is absent is also considered.

For example, in Fig. 5, when the power change unit 506A (power adjuster 506A) and the power change unit 506B (power adjuster 506B) do not exist, z ₁ (i) and z ₂ (i) are as follows. is displayed

In Fig. 5, when the power changing unit 510A (the power adjusting unit 510A) and the power changing unit 510B (the power adjusting unit 510B) do not exist, z ₁ (i) and z ₂ (i) are displayed as follows do.

5, a power change unit 506A (power adjustment unit 506A), a power change unit 506B (power adjustment unit 506B), a power change unit 510A (power adjustment unit 510A), a power change unit 510B (power When the adjustment unit 510B does not exist, z ₁ (i) and z ₂ (i) are expressed as follows.

In addition, in FIG. 6 or FIG. 7, when the power changing part 506A (power adjusting part 506A) and the power changing part 506B (power adjusting part 506B) do not exist, z ₁ (i) and z ₂ (i) are the following is displayed as

In addition, in Fig. 6 or Fig. 7, when the power change unit 510A (power adjuster 510A) and the power change unit 510B (power adjuster 510B) do not exist, z ₁ (i) and z ₂ (i) are as follows is displayed as

6 or 7, a power change unit 506A (power adjustment unit 506A), a power change unit 506B (power adjustment unit 506B), a power change unit 510A (power adjustment unit 510A), and a power change unit 510B ) (the power adjusting unit 510B) does not exist, z ₁ (i) and z ₂ (i) are expressed as follows.

Next, a mapping method of QPSK, 16QAM, 64QAM, and 256QAM will be described as an example of a mapping method of a modulation scheme for generating the baseband signal s1(t) 505A and the baseband signal s ₁ (t) 505B. .

A mapping method of QPSK will be described. 1 shows an example of the arrangement of the signal points of QPSK in the in-phase I-orthogonal Q plane. Moreover, in Fig. 1, four ? denote QPSK signal points, the horizontal axis is I, and the vertical axis is Q.

Each of the coordinates in the in-phase I-orthogonal Q plane of the four signal points of QPSK (“○” in Fig. 1 is the signal point) is (w _q , w _q ), (-w _q , w _qq ), (w _q ,-w _q ), (-w _q ,-w _q ) (w _q is a real number greater than zero).

Here, the bits to be transmitted (input bits) are referred to as b0 and b1. For example, if the transmitted bit is (b0, b1) = (0, 0), it is mapped to the signal point 501 in FIG. 1, and if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q (I, Q)=(w _q , w _q ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (during QPSK modulation) are determined based on the transmitted bits b0 and b1. An example of the relationship between the b0B1 set (0 0 to 1 1) and the coordinates of the signal point is as shown in FIG. 1 . Four signal points of QPSK (“○” in Fig. 1) (w _q , w _q ), (-w _q , w _q ), (w _q ,-w _q ), (-w _q ,-w _q ) The values of set 0 0 to 1 1 of b0b1 are shown immediately below. Each coordinate in the in-phase I- orthogonal Q plane of the signal point ("○") immediately above the b0B1 set 0 0 to 1 1 becomes the in-phase component I and the quadrature component Q of the baseband signal after mapping. In addition, the relationship between the b0B1 set (0 0 - 1 1) and the coordinates of a signal point at the time of QPSK is not limited to FIG. Then, a value obtained by complex expression of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of QPSK modulation) becomes the baseband signal s ₁ (t) or s ₂ (t).

A mapping method of 16QAM will be described. Fig. 2 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 2, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 2 is the signal point) in the in-phase I-orthogonal Q plane are (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ) ,-w ₁₆ ), (3w ₁₆ ,-3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), ( -w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ , -3w ₁₆ ) (w ₁₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, when the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 201 in FIG. 2, and the in-phase component of the baseband signal after mapping If I is I and the orthogonal component is Q, then (I, Q)=(3w ₁₆ , 3w ₁₆ ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in FIG. 2) (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ,-w ₁₆ ), (3w ₁₆ , -3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (-w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (- 3w ₁₆ , -3w ₁₆ ), the values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. In addition, the relationship between the set (0000-1111) of b0, b1, b2, b3 and the coordinates of a signal point at the time of 16QAM is not limited to FIG. And the value obtained by complex expression of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in case of 16QAM) becomes the baseband signal s ₁ (t) or s ₂ (t).

The 64QAM mapping method will be described. 3 shows an example of the signal point arrangement of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 3, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

Each coordinate of 64 signal points of 64QAM (“○” in FIG. 3 is a signal point) in the in-phase I-orthogonal Q plane is,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ , -5w ₆₄ ), (7w ₆₄ , -7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-w ₆₄ ), (5w ₆₄ ,-3w ₆₄ ), (5w ₆₄ , -5w ₆₄ ), (5w ₆₄ , -7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3w ₆₄ ), (3w ₆₄ , -5w ₆₄ ), (3w ₆₄ , -7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ , -7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ),(-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 301 in FIG. , if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in Fig. 3) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-w ₆₄ ), (5w ₆₄ ,-3w ₆₄ ), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3w ₆₄ ), (3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), (-7w ₆₄ , -7w ₆₄ ), the sets b0, b1, b2, b3, b4, b5 set values from 000000 to 111111 are shown. . Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 3 . Then, a value obtained by complex expression of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) becomes the baseband signal s ₁ (t) or s ₂ (t).

A mapping method of 256QAM will be described. 4 shows an example of 256QAM signal point arrangement in the in-phase I-orthogonal Q plane. In addition, in Fig. 4, 256 ? are signal points of 256QAM.

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 4 is the signal point) in the in-phase I-orthogonal Q plane are,

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ , -15w ₂₅₆ ), (15w ₂₅₆ , -13w ₂₅₆ ), (15w ₂₅₆ , -11w ₂₅₆ ), (15w ₂₅₆ , -9w ₂₅₆ ), (15w ₂₅₆ , -7w ₂₅₆ ), (15w ₂₅₆ , -5w ₂₅₆ ), (15w ₂₅₆ , -3w ₂₅₆ ), (15w ₂₅₆ , -w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13w ₂₅₆ , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ , -15w ₂₅₆ ), (13w ₂₅₆ , -13w ₂₅₆ ), (13w ₂₅₆ , -11w ₂₅₆ ), (13w ₂₅₆ , -9w ₂₅₆ ), (13w ₂₅₆ , -7w ₂₅₆ ), (13w ₂₅₆ , -5w ₂₅₆ ), (13w ₂₅₆ , -3w ₂₅₆ ), (13w ₂₅₆ , -w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ , -15w ₂₅₆ ), (11w ₂₅₆ , -13w ₂₅₆ ), (11w ₂₅₆ , -11w ₂₅₆ ), (11w ₂₅₆ , -9w ₂₅₆ ), (11w ₂₅₆ , -7w ₂₅₆ ), (11w ₂₅₆ , -5w ₂₅₆ ), (11w ₂₅₆ , -3w ₂₅₆ ), (11w ₂₅₆ , -w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ), (9w ₂₅₆ , -15w ₂₅₆ ), (9w ₂₅₆ , -13w ₂₅₆ ), (9w ₂₅₆ , -11w ₂₅₆ ), (9w ₂₅₆ , -9w ₂₅₆ ), (9w ₂₅₆ , -7w ₂₅₆ ), (9w ₂₅₆ , -5w ₂₅₆ ), (9w ₂₅₆ , -3w ₂₅₆ ), (9w ₂₅₆ , -w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ), (7w ₂₅₆ , -15w ₂₅₆ ), (7w ₂₅₆ , -13w ₂₅₆ ), (7w ₂₅₆ , -11w ₂₅₆ ), (7w ₂₅₆ , -9w ₂₅₆ ), (7w ₂₅₆ , -7w ₂₅₆ ), (7w ₂₅₆ , -5w ₂₅₆ ), (7w ₂₅₆ , -3w ₂₅₆ ), (7w ₂₅₆ , -w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ), (5w ₂₅₆ , -15w ₂₅₆ ), (5w ₂₅₆ , -13w ₂₅₆ ), (5w ₂₅₆ , -11w ₂₅₆ ), (5w ₂₅₆ , -9w ₂₅₆ ), (5w ₂₅₆ , -7w ₂₅₆ ), (5w ₂₅₆ , -5w ₂₅₆ ), (5w ₂₅₆ , -3w ₂₅₆ ), (5w ₂₅₆ , -w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ , -15w ₂₅₆ ), (3w ₂₅₆ , -13w ₂₅₆ ), (3w ₂₅₆ , -11w ₂₅₆ ), (3w ₂₅₆ , -9w ₂₅₆ ), (3w ₂₅₆ , -7w ₂₅₆ ), (3w ₂₅₆ , -5w ₂₅₆ ), (3w ₂₅₆ , -3w ₂₅₆ ), (3w ₂₅₆ , -w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ , -15w ₂₅₆ ), (w ₂₅₆ , -13w ₂₅₆ ), (w ₂₅₆ , -11w ₂₅₆ ), (w ₂₅₆ , -9w ₂₅₆ ), ( w ₂₅₆ , -7w ₂₅₆ ), (w ₂₅₆ , -5w ₂₅₆ ), (w ₂₅₆ , -3w ₂₅₆ ), (w ₂₅₆ , -w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ), (-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ ), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), (-15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ) ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ), (-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ), (-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ) ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ), (-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ), (-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ 6), (-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ 6), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,- w ₂₅₆ ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ), (-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ) ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ), (-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

(w ₂₅₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. 4 It is mapped to the point 401, and when the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (15w ₂₅₆ , 15w ₂₅₆ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). In addition, an example of the relationship between the set (00000000-11111111) of b0, b1, b2, b3, b4, b5, b6, b7, and the coordinate of a signal point is as shown in FIG. 256 signal points of 256QAM (“○” in Fig. 4)

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ , -15w ₂₅₆ ), (15w ₂₅₆ , -13w ₂₅₆ ), (15w ₂₅₆ , -11w ₂₅₆ ), (15w ₂₅₆ , -9w ₂₅₆ ), (15w ₂₅₆ , -7w ₂₅₆ ), (15w ₂₅₆ , -5w ₂₅₆ ), (15w ₂₅₆ , -3w ₂₅₆ ), (15w ₂₅₆ , -w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13w ₂₅₆ , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ , -15w ₂₅₆ ), (13w ₂₅₆ ,-13w ₂₅₆ ), (13w ₂₅₆ ,-11w ₂₅₆ ), (13w ₂₅₆ ,-9w ₂₅₆ ), (13w ₂₅₆ ,-7w ₂₅₆ ), (13w ₂₅₆ ,-5w ₂₅₆ ), (13w ₂₅₆ ,-3w ₂₅₆ ), (13w ₂₅₆ ,-w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ ,-15w ₂₅₆ ), (11w ₂₅₆ ,-13w ₂₅₆ ), (11w ₂₅₆ ,-11w ₂₅₆ ), (11w ₂₅₆ ,-9w ₂₅₆ ), (11w ₂₅₆ ,-7w ₂₅₆ ), (11w ₂₅₆ ,-5w ₂₅₆ ), (11w ₂₅₆ ,-3w ₂₅₆ ), (11w ₂₅₆ ,-w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ), (9w ₂₅₆ ,-15w ₂₅₆ ), (9w ₂₅₆ ,-13w ₂₅₆ ), (9w ₂₅₆ ,-11w ₂₅₆ ), (9w ₂₅₆ ,-9w ₂₅₆ ), (9w ₂₅₆ ,-7w ₂₅₆ ), (9w ₂₅₆ ,-5w ₂₅₆ ), (9w ₂₅₆ ,-3w ₂₅₆ ), (9w ₂₅₆ ,-w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (7w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ), (7w ₂₅₆ ,-15w ₂₅₆ ), (7w ₂₅₆ ,-13w ₂₅₆ ), (7w ₂₅₆ ,-11w ₂₅₆ ), (7w ₂₅₆ ,-9w ₂₅₆ ), (7w ₂₅₆ ,-7w ₂₅₆ ), (7w ₂₅₆ ,-5w ₂₅₆ ), (7w ₂₅₆ ,-3w ₂₅₆ ), (7w ₂₅₆ ,-w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ), (5w ₂₅₆ ,-15w ₂₅₆ ), (5w ₂₅₆ ,-13w ₂₅₆ ), (5w ₂₅₆ ,-11w ₂₅₆ ), (5w ₂₅₆ ,-9w ₂₅₆ ), (5w ₂₅₆ ,-7w ₂₅₆ ), (5w ₂₅₆ ,-5w ₂₅₆ ), (5w ₂₅₆ ,-3w ₂₅₆ ), (5w ₂₅₆ ,-w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ ,-15w ₂₅₆ ), (3w ₂₅₆ ,-13w ₂₅₆ ), (3w ₂₅₆ ,-11w ₂₅₆ ), (3w ₂₅₆ ,-9w ₂₅₆ ), (3w ₂₅₆ ,-7w ₂₅₆ ), (3w ₂₅₆ ,-5w ₂₅₆ ), (3w ₂₅₆ ,-3w ₂₅₆ ), (3w ₂₅₆ ,-w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ , 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ ,-15w ₂₅₆ ), (w ₂₅₆ ,-13w ₂₅₆ ), (w ₂₅₆ ,-11w ₂₅₆ ), (w ₂₅₆ ,-9w ₂₅₆ ), (w ₂₅₆ ,-7w ₂₅₆ ), (w ₂₅₆ ,-5w ₂₅₆ ), (w ₂₅₆ ,-3w ₂₅₆ ), (w ₂₅₆ ,-w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ), (-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ 6), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), (-15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ), (-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ), (-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ) ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ), (-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ), (-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ ), (-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ ), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,-w ₂₅₆ ) ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ), (-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ) ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ), (-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q.

The relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 4 . Then, a value obtained by complex expression of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) becomes the baseband signal (s ₁ (t) or s ₂ (t)).

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₂ (i))) that is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( It is common to make the average power of t)(s ₂ (i))) the same. Therefore, the coefficient w _q described in the mapping method of QPSK described above, the coefficient w ₁₆ described in the mapping method of 16QAM described above, the coefficient w 64 described in the mapping method of 64QAM described above, and the coefficient w ₆₄ described in the mapping method of 256QAM described above The following relation holds for the coefficient w ₂₅₆ .

In the DVB standard, when the modulated signal #1 and modulated signal #1 are transmitted from two antennas in the MIMO transmission method, there is a case where the transmit average power of the modulated signal #1 and the transmit average power of the modulated signal #1 are set differently. do. For example, in the case of formulas (R2), (R3), (R4), (R5), and (R8) in the preceding description, Q1≠Q2 is the case.

As a more specific example, consider the following.

<1> When the precoding matrix F (or F(i)) in the formula (R2) is expressed by any of the following formulas.

or,

or,

or,

or,

or,

or,

or,

In addition, in formulas (R15), (R16), (R17), (R18), (R19), (R20), (R21), and (R22), α may be a real number or an imaginary number. good, and β may be a real number or an imaginary number. However, α is not 0 (zero). Also, β is not 0 (zero).

or,

or,

or,

or,

or,

or,

or,

or,

In the formulas (R23), (R25), (R27), and (R29), β may be a real number or an imaginary number. However, β is not 0 (zero).

or,

or,

or,

or,

However, θ ₁₁ (i) and θ ₂₁ (i) are functions of i (time or frequency), λ is a fixed value, α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). Also, β is not 0 (zero).

<2> When the precoding matrix F (or F(i)) in the formula (R3) is expressed by any of the formulas (15) to (30).

<3> When the precoding matrix F (or F(i)) in the formula (R4) is expressed by any of the formulas (15) to (30).

<4> When the precoding matrix F (or F(i)) in the formula (R5) is expressed by any of the formulas (15) to (34).

<5> When the precoding matrix F (or F(i)) in the formula (R8) is expressed by any of the formulas (15) to (30).

In <1> to <5>, it is assumed that the modulation method of s1(t) and the modulation method of s2(t) (the modulation method of s1(i) and the modulation method of s2(i)) are different.

In the above, the important point of this structural example is demonstrated. In addition, the points described below are particularly important when the precoding method in <1> to <5> is, in particular, in the precoding method in <1> to <5>, Equations (15) to (34) It can also be implemented when using other precoding matrices.

The modulation level of the modulation scheme of s ₁ (t) (s ₁ (i)) (ie, the baseband signal 505A) in <1> to <5> (in the in-phase I-orthogonal Q plane) 2g (g is an integer greater than or equal to 1), s ₂ (t) in <1> to <5> (s ₂ (i) 2h (h) is an integer greater than or equal to 1) (also set as g≠h).

Then, g-bit data is transmitted by 1 symbol of s ₁ (t)(s ₁ (i)), and h-bit data is transmitted by 1 symbol of s ₂ (t)(s ₂ (i)). Accordingly, g+h bits are transmitted in one slot formed of s ₁ (t)(s ₁ (i)) 1 symbol and s ₂ (t)(s ₂ (i)) 1 symbol. At this time, in order to obtain a high spatial diversity gain, the following conditions become important.

<Condition R-1>

When any precoding of Formula (R2), or Formula (R3), or Formula (R4), or Formula (R5), or Formula (R8) (however, processing other than precoding is included) is performed In one symbol of the signal z ₁ (t) (z ₁ (i)) after processing such as coding, the number of candidate signal points in the in-phase I-orthogonal Q plane becomes 2 g + h (g + h in 1 symbol) For all possible values of bit data, if signal points are created on the in-phase I-orthogonal Q plane, 2g+h signal points can be created (this number becomes the number of candidate signal points).

In addition, in one symbol of the signal z ₂ (t) (z ₂ (i)) after processing such as precoding, the number of candidate signal points in the in-phase I-orthogonal Q plane becomes 2 g + h (1 symbol). For all values that g+h bit of data can take, if signal points are created on the in-phase I-orthogonal Q plane, 2g+h signal points can be created (this number becomes the number of candidate signal points).

Next, while implementing a different expression for <condition R-1>, a new additional condition is divided into Formula (R2), Formula (R3), Formula (R4), Formula (R5), and Formula (R8). do

(Case 1)

When the processing of formula (R2) is performed using a fixed precoding matrix:

The following formula is considered as an expression of a step in the middle of the calculation of formula (R2).

(In addition, in Case 1, the precoding matrix F is a fixed precoding matrix (provided, however, that the modulation method in s ₁ (t) (s ₁ (i)) and/or s ₂ (t)(s ₂ ) If the modulation method in (i)) is changed, the precoding matrix may be changed).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following conditions are satisfied, a high spatial diversity gain can be obtained.

<Condition R-2>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2g+h signal points can be created. This number becomes the number of candidate signal points).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^{g + h} (g + h in 1 symbol) For all possible values of bit data, if signal points are created on the in-phase I-orthogonal Q plane, 2g+h signal points can be created (this number becomes the number of candidate signal points).

And when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is larger than the absolute value of Q ₂ ) in Formula (R2), the following conditions are considered.

<Condition R-3>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . Then, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) ) or more (D ₁ ≥ 0) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ >D ₂ (D ₁ is greater than D ₂ ) holds.

By the way, FIG. 53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (5301A) is transmitted from the transmission antenna #1 (5302A) of the transmitter, and the modulated signal #1 (5301B) is transmitted from the transmission antenna #1 (5302B). At this time, z ₁ (t) (z ₁ (i)) (that is, u ₁ (t) (u ₁ (i))) is transmitted from the transmission antenna #1 (5302A), and the transmission antenna #1 (5302B) is It is assumed that z ₂ (t)(z ₂ (i)) (that is, u ₂ (t)(u ₂ (i))) is transmitted.

And, the reception antenna #1 (5303X) and the reception antenna #1 (5303Y) of the reception device receive the modulated signal transmitted by the transmission device (the reception signal 530X and the reception signal 5304Y are obtained), but at this time, the transmission antenna Let the propagation coefficient of the receiving antenna #1 (5303X) from #1 (5302A) be h11(t), the propagation coefficient of the receiving antenna #1 (5302A) from the transmitting antenna #1 (5302A) to h21(t), Let the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302B) be h12(t), and the propagation coefficient of the receiving antenna #2 (5303Y) from the transmitting antenna #2 (5302B) to h22(t) do (t is time).

At this time, since |Q1|>|Q2| holds true, the reception state of the modulated signal of z1(t)(z1(i)) (that is, u1(t)(u1(i))) determines the reception quality of the received data. likely to be the dominant factor in Accordingly, by satisfying the <condition R-3>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-3'> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-3'>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2g+h signal points can be created. This number becomes the number of candidate signal points). And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ 1 < D ₂ (D ₁ is smaller than D ₂ ) holds.

In Case 1, for example, as a modulation method in s ₁ (t) (s ₁ (i)) and a modulation method in s ₂ (t) (s ₂ (i)), QPSK, 16QAM, 64QAM and 256QAM will be applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 2)

When the processing of formula (R2) is executed using any precoding matrix of the precoding matrices of formulas (R15) to (R30):

Consider the formula (R35) as an expression of a step in the middle of the operation of the formula (R2). In the case of Case 2, it is assumed that the precoding matrix F is a fixed precoding matrix, and the precoding matrix F is expressed by any one of formulas (R15) to (R30) (provided that s ₁ (t) ( When the modulation method in s ₁ (i)) and/or the modulation method in s ₂ (t)(s ₂ (i)) are changed, the precoding matrix may be changed.

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if <condition R-2> is satisfied, a high spatial diversity gain can be obtained.

And it is considered that <condition R-3> holds true as in Case 1 when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R2) do.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-3>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Moreover, even if the following conditions are satisfied, the possibility that the reception apparatus can obtain high data reception quality increases.

<Condition R-3''>

<Condition R-3> holds, and at the same time, P ₁ =P ₂ in the formula (R2) holds.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-3''>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-3'> may be satisfied when |Q ₁ |<|Q ₂ |.

Further, for the same reason, when |Q ₁ |< | Q ₂ |, the possibility that the receiving apparatus can obtain high data reception quality is increased even if the following conditions are satisfied.

<Condition R-3'''>

<Condition R-3'> is satisfied, and P ₁ =P ₂ in the formula (R2) holds.

In Case 2, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 3)

When the processing of formula (R2) is performed using any precoding matrix of the precoding matrices of formulas (R31) to (R34):

Consider the formula (R35) as an expression of a step in the middle of the operation of the formula (R2). In the case of Case 3, it is assumed that the precoding matrix F changes with time (or frequency). And it is assumed that the precoding matrix F(F(i)) is expressed by any one of formulas (R31) to (R34).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following <condition R-4> is satisfied, a high spatial diversity gain can be obtained.

<Condition R-4>

Symbol number i is N or more and M or less (N is an integer, M is an integer, and N<M (M is smaller than N)) in s ₁ (t)(s ₁ (i)) (that is, It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and that the modulation method of s ₂ (t) (s ₂ (i)) (that is, the baseband signal 505B) is fixed (does not change). do.

And when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), candidates in the in-phase I-orthogonal Q plane The number of signal points becomes 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And it is considered that <condition R-5> is satisfied when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R2).

<Condition R-5>

s ₁ (t)(s ₁ (i)) (i.e., the symbol number i is N or more and M or less (N is an integer, M is an integer, and N < M (M is smaller than N)). It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and the modulation method _of s2( _t )(s2(i)) (that is, the baseband signal 505B) is fixed (doesn't change). .

When the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), a candidate is found in the in-phase I-orthogonal Q plane. The number of signal points to be formed becomes 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And in symbol number i, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (i) (also, D ₁ (i) is a real number greater than or equal to 0 (zero) (D ₁ (i) ≥ 0) When D ₁ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

In addition, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in symbol number i, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) in the in-phase I-orthogonal Q plane is D ₂ (i) ( D ₂ (i) becomes a real number greater than or equal to 0 (zero) (D ₂ (i) ≥ 0) When D ₂ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

At this time, when the symbol number i is N or more and M or less, D ₁ (i) > D ₂ (i) (D ₁ (i) is greater than D ₂ (i)) holds for all i that satisfy this.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-5>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Moreover, even if the following conditions are satisfied, the possibility that the reception apparatus can obtain high data reception quality increases.

<Condition R-5'>

<Condition R-5> holds, and at the same time, P ₁ =P ₂ in the formula (R2) holds.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-5'>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-5''> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-5''>

Symbol number i is N or more and M or less (N is an integer, M is an integer, and N<M (M is smaller than N)) in s ₁ (t)(s ₁ (i)) (that is, It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and the modulation method _of s2( _t )(s2(i)) (that is, the baseband signal 505B) is fixed (doesn't change). .

When the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R35), a candidate is found in the in-phase I-orthogonal Q plane. The number of signal points to be formed becomes 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And in symbol number i, in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) is D ₁ (i) ( D ₁ (i) is a real number greater than or equal to 0 (zero) (D ₁ (i) ≥ 0) When D ₁ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

In addition, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R35), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in symbol number i, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) in the in-phase I-orthogonal Q plane is D ₂ (i) ( D ₂ (i) becomes a real number greater than or equal to 0 (zero) (D ₂ (i) ≥ 0) When D ₂ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

At this time, when the symbol number i is N or more and M or less, D ₁ (i) < D ₂ (i) (D ₁ (i) is smaller than D ₂ (i)) holds for all i that satisfy this.

Further, for the same reason, when |Q ₁ |< | Q ₂ |, the possibility that the receiving apparatus can obtain high data reception quality is increased even if the following conditions are satisfied.

<Condition R-5'''>

<Condition R-5''> is satisfied, and P ₁ =P ₂ in the formula (R2) holds.

In Case 3, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, modulation schemes other than PSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 4)

When the processing of formula (R3) is performed using a fixed precoding matrix:

The following expression is considered as an expression of a step in the middle of the calculation of Expression (R3).

(In addition, in the case of Case 4, the precoding matrix F is a fixed precoding matrix (however, the modulation method in s ₁ (t) (s ₁ (i)) and/or s ₂ (t) (s ₂ ) If the modulation method in (i)) is changed, the precoding matrix may be changed).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following conditions are satisfied, a high spatial diversity gain can be obtained.

<Condition R-6>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is larger than the absolute value of Q ₂ ) in Formula (R3), the following conditions are considered.

<Condition R-7>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ >D ₂ (D ₁ is greater than D ₂ ) holds.

By the way, FIG. 53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (5301A) is transmitted from the transmission antenna #1 (5302A) of the transmitter, and the modulated signal #1 (5301B) is transmitted from the transmission antenna #1 (5302B). At this time, z ₁ (t) (z ₁ (i)) (that is, u ₁ (t) (u ₁ (i))) is transmitted from the transmission antenna #1 (5302A), and the transmission antenna #1 (5302B) is It is assumed that z ₂ (t)(z ₂ (i)) (that is, u ₂ (t)(u ₂ (i))) is transmitted.

Then, the reception antenna #1 (5303X) and the reception antenna #2 (5303Y) of the reception device receive the modulated signal transmitted by the transmission device (the reception signal 530X and the reception signal 5304Y are obtained), but at this time, the transmission Let the propagation coefficient of the reception antenna #1 (5303X) from the antenna #1 (5302A) be h ₁₁ (t), and the propagation coefficient of the reception antenna #1 (5302A) from the transmission antenna #1 (5302A) to h ₂₁ (t) Let h ₁₂ (t) be the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302B), and the propagation coefficient of the receiving antenna #1 (5303Y) from the transmitting antenna #1 (5302B) to h _{22 Let} (t) be (t is time).

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-7>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Further, for the same reason, <condition R-7'> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-7'>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) is D ₁ (and Dv is a real number of 0 (zero) or more (D ₁ ≥ 0) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R36), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ < D ₂ (D ₁ is smaller than D ₂ ) holds.

In Case 4, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 5)

When the processing of formula (R3) is executed using any precoding matrix of the precoding matrices of formulas (R15) to (R30):

Consider the formula (R36) as an expression of a step in the middle of the operation of the formula (R3). In the case of Case 5, it is assumed that the precoding matrix F is a fixed precoding matrix, and the precoding matrix F is expressed by any one of formulas (R15) to (R30) (provided that s ₁ (t) ( When the modulation method in s ₁ (i)) and/or the modulation method in s ₂ (t)(s ₂ (i)) are changed, the precoding matrix may be changed.

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) ) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if <condition R-6> is satisfied, a high spatial diversity gain can be obtained.

And it is considered that <condition R-7> holds true as in Case 4 when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R3) do.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-7>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Moreover, even if the following conditions are satisfied, the possibility that the reception apparatus can obtain high data reception quality increases.

<Condition R-7''>

<Condition R-7> holds, and at the same time, P ₁ =P ₂ in the formula (R3) holds.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-7''>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Further, for the same reason, <condition R-7'> may be satisfied when |Q ₁ |<|Q ₂ |.

Further, for the same reason, when |Q ₁ |< | Q ₂ |, the possibility that the receiving apparatus can obtain high data reception quality is increased even if the following conditions are satisfied.

<Condition R-7'''>

<Condition R-7'> holds, and at the same time, P ₁ =P ₂ in the formula (R3) holds.

In Case 5, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 6)

When the processing of formula (R4) is performed using a fixed precoding matrix:

The following expression is considered as an expression of a step in the middle of the calculation of Expression (R4).

(In addition, in Case 6, the precoding matrix F is a fixed precoding matrix (provided, however, that the modulation method in s ₁ (t) (s ₁ (i)) and/or s ₂ (t)(s ₂ )) If the modulation method in (i)) is changed, the precoding matrix may be changed).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following conditions are satisfied, a high spatial diversity gain can be obtained.

<Condition R-8>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is larger than the absolute value of Q ₂ ) in Formula (R4), the following conditions are considered.

<Condition R-9>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ >D ₂ (D ₁ D ₂ are all greater) holds.

By the way, FIG. 53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (5301A) is transmitted from the transmission antenna #1 (5302A) of the transmitter, and the modulated signal #1 (5301B) is transmitted from the transmission antenna #1 (5302B). At this time, z ₁ (t) (z ₁ (i)) (that is, u ₁ (t) (u ₁ (i))) is transmitted from the transmission antenna #1 (5302A), and the transmission antenna #1 (5302B) is It is assumed that z ₂ (t)(z ₂ (i)) (that is, u ₂ (t)(u ₂ (i))) is transmitted.

Then, the reception antenna #1 (5303X) and the reception antenna #2 (5303Y) of the reception device receive the modulated signal transmitted by the transmission device (the reception signal 530X and the reception signal 5304Y are obtained), but at this time, the transmission Let the propagation coefficient of the reception antenna #1 (5303X) from the antenna #1 (5302A) be h ₁₁ (t), and the propagation coefficient of the reception antenna #1 (5302A) from the transmission antenna #1 (5302A) to h ₂₁ (t) Let h ₁₂ (t) be the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302B), and the propagation coefficient of the receiving antenna #1 (5303Y) from the transmitting antenna #1 (5302B) to h _{22 Let} (t) be (t is time).

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-9>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-9'> may be satisfied when |Q ₁ |<|Q ₂ .

<Condition R-9'>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ t) (u ₂ (i)) of the formula (R37), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ < D ₂ (D ₁ is smaller than D ₂ ) holds.

In Case 6, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 7)

When the processing of formula (R4) is performed using any precoding matrix of the precoding matrices of formulas (R15) to (R30):

Consider the formula (R37) as an expression of a step in the middle of the operation of the formula (R4). Incidentally, in Case 7, the precoding matrix F is a fixed precoding matrix, and the precoding matrix F is assumed to be expressed by any one of formulas (R15) to (R30) (provided that s ₁ (t) ( When the modulation method in s ₁ (i)) and/or the modulation method in s ₂ (t)(s ₂ (i)) are changed, the precoding matrix may be changed.

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if <condition R-8> is satisfied, a high spatial diversity gain can be obtained.

And it is considered that <condition R-9> holds true as in Case 6 when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R4) do.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-9>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Moreover, even if the following conditions are satisfied, the possibility that the reception apparatus can obtain high data reception quality increases.

<Condition R-9''>

<Condition R-9> holds, and at the same time, P1 = P2 in the formula (R4) holds.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-9''>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-9'> may be satisfied when |Q ₁ |<|Q ₂ |.

Further, for the same reason, when |Q ₁ |< | Q ₂ |, the possibility that the receiving apparatus can obtain high data reception quality is increased even if the following conditions are satisfied.

<Condition R-9'''>

<Condition R-9'> holds, and at the same time, P ₁ =P ₂ in the formula (R4) holds.

In Case 7, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 8)

When the processing of formula (R5) is performed using a fixed precoding matrix:

The following expression is considered as an expression of a step in the middle of the calculation of Expression (R5).

(In addition, in Case 8, the precoding matrix F is a fixed precoding matrix (provided, however, that the modulation method in s ₁ (t) (s ₁ (i)) and/or s ₂ (t) (s ₂ ) If the modulation method in (i)) is changed, the precoding matrix may be changed).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following conditions are satisfied, a high spatial diversity gain can be obtained.

<Condition R-10>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is larger than the absolute value of Q ₂ ) in Formula (R5), the following conditions are considered.

<Condition R-11>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ >D ₂ (D ₁ is greater than D ₂ ) holds.

By the way, FIG. 53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (5301A) is transmitted from the transmission antenna #1 (5302A) of the transmitter, and the modulated signal #1 (5301B) is transmitted from the transmission antenna #1 (5302B). At this time, z ₁ (t)(z ₁ (i)) (ie, u ₁ (t)(u ₁ (i))) is transmitted from the transmit antenna #1 (5302A), and z is transmitted from the transmit antenna #1 (5302B). It is assumed that ₂ (t)(z ₂ (i)) (that is, u ₂ (t)(u ₂ (i))) is transmitted.

Then, the reception antenna #1 (5303X) and the reception antenna #2 (5303Y) of the reception device receive the modulated signal transmitted by the transmission device (the reception signal 530X and the reception signal 5304Y are obtained), but at this time, the transmission Let the propagation coefficient of the reception antenna #1 (5303X) from the antenna #1 (5302A) be h ₁₁ (t), and the propagation coefficient of the reception antenna #1 (5302A) from the transmission antenna #1 (5302A) to h ₂₁ (t) Let h ₁₂ (t) be the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302B), and the propagation coefficient of the receiving antenna #1 (5303Y) from the transmitting antenna #1 (5302B) to h _{22 Let} (t) be (t is time).

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-11>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Further, for the same reason, <condition R-11'> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-11'>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, ^2g+h signal points can be created. This number becomes the number of candidate signal points). And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ < D ₂ (D ₁ is smaller than D ₂ ) holds.

In Case 8, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 9)

When the processing of formula (R5) is performed using any precoding matrix of the precoding matrices of formulas (R15) to (R30):

Consider the formula (R38) as an expression of a step in the middle of the operation of the formula (R5). In the case of Case 9, the precoding matrix F is a fixed precoding matrix, and the precoding matrix F is assumed to be expressed by any one of formulas (R15) to (R30) (provided that s ₁ (t) ( When the modulation method in s ₁ (i)) and/or the modulation method in s ₂ (t)(s ₂ (i)) are changed, the precoding matrix may be changed.

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if <condition R-10> is satisfied, a high spatial diversity gain can be obtained.

And it is considered that <condition R-11> holds true as in Case 8 when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R5) do.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-11>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Further, for the same reason, <condition R-11'> may be satisfied when |Q ₁ |<|Q ₂ |.

In Case 9, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 10)

When the processing of formula (R5) is performed using any precoding matrix of the precoding matrices of formulas (R31) to (R34):

Consider the formula (R38) as an expression of a step in the middle of the operation of the formula (R5). In the case of Case 10, it is assumed that the precoding matrix F changes with time (or frequency). And it is assumed that the precoding matrix F(F(i)) is expressed by any one of formulas (R31) to (R34).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following <condition R-12> is satisfied, a high spatial diversity gain can be obtained.

<Condition R-12>

Symbol number i is N or more and M or less (N is an integer, M is an integer, and N<M (M is smaller than N)) in s ₁ (t)(s ₁ (i)) (that is, It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and the modulation method _of s2( _t )(s2(i)) (that is, the baseband signal 505B) is fixed (doesn't change). .

And when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R38), candidates in the in-phase I-orthogonal Q plane The number of signal points becomes 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And it is considered that <condition R-13> is satisfied when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R5).

<Condition R-13>

Symbol number i is N or more and M or less (N is an integer, M is an integer, and N<M (M is smaller than N)) in s ₁ (t)(s ₁ (i)) (that is, It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and the modulation method _of s2( _t )(s2(i)) (that is, the baseband signal 505B) is fixed (doesn't change). .

When the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (uv(i)) of the formula (R38), it is a candidate in the in-phase I-orthogonal Q plane. The number of signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And in symbol number i, in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) is D ₁ (i) ( D ₁ (i) is a real number greater than or equal to 0 (zero) (D ₁ (i) ≥ 0) When D ₁ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

Further, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in symbol number i, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) in the in-phase I-orthogonal Q plane is D ₂ (i) ( D ₂ (i) is a real number greater than or equal to 0 (zero) (D ₂ (i) ≥ 0) When D ² (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

At this time, when the symbol number i is N or more and M or less, D ₁ (i) > D ₂ (i) (D ₁ (i) is greater than D ₂ (i)) holds for all i that satisfy this.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-13>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Moreover, even if the following conditions are satisfied, the possibility that the reception apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-13''> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-13''>

Symbol number i is N or more and M or less (N is an integer, M is an integer, and N<M (M is smaller than N)) in s ₁ (t)(s ₁ (i)) (that is, It is assumed that the modulation method of the baseband signal 505A) is fixed (does not change) and the modulation method _of s2( _t )(s2(i)) (that is, the baseband signal 505B) is fixed (doesn't change). .

When the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R38), a candidate is found in the in-phase I-orthogonal Q plane. The number of signal points to be formed becomes 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And in symbol number i, in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) is D ₁ (i) ( D ₁ (i) is a real number greater than or equal to 0 (zero) (D ₁ (i) ≥ 0) When D ₁ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

In addition, when the symbol number i is N or more and M or less, in all i that satisfy this, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R38), in the in-phase I-orthogonal Q plane The number of candidate signal points is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in symbol number i, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) in the in-phase I-orthogonal Q plane is D ₂ (i) ( D ₂ (i) becomes a real number greater than or equal to 0 (zero) (D ₂ (i) ≥ 0) When D ₂ (i) is 0 (zero), among 2 ^{g + h} signal points, in the in-phase I-orthogonal Q plane A signal point that exists in the same position exists).

At this time, when the symbol number i is N or more and M or less, D ₁ (i) < Dv(i) (D ₁ (i) is smaller than D ₂ (i)) holds for all i that satisfy this.

In Case 10, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 11)

When the processing of formula (R8) is performed using a fixed precoding matrix:

The following expression is considered as an expression of a step in the middle of the calculation of Expression (R8).

(In addition, in Case 11, the precoding matrix F is a fixed precoding matrix (provided, however, that the modulation method in s ₁ (t) (s ₁ (i)) and/or s ₂ (t) (s ₂ ) If the modulation method in (i)) is changed, the precoding matrix may be changed).

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if the following conditions are satisfied, a high spatial diversity gain can be obtained.

<Condition R-14>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 _g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) .

And when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is larger than the absolute value of Q ₂ ) in Formula (R8), the following conditions are considered.

<Condition R-15>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2 ^g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ >D ₂ (D ₁ is greater than D ₂ ) holds.

By the way, FIG. 53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (5301A) is transmitted from the transmission antenna #1 (5302A) of the transmitter, and the modulated signal #1 (5301B) is transmitted from the transmission antenna #1 (5302B). At this time, z ₁ (t)(z ₁ (i)) (ie, u ₁ (t)(u ₁ (i))) is transmitted from the transmit antenna #1 (5302A), and z is transmitted from the transmit antenna #1 (5302B). It is assumed that ₂ (t)(z ₂ (i)) (that is, u ₂ (t)(u ₂ (i))) is transmitted.

Then, the reception antenna #1 (5303X) and the reception antenna #2 (5303Y) of the reception device receive the modulated signal transmitted by the transmission device (the reception signal 530X and the reception signal 5304Y are obtained), but at this time, the transmission Let the propagation coefficient of the reception antenna #1 (5303X) from the antenna #1 (5302A) be h ₁₁ (t), and the propagation coefficient of the reception antenna #1 (5302A) from the transmission antenna #1 (5302A) to h ₂₁ (t) , the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302B) is h ₁₂ (t), and the propagation coefficient of the receiving antenna #1 (5303Y) from the transmitting antenna #1 (5302B) is h _{22 Let} (t) be (t is time).

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-15>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-15'> may be satisfied when |Q ₁ |<|Q ₂ |.

<Condition R-15'>

In one symbol of the signal u ₁ (t) (u ₁ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₁ (t) (u ₁ (i)) in the in-phase I-orthogonal Q plane is D ₁ (and D ₁ is 0 (zero) or more It becomes a real number (D ₁ ≥ 0.) When D ₁ is 0 (zero), among 2g+h signal points, there are signal points located at the same position in the in-phase I-orthogonal Q plane).

In addition, in one symbol of the signal u ₂ (t) (u ₂ (i)) of the formula (R39), the number of candidate signal points in the in-phase I-orthogonal Q plane is 2 ^g+h . (For all possible values of g+h bits of data in one symbol, if signal points are created on the in-phase I-orthogonal Q plane, 2 ^g+h signal points can be created. This number becomes the number of candidate signal points) . And in the in-phase I-orthogonal Q plane, the minimum Euclidean distance of 2 ^g+h candidate signal points of u ₂ (t) (u ₂ (i)) is D ₂ (and D ₂ is 0 (zero) or more It becomes a real number (D ₂ ≥ 0.) When D ₂ is 0 (zero), among 2 ^g+h signal points, there are signal points at the same position in the in-phase I-orthogonal Q plane).

At this time, D ₁ < D ₂ (D ₁ is smaller than D ₂ ) holds.

In Case 11, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

(Case 12)

When the processing of formula (R8) is executed using any precoding matrix of the precoding matrices of formulas (R15) to (R30):

Consider the formula (R39) as an expression of a step in the middle of the operation of the formula (R8). Incidentally, in Case 12, the precoding matrix F is a fixed precoding matrix, and the precoding matrix F is assumed to be expressed by any one of formulas (R15) to (R30) (provided that s ₁ (t) ( When the modulation method in s ₁ (i)) and/or the modulation method in s ₂ (t)(s ₂ (i)) are changed, the precoding matrix may be changed.

₂ ^g (g is an integer greater than or equal to _{1), s 2 (} t) (s ₂ (i)) )) (i.e., the baseband signal 505B), the modulation multi-valued number of the modulation method is 2 ^h (h is an integer greater than or equal to 1), and g≠h.

At this time, if <condition R-14> is satisfied, a high spatial diversity gain can be obtained.

And it is considered that <condition R-15> holds true as in Case 11 when |Q ₁ |> | Q ₂ | (the absolute value of Q ₁ is greater than the absolute value of Q ₂ ) in the formula (R8) do.

At this time, in that |Q ₁ |> | Q ₂ | holds, the reception state of the modulated signal of z ₁ (t)(z ₁ (i)) (that is, u ₁ (t)(u ₁ (i))) is likely to be the dominant factor in the reception quality of received data. Accordingly, by satisfying the <condition R-15>, the possibility that the receiving apparatus can obtain high data reception quality increases.

Also, for the same reason, <condition R-15'> may be satisfied when |Q ₁ |<|Q ₂ |.

In Case 12, for example, the modulation method in s ₁ (t) (s ₁ (i)) and the modulation method in s ₂ (t) (s ₂ (i)) are QPSK, 16QAM, and 64QAM as described above. , 256QAM is applied. At this time, the specific mapping method is as described above in this configuration example. However, a modulation method other than QPSK, 16QAM, 64QAM, and 256QAM may be used.

As described above in this configuration example, in the transmission method for transmitting two modulated signals after precoding from different antennas, the signal point of the modulated signal having the larger average transmit power is in the in-phase I-orthogonal Q plane. By increasing the minimum Euclidean distance, the possibility that the reception apparatus can obtain the effect that high data reception quality can be obtained increases.

In addition, each of the transmitting antenna and the receiving antenna described in the above configuration example may be constituted by a plurality of antennas. Further, another antenna for transmitting each of the two modulated signals after precoding may be used to simultaneously transmit one modulated signal at different times.

In addition, the above-described precoding method can be similarly implemented when a single carrier method, an OFDM method, a multi-carrier method such as an OFDM method using wavelet transformation, and a spread spectrum method are applied.

Further, specific examples of the present embodiment will be described in detail in the following embodiments, and operations of the receiver will also be described.

(Configuration example S1)

In this configuration example, a more specific example of the precoding method when the transmission average powers of the two transmission signals described in configuration example R1 are different will be described.

Fig. 5 shows an example of the configuration of a part that generates a modulated signal at one time in a transmission apparatus of a base station (broadcasting station, access point, etc.) that allows switching of a transmission method.

A transmission apparatus of a base station (broadcasting station, access point, etc.) will be described with reference to FIG. 5 .

The encoding unit 502 of FIG. 5 receives the information 501 and the control signal 512 as inputs, and performs encoding based on the information on the encoding rate and the code length (block length) included in the control signal 512 , , the encoded data 503 is output.

The mapping unit 504 receives the encoded data 503 and the control signal 512 as inputs. In addition, the control signal 512 specifies that two streams are transmitted as a transmission method. Also, it is assumed that the control signal 512 designates the modulation method α and the modulation method β as the respective modulation methods of the two streams. In addition, modulation method α is a modulation method that modulates x-bit data, and modulation method β is a modulation method that modulates y-bit data (for example, in the case of 16 QAM (16 Quadrature Amplitude Modulation), 4-bit data is modulated. It is a modulation method that modulates 6-bit data in the case of 64QAM (64 Quadrature Amplitude Modulation).

Then, the mapping unit 504 modulates the x-bit data among the x+y-bit data by the modulation method α to generate and output the baseband signal s ₁ (t) 505A, and also the remaining y-bit data. The data of ? is modulated with the modulation method β and _a baseband signal s ₂ (t) 505B is output. A mapping unit and a mapping unit for generating s ₂ (t) may exist separately, in this case, the encoded data 503 includes a mapping unit for generating s ₁ (t) and a mapping unit for generating s ₂ (t) mapping unit).

Note that s ₁ (t) and s ₂ (t) are expressed by complex numbers (however, either a complex number or a real number may be used), and t is time. In addition, when a transmission method using a multi-carrier such as OFDM (Orthogonal Frequency Division Multiplexing) is used, s ₁ and s ₂ are functions of frequency f like s ₁ (f) and s ₂ (f), or s ₁ It can also be thought of as a function of time t, frequency f, such as (t, f) and s ₂ (t, f).

Hereinafter, the baseband signal, the precoding matrix, the phase change, etc. are described as a function of time t, but it may be considered as a function of frequency f, time t and frequency f.

Therefore, there are cases where the baseband signal, the precoding matrix, and the phase change are described as a function of the symbol number i, but in this case, a function of time t, a function of frequency f, and a function of time t and frequency f good to think That is, the symbol and the baseband signal may be generated and disposed in the time axis direction or may be generated and disposed in the frequency axis direction. Further, the symbol and the baseband signal may be generated and arranged in the direction of the time axis and the direction of the frequency axis.

The power change unit 506A (power adjuster 506A) receives the baseband signal s ₁ (t) 505A and the control signal 512 as inputs, and sets a real number P ₁ based on the control signal 512, P ₁ x s ₁ (t) is output as the signal 507A after power change (note that P ₁ is a real number, but may be a complex number).

Similarly, the power change unit 506B (power adjuster 506B) receives the baseband signal s ₂ (t) 505B and the control signal 512 as inputs, sets a real number P ₂ , and sets P ₂ ×s ₂ (t) ) is output as the signal 507B after power change (note that P ₂ is a real number, but may be a complex number).

The weighted synthesis unit 508 receives the signal after power change 507A, the signal after power change 507B, and the control signal 512 as inputs, and based on the control signal 512, the precoding matrix F (or F(i) )) is set. When the slot number (symbol number) is i, the weighted synthesis unit 508 performs the following operation.

Here, a(i), b(i), c(i), and d(i) can be expressed as complex numbers (which may be real numbers)., a(i), b(i), c(i), d 3 or more of (i) must not be 0 (zero). Further, the precoding matrix may be a function of i or may not be a function of i. And when the precoding matrix is a function of i, the precoding matrix is changed by the slot number (symbol number).

Then, the weighted synthesis unit 508 outputs u ₁ (i) in the equation (S1) as the signal 509A after weight synthesis, and converts u ₂ (i) in the equation (S1) to the signal 509B after weight synthesis. output as

The power change unit 510A receives the signal 509A (u ₁ (i)) and the control signal 512 after weight synthesis as inputs, and sets a real number Q ₁ based on the control signal 512, Q ₁ × u ₁ (t) is output as the signal 511A (z ₁ (i)) after power change (although Q ₁ is a real number, it may be a complex number).

Similarly, the power change unit 510B receives the weighted synthesis signal 509B (u ₂ (i)) and the control signal 512 as inputs, and sets a real number Q ₂ based on the control signal 512, Q ₂ x u ₂ (t) is output as the signal 511A (z ₂ (i)) after power change (although Q ₂ is a real number, it may be a complex number).

Therefore, the following expression holds.

Next, a transmission method in the case of transmitting two streams different from that of FIG. 5 will be described with reference to FIG. Incidentally, in Fig. 6, the same reference numerals are assigned to those operating in the same manner as in Fig. 5 .

The phase change unit 601 receives the signal 509B and the control signal 512 after weight synthesis of u ₂ (i) in the equation (S1), and, based on the control signal 512, in the equation (S1) Change the phase of the signal 509B after weighting u ₂ (i). Therefore, the signal after changing the phase of the signal 509B after weighting u ₂ (i) in Equation (S1) is e ^jθ (i) × u ₂ (i), and e ^jθ (i) × u ₂ (i) is a signal 602 after the phase change, which is output by the phase change unit 601 (j is an imaginary number unit). Moreover, it becomes a characteristic part that the value of the phase to change is a function of i like (theta)(i).

In addition, the power changing units 510A and 510B of FIG. 6 change the power of the input signal, respectively. Accordingly, the respective outputs z ₁ (i) and z ₂ (i) of the power changing units 510A and 510B in FIG. 6 are expressed as follows.

In addition, as a method of realizing the formula (S3), there is a configuration different from FIG. 6 in FIG. 7 . The difference between FIG. 6 and FIG. 7 is that the order of the power change unit and the phase change unit is changed. (The function itself of executing a power change and a phase change does not change). In this case, z ₁ (i) and z ₂ (i) are expressed as follows.

In addition, z 1 (i) of Formula (S3) and z ₁ (i) of Formula (S4) are the same, and z ₂ (i) of Formula (S3) _and z ₂ (i) of Formula (S4) is also the same

The changing phase value θ(i) in equations (S3) and (S4) is, for example, set so that θ(i+1)-θ(i) is a fixed value, in the propagation environment of radio waves dominated by direct waves. Therefore, there is a high possibility that the receiving device can obtain good data reception quality. However, the method of assigning the value θ(i) of the phase to be changed is not limited to this example.

Fig. 8 shows an example of the configuration of the signal processing unit performed on the signals z ₁ (i) and z ₂ (i) obtained in Figs. 5 to 7 .

The inserting unit 804A receives the signal z ₁ (i) 801A, the pilot symbol 802A, the control information symbol 803A, and the control signal 512 as inputs, so as to construct a frame included in the control signal 512. Accordingly, a pilot symbol 802A and a control information symbol 803A are inserted into the signal (symbol) z ₁ (i) 801A, and a modulated signal 805A according to the frame configuration is output.

In addition, the pilot symbol 802A and the control information symbol 803A are symbols modulated by BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), or the like (other modulation schemes may be used).

The radio unit 806A receives the modulated signal 805A and the control signal 512 as inputs, and performs frequency conversion, amplification, etc. processing on the modulated signal 805A based on the control signal 512 (OFDM method). is used, processing such as an inverse Fourier transform is performed) A transmission signal 807A is output, and the transmission signal 807A is output as a radio wave from the antenna 808A.

The inserting unit 804B receives the signal z ₂ (i) 801B, the pilot symbol 802B, the control information symbol 803B, and the control signal 512 as inputs, so as to construct a frame included in the control signal 512 . Accordingly, a pilot symbol 802B and a control information symbol 803B are inserted into the signal (symbol) z ₂ (i) 801B to output a modulated signal 805B according to the frame configuration.

The pilot symbol 802B and the control information symbol 803B are symbols modulated by BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), or the like (other modulation schemes may be used).

The radio unit 806B receives the modulated signal 805B and the control signal 512 as inputs, and performs frequency conversion and amplification on the modulated signal 805B based on the control signal 512 (OFDM method). is used, processing such as an inverse Fourier transform is performed) A transmission signal 807B is output, and the transmission signal 807B is output as a radio wave from the antenna 808B.

Here, in the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B), the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B) of which i is the same number are the same ( common) frequency is transmitted from different antennas at the same time. (that is, it becomes a transmission method using the MIMO method).

The pilot symbol 802A and the pilot symbol 802B are symbols for signal detection, frequency offset estimation, gain control, channel estimation, and the like in the receiving apparatus, and are called pilot symbols here. You may use other names, etc.

In addition, the control information symbol 803A and the control information symbol 803B include information on the modulation method used by the transmitter, information on the transmission method, information on the precoding method, information on the error correction coding method, information on the coding rate of the error correction code, It is a symbol for transmitting information on the block length (code length) of the error correction code to the receiving device. Alternatively, the control information symbol may be transmitted using only one of the control information symbol 803A and the control information symbol 803B.

9 shows an example of a frame configuration in time-frequency in the case of transmitting two streams. In FIG. 9 , the horizontal axis represents frequency and the vertical axis represents time. For example, the configuration of symbols from carrier 1 to carrier 38 and time $1 to time $11 is shown.

9 shows the frame structure of the transmission signal transmitted from the antenna 806A in FIG. 8 and the frame of the transmission signal transmitted from the antenna 808B at the same time.

In Fig. 9, in the case of a frame of a transmission signal transmitted from the antenna 806A in Fig. 8, the data symbol corresponds to the signal (symbol) z ₁ (i). And the pilot symbol corresponds to the pilot symbol 802A.

In Fig. 9, in the case of a frame of a transmission signal transmitted from the antenna 806B in Fig. 8, the data symbol corresponds to the signal (symbol) z ₂ (i). And the pilot symbol corresponds to the pilot symbol 802B.

(Therefore, as described above, in the signal z ₁ (i) (801A) and the signal z ₂ (i) (801B), i is the signal z ₁ (i) (801A) and the signal z ₂ (i) of the same number. ) 801B transmits the same (common) frequency from different antennas at the same time, and the configuration of the pilot symbol is not limited to Fig. 9. For example, the time interval of the pilot symbol and the frequency interval are It is not limited to Fig. 9. And, in Fig. 9, a frame structure in which pilot symbols are transmitted from the antenna 806A of Fig. 8 and the antenna 806B of Fig. 8 at the same time and on the same frequency (same (sub-carrier)) However, the present invention is not limited thereto, and for example, a pilot symbol is disposed in the antenna 806A of FIG. 8 at time A and frequency a ((sub) carrier a), and at time A, frequency a ((sub) carrier a) ), it is assumed that no symbols are arranged on the antenna 806B of Fig. 8, and that no symbols are arranged on the antenna 806A of Fig. 8 at time B and frequency b ((sub)carrier b); It is good also as a configuration in which pilot symbols are arranged in the antenna 806B of FIG. 8 at B and frequency b ((sub)carrier b).

In addition, although only data symbols and pilot symbols are described in FIG. 9, other symbols, for example, symbols such as control information symbols, may be included in the frame.

5 to 7 , a case in which some (or all) of the power changing unit is present has been described in the example, but a case in which a part of the power changing unit is absent is also considered.

For example, in Fig. 5, when the power change unit 506A (power adjuster 506A) and the power change unit 506B (power adjuster 506B) do not exist, z ₁ (i) and z ₂ (i) are as follows. is displayed

In Fig. 5, when the power changing unit 510A (the power adjusting unit 510A) and the power changing unit 510B (the power adjusting unit 510B) do not exist, z ₁ (i) and z ₂ (i) are displayed as follows do.

5, a power change unit 506A (power adjustment unit 506A), a power change unit 506B (power adjustment unit 506B), a power change unit 510A (power adjustment unit 510A), a power change unit 510B (power When the adjustment unit 510B does not exist, z ₁ (i) and z ₂ (i) are expressed as follows.

In addition, in FIG. 6 or FIG. 7, when the power changing part 506A (power adjusting part 506A) and the power changing part 506B (power adjusting part 506B) do not exist, z ₁ (i) and z ₂ (i) are the following is displayed as

In addition, in Fig. 6 or Fig. 7, when the power change unit 510A (power adjuster 510A) and the power change unit 510B (power adjuster 510B) do not exist, z ₁ (i) and z ₂ (i) are as follows is displayed as

6 or 7, a power change unit 506A (power adjustment unit 506A), a power change unit 506B (power adjustment unit 506B), a power change unit 510A (power adjustment unit 510A), and a power change unit 510B ) (the power adjusting unit 510B) does not exist, z ₁ (i) and z ₂ (i) are expressed as follows.

Next, when using the transmission method of transmitting the two streams (MIMO (Multiple Input Multiple Output) method) described above, the precoding method when the transmission average power of the two transmission signals described in Configuration Example R1 is different A specific example will be described.

(Example 1)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 16QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 64QAM, for example, any precoding and/or power change of Equation (S2), Equation (S3), Equation (S4), Equation (S5), Equation (S8) is performed. An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 16QAM will be described. 10 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 10, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 10 is the signal point) in the in-phase I-orthogonal Q plane are (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ) ,-w ₁₆ ), (3w ₁₆ ,-3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), ( -w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ , -3w ₁₆ ) (w ₁₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 1001 in FIG. 10, and the in-phase component of the baseband signal after mapping is I, If the orthogonal component is Q, (I, Q)=(3w ₁₆ , 3w ₁₆ ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in FIG. 10) (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ,-w ₁₆ ), (3w ₁₆ , -3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (-w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (- 3w ₁₆ , -3w ₁₆ ), the values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000 to 1111) and the coordinates of the signal points in 16QAM is not limited to FIG. 10 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 16QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

The 64QAM mapping method will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, if the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. 11, and the base after mapping If the in-phase component of the band signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

The values of sets 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . In addition, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 16QAM, and the baseband signal 505B (s ₂ (t)) The configuration of the precoding matrix will be described with the modulation scheme of (s ₂ (i))) being 64QAM.

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₁ (i))) which is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( t)(s ₂ (i))) It is common to make the average power equal. Accordingly, the following relational expression holds for the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above.

In the formulas (S11) and (S12), z is a real number larger than 0. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The precoding matrix F when performing the operation of

The structure of and the relationship between Q ₁ and Q ₂ will be described in detail below ((Example 1-1) to (Example 1-8)).

(Example 1-1)

In the case of any one of <1> to <5> described above, it is assumed that the precoding matrix F is set to any of the following.

or,

or,

or,

In the formulas (S14), (S15), (S16), and (S17), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

In addition, in this structural example (common in this specification), the unit of the phase, for example, the declination in a complex plane, is set as "radian". (Exceptionally, when using degree(“degree”), it indicates the unit).

If the complex plane is used, the complex number can be displayed in polar form in terms of polar coordinates. When the complex number z = a + jb (a, b are both real and j is an imaginary unit) is mapped to a point (a, b) on the complex plane, if this point is expressed as [r, θ in polar coordinates,

a=r×cosθ,

b=r×sinθ

Equation (49) holds, r is the absolute value of z (r = |z|), and θ is the argument. And z = a + jb is expressed as rejθ. Therefore, for example, although ejπ is described in Formulas (S14) to (S17), the unit of the declination angle π is "radian".

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of α for obtaining the reception quality of α are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

And the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 16QAM, and the modulation method of the base band signal 505B (s ₂ (t) (s ₂ (i))) becomes 64QAM. Therefore, when transmitting a modulated signal from each antenna by performing precoding (and phase change, power change) as described above, the antenna 808A of FIG. 8 by (unit) time and frequency (carrier) v of time u ) and the total number of bits transmitted by the symbol transmitted from the antenna 808B is 10 bits, which is the sum of 4 bits (by using 16QAM) and 6 bits (by using 64QAM).

Input bits for mapping of 16QAM to b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , and input bits for mapping of 64QAM to b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3 , 64} , b _{4 , 64 ,} b _{5 , 64} , the signal z ₁ (t) For (z ₁ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) A signal point corresponding to is in the in-phase I-orthogonal Q plane,

Similarly, for the signal z ₂ (t) (z ₂ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) A signal point corresponding to is in the in-phase I-orthogonal Q plane.

In the preceding statement, “Paying attention to the signal z ₁ (t)(z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device Equations (S18) to (S21) have been described as "values of α for obtaining good data reception quality", but this point will be described.

For signal z ₁ (t)(z ₁ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) Signal points corresponding to ? exist in the in-phase I-orthogonal Q plane, but preferably, these 210=1024 signal points do not overlap in the in-phase I-orthogonal Q plane and exist as 1024 signal points.

Because, when the modulated signal transmitted from the antenna transmitting the signal z ₂ (t) (z ₂ (i)) does not reach the receiving device, the receiving device uses the signal z ₁ (t)(z ₁ (i)) Thus, detection and error correction decoding are performed, but in this case, in order for the receiving device to obtain high data reception quality, it is good if there are "1024 signal points without overlapping".

Set the precoding matrix F to any one of formulas (S14), (S15), (S16), and (S17), and formulas (S18), (S19), (S20), and (S21) and Similarly, when α is set, (b _{0 , 16} , b _{1 , 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) is (0, 0, 0, 0, 0, 0, The arrangement of the signal points corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) from the signal points corresponding to 0, 0, 0, 0) is as shown in FIG. 12 . In Fig. 12, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 12, it can be seen that the signal points do not overlap and there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S14), Equation (S15), Equation (S16), Equation (S17), Equation (S18), Equation (S19), Equation (S20), Equation (S21) When α is set as follows, (b _{0, 16} , b _{1 , 16} , b _{2 , 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) is (0, 0, 0, 0, 0, 0) The arrangement of the signal points corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) from the signal points corresponding to , 0, 0, 0, 0) is as shown in FIG. 13 . Moreover, in FIG. 13, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from Fig. 13, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 12 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 13 is D ₂ . Then D ₁ > D ₂ holds. Therefore, from the structural example R1, in the formula (S2), the formula (S3), the formula (S4), the formula (S5), and the formula (S8), when Q ₁ ≠ Q ₂ , Q ₁ >Q ₂ may be satisfied. .

(Example 1-2)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S22) and (S24), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z1(t)(z1(i)) in the equations (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of θ for obtaining quality are as follows.

or,

or,

or,

Also, in formulas (S26), (S27), (S28), and (S29), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function that has appropriately limited the domain of the trigonometric function). ) and

becomes Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S22), (S23), (S24), and (S25), and with formulas (S26), (S27), (S28), and (S29) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u1t) (u1(i)) described in the configuration example R1 is shown in FIG. become together In Fig. 12, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 12, it can be seen that the signal points do not overlap and there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S22), Equation (S23), Equation (S24), Equation (S25), Equation (S26), Equation (S27), Equation (S28), Equation (S29) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u2(t)(u2(i)) described in the configuration example R1 of the signal points corresponding to 1, 1, 1, 1, 1, 1, 1) is As shown in FIG. 13 . Moreover, in FIG. 13, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from Fig. 13, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 12 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 13 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 1-3)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S31), (S32), (S33), and (S34), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

The precoding matrix F is set to any one of formulas (S31), (S32), (S33), and (S34), and with formulas (S35), (S36), (S37), and (S38) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 14 . Moreover, in FIG. 14, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from FIG. 14 , the signal points do not overlap, and it can be seen that there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S31), Equation (S32), Equation (S33), Equation (S34), Equation (S35), Equation (S36), Equation (S37), Equation (S38) If α is set as in (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 15 . In Fig. 15, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 15, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 14 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 15 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, from the structural example R1, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8), it is good if Q ₁ >Q ₂ holds do.

(Example 1-4)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S39) and (S41), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S43), (S44), (S45), and (S46), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain) ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

The precoding matrix F is set to any one of formulas (S39), (S40), (S41), and (S42), and with formulas (S43), (S44), (S45), and (S46) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 14 .

Moreover, in FIG. 14, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from FIG. 14 , the signal points do not overlap, and it can be seen that there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S39), Equation (S40), Equation (S41), Equation (S42), Equation (S43), Equation (S44), Equation (S45), Equation (S46) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 15 . In Fig. 15, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from FIG. 15 , it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 14 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 15 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 1-5)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S48), (S49), (S50), and (S51), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

The precoding matrix F is set to any one of formulas (S48), (S49), (S50), and (S51), and with formulas (S52), (S53), (S54), and (S55) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 16 . In Fig. 16, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 16, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S48), Equation (S49), Equation (S50), Equation (S51), Equation (S52), Equation (S53), Equation (S54), Equation (S55) If α is set as in (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 17 . In Fig. 17, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 17, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 16 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 17 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is better if Q ₁ < Q ₂ holds. do.

(Example 1-6)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S56) and (S58), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S60), (S61), (S62), and (S63), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain). ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S56), (S57), (S58), and (S59), and formulas (S60), (S61), (S62), and (S63) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 16 .

In Fig. 16, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 16, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S56), (S57), (S58), and (S59), and formulas (S60), (S61), (S62), and (S63) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 17 . In Fig. 17, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 17, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 16 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 17 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 1-7)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S65), (S66), (S67), and (S68), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

The precoding matrix F is set to any one of formulas (S65), (S66), (S67), and (S68), and with formulas (S69), (S70), (S71), and (S72) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64} , b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64} , b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 18 . In Fig. 18, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 18, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S65), Equation (S66), Equation (S67), Equation (S68), Equation (S69), Equation (S70), Equation (S71), Equation (S72) _{When α is set like _ _} b _{3, 64} , b _{4, 64} , b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 19 . In Fig. 19, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 19, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 18 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 19 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 1-8)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S73) and (S75), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S77), (S78), (S79), and (S80), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately limited domain) ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S73), (S74), (S75), and (S76), and formulas (S77), (S78), (S79), (S80) and If θ is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64} , b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64} , b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 18 . In Fig. 18, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 18, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S73), Equation (S74), Equation (S75), Equation (S76), Equation (S77), Equation (S78), Equation (S79), Equation (S80) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64} , b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64} , b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 19 . In Fig. 19, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 19, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 18 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 19 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 1 - Supplement)

In (Example 1-1) to (Example 1-8), examples of values of α and examples of values of θ that are likely to obtain high data reception quality are shown, but the values of α and θ are Even if it is not a value, high data reception quality can be obtained by satisfying the condition shown in the configuration example R1.

(Example 2)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 64QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 16QAM, for example, any precoding and/or power change of Equation (S2), Equation (S3), Equation (S4), Equation (S5), Equation (S8) is performed. An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 16QAM will be described. 10 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 10, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 10 is the signal point) in the in-phase I-orthogonal Q plane are (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ) ,-w ₁₆ ), (3w ₁₆ ,-3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), ( -w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ , -3w ₁₆ ) (w ₁₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 1001 in FIG. 10, and the in-phase component of the baseband signal after mapping is I , when the orthogonal component is Q, (I, Q) = (3w16, 3w16).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in FIG. 10) (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w ₁₆ ,-w ₁₆ ), (3w ₁₆ , -3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (-w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (- 3w ₁₆ , -3w ₁₆ ), the values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000-1111) and the coordinates of the signal points in 16QAM is not limited to FIG. 10 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 16QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

A mapping method of 64QAM will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-w ₆₄ ), (5w ₆₄ ,-3w ₆₄ ), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3w ₆₄ ), (3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ ) (w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. If the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-w ₆₄ ), (5w ₆₄ ,-3w ₆₄ ), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3w ₆₄ ), (3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), (-7w ₆₄ , -7w ₆₄ ), the sets b0, b1, b2, b3, b4, b5 set values from 000000 to 111111 are shown. . Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . In addition, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the baseband signal 505B (s ₂ (t)) Assuming that the modulation method of (s ₂ (i))) is 16QAM, the configuration of the precoding matrix will be described.

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₁ (i))) which is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( t)(s ₂ (i))) It is common to make the average power equal.

Accordingly, the following relational expression holds for the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above.

In the formulas (S82) and (S83), z is a real number greater than zero. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The precoding matrix F when performing the operation of

(Example 2-1) to (Example 28)) will be described in detail below regarding the configuration of , and the relationship between Q1 and Q2.

(Example 2-1)

In any one of <1> to <5> described above, it is assumed that the precoding matrix F is set to one of the following.

or,

or,

or,

In the formulas (S85), (S86), (S87), and (S88), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of α for obtaining the reception quality of α are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

By the way, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the modulation method of the base band signal 505B (s ₂ (t) (s ₂ (i))) The method becomes 16QAM. Therefore, when transmitting a modulated signal from each antenna by performing precoding (and phase change, power change) as described above, the antenna 808A of FIG. 8 by (unit) time and frequency (carrier) v of time u. ) and the total number of bits transmitted by the symbol transmitted from the antenna 808B is 10 bits of the sum of 4 bits (by using 16QAM) and 6 bits (by using 64QAM).

Input bits for mapping of 16QAM are b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16,} 64 Input bits for mapping of QAM are set to b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3 , 64} , b _{4 , 64 ,} b _{5 , 64} , the signal z ₁ (t) For (z ₁ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) A signal point corresponding to is in the in-phase I-orthogonal Q plane,

Similarly, for the signal z ₂ (t) (z ₂ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) A signal point corresponding to is in the in-phase I-orthogonal Q plane.

In the previous explanation,

"Paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device Expressions (S89) to (S92) are described as "values of α for obtaining reception quality", but this point will be described.

For signal z ₂ (t)(z ₂ (i)),

(b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) Signal points corresponding to ? exist in the in-phase I-orthogonal Q plane, but these 210=1024 signal points do not overlap in the in-phase I-orthogonal Q plane, and preferably exist as 1024 signal points.

Because, when the modulated signal transmitted from the antenna transmitting the signal z ₁ (t) (z ₁ (i)) does not reach the receiving device, the receiving device uses the signal z ₂ (t)(z ₂ (i)) Therefore, detection and error correction decoding are performed, but in this case, in order for the receiving apparatus to obtain high data reception quality, it is sufficient that "1024 signal points without overlapping" exist.

The precoding matrix F is set to any one of formulas (S85), (S86), (S87), and (S88), and with formulas (S89), (S90), (S91), and (S92) Similarly, when α is set, (b _{0, 16} , b _{1 , 16} , b _{2 , 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) is (0, 0, 0, 0, 0, 0, The arrangement of the signal points corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) from the signal points corresponding to 0, 0, 0, 0) is as shown in FIG. 16 . In Fig. 16, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 16, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S85), Equation (S86), Equation (S87), Equation (S88), Equation (S89), Equation (S90), Equation (S91), Equation (S92) When α is set as , (b _{0 , 16} , b _{1 , 16} , b _{2 , 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) is (0, 0, 0, 0, 0, 0) , 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) the arrangement of the signal points corresponding to (1, 1, 1) is as shown in FIG. In Fig. 17, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 17, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 16 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 17 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 2-2)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S93) and (S95), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, in formulas (S97), (S98), (S99), and (S100), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately limited domain) ) and

becomes this In addition, "tan-1(x)" may be described as -1an-1(x)", "arctan(x)", or "Arctan(x)". And N is an integer.

The precoding matrix F is set to any one of formulas (S93), (S94), (S95), and (S96), and with formulas (S97), (S98), (S99), and (S100) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 16 . In Fig. 16, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 16, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S93), Equation (S94), Equation (S95), Equation (S96), Equation (S97), Equation (S98), Equation (S99), Equation (S100) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 17 . In Fig. 17, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 17, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 1024 signal points of FIG. 16 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 17 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is good if Q ₁ < Q ₂ holds.

(Example 2-3)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S102), (S103), (S104), and (S105), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S102), (S103), (S104), and (S105), and formulas (S106), (S107), (S108), and (S109) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 18 . In Fig. 18, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 18, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of formulas (S102), (S103), (S104), and (S105), and formulas (S106), (S107), (S108), and (S109) If α is set as in (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 corresponding to 1, 1, 1, 1, 1, 1, 1) is shown in Fig. 19 and so on. In Fig. 19, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 19, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

Then, the minimum Euclidean distance of 1024 signal points of FIG. 18 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 19 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is good if Q ₁ < Q ₂ holds.

(Example 2-4)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S110) and (S112), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, in formulas (S114), (S115), (S116), and (S117), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain) ) and

becomes Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S110), (S111), (S112), and (S113), and formulas (S114), (S115), (S116), and (S117) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. 18 . In Fig. 18, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 18, it can be seen that there are 1024 signal points without overlapping. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S110), Equation (S111), Equation (S112), Equation (S113), Equation (S114), Equation (S115), Equation (S116), Equation (S117) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 19 . In Fig. 19, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 19, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

Then, the minimum Euclidean distance of 1024 signal points of FIG. 18 is D ₂ , and the minimum Euclidean distance of 1024 signal points of FIG. 19 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is good if Q ₁ < Q ₂ holds.

(Example 2-5)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P12 = P22 in formula (S2)

<2> When P12 = P22 in formula (S3)

<3> When P12 = P22 in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S119), (S120), (S121), and (S122), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

The precoding matrix F is set to any one of formulas (S119), (S120), (S121), and (S122), and with formulas (S123), (S124), (S125), and (S126) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 12 . In Fig. 12, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 12, it can be seen that the signal points do not overlap and there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S119), Equation (S120), Equation (S121), Equation (S122), Equation (S123), Equation (S124), Equation (S125), Equation (S126) If α is set as in (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 corresponding to 1, 1, 1, 1, 1, 1, 1) is shown in Fig. 13 and so on. Moreover, in FIG. 13, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from Fig. 13, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 12 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 13 is D ₂ . Then, D ₁ > D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds.

(Example 2-6)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S127) and (S129), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S131), (S132), (S133), and (S134), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain). ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S127), (S128), (S129), and (S130), and formulas (S131), (S132), (S133), and (S134) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 12 . In Fig. 12, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 12, it can be seen that the signal points do not overlap and there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S127), Equation (S128), Equation (S129), Equation (S130), Equation (S131), Equation (S132), Equation (S133), Equation (S134) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 corresponding to 1, 1, 1, 1, 1, 1, 1) is shown in Fig. 13 and so on. Moreover, in FIG. 13, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from Fig. 13, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 12 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 13 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 2-7)

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S136), (S137), (S138), and (S139), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S136), (S137), (S138), and (S139), and formulas (S140), (S141), (S142), and (S143) If α is set in the same way as described above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 14 . Moreover, in FIG. 14, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from FIG. 14 , the signal points do not overlap, and it can be seen that there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S136), Equation (S137), Equation (S138), Equation (S139), Equation (S140), Equation (S141), Equation (S142), Equation (S143) When α is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, The arrangement of the signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 corresponding to 1, 1, 1, 1, 1, 1, 1) is shown in Fig. like 15. In Fig. 15, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 15, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 14 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 15 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 2-8)

Next, with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S11) and (S12) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S144) and (S146), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S148), (S149), (S150), and (S151), tan-1(x) is an inverse trigonometric function (the inverse function of an inverse trigonometric function that appropriately limits the domain of the trigonometric function) ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S144), (S145), (S146), and (S147), and formulas (S148), (S149), (S150), and (S151) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. 14 . Moreover, in FIG. 14, the horizontal axis|shaft is I, the vertical axis|shaft is Q, and "-" is a signal point.

As can be seen from FIG. 14 , the signal points do not overlap, and it can be seen that there are 1024 signal points. In addition, among 1024 signal points in the in-phase I-orthogonal Q plane, the most of the 1020 signal points except for the rightmost top, rightmost bottom, rightmost top, and leftmost bottom 4 Euclidean distances between adjacent signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S144), Equation (S145), Equation (S146), Equation (S147), Equation (S148), Equation (S149), Equation (S150), Equation (S151) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 15 .

In Fig. 15, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 15, it can be seen that the signal points do not overlap and there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points of FIG. 14 is D ₁ , and the minimum Euclidean distance of 1024 signal points of FIG. 15 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 2 - Supplement)

In (Example 2-1) to (Example 2-8), examples of values of α and examples of values of θ that are likely to obtain high data reception quality are shown, but the values of α and θ are Even if it is not a value, high data reception quality can be obtained by satisfying the condition shown in the configuration example R1.

(Example 3)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 64QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 256QAM, for example, when any precoding and/or power change of Equation (S2), Equation (S3), Equation (S4), Equation (S5), Equation (S8) is executed, An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 64QAM will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. If the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), (-7w ₆₄ , -7w ₆₄ ), the sets b0, b1, b2, b3, b4, b5 set values from 000000 to 111111 are shown. . Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . In addition, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

A mapping method of 256QAM will be described. 20 shows an example of 256QAM signal point arrangement in the in-phase I-orthogonal Q plane. In addition, in Fig. 20, 256 ? denote 256QAM signal points.

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 20 is the signal point) in the in-phase I-orthogonal Q plane are,

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ ,-15w ₂₅₆ ), (15w ₂₅₆ ,-13w ₂₅₆ ), (15w ₂₅₆ ,-11w ₂₅₆ ), (15w ₂₅₆ ,-9w ₂₅₆ ), (15w ₂₅₆ ,-7w ₂₅₆ ), (15w ₂₅₆ ,-5w ₂₅₆ ), (15w ₂₅₆ ,-3w ₂₅₆ ), (15w ₂₅₆ ,-w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13wv , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ ,-15w ₂₅₆ ), (13w ₂₅₆ ,-13w ₂₅₆ ), (13w ₂₅₆ ,-11w ₂₅₆ ), (13w ₂₅₆ ,-9w ₂₅₆ ), ( 13w ₂₅₆ ,-7w ₂₅₆ ), (13w ₂₅₆ ,-5w ₂₅₆ ), (13w ₂₅₆ ,-3w ₂₅₆ ), (13w ₂₅₆ ,-w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ ,-15w ₂₅₆ ), (11w ₂₅₆ ,-13w ₂₅₆ ), (11w ₂₅₆ ,-11w ₂₅₆ ), (11w ₂₅₆ ,-9w ₂₅₆ ), (11w ₂₅₆ ,-7w ₂₅₆ ), (11w ₂₅₆ ,-5w ₂₅₆ ), (11w ₂₅₆ ,-3w ₂₅₆ ), (11w ₂₅₆ ,-w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ), (9w ₂₅₆ ,-15w ₂₅₆ ), (9w ₂₅₆ ,-13w ₂₅₆ ), (9w ₂₅₆ ,-11w ₂₅₆ ), (9w ₂₅₆ ,-9w ₂₅₆ ), (9w ₂₅₆ ,-7w ₂₅₆ ), (9w ₂₅₆ ,-5w ₂₅₆ ), (9w ₂₅₆ ,-3w ₂₅₆ ), (9w ₂₅₆ ,-w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (7w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ), (7w ₂₅₆ ,-15w ₂₅₆ ), (7w ₂₅₆ ,-13w ₂₅₆ ), (7w ₂₅₆ ,-11w ₂₅₆ ), (7w ₂₅₆ ,-9w ₂₅₆ ), (7w ₂₅₆ ,-7w ₂₅₆ ), (7w ₂₅₆ ,-5w ₂₅₆ ), (7w ₂₅₆ ,-3w ₂₅₆ ), (7w ₂₅₆ ,-w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ), (5w ₂₅₆ ,-15w ₂₅₆ ), (5w ₂₅₆ ,-13w ₂₅₆ ), (5w ₂₅₆ ,-11w ₂₅₆ ), (5w ₂₅₆ ,-9w ₂₅₆ ), (5w ₂₅₆ ,-7w ₂₅₆ ), (5w ₂₅₆ ,-5w ₂₅₆ ), (5w ₂₅₆ ,-3w ₂₅₆ ), (5w ₂₅₆ ,-w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ ,-15w ₂₅₆ ), (3w ₂₅₆ ,-13w ₂₅₆ ), (3w ₂₅₆ ,-11w ₂₅₆ ), (3w ₂₅₆ ,-9w ₂₅₆ ), (3w ₂₅₆ ,-7w ₂₅₆ ), (3w ₂₅₆ ,-5w ₂₅₆ ), (3w ₂₅₆ ,-3w ₂₅₆ ), (3w ₂₅₆ ,-w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ , 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ ,-15w ₂₅₆ ), (w ₂₅₆ ,-13w ₂₅₆ ), (w ₂₅₆ ,-11w ₂₅₆ ), (w ₂₅₆ ,-9w ₂₅₆ ), (w ₂₅₆ ,-7w ₂₅₆ ), (w ₂₅₆ ,-5w ₂₅₆ ), (w ₂₅₆ ,-3w ₂₅₆ ), (w ₂₅₆ ,-w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ), (-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ ), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), (-15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ) ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ), (-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ), (-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ) ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ), (-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ), (-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ ), (-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ ), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,-w ₂₅₆ ) ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ), (-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ) ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ), (-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

(w ₂₅₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. 20 It is mapped to the point 2001, and when the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q)=(15w ₂₅₆ , 15w ₂₅₆ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). An example of the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal point is shown in FIG. 20 . 256 signal points of 256QAM (“○” in Fig. 20)

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ ,-15w ₂₅₆ ), (15w ₂₅₆ ,-13w ₂₅₆ ), (15w ₂₅₆ ,-11w ₂₅₆ ), (15w ₂₅₆ ,-9w ₂₅₆ ), (15w ₂₅₆ ,-7w ₂₅₆ ), (15w ₂₅₆ ,-5w ₂₅₆ ), (15w ₂₅₆ ,-3w ₂₅₆ ), (15w ₂₅₆ ,-w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13wv , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ ,-15w ₂₅₆ ), (13w ₂₅₆ ,-13w ₂₅₆ ), (13w ₂₅₆ ,-11w ₂₅₆ ), (13w ₂₅₆ ,-9w ₂₅₆ ), ( 13w ₂₅₆ ,-7w ₂₅₆ ), (13w ₂₅₆ ,-5w ₂₅₆ ), (13w ₂₅₆ ,-3w ₂₅₆ ), (13w ₂₅₆ ,-w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ ,-15w ₂₅₆ ), (11w ₂₅₆ ,-13w ₂₅₆ ), (11w ₂₅₆ ,-11w ₂₅₆ ), (11w ₂₅₆ ,-9w ₂₅₆ ), (11w ₂₅₆ ,-7w ₂₅₆ ), (11w ₂₅₆ ,-5w ₂₅₆ ), (11w ₂₅₆ ,-3w ₂₅₆ ), (11w ₂₅₆ ,-w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ), (9w ₂₅₆ ,-15w ₂₅₆ ), (9w ₂₅₆ ,-13w ₂₅₆ ), (9w ₂₅₆ ,-11w ₂₅₆ ), (9w ₂₅₆ ,-9w ₂₅₆ ), (9w ₂₅₆ ,-7w ₂₅₆ ), (9w ₂₅₆ ,-5w ₂₅₆ ), (9w ₂₅₆ ,-3w ₂₅₆ ), (9w ₂₅₆ ,-w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (7w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ), (7w ₂₅₆ ,-15w ₂₅₆ ), (7w ₂₅₆ ,-13w ₂₅₆ ), (7w ₂₅₆ ,-11w ₂₅₆ ), (7w ₂₅₆ ,-9w ₂₅₆ ), (7w ₂₅₆ ,-7w ₂₅₆ ), (7w ₂₅₆ ,-5w ₂₅₆ ), (7w ₂₅₆ ,-3w ₂₅₆ ), (7w ₂₅₆ ,-w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ), (5w ₂₅₆ ,-15w ₂₅₆ ), (5w ₂₅₆ ,-13w ₂₅₆ ), (5w ₂₅₆ ,-11w ₂₅₆ ), (5w ₂₅₆ ,-9w ₂₅₆ ), (5w ₂₅₆ ,-7w ₂₅₆ ), (5w ₂₅₆ ,-5w ₂₅₆ ), (5w ₂₅₆ ,-3w ₂₅₆ ), (5w ₂₅₆ ,-w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ ,-15w ₂₅₆ ), (3w ₂₅₆ ,-13w ₂₅₆ ), (3w ₂₅₆ ,-11w ₂₅₆ ), (3w ₂₅₆ ,-9w ₂₅₆ ), (3w ₂₅₆ ,-7w ₂₅₆ ), (3w ₂₅₆ ,-5w ₂₅₆ ), (3w ₂₅₆ ,-3w ₂₅₆ ), (3w ₂₅₆ ,-w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ , 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ ,-15w ₂₅₆ ), (w ₂₅₆ ,-13w ₂₅₆ ), (w ₂₅₆ ,-11w ₂₅₆ ), (w ₂₅₆ ,-9w ₂₅₆ ), (w ₂₅₆ ,-7w ₂₅₆ ), (w ₂₅₆ ,-5w ₂₅₆ ), (w ₂₅₆ ,-3w ₂₅₆ ), (w ₂₅₆ ,-w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ), (-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ ), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), (-15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ) ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ), (-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ), (-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ) ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ), (-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ), (-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ ), (-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ ), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,-w ₂₅₆ ) ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ), (-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ) ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ), (-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 20 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the baseband signal 505B (s ₂ (t)) The configuration of the precoding matrix will be described with the modulation scheme of (s ₂ (i))) being 256QAM.

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₁ (i))) which is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( t)(s ₂ (i))) It is common to make the average power equal. Accordingly, the following relational expression holds for the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above.

In the formulas (S153) and (S154), z is a real number greater than zero. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The precoding matrix F when performing the operation of

The configuration of (Example 3-1) to (Example 3-8) will be described in detail below.

(Example 3-1)

In the case of any one of <1> to <5> described above, it is assumed that the precoding matrix F is set to one of the following.

or,

or,

or,

In the formulas (S156), (S157), (S158), and (S159), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of α for obtaining the reception quality of α are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

By the way, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the modulation method of the base band signal 505B (s ₂ (t) (s ₂ (i))) The method is set to 256QAM. Therefore, when precoding (and phase change, power change) is performed as described above and the modulated signal is transmitted from each antenna, the antenna ( The total number of bits transmitted by the symbols transmitted from 808A) and the symbols transmitted from the antenna 808B is 14 bits of the sum of 6 bits (by using 64QAM) and 8 bits (by using 256QAM).

Input bits for mapping of 64QAM to b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , 256 Input bits for mapping of QAM to b _{0, 256} When , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} , Formula (S160), Formula (S161), Formula (S162), no matter which α of the formula (S163) is set,

For the signal z ₁ (t)(z ₁ (i)), (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0) , 0, 0, 0, 0, 0, 0, 0, 0) from the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, A signal point corresponding to 1) exists in the in-phase I-orthogonal Q plane,

Similarly, for the signal z ₂ (t) (z ₂ (i)),

(b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0) From the signal point corresponding to ) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1) exists in the in-phase I-orthogonal Q plane. .

In the previous explanation,

"Paying attention to the signals z1(t)(z1(i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data reception quality Expressions (S160) to (S163) have been described as "values of α for obtaining

For signal z1(t)(z1(i)),

(b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0) ) from the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1) so that the signal point corresponding to (1, 1, 1, 1, 1, 1) exists in the in-phase I-orthogonal Q plane. However, these 214 = 16384 signal points do not overlap in the in-phase I-orthogonal Q plane, and preferably exist as 16384 signal points.

Because, when the modulated signal transmitted from the antenna transmitting the signal z ₂ (t) (z ₂ (i)) does not reach the receiving device, the receiving device uses the signal z1(t)(z1(i)) to This is because detection and error correction decoding are performed, but in this case, in order for the receiving device to obtain high data reception quality, "no overlapping, 16384 signal points" is sufficient. The precoding matrix F is set to any one of formulas (S156), (S157), (S158), and (S159), and with formulas (S160), (S161), (S162), and (S163) Similarly, when α is set, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ), the arrangement of the signal points present in the first upper limit is the same as in FIG. 21 , the arrangement of the signal points present in the second upper limit is the same as in FIG. 22 , and the signal points present in the third upper limit The arrangement is the same as in FIG. 23, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 24 . In addition, in Figs. 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 21, 22, 23, and 24, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 21 , the rightmost bottom of FIG. 24 , the rightmost top of FIG. 22 , and the leftmost bottom of FIG. 23 . The Euclidean distances between the 16,380 signal points except for 4 of the nearest other signal points are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S156), Equation (S157), Equation (S158), Equation (S159), Equation (S160), Equation (S161), Equation (S162), Equation (S163) When α is set as follows, (b _{0, 64,} b _{1 , 64} , b _{2 , 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7 , 256} ), the arrangement of the signal points present in the first upper limit is the same as that of FIG. 25 , the arrangement of the signal points present in the second upper limit is the same as that of FIG. The arrangement of the signal points is as shown in FIG. 27, and the arrangement of the signal points existing in the fourth upper limit is as shown in FIG. 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 25, 26, 27, and 28, the signal points do not overlap, and it can be seen that there are 16,384 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 21, 22, 23, and 24 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 25, 26, 27, and 28 is D ₂ do it with Then, D1>D2 holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 3-2)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S153) and (S154) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

A case in which the precoding matrix F when performing the operation of is set to any of the following is considered.

or,

or,

or,

In the formulas (S164) and (S166), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, in formulas (S168), (S169), (S170), and (S171), tan-1(x) is an inverse trigonometric function (the inverse function of an inverse trigonometric function that appropriately limits the domain of the trigonometric function) ) and

becomes Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S164), (S165), (S166), and (S167), and formulas (S168), (S169), (S170), and (S171) When θ is set in the same way, if it is considered as described above, in the signal u ₁₍ t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 21 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 23, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 24. In addition, in Figs. 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 21, 22, 23 and 24, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 21 , the rightmost bottom of FIG. 24 , the rightmost top of FIG. 22 , and the leftmost bottom of FIG. 23 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S164), Equation (S165), Equation (S166), Equation (S167), Equation (S168), Equation (S169), Equation (S170), Equation (S171) When θ is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of the signal points present in the third upper limit is as shown in FIG. 27, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 28. 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 25, 26, 27, and 28, the signal points do not overlap, and it can be seen that there are 16,384 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 21, 22, 23, and 24 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 25, 26, 27, and 28 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 3-3)

Equations (S153) and (S154) are established with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S173), (S174), (S175), and (S176), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S173), (S174), (S175), and (S176), and formulas (S177), (S178), (S179), and (S180) When α is set in the same way, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 29 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is the same as in FIG. 31, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 32 . Further, in Figs. 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 29, 30, 31, and 32, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of Fig. 29, the rightmost bottom of Fig. 32, the rightmost top of Fig. 30, and the leftmost bottom of Fig. 31 The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S173), Equation (S174), Equation (S175), Equation (S176), Equation (S177), Equation (S178), Equation (S179), Equation (S180) When α is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b ₁ ) _{, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points present in the third upper limit is the same as in FIG. 35 , and the arrangement of signal points present in the fourth upper limit is as shown in FIG. 36 . 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 33, 34, 35, and 36, the signal points do not overlap, and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 29, 30, 31, and 32 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 33, 34, 35 and 36 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 3-4)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S153) and (S154) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S181) and (S183), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, in formulas (S185), (S186), (S187), and (S188), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately limited domain) ) and

becomes Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S181), (S182), (S183), and (S184), and formulas (S185), (S186), (S187), and (S188) When θ is set in the same way, if it is considered as described above, in the signal u ₁ (t)(u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 29 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is the same as in FIG. 31, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 32 . Further, in Figs. 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 29, 30, 31 and 32, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of Fig. 29, the rightmost bottom of Fig. 32, the rightmost top of Fig. 30, and the leftmost bottom of Fig. 31 The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S181), Equation (S182), Equation (S183), Equation (S184), Equation (S185), Equation (S186), Equation (S187), Equation (S188) When θ is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points present in the third upper limit is the same as in FIG. 35 , and the arrangement of signal points present in the fourth upper limit is as shown in FIG. 36 . 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 33, 34, 35, and 36, the signal points do not overlap and it can be seen that there are 16,384 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 29, 30, 31, and 32 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 33, 34, 35 and 36 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 3-5)

Equations (S153) and (S154) are established with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S190), (S191), (S192), and (S193), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S190), (S191), (S192), and (S193), and formulas (S194), (S195), (S196), and (S197) When α is set in the same way, if it is considered as described above, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ), the arrangement of the signal points existing in the first upper limit is the same as in FIG. 37 , the arrangement of the signal points existing in the second upper limit is the same as in FIG. 38 , and the third The arrangement of the signal points present in the upper limit is the same as in FIG. 39, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 40 . 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 37, 38, 39, and 40, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 37 , the rightmost bottom of FIG. 40 , the rightmost top of FIG. 38 , and the leftmost bottom of FIG. 39 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S190), Equation (S191), Equation (S192), Equation (S193), Equation (S194), Equation (S195), Equation (S196), Equation (S197) When α is set as shown above, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of the signal points present in the third upper limit is the same as in FIG. 43, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 44 . In addition, in Figs. 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 41, 42, 43, and 44, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points in FIGS. 37, 38, 39, and 40 is D ₂ , and the minimum Euclidean distance of 16384 signal points in FIGS. 41, 42, 43 and 44 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 3-6)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S153) and (S154) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S198) and (S200), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S202), (S203), (S204), and (S205), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having a domain appropriately limited). ) and

becomes Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

The precoding matrix F is set to any one of formulas (S198), (S199), (S200), and (S201), and with formulas (S202), (S203), (S204), and (S205) When θ is set in _the same way, if it is considered as described above _, (b0, 64, b1, 64, b2, 64, b3, 64, b4, 64, b5, 64, b0, 256, b1, 256, b2, 256, b3, 256, b4, 256, b5, 256, b6, 256, b7, 256) The arrangement of the signal points present in the first upper limit among the signal points to The arrangement of the signal points existing in the fourth upper limit is as shown in FIG. 40 . 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 37, 38, 39, and 40, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 37 , the rightmost bottom of FIG. 40 , the rightmost top of FIG. 38 , and the leftmost bottom of FIG. 39 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S198), Equation (S199), Equation (S200), Equation (S201), Equation (S202), Equation (S203), Equation (S204), Equation (S205) When θ is set as shown above, in the same way as described above, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ), the arrangement of the signal points existing in the first upper limit is the same as in FIG. 41 , the arrangement of the signal points existing in the second upper limit is the same as in FIG. 42 , and the third The arrangement of the signal points existing in the upper limit is the same as in FIG. 43, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 44 . In addition, in Figs. 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 41, 42, 43, and 44, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points in FIGS. 37, 38, 39, and 40 is D ₂ , and the minimum Euclidean distance of 16384 signal points in FIGS. 41, 42, 43 and 44 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 3-7)

Equations (S153) and (S154) are established with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S207), (S208), (S209), and (S210), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

The precoding matrix F is set to any one of formulas (S207), (S208), (S209), and (S210), and with formulas (S211), (S212), (S213), and (S214) When α is set in the same way, if it is considered as described above _, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 45 , the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 47, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 48. 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 45, 46, 47, and 48, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 45 , the rightmost bottom of FIG. 48 , the rightmost top of FIG. 46 , and the leftmost bottom of FIG. 47 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S207), (S208), (S209), and (S210), and formulas (S211), (S212), (S213), (S214) When α is set as shown above, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points existing in the third upper limit is the same as in FIG. 51 , and the arrangement of signal points existing in the fourth upper limit is as shown in FIG. 52 . Further, in Figs. 49, 50, 51 and 52, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 49, 50, 51, and 52, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 45, 46, 47, and 48 is D ₂ , and the minimum Euclidean distance of 16384 signal points of FIGS. 49, 50, 51 and 52 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q1 ≠ Q2 in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is good if Q1 < Q2 holds.

(Example 3-8)

Equations (S153) and (S154) are established with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S215) and (S217), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in the formulas (S219), (S220), (S221), and (S222), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain). ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

The precoding matrix F is set to any one of formulas (S215), (S216), (S217), and (S218), and with formulas (S219), (S220), (S221), and (S222) When θ is set in _the same way, if it is considered as described above, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 45 , the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 47, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 48. 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 45, 46, 47, and 48, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 45 , the rightmost bottom of FIG. 48 , the rightmost top of FIG. 46 , and the leftmost bottom of FIG. 47 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S215), Equation (S216), Equation (S217), Equation (S218), Equation (S219), Equation (S220), Equation (S221), Equation (S222) When θ is set as shown above, if it is considered as described above, in the signal u ₁ (t)(u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points existing in the third upper limit is the same as in FIG. 51 , and the arrangement of signal points existing in the fourth upper limit is as shown in FIG. 52 . Further, in Figs. 49, 50, 51 and 52, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 49, 50, 51, and 52, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 45, 46, 47, and 48 is D ₂ , and the minimum Euclidean distance of 16384 signal points of FIGS. 49, 50, 51 and 52 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 3 - Supplement)

In (Example 3-1) to (Example 3-8), examples of values of α and examples of values of θ that are likely to obtain high data reception quality are shown, but the values of α and θ are Even if it is not a value, high data reception quality can be obtained by satisfying the condition shown in the configuration example R1.

(Example 4)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 256QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 64QAM, for example, any precoding and/or power change of equations (S2), (S3), (S4), (S5), and (S8) is performed. An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 64QAM will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. If the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), (-7w ₆₄ , -7w ₆₄ ), the sets b0, b1, b2, b3, b4, b5 set values from 000000 to 111111 are shown. . Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . In addition, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

A mapping method of 256QAM will be described. 20 shows an example of 256QAM signal point arrangement in the in-phase I-orthogonal Q plane. In addition, in Fig. 20, 256 ? denote 256QAM signal points.

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 20 is the signal point) in the in-phase I-orthogonal Q plane are,

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ ,-15w ₂₅₆ ), (15w ₂₅₆ ,-13w ₂₅₆ ), (15w ₂₅₆ ,-11w ₂₅₆ ), (15w ₂₅₆ ,-9w ₂₅₆ ), (15w ₂₅₆ ,-7w ₂₅₆ ), (15w ₂₅₆ ,-5w ₂₅₆ ), (15w ₂₅₆ ,-3w ₂₅₆ ), (15w ₂₅₆ ,-w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13wv , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ ,-15w ₂₅₆ ), (13w ₂₅₆ ,-13w ₂₅₆ ), (13w ₂₅₆ ,-11w ₂₅₆ ), (13w ₂₅₆ ,-9w ₂₅₆ ), ( 13w ₂₅₆ ,-7w ₂₅₆ ), (13w ₂₅₆ ,-5w ₂₅₆ ), (13w ₂₅₆ ,-3w ₂₅₆ ), (13w ₂₅₆ ,-w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ ,-15w ₂₅₆ ), (11w ₂₅₆ ,-13w ₂₅₆ ), (11w ₂₅₆ ,-11w ₂₅₆ ), (11w ₂₅₆ ,-9w ₂₅₆ ), (11w ₂₅₆ ,-7w ₂₅₆ ), (11w ₂₅₆ ,-5w ₂₅₆ ), (11w ₂₅₆ ,-3w ₂₅₆ ), (11w ₂₅₆ ,-w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ),

(9w ₂₅₆ ,-15w ₂₅₆ ), (9w ₂₅₆ ,-13w ₂₅₆ ), (9w ₂₅₆ ,-11w ₂₅₆ ), (9w ₂₅₆ ,-9w ₂₅₆ ), (9w ₂₅₆ ,-7w ₂₅₆ ), (9w ₂₅₆ ,- 5w ₂₅₆ ), (9w ₂₅₆ ,-3w ₂₅₆ ), (9w ₂₅₆ ,-w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (7w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ),

(7w ₂₅₆ ,-15w ₂₅₆ ), (7w ₂₅₆ ,-13w ₂₅₆ ), (7w ₂₅₆ ,-11w ₂₅₆ ), (7w ₂₅₆ ,-9w ₂₅₆ ), (7w ₂₅₆ ,-7w ₂₅₆ ), (7w ₂₅₆ ,- 5w ₂₅₆ ), (7w ₂₅₆ ,-3w ₂₅₆ ), (7w ₂₅₆ ,-w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ),

(5w ₂₅₆ ,-15w ₂₅₆ ), (5w ₂₅₆ ,-13w ₂₅₆ ), (5w ₂₅₆ ,-11w ₂₅₆ ), (5w ₂₅₆ ,-9w ₂₅₆ ), (5w ₂₅₆ ,-7w ₂₅₆ ), (5w ₂₅₆ ,- 5w ₂₅₆ ), (5w ₂₅₆ ,-3w ₂₅₆ ), (5w ₂₅₆ ,-w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ ,-15w ₂₅₆ ), (3w ₂₅₆ ,-13w ₂₅₆ ), (3w ₂₅₆ ,-11w ₂₅₆ ), (3w ₂₅₆ ,-9w ₂₅₆ ), (3w ₂₅₆ ,-7w ₂₅₆ ), (3w ₂₅₆ ,-5w ₂₅₆ ), (3w ₂₅₆ ,-3w ₂₅₆ ), (3w ₂₅₆ ,-w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ , 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ ,-15w ₂₅₆ ), (w ₂₅₆ ,-13w ₂₅₆ ), (w ₂₅₆ ,-11w ₂₅₆ ), (w ₂₅₆ ,-9w ₂₅₆ ), (w ₂₅₆ ,-7w ₂₅₆ ), (w ₂₅₆ ,-5w ₂₅₆ ), (w ₂₅₆ ,-3w ₂₅₆ ), (w ₂₅₆ ,-w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ),

(-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ ), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), ( -15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ),

(-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ),

(-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ),

(-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ),

(-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ ),

(-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ ), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,-w ₂₅₆ ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ),

(-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ),

(-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

(w ₂₅₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. 20 It is mapped to the point 2001, and if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (15w ₂₅₆ , 15w256).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). An example of the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal point is shown in FIG. 20 . 256 signal points of 256QAM (“○” in Fig. 20)

(15w ₂₅₆ , 15w ₂₅₆ ), (15w ₂₅₆ , 13w ₂₅₆ ), (15w ₂₅₆ , 11w ₂₅₆ ), (15w ₂₅₆ , 9w ₂₅₆ ), (15w ₂₅₆ , 7w ₂₅₆ ), (15w ₂₅₆ , 5w ₂₅₆ ), (15w ₂₅₆ , 3w ₂₅₆ ), (15w ₂₅₆ , w ₂₅₆ ), (15w ₂₅₆ ,-15w ₂₅₆ ), (15w ₂₅₆ ,-13w ₂₅₆ ), (15w ₂₅₆ ,-11w ₂₅₆ ), (15w ₂₅₆ ,-9w ₂₅₆ ), (15w ₂₅₆ ,-7w ₂₅₆ ), (15w ₂₅₆ ,-5w ₂₅₆ ), (15w ₂₅₆ ,-3w ₂₅₆ ), (15w ₂₅₆ ,-w ₂₅₆ ),

(13w ₂₅₆ , 15w ₂₅₆ ), (13w ₂₅₆ , 13w ₂₅₆ ), (13w ₂₅₆ , 11w ₂₅₆ ), (13w ₂₅₆ , 9w ₂₅₆ ), (13w ₂₅₆ , 7w ₂₅₆ ), (13w ₂₅₆ , 5w ₂₅₆ ), (13wv , 3w ₂₅₆ ), (13w ₂₅₆ , w ₂₅₆ ), (13w ₂₅₆ ,-15w ₂₅₆ ), (13w ₂₅₆ ,-13w ₂₅₆ ), (13w ₂₅₆ ,-11w ₂₅₆ ), (13w ₂₅₆ ,-9w ₂₅₆ ), ( 13w ₂₅₆ ,-7w ₂₅₆ ), (13w ₂₅₆ ,-5w ₂₅₆ ), (13w ₂₅₆ ,-3w ₂₅₆ ), (13w ₂₅₆ ,-w ₂₅₆ ),

(11w ₂₅₆ , 15w ₂₅₆ ), (11w ₂₅₆ , 13w ₂₅₆ ), (11w ₂₅₆ , 11w ₂₅₆ ), (11w ₂₅₆ , 9w ₂₅₆ ), (11w ₂₅₆ , 7w ₂₅₆ ), (11w ₂₅₆ , 5w ₂₅₆ ), (11w ₂₅₆ , 3w ₂₅₆ ), (11w ₂₅₆ , w ₂₅₆ ), (11w ₂₅₆ ,-15w ₂₅₆ ), (11w ₂₅₆ ,-13w ₂₅₆ ), (11w ₂₅₆ ,-11w ₂₅₆ ), (11w ₂₅₆ ,-9w ₂₅₆ ), (11w ₂₅₆ ,-7w ₂₅₆ ), (11w ₂₅₆ ,-5w ₂₅₆ ), (11w ₂₅₆ ,-3w ₂₅₆ ), (11w ₂₅₆ ,-w ₂₅₆ ),

(9w ₂₅₆ , 15w ₂₅₆ ), (9w ₂₅₆ , 13w ₂₅₆ ), (9w ₂₅₆ , 11w ₂₅₆ ), (9w ₂₅₆ , 9w ₂₅₆ ), (9w ₂₅₆ , 7w ₂₅₆ ), (9w ₂₅₆ , 5w ₂₅₆ ), (9w ₂₅₆ , 3w ₂₅₆ ), (9w ₂₅₆ , w ₂₅₆ ),

(9w ₂₅₆ ,-15w ₂₅₆ ), (9w ₂₅₆ ,-13w ₂₅₆ ), (9w ₂₅₆ ,-11w ₂₅₆ ), (9w ₂₅₆ ,-9w ₂₅₆ ), (9w ₂₅₆ ,-7w ₂₅₆ ), (9w ₂₅₆ ,- 5w ₂₅₆ ), (9w ₂₅₆ ,-3w ₂₅₆ ), (9w ₂₅₆ ,-w ₂₅₆ ),

(7w ₂₅₆ , 15w ₂₅₆ ), (7w ₂₅₆ , 13w ₂₅₆ ), (7w ₂₅₆ , 11w ₂₅₆ ), (7w ₂₅₆ , 9w ₂₅₆ ), (7w ₂₅₆ , 7w ₂₅₆ ), (7w ₂₅₆ , 5w ₂₅₆ ), (7w ₂₅₆ , 3w ₂₅₆ ), (7w ₂₅₆ , w ₂₅₆ ),

(7w ₂₅₆ ,-15w ₂₅₆ ), (7w ₂₅₆ ,-13w ₂₅₆ ), (7w ₂₅₆ ,-11w ₂₅₆ ), (7w ₂₅₆ ,-9w ₂₅₆ ), (7w ₂₅₆ ,-7w ₂₅₆ ), (7w ₂₅₆ ,- 5w ₂₅₆ ), (7w ₂₅₆ ,-3w ₂₅₆ ), (7w ₂₅₆ ,-w ₂₅₆ ),

(5w ₂₅₆ , 15w ₂₅₆ ), (5w ₂₅₆ , 13w ₂₅₆ ), (5w ₂₅₆ , 11w ₂₅₆ ), (5w ₂₅₆ , 9w ₂₅₆ ), (5w ₂₅₆ , 7w ₂₅₆ ), (5w ₂₅₆ , 5w ₂₅₆ ), (5w ₂₅₆ , 3w ₂₅₆ ), (5w ₂₅₆ , w ₂₅₆ ),

(5w ₂₅₆ ,-15w ₂₅₆ ), (5w ₂₅₆ ,-13w ₂₅₆ ), (5w ₂₅₆ ,-11w ₂₅₆ ), (5w ₂₅₆ ,-9w ₂₅₆ ), (5w ₂₅₆ ,-7w ₂₅₆ ), (5w ₂₅₆ ,- 5w ₂₅₆ ), (5w ₂₅₆ ,-3w ₂₅₆ ), (5w ₂₅₆ ,-w ₂₅₆ ),

(3w ₂₅₆ , 15w ₂₅₆ ), (3w ₂₅₆ , 13w ₂₅₆ ), (3w ₂₅₆ , 11w ₂₅₆ ), (3w ₂₅₆ , 9w ₂₅₆ ), (3w ₂₅₆ , 7w ₂₅₆ ), (3w ₂₅₆ , 5w ₂₅₆ ), (3w ₂₅₆ , 3w ₂₅₆ ), (3w ₂₅₆ , w ₂₅₆ ), (3w ₂₅₆ ,-15w ₂₅₆ ), (3w ₂₅₆ ,-13w ₂₅₆ ), (3w ₂₅₆ ,-11w ₂₅₆ ), (3w ₂₅₆ ,-9w ₂₅₆ ), (3w ₂₅₆ ,-7w ₂₅₆ ), (3w ₂₅₆ ,-5w ₂₅₆ ), (3w ₂₅₆ ,-3w ₂₅₆ ), (3w ₂₅₆ ,-w ₂₅₆ ),

(w ₂₅₆ , 15w ₂₅₆ ), (w ₂₅₆ , 13w ₂₅₆ ), (w ₂₅₆ , 11w ₂₅₆ ), (w ₂₅₆ , 9w ₂₅₆ ), (w ₂₅₆ , 7w ₂₅₆ ), (w ₂₅₆ , 5w ₂₅₆ ), (w ₂₅₆ , 3w ₂₅₆ ), (w ₂₅₆ , w ₂₅₆ ), (w ₂₅₆ ,-15w ₂₅₆ ), (w ₂₅₆ ,-13w ₂₅₆ ), (w ₂₅₆ ,-11w ₂₅₆ ), (w ₂₅₆ ,-9w ₂₅₆ ), (w ₂₅₆ ,-7w ₂₅₆ ), (w ₂₅₆ ,-5w ₂₅₆ ), (w ₂₅₆ ,-3w ₂₅₆ ), (w ₂₅₆ ,-w ₂₅₆ ),

(-15w ₂₅₆ , 15w ₂₅₆ ), (-15w ₂₅₆ , 13w ₂₅₆ ), (-15w ₂₅₆ , 11w ₂₅₆ ), (-15w ₂₅₆ , 9w ₂₅₆ ), (-15w ₂₅₆ , 7w ₂₅₆ ), (-15w ₂₅₆ , 5w ₂₅₆ ), (-15w ₂₅₆ , 3w ₂₅₆ ),

(-15w ₂₅₆ , w ₂₅₆ ), (-15w ₂₅₆ ,-15w ₂₅₆ ), (-15w ₂₅₆ ,-13w ₂₅₆ ), (-15w ₂₅₆ ,-11w ₂₅₆ ), (-15w ₂₅₆ ,-9w ₂₅₆ ), ( -15w ₂₅₆ ,-7w ₂₅₆ ), (-15w ₂₅₆ ,-5w ₂₅₆ ), (-15w ₂₅₆ ,-3w ₂₅₆ ), (-15w ₂₅₆ ,-w ₂₅₆ ),

(-13w ₂₅₆ , 15w ₂₅₆ ), (-13w ₂₅₆ , 13w ₂₅₆ ), (-13w ₂₅₆ , 11w ₂₅₆ ), (-13w ₂₅₆ , 9w ₂₅₆ ), (-13w ₂₅₆ , 7w ₂₅₆ ), (-13w ₂₅₆ , 5w ₂₅₆ ), (-13w ₂₅₆ , 3w ₂₅₆ ), (-13w ₂₅₆ , w ₂₅₆ ),

(-13w ₂₅₆ ,-15w ₂₅₆ ), (-13w ₂₅₆ ,-13w ₂₅₆ ), (-13w ₂₅₆ ,-11w ₂₅₆ ), (-13w ₂₅₆ ,-9w ₂₅₆ ), (-13w ₂₅₆ ,-7w ₂₅₆ ), (-13w ₂₅₆ ,-5w ₂₅₆ ), (-13w ₂₅₆ ,-3w ₂₅₆ ), (-13w ₂₅₆ ,-w ₂₅₆ ),

(-11w ₂₅₆ , 15w ₂₅₆ ), (-11w ₂₅₆ , 13w ₂₅₆ ), (-11w ₂₅₆ , 11w ₂₅₆ ), (-11w ₂₅₆ , 9w ₂₅₆ ), (-11w ₂₅₆ , 7w ₂₅₆ ), (-11w ₂₅₆ , 5w ₂₅₆ ), (-11w ₂₅₆ , 3w ₂₅₆ ), (-11w ₂₅₆ , w ₂₅₆ ),

(-11w ₂₅₆ ,-15w ₂₅₆ ), (-11w ₂₅₆ ,-13w ₂₅₆ ), (-11w ₂₅₆ ,-11w ₂₅₆ ), (-11w ₂₅₆ ,-9w ₂₅₆ ), (-11w ₂₅₆ ,-7w ₂₅₆ ), (-11w ₂₅₆ ,-5w ₂₅₆ ), (-11w ₂₅₆ ,-3w ₂₅₆ ), (-11w ₂₅₆ ,-w ₂₅₆ ),

(-9w ₂₅₆ , 15w ₂₅₆ ), (-9w ₂₅₆ , 13w ₂₅₆ ), (-9w ₂₅₆ , 11w ₂₅₆ ), (-9w ₂₅₆ , 9w ₂₅₆ ), (-9w ₂₅₆ , 7w ₂₅₆ ), (-9w ₂₅₆ , 5w ₂₅₆ ), (-9w ₂₅₆ , 3w ₂₅₆ ), (-9w ₂₅₆ , w ₂₅₆ ),

(-9w ₂₅₆ ,-15w ₂₅₆ ), (-9w ₂₅₆ ,-13w ₂₅₆ ), (-9w ₂₅₆ ,-11w ₂₅₆ ), (-9w ₂₅₆ ,-9w ₂₅₆ ), (-9w ₂₅₆ ,-7w ₂₅₆ ), (-9w ₂₅₆ ,-5w ₂₅₆ ), (-9w ₂₅₆ ,-3w ₂₅₆ ), (-9w ₂₅₆ ,-w ₂₅₆ ),

(-7w ₂₅₆ , 15w ₂₅₆ ), (-7w ₂₅₆ , 13w ₂₅₆ ), (-7w ₂₅₆ , 11w ₂₅₆ ), (-7w ₂₅₆ , 9w ₂₅₆ ), (-7w ₂₅₆ , 7w ₂₅₆ ), (-7w ₂₅₆ , 5w ₂₅₆ ), (-7w ₂₅₆ , 3w ₂₅₆ ), (-7w ₂₅₆ , w ₂₅₆ ),

(-7w ₂₅₆ ,-15w ₂₅₆ ), (-7w ₂₅₆ ,-13w ₂₅₆ ), (-7w ₂₅₆ ,-11w ₂₅₆ ), (-7w ₂₅₆ ,-9w ₂₅₆ ), (-7w ₂₅₆ ,-7w ₂₅₆ ), (-7w ₂₅₆ ,-5w ₂₅₆ ), (-7w ₂₅₆ ,-3w ₂₅₆ ), (-7w ₂₅₆ ,-w ₂₅₆ ),

(-5w ₂₅₆ , 15w ₂₅₆ ), (-5w ₂₅₆ , 13w ₂₅₆ ), (-5w ₂₅₆ , 11w ₂₅₆ ), (-5w ₂₅₆ , 9w ₂₅₆ ), (-5w ₂₅₆ , 7w ₂₅₆ ), (-5w ₂₅₆ , 5w ₂₅₆ ), (-5w ₂₅₆ , 3w ₂₅₆ ), (-5w ₂₅₆ , w ₂₅₆ ),

(-5w ₂₅₆ ,-15w ₂₅₆ ), (-5w ₂₅₆ ,-13w ₂₅₆ ), (-5w ₂₅₆ ,-11w ₂₅₆ ), (-5w ₂₅₆ ,-9w ₂₅₆ ), (-5w ₂₅₆ ,-7w ₂₅₆ ), (-5w ₂₅₆ ,-5w ₂₅₆ ), (-5w ₂₅₆ ,-3w ₂₅₆ ), (-5w ₂₅₆ ,-w ₂₅₆ ),

(-3w ₂₅₆ , 15w ₂₅₆ ), (-3w ₂₅₆ , 13w ₂₅₆ ), (-3w ₂₅₆ , 11w ₂₅₆ ), (-3w ₂₅₆ , 9w ₂₅₆ ), (-3w ₂₅₆ , 7w ₂₅₆ ), (-3w ₂₅₆ , 5w ₂₅₆ ), (-3w ₂₅₆ , 3w ₂₅₆ ), (-3w ₂₅₆ , w ₂₅₆ ),

(-3w ₂₅₆ ,-15w ₂₅₆ ), (-3w ₂₅₆ ,-13w ₂₅₆ ), (-3w ₂₅₆ ,-11w ₂₅₆ ), (-3w ₂₅₆ ,-9w ₂₅₆ ), (-3w ₂₅₆ ,-7w ₂₅₆ ), (-3w ₂₅₆ ,-5w ₂₅₆ ), (-3w ₂₅₆ ,-3w ₂₅₆ ), (-3w ₂₅₆ ,-w ₂₅₆ ),

(-w ₂₅₆ , 15w ₂₅₆ ), (-w ₂₅₆ , 13w ₂₅₆ ), (-w ₂₅₆ , 11w ₂₅₆ ), (-w ₂₅₆ , 9w ₂₅₆ ), (-w ₂₅₆ , 7w ₂₅₆ ), (-w ₂₅₆ , 5w ₂₅₆ ), (-w ₂₅₆ , 3w ₂₅₆ ), (-w ₂₅₆ , w ₂₅₆ ),

(-w ₂₅₆ ,-15w ₂₅₆ ), (-w ₂₅₆ ,-13w ₂₅₆ ), (-w ₂₅₆ ,-11w ₂₅₆ ), (-w ₂₅₆ ,-9w ₂₅₆ ), (-w ₂₅₆ ,-7w ₂₅₆ ), (-w ₂₅₆ ,-5w ₂₅₆ ), (-w ₂₅₆ ,-3w ₂₅₆ ), (-w ₂₅₆ ,-w ₂₅₆ )

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q. Note that the relationship between the sets of b0, 1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 20 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s1(t) (s1(i))) is 256QAM, and the baseband signal 505B (s2(t) (s2()) Assuming that the modulation method of i))) is 64QAM, the configuration of the precoding matrix will be described.

At this time, the average power of the baseband signal 505A (s1(t)(s1(i))) output from the mapping unit 504 of FIGS. 5 to 7 and the baseband signal 505B (s2(t)( s2(i))) It is common to make the average power equal.

Accordingly, the following relational expression holds for the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above.

In the formulas (S224) and (S225), z is a real number larger than 0. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The precoding matrix F when performing the operation of

The configuration of (Example 4-1) to (Example 4-8) will be described in detail below.

(Example 4-1)

In the case of any one of <1> to <5> described above, it is assumed that the precoding matrix F is set to any of the following.

or,

or,

or,

In the formulas (S227), (S228), (S229), and (S230), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero).

And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of α for obtaining the reception quality of α are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

However, the modulation method of the baseband signal 505A (s1(t)(s1(i))) is 256QAM, and the modulation method of the baseband signal 505B (s2(t)(s2(i))) is 64QAM. do. Therefore, when precoding (and phase change, power change) is performed as described above and the modulated signal is transmitted from each antenna, the antenna ( The total number of bits transmitted by the symbols transmitted from 808A) and the symbols transmitted from the antenna 808B is 14 bits of the sum of 6 bits (by using 64QAM) and 8 bits (by using 256QAM).

Input bits for mapping of 64QAM to b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} 4, and input bits for mapping of 256QAM to b _0, When ₂₅₆ , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} , Formula (S231), Formula (S232), Even if it is set to either α of the formulas (S233) and (S234),

For signal z ₁ (t)(z ₁ (i)),

(b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0) ) from the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1) exists in the in-phase I-orthogonal Q plane. ,

Similarly, for the signal z ₂ (t) (z ₂ (i)),

(b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0) From the signal point corresponding to ) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1) exists in the in-phase I-orthogonal Q plane. .

In the previous explanation,

"Paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device Expressions (S231) to (S234) have been described as "values of α for obtaining reception quality", but this point will be described.

For signal z ₂ (t)(z ₂ (i)),

(b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ) is (0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0, 0) ) from the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1, 1) so that the signal point corresponding to (1, 1, 1, 1, 1, 1) exists in the in-phase I-orthogonal Q plane. However, these 214 = 16384 signal points do not overlap in the in-phase I-orthogonal Q plane, and preferably exist as 16384 signal points.

Because, when the modulated signal transmitted from the antenna transmitting the signal z ₁ (t) (z ₁ (i)) does not reach the receiving device, the receiving device uses the signal z ₂ (t)(z2(i)) In this case, detection and error correction decoding are performed, but in this case, in order for the receiving device to obtain high data reception quality, "no overlapping, 16384 signal points" is sufficient. Set the precoding matrix F to any one of formulas (S227), (S228), (S229), and (S230), and formulas (S231), (S232), (S233), (S234) and Similarly, when α is set, (b _{0, 64,} b _{1 , 64} , b _{2 , 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7, 256} ), the arrangement of the signal points existing in the first upper limit is the same as in FIG. 37 , the arrangement of the signal points existing in the second upper limit is the same as in FIG. 38 , and the signal present in the third upper limit The arrangement of dots is the same as in FIG. 39, and the arrangement of signal points existing in the fourth upper limit is the same as in FIG. 40. 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 37, 38, 39, and 40, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 37 , the rightmost bottom of FIG. 40 , the rightmost top of FIG. 38 , and the leftmost bottom of FIG. 39 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S227), Equation (S228), Equation (S229), Equation (S230), Equation (S231), Equation (S232), Equation (S233), Equation (S234) When α is set as follows, (b _{0 , 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6, 256} , b _{7 , 256} ), the arrangement of the signal points existing in the first upper limit is the same as in FIG. 41 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points is the same as that of FIG. 43, and the arrangement of the signal points existing in the fourth upper limit is the same as that of FIG. In addition, in Figs. 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 41, 42, 43, and 44, the signal points do not overlap, and it can be seen that there are 16,384 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points in FIGS. 37, 38, 39, and 40 is D ₂ , and the minimum Euclidean distance of 16384 signal points in FIGS. 41, 42, 43 and 44 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 4-2)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S224) and (S225) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In addition, in the formulas (S235) and (S237), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in the formulas (S239), (S240), (S241), and (S242), tan-1(x) is an inverse trigonometric function (the inverse function of that which appropriately limits the domain of the trigonometric function) ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of Equation (S235), Equation (S236), Equation (S237), Equation (S238), Equation (S239), Equation (S240), Equation (S241), Equation (S242) and When θ is set in _the same way, if it is considered as described above, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 37 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 39, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 40 . 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 37, 38, 39, and 40, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 37 , the rightmost bottom of FIG. 40 , the rightmost top of FIG. 38 , and the leftmost bottom of FIG. 39 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S235), Equation (S236), Equation (S237), Equation (S238), Equation (S239), Equation (S240), Equation (S241), Equation (S242) When θ is set as shown above, if it is considered as described above, in the signal u ₁ (t)(u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of the signal points present in the third upper limit is the same as in FIG. 43, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 44 . In addition, in Figs. 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 41, 42, 43, and 44, the signal points do not overlap, and it can be seen that there are 16,384 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points in FIGS. 37, 38, 39, and 40 is D ₂ , and the minimum Euclidean distance of 16384 signal points in FIGS. 41, 42, 43 and 44 is D ₁ do it with Then, D1<D2 holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 4-3)

Equations (S224) and (S225) are established with respect to the coefficient w ₆₄ described in the mapping method of 64QAM described above and the coefficient w ₂₅₆ described in the mapping method of 256QAM described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S244), (S245), (S246), and (S247), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S244), (S245), (S246), and (S247), and formulas (S248), (S249), (S250), and (S251) When α is set in the same way, if it is considered as described above _, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 45 , the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 47, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 48. 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from FIGS. 45, 46, 47, and 48, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 45 , the rightmost bottom of FIG. 48 , the rightmost top of FIG. 46 , and the leftmost bottom of FIG. 47 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S244), Equation (S245), Equation (S246), Equation (S247), Equation (S248), Equation (S249), Equation (S250), Equation (S251) When α is set as shown above, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points existing in the third upper limit is the same as in FIG. 51 , and the arrangement of signal points existing in the fourth upper limit is as shown in FIG. 52 . Further, in Figs. 49, 50, 51 and 52, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 49, 50, 51, and 52, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 45, 46, 47, and 48 is D ₂ , and the minimum Euclidean distance of 16384 signal points of FIGS. 49, 50, 51 and 52 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 4-4)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S224) and (S225) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S252) and (S254), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in the formulas (S256), (S257), (S258), and (S259), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain). ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

The precoding matrix F is set to any one of formulas (S252), (S253), (S254), and (S255), and with formulas (S256), (S257), (S258), and (S259) When θ is set in _the same way, if it is considered as described above, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 45 , the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 47, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 48. 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from FIGS. 45, 46, 47, and 48, the signal points do not overlap on the in-phase I-orthogonal Q plane, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 45 , the rightmost bottom of FIG. 48 , the rightmost top of FIG. 46 , and the leftmost bottom of FIG. 47 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of Equation (S252), Equation (S253), Equation (S254), Equation (S255), Equation (S256), Equation (S257), Equation (S258), Equation (S259) When θ is set as shown above, if it is considered as described above, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points present in the upper limit 3 is the same as that of FIG. 51, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 52. Further, in Figs. 49, 50, 51 and 52, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 49, 50, 51, and 52, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 45, 46, 47, and 48 is D ₂ , and the minimum Euclidean distance of 16384 signal points of FIGS. 49, 50, 51 and 52 is D ₁ do it with Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 4-5)

Equations (S224) and (S225) are established with respect to the coefficient w ₆₄ described in the mapping method of 64QAM described above and the coefficient w ₂₅₆ described in the mapping method of 256QAM described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S261), (S262), (S263), and (S264), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S261), (S262), (S263), and (S264), and formulas (S265), (S266), (S267), and (S268) When α is set in the same way, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 21 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 23, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 24. In addition, in Figs. 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 21, 22, 23, and 24, the signal points do not overlap and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 21 , the rightmost bottom of FIG. 24 , the rightmost top of FIG. 22 , and the leftmost bottom of FIG. 23 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S261), (S262), (S263), and (S264), and formulas (S265), (S266), (S267), (S268) When α is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b ₁ ) _{, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of the signal points present in the third upper limit is as shown in FIG. 27, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 28. 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 25, 26, 27, and 28, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 21, 22, 23, and 24 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 25, 26, 27, and 28 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 4-6)

Next, with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S224) and (S225) are established,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In addition, in the formulas (S269) and (S271), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in formulas (S273), (S274), (S275), and (S276), tan-1(x) is an inverse trigonometric function (the inverse function of a trigonometric function having an appropriately limited domain). ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S269), (S270), (S271), and (S272), and formulas (S273), (S274), (S275), and (S276) When θ is set in the same way, if it is considered as described above, in the signal u ₁ (t)(u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 21 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is as shown in FIG. 23, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 24. In addition, in Figs. 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 21, 22, 23, and 24, the signal points do not overlap and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of FIG. 21 , the rightmost bottom of FIG. 24 , the rightmost top of FIG. 22 , and the leftmost bottom of FIG. 23 . The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S269), (S270), (S271), and (S272), and formulas (S273), (S274), (S275), (S276) When θ is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of the signal points present in the third upper limit is as shown in FIG. 27, and the arrangement of the signal points present in the fourth upper limit is as shown in FIG. 28. 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 25, 26, 27, and 28, the signal points do not overlap and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 21, 22, 23, and 24 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 25, 26, 27, and 28 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 4-7)

Equations (S224) and (S225) are established with respect to the coefficient w ₆₄ described in the mapping method of 64QAM described above and the coefficient w ₂₅₆ described in the mapping method of 256QAM described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

In the formulas (S278), (S279), (S280), and (S281), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

At this time, the receiving apparatus thinks about the value of α for obtaining good data reception quality.

Paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving apparatus receives good data The values of α for obtaining quality are as follows.

When α is a real number:

or,

When α is an imaginary number:

or,

Set the precoding matrix F to any one of formulas (S278), (S279), (S280), and (S281), and formulas (S282), (S283), (S284), (S285) and When α is set in the same way, when considered as described above, in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 29 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is the same as in FIG. 31, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 32 . Further, in Figs. 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 29, 30, 31, and 32, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of Fig. 29, the rightmost bottom of Fig. 32, the rightmost top of Fig. 30, and the leftmost bottom of Fig. 31 The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of formulas (S278), (S279), (S280), and (S281), and formulas (S282), (S283), (S284), (S285) When α is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b ₁ ) _{, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points present in the third upper limit is the same as in FIG. 35 , and the arrangement of signal points present in the fourth upper limit is as shown in FIG. 36 . 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 33, 34, 35, and 36, the signal points do not overlap, and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 29, 30, 31, and 32 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 33, 34, 35 and 36 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 4-8)

Equations (S224) and (S225) are established with respect to the coefficient w ₆₄ described in the mapping method of 64QAM described above and the coefficient w ₂₅₆ described in the mapping method of 256QAM described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Consider a case where the precoding matrix F when performing the operation of is set to one of the following.

or,

or,

or,

Further, in the formulas (S286) and (S288), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

Also, in the formulas (S290), (S291), (S292), and (S293), tan-1(x) is an inverse trigonometric function (the inverse function of that which appropriately limits the domain of the trigonometric function) ) and

becomes this Moreover, you may describe "tan-1(x)" as "Tan-1(x)", "arctan(x)", and "Arctan(x)". And N is an integer.

Set the precoding matrix F to any one of formulas (S286), (S287), (S288), and (S289), and formulas (S290), (S291), (S292), (S293) and When θ is set in the same way, if it is considered as described above, in the signal u ₁ (t)(u ₁ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5, 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. 29 , and the arrangement of the signal points present in the second upper limit is the same as in FIG. The arrangement of the signal points present in the upper limit 3 is the same as in FIG. 31, and the arrangement of the signal points present in the fourth upper limit is the same as in FIG. 32 . Further, in Figs. 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 29, 30, 31, and 32, the signal points do not overlap, and it can be seen that there are 16,384 signal points. In addition, among 16384 signal points in the in-phase I-orthogonal Q plane, the rightmost top of Fig. 29, the rightmost bottom of Fig. 32, the rightmost top of Fig. 30, and the leftmost bottom of Fig. 31 The Euclidean distances between 16380 signal points except for 4 of the signal points that are closest to each other are equal to each other. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S286), (S287), (S288), and (S289), and formulas (S290), (S291), (S292), (S293) When θ is set as shown above, when considered as described above, in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 in the in-phase I-orthogonal Q plane, (b _{0, 64,} b _{1 , 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} , b _{0, 256} , b _{1, 256} , b _{2, 256} , b _{3, 256} , b _{4, 256} , b _{5 , 256} , b _{6 , 256} , b _{7 , 256} ) among the signal points corresponding to the first upper limit, the arrangement of the signal points present in the first upper limit is the same as in FIG. The arrangement of signal points present in the third upper limit is the same as in FIG. 35 , and the arrangement of signal points present in the fourth upper limit is as shown in FIG. 36 . 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, "●" is the signal point, and "Δ" is the origin (0).

As can be seen from Figs. 33, 34, 35, and 36, the signal points do not overlap, and it can be seen that there are 1024 signal points. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the minimum Euclidean distance of 16384 signal points of FIGS. 29, 30, 31, and 32 is D ₁ , and the minimum Euclidean distance of 16384 signal points of FIGS. 33, 34, 35 and 36 is D ₂ do it with Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 4 - Supplement)

In (Example 4-1) to (Example 4-8), examples of values of α and examples of values of θ that are likely to obtain high data reception quality are shown. However, the values of α and θ are Even if it is not a value, high data reception quality can be obtained by satisfying the condition shown in the configuration example R1.

(variation example)

Next, a precoding method modified from (Example 1) to (Example 4) will be described. In Fig. 5, the baseband signal 511A (z ₁ (t) (z ₁ (i))) and the base band signal 511B (z ₂ (t) (z ₂ (i))) are expressed by any of the following equations Think of a case where

However, θ11(i) and θ21(i) are functions of i (time or frequency), λ is a fixed value, α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

And as a modification of (Example 1), the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 16QAM, the baseband signal 505B (s ₂ (t) (s ₂ ( i)))) is set to 64QAM, and equations (S11) and (S12) are established for the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above. do,

In α of the formulas (S295) and (S296),

Any one of formula (S18), formula (S19), formula (S20), and formula (S21) is used, and Q ₁ >Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formula (S35), formula (S36), formula (S37), and formula (S38) is used, and Q ₁ >Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formula (S52), formula (S53), formula (S54), and formula (S55) is used, and Q ₁ < Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formula (S69), formula (S70), formula (S71), and formula (S72) is used, and Q ₁ <Q ₂ ,

The same effect as that of the sea-island (Example 1) can be obtained.

As a modification of (Example 2), the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the baseband signal 505B (s ₂ (t) (s ₂ (i)) )))), with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above, equations (S82) and (S83) are established, ,

In α of the formulas (S295) and (S296),

Any one of formula (S89), formula (S90), formula (S91), and formula (S92) is used, and Q ₁ < Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formula (S106), formula (S107), formula (S108), and formula (S109) is used, and Q ₁ < Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formula (S123), formula (S124), formula (S125), and formula (S126) is used, and Q ₁ >Q ₂ , or

or,

In α of the formulas (S295) and (S296),

Using any one of formula (S140), formula (S141), formula (S142), and formula (S143), and Q ₁ >Q ₂ ,

Even if it is set as the sea-island (Example 2), the same effect can be acquired.

As a modification of (Example 3), the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the baseband signal 505B (s ₂ (t) (s ₂ (i)) )))) is 256QAM, and with respect to the coefficient w ₆₄ described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, equations (S153) and (S154) are established, ,

In α of the formulas (S295) and (S296),

Formula (S160), Formula (S161), Formula (S162), Formula (S163), using any one of, and, Q ₁ >Q ₂ , or

or,

In α of the formulas (S295) and (S296),

Formula (S177), Formula (S178), Formula (S179), Formula (S180), any one of, and Q ₁ >Q ₂ , or

or,

In α of the formulas (S295) and (S296),

Formula (S194), Formula (S195), Formula (S196), Formula (S197), any one of, and Q ₁ <Q ₂ ,

or,

In α of the formulas (S295) and (S296),

Any one of formulas (S211), (S212), (S213), and (S214) is used, and Q ₁ <Q ₂ ,

The same effect as that of the sea-island (Example 3) can be obtained.

As a modification of (Example 4), the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 256QAM, and the baseband signal 505B (s ₂ (t) (s ₂ (i)) ))) as the modulation method of 64QAM, with respect to the coefficient w64 described in the 64QAM mapping method described above and the coefficient w ₂₅₆ described in the 256QAM mapping method described above, Equations (S224) and (S225) are established,

In α of the formulas (S295) and (S296),

Any one of formula (S231), formula (S232), formula (S233), and formula (S234) is used, and Q ₁ <Q ₂ ,

In α of the formulas (S295) and (S296),

Any one of formula (S248), formula (S249), formula (S250), and formula (S251) is used, and Q ₁ < Q ₂ ,

In α of the formulas (S295) and (S296),

Any one of formula (S265), formula (S266), formula (S267), and formula (S268) is used, and Q ₁ >Q ₂ , or

In α of the formulas (S295) and (S296),

Any one of formula (S282), formula (S283), formula (S284), and formula (S285) is used, and Q ₁ >Q ₂ ,

The same effect as that of the sea-island (Example 4) can be obtained.

In addition, in the above-described modified example, examples of values of α and examples of values of θ that are likely to obtain high data reception quality are shown. By satisfying the condition shown in R1, high data reception quality can be obtained.

Next, examples different from (Example 1) to (Example 4) and their modification examples will be described.

(Example 5)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 16QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 64QAM, for example, any precoding and/or power change of equations (S2), (S3), (S4), (S5), and (S8) is performed. An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 16QAM will be described. 10 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 10, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 10 is the signal point) in the in-phase I-orthogonal Q plane are (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w16, -w ₁₆ ), (3w ₁₆ ,-3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (- w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ ,-3w ₁₆ ) (w ₁₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 1001 in FIG. 10, and the in-phase component of the baseband signal after mapping is I , if the orthogonal component is Q, (I, Q)=(3w ₁₆ , 3w ₁₆ ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in Fig. 10) (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w16,-w ₁₆ ), (3w ₁₆ , -3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (-w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), ( -w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ , -3w ₁₆ ), values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000-1111) and the coordinates of the signal points in 16QAM is not limited to FIG. 10 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 16QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

The 64QAM mapping method will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q. The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. If the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (7w ₆₄ , -3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), and (-7w ₆₄ , -7w ₆₄ ), the values of sets 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown. Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . Then, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s1(t) or s2(t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 16QAM, and the baseband signal 505B (s ₂ (t)) Assuming that the modulation method of (s ₂ (i))) is 64QAM, the structure of the precoding matrix will be described.

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₁ (i))) which is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( t)(s ₂ (i))) It is common to make the average power equal.

Accordingly, Equations (S11) and (S12) hold for the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above. In the formulas (S11) and (S12), z is a real number larger than 0. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The configuration of the precoding matrix F and the relationship between Q1 and Q2 at the time of executing the operation of ? will be described below.

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Any one of Expressions (S22), (S23), (S24), and (S25) is considered as the precoding matrix F when performing the calculation of .

In the formulas (S22) and (S24), β may be either a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signals z ₁ (t) (z ₁ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, let N be an integer.

Set the precoding matrix F to any one of formulas (S22), (S23), (S24), and (S25), and formulas (S297), (S298), (S299), and (S300) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) Arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 is as shown in FIG. In Fig. 55, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 55, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And set the precoding matrix F to any one of Equation (S22), Equation (S23), Equation (S24), Equation (S25), Equation (S297), Equation (S298), Equation (S299), Equation (S300) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 56 . In Fig. 56, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 56, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

Then, the minimum Euclidean distance of 1024 signal points in FIG. 55 is D ₁ , and the minimum Euclidean distance of 1024 signal points in FIG. 56 is D ₂ . Then, D ₁ >D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ >Q ₂ holds. .

(Example 5 - Supplement)

In the example described above, an example of a value of θ that is likely to obtain high data reception quality is shown, but even if the value of θ is not these values, it is possible to obtain high data reception quality by satisfying the conditions shown in Configuration Example R1. can

(Example 6)

Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s ₁ (t) (s ₁ (i)) is 64QAM, and s ₂ (t) (s ₂ (i)) is When the modulation method to obtain is 16QAM, for example, any precoding and/or power change of equations (S2), (S3), (S4), (S5), and (S8) is performed. An example of the configuration of the precoding matrix F and the conditions for power change will be described.

First, a mapping method of 16QAM will be described. 10 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 10, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 10 is the signal point) in the in-phase I-orthogonal Q plane are (3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w16, -w ₁₆ ), (3w ₁₆ ,-3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (- w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (-3w ₁₆ ,-3w ₁₆ ) (w ₁₆ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 1001 in FIG. 10, and the in-phase component of the baseband signal after mapping is I , if the orthogonal component is Q, (I, Q)=(3w ₁₆ , 3w ₁₆ ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in FIG. 10) ((3w ₁₆ , 3w ₁₆ ), (3w ₁₆ , w ₁₆ ), (3w16,-w ₁₆ ), (3w ₁₆ , -3w ₁₆ ), (w ₁₆ , 3w ₁₆ ), (w ₁₆ , w ₁₆ ), (w ₁₆ ,-w ₁₆ ), (w ₁₆ ,-3w ₁₆ ), (-w ₁₆ , 3w ₁₆ ), (-w ₁₆ , w ₁₆ ), (-w ₁₆ ,-w ₁₆ ), (-w ₁₆ ,-3w ₁₆ ), (-3w ₁₆ , 3w ₁₆ ), (-3w ₁₆ , w ₁₆ ), (-3w ₁₆ ,-w ₁₆ ), (- The values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown just below 3w ₁₆ , -3w ₁₆ ). '), each coordinate in the in-phase I-quadrature Q plane becomes the in-phase component I and the quadrature component Q of the baseband signal after mapping, and a set of b0, b1, b2, b3 at 16QAM ) and the coordinates of the signal points are not limited to Fig. 10. And the values of complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in case of 16QAM) are the baseband values of Figs. signal s ₁ (t) or s ₂ (t).

The 64QAM mapping method will be described. 11 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. Moreover, in Fig. 11, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I and the vertical axis denotes Q.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 11 are signal points) in the in-phase I-orthogonal Q plane are,

(7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ ,-w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ ,-5w ₆₄ ), (-7w ₆₄ ,-7w ₆₄ )

(w ₆₄ is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 1101 in FIG. If the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7w ₆₄ , 7w ₆₄ ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in FIG. 11) (7w ₆₄ , 7w ₆₄ ), (7w ₆₄ , 5w ₆₄ ), (7w ₆₄ , 3w ₆₄ ), (7w ₆₄ , w ₆₄ ), (7w ₆₄ , -w ₆₄ ), (7w ₆₄ ,-3w ₆₄ ), (7w ₆₄ ,-5w ₆₄ ), (7w ₆₄ ,-7w ₆₄ )

(5w ₆₄ , 7w ₆₄ ), (5w ₆₄ , 5w ₆₄ ), (5w ₆₄ , 3w ₆₄ ), (5w ₆₄ , w ₆₄ ), (5w ₆₄ ,-wv), (5w ₆₄ ,-3wv), (5w ₆₄ ,-5w ₆₄ ), (5w ₆₄ ,-7w ₆₄ )

(3w ₆₄ , 7w ₆₄ ), (3w ₆₄ , 5w ₆₄ ), (3w ₆₄ , 3w ₆₄ ), (3w ₆₄ , w ₆₄ ), (3w ₆₄ ,-w ₆₄ ), (3w ₆₄ ,-3wv), ( 3w ₆₄ ,-5w ₆₄ ), (3w ₆₄ ,-7w ₆₄ )

(w ₆₄ , 7w ₆₄ ), (w ₆₄ , 5w ₆₄ ), (w ₆₄ , 3w ₆₄ ), (w ₆₄ , w ₆₄ ), (w ₆₄ ,-w ₆₄ ), (w ₆₄ ,-3w ₆₄ ), (w ₆₄ ,-5w ₆₄ ), (w ₆₄ ,-7w ₆₄ )

(-w ₆₄ , 7w ₆₄ ), (-w ₆₄ , 5w ₆₄ ), (-w ₆₄ , 3w ₆₄ ), (-w ₆₄ , w ₆₄ ), (-w ₆₄ ,-w ₆₄ ), (-w ₆₄ ) ,-3w ₆₄ ), (-w ₆₄ ,-5w ₆₄ ), (-w ₆₄ ,-7w ₆₄ )

(-3w ₆₄ , 7w ₆₄ ), (-3w ₆₄ , 5w ₆₄ ), (-3w ₆₄ , 3w ₆₄ ), (-3w ₆₄ , w ₆₄ ), (-3w ₆₄ ,-w ₆₄ ), (-3w ₆₄ ) ,-3w ₆₄ ), (-3w ₆₄ ,-5w ₆₄ ), (-3w ₆₄ ,-7w ₆₄ )

(-5w ₆₄ , 7w ₆₄ ), (-5w ₆₄ , 5w ₆₄ ), (-5w ₆₄ , 3w ₆₄ ), (-5w ₆₄ , w ₆₄ ), (-5w ₆₄ ,-w ₆₄ ), (-5w ₆₄ ) ,-3w ₆₄ ), (-5w ₆₄ ,-5w ₆₄ ), (-5w ₆₄ ,-7w ₆₄ )

(-7w ₆₄ , 7w ₆₄ ), (-7w ₆₄ , 5w ₆₄ ), (-7w ₆₄ , 3w ₆₄ ), (-7w ₆₄ , w ₆₄ ), (-7w ₆₄ ,-w ₆₄ ), (-7w ₆₄ ) ,-3w ₆₄ ), (-7w ₆₄ , -5w ₆₄ ), (-7w ₆₄ , -7w ₆₄ ), the sets b0, b1, b2, b3, b4, b5 set values from 000000 to 111111 are shown. . Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 11 . In addition, values obtained by complex representations of the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signals s ₁ (t) or s ₂ (t) of FIGS. 5 to 7 .

In this example, in Figs. 5 to 7, the modulation method of the baseband signal 505A (s ₁ (t) (s ₁ (i))) is 64QAM, and the baseband signal 505B (s ₂ (t)) Assuming that the modulation method of (s ₂ (i))) is 16QAM, the structure of the precoding matrix will be described.

At this time, the average power of the baseband signal 505A (s ₁ (t) (s ₁ (i))) which is the output of the mapping unit 504 of FIGS. 5 to 7 and the base band signal 505B (s ₂ ( t)(s ₂ (i))) It is common to make the average power equal. Therefore, Equations (82) and (83) hold for the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above. In the formulas (S82) and (S83), z is a real number greater than zero. and,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

The configuration of the precoding matrix F and the relationship between Q1 and Q2 at the time of executing the operation of ? will be described below.

Equations (S11) and (S12) are established with respect to the coefficient w ₁₆ described in the 16QAM mapping method described above and the coefficient w ₆₄ described in the 64QAM mapping method described above,

<1> When P ₁ ² =P ₂ ² in formula (S2)

<2> When P ₁ ² =P ₂ ² in formula (S3)

<3> When P ₁ ² =P ₂ ² in formula (S4)

In case of <4> formula (S5)

In case of <5> formula (S8)

Any one of Expressions (S93), (S94), (S95), and (S96) is considered as the precoding matrix F when performing the calculation of .

In the formulas (S93) and (S95), β may be a real number or an imaginary number. However, β is not 0 (zero).

At this time, the receiving apparatus thinks about the value of ? for obtaining good data reception quality.

First, paying attention to the signal z ₂ (t) (z ₂ (i)) in the formulas (S2), (S3), (S4), (S5), and (S8), the receiving device can provide good data The values of θ for obtaining the reception quality of are as follows.

or,

or,

or,

In addition, let N be an integer.

The precoding matrix F is set to any one of formulas (S93), (S94), (S95), and (S96), and with formulas (S301), (S302), (S303), and (S304) If θ is set in the same way, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1) , 1, 1, 1, 1, 1, 1) arrangement of signal points in the in-phase I-orthogonal Q plane in the signal u ₂ (t) (u ₂ (i)) described in the configuration example R1. is as shown in FIG. In Fig. 55, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 55, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

And the precoding matrix F is set to any one of formulas (S93), (S94), (S95), and (S96), and formulas (S301), (S302), (S303), (S304) When θ is set as shown above, (b _{0, 16} , b _{1, 16} , b _{2, 16} , b _{3, 16} , b _{0, 64,} b _{1, 64} , b _{2, 64} , b _{3, 64} , b _{4, 64,} b _{5, 64} ) from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) of the signal point of the in-phase I-orthogonal Q plane in the signal u ₁ (t) (u ₁ (i)) described in the configuration example R1 The arrangement is as shown in FIG. 56 . In Fig. 56, the horizontal axis is I, the vertical axis is Q, and "-" is the signal point.

As can be seen from Fig. 56, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility that high reception quality can be obtained in the receiving apparatus.

In addition, the minimum Euclidean distance of 1024 signal points in FIG. 55 is D ₂ , and the minimum Euclidean distance of 1024 signal points in FIG. 56 is D ₁ . Then, D ₁ < D ₂ holds. Therefore, in the case of Q ₁ ≠ Q ₂ in the formulas (S2), (S3), (S4), (S5), and (S8) from the structural example R1, it is sufficient if Q ₁ < Q ₂ holds. .

(Example 6 - Supplement)

In the example described above, an example of a value of θ that is likely to obtain high data reception quality is shown, but even if the value of θ is not these values, it is possible to obtain high data reception quality by satisfying the conditions shown in Configuration Example R1. can

Next, the operation of the receiving device when the transmitting device transmits a modulated signal will be described using (Example 1) to (Example 4) and its modifications, (Example 5) and (Example 6).

53 shows the relationship between the transmitting antenna and the receiving antenna. It is assumed that the modulated signal #1 (S4901A) is transmitted from the transmission antenna #1 (S4902A) of the transmitter, and the modulated signal #1 (S4901B) is transmitted from the antenna #1 (S4902B).

In addition, the receiving antenna #1 (S4903X) and the receiving antenna #1 (S4903Y) of the receiving device receive the modulated signal transmitted by the transmitting device (the receiving signal (S490X) and the receiving signal (S4904Y) are obtained), but at this time, the transmission Let the propagation coefficient of antenna #1 (S4902A) to receive antenna #1 (S4903X) be h ₁₁ (t), and the propagation coefficient from transmit antenna #1 (S4902A) to receive antenna #1 (S4903Y) is h ₂₁ (t) Let h ₁₂ (t) be the propagation coefficient of the receiving antenna #1 (S4903X) from the transmitting antenna #1 (S4902B), and h _{22 Let} (t) be (t is time).

54 is an example of the configuration of a receiving apparatus. The radio unit 5402X receives the received signal 5401X received from the receiving antenna #1 (S4903X) as an input, and outputs the signal 5403X by performing processing such as amplification and frequency conversion.

The signal processing unit 5404X obtains a baseband signal 5405X by performing processing such as a Fourier transform, a parallel serial transform, or the like, if the OFDM method is used, for example. At this time, it is assumed that the baseband signal 5405X is expressed as r' ₁ (t).

The radio unit 5402Y receives the received signal 5401Y received by the reception antenna #2 (S4903Y) as an input, and outputs a signal 5403Y by processing such as amplification and frequency conversion.

The signal processing unit 5404Y obtains a baseband signal 5405Y by performing processing such as a Fourier transform, a parallel serial transform, or the like, if the OFDM method is used, for example. At this time, it is assumed that the baseband signal 5405Y is expressed as r' ₂ (t).

The channel estimator 5406X receives the baseband signal 5405X as an input, performs channel estimation (estimation of propagation coefficient) from the pilot symbols in the frame configuration shown in Fig. 9, for example, and outputs the channel estimation signal 5407X. do. In addition, it is assumed that the channel estimation signal 5407X is an estimation signal of h ₁₁ (t) and is denoted by h' ₁₁ (t).

The channel estimator 5408X receives the baseband signal 5405X as an input, performs channel estimation (estimation of propagation coefficient) from the pilot symbols in the frame configuration shown in Fig. 9, for example, and outputs the channel estimation signal 5409X. do. It is assumed that the channel estimation signal 5409X is an estimation signal of h ₁₂ (t), and is expressed as h' ₁₂ (t).

The channel estimator 5406Y receives the baseband signal 5405Y as an input, performs channel estimation (estimation of propagation coefficient) from, for example, pilot symbols in the frame configuration of Fig. 9, and outputs the channel estimation signal 5407Y. do. In addition, it is assumed that the channel estimation signal 5407Y is an estimation signal of h ₂₁ (t) and is denoted by h' ₂₁ (t).

The channel estimator 5408Y receives the baseband signal 5405Y as an input, performs channel estimation (estimation of propagation coefficient) from the pilot symbols in the frame configuration shown in Fig. 9, for example, and outputs the channel estimation signal 5409Y. do. In addition, it is assumed that the channel estimation signal 5409Y is an estimation signal of h ₂₂ (t), and is expressed as h' ₂₂ (t).

The control information demodulator 5410 receives the baseband signal 5005X and the baseband signal 540Y as inputs, and includes information about the transmission method, modulation method, transmission power, etc. transmitted by the transmitting device together with data (symbol). Control information 5411 is output by demodulating (detecting/decoding) a symbol for transmitting control information.

Using any one of the transmission methods described above, the transmission device is transmitting the modulated signal. Therefore, it becomes any one of the following transmission methods.

<1> Transmission method of formula (S2)

<2> Transmission method of formula (S3)

<3> Transmission method of formula (S4)

<4> Transmission method of formula (S5)

<5> Transmission method of formula (S6)

<6> Transmission method of formula (S7)

<7> Transmission method of formula (S8)

<8> Transmission method of formula (S9)

<9> Transmission method of formula (S10)

<10> Transmission method of formula (S295)

<11> Transmission method of formula (S296)

By the way, in the case of transmission by the method of formula (S2), the following relationship holds.

When transmitted by the method of formula (S3), the following relationship holds.

When transmitted by the method of formula (S4), the following relationship holds.

When transmitted by the method of formula (S5), the following relationship holds.

When transmitted by the method of formula (S6), the following relationship holds.

When transmitted by the method of formula (S7), the following relationship holds.

When transmitted by the method of formula (S8), the following relationship holds.

When transmitted by the method of formula (S9), the following relationship holds.

When transmitted by the method of formula (S10), the following relationship holds.

In the case of transmission by the method of formula (S295), the following relationship holds.

In the case of transmission by the method of formula (S296), the following relationship holds.

The detection unit 5412 receives baseband signals 5405X and 5405Y, channel estimation signals 5407X, 5409X, 5407Y and 5409Y, and control information 5411 as inputs. And based on the control information 5411, the above formulas (S305), (S306), (S307), (S308), (S309), (S310), (S311), and (S312) , Equation (S313), Equation (S314), Equation (S315), the detection unit 5412 can know which relation holds true.

So, Formula (S305), Formula (S306), Formula (S307), Formula (S308), Formula (S309), Formula (S310), Formula (S311), Formula (S312), Formula (S313), Formula (S314) ), the data transmitted by the detection unit 5412 by s ₁ (t)(s ₁ (i)) and s ₂ (t)(s ₂ (i)) based on any one relational expression of Equation (S315). Each bit is detected (to obtain the log-likelihood of each bit or the log-likelihood ratio of each bit), and a detection result 5413 is output.

Then, the decoding unit 5414 receives the detection result 5413 as an input, decodes the error correction code, and outputs the received data 5415 .

In the above, in this configuration example, the precoding method in the MIMO transmission method and the configuration of the transmitting apparatus and the receiving apparatus using the precoding method have been described. By using this precoding method, the effect that high data reception quality can be obtained in the receiving apparatus can be obtained.

In addition, each of the transmitting antenna and the receiving antenna described in the above configuration example may be one antenna unit constituted by a plurality of antennas. Further, a plurality of antennas for transmitting each of the two modulated signals after precoding may be used to simultaneously transmit one modulated signal at different times.

In addition, although the description has been given of a receiving device in which two receiving antennas are provided in the receiving device, the present invention is not limited thereto, and even if three or more receiving antennas are provided, received data can be obtained in the same manner.

In addition, the precoding method of this configuration example can be implemented similarly when a single carrier method, an OFDM method, a multi-carrier method such as an OFDM method using wavelet transform, and a spread spectrum method are applied.

In addition, the transmission method, reception method, transmission apparatus, and reception apparatus demonstrated in each structural example above are examples of a structure to which the invention demonstrated in each subsequent embodiment can be applied to the last. It goes without saying that the invention described in each of the following embodiments is also applicable to the transmission method, reception method, transmission apparatus, and reception apparatus different from the transmission method, reception method, transmission apparatus, and reception apparatus described above.

<About Embodiments 1-4>

In the following embodiment, modified examples of the processing performed in the coding unit and mapping unit and/or before and after the coding unit and the mapping unit in (Structure Example R1) and (Configuration Example S1) described above will be described. This configuration including an encoding unit and a mapping unit is sometimes called BICM (Bit Interleaved Coded Modulation).

The first complex signal s ₁ (s ₁ (t) or s ₁ (f) or s ₁ (t, f) (t is time, f is frequency)) is determined by any modulation scheme, for example, BPSK (Binary Phase Shift Keying). , QPSK (Quadrature Phase Shift Keying), 16QAM (16 Quadrature Amplitude Modulation), 64QAM (64 Quadrature Amplitude Modulation), 256QAM (256 Quadrature Amplitude Modulation), etc. Based on the mapping, the baseband that can be expressed as in-phase component I and quadrature component Q it's a signal Similarly, the second complex signal s2 (s2(t) or s2(f) or s2(t, f)) is also used in any modulation scheme, for example, BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), 16QAM ( 16 Quadrature Amplitude Modulation), 64QAM (64 Quadrature Amplitude Modulation), and 256QAM (256 Quadrature Amplitude Modulation) are baseband signals that can be expressed as in-phase component I and quadrature component Q based on mapping.

The mapping unit 504 receives the second bit string as an input. Then, the mapping unit 504 receives a (X+Y) bit string as an input. The mapping unit 504 generates a first complex signal s1 based on the mapping of the first modulation method by using the first number of bits X in the (X+Y) bit string. Similarly, the mapping unit 504 generates a second complex signal s2 based on the mapping of the second modulation method by using the second number of bits Y in the (X+Y) bit string.

In addition, in the following embodiment of this specification, after the mapping part 504 (configuration example R1) (configuration example S1), the specific precoding demonstrated in (configuration example S1) may be performed, and Formula (R2), Formula (R3), Formula (R4), Formula (R5), Formula (R6), Formula (R7), Formula (R8), Formula (R9), Formula (R10), Formula (S2), Formula (S3), Formula (S4), Precoding represented by any one of formulas (S5), (S6), (S7), (S8), (S9), and (S10) may be performed.

The encoding unit 502 performs encoding (of an error correction code) from the K-bit information bit string, and outputs a first bit string 503 that is an N-bit code word. Therefore, it is assumed here that an N-bit codeword, that is, a block code having a block length (code length) of N bits, is used as the error correction code. Examples of block codes include, for example, LDPC (block) codes described in Non-Patent Document 1 and Non-Patent Document 6, turbo codes using tail-biting, Non-Patent Document 3, Non-Patent Document 4, etc. There are codes such as a duo-binary turbo code using tail biting described and a code obtained by concatenating an LDPC (block) code and a BCH code (Bose-Chaudhuri-Hocquenghem code) described in Non-Patent Document 5 and the like.

Moreover, K and N are natural numbers, and the relationship of N>K holds. In addition, in an organization code frequently used as an LDPC code, a K-bit information bit string is included in the first bit string.

However, depending on the value of the number of bits X+Y, there are cases in which the codeword length (N bits) output from the encoding unit does not become a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2.

For example, consider a case where the codeword length N is 64800 bits, 64QAM is used as the modulation method, X=6, and 256QAM is used as the modulation method, Y=8, and X+Y=14. Also, for example, consider the case where the codeword length N is 16200 bits, 256QAM is used as the method, X=8, and 256QAM is used as the modulation method, Y=8, and X+Y=16. do.

In either case, "the length of the codeword output from the encoding unit (N bits) does not become a multiple of the number of bits (X + Y) bits for generating the two complex signals s1 and s2".

In each of the following embodiments, the mapping unit makes adjustments to execute processing without leaving the number of bits even if the length (N bits) of the codeword output by the encoding unit is any length.

Additionally, an advantage will be described in the case where the codeword length (N bits) output from the encoding unit is a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2.

A method of efficiently transmitting one block of an error correction code having a codeword length of N bits that a transmitter uses for encoding is considered. At this time, in the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and the same time, the number of bits (X+Y) does not consist of bits of a plurality of blocks It is highly likely that the memory of this transmitter and/or receiver can be reduced.

For example, when (modulation method of the first complex signal s1, the modulation method of the second complex signal s2) = (16QAM, 16QAM), by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and time The number of bits that can be transmitted (X+Y) is 8 bits, and it is preferable that these 8 bits do not contain data of a plurality of blocks (of the error correction code). That is, in the modulation method selected by the transmitter, the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time is equal to the number of blocks (of the error correction code) It is better not to include the data of

Accordingly, "the length of the codeword (N bits) that is the output of the encoding unit is a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2".

However, in the transmitter, it is highly likely that the modulation method of the first complex signal s1 and the modulation method of the second complex signal s2 can be switched between a plurality of modulation methods. Therefore, the possibility that the number of bits (X+Y) takes a plurality of values increases.

At this time, in all possible values of the number of bits (X + Y), "the codeword length (N bits) that is the output of the encoding unit is a multiple of the number of bits (X + Y) bits for generating the two complex signals s1 and s2" cannot be said to be satisfied with

Therefore, there is a need for a processing method described in the following embodiments. Hereinafter, this will be described.

(Embodiment 1)

Fig. 57 shows the configuration of &quot;a portion for generating a modulated signal of the transmitter&quot; (hereinafter referred to as a modulator) according to the first embodiment. In the figure, the same reference numerals are assigned to the same functions or signals as the "part for generating a modulated signal" described in the configuration example R1 described above.

The modulator of the present embodiment includes a bit length adjustment unit 5701 between the encoding unit 502 and the mapping unit 504 .

The encoder 502 outputs a first bit string 503 that is an N-bit codeword (block length (code length)) from a K-bit information bit string according to the control signal 512 .

The mapping unit 504 selects a first modulation method that is a modulation method used to generate the complex signal s1(t) and a second modulation method that is a modulation method used to generate the complex signal s2(t) according to the control signal 512 . do. The number of bits (X+Y) obtained from the first number of bits X for generating the first complex signal s1 and the second number of bits Y for generating the second complex signal s2 among the input second bit strings 5703 is used. Thus, a first complex signal s1(t) and a second complex signal s2(t) are generated (the details are the same as described above).

The bit length adjusting unit 5701 is located at the rear end of the encoding unit 502 and at the front end of the mapping unit 504 . The bit length adjusting unit 5701 inputs the first bit string 503, and the bit length of the first bit string 503 (here, the codeword length of the codeword (block) of the error correction code (block length (code length)) )))) to generate a second bit string 5703 by adjusting the bit length.

58 is a diagram showing bit length adjustment processing in the modulation processing method of the present embodiment.

A control unit (not shown) acquires the number of bits (X+Y) obtained from the first number of bits X for generating the first complex signal s1 and the second number of bits Y for generating the second complex signal s2 (step S5801).

Next, the control unit determines whether bit length adjustment is performed on the codeword length (block length (code length)) of the codeword (block) of the error correction code (S5803). As a condition for judgment, "is it a multiple/multiple" of the codeword length (block length (code length)) N bits of the error correction code obtained from the control signal is the value of X+Y. Moreover, you may perform this determination according to the value of the correspondence table of the value of X+Y and the value of the number of bits N. Further, the information of X+Y may be information of the first modulation method used for generating the complex signal s1(t) and the second modulation method which is the modulation method used for generating the complex signal s2(t).

For example, if the codeword length (block length (code length)) N of the error correction code is 64800 bits and the value of X+Y is 16, the codeword length N bits of the error correction code is a multiple of the value of X+Y. The control unit determines that &quot;bit length adjustment is not performed&quot; (the result of S5803 is NO).

When the control unit determines that the bit length adjustment is unnecessary (the result of S5803 is NO), the control unit sets the first bit string 503 input to the bit length adjustment unit 5701 to be output as the second bit string 5703 as it is. (S5805). That is, in the example described above, the 64800-bit codeword of the error correction code is input from the bit length adjusting unit 5701, and the 64800-bit codeword of the error correction code is output (the bit length adjusting unit 5701 receives the input bit string ( 503) as it is as 5703 and output to the mapping unit).

And, when the codeword length (block length (code length)) of the error correction code is 64800 bits and the value of X+Y is 14, the codeword length N bits of the error-correction code is not a multiple of the value of X+Y. In this case, the control unit determines that &quot;adjust the bit length&quot; (the result of S5803 is YES).

When it is determined that "the bit length is adjusted", the control unit sets the first bit string 503 input to the bit length adjustment unit 5701 to execute the bit length adjustment process (S5805).

59 is a flowchart of bit length adjustment processing in the present embodiment.

The control unit determines a value PadNuM corresponding to which bit in the first bit string 503 needs to be adjusted (S5901). That is, the number of bits added to the codeword length N bits of the error correction code becomes PadNum.

In Embodiment 1, the number (deficiency) equal to the value derived from the following equation is determined as the value of PadNum (bit).

PadNum = ceil(N/(X+Y)) × (X+Y) -N

Here, the ceil function is a function that returns an integer rounded off after the decimal point.

In addition, this decision processing may use the value held in the table without resorting to arithmetic, as long as it can obtain the same result as the value of the above expression.

For example, it is necessary to adjust in advance the control signal (the codeword length (block length (code length)) of the error correction code, the modulation method information for generating s1, and the set of modulation method information for generating s2). The number of bits (the value of PadNum) may be reserved, and the value of PadNum corresponding to the current value of X+Y may be determined as the number of bits to be adjusted. In the table, if the number of adjustment bits can be obtained according to the relationship between the codeword length (block length (code length)) N of the error correction code and the value of X + Y, what index values such as the coding rate and the power imbalance value are used as index values. no matter what

In addition, the above control is particularly necessary in the case of a communication system in which the modulation method for generating s1 and the modulation method for generating s2 are respectively changed.

Next, the control unit instructs the bit length adjustment unit 5701 to generate an adjustment bit string for bit length adjustment constituted by the PadNum bits (S5903).

In addition, the adjustment bit string for bit length adjustment comprised by the PadNum bit may be comprised with "0 (zero)" of the PadNum bit, and may be comprised with "1" of the PadNum bit, for example. An important point is that the transmitting device having the modulator in FIG. 57 and the receiving device receiving the modulated signal transmitted by the transmitting device can share information about the adjustment bit string for bit length adjustment constituted by the PadNum bits. Therefore, it is good if an adjustment bit string for bit length adjustment constituted by PadNum bits is generated according to a specific rule, and this specific rule is shared by the transmitting apparatus and the receiving apparatus. Therefore, the adjustment bit string for adjusting the bit length constituted by the PadNum bit is not limited to the example described above.

In addition, the bit length adjusting unit 5701 receives the first bit string 503 as an input, and a codeword of an error correction code having a codeword length (block length (code length)) N of a predetermined codeword such as a trailing end or a leading end, for example. By adding an adjustment bit string (i.e., an adjustment bit string for adjusting the bit length constituted by the PadNum bits) to the position, the second bit string for the mapping unit is output in which the number of bits constituting the bit is a multiple of the number of bits (X + Y) .

<Effect of this embodiment>

When the encoding unit outputs a codeword of N codeword length (block length (code length)) of the error correction code, the same frequency, It is assumed that the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same time does not include data of a plurality of blocks (of the error correction code). Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

Note that the bit length adjustment unit 5701 may serve as one function of the encoding unit 502 or may be included in one function of the mapping unit 504 .

(Embodiment 2)

Fig. 60 shows the configuration of the modulator of the present embodiment.

The modulator of the present embodiment includes an encoding unit 502LA, a bit length adjusting unit 6001 and a mapping unit 504 . Since the processing of the mapping unit 504 is the same, the description is given.

<Encoding unit 502LA>

The encoding unit 502LA receives, as an input, information bits of K bits (K is a natural number), and obtains and outputs, for example, a codeword of an LDPC code of an organization code consisting of N bits (N is a natural number). However, N > K. In order to obtain the bit string of the parity part of N-K bits of the parity part other than the information part, it is assumed that the parity check matrix of the LDPC code has an accumulate structure.

Information on the i-th block, which is an input for performing LDPC encoding, is expressed as Xi, j (i is an integer, and j is an integer of 1 or more and N or less). Then, the parity obtained after encoding is expressed as Pi, k (k is an integer greater than or equal to N+1 and less than or equal to K). And u=(X ₁ , X ₂ , X ₃ , …, X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) ^T , and the parity check matrix of this LDPC code is H. Then, Hu=0 (in addition, "0 (zero) of Hu=0" here means that all elements are a vector of 0).

At this time, the parity check matrix H is displayed as shown in FIG. 61 . As shown in Fig. 61, in the parity check matrix H, the number of rows is N-K (exists from the first row to the N-Kth row), and the number of columns is N (exists from the first column to the Nth column). And the number of rows of the submatrix 61-1 (Hcx) related to information becomes N-K (exists from the 1st row to the N-Kth row), and the number of columns is K (exists from the 1st column to the Kth column) ) becomes In addition, the number of rows of the submatrix 61-2 (Hcp) related to parity is N-K (exists from the first row to the N-Kth row), and the number of columns is N-K (there exists from the first column to the N-Kth column) do) becomes Then, the parity check matrix H = [Hcx Hcp] is expressed.

62 shows the configuration of a sub-matrix Hcp related to parity in the parity check matrix H of an LDPC code having an accumulate structure exemplified in the present embodiment. As shown in FIG. 62, the elements of the i row and j column of the submatrix Hcp related to parity are H _cp , _comp [i][j] (i and j are integers 1 or more and NK or less (i, j = 1, 2) , 3, ..., NK-1, NK))), the following holds true.

63 is a flowchart of the LDPC encoding process executed by the encoding unit 502LA.

First, the encoding unit 502LA executes an operation related to the information part of the codeword of the LDPC code. For example, j of the parity check matrix H (however, j is an integer greater than or equal to 1 and less than or equal to N-K). The row is explained with an example.

The j-th vector of the sub-matrix 61-1 (Hcx) related to the information of the parity check matrix H and the information of the i-th block are calculated using Xi, j to obtain an intermediate value Yi, j ( S6301).

Next, the encoding unit 502LA obtains parity by executing the following operation since the submatrices 61-2 (Hcp) related to parity have an accumulate structure.

P _{i, N+j} = Y _{i, j} EXOR P _{i, N+j-1}

(EXOR is an addition made by law). However, when j is 1, the following operations are executed.

P _{i, N+1} = Y _{i, j} EXOR 0

Fig. 64 is an example of a configuration for realizing the accumulate processing. In Fig. 64, 64-1 is an exclusive-OR, 64-2 is a register, and the initial value of the register 64-2 is &quot;0 (zero)&quot;.

<Bit length adjustment unit (6001)>

The bit length adjustment unit 6001 inputs a first bit string 503 that is an N-bit codeword (block length (sign length)) and performs bit length adjustment, similarly to the bit length adjustment unit of the first embodiment, and performs a bit length adjustment to the second bit string. (6003) is output.

A characteristic feature is that the bit value of a predetermined part of the N-bit codeword (of the i-th block) obtained by the encoding process is partially used repeatedly by one or more.

Fig. 65 is a flowchart of bit length adjustment processing of the present embodiment.

The bit length adjustment processing is started under the conditions corresponding to those in which step S5807 in Fig. 58 of the first embodiment is activated.

58, it is determined which bit needs to be adjusted (step S6501). This processing is a step corresponding to step S5901 in FIG. 59 of the first embodiment.

Next, the control unit instructs the bit length adjustment unit 6001 to generate an adjustment bit string (herein referred to as an "adjustment bit string") by repeating the bit value of a predetermined part of the N-bit codeword (S6503)

Hereinafter, an example of a method of generating an "adjustment bit string" will be described with reference to FIGS. 66, 67, and 68. FIG.

As described above, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , …, X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) ^T becomes.

<Generation method of “adjustment bit string” according to FIG. 66 (Example 1)>

In FIG. 66 (Example 1), first, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+ 2, P _K+3 , …, P _N-2 , P _N-1 , P _N ) Extract the bit of X _a among the information bits of ^T (66-1). Then, by repeating X _a to generate a plurality (plural bits) of X _a , this is referred to as an "adjustment bit string" (66-2), and the "adjustment bit string" (66-2) of the LDPC code of the i-th block It is added to the codeword (it becomes 66-1 and 66-2 in FIG. 66). Accordingly, in the bit length adjusting unit 6001 of FIG. 60, the first bit string 503 that is the input of the bit length adjusting unit 6001 of FIG. 60 is the codeword of the LDPC code of the i-th block, and the bit length of FIG. The second bit string 6003 that is the output of the adjustment unit 6001 becomes the codeword 66-1 and the "adjustment bit string" 66-2 of the LDPC code of the i-th block.

In addition, although the "adjustment bit string" is inserted (added) at the very end in Fig. 66 (Example 1), the present invention is not limited thereto, and it may be inserted at any position in the codeword of the LDPC code of the i-th block. Moreover, it is good also as a structure in which a plurality of blocks composed of 1 bit or more are generated from the "adjustment bit string", and each block is inserted at any one position of the codeword of the LDPC code of the i-th block.

<Generation method of "adjustment bit string" according to FIG. 66 (Example 2)>

In FIG. 66 (Example 2), first, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) Extract the bit of P _b among the parity bits of ^T (66-3). Then, P _b is repeatedly generated to generate a plurality (plural bits) of P _b , which is referred to as an “adjustment bit string” (66-2), and the “adjustment bit string” (66-4) of the LDPC code of the i-th block. It is added to the codeword (it becomes 66-3 and 66-4 in FIG. 66). Accordingly, in the bit length adjusting unit 6001 of FIG. 60, the first bit string 503 that is the input of the bit length adjusting unit 6001 of FIG. 60 is the codeword of the LDPC code of the i-th block, and the bit length of FIG. The second bit string 6003 that is the output of the adjustment unit 6001 becomes the codeword 66-3 and the "adjustment bit string" 66-4 of the LDPC code of the i-th block.

In addition, although the "adjustment bit string" is inserted (added) at the very end in Fig. 66 (Example 2), the present invention is not limited thereto, and it may be inserted at any position in the codeword of the LDPC code of the i-th block. Moreover, it is good also as a structure in which a plurality of blocks composed of 1 bit or more are generated from the "adjustment bit string", and each block is inserted at any one position of the codeword of the LDPC code of the i-th block.

<A method of generating an “adjustment bit string” according to FIG. 67>

In FIG. 67, first, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , …, P _N-2 , P _N-1 , P _N ) Select M bit from ^T (67-1). For example, each bit of the selected M bits including X _a and P _b is copied once. In this case, the vector M composed of M bits is set to m = [Xa, Pb, ... ] is indicated. And the vector m=[X _a , P _b , … ] as "adjustment bit string" 67-2, and "adjustment bit string" 67-2 is added to the codeword of the LDPC code of the i-th block (67-1 and 67-2 in Fig. 67) becomes). Accordingly, in the bit length adjusting unit 6001 of FIG. 60, the first bit string 503 that is the input of the bit length adjusting unit 6001 of FIG. 60 is the codeword of the LDPC code of the i-th block, and the bit length of FIG. The second bit string 6003 that is the output of the adjustment unit 6001 becomes the codeword 67-1 and the "adjustment bit string" 67-2 of the LDPC code of the i-th block.

In addition, although the "adjustment bit string" is inserted (added) at the very end in FIG. 67, the present invention is not limited thereto, and may be inserted at any position in the codeword of the LDPC code of the i-th block. Moreover, it is good also as a structure in which a plurality of blocks composed of 1 bit or more are generated from the "adjustment bit string", and each block is inserted at any one position of the codeword of the LDPC code of the i-th block.

In addition, the "adjustment bit string" may be generated from only the information bits, from only the parity bits, or may be generated using both the information bits and the parity bits.

<A method of generating an “adjustment bit string” according to FIG. 68>

In FIG. 68, first, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , …, P _N-2 , P _N-1 , P _N ) Select M bit from ^T (68-1). For example, each bit of the selected M bits including X _a and P _b is copied once. In this case, the vector M composed of M bits is m=[X _a , P _b , … ] is indicated.

vector of M bits m=[X _a , P _b , … ] is copied at least once, and the vector γ composed of Γ bits is converted to γ=[X _a , X _a , P _b , … ] (it becomes M<Γ). and the vector γ=[X _a , X _a , P _b , … ] as "adjustment bit string" 68-2, and "adjustment bit string" 68-2 is added to the codeword of the LDPC code of the i-th block (68-1 and 68-2 in Fig. 68) becomes).

Accordingly, in the bit length adjusting unit 6001 of FIG. 60, the first bit string 503 that is the input of the bit length adjusting unit 6001 of FIG. 60 is the codeword of the LDPC code of the i-th block, and the bit length of FIG. The second bit string 6003 that is the output of the adjustment unit 6001 becomes the codeword 68-1 and the "adjustment bit string" 68-2 of the LDPC code of the i-th block.

In addition, although the "adjustment bit string" is inserted (added) at the very end in Fig. 68, the present invention is not limited thereto, and it may be inserted at any position in the codeword of the LDPC code of the i-th block. Moreover, it is good also as a structure which generate|occur|produces a plurality of blocks comprising one bit or more from the "adjustment bit string" and inserts each block at any one position of the codeword of the LDPC code of the i-th block.

In addition, the "adjustment bit string" may be generated from only the information bits, from only the parity bits, or may be generated using both the information bits and the parity bits.

<About the number of "adjustment bit strings" generated by the bit length adjustment unit 6001>

The number of "adjustment bit strings" generated by the bit length adjusting unit 6001 can be determined as described in Embodiment 1 or the like. This point will be described with reference to FIG. 60 .

In FIG. 60, the first complex signal s1 (s1(t) or s1(f) or s1(t, f) (t is time, f is frequency)) is a modulation scheme, for example, BPSK, QPSK, 16QAM, It is a baseband signal that can be expressed as in-phase component I and quadrature component Q based on mapping such as 64QAM and 256QAM. Similarly, the second complex signal s2 (s2(t) or s2(f) or s2(t, f)) also has an in-phase component I based on any modulation scheme, for example, mapping of BPSK, QPSK, 16QAM, 64QAM, 256QAM, etc. , is a baseband signal that can be expressed as a quadrature component Q.

The mapping unit 504 receives the second bit string as an input. Then, the mapping unit 504 receives a (X+Y) bit string as an input. The mapping unit 504 generates a first complex signal s1 based on the mapping of the first modulation method by using the first number of bits X in the (X+Y) bit string. Similarly, the mapping unit 504 generates a second complex signal s2 based on the mapping of the second modulation method by using the second number of bits Y in the (X+Y) bit string. The encoding unit 502 performs encoding (of an error correction code) from the K-bit information bit string, and outputs a first bit string 503 that is an N-bit codeword.

However, depending on the value of the number of bits X+Y, there are cases in which the codeword length (N bits) output from the encoding unit does not become a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2.

For example, consider a case where the codeword length N is 64800 bits, 64QAM is used as the modulation method, X=6, and 256QAM is used as the modulation method, Y=8, and X+Y=14. Also, for example, consider the case where the codeword length N is 16200 bits, 256QAM is used as the modulation method, X = 8, and 256QAM is used as the modulation method, Y = 8, and X + Y = 16. do.

In either case, "the length of the codeword output from the encoding unit (N bits) does not become a multiple of the number of bits (X + Y) bits for generating the two complex signals s1 and s2".

Therefore, in the present embodiment, the bit length adjusting unit 6001 performs adjustment so that the mapping unit executes processing without leaving the number of bits even if the length (N bits) of the codeword output by the encoding unit is any length.

Supplementally, an advantage will be described in the case where the codeword length (N bits), which is the output of the encoding unit, is a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2.

A method of efficiently transmitting one block of an error correction code having a codeword length of N bits that a transmitter uses for encoding is considered. At this time, in the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and the same time, the number of bits (X+Y) does not consist of bits of a plurality of blocks It is highly likely that the memory of this transmitter and/or receiver can be reduced.

For example, when (modulation method of the first complex signal s1, the modulation method of the second complex signal s2) = (16QAM, 16QAM), the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and time The number of bits (X+Y) that can be transmitted by means of 8 bits is 8 bits, and it is better not to include data of a plurality of blocks (of the error correction code). That is, in the modulation method selected by the transmitter, the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time is equal to the number of blocks (of the error correction code) It is better not to include the data of

Therefore, it is preferable that "the length of the codeword (N bits) output from the encoding unit is a multiple of the number of bits (X+Y) bits for generating the two complex signals s1 and s2".

However, in the transmitter, it is highly likely that the modulation method of the first complex signal s1 and the modulation method of the second complex signal s2 can be switched between a plurality of modulation methods. Therefore, the possibility that the number of bits (X+Y) takes a plurality of values increases.

At this time, in all possible values of the number of bits (X + Y), "the codeword length (N bits) that is the output of the encoding unit is a multiple of the number of bits (X + Y) bits for generating the two complex signals s1 and s2" cannot be said to be satisfied with

Therefore, there is a need for a processing method described in the following embodiments.

The mapping unit 504 selects a first modulation method that is a modulation method used to generate the complex signal s1(t) and a second modulation method that is a modulation method used to generate the complex signal s2(t) according to the control signal 512 . do. The number of bits (X+Y) obtained from the first number of bits X for generating the first complex signal s1 and the second number of bits Y for generating the second complex signal s2 among the input second bit string 6003 is used. Thus, a first complex signal s1(t) and a second complex signal s2(t) are generated.

The bit length adjusting unit 6001 inputs the first bit string 503, and the bit length of the first bit string 503 (here, the codeword length of the codeword (block) of the error correction code (block length (code length)) ))), to generate a second bit string 5703 by adjusting the bit length.

58 is a diagram showing bit length adjustment processing in the modulation processing method of the present embodiment.

A control unit (not shown) obtains the number of bits (X+Y) obtained from the first number of bits X for generating the first complex signal s1 and the second number of bits Y for generating the second complex signal s2 (step S5801)

Next, the control unit determines whether bit length adjustment is performed on the codeword length (block length (code length)) of the codeword (block) of the error correction code (S5803). As a condition for judgment, "is it a multiple/multiple" of the codeword length (block length (code length)) N bits of the error correction code obtained from the control signal is the value of X+Y. Moreover, you may make this determination based on the value of the correspondence table of the value of X+Y and the value of the number of bits N. Further, the information of X+Y may be information of the first modulation method used for generating the complex signal s1(t) and the second modulation method which is the modulation method used for generating the complex signal s2(t).

For example, if the codeword length (block length (code length)) N of the error correction code is 64800 bits and the value of X+Y is 16, the codeword length N bits of the error correction code is a multiple of the value of X+Y. The control unit determines that &quot;bit length adjustment is not performed&quot; (the result of S5803 is NO).

When the control unit determines that the bit length adjustment is unnecessary (the result of S5803 is NO), the control unit sets the first bit string 503 input to the bit length adjustment unit 5701 to be output as the second bit string 5703 as it is. do (S5805). That is, in the example described above, the 64800-bit codeword of the error correction code is input to the bit length adjusting unit 5701 and the 64800-bit codeword of the error correction code is output. (The bit length adjustment unit 5701 outputs the input bit string 503 as it is as 5703 to the mapping unit)

And when the codeword length (block length (code length)) N of the error correction code is 64800 bits and the value of X+Y is 14, the codeword length N bits of the error correction code is not a multiple of the value of X+Y. In this case, the control unit determines that &quot;adjust the bit length&quot; (the result of S5803 is YES).

When it is determined that "the bit length is adjusted", the control unit sets the bit length adjustment process to be performed on the first bit string 503 input to the bit length adjustment unit 5701 (S5805). That is, as described above, the bit length adjustment process and the "adjustment bit string" in this embodiment are generated, and the "adjustment bit string" is added to the vector of the codeword of the LDPC code of the i-th block (e.g. For example, as shown in FIGS. 66, 67, and 68).

Therefore, for example, when the codeword length (block length (code length)) N of the codeword vector of the LDPC code of the i-th block is fixed as 64800 bits, the value of X+Y, that is, the first modulation method and When the set of the second modulation method is changed (or when it is possible to change the settings of the set of the first modulation method and the second modulation method), the number of bits in the "adjustment bit string" is appropriately changed (and the value of X+Y) (The "adjustment bit string" may not be necessary depending on the set of the modulation method 1 and the second modulation method).

And one important point is that the number of bits of the second bit string 6003 composed of the codeword of the LDPC code of the i-th block and the “adjustment bit string” is determined by the set of the first modulation method and the second modulation method. It is a multiple of the number of bits (X+Y).

Next, an example of a method for generating a characteristic &quot;adjustment bit string&quot;

69 and 70 show modified examples of the "adjustment bit string" generated by the bit length adjusting unit. 503 of FIGS. 69 and 70 becomes the first bit string 503 that is input to the bit length adjusting unit 6001 of FIG. 60 . Reference numeral 6003 in FIGS. 69 and 70 indicates the second bit string output by the bit length adjusting unit. 69 and 70, for ease of understanding, the second bit string 6003 has a configuration in which an "adjustment bit string" is added after the first bit string 503 (however, the "adjustment bit string" The position of adding , is not limited thereto).

<Legend>

Each square frame indicates individual bits of the first bit string 503 or the second bit string 6003 .

In the figure, the square frame surrounding "0" represents a bit whose value is "0".

In the figure, the square frame surrounding "1" represents a bit whose value is "1".

In the figure, p_last, which is a hatched (slanted) rectangular frame, is "a bit value of a bit corresponding to a bit at a position corresponding to the final output bit of the accumulate process". That is, in the LDPC code in which the parity-related submatrix in the parity check matrix described above has an accumulate structure, p_last represents the vector of the codeword of the LDPC code of the i-th block, u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) becomes P _N in the case of ^T (p_last is a bit related to the last column of a submatrix related to parity of an accumulate structure in an LDPC code in which a submatrix related to parity in the parity check matrix has an accumulate structure).

Black squares (connected) indicate "any bit used for deriving the value of p_last" by the encoding unit 502 in the process of FIG. 63 .

One of the connected bits is the bit value of the bit corresponding to the second to last bit p_2ndlast used for derivation of p_last in the accumulate process of step S6303. That is, in the parity check matrix described above, in the LDPC code in which the parity-related submatrix has an accumulate structure, p_2ndlast represents the vector of the codeword of the LDPC code of the i-th block with u=(X ₁ , X ₂ , X ₃ , …, X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , …, P _N-2 , P _N-1 , P _N ) In the case of ^T , one of the connected bits is It becomes P _N-1 .

In addition, the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) NKth in the parity check matrix H (matrix of NK rows and N columns) of the LDPC code in which the submatrix related to the parity of ^T has an accumulate structure Let the vectors constituting the row be h _NK . At this time, h _NK is a vector of 1 row and N column.

And let g be the column which becomes "1" in vector _hNK . In addition, let g be an integer of 1 or more and K or less. At this time, as a connected bit, X _g is also a candidate.

In the figure, the quadrangular frame surrounding any is a bit of any one of "0" and "1".

In addition, the length of the arrow indicated by PadNum is the number of adjustment bits in the case of adjusting the bit length (by making up for the shortfall).

Hereinafter, an example is demonstrated. The hatched (slanted) p_last becomes P _N .

The bit length adjusting unit 6001 of FIG. 60 generates an "adjustment bit string" of any one of the following modified examples (in addition, the arrangement method of the "adjustment bit string" is not limited to that of FIG. )

<The first modification of FIG. 69>

The bit length adjusting unit 6001 generates an "adjusted bit string" by repeating the value of p_last by one or more.

<Second modification of FIG. 69>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" by repeating the value of p_last by one or more. Also for "any", the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) is generated from any one bit of ^T.

<Third modified example of FIG. 69>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" by repeating the value of p_last by one or more. In addition, a part of the &quot;adjustment bit string&quot; is composed of predetermined bits.

<Fourth modification of FIG. 70>

The bit length adjusting unit 6001 generates an "adjusted bit string" by repeating the value of the connected bit by one or more.

<Fifth modified example of FIG. 70>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" by repeating the value of the connected bit by one or more. Also for "any", the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) It is generated from any one bit of ^T.

<Sixth modification of FIG. 70>

The bit length adjusting unit 6001 generates an "adjustment bit string" from the value of p_last and the value of the connected bit.

<Seventh modification of FIG. 70>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" from the value of p_last and the value of the connected bit. Also for "any", the vector of the codeword of the LDPC code of the i-th block is u=(X ₁ , X ₂ , X ₃ , ..., X _K-2 , X _K-1 , X _K , P _K+1 , P _K+2 , P _K+3 , ..., P _N-2 , P _N-1 , P _N ) is generated from any one bit of ^T.

<Eighth modification of FIG. 70>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" from the value of p_last and the value of the connected bit. In addition, a part of the &quot;adjustment bit string&quot; is composed of predetermined bits.

<The ninth modification of FIG. 70>

The bit length adjusting unit 6001 generates a part of the "adjusted bit string" from the value of the connected bit. In addition, a part of the &quot;adjustment bit string&quot; is composed of predetermined bits.

<Effect of this embodiment>

71 is a diagram for explaining one of the points of the invention according to the present embodiment.

The upper part of the drawing is a diagram again illustrating the first bit string (codeword of the LDPC code of the i-th block) 503 of FIGS. 69 and 70 .

The middle part of the figure is the parity check matrix H of the conceptual LDPC code conceived by the LDPC encoding process accompanying the accumulate process (in step S6303).

In the figure, "1" forms an edge when a Tanner graph is drawn in the parity check matrix of the conceptual LDPC code. As described in step S6303, the value of p_last is calculated using the value of p_2ndlast. However, the value of p_last is the last bit in the accumulate processing sequence, and has no relation to the next bit value. Accordingly, in the conceptual parity check matrix H, the column weight of p_last (or the bit corresponding to p_last) is smaller than the column weight of 2 of the bits of other parity parts, and the column weight is 1. (The column weight is a number having an element of "1" in the column vector of each column of the parity check matrix).

The lower part of the drawing is a Tanner graph of the above-mentioned parity check matrix H.

A circle (○) indicates a variable (bit) node. Among the circles, hatched (slanted) circles are variable (bit) nodes that abstract p_last. Also, black circles are bit nodes that abstract connected bits. Also, in the lower part of this figure, a square (□) indicates a check node to which these variable (bit) nodes are connected. In particular, a check node indicated by checknode_last is a check node to which a bit node abstracting p_last is connected. Also, a solid line at the bottom of the figure is a variable (bit) node having checknode_last and an edge.

The connected bit described above is a group of bits directly connected to checknode_last including p_2ndlast. At the bottom of the figure, a solid line indicates an edge that is directly connected to a bit node connected to checknode_last. In addition, the dotted line in the lower part of the figure indicates the edge of the parity check matrix H in the concept of another check node.

By the way, consider a case where BP (Belief Propagation) decoding such as sum-product decoding is performed in an LDPC code in which a submatrix related to parity has an accumulate structure.

Pay attention to the Tanner graph at the bottom of FIG. 71 . In particular, pay attention to a graph formed by a variable (bit) node of parity and a check node.

At this time, a variable (bit) node that abstracts a bit of a parity part different from p_last, such as p_2ndlast, is connected to two check nodes (the number of edges in the figure 2).

When paying attention to a graph formed by parity variable (bit) nodes and check nodes, when the number of parity edges is 2, external values can be obtained from (check nodes) in two directions. And since iterative decoding is performed, reliability is propagated from distant check nodes and variable (bit) nodes.

In contrast, the variable (bit) node that abstracts p_last has only one check node (checknode_last) edge when paying attention to the graph formed by the parity variable (bit) node and the check node (indicated by the number of edges in the drawing as 1) one line).

Therefore, the variable (bit) node of p_last means that the external value can only be obtained from the 1 direction. And since iterative decoding is performed, reliability propagates from distant check nodes and variable (bit) nodes. However, the variable (bit) node of p_last can only obtain external values from one direction, so it is difficult to obtain a lot of reliability. Reliability is lower than that of other parity bits.

Therefore, since the reliability of p_last is low, error propagation occurs for other bits.

Therefore, if the reliability of p_last is improved, the occurrence of error propagation can be suppressed, so that the reliability of other bits is improved. In the invention according to the present embodiment, paying attention to this point, repeatedly transmitting p_last is proposed.

In addition, since the reliability of p_last is low, the bit with low reliability is the connected bit (this point can be derived from the relationship "Hu=0" described above). And since the reliability of the connected bit is low, error propagation occurs in other bits.

Therefore, if the reliability of the connected bit is improved, the occurrence of error propagation can be suppressed, so that the reliability of the other bit is improved. In the invention according to the present embodiment, paying attention to this point, repeated transmission of the connected bit is proposed.

Of course, you may implement by combining two or more embodiment demonstrated in this specification.

(Embodiment 3)

73 shows the configuration of the modulator of the present embodiment.

The modulator of FIG. 73 includes an encoding unit 502LA, a bit interleaver 502BI, a bit length adjusting unit 7301 and a mapping unit 504 .

Since the mapping unit 504 operates as described in the previous embodiment, a description of its operation is omitted.

The encoder 502LA receives K-bit information in the i-th block as an input and outputs an N-bit codeword 503Λ in the i-th block. Here, the N-bit bit string 5 is assumed to be a specific number of bits, such as 4320 bits, 16800 bits, and 64800 bits.

The bit interleaver 502BI, for example, inputs an N-bit bit string 503? constituting the i-th block, executes a bit interleaving process, and outputs an N-bit (after interleaving) bit string 503V. The interleaving process is a process in which sequence numbers are replaced with respect to the sequence numbers of the input bits of the bit interleaver 502BI, and the bit string in which the sequence numbers are replaced is output. For example, when the input bit string of the bit interleaver 502BI is arranged in the order of b1, b2, b3, b4, b5, the output bit string of the bit interleaver 502BI is b2, b4 by executing interleaving processing. , b5, b1, b3 (however, the order is not limited thereto).

The bit length adjusting unit 7301 adjusts the bit length by inputting, for example, an N-bit (after bit interleaved) bit string 503V, and outputs the bit length adjusted bit string 7303.

FIG. 74 is a diagram for explaining the operation of the bit interleaver 502BI of FIG. 73 with an output bit string. However, Fig. 74 is an example of the bit interleaving method, and the bit interleaving method may be a method other than the present method. In the drawing, the hatched (slanted) rectangular frame and the black rectangular frame are used in the same meaning as described in FIG. 69 of the second embodiment.

Reference numeral 503Λ in Fig. 74 indicates the sequence of the bit sequence before the bit interleaving process.

503U in FIG. 74 shows the sequence of the bit string after the first bit interleaving process (?1).

503V in FIG. 74 shows the sequence of the bit string after the second bit interleaving process (?2).

The solid arrow indicates that the bit at the position (order number) of the start point of the arrow is moved to the position (order number) at the point where the arrow ends by the first bit interleaving process. For example, sigma 1(N-1) represents the state of movement of the position of the N-1 position (N-th) p_last by the first interleaving, which is the last bit value of the parity part. In the example of this figure, ?1(N-1) is N-1, and the position does not change. In addition, ?1(N-2) represents the state of movement of the position of p_2ndlast.

The bit interleaver is a process performed in order to strengthen the resistance to burst errors in the communication path by lengthening the distance between the positions of two adjacent bits, particularly in parity, among the codewords generated by the encoding of the LDPC code. The adjacent p_last and p_2ndlast in 503? immediately after the encoding process have the same spacing as indicated by 503U by the interleaving process ?1.

The dotted arrow indicates that the bit at the position (order number) of the start point of the arrow moves to the position (order number) where the arrow ends as a result of performing bit interleaving processing (σ1, σ2, ...) a plurality of times. σ(N-1) is a composite substitution of σ1 and σ2 multiple times. In the example of this figure using two permutations, it is equivalent to ?2(?1(N-1)).

In this way, the bit interleaver 502BI exchanges the sequence number of the input bits of the bit interleaver 502BI, and outputs the bit sequence in which the sequence is replaced.

Fig. 75 shows an example of the implementation of the bit interleaver 502.

The bit interleaving process is performed by storing the bit string to be interleaved in a memory having sizes Nr and Nc, which are divisors of the number of bits in the bit string, and changing the writing order and reading order in the memory.

First, the bit interleaver secures a memory with the number of bits N to be subjected to bit interleaving. However, N = Nr x Nc.

Nr and Nc may be changed according to a coding rate of the error correction code and/or a set modulation method (or a set of modulation methods).

In Fig. 75, Nr x Nc individual squares indicate a storage section (in which the value 0 or the value 1 is accumulated) in which the value of the corresponding bit is written.

A solid arrow returning in the vertical direction (in the WRITE direction) means writing a bit string into the memory from the start point of the arrow to the end point of the arrow. Bitfirst in the figure indicates the position at which the first bit is written. Moreover, in each column, the writing position at the head of each column may be changed.

And the dotted arrow (READ direction) returning in the vertical direction indicates the reading direction.

The example of FIG. 75 shows the process of rearranging the bit string of the parity part of 503Λ (so-called parity interleaving process). A gap is formed between p_2ndlast and p_last written in a memory having consecutive addresses in the WRITE direction.

Fig. 76 shows the bit length adjustment processing in the present embodiment.

First, a control unit (not shown) in Fig. 73 determines which bit adjustment is necessary (step S7601). This process is a step corresponding to step S5901 of the first embodiment.

Next, the control unit sends the bit length adjustment unit 7301 of FIG. 73 to, for example, the bit string added to the N-bit codeword of the i-th block (for example, the bit to be added as described in the first embodiment; The position to be added after bit interleaving of the described "adjustment bit string") is designated (S7603).

An example is demonstrated using FIG. 77. In FIG. 77, 503V indicates the bit string after interleaving in FIG. 73, and it is assumed that, for example, it is an N-bit codeword of the i-th block after interleaving. 7303 indicates the bit string after bit length adjustment in FIG. 73, and it is assumed that an additional bit string is added to the N-bit codeword of the i-th block after interleaving.

And in Fig. 77, a square frame (□) indicates each bit of the N-bit codeword of the i-th block after interleaving, and a black square frame (■) indicates a bit of a bit string to be added.

In the example of Fig. 77, bit (■) 7314#1 of the bit string to be added is inserted between □ of 7314#1A and □ of 7314#1B, and is added between □ of 7314#1A and □ of 7314#1B. The bit string 7303 after bit length adjustment is formed by inserting the bit (■) 7314#2 of the bit string. That is, by inserting and adding a bit string to be added to the N-bit codeword of the i-th block after interleaving, a bit string 7303 after bit length adjustment is generated (S7605).

In addition, as described in the first and second embodiments, when "the codeword length (block length (code length)) of the codeword vector of the ith block (LDPC code) N is fixed, such as 64800 bits, When the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation of s2(t)) If it is possible to change the setting of the method set), the number of bits in the bit string to be added is appropriately changed. (In addition, depending on the value of X+Y (a set of the first modulation method of s1(t) and the second modulation method of s2(t)), an additional bit string may not be required).

And one important point is that the first modulation scheme of s1(t) and the first modulation method of s2(t) in which the number of bits of the bit string 7303 after the bit length adjustment, which is composed of the codeword of the LDPC code of the i-th block and the bit string to be added, is set. It is a multiple of the number of bits (X+Y) determined by the set of the second modulation method.

In the previous description, "the bit length adjusting unit 7301 inputs an N-bit (after bit interleaved) bit string 503V, adjusts the bit length, and outputs the bit length adjusted bit string 7303. ', but "the bit length adjusting unit 7301 inputs an Nxz bit (after bit interleaving) bit string 503V, adjusts the bit length, and adjusts the bit length 7303. is output (z is an integer greater than or equal to 1)".

Fig. 75 shows an example of the implementation of the bit interleaver 502.

The bit interleaving process is performed by storing the bit string to be interleaved in a memory having a size of Nr and Nc, which are divisors of the number of bits in the bit string, and changing the writing order and reading order in the memory.

First, the bit interleaver secures a memory with the number of bits Nxz to be subjected to the bit interleaving process. However, N x z = Nr x Nc.

Nr and Nc may be changed according to a coding rate of the error correction code and/or a set modulation method (or a set of modulation methods).

In Fig. 75, Nr x Nc individual squares are written with the value of the corresponding bit (the value 0 or the value 1 is accumulated). It represents memory.

A solid arrow returning in the vertical direction (in the WRITE direction) means writing a bit string into the memory from the start point of the arrow to the end point of the arrow. Bitfirst in the figure indicates the position at which the first bit is written. Moreover, in each column, the writing position at the head of each column may be changed.

And the dotted arrow returning to the vertical direction (READ direction) indicates the reading direction.

The example of FIG. 75 shows the process of rearranging the bit string of the parity part of 503Λ (so-called parity interleaving process). A gap is created between p_2ndlast and p_last written in a memory whose addresses are continuous in the WRITE direction.

Fig. 76 shows the bit length adjustment processing in the present embodiment. First, a control unit (not shown) in Fig. 73 determines which bit needs to be adjusted (step S7601). This process is a step corresponding to step S5901 of the first embodiment.

Next, the control unit adds, to the bit length adjusting unit 7301 of FIG. 73, blocks formed of, for example, N-bit codewords for z pieces (for example, bits to be added as described in Embodiment 1, Embodiment 2) The position to be added after bit interleaving of the "adjustment bit string" described above is designated (S7603).

An example is demonstrated using FIG. 77. In Fig. 77, 503V indicates the bit string after interleaving in Fig. 73, and it is assumed that, for example, it is the number of z blocks formed of the interleaved N-bit codeword.

7303 indicates a bit string after bit length adjustment in FIG. 73, and it is assumed that an additional bit string is added to z blocks formed of N-bit codewords after interleaving.

And in Fig. 77, a square frame (□) represents each bit for z blocks formed of an N-bit codeword, and a black square frame (■) represents a bit of a bit string to be added.

In the example of FIG. 77, the bit (■) 7314#1 of the bit string added between □ of 7314#1A and □ of 7314#1B is inserted between □ of 7314#1A and □ of 7314#1B. A bit string 7303 after bit length adjustment is formed by inserting bit (■) 7314#2. That is, by inserting/adding a bit string to be added to z blocks formed of N-bit codewords after interleaving, a bit string 7303 after bit length adjustment is generated (S7605).

In addition, when thinking as described in the first and second embodiments, "the codeword length (block length (code length)) of a vector of codewords of the i-th block (in the LDPC code) N is fixed like 64800 bits. When the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation method of s2(t)) If it is possible to change the setting of the modulation method set), the number of bits in the bit string to be added is appropriately changed (in addition, the value of X+Y (the first modulation method of s1(t) and the second modulation method of s2(t)) is changed. set), the additional bit string may not be necessary).

And one important point is that the bit string after adjusting the bit length (7303) is composed of "a bit string corresponding to z codewords of the LDPC code of the i-th block, that is, an N×z bit string" and an "additional bit string". ) is a multiple of the number of bits (X+Y) determined by the set first modulation method of s1(t) and the second modulation method of s2(t).

<Intention of this embodiment>

(1) Correspondence to change of modulation method

One problem of the present invention is to cope with the lack of bits in the exchange of sets of the modulation method of the complex signal s1(t) and the modulation method of the complex signal s2(t) as described in the first and second embodiments.

(When the size of the interleave is N bits)

(Effect 1)

As described above, "the first modulation method of s1(t) and s2(t) in which the number of bits of the bit string 7303 after bit length adjustment consisting of the codeword of the LDPC code of the i-th block and the bit string to be added is set. It is a multiple of the number of bits (X + Y) determined by the set of the second modulation method”.

As a result, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is the same for a set of complex signals based on a combination of all modulation methods regardless of the value of N. The number of bits (X+Y) that can be transmitted by the frequency and the first complex signal s1 and the second complex signal s2 transmitted at the same time is such that data of a plurality of blocks (of the error correction code) is not included. Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

(Effect 2)

When the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation of s2(t)) 73, by installing the bit length adjusting unit 7301 at the rear end of the bit interleaver 502BI, the memory size of the bit interleaver can be adjusted to the first modulation method of s1(t) and s2 It can be made constant regardless of the set of the second modulation scheme in (t). Thereby, an effect that an increase in the memory of the bit interleaver can be prevented can be obtained. (If the order of the bit length adjusting unit 7301 and the bit interleaver 502BI is reversed, it is necessary to change the memory size according to the set of the first modulation method of s1(t) and the second modulation method of s2(t). Therefore, it becomes important to arrange the bit length adjusting unit 7301 at the rear end of the bit interleaver 502BI. In FIG. 73, the bit length adjusting unit 7301 is disposed immediately after the bit interleaver 502BI. 502BI) and an interleaver for performing another interleaving may be inserted between the bit length adjusting unit 7301, or other processing units may be inserted).

In addition, a plurality of codeword lengths (block length (code length)) of the error correction code may be prepared. For example, it is assumed that Na bits and Nb bits are prepared as the codeword length (block length (code length)) of the error correction code. Codeword length (block length (code length)) When an error correction code of Na bits is used, the bit interleaver memory size is set to Na bits to perform bit interleaver, and then, the bit length adjusting unit 7301 of FIG. An additional bit string is added to . Similarly, when the error correction code of the codeword length (block length (code length)) Nb bits is used, the bit interleaver memory size is Nb bits to perform bit interleaver, and then, the bit length adjusting unit 7301 of FIG. In this case, an additional bit string is added.

(When the interleave size is N×z bits)

(Effect 3)

As described above, the bit length adjusted bit string 7303 is composed of "a bit string corresponding to z codewords of the LDPC code of the i-th block, that is, a bit string of Nxz bits" and an "additional bit string". ) is a multiple of the number of bits (X+Y) determined by the set of the first modulation method of s1(t) and the second modulation method of s2(t).

As a result, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is the same for a set of complex signals based on a combination of all modulation methods regardless of the value of N. The number of bits (X+Y) that can be transmitted by the frequency and the first complex signal s1 and the second complex signal s2 transmitted at the same time is such that data of blocks other than z codewords is not included. Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

(Effect 4)

When the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation of s2(t)) 73), by installing the bit length adjusting unit 7301 at the rear end of the bit interleaver 502BI as shown in FIG. t) can be made constant regardless of the second set of modulation schemes. Thereby, the effect that an increase in the memory of the bit interleaver can be prevented can be acquired. (If the order of the bit length adjusting unit 7301 and the bit interleaver 502BI is reversed, it is necessary to change the memory size according to the set of the first modulation method of s1(t) and the second modulation method of s2(t). Therefore, it becomes important to arrange the bit length adjusting unit 7301 at the rear end of the bit interleaver 502BI. In FIG. 73, the bit length adjusting unit 7301 is disposed immediately after the bit interleaver 502BI. 502BI) and an interleaver for performing another interleaving may be inserted between the bit length adjusting unit 7301, or other processing units may be inserted).

In addition, a plurality of codeword lengths (block length (code length)) of the error correction code may be prepared. For example, it is assumed that Na bits and Nb bits are prepared as the codeword length (block length (code length)) of the error correction code. Codeword length (block length (code length)) When an error correction code of Na bits is used, the bit interleaver memory size is Na × z bits to perform bit interleaver, and then, the bit length adjusting unit 7301 of FIG. 73 will add an additional bit stream if necessary. Similarly, when the error correction code of the codeword length (block length (code length)) Nb bits is used, the bit interleaver memory size is Nb × z bits to perform bit interleaver, and then, the bit length adjusting unit 7301 in FIG. ) adds an additional bit string if necessary.

Also, a plurality of bit interleave sizes may be prepared for the code length (block length (code length)) of each error correction code. For example, when the codeword length of the error correction code is N bits, it is assumed that N×a bits and N×b bits are prepared as the bit interleave size (provided that both a and b are integers greater than or equal to 1). Then, when Nxa bits are used as the bit interleave size, bit interleaver is performed. After that, the bit length adjusting unit 7301 of FIG. 73 adds an additional bit string if necessary. Similarly, bit interleaver is performed when N×b bits are used as the bit interleave size, and thereafter, the bit length adjusting unit 7301 of FIG. 73 adds an additional bit string if necessary.

(Supplementary Embodiment 3)

(Method 1), Correspondence by changing the codeword length N of the error correction code

The original solution can be achieved by determining the codeword length N of the error correction code as a value including the factors X+Y.

However, first, there is a limit to making the codeword length N of the error correction code a number obtained by taking the values of all patterns of X+Y by a new modulation method set as a factor. For example, in order to correspond to 14 when X+Y is 6+8, the codeword length N of the error correction code must be a number including 7 as an argument. After that, when the set of modulation schemes corresponds to the total value of 22 of X=10 and Y=12, the codeword length N of the error correction code needs to be set to a new factor of 11 degrees.

(Method 2) backward compatibility with the Nr×Nc memory of the past bit interleaver

Also, as described with reference to Fig. 75, in some cases, the bit interleaver is realized by using the difference in write or read addresses of a predetermined number of NcxNr memories for a predetermined number of bits. However, when the selectable modulation method in the specification (standard) in the first step is, for example, a number such that X+Y is 12 or less, it is assumed that an appropriate bit interleaving process is performed for the codeword N of the error correction code. In the specification (standard) in the second step, for example, 14 is added as a new number of X+Y. Then, when X+Y=14, it is difficult to control including the appropriate bit interleaving of the specification (standard) in the first step. This point will be described with &quot;bit to repeat a value&quot; as p_last.

In Fig. 78, the bit string adjusting section is inserted at the front end (not at the rear end) of the bit interleaver 502BI. A dotted quadrangular frame in the drawing is a bit length adjusting unit temporarily inserted.

If the bit length adjustment unit is located at the front end (not at the rear end) of the bit interleaver 502BI, the bit position of p_last is the last bit of the bit string 503Λ.

In this case, 6003 obtained by adding a 6-bit adjustment bit to the N-bit bit string 503 is output at the rear end. The interleaver that has received the 6-bit adjustment bit must interleave the bit string of the number of bits with a new factor (eg 7 or 11) that is not a multiple of Nr×Nc bits determined in the specification (standard) in the first step. will do Accordingly, when the bit string adjusting unit is inserted at the front end (not at the rear end) of the bit interleaver 502BI, the affinity for the bit interleaver of the specification (standard) in the first step is low.

On the other hand, in the configuration of the present embodiment shown in Fig. 73, the bit length adjusting unit 7301 is located at the rear end (not the front end) of the bit interleaver 502BI.

According to the configuration of this order, the bit interleaver 502BI inputs N bits of the codeword of the error correction code of the specification (standard) in the first step, and bits suitable for the codeword length of 503 or a predetermined number of bits in the codeword. Interleaving processing can be performed.

Further, like other embodiments, it is possible to cope with the lack of bits with respect to the number of bits (X+Y) for generating sets of complex signals s1(t) and s2(t).

<Another example>

79 is a modified example of the modulator of the present embodiment.

At the rear end of the encoding unit 502LA, a bit value holding unit 7301A and an adjustment bit string generating unit 7301B constituting the bit length adjusting unit 7301 are provided.

The bit value holding unit 7301A first supplies the inputted N bits 503 to the bit interleaver as it is. Thereafter, the bit interleaver 502BI performs bit interleaving on the bit string 503 of N bits in bit length (the code length of the error correction code) to output the bit string 503V.

In addition, the bit value holding unit 7301A holds the bit value of "the bit position at which the value is to be repeated" among the first bit string 503 output by the encoding unit, and supplies it to the adjusted bit string generating unit 7301B.

The adjustment bit string generation unit 7301B uses the acquired "bit value of the bit whose value is to be repeated" to generate the adjustment bit string according to any one of the second embodiments, and generates the adjustment bit string together with the N-bit bit string 503V. Included in 503 and printed.

According to this variant,

(1) The position of the "bit whose value is to be repeated" can be easily obtained without being affected by the bit interleaving pattern that is changed by, for example, the encoding rate of the error correction code. For example, when "bit to repeat a value" is p_last, the position of plast can be easily acquired. Therefore, the bit length adjusting unit can generate the bit string from repetition of the last bit input at a fixed position.

(2) The bit interleaver designed for the codeword length of a predetermined error correction code is also very suitable in terms of processing and compatibility.

In addition, as shown by the dotted rectangle in the figure, the functions of 7301A and 7301B may be included in the function of the bit interleaver 502BI.

(Embodiment 4)

In Embodiments 1 to 3, it has been described that the bit length of the bit string 503 is supplemented by an adjustment bit string to compensate for the shortfall (PadNum bits) in multiples of the value of X+Y.

In Embodiment 4, a method of adjusting the bit length by shortening the bit length by a surplus that is a multiple of the value of X+Y will be described. In particular, a method of adjusting the bit sequence length by inserting known information in the previous stage of encoding the error correction code, encoding information including the known information, and then deleting the known information will be described. In addition, TmpPadNuM is the number of bits of known information to be inserted and also the number of bits to be deleted thereafter.

Fig. 80 shows the configuration of the modulator of the present embodiment.

The bit length adjustment unit 8001 of the present embodiment includes a front end portion 8001A and a bit length adjustment portion rear end portion 8001B.

The front end portion 8001A executes “processing on the front end portion”. The front end temporarily adds an "adjustment bit string", which is known information, to the bit string of the input information, and outputs a K-bit bit string.

The encoding unit 502 receives as an input an information bit string including K-bit known information, performs encoding, and outputs a first bit string 503 that is an N-bit codeword. It is assumed that the error correction code used by the encoding unit 502 is an organization code (a code composed of information and parity).

The rear end portion 8001B executes &quot;process related to the rear end portion&quot;. The rear end inputs the bit string 503, and removes the "adjustment bit string", which is known information temporarily inserted by the front end 8001A. Accordingly, the sequence length of the bit string 8003 after the bit length adjustment output from the front end unit 8001A is a multiple of the value of X+Y.

In addition, about "the value of X+Y", it is the same as that of Embodiment 1 - Embodiment 3 demonstrated above.

81 is a flowchart showing the processing of the present embodiment.

The dotted square OUTER indicates "processing related to the front end".

The process related to the front end is a process for the control unit to set the processing contents to the front end. In addition, although not shown in FIG. 80, the control part outputs the signal line 512 becomes a control part.

Based on the value of X+Y, the control unit acquires the bit length TmpPadNuM of the known information from among the K bits of the N bits of the codeword of the error correction code (S8101).

For example, consider the following calculation formula as a value to be acquired.

TmpPadNum = N -(floor(N/(X+Y))× (X+Y))

Here, floor is a round-up function after the decimal point.

It is not necessary to obtain this value by calculation, and for example, it may be obtained from a table by parameters such as the codeword length (block length) N of the error correction code of the encoding unit 502 .

Next, the control unit secures a field with a length of TmpPadNum so that the output bit string 501 of the previous stage becomes K bits. That is, control is performed so that information among K bits becomes K-TmpPadNum (bits) and known information to be inserted becomes TmpPadNum (bits) (S8103).

(Example 1) When the front end portion 8001A in Fig. 80 is a part of the frame generation processing unit:

The front end portion 8001A in Fig. 80 may be located in the frame configuration portion of the front end functionally rather than the modulation portion.

For example, in a system such as DVB, a field having a length of TmpPadNum may be reserved in advance in a baseband frame (so-called BBFRAME) usually composed of a K-bit (information) bit string according to the value of X+Y. 82 is a diagram showing the relationship between the length of K bits of the BBFRAME and the length of the secured TmpPadNum. BBHEADER is the header of BBFRAME. DATAFIELD is a data bit string of length DFL (bits). The first padding length, which is the length of the hatched portion, does not depend on the value of X+Y, and is a padding used to adjust the number of bits less than the DFL, such as an integer multiple of a TS packet. As shown in the figure, TmpPadNuM is a bit length for securing TmpPadNum, which is the number to temporarily pad separately from the first padding.

Further, the front end located at the input end may secure the field length based on the codeword length N (or the index of a table giving information equivalent thereto (including the encoding rate, etc.)).

(Example 2) When the front end portion 8001A in Fig. 80 is another encoding portion that executes an outer code encoding process:

The front end 8001A of FIG. 80 may be an outer code processing unit that generates an outer code concatenated as an outer code of the codeword of the encoding unit 502 in the modulator.

In this case, by changing the encoding rate (codeword length) of the outer code, it is possible to secure a field corresponding to X+Y. For example, when the BCH code is used for the outer code processing, the codeword length Nouter (of the outer code) can be shortened by X+Y by reducing the degree of the generated polynomial g(x) by X+Y. In this way, it is possible to secure a field of X+y bits.

Various modifications can be considered for changing the order. For example, the value (or index for order change) is set in the table so that the degree of the generated polynomial g(x) is smaller than when adjustment is unnecessary, and g(x) is generated through the control signal by this table. It may be given as much as possible.

A "field" is a field containing one or more plural values for padding or intermittently inserting the number of TmpPadNum regardless of whether continuous or discrete in the bit array among the K-bit bit string processed by the encoding unit at the rear stage.

The control unit instructs to fill the adjustment bit string (known information) in the field of the length TmpPadNum secured at the front end (S8105). The front end unit 8001A of FIG. 80 then fills the field with an adjustment bit stream and outputs a K-bit bit stream 501 to the encoder 502 (S8105).

Here, it is assumed that the known information (adjustment bit string) is, for example, &quot;all values are 0 (zero)&quot;. Then, the encoding unit 102 of FIG. 80 encodes the K bits composed of the known information and the information to be transmitted to obtain an N-bit codeword composed of the information and parity (S8107). In addition, as a simple method of encoding, there is a method in which known information (adjustment bit string) is set to "all values are 0 (zero)", but the known information is not limited thereto. It is good if the known information sequence can be shared by both parties on the decoding side. It is also possible to include bit interleaving processing in the processing result of the encoding unit 502 in FIG.

The rear end 8001B of FIG. 80 removes the temporarily inserted adjustment bit string (known information) (or a bit group corresponding to individual bits of the original adjustment bit string after being interleaved), so that the A second bit string (bit string after bit length adjustment) 8003 having a short number of bits is output (S8109). This processing may also be instructed by a value in a table indicating the position to be deleted according to the value of X+Y.

(effect)

In the second bit string (bit string after bit length adjustment) 8003 of N-TmpPadNum (bit) in which the adjustment bit string temporarily inserted for the code length N of the codeword of the LDPC code of the i-th block is deleted The number of bits in the 2-bit string (bit string after bit length adjustment) 8003 is determined by the set of the first modulation method of s1(t) and the second modulation method of s2(t) for which N-TmpPadNum is set (X+Y) ) is a multiple of

And when the codeword length (block length (code length)) N of the codeword vector (of the LDPC code) of the i-th block is fixed as 64800 bits, the value of X+Y, that is, the first modulation of s1(t) When the set of the method and the second modulation method of s2(t) is changed (or the setting of the set of the set of the first modulation method of s1(t) and the set of the second modulation method of s2(t) is changeable), appropriately temporarily to change the number of control bit strings (number of bits TmpPadNum) to be inserted and then deleted. (Also, depending on the value of X+Y (the set of the first modulation method of s1(t) and the second modulation method of s2(t)), TmpPadNum may be zero in some cases).

As a result, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is the same for a set of complex signals based on a combination of all modulation methods regardless of the value of N. The number of bits (X+Y) that can be transmitted by the frequency and the first complex signal s1 and the second complex signal s2 transmitted at the same time is such that data of a plurality of blocks (of the error correction code) is not included. Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

FIG. 83 is a configuration of a modulator different from that of FIG. 80 . Note that, in Fig. 83, the same reference numerals are assigned to those operating in the same manner as in Fig. 80. As shown in Figs. 83 differs from FIG. 80 in that the bit interleaver 502BI is inserted at the rear end of the encoder 502 and the front end of the rear end 8001B. Note that the operation of FIG. 83 will be described with reference to FIG. 84 .

84 is a diagram for explaining the bit length of the bit strings 501 to 8003.

The bit string 501 is a bit string output from the front end unit 8001A, and is a K-bit (information) bit string including a field of length TmpPadNum (bits) for known information.

The bit string 503Λ is a bit string output by the encoder 502, and is a bit string (first bit string) of length N bits, which is a codeword of an error correction code.

The bit string 503V is a bit string having a length of N bits in which the order of bit values is changed by the bit interleaver.

The bit string 8003 is a second bit string (bit string after bit length adjustment) adjusted to a length of N-TmpPadNum bits output from the rear end portion 8001B. Further, the bit string 8003 is a bit string in which the known information of the TmpPadNum bit is deleted from the bit string 503V.

<Effect of this embodiment>

With the above configuration, it is possible to estimate (decode processing) the codeword of the error correction code without requiring special processing in decoding on the receiving side.

Further, a configuration is adopted in which, on the transmitting side, the inserted adjustment bit string is known information, and only the primarily inserted adjustment bit string (known information) is deleted. For this reason, in the decoding of the receiver, since the error correction code is decoded using known information, the possibility of obtaining a high error correction capability increases.

In addition, in the case where the pre-processing unit generates an external code of BCH or RS, it is easy to secure a field, and it is more suitable.

(Embodiment 5)

In the fifth and sixth embodiments, the invention relating to a method and configuration for decoding (on the receiving device side) the bit string 501 transmitted from the transmitting device will be described.

More specifically, it is generated from the (information) bit string 501 by the "modulation signal generating part" (modulation unit) of the first to fourth embodiments, and transmitted via processing such as MIMO precoding processing. This is a process of performing demodulation (detection) processing on the complex signals s1(t) and s2(t) and restoring the complex signals x1(t) and x2(t) into a bit string.

Also, x1(t) and x2(t) are complex baseband signals obtained from the reception signals received by the respective reception antennas.

Fig. 85 is a bit string decoding unit of a receiving apparatus that receives a modulated signal transmitted based on the transmission method of the first to third embodiments;

In the figure, a 'carrier' (caret) indicates an estimation result of a signal of a reference sign below the caret. In the following description, a carry is omitted by adding a ^ in front of the reference sign.

The bit string decoding unit of FIG. 85 includes a detection (demodulation) unit, a bit length adjustment unit, and an error correction decoding unit.

The detection (demodulation) unit includes the first number of bits X included in the first complex signal s1 and the second complex signal s2 from the complex baseband signals x1(t) and x2(t) obtained from the received signal received from each receiving antenna. Data such as a hard decision value or soft decision value or log log likelihood or log likelihood ratio corresponding to the number of bits (X + Y) bits of the second number of bits Y is generated, and data corresponding to a second bit string that is an integer multiple of X + Y print the heat In addition, ^5703 is a data string corresponding to the "second bit string" (R202) of N+PadNum, for example.

The bit length adjusting unit of FIG. 85 receives a data string ^5703 corresponding to the bit string of the second bit length as an input. Then, the bit length adjustment unit extracts data corresponding to the "adjustment bit string" of the length PadNum inserted from the transmitting side and outputs it to the error correction decoding unit, and also outputs the data string (^503V) corresponding to the N bit strings. .

The deinterleaver deinterleaves the data streams (^503V) corresponding to the N bit streams, and outputs the deinterleaved N data streams (^503Λ) to the error correction decoding unit. ^503V and ^503A are data strings corresponding to bit strings 503V and 503A, respectively.

The error correction decoding unit of Fig. 85 receives data corresponding to the "adjustment bit string" of length PadNum and N data strings (^503Λ) after deinterleaving as inputs, and error correction decoding (for example, when using the LDPC code) A K-bit information bit estimation sequence is obtained by performing reliability propagation (BP (Belief Propagation)) decoding (eg sum-product decoding, min-sum decoding, normalized BP decoding, offset BP decoding, etc.) or bit flipping decoding). .

In addition, when a bit interleaver is used on the transmitting side, a deinterleaver is inserted as shown in FIG. 85 . On the other hand, when the bit interleaver is not used on the transmission side, the deinterleaver in FIG. 85 becomes unnecessary.

Fig. 86 is a diagram for explaining input/output of the bit string adjusting unit of the present embodiment.

^5703 is a data string corresponding to a bit string having a length of N bits + PadNum. Zeros surrounded by six squares are the steering bit string. ^503 denotes a data string corresponding to an N-bit codeword output by the bit length adjusting unit.

87 is a bit string decoding unit of a receiving apparatus that receives a modulated signal transmitted based on the transmission method of the fourth embodiment;

The detection (demodulation) unit includes the first number of bits X included in the first complex signal s1 and the second complex signal s2 from the complex baseband signals x1(t) and x2(t) obtained from the received signal received from each receiving antenna. Data such as a hard decision value or soft decision value or log log likelihood or log likelihood ratio corresponding to the number of bits (X + Y) bits of the second number of bits Y is generated, and data corresponding to a second bit string that is an integer multiple of X + Y A column 8701 is output. Note that 8701 is a data string corresponding to, for example, "second bit string" 8003 (FIG. 83) of N-TmpPadNum.

The log-likelihood ratio inserting unit in Fig. 87 receives a data string 8701 corresponding to the second bit string as an input, and for the data string 8701 corresponding to the second bit string as described in Embodiment 4 "Known information deleted by the transmitting side" A data string 8702 after adjustment is output by inserting a log-likelihood ratio (for TmpPadNum) corresponding to the information "adjustment bit string" (for example). Accordingly, the data columns 8702 after adjustment are N data columns.

The deinterleaver of FIG. 87 receives the adjusted data string 8702 as an input, rearranges the data, and outputs the rearranged data string 8703 .

The error correction decoding unit of FIG. 87 receives the rearranged data string 8703 as an input, and decodes the error correction decoding (eg, belief propagation (BP) when using the LDPC code) decoding (eg, sum- product decoding, min-sum decoding, normalized BP decoding, offset BP decoding, etc.) or bit flipping decoding) to obtain a K-bit information bit estimation sequence. Then, the known information deletion unit obtains and outputs data 8704 in which known information is deleted from the K-bit information bit estimation sequence.

In addition, when a bit interleaver is used on the transmitting side, a deinterleaver is inserted as shown in FIG. On the other hand, when the bit interleaver is not used on the transmission side, the deinterleaver in FIG. 87 becomes unnecessary.

<Effect of this embodiment>

With reference to Figs. 85 and 87, the operation of the receiving apparatus in the case of transmitting the modulated signal using the transmission method of the first to fourth embodiments has been described.

In any receiving device, the operation of the receiving device is changed based on the information corresponding to the modulation method for s1(t) and the modulation method for s2(t) used by the transmitting device, and the operation of error correction decoding is performed to obtain high data. It is highly probable that the reception quality of

In addition, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is the same for a set of complex signals based on a combination of all modulation methods regardless of the value of N. The frequency and the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same time are such that data of a plurality of blocks (of the error correction code) are not included; Accordingly, there is a high possibility that the memory of the receiving apparatus can be reduced by properly operating the error correction decoding unit to perform demodulation and decoding.

(Embodiment 6)

88 is a bit string decoding unit of the receiving apparatus of the present embodiment.

The operations of the deinterleave unit and the detection unit are the same as those of the fifth embodiment.

The detection unit outputs a bit string (^6003) into which the adjustment bit string of any one of the first to ninth modifications of the adjustment bit string described in Embodiment 2 is inserted as the bit string.

The bit length adjusting unit of the present embodiment includes a data string corresponding to the second bit string (for example, log-likelihood ratio corresponding to the second bit string), partial data corresponding to a bit value of a predetermined portion among the N bits (for example, log-likelihood ratio).

The bit string adjusting section executes, for example, the following processing in order to obtain a high error correction capability.

• Data corresponding to the adjustment bit string is selectively extracted from the bit string (^6003) of N+TmpPadNum bits.

• Generate, for example, a logarithmic likelihood ratio Additional-Prob, related to, for example, the adjustment bit string from data corresponding to individual bits of the adjustment bit string.

· The created AdditionalProb is supplied to the error correction decoding unit.

The error correction decoding unit estimates the N-bit codeword of the error correction code using the AdditionalProb and partial data (eg, log-likelihood ratio) corresponding to the bit value of a predetermined part among the N bits.

At that time, the error correction decoding unit performs, for example, sum-product decoding based on the Tanner graph structure (parity check matrix) of the second embodiment.

89 is a diagram conceptually explaining the processing of the present embodiment.

In the drawings, circles and squares indicate the same information as those described in the second embodiment.

In the figure, ^6003 is the second bit string of the bit length N+padNum output by the demapper.

In the figure, ^503 is a bit string (^503) of bit length N output by the bit length adjusting unit. In the figure, Additional-Prob is a new log-likelihood ratio obtained from, for example, a log-likelihood ratio of an adjustment bit string. Using this new log-likelihood ratio, the log-likelihood ratio of the "predetermined portion" described in the various modifications of the second embodiment is given.

For example, when the "predetermined part" is p_last, a log-likelihood ratio of p_last can be given. Further, by adding p_2ndlast to a predetermined portion, a log-likelihood ratio of p_2ndlast, or indirectly, a log-likelihood ratio of p_last is given.

Thereby, the possibility of obtaining a high error correction capability increases.

(Embodiment 7)

In Embodiments 1 to 4, the transmission method and the apparatus on the transmission side were described, and in the Embodiments 5 and 6, the reception method and the apparatus on the reception side were described. In this embodiment, a supplementary explanation will be given on the relationship between the transmission method and the apparatus on the transmission side, the reception method, and the apparatus on the reception side.

Fig. 90 is a diagram showing the relationship between the transmitting apparatus and the receiving apparatus according to the present embodiment.

As shown in FIG. 90, the transmitter transmits two modulated signals from different antennas, respectively. The radio processing unit of the transmitter executes, for example, OFDM signal processing, frequency conversion, power amplification, and the like.

Then, the signal generating unit 9001 of the transmitting apparatus of FIG. 90 receives the transmission information as input, executes processing such as encoding, mapping, and precoding, and outputs the modulated signals z1(t) and z2(t) after precoding. do. Accordingly, the signal generating unit 9001 performs the processing related to the transmission method described in the first to fourth embodiments and the processing of the precoding described above.

The receiving antenna RX1 of the receiving device of FIG. 90 receives a multiplexed signal in a space between the signal transmitted from the antenna TX1 of the transmitting device and the signal transmitted from the transmitting antenna TX2.

Similarly, the receiving antenna RX2 of the receiving device receives the multiplexed signal in the space of the signal transmitted from the antenna TX1 of the transmitting device and the signal transmitted from the transmitting antenna TX2.

In the channel estimator of the receiving apparatus of FIG. 90, estimation of the channel variation of the modulated signal z1(t) and the channel variation of the modulated signal z2(t) is performed at each antenna.

Then, in the signal processing unit 9002 of the receiving apparatus in Fig. 90, the reception processing described in the fifth and sixth embodiments is performed, and as a result, the receiving apparatus obtains the estimation result of the transmission information transmitted by the transmitting apparatus.

In addition, in the preceding description, the description was made according to the first to sixth embodiments, but in the following embodiments, the transmission method and the configuration of the transmitting device are described, the description is about the transmitting device in FIG. In the case where the method and the configuration of the receiving device are described, the description of the receiving device in FIG. 90 is given.

(Embodiment 8)

In this embodiment, a modified example of the "adjustment method for shortening the surplus so that the bit length is a multiple of the value of X+Y" described in the fourth embodiment will be described.

(Example 1)

Fig. 91 shows the configuration of the modulator on the transmission side of the present embodiment. In Fig. 91, the same reference numerals are assigned to those operating in the same manner as in the drawings shown in the embodiment described above.

The encoding unit 502 receives the control information 512 and the K-bit information 501 of the i-th block as inputs, and includes an error correction code method, a coding rate, and a block length (code length) included in the control information 512 . ), an N-bit codeword 503 of the i-th block is output by executing error correction encoding such as LDPC encoding.

The bit length adjusting unit 9101 receives the control information 512 and the N-bit codeword 503 of the i-th block as inputs, and a modulation method and s2(t) for s1(t) included in the control information 512 . ), the number of bits to be deleted from the N-bit codeword 503 is determined based on the modulation method information for A data string 9102 of N-PunNum bits is output by deleting the data of . Also, similar to the embodiment described above, N-PunNum determines PunNuM that is a multiple of "the value of X+Y" (in addition, the first modulation method of the value of X+Y (s1(t) and the second modulation method of s2(t)) Depending on the set of modulation schemes), PunNum may be 0 (zero)).

However, the "value of X+Y" is the same as that described in the embodiment described above.

The mapping unit 504 receives the control information 512 and a data string 9102 of N-PunNum bits as inputs, and a modulation method for s1(t) included in the control information 512 and a modulation method for s2(t). From the information on the modulation method, mapping is performed based on the modulation method for s1(t) and the modulation method for s2(t) to obtain a first complex signal s1(t) (505A) and a second complex signal s2(t). (505B) is output.

92 shows the bit length of each bit string, and one square represents one bit. The K-bit information 501 of the i-th block of FIG. 91 is as shown in FIG. 92 .

In addition, the N-bit codeword 503 of the i-th block of FIG. 91 is as shown in FIG. 92 . Then, the PunNum bit is selected from the N-bit codeword 503 of the i-th block and deleted to generate an N-PunNum-bit data string 9102 (refer to FIG. 92).

(Example 2)

Fig. 93 shows the configuration of a modulator on the transmission side different from that in Fig. 91 of the present embodiment. In Fig. 93, the same reference numerals are assigned to those operating in the same manner as in the drawings shown in the embodiment described above.

The encoding unit 502 receives the control information 512 and the K-bit information 501 of the i-th block as inputs, and includes an error correction code method, a coding rate, and a block length (code length) included in the control information 512 . ), an N-bit codeword 503 of the i-th block is output by performing error correction encoding such as LDPC encoding.

The bit interleaver 9103 receives the control information 512 and the N-bit codeword 503 of the i-th block as inputs, and based on the information of the bit interleaving method included in the control information 512, the N of the i-th block. An N-bit codeword 9104 of the interleaved i-th block is output by rearranging the order numbers of the bit codewords.

The bit length adjusting unit 9101 receives the control information 512 and the N-bit codeword 9104 of the interleaved i-th block as inputs, and a modulation method and s2 for s1(t) included in the control information 512 . The number of bits to be deleted from the N-bit codeword 9104 of the i-th block after interleaving is determined based on the modulation method information for (t) or the “value of X+Y”, and the number of bits PunNum after interleaving is determined. PunNum-bit data is deleted from the N-bit codeword 9104 of the i block, and an N-PunNum-bit data string 9102 is output. Also, similarly to the embodiment described above, N-PunNum determines PunNuM that is a multiple of "the value of X+Y" (in addition, the first modulation method of the value of X+Y (s1(t) and the second modulation method of s2(t)) 2 (PunNum may be 0 (zero) depending on the set of modulation schemes).

However, the "value of X+Y" is the same as that described in the embodiment described above.

The mapping unit 504 receives the control information 512 and a data string 9102 of N-PunNum bits as inputs, and a modulation method for s1(t) included in the control information 512 and a modulation method for s2(t). The first complex signal s1(t) (505A) and the second complex signal s2(t) ( 505B).

94 shows the bit length of each bit string, and each square represents 1 bit. The K-bit information 501 of the i-th block of FIG. 94 is as shown in FIG.

In addition, the N-bit codeword 503 of the i-th block of FIG. 93 is as shown in FIG. 94 . Thereafter, as shown in FIG. 94, bit interleaving, that is, bit rearrangement, is performed on the N-bit codeword 503 of the i-th block to generate the interleaved N-bit codeword 9104 of the i-th block. .

Then, PunNum bits are selected from the N-bit codeword 9104 of the i-th block after interleaving, and an N-PunNum-bit data string 9102 is generated by performing deletion (refer to FIG. 94).

(effect)

As described above, in the N-PunNum-bit data string 9102 output from the bit length adjusting unit 9101, N-PunNum determines PunNuM in which N-PunNum is a multiple of “the value of X+Y”.

As a result, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, N for a set of complex signals based on a combination of all modulation methods, not depending on the value of N. Since -PunNum is a multiple of "the value of X+Y", the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time is plural (error correction). It is assumed that the data of the block of code is not included. Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

Also, when the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation method of s2(t)) 93, by installing the bit length adjusting unit 9101 at the rear end of the bit interleaver 9103, the memory size of the bit interleaver can be adjusted to the first modulation method of s1(t) as shown in FIG. and s2(t) can be made constant regardless of the set of the second modulation scheme. Thereby, the effect that an increase in the memory of the bit interleaver can be prevented can be acquired. (If the order of the bit length adjusting unit 9101 and the bit interleaver 9103 is reversed, it is necessary to change the memory size according to the set of the first modulation method of s1(t) and the second modulation method of s2(t). Therefore, it becomes important to arrange the bit length adjusting unit 9101 at the rear end of the bit interleaver 9103. Also, in Fig. 93, the bit length adjusting unit 9101 is disposed immediately after the bit interleaver 9103. An interleaver for performing other interleaving may be inserted between 9103) and the bit length adjusting unit 9101, or other processing units may be inserted).

In addition, a plurality of codeword lengths (block length (code length)) of the error correction code may be prepared. For example, it is assumed that Na bits and Nb bits are prepared as the codeword length (block length (code length)) of the error correction code. Codeword length (block length (code length)) When an error correction code of Na bits is used, the bit interleaver memory size is Na bits to perform bit interleaver, and then, the bit length adjusting unit 9101 of FIG. Delete the required number of bits in Similarly, when the error correction code of the codeword length (block length (code length)) Nb bits is used, the bit interleaver memory size is Nb bits to perform the bit interleaver, and the bit length adjusting unit 9101 of FIG. 93 is necessary if necessary. A number of bits are deleted.

(Example 3)

Fig. 93 shows the configuration of a modulator on the transmission side different from that in Fig. 91 of the present embodiment. In Fig. 93, the same reference numerals are assigned to those operating in the same manner as in the drawings shown in the embodiment described above.

The encoding unit 502 receives the control information 512 and the K-bit information 501 of the i-th block as inputs, and includes an error correction code method, a coding rate, and a block length (code length) included in the control information 512 . ), an N-bit codeword 503 of the i-th block is output by performing error correction encoding such as LDPC encoding.

The bit interleaver 9103 receives the control information 512 and z number of N-bit codewords, that is, N×z bits as inputs (where z is an integer greater than or equal to 1). Based on the information on the bit interleaving method included, the order of the bits of N×z is rearranged to output the interleaved bit string 9104 .

The bit length adjusting unit 9101 receives the control information 512 and the interleaved bit string 9104 as inputs, and includes a modulation method for s1(t) and a modulation method for s2(t) included in the control information 512 . The number of bits to be deleted from the interleaved bit string 9104 is determined based on the information of , or the “value of X + Y”, and the PunNum bit data is deleted from the interleaved interleaved bit string 9104. A data string 9102 of N×z-PunNum bits is output.

Also, as in the above-described embodiment, N×z-PunNum determines PunNuM that is a multiple of “the value of X+Y” (in addition, the first modulation method of the value of X+Y (s1(t) and s2(t)) PunNum may be 0 (zero) depending on the set of the second modulation scheme of .

However, the "value of X+Y" is the same as that described in the embodiment described above.

The mapping unit 504 receives the control information 512 and the data string 9102 of N×z-PunNum bits as inputs, and a modulation method and s2(t) for s1(t) included in the control information 512 . Mapping based on the modulation method for s1(t) and the modulation method for s2(t) is performed from the information of the modulation method for ) 505B.

95 shows the bit length of each bit string, and each square represents 1 bit. Reference numeral 501 in Fig. 95 denotes z bundles of K-bit information.

In addition, 503 of z codewords of N bits in FIG. 95 are as shown in FIG. 95 . Thereafter, as shown in FIG. 95 , bit interleaving, that is, bit rearrangement, is performed for z number of N-bit codewords 503 to generate an N×z-bit interleaved bit string 9104 .

Then, PunNum bits are selected from the Nxz-bit interleaved bit stream 9104 and deleted to generate an Nxz-PunNum-bit data stream 9102 (refer to Fig. 95).

(effect)

As described above, in the data string 9102 of N×z-PunNum bits output from the bit length adjusting unit 9101, PunNuM in which N×z-PunNum is a multiple of “the value of X+Y” is determined.

As a result, when the encoder outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, for a set of complex signals based on a combination of all modulation methods, not depending on the value of N, N Since xz-PunNum is a multiple of “the value of X+Y”, the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time is z It is assumed that data of blocks other than words are not included. Thereby, there is a high possibility that the memory of the transmitting apparatus and/or the receiving apparatus can be reduced.

Also, when the value of X+Y, that is, the set of the first modulation method of s1(t) and the second modulation method of s2(t) is changed (or the first modulation method of s1(t) and the second modulation method of s2(t)) 2), by installing the bit length adjusting unit 9101 at the rear end of the bit interleaver 9103 as shown in FIG. s2(t) can be made constant regardless of the set of the second modulation scheme. Thereby, the effect that an increase in the memory of the bit interleaver can be prevented can be acquired. (If the order of the bit length adjusting unit 9101 and the bit interleaver 9103 is reversed, it is necessary to change the memory size according to the set of the first modulation method of s1(t) and the second modulation method of s2(t). Therefore, it becomes important to arrange the bit length adjusting unit 9101 at the rear end of the bit interleaver 9103. In FIG. 93, the bit length adjusting unit 9101 is disposed immediately after the bit interleaver 9103. An interleaver for performing other interleaving may be inserted between 9103) and the bit length adjusting unit 9101, or other processing units may be inserted).

In addition, a plurality of codeword lengths (block length (code length)) of the error correction code may be prepared. For example, it is assumed that Na bits and Nb bits are prepared as the codeword length (block length (code length)) of the error correction code. Codeword length (block length (code length)) When an error correction code of Na bits is used, the bit interleaver memory size is Na bits to perform bit interleaver, and then, the bit length adjusting unit 9101 of FIG. Delete the required number of bits. Similarly, when the error correction code of the codeword length (block length (code length)) Nb bits is used, the bit interleaver memory size is Nb bits to perform the bit interleaver, and the bit length adjusting unit 9101 in FIG. bit is deleted.

Also, a plurality of bit interleave sizes may be prepared for the code length (block length (code length)) of each error correction code. For example, when the codeword length of the error correction code is N bits, it is assumed that N×a bits and N×b bits are prepared as the bit interleave size (provided that both a and b are integers greater than or equal to 1). Then, bit interleaver is performed when N×a bits are used as the bit interleave size. After that, the bit length adjusting unit 9101 of FIG. 93 deletes the necessary number of bits if necessary. Similarly, bit interleaver is performed when N×b bits are used as the bit interleave size, and thereafter, the bit length adjusting unit 9101 of FIG. 93 deletes the required number of bits if necessary.

(Embodiment 9)

In this embodiment, the operation of the receiving apparatus receiving the modulated signal transmitted by the transmission method described in the eighth embodiment, in particular, the operation of the bit string decoding unit will be described.

Complex signals s1(t), s2 ( t) This is a process of performing demodulation (detection) processing on the signal and restoring it to a bit string from the complex signals x1(t) and x2(t).

Also, x1(t) and x2(t) are complex baseband signals obtained from the reception signals received by the respective reception antennas.

96 is a bit string decoding unit of a receiving apparatus that receives a modulated signal transmitted based on the transmission method of the eighth embodiment.

In the figure, a 'carrier' (caret) indicates an estimation result of a signal of a reference sign below the caret. In the following description, the carriage is omitted by adding ^ before the reference sign.

The bit string decoding unit of FIG. 96 includes a detection (demodulation) unit, a bit length adjustment unit, and an error correction decoding unit.

The detection (demodulation) unit of FIG. 96 includes the first number of bits X and the second complex signal included in the first complex signal s1 from the complex baseband signals x1(t) and x2(t) obtained from the received signal received from each receiving antenna. N-PunNum-bit data that is an integer multiple of X+Y by generating data such as a hard decision value or soft decision value or log likelihood or log likelihood ratio corresponding to the number of bits (X+Y) bits of the second number of bits Y included in s2 A data string 9601 corresponding to a column or a data string 9102 of N×z-PunNum bits is output.

The log-likelihood ratio insertion unit of FIG. 96 receives as an input a data string 9601 corresponding to an N-PunNum-bit data string or N×z-PunNum-bit data string 9102, Inserting log-likelihood ratios in bits, that is, inserting PunNum log-likelihood ratios into a data string 9601 corresponding to a data string of N-PunNum bits or a data string 9102 of N×z-PunNum bits, Alternatively, N×z log-likelihood ratio sequences 9602 are output.

The deinterleaver of FIG. 96 receives N or N×z log-likelihood ratio sequences 9602 as inputs, performs deinterleaving, and outputs N or N×z log-likelihood ratio sequences 9603 after deinterleaving.

The error correction decoding unit of FIG. 96 receives as input N or N×z log-likelihood ratio sequences 9603 after deinterleaving, and performs error correction decoding (for example, when using the LDPC code, reliability propagation (BP) )) decoding (eg, sum-product decoding, min-sum decoding, normalized BP decoding, offset BP decoding, etc.) or bit flipping decoding) to obtain a K-bit or K×z-bit information bit estimation sequence.

In addition, when a bit interleaver is used on the transmitting side, a deinterleaver is inserted as shown in FIG. On the other hand, when the bit interleaver is not used on the transmission side, the deinterleaver in FIG. 96 becomes unnecessary.

<Effect of this embodiment>

96, the operation of the reception apparatus when the modulated signal is transmitted using the transmission method of the eighth embodiment has been described.

In any receiving apparatus, the operation of the receiving apparatus is changed based on information corresponding to the modulation method for s1(t) and the modulation method for s2(t) used by the transmitting apparatus, and the operation of error correction decoding is performed, resulting in high data It is highly probable that the reception quality of

In addition, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is the same for a set of complex signals based on a combination of all modulation methods regardless of the value of N. The frequency and the number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same time are such that data of a plurality of blocks (of the error correction code) are not included; Accordingly, there is a high possibility that the memory of the receiving apparatus can be reduced by properly operating the error correction decoding unit to perform demodulation and decoding.

(Embodiment 10)

So far, the bit length adjustment method when widely applied to the precoding method has been described. In this embodiment, a description will be given of a bit length adjustment method when a transmission method in which a phase change is performed regularly after precoding is used is used.

Fig. 97 is a diagram of a portion for executing precoding-related processing in the transmitting apparatus of the present embodiment.

The mapping unit 9702 of FIG. 97 receives a bit sequence 9701 and a control signal 9712 as inputs. And it is assumed that the control signal 9712 specifies that two streams are transmitted as a transmission method. Also, it is assumed that the control signal 9712 designates the modulation method ? and the modulation method ? as the respective modulation methods of the two streams. In addition, modulation method α is a modulation method that modulates x-bit data, and modulation method β is a modulation method that modulates y-bit data (for example, in the case of 16 QAM (16 Quadrature Amplitude Modulation), 4-bit data is modulated. It is a modulation method that modulates 6-bit data in the case of 64QAM (64 Quadrature Amplitude Modulation).

Then, the mapping unit 9702 modulates the x-bit data among the x+y-bit data by the modulation method α to generate and output the baseband signal s1(t) 9703A, and also the remaining y-bit data data. is modulated with the modulation method β to output a baseband signal s2(t) _9703B (in addition, in FIG. A separate mapping unit for generating ₂ (t) may exist, in this case, the bit sequence 9701 is distributed to a mapping unit for generating s ₁ (t) and a mapping unit for generating s ₂ (t) do).

Further, s ₁ (t) and s ₂ (t) are expressed by complex numbers (however, either a complex number or a real number may be used), and t is time. In addition, when a transmission method using a multi-carrier such as OFDM (Orthogonal Frequency Division Multiplexing) is used, s ₁ and s ₂ are functions of frequency f like s ₁ (f) and s ₂ (f), or s ₁ It can also be thought of as a function of time t, frequency f, such as (t, f) and s ₂ (t, f).

Hereinafter, the baseband signal, the precoding matrix, the phase change, etc. are described as a function of time t, but it may be considered as a function of frequency f, time t and frequency f.

Therefore, there are cases where the baseband signal, the precoding matrix, and the phase change are described as a function of the symbol number i, but in this case, a function of time t, a function of frequency f, and a function of time t and frequency f good to think That is, the symbol and the baseband signal may be generated and disposed in the time axis direction or may be generated and disposed in the frequency axis direction. Further, the symbol and the baseband signal may be generated and arranged in the direction of the time axis and the direction of the frequency axis.

The power changing unit 9704A (power adjusting unit 9704A) receives the baseband signal s ₁ (t) 9703A and the control signal 9712 as inputs, and sets a real number P ₁ based on the control signal 9712, , P ₁ ×s ₁ (t) is output as the signal 9705A after power change (note that P ₁ is a real number, but may be a complex number).

Similarly, the power changing unit 9704B (the power adjusting unit 9704B) receives the baseband signal s ₂ (t) 9703B and the control signal 9712 as inputs, sets a real number P ₂ , and sets P ₂ ×s ₂ (t) ) is output as the signal 9705B after power change (note that P ₂ is a real number, but may be a complex number).

The weight synthesizing unit 9706 receives the signal after power change 9705A, the signal after power change 9705B, and the control signal 9712 as inputs, and based on the control signal 9712, the precoding matrix F (or F(i) )) is set. When the slot number (symbol number) is i, the weighted synthesizing unit 9706 executes the following operation.

Here, a, b, c, and d can be expressed as complex numbers (which may be real numbers), and three or more of a, b, c, and d must not be 0 (zero). It is assumed that a, b, c, and d are coefficients determined by determining the sets of the modulation method of s ₁ (t) and the modulation method of s ₂ (t).

Then, the weighted synthesis unit 9706 outputs u ₁ (i) in the formula (R10-1) as the post-weighted signal 9707A, and converts u ₂ (i) in the formula (R10-1) to the post-weighted synthesis signal 9707A. output as a signal 9707B.

The phase change unit 9708 receives the u ₂ (i) (signal 9707B after weighted synthesis) and the control signal 9712 in the equation (R10-1) as inputs, and based on the control signal 9712, the equation ( The phase of u ₂ (i) (signal 9707B after weighted synthesis) in R10-1) is changed.

Therefore, the signal after changing the phase of u ₂ (i) (signal 9707B after weighted synthesis) in equation (R10-1) is expressed as e ^jθ (i) × u ₂ (i), and e ^jθ ( The phase change unit 9708 outputs i)×u ₂ (i) as a signal 9709 after the phase change (j is an imaginary number unit). In addition, a characteristic part is that the value of the phase to be changed is a function of i as in θ(i).

The power change unit 9710A receives the weighted synthesis signal 9707A (u ₁ (i)) and the control signal 9712 as inputs, and sets a real number Q ₁ based on the control signal 9712, Q ₁ × u ₁ (t) is output as the signal 9711A (z ₁ (i)) after power change (note that Q ₁ is a real number, but may be a complex number).

Similarly, the power change unit 9710B receives the signal 9709 (e ^jθ (i) × u ₂ (i)) and the control signal 9712 after the phase change as inputs, and based on the control signal 9712, the real number Q ₂ is set, and Q ₂ ×e ^jθ (i) × u ₂ (i) is output as the signal 9711B (z ₂ (i)) after power change (note that Q ₂ is a real number, but may be a complex number).

Accordingly, the respective outputs z ₁ (i) and z ₂ (i) of the power changing units 9710A and 9710B in FIG. 97 are expressed as follows.

Also, as a method of realizing the formula (R10-2), there is a configuration in FIG. 98 different from that in FIG. The difference between FIGS. 97 and 98 is that the order of the power change unit and the phase change unit is changed. (The function itself of executing power change and phase change does not change). In this case, z ₁ (i) and z ₂ (i) are expressed as follows.

In addition, z ₁ (i) of the formula (R10-2) and z ₁ (i) of the formula (R10-3) are the same, and z 2 (i) of the formula (R10-2) and z ₂ (i) of the formula (R10-) The same is true for z ₂ (i) in 3).

The value θ(i) of the changing phase in the equations (R10-2) and (R10-3) is, for example, set so that θ(i+1)-θ(i) is a fixed value, then the direct wave dominates the propagation There is a high possibility that the receiving device can obtain good data reception quality in a radio wave environment of However, the method of assigning the value θ(i) of the phase to be changed is not limited to this example. Incidentally, the relationship between the method of assigning θ(i) and the operation of the bit length adjusting unit will be described in detail later.

Fig. 99 shows an example of the configuration of a signal processing unit that is performed on the signals z ₁ (i) and z ₂ (i) obtained in Figs. 97 and 98 .

The inserting unit 9724A receives the signal z ₁ (i) 9721A, the pilot symbol 9722A, the control information symbol 9723A, and the control signal 9712 as inputs, so as to construct a frame included in the control signal 9712. Accordingly, a pilot symbol 9722A and a control information symbol 9723A are inserted into the signal (symbol) z ₁ (i) 9721A, and a modulated signal 9725A according to the frame configuration is output.

The pilot symbol 9722A and the control information symbol 9723A are symbols modulated by BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), or the like (other modulation schemes may be used).

The radio unit 9726A receives the modulated signal 9725A and the control signal 9712 as inputs, and performs frequency conversion, amplification, etc. processing on the modulated signal 9725A based on the control signal 9712 (OFDM method). is used, processing such as an inverse Fourier transform is performed) A transmission signal 9727A is output, and the transmission signal 9727A is output as a radio wave from the antenna 9728A.

The inserting unit 9724B receives the signal z ₂ (i) 9721B, the pilot symbol 9722B, the control information symbol 9723B, and the control signal 9712 as inputs, so as to construct a frame included in the control signal 9712. Accordingly, a pilot symbol 9722B and a control information symbol 9723B are inserted into the signal (symbol) z ₂ (i) 9721B, and a modulated signal 9725B according to the frame configuration is output.

The pilot symbol 9722B and the control information symbol 9723B are symbols modulated by BPSK (Binary Phase Shift Keying), QPSK (Quadrature Phase Shift Keying), or the like (other modulation schemes may be used).

The radio unit 9726B receives the modulated signal 9725B and the control signal 9712 as inputs, and performs frequency conversion, amplification, etc. processing on the modulated signal 9725B based on the control signal 9712 (OFDM method). is used, processing such as an inverse Fourier transform is performed) A transmission signal 9727B is output, and the transmission signal 9727B is output as a radio wave from the antenna 9728B.

Here, in the signal z ₁ (i) (9721A) and the signal z ₂ (i) (9721B), the signal z ₁ (i) (9721A) and the signal z ₂ (i) (9721B) of which i is the same number are the same ( A common) frequency is transmitted from different antennas at the same time (that is, it becomes a transmission method using the MIMO method).

The pilot symbol 9722A and the pilot symbol 9722B are symbols for performing signal detection, frequency offset estimation, gain control, channel estimation, and the like in the receiving apparatus, and are referred to as pilot symbols here. It may be used by another name of

In addition, the control information symbol 9723A and the control information symbol 9723B include information on a modulation method used by the transmitter, information on a transmission method, information on a precoding method, information on an error correction coding method, information on a coding rate of an error correction code, It is a symbol for transmitting information on the block length (code length) of the error correction code to the receiving device. Alternatively, the control information symbol may be transmitted using only one of the control information symbol 9723A and the control information symbol 9723B.

100 shows an example of a frame configuration in time-frequency in the case of transmitting two streams. In FIG. 100 , the horizontal axis represents frequency and the vertical axis represents time. For example, the configuration of symbols from carrier 1 to carrier 38 and time $1 to time $11 is shown.

100 shows the frame structure of the transmission signal transmitted from the antenna 9728A in FIG. 99 and the frame of the transmission signal transmitted from the antenna 9728B at the same time.

In FIG. 100, in the case of a frame of a transmission signal transmitted from the antenna 9728A in FIG. 99, a data symbol corresponds to a signal (symbol) z ₁ (i). And the pilot symbol corresponds to the pilot symbol 9722A.

In Fig. 100, in the case of a frame of a transmission signal transmitted from the antenna 9728B in Fig. 99, the data symbol corresponds to the signal (symbol) z ₂ (i). And the pilot symbol corresponds to the pilot symbol 9722B.

(Therefore, as previously described, in the signal z ₁ (i) (9721A) and the signal z ₂ (i) (9721B), i is the same number of the signal z ₁ (i) (9721A) and the signal z ₂ (i) ) 9721B are transmitted from different antennas with the same (common) frequency at the same time, and the configuration of the pilot symbol is not limited to Fig. 100. For example, the pilot symbol time interval and frequency interval are It is not limited to Fig. 100. In Fig. 100, a frame structure in which pilot symbols are transmitted from the antenna 9728A of Fig. 99 and the antenna 9728B of Fig. 99 at the same time and the same frequency (same (sub)carrier) is assumed, However, the present invention is not limited thereto, and for example, a pilot symbol is disposed in the antenna 9728A of FIG. 99 at time A and frequency a ((sub) carrier a), and at time A, frequency a ((sub) carrier a) ), it is assumed that no symbols are arranged on the antenna 9728B of Fig. 99, and that no symbols are arranged on the antenna 9728A of Fig. 99 at time B and frequency b ((sub) carrier b), It is good also as a configuration in which pilot symbols are arranged at 9728 B in FIG. 99 at B and frequency b ((sub)carrier b).

Note that, although only data symbols and pilot symbols are described in FIG. 99, other symbols, for example, symbols such as control information symbols, may be included in the frame.

97 and 98 , a case in which some (or all) of the power changing unit is present has been described as an example, but a case in which a part of the power changing unit is absent is also conceivable.

For example, in Fig. 97 or 98, when the power changing unit 9704A (power adjusting unit 9704A) and the power changing unit 9704B (power adjusting unit 9704B) do not exist, z ₁ (i) and z ₂ (i) is represented as follows.

97 or 98, when the power changing unit 9710A (power adjusting unit 9710A) and the power changing unit 9710B (power adjusting unit 9710B) do not exist, z ₁ (i) and z ₂ ( i) is expressed as follows.

97 or 98, a power changing unit 9704A (power adjusting unit 9704A), a power changing unit 9704B (power adjusting unit 9704B), a power changing unit 9710A (power adjusting unit 9710A)) , when the power changing unit 9710B (the power adjusting unit 9710B) does not exist, z ₁ (i) and z ₂ (i) are expressed as follows.

Next, the relationship between the method of assigning ?(i) and the operation of the bit length adjusting unit in the precoding-related processing will be described.

Incidentally, in the present embodiment, the unit of phase, for example, declination in the complex plane, is "radian".

If the complex plane is used, the complex number can be displayed in polar form in terms of polar coordinates. When a point (a, b) on the complex plane is mapped to a complex number z = a + jb (a and b are both real numbers, and j is an imaginary unit), if this point is expressed as [r, θ] in polar coordinates, a= r×cosθ, b=r×sinθ,

is established, r is the absolute value of z (r = |z|), and θ is the argument. And z = a + jb is expressed as r×e ^jθ .

In addition, the baseband signals, s1, s2, z1, and z2, become complex signals, but when the in-phase signal is I and the quadrature signal is Q, the complex signal is expressed as I+jQ (j is an imaginary unit). . At this time, I may be set to zero, and Q may be set to zero.

First, an example of a method for assigning ?(i) in the precoding-related processing will be described.

In the present embodiment, as an example, it is assumed that θ(i) is changed regularly. Specifically, for example, it is assumed that a period is given to the change of θ(i). It is assumed that the period of change of θ(i) is represented by z (however, z is an integer of 2 or more). At this time, when the period of change of θ(i) is set to z=9, it is assumed that the change of θ(i) is performed as follows, for example.

Slot number (symbol number) i,

When i = 9 × k + 0, θ (i = 9 × k + 0) = 0 radians

When i=9×k+1, θ(i=9×k+1)=(2×1×π)/9 radians

When i=9×k+2, θ(i=9×k+2)=(2×2×π)/9 radians

When i=9×k+3, θ(i=9×k+3)=(2×3×π)/9 radians

When i=9×k+4, θ(i=9×k+4)=(2×4×π)/9 radians

When i=9×k+5, θ(i=9×k+5)=(2×5×π)/9 radians

When i=9×k+6, θ(i=9×k+6)=(2×6×π)/9 radians

When i=9×k+7, θ(i=9×k+7)=(2×7×π)/9 radians

When i=9×k+8, θ(i=9×k+8)=(2×8×π)/9 radians

It is possible to form a period z=9 of change of θ(i) so that

In addition, the method of forming the period z=9 of the change of θ(i) is not limited to the above, and the nine phases λ ₀ , λ ₁ , λ ₂ , λ ₃ , λ ₄ , λ ₅ , λ ₆ , λ ₇ . , prepare λ ₈ ,

Slot number (symbol number) i,

When i=9×k+0, θ(i=9×k+0)=λ ₀ radians

When i=9×k+1, θ(i=9×k+1)=λ ₁ radian

When i=9×k+2, θ(i=9×k+2)=λ ₂ radians

When i=9×k+3, θ(i=9×k+3)=λ ₃ radians

When i=9×k+4, θ(i=9×k+4)=λ ₄ radians

When i = 9 × k + 5, θ (i = 9 × k + 5) = λ ₅ radians

When i=9×k+6, θ(i=9×k+6)=λ ₆ radians

When i=9×k+7, θ(i=9×k+7)=λ ₇ radians

When i=9×k+8, θ(i=9×k+8)=λ ₈ radians

A period z=9 of change of θ(i) can be formed such that (provided, k is an integer, and 0≤λ _v <2π (v is an integer of 0 or more and 8 or less)).

However, as a method for establishing the period z=9, there are the following two methods.

(1) Let x be an integer of 0 or more and 8 or less, and y be an integer of 0 or more and 8 or less y ≠ x, and λ _x ≠λ _y holds for all x and y satisfying these conditions.

(2) A period 9 is formed in which x and y exist in which x is an integer of 0 or more and 8 or less, y is an integer of 0 or more and y ≠ x, and λ _x ≠λ _y is satisfied.

Considering this in general, the period of change of θ(i) z (provided that z is an integer of 2 or more). The formation method is z phases, λ _v (v is an integer greater than or equal to 0 and less than or equal to z-1). prepare,

Slot number (symbol number) i,

When i = z × k + v, θ (i = z × k + v) = λ _v radians

_The period z of the change of θ(i) can be formed so that

However, there are the following two methods as a method for establishing the period z.

(1) Let x be an integer between 0 and z-1, and y be an integer of _y ≠ _x between 0 and z-1.

(2) Let x be an integer of 0 or more and z-1 and y be an integer of 0 or more and z-1 or less y≠x, and a period z in which x and y exist for which λ _x ≠λ _y holds is formed .

Next, the processing before the mapping unit 9702 in FIGS. 97 and 98 is the same as that described in the first to ninth embodiments. Hereinafter, a particularly important point in the present embodiment will be described in detail.

<Modified example of Embodiment 1>

In the first embodiment, the configuration of the modulation unit that executes the processing before the mapping unit 9702 in Figs. 97 and 98 is as shown in Fig. 57 . And the characteristic of Embodiment 1 is,

"When the encoding unit 502 of FIG. 57 outputs a codeword of N of the codeword length (block length (code length)) of the error correction code, the two The number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time for a set of complex signals in which the modulation method is based on a combination of all modulation methods is plural. In order not to include block data (of the error correction code), the bit length adjusting unit 5701 receives the first bit string 503 as an input, and error correction of the codeword length (block length (code length)) N An adjustment bit string is added to the codeword of the code, for example, at the trailing end, at the front end, or at a predetermined position to output a second bit string for the mapping unit in which the number of bits is a multiple of the number of bits (X+Y).”

to be.

Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In the modified example of Embodiment 1 in this embodiment, the number of bits of the adjustment bit string is determined by further considering the period z of the change of θ(i) described above. It will be described in detail below.

In order to simplify the explanation, a more specific example will be given.

The code length (block length) of the error correction code to be used is set to 64800 bits, and the period z of the change of ?(i) is set to 9. And it is assumed that QPSK, 16QAM, 64QAM, and 256QAM can be used as the modulation method. Therefore, (QPSK, QPSK), (QPSK, 16QAM), (QPSK) (modulation method of s ₁ (t) (first complex signal s1), s ₂ (t) (modulation method of second complex signal s2)) , 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) sets can be considered, but any one of these Pick up an example and explain.

In this embodiment, similarly to the other embodiments, both the modulation method of the _first complex signal s1(s1(t)) and the modulation method of the _second complex signal s2(s2(t)) can be switched from a plurality of modulation methods. make it as

For the following description, the following definitions are made.

Let α be an integer of 0 or more, and let β be an integer of 0 or more. And, it is assumed that the least common multiple of α and β is expressed as LCM(α,β). For example, if α is 8 and β is 6, LCM(α,β) becomes 24.

And as a characteristic of the modification example of Embodiment 1 in this embodiment, γ for the sum of the value of (X+Y), the period z of the change of θ(i), the number of bits of the code length (N), and the number of bits in the adjustment bit string If =LCM(X+Y, z), it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of γ. That is, it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of the least common multiple of X+Y and z. However, X is an integer of 1 or more, Y is an integer of 1 or more, Therefore, X+Y is made into an integer of 2 or more, and z is made into an integer of 2 or more. In addition, although it is ideal when the number of bits in the adjustment bit string is 0, there is a possibility that the number cannot be 0. At this time, it is an important point to add an adjustment bit string as described above.

Hereinafter, this point is demonstrated using an example.

(Example 1)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (16QAM, 16QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(8, 9)=72. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (provided that N is an integer greater than or equal to 0).

FIG. 101 (A) shows the state of the first bit string 503 output by the encoding unit 502 of the modulator of FIG. 57 . In Fig. 101(A), 10101 denotes the codeword of the i-th block with 64800 bits, 10102 denotes the codeword of the i+1th block with 64800 bits, and 10103 denotes the i+2th block with 64800 bits. The codeword of the block is shown, and 10104 denotes the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (however, N is an integer greater than or equal to 0). Here, "the number of bits in the adjustment bit string" is set to 0 (zero) bits. Accordingly, the state of the second bit string 5703 output by the bit length adjusting unit 5701 of the modulation unit of FIG. 57 is as shown in FIG. 101(B). That is, FIG. 101 (B) is the same as the first bit string 503 output by the encoding unit 502 of the modulator of FIG. 57, and the second bit output by the bit length adjusting unit 5701 of the modulation unit of FIG. 57 In the column 5703, the codeword 10101 of the i-th block of 64800 bits, the codeword 10102 of the i+1th block of 64800 bits, the codeword 10103 of the i+2th block of 64800 bits, and the i+3th block of 64800 bits The codeword 10104 of the th block, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

(Example 2)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (64QAM, 256QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(14, 9)=126. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0).

FIG. 102 (A) shows the state of the first bit string 503 output by the encoding unit 502 of the modulation unit of FIG. 57 . In Fig. 102(A), 10101 denotes the codeword of the i-th block with 64800 bits, 10102 denotes the codeword of the i+1th block with 64800 bits, and 10103 denotes the i+2th block with 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0). Here, the &quot;number of bits in the adjustment bit string&quot; is set to 90 bits. Accordingly, the state of the second bit string 5703 output by the bit length adjusting unit 5701 of the modulation unit of FIG. 57 is as shown in FIG. 102(B).

In Fig. 102(B), 10201, 10202, and 10203 indicate &quot;adjustment bit strings&quot;. "Adjustment bit string" 10201 is an adjustment bit string for the codeword 10101 of the i-th block of 64800 bits, and the number of bits is 90 bits. Accordingly, the total number of bits of the codeword 10101 of the i-th block of 64800 bits and the "adjustment bit string" 10201 is 64890 bits. Thereby, the effect demonstrated in Embodiment 1 can be acquired. And the total number of bits of the codeword 10101 of the i-th block of 64800 and the “adjustment bit string” 10201 is the number of slots required to transmit 64890 bits (here, 1 slot is symbol 1 symbol of s1 and symbol 1 symbol of s2) ) is an integer multiple of the period z=9 of the change of θ(i).

Accordingly, the total number of bits of the codeword 10101 of the i-th block of 64800 bits and the "adjustment bit string" 10201 is the same as the number of occurrences of each of the nine values θ(i) can take in the slots forming 64890 bits. Therefore, the possibility that the information included in the codeword 10101 of the i-th block can be obtained with high reception quality increases.

Similarly, the "adjustment bit string" 10202 is an adjustment bit string for the codeword 10102 of the i+1th block of 64800 bits, and the number of bits is 90 bits. Therefore, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is 64890 bits. Thereby, the effect demonstrated in Embodiment 1 can be acquired. And the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is an integer multiple of the period z=9 of the change in the number of slots θ(i) required to transmit 64890 bits. Therefore, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is the number of occurrences of each of the nine values that θ(i) can take in a slot forming 64890 bits. Since it becomes the same, the possibility that the information included in the codeword 10102 of the i+1th block can be obtained with high reception quality increases.

Similarly, the "adjustment bit string" 10203 is an adjustment bit string for the codeword 10103 of the i+2th block of 64800 bits, and the number of bits is 90 bits. Accordingly, the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 becomes 64890 bits. Thereby, the effect demonstrated in Embodiment 1 can be acquired. And the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 is an integer multiple of the period z=9 of the change in the number of slots θ(i) required to transmit 64890 bits. Therefore, the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 is the number of occurrences of each of the nine values that θ(i) can take in a slot forming 64890 bits. Since it becomes the same, the possibility that the information included in the codeword 10103 of the i+2th block can be obtained with high reception quality increases.

The method of inserting the adjustment bit string is not limited to that shown in Fig. 102, and a total of 64890 bits of a 64800-bit codeword and a 90-bit adjustment bit string may be arranged in any order.

<Modification of Embodiment 2>

In the second embodiment, the configuration of the modulation unit that executes the processing before the mapping unit 9702 in Figs. 97 and 98 is as shown in Fig. 60 . And the characteristic of Embodiment 2 is,

"When the encoding unit 502LA of FIG. 60 outputs a codeword of N of the codeword length (block length (code length)) of the error correction code, two The number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time for a set of complex signals in which the modulation method is based on a combination of all modulation methods is plural. In order not to include block data (of the error correction code), the bit length adjusting unit 6001 receives the first bit string 503 as an input, and error correction of the codeword length (block length (code length)) N A second bit string for the mapping unit is output in which the number of bits constituted by adding an adjustment bit string at the trailing end, the front end, or a predetermined position of the code word of the code is a multiple of the number of bits (X+Y). And the adjustment bit string is configured by partially repeating one or more bit values of a predetermined portion among the N-bit codewords obtained by the encoding process.”

to be. Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In the modified example of Embodiment 2 in this embodiment, the number of bits of the adjustment bit string is determined by further considering the period z of the change of θ(i) described above. It will be described in detail below.

In order to simplify the explanation, a more specific example will be given.

The code length (block length) of the error correction code to be used is set to 64800 bits, and the period z of the change of ?(i) is set to 9. And it is assumed that QPSK, 16QAM, 64QAM, and 256QAM can be used as the modulation method. Therefore, (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) are (QPSK, QPSK), (QPSK, 16QAM), ( QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) sets are conceivable, but any of these Pick up an example and explain it.

Also, in this embodiment, as in the other embodiments, both the modulation method of the _first complex signal s1(s1(t)) and the modulation method of the _second complex signal s2(s2(t)) can be switched from a plurality of modulation methods. make it possible

In addition, as a characteristic of the modified example of Embodiment 2 in this embodiment, γ for the value of (X+Y), the period z of change of θ(i), and the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string If =LCM(X+Y, z), it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of γ. That is, it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of the least common multiple of X+Y and z. However, X is an integer of 1 or more, Y is an integer of 1 or more, Therefore, X+Y is made into an integer of 2 or more, and z is made into an integer of 2 or more. In addition, although it is ideal when the number of bits in the adjustment bit string is 0, there is a possibility that the number cannot be 0. At this time, it is an important point to add an adjustment bit string as described above.

Hereinafter, this point is demonstrated using an example.

(Example 3)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (16QAM, 16QAM), and an error correction code (for example, DPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(8, 9)=72. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (provided that N is an integer greater than or equal to 0).

FIG. 101A shows the state of the first bit string 503 output by the encoding unit 502LA of the modulator of FIG. 60 . In Fig. 101(A), reference numeral 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and 10103 denotes the i+2th block of 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (however, N is an integer greater than or equal to 0). Here, "the number of bits in the adjustment bit string" is set to 0 (zero) bits. Accordingly, the second bit string 6003 output by the bit length adjusting unit 6001 of the modulation unit of FIG. 60 is as shown in FIG. 101(B). That is, FIG. 101 (B) shows the second bit string 6003 output by the bit length adjusting unit 6001 of the modulator of FIG. In , the codeword 10101 of the i-th block of 64800 bits, the codeword 10102 of the i+1th block of 64800 bits, the codeword 10103 of the i+2th block of 64800 bits, and the code of the i+3th block of 64800 bits Word 10104, after that, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

(Example 4)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (64QAM, 256QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(14, 9)=126. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0).

102 (A) shows the state of the first bit string 503 output by the encoding unit 502LA of the modulator of FIG. 60 . In Fig. 102(A), 10101 denotes the codeword of the i-th block with 64800 bits, 10102 denotes the codeword of the i+1th block with 64800 bits, and 10103 denotes the i+2th block with 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0). Here, the &quot;number of bits in the adjustment bit string&quot; is set to 90 bits. Accordingly, the second bit string 6003 output by the bit length adjusting unit 6001 of the modulation unit of FIG. 60 is as shown in FIG. 102(B).

In Fig. 102(B), 10201, 10202, and 10203 indicate &quot;adjustment bit strings&quot;. "Adjustment bit string" 10201 is an adjustment bit string for the codeword 10101 of the i-th block of 64800 bits, and the number of bits is 90 bits. Accordingly, the total number of bits of the codeword 10101 of the i-th block of 64800 bits and the "adjustment bit string" 10201 is 64890 bits. Thereby, the effect demonstrated in Embodiment 2 can be acquired. And the total number of bits of the codeword 10101 of the i-th block of 64800 and the "adjustment bit string" 10201 is the number of slots required to transmit 64890 bits (here, 1 slot means symbol 1 symbol of s1 and symbol 1 symbol of s2). ) is an integer multiple of the period z=9 of the change of θ(i).

As a result, the total number of bits of the codeword 10101 of the i-th block of 64800 bits and the "adjustment bit string" 10201 is the number of occurrences of each of the nine values θ(i) can take in the slot forming 64890 bits. Since they are identical, the possibility that information included in the codeword 10101 of the i-th block can be obtained with high reception quality increases.

Similarly, the "adjustment bit string" 10202 is an adjustment bit string for the codeword 10102 of the i+1th block of 64800 bits, and the number of bits is 90 bits. Therefore, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is 64890 bits. Thereby, the effect demonstrated in Embodiment 2 can be acquired. And the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is an integer multiple of the period z=9 of the change in the number of slots θ(i) required to transmit 64890 bits. Therefore, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" 10202 is the number of occurrences of each of the nine values that θ(i) can take in a slot forming 64890 bits. Since it becomes the same, the possibility that the information included in the codeword 10102 of the i+1th block can be obtained with high reception quality increases.

Similarly, the "adjustment bit string" 10203 is an adjustment bit string for the codeword 10103 of the i+2th block of 64800 bits, and the number of bits is 90 bits. Accordingly, the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 becomes 64890 bits. Thereby, the effect demonstrated in Embodiment 2 can be acquired. And the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 is an integer multiple of the period z=9 of the change in the number of slots θ(i) required to transmit 64890 bits. Therefore, the total number of bits of the codeword 10103 of the i+2th block of 64800 bits and the "adjustment bit string" 10203 is the same as the number of occurrences of 9 values that θ(i) can take in the slot forming 64890 bits. Therefore, the possibility that the information included in the codeword 10103 of the i+2th block can be obtained with high reception quality increases.

Further, as described in the second embodiment, the adjustment bit string is constituted by partially repeating one or more bit values of a predetermined portion among the N-bit codewords obtained by the encoding process. Note that the specific configuration method of the adjustment bit string is the same as that described in the second embodiment.

The insertion method of the adjustment bit string is not limited to that shown in FIG. 102, and a total of 64890 bits of a 64800-bit codeword and a 90-bit adjustment bit string may be arranged in any order.

<Modification of Embodiment 3>

In the third embodiment, the configuration of the modulator for executing the processing before the mapping unit 9702 in Figs. 97 and 98 is as shown in Fig.73. And the characteristic of Embodiment 3 is,

"When the encoding unit 502LA of FIG. 73 outputs a codeword of N of the codeword length (block length (code length)) of the error correction code, the two The number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time for a set of complex signals in which the modulation method is based on a combination of all modulation methods is plural. In order not to include data of the block (of the error correction code), the bit length adjusting unit 7301 receives the bit string 503V as an input, and the codeword length (block length (code length)) of the error correction code of N For example, a bit string after bit length adjustment is output for a mapping unit in which the number of bits constituted by adding an adjustment bit string to the trailing or leading end or a predetermined position of the codeword is a multiple of the number of bits (X+Y). And the adjustment bit string is configured by partially repeating one or more bit values of a predetermined part among the N-bit codewords obtained by the encoding process, or is constituted by a predetermined bit string.”

to be. Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In the modified example of Embodiment 2 in this embodiment, the number of bits in the adjustment bit string is determined in consideration of the period z of the change of θ(i) described above. It will be described in detail below.

In order to simplify the explanation, a more specific example will be given.

The code length (block length) of the error correction code to be used is set to 64800 bits, and the period z of the change of ?(i) is set to 9. And it is assumed that QPSK, 16QAM, 64QAM, and 256QAM can be used as the modulation method. Therefore, (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) are (QPSK, QPSK), (QPSK, 16QAM), ( QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) sets are conceivable, but any of these Pick up an example and explain it.

Also, in this embodiment, as in the other embodiments, both the modulation method of the _first complex signal s1(s1(t)) and the modulation method of the _second complex signal s2(s2(t)) can be switched from a plurality of modulation methods. make it possible In addition, as a characteristic of the modified example of Embodiment 3 in this embodiment, γ for the value of (X+Y), the period z of the change of θ(i), the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string If =LCM(X+Y, z), it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of γ. That is, it is assumed that the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string is a multiple of the least common multiple of X+Y and z. However, X is an integer of 1 or more, Y is an integer of 1 or more, Therefore, X+Y is made into an integer of 2 or more, and z is made into an integer of 2 or more. In addition, although it is ideal when the number of bits in the adjustment bit string is 0, there is a possibility that the number cannot be 0. At this time, it is an important point to add an adjustment bit string as described above.

Hereinafter, this point is demonstrated using an example.

(Example 5)

(the modulation method of s1(t) (the first complex signal s1), the modulation method of s2(t) (the second complex signal s2)) is (16QAM, 16QAM), and an error correction code (for example, LDPC code, etc.) The codeword length (block length (code length)) of the block code of ) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(8, 9)=72. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (provided that N is an integer greater than or equal to 0).

FIG. 101A shows the state of the first bit string 503Λ output by the encoding unit 502LA of the modulator of FIG. 73 . In Fig. 101(A), reference numeral 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and 10103 denotes the i+2th block of 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 72 x N bits (however, N is an integer greater than or equal to 0). Here, "the number of bits in the adjustment bit string" is set to 0 (zero) bits. Accordingly, the state of the bit string 7303 after the bit length adjustment output by the bit length adjusting unit 7301 of the modulation unit of FIG. 73 is as shown in FIG. 101(B). That is, FIG. 101 (B) shows the bit string after bit length adjustment output by the bit length adjusting unit 7301 of the modulator of FIG. 7303), the codeword 10101 of the i-th block of 64800 bits, the codeword 10102 of the i+1th block of 64800 bits, the codeword 10103 of the i+2th block of 64800 bits, and the i+3th block of 64800 bits of codeword 10104, after that, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

(Example 6)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (64QAM, 256QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(14, 9)=126. Therefore, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0).

FIG. 103(A) shows the state of the first bit string 503Λ output by the encoding unit 502LA of the modulation unit of FIG. 73 . In Fig. 103(A), 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and thereafter, the codeword of the i+2th block. , the codeword of the i+3th block, ... will lead with

As described above, the &quot;number of bits in the adjustment bit string&quot; required to satisfy the above characteristics is 126 x n + 90 bits (provided that N is an integer greater than or equal to 0). Here, the &quot;number of bits in the adjustment bit string&quot; is set to 90 bits. Accordingly, the state of the bit string 7303 after the bit length adjustment output by the bit length adjusting unit 7301 of the modulation unit of FIG. 73 is as shown in FIG. 103(B).

In Fig. 103(B), 103A denotes a bit (1) of a codeword, and 103B denotes a bit in an adjustment bit string. In 10301, the total number of bits composed of the codeword 10101 of the i-th block and the adjustment bit string for the codeword 10101 of the i-th block is 64890 bits. In addition, in 10302, the total number of bits composed of the control bit string for the codeword 10102 of the i+1th block and the codeword 10102 of the i+1th block becomes 64890 bits.

Thereby, the effect demonstrated in Embodiment 3 can be acquired. And the total number of bits of the codeword 10101 of the i-th block of 64800 and the “adjustment bit string” is the number of slots required to transmit 64890 bits (here, 1 slot is 1 symbol of s1 and 1 symbol of s2. (meaning that it is formed) becomes an integer multiple of the period z=9 of the change of θ(i).

As a result, the total number of bits of the codeword 10101 of the i-th block of 64800 bits and the "adjustment bit string" is the same as the number of occurrences of 9 values that θ(i) can take in the slot forming 64890 bits. Therefore, the possibility that the information included in the codeword 10101 of the i-th block can be obtained with high reception quality increases.

Similarly, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" is an integer multiple of the period z=9 of the change in the number of slots θ(i) required to transmit 64890 bits. Therefore, the total number of bits of the codeword 10102 of the i+1th block of 64800 bits and the "adjustment bit string" is the same as the number of occurrences of 9 values that θ(i) can take in the slot forming 64890 bits. Therefore, the possibility that the information included in the codeword 10102 of the i+1th block can be obtained with high reception quality increases.

Further, as described in the third embodiment, the adjustment bit string is composed of one or more repetitions of the bit values of a predetermined part of the N-bit codeword obtained by the encoding process, or is composed of a predetermined bit string. will do In addition, the specific configuration method of the adjustment bit string is the same as that described in the third embodiment.

The insertion method of the adjustment bit string is not limited to that shown in FIG. 103, and a total of 64890 bits of a 64800-bit codeword and a 90-bit adjustment bit string may be arranged in any order.

Also, as described in the third embodiment, there is a case where the size of the interleave is Nxz bits. In this case, it has the following characteristics.

"When the encoding unit 502LA of FIG. 73 outputs a codeword of N of the codeword length (block length (code length)) of the error correction code, the two The number of bits (X+Y) that can be transmitted by the first complex signal s1 and the second complex signal s2 transmitted at the same frequency and at the same time for a set of complex signals in which the modulation method is based on a combination of all modulation methods is plural. In order not to include the block data (of the error correction code), the bit length adjusting unit 7301 adds an adjustment bit string to the N × z bits accumulated in the interleaver, and the sum of the N × z bits and the adjustment bit string. The number is a multiple of γ=LCM(X+Y, z).”

<Modified example of Embodiment 4>

In the fourth embodiment, the configuration of the modulation unit that executes the processing before the mapping unit 9702 in Figs. 97 and 98 is shown in Figs. 80 and 83 . And the characteristic of Embodiment 4 is,

"The second bit string in the second bit string (bit length adjusted bit string) 8003 in which the adjustment bit string temporarily inserted before encoding in the code length N of the codeword of the LDPC code of the i-th block is deleted The number of bits in (bit string after bit length adjustment) 8003 is a multiple of the number of bits (X+Y) determined by the set of the first modulation method of s1(t) and the second modulation method of s2(t). .”

to be. Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In the modified example of Embodiment 4 in the present embodiment, the number of bits in the adjustment bit string is determined in consideration of the period z of the change of θ(i) described above. It will be described in detail below.

In order to simplify the explanation, a more specific example will be given.

The code length (block length) of the error correction code to be used is set to 64800 bits, and the period z of the change of ?(i) is set to 9. And it is assumed that QPSK, 16QAM, 64QAM, and 256QAM can be used as the modulation method. Therefore, (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) are (QPSK, QPSK), (QPSK, 16QAM), ( QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) sets are conceivable, but any of these Pick up an example and explain it.

Also, in this embodiment, as in the other embodiments, both the modulation method of the _first complex signal s1(s1(t)) and the modulation method of the _second complex signal s2(s2(t)) can be switched from a plurality of modulation methods. make it possible

And as a characteristic of the modified example of Embodiment 4 in this embodiment, γ for the value of (X+Y), the period z of the change of θ(i), and the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string If =LCM(X+Y, z), the number of bits in the bit string after bit length adjustment is assumed to be a multiple of γ. That is, it is assumed that the number of bits in the bit string after bit length adjustment is a multiple of the least common multiple of X+Y and z. However, X is an integer of 1 or more, Y is an integer of 1 or more, Therefore, X+Y is made into an integer of 2 or more, and z is made into an integer of 2 or more. In addition, although it is ideal when the difference between the number of bits in the bit string and the number of bits in the codeword after bit length adjustment is 0, there is a possibility that the difference cannot be 0. At this time, it is an important point to adjust the bit length as described above.

Hereinafter, this point is demonstrated using an example.

(Example 7)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (16QAM, 16QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(8, 9)=72. Accordingly, the "number of bits of the temporarily inserted adjustment bit string (known information)" required to satisfy the above characteristics is 72 x N bits (provided that N is an integer greater than or equal to 0).

FIG. 101A shows the state of the first bit string 503' (or 503Λ) output by the encoding unit 502 of the modulator of FIGS. 80 and 83 . In Fig. 101(A), reference numeral 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and 10103 denotes the i+2th block of 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with In addition, the codewords 10101, 10102, 10103, and 10104 of the block do not include the temporarily inserted adjustment bit string (known information).

As described above, the "number of bits of the temporarily inserted adjustment bit string (known information)" required to satisfy the above characteristics is 72 x N bits (provided that N is an integer greater than or equal to 0). Here, "the number of bits of the temporarily inserted adjustment bit string (known information)" is set to 0 (zero) bits. Accordingly, the state of the bit string 8003 after adjusting the bit length output from the rear end portion 8001B of FIGS. 80 and 83 is as shown in FIG. 101(B). That is, FIG. 101 (B) shows the first bit string 503 ′ (or 503Λ) output by R102 of the modulator of FIGS. 80 and 83 , and the rear end portion 8001B of FIGS. 80 and 83 is output. In the bit string 8003 after adjusting the bit length to The codeword 10104 of the i+3th block of 64800 bits, the codeword of the i+4th block, the codeword of the i+5th block, . . . will lead with

(Example 8)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (64QAM, 256QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(14, 9)=126. Therefore, the "number of bits of the temporarily inserted adjustment bit string (known information)" required to satisfy the above characteristics is 126 x n + 36 bits (provided that N is an integer greater than or equal to 0).

FIG. 104 (A) shows the state of the first bit string 503' (or 503Λ) output by the encoding unit 502 of the modulator of FIGS. 80 and 83 . In Fig. 104(A), 10401 denotes the codeword of the i-th block of 64800 bits, 10402 denotes the codeword of the i+1th block of 64800 bits, and thereafter, the codeword of the i+2th block. , the codeword of the i+3th block, ... will lead with

Note that, in Fig. 104, 104b indicates bits of the temporarily inserted adjustment bit string, and 104a indicates other bits.

Therefore, in the codeword 10401 of the i-th block of 64800 bits in Fig. 104(A), bit 104b of the 36-bit temporarily inserted adjustment bit string exists, and the code of the i+1th block having 64800 bits In word 10402, bit 104b of a 36-bit temporarily inserted control bit string exists.

As described above, the "number of bits of the temporarily inserted adjustment bit string (known information)" required to satisfy the above characteristics is 126 x n + 36 bits (provided that N is an integer greater than or equal to 0). Here, "the number of bits in the temporarily inserted adjustment bit string (known information)" is set to 36 bits. And, in the rear end portion 8001B in FIGS. 80 and 83, the &quot;temporarily inserted adjustment bit string (known information)&quot; is deleted. Accordingly, the state of the bit string 8003 after the bit length adjustment output by the rear end portion 8001B of the modulation unit of FIGS. 80 and 83 is as shown in FIG. 104 (B).

In Fig. 104(B), reference numeral 10403 denotes a bit string after the i-th bit length adjustment, and consists of only bit 104a. And the number of bits of the bit string 10403 after the i-th bit length adjustment is 64800-36=64764.

Similarly, 10404 indicates the bit string after the i+1th bit length adjustment, and consists of only bit 104a. Then, the number of bits in the bit string 10404 after the i+1th bit length adjustment is 64800-36=64764.

…

Accordingly, the effects described in the fourth embodiment can be obtained.

And the number of slots required to transmit the bit string after the i-th bit length adjustment (here, 1 slot means that it is formed of 1 symbol of s1 and 1 symbol of s2) Period of change of θ(i) z = an integer multiple of 9.

As a result, the number of occurrences of each of the nine values θ(i) in the slot forming the bit string after the i-th bit length adjustment becomes the same. Information included in the bit string after the i-th bit length adjustment is more likely to be obtained with high reception quality.

In addition, the number of slots required to transmit the bit string after the i+1th bit length adjustment (here, 1 slot means that one symbol of s1 and one symbol of s2 are formed) Period of change of θ(i) It becomes an integer multiple of z=9.

Accordingly, in the slot forming the bit string after the i+1th bit length adjustment, the number of occurrences of each of the nine values that θ(i) can take becomes the same. Information included in the bit string after the i+1th bit length adjustment is more likely to be obtained with high reception quality.

…

In addition, the specific configuration method of the temporarily inserted adjustment bit string (known information) is the same as that described in the fourth embodiment.

<Modification of Embodiment 8>

In the eighth embodiment, the configuration of the modulation unit that executes the processing before the mapping unit 9702 in Figs. 97 and 98 is shown in Figs. 91 and 93 . And the characteristic of Embodiment 8 is,

“The bit length adjusting unit deletes PunNum-bit data from the N-bit codeword and outputs an N-PunNum-bit data string. At this time, NPunNum determines PunNuM which is a multiple of "the value of X+Y".

to be. Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In the modified example of Embodiment 8 in this embodiment, the number of bits of data to be erased PunNuM is determined in consideration of the period z of change of θ(i) described above. It will be described in detail below.

In order to simplify the explanation, a more specific example will be given.

The code length (block length) of the error correction code to be used is set to 64800 bits, and the period z of the change of ?(i) is set to 9. And it is assumed that QPSK, 16QAM, 64QAM, and 256QAM can be used as the modulation method. Therefore, (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) are (QPSK, QPSK), (QPSK, 16QAM), ( QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) sets are conceivable, but any of these Pick up an example and explain it.

Also, in this embodiment, as in the other embodiments, both the modulation method of the _first complex signal s1(s1(t)) and the modulation method of the _second complex signal s2(s2(t)) can be switched from a plurality of modulation methods. make it possible And as a characteristic of the modified example of Embodiment 8 in this embodiment, γ for the value of (X+Y), the period z of the change of θ(i), and the sum of the number of bits of the code length (N) and the number of bits of the adjustment bit string If =LCM(X+Y, z), it is assumed that the number of bits in the N-PunNum-bit data string N-PunNuM is a multiple of γ. That is, it is assumed that N-PunNuM is a multiple of the least common multiple of X+Y and z. However, X is an integer of 1 or more, Y is an integer of 1 or more, Therefore, X+Y is made into an integer of 2 or more, and z is made into an integer of 2 or more. Moreover, although it is ideal when PunNuM is 0, there may be a case where it cannot become 0. At this time, it is an important point to adjust the N-PunNuM as described above.

Hereinafter, this point is demonstrated using an example.

(Example 9)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (16QAM, 16QAM), and an error correction code (for example, DPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(8, 9)=72. Therefore, PunNuM required to satisfy the above characteristics is 72 x N bits (however, N is an integer greater than or equal to 0).

FIG. 101A shows the state of the N-bit codeword 503 output by the encoding unit 502 of the modulation unit of FIGS. 91 and 93 . In Fig. 101(A), reference numeral 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and 10103 denotes the i+2th block of 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, PunNuM required to satisfy the above characteristics is 72 × N bits (however, N is an integer greater than or equal to 0). Here, PunNuM is set to 0 (zero) bit. Accordingly, the state of the N-PunNum bit data string 9102 output by the bit length adjusting unit 9101 of FIGS. 91 and 93 is as shown in FIG. 101 (B). That is, FIG. 101 (B) shows an N-PunNum-bit data string 9102 output by the bit length adjusting unit 9101, like the first bit string 503 output by R102 of the modulator of FIGS. 91 and 93 . ), the codeword 10101 of the i-th block of 64800 bits, the codeword 10102 of the i+1th block of 64800 bits, the codeword 10103 of the i+2th block of 64800 bits, of the i+3th block of 64800 bits Codeword 10104, after that, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

(Example 10)

Let (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) be (64QAM, 256QAM), and an error correction code (for example, LDPC The codeword length (block length (code length)) of the block code such as code) is 64800 bits, and the period z of the change of θ(i) is 9. Then γ=LCM(X+Y, z)=(14, 9)=126. Therefore, PunNuM required to satisfy the above characteristics is 126 x n + 36 bits (however, N is an integer greater than or equal to 0).

FIG. 105(A) shows the state of the N-bit codeword 503 output by the encoding unit 502 of the modulation unit of FIGS. 91 and 93 . In Fig. 105(A), 10101 denotes the codeword of the i-th block of 64800 bits, 10102 denotes the codeword of the i+1th block of 64800 bits, and 10103 denotes the i+2th block of 64800 bits. represents the codeword of the block, 10104 represents the codeword of the i+3th block of 64800 bits, and thereafter, the codeword of the i+4th block, the codeword of the i+5th block, ... will lead with

As described above, PunNuM required to satisfy the above characteristics is 126 x n + 36 bits (however, N is an integer greater than or equal to 0). Here, PunNuM is set to 36 bits. Accordingly, the state of the N-PunNum bit data string 9102 output by the bit length adjusting unit 9101 of FIGS. 91 and 93 is as shown in FIG. 105 (B).

In Fig. 105(B), 10501 is the i-th bit length adjusted bit string, that is, the i-th N-PunNum bit data string. Accordingly, it is a block after the i-th bit length adjustment made by 64800-36=64764 bits.

Similarly, 10502 becomes the i+1th bit length adjusted bit string, that is, the i+1th N-PunNum bit data string. Therefore, it is a block after the length adjustment of the i+1th bit constituted by 64800-36=64764 bits. And 10503 becomes the i+2th bit length adjusted bit string, that is, the i+2th N-PunNum bit data string. Therefore, it is a block after the i+2th bit length adjustment, which is constituted by 64800-36=64764 bits.

10504 becomes the i+3th bit length adjusted bit string, that is, the i+3th N-PunNum bit data string. Therefore, it is a block after the i + 3 th bit length adjustment, which is constituted by 64800-36 = 64764 bits.

…

Accordingly, the effects described in the eighth embodiment can be obtained.

And the number of slots required to transmit the i-th bit-length-adjusted block (here, 1 slot means that it is formed of 1 symbol of s1 and 1 symbol of s2) Period of change of θ(i) z= It becomes an integer multiple of 9.

As a result, the number of occurrences of each of the nine values that θ(i) can take in the slot forming the block after the i-th bit length adjustment is the same, so the information included in the block after the i-th bit length adjustment is Higher reception quality is more likely to be obtained.

In addition, the number of slots required to transmit the i+1th bit length-adjusted block (here, 1 slot means that one symbol of s1 and one symbol of s2 are formed) Period z of change of θ(i) = an integer multiple of 9.

As a result, the number of occurrences of each of the nine values that θ(i) can take in the slots forming the block after the i+1th bit length adjustment is the same. Therefore, the information contained in the i+1th bit length adjustment block Higher reception quality is more likely to be obtained.

The number of slots required to transmit the i+2th bit length-adjusted block (here, 1 slot means that one symbol of s1 and one symbol of s2 are formed) Period of change of θ(i) z=9 becomes an integer multiple of

As a result, the number of occurrences of each of the nine values that θ(i) can take in the slots forming the block after the i+2th bit length adjustment is the same, so the information included in the i+2th bit length adjustment block Higher reception quality is more likely to be obtained.

The number of slots required to transmit the i+3th bit length-adjusted block (here, 1 slot means that one symbol of s1 and one symbol of s2 are formed) Period of change of θ(i) z=9 becomes an integer multiple of

As a result, the number of occurrences of each of the nine values that θ(i) can take in the slot forming the block after the i+3th bit length adjustment is the same. Therefore, the information contained in the i+3th bit length adjustment block Higher reception quality is more likely to be obtained.

The same applies to blocks after bit length adjustment.

By carrying out the above example, the receiving apparatus can obtain high data reception quality. Note that the configuration of the receiving apparatus is the same as that described in the fifth, sixth, seventh, and eighth embodiments (however, the bit length adjustment method is the same as described in the present embodiment).

In addition, when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, it is a complex based on the combination of all (s1 and s2) modulation methods regardless of the value of N. If the block after bit length adjustment for a set of signals satisfies any one of the above examples, the effect of reducing the memory of the transmitting apparatus and/or the receiving apparatus is more likely to be more effective.

(Embodiment 11)

In Embodiments 1 to 10, when the "encoding unit outputs a codeword of N bits of the codeword length (block length (code length)) of the error correction code using a plurality of examples, the block after bit length adjustment is The method of controlling as it is a multiple of” has been described. In this embodiment, "when the encoding unit outputs a codeword of N bits in the codeword length (block length (code length)) of the error correction code, the block after bit length adjustment is a multiple of "the value of X+Y" explain once more.

Note that the "value of X+Y" is the same as that described in the first to third embodiments described above.

In this embodiment, the code length (block length) of the error correction code used is 16200 bits or 64800 bits, the modulation method of (s ₁ (t) (first complex signal s1), s ₂ (t) (second complex signal) (QPSK, QPSK), (QPSK, 16QAM), (QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM) , (64QAM, 256QAM), and (256QAM, 256QAM) are considered (in the following, N is an integer greater than or equal to 0). Then it becomes like this:

[One]

(QPSK, QPSK) is (QPSK, QPSK) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 4).

[1-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string is 4xN.

[1-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 4xN (provided that 4xn<16200).

[1-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 4xN (provided that 4xn<16200).

[2]

(QPSK, 16QAM) is (QPSK, 16QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 16200 bits (“value of X+Y” becomes 6).

[2-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 6xN.

[2-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 6xN (provided that 6xn<16200).

[2-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 6xN (however, it is assumed that 6xn<16200).

[3]

(QPSK, 64QAM) is (QPSK, 64QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 16200 bits (“value of X+Y” becomes 8).

[3-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 8xN.

[3-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 8xN (however, 8xn<16200).

[3-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 8xN (however, 8xn<16200).

[4]

(The modulation method of s1(t) (the first complex signal s1), the modulation method of s2(t) (the second complex signal s2)) is (QPSK, 256QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 10).

[4-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 10xN.

[4-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 10xN (provided that 10xn<16200).

[4-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 10xN (provided that 10xn<16200).

[5]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 16QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 8).

[5-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 8xN.

[5-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 8xN (provided that 8xn<16200).

[5-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 8xN (however, 8xn<16200).

[6]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 64QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 10).

[6-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 10xN.

[6-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 10xN (provided that 10xn<16200).

[6-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 10xN (provided that 10xn<16200).

[7]

(16QAM, 256QAM) is (16QAM, 256QAM) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2) length) is 16200 bits (“value of X+Y” becomes 12).

[7-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 12xN.

[7-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 12xN (provided that 12xn<16200).

[7-3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 12xN (however, 12xn<16200).

[8]

(The modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 14).

[8-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 14xn+12.

[8-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 14xn+2 (provided that 14xn+2<16200).

[8-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 14xn+2 (provided that 14xn+2<16200).

[9]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (256QAM, 256QAM), the code length of the error correction code used (block length) is 16200 bits ("value of X+Y" becomes 16).

[9-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string is 16xn+8.

[9-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 16xn+8 (however, 16xn+8<16200).

[9-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 16xn+8 (however, 16xn+8<16200).

[10]

(QPSK, QPSK) is (QPSK, QPSK) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 4).

[10-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 4xN.

[10-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 4xN (however, 4xn<64800).

[10-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 4xN (however, it is assumed that 4xn<64800).

[11]

(QPSK, 16QAM) is (QPSK, 16QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 64800 bits (“value of X+Y” becomes 6).

[11-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 6xN.

[11-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 6xN (provided that 6xn<64800).

[11-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 6xN (however, it is assumed that 6xn<64800).

[12]

(QPSK, 64QAM) is (QPSK, 64QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 64800 bits (“value of X+Y” becomes 8).

[12-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 8xN.

[12-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 8xN (however, 8xn<64800).

[12-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 8 x N (however, 8 x n < 64800).

[13]

(QPSK, 256QAM) is (QPSK, 256QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 64800 bits (“value of X+Y” becomes 10).

[13-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 10xN.

[13-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 10xN (provided that 10xn<64800). -3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 10xN (provided that 10xn<64800).

[14]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 16QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 8).

[14-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 8xN.

[14-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 8xN (provided that 8xn<64800).

[14-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 8 x N (however, 8 x n < 64800).

[15]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 64QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 10).

[15-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 10xN.

[15-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 10xN (provided that 10xn<64800). -3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 10xN (provided that 10xn<64800).

[16]

(16QAM, 256QAM) is (16QAM, 256QAM) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2) length) is 64800 bits (“value of X+Y” becomes 12).

[16-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 12xN.

[16-2] When the method of Embodiment 4 is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 12 x N (provided that 12 x n < 64800). -3] When the method of Embodiment 8 is used, the number of bits of PunNum (bits to be deleted) becomes 12xN (however, 12xn<64800).

[17]

(The modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM), the code length of the error correction code used (block length) is 64800 bits ("value of X+Y" becomes 14).

[17-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string is 14xn+6.

[17-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 14xn+8 (provided that 14xn+8<64800).

[17-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 14xn+8 (provided that 14xn+8<64800).

[18]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (256QAM, 256QAM), the code length of the error correction code used (block length) is 64800 bits ("value of X+Y" becomes 16).

[18-1] When the method of any one of Embodiments 1 to 3 is used, the number of bits in the (added) adjustment bit string becomes 16xN.

[18-2] When the method of the fourth embodiment is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 16xN (however, 16xn<64800).

[18-3] When the method of the eighth embodiment is used, the number of bits of PunNum (bits to be deleted) becomes 16 x N (however, 16 x n < 64800).

For example, in the communication system (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)), (QPSK, QPSK), (QPSK, 16QAM), (QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) any one modulation method It is assumed that a set of can be set, and the code length (block length) of the error correction code can be set to either 16200 bits or 64800 bits.

At this time, it becomes important to satisfy any one of the conditions described in [1] to [18] described above. As a characteristic point, the code of the error correction code is any set of modulation methods (s ₁ (t) (the modulation method of the first complex signal s1), s ₂ (t) (the modulation method of the second complex signal s2)). The point is that the number of bits to be added or the number of bits to be deleted differs depending on the length (block length).

Specifically, case 1 and case 2 are given, for example.

Case 1:

Assume that (the modulation method of s ₁ (t) (the first complex signal s1) and the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM). And it is assumed that the transmitter can set the code length (block length) of the error correction code to either 16200 bits or 64800 bits.

When the transmitter selects 16200 bits as the code length (block length) of the error correction code, when applying [8-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 12, and When applying the [8-2] described above, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 2, and when applying [8-3] described above, PunNum (bit to be deleted) set the number of bits to 2.

And when the transmitter selects 64800 bits as the code length (block length) of the error correction code, when applying [17-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 6, When applying [17-2] described above, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 8, and when applying [17-3] described above, PunNum (bit to be deleted) ) is set to 8.

Case 2:

It is assumed that (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the modulation method of the second complex signal s2)) is (256QAM, 256QAM). And it is assumed that the transmitter can set the code length (block length) of the error correction code to either 16200 bits or 64800 bits.

When the transmitter selects 16200 bits as the code length (block length) of the error correction code, when applying [9-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 8, and When applying [9-2] described above, set “the number of bits in the temporarily inserted adjustment bit string (known information)” to 8, and when applying [9-3] described above, PunNum (bit to be deleted) set the number of bits to 8.

And when the transmitter selects 64800 bits as the code length (block length) of the error correction code, when applying [18-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 0, When applying [18-2] described above, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 0, and when applying [18-3] described above, PunNum (bit to be deleted) ) is set to 0.

Next, the code length (block length) of the error correction code used is set to 16200 bits or 64800 bits, the modulation method of (s ₁ (t) (first complex signal s1), s ₂ (t) (second complex signal) s2) as (QPSK, QPSK), (QPSK, 16QAM), (QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), A case in which the method of Embodiment 10 is applied in consideration of the sets of (64QAM, 256QAM) and (256QAM, 256QAM) is considered. However, the period z of the change of θ(i) described in the tenth embodiment is set to 9 (in the following, N is an integer greater than or equal to 0). Then it becomes as follows.

[19]

(QPSK, QPSK) is (QPSK, QPSK) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 4).

[19-1] The number of bits in the adjustment bit string (to be added) is 36 × N when any one of the methods of “Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10” is used do.

[19-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 36xN (however, 36xN) Let n<16200).

[19-3] The number of bits of PunNum (bits to be deleted) is 36 x N (provided that 36 x n < 16200) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[20]

(QPSK, 16QAM) is (QPSK, 16QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 16200 bits (“value of X+Y” becomes 6).

[20-1] The number of bits in the adjustment bit string (to be added) is 18 x N when any one of the methods "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10 is used" is used do.

[20-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 18xN (however, 18xN) Let n<16200).

[20-3] The number of bits of PunNum (bits to be deleted) becomes 18xN (provided that 18xn<16200) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[21]

(QPSK, 64QAM) is (QPSK, 64QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 16200 bits (“value of X+Y” becomes 8).

[21-1] The number of bits in the (added) adjustment bit string is 72 × N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modified example of Embodiment 3 of Embodiment 10" is used do.

[21-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 72xN (however, 72xN) Let n<16200).

[21-3] The number of bits of PunNum (bits to be deleted) becomes 72 x N (provided that 72 x n < 16200) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[22]

(QPSK, 256QAM) is (QPSK, 256QAM), the code length of the error correction code used (block s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) length) is 16200 bits (“value of X+Y” becomes 10).

[22-1] When the method of any one of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used, the number of bits in the (added) adjustment bit string is 90xN do.

[22-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 90xN (however, 90xN Let n<16200).

[22-3] The number of bits of PunNum (bits to be deleted) becomes 90xN (provided that 90xn<16200) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[23]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 16QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 8).

[23-1] The number of bits in the adjustment bit string (to be added) is 72 x N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used do.

[23-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 72xN (however, 72xN) Let n<16200).

[23-3] The number of bits of PunNum (bits to be deleted) becomes 72 x N (provided that 72 x n < 16200) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[24]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 64QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 10).

[24-1] When the method of any one of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used, the number of bits in the (added) adjustment bit string is 90xN do.

[24-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 90 × N (however, 90 × N Let n<16200).

[24-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 90xN (provided that 90xn<16200).

[25]

(16QAM, 256QAM) is (16QAM, 256QAM) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2) length) is 16200 bits (“value of X+Y” becomes 12).

[25-1] The number of bits in the adjustment bit string (to be added) is 36 × N when any one of the methods “Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10” is used is used do.

[25-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 36xN (however, 36xN) Let n<16200).

[25-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 36xN (however, set to 36xn<16200).

[26]

(The modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM), the code length of the error correction code used (block length) is 16200 bits (“value of X+Y” becomes 14).

[26-1] The number of bits in the adjustment bit string (to be added) is 126 x n + 54 when any one of the methods "Modified example of Embodiment 1 of Embodiment 10 to Embodiment 3 of Embodiment 10 is used" is used do.

[26-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 126 x n + 72 (however, 126 x n + 72) Let n+72<16200).

[26-3] When the method of "Modification of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 126 × n + 72 (however, 126 × n + 72 < 16200).

[27]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (256QAM, 256QAM), the code length of the error correction code used (block length) is 16200 bits ("value of X+Y" becomes 16).

[27-1] The number of bits in the adjustment bit string (to be added) is 144 x n + 72 when any one method is used in "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" do.

[27-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 144 × n + 72 (however, 144 × Let n+72<16200).

[27-3] When the method of "Modified example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 144xn+72 (provided that 144xn+72<16200).

[28]

(QPSK, QPSK) is (QPSK, QPSK) where s1(t) (modulation method of the first complex signal s1) and s2(t) (modulation method of the second complex signal s2) is used, the code length of the error correction code (block length) is 64800 bits (“value of X+Y” becomes 4).

[28-1] The number of bits in the adjustment bit string (to be added) is 36 × N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used do.

[28-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 36xN (however, 36xN) Let n<64800).

[28-3] When the method of "Modified example of the eighth embodiment of the tenth embodiment" is used, the number of bits of PunNum (bits to be deleted) becomes 36xN (however, 36xn<64800).

[29]

(the modulation method of s1(t) (the first complex signal s1), the modulation method of s2(t) (the second complex signal s2)) is (QPSK, 16QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 6).

[29-1] The number of bits in the adjustment bit string (to be added) is 18 x N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modified example of Embodiment 3 of Embodiment 10" is used do.

[29-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 18xN (however, 18xN) Let n<64800).

[29-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 18xN (provided that 18xn<64800).

[30]

(the modulation method of s1(t) (the first complex signal s1), the modulation method of s2(t) (the second complex signal s2)) is (QPSK, 64QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 8).

[30-1] The number of bits in the adjustment bit string (to be added) is 72 × N when any one of the methods “Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10” is used is used. do.

[30-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 72xN (however, 72xN) Let n<64800).

[30-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 72xN (however, let 72xn<64800).

[31]

(The modulation method of s1(t) (the first complex signal s1), the modulation method of s2(t) (the second complex signal s2)) is (QPSK, 256QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 10).

[31-1] When any method of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used, the number of bits in the (added) adjustment bit string is 90xN do.

[31-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 90xN (however, 90xN Let n<64800).

[31-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 90xN (however, let 90xn<64800).

[32]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 16QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 8).

[32-1] The number of bits in the adjustment bit string (to be added) is 72 x N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used do.

[32-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 72xN (however, 72xN) Let n<64800).

[32-3] The number of bits of PunNum (bits to be deleted) becomes 72xN (provided, however, that 72xn<64800) when the method of "Modified example of the eighth embodiment of the tenth embodiment" is used.

[33]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (16QAM, 64QAM), the code length of the error correction code used (block length) is 64800 bits (“value of X+Y” becomes 10).

[33-1] The number of bits in the adjustment bit string (to be added) is 90 × N when any one of the methods “Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10” is used is used. do.

[33-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 90xN (however, 90xN Let n<64800).

[33-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 90xN (however, let 90xn<64800).

[34]

(16QAM, 256QAM) is (16QAM, 256QAM) of (s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2) length) to 64800 bits ("value of X+Y" becomes 12).

[34-1] The number of bits in the adjustment bit string (to be added) is 36 × N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used do.

[34-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of an adjustment bit string (known information) temporarily inserted" becomes 36xN (however, 36xN) Let n<64800).

[34-3] When the method of "Modified Example of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 36xN (however, set to 36xn<64800).

[35]

(The modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM), the code length of the error correction code used (block length) is 64800 bits ("value of X+Y" becomes 14).

[35-1] The number of bits in the (added) adjustment bit string is 126 x n + 90 when any one of the methods "Modified example of Embodiment 1 of Embodiment 10 to Embodiment 3 of Embodiment 10 is used" is used do.

[35-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits in the temporarily inserted adjustment bit string (known information)" becomes 126 x n + 36 (however, 126 x n + 36) Let n+36<64800).

[35-3] When the method of "Modification of Embodiment 8 of Embodiment 10" is used, the number of bits of PunNum (bits to be deleted) becomes 126xn+36 (however, 126xn+36<64800).

[36]

(s ₁ (t) (modulation method of the first complex signal s1), s ₂ (t) (modulation method of the second complex signal s2)) is (256QAM, 256QAM), the code length of the error correction code used (block length) is 64800 bits ("value of X+Y" becomes 16).

[36-1] The number of bits in the adjustment bit string (to be added) is 144 × N when any one of the methods of "Modified example of Embodiment 1 of Embodiment 10 to Modification of Embodiment 3 of Embodiment 10" is used do.

[36-2] When the method of "Modified example of Embodiment 4 of Embodiment 10" is used, "the number of bits of the temporarily inserted adjustment bit string (known information)" becomes 144 × N (however, 144 × N Let n<64800).

[36-3] The number of bits of PunNum (bits to be deleted) becomes 144xN (provided that 144xn<64800) when the method of "Modified example of Embodiment 8 of Embodiment 10" is used.

For example, in the communication system (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the second complex signal s2)), (QPSK, QPSK), (QPSK, 16QAM), (QPSK, 64QAM), (QPSK, 256QAM), (16QAM, 16QAM), (16QAM, 64QAM), (16QAM, 256QAM), (64QAM, 256QAM), (256QAM, 256QAM) any one modulation method It is assumed that a set of can be set, and the code length (block length) of the error correction code can be set to either 16200 bits or 64800 bits. However, the period z of the change of θ(i) described in the tenth embodiment is set to 9.

At this time, it becomes important to satisfy any one of the conditions described in [19] to [36] described above. As a characteristic point, the code of the error correction code is any set of modulation methods (s ₁ (t) (the modulation method of the first complex signal s1), s ₂ (t) (the modulation method of the second complex signal s2)). The point is that the number of bits to be added or the number of bits to be deleted differs depending on the length (block length).

Specifically, case 3 and case 4 are given, for example.

Case 3:

Assume that (the modulation method of s ₁ (t) (the first complex signal s1) and the modulation method of s ₂ (t) (the second complex signal s2)) is (64QAM, 256QAM). And it is assumed that the transmitter can set the code length (block length) of the error correction code to either 16200 bits or 64800 bits.

When the transmitter selects 16200 bits as the code length (block length) of the error correction code, when applying [26-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 54, and When applying the [26-2] described above, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 72, and when applying [26-3] described above, PunNum (bit to be deleted) set the number of bits to 72.

And when the transmitter selects 64800 bits as the code length (block length) of the error correction code, when applying [35-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 90, When [35-2] described above is applied, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 36, and when applying [35-3] described above, PunNum (bit to be deleted) ) is set to 36.

Case 4:

It is assumed that (the modulation method of s ₁ (t) (the first complex signal s1), the modulation method of s ₂ (t) (the modulation method of the second complex signal s2)) is (256QAM, 256QAM). And it is assumed that the transmitter can set the code length (block length) of the error correction code to either 16200 bits or 64800 bits.

When the transmitter selects 16200 bits as the code length (block length) of the error correction code, when applying [27-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 72, and When applying the [27-2] described above, set “the number of bits in the temporarily inserted adjustment bit string (known information)” to 72, and when applying [27-3] described above, PunNum (bit to be deleted) set the number of bits to 72.

And when the transmitter selects 64800 bits as the code length (block length) of the error correction code, when applying [36-1] described above, for example, the number of bits in the (additional) adjustment bit string is set to 0, When applying [36-2] described above, “the number of bits in the temporarily inserted adjustment bit string (known information)” is set to 0, and when applying [36-3] described above, PunNum (bit to be deleted) ) is set to 0.

(Embodiment 12)

In this embodiment, the method of applying the bit length adjustment method described in Embodiments 1 to 11 to the DVB standard will be described.

A case of application to a broadcasting system using the DVB (Digital Video Broadcasting)-T2 (T: Terrestrial) standard will be described. First, a frame configuration of a broadcasting system using the DVB-T2 standard will be described.

Fig. 106 shows an outline of the frame structure of a signal transmitted by a broadcasting station in the DVB-T2 standard. Since OFDM is used in the DVB-T2 standard, the frame is configured on the time-frequency axis. Fig. 106 shows the frame configuration on the time-frequency axis, and the frames are P1 Signaling data (hereinafter, sometimes referred to as P1 symbol) 10601, L1 Pre-Signalling data 10602, and L1 Post-Signalling data 10603. ), Common PLP (10604), and PLP#1 to #N (10605-1 to 10605-N) (PLP: Physical Layer Pipe). (Here, L1 Pre-Signalling data 10602 and L1 Post-Signalling data 10603 are called P2 symbols).

In this way, P1 Signaling data (10601), L1 Pre-Signalling data (10602), L1 Post-Signalling data (10603), Common PLP (10604), PLP#1 to #N (10605-1 to 10605-N) The constituted frame is called a T2 frame, and is a unit of the frame composition.

The P1 Signaling data 10601 is a symbol for the reception device to perform signal detection and frequency synchronization (including frequency offset estimation), information on the FFT (Fast Fourier Transform) size in the frame, and SISO (Single-Input) Transmits information on which method of transmitting a modulated signal among Single-Output)/MISO (Multiple-Input Single-Output). In the case of the MISO method, it is a method of transmitting a plurality of modulated signals, and the space-time block codes shown in Non-Patent Document 5, Non-Patent Document 7, and Non-Patent Document 8 are used).

Further, in the present embodiment, in the case of the SISO method, a plurality of modulated signals may be generated from one stream and transmitted through a plurality of antennas.

Information on the guard interval used in the transmission frame by the L1 Pre-Signalling data 10602, information on the signal processing method implemented to reduce the Peak to Average Power Ratio (APR), information on the L1 Post-Signalling data when transmitting Modulation method, error correction method (FEC: Forward Error Correction), information on coding rate of error correction method, information on size and information size of L1 Post-Signalling data, information on pilot pattern, information on cell (frequency domain) unique number , information on which method of the normal mode and the extended mode (the number of subcarriers used for data transmission is different in the normal mode and the extended mode) is transmitted, and the like.

By L1 Post-Signalling data (10603), information on the number of PLPs, information on the frequency domain to be used, information on the unique number of each PLP, modulation method used to transmit each PLP, error correction method, and error correction method Information on the encoding rate, information on the number of blocks to be transmitted in each PLP, and the like are transmitted. Common PLP 10604 and PLP#1 to #N (10605-1 to 10605-N) are areas for data transmission.

In the frame configuration of FIG. 106, P1 Signaling data 10601, L1 Pre-Signalling data 10602, L1 Post-Signalling data 10603, Common PLP 10604, PLP#1 to #N (10605-1 to 10605-) N) is transmitted in time division and is described as ssm, but in reality, two or more types of signals exist at the same time. An example thereof is shown in FIG. 107 . As shown in FIG. 107, L1 Pre-Signalling data, L1 Post-Signalling data, and Common PLP may exist at the same time, or PLP#1 and PLP#2 may exist at the same time. That is, each signal is composed of a frame using both time division and frequency division.

Fig. 108 shows an example of the configuration of a transmission apparatus to which the transmission method for performing the precoding and phase change described above is applied to the transmission apparatus of the DVB-T2 standard (for example, a broadcasting station).

The PLP signal generation unit 10802 receives the transmission data 10801 for PLP (data for multiple PLPs) and the control signal 10809 as inputs, and error correction encoding information of each PLP included in the control signal 10809, Based on information such as information on the modulation method, error correction coding and mapping based on the modulation method are performed to output the (orthogonal) baseband signal 10803 of the PLP.

The P2 symbol signal generator 10805 receives the P2 symbol transmission data 10804 and the control signal 10809 as inputs, and includes information such as error correction information of the P2 symbol included in the control signal 10809, information on the modulation method, and the like. Mapping based on the error correction coding and modulation method is performed based on the P2 symbol (orthogonal) baseband signal 10806 is output.

The control signal generation unit 10808 receives, as input, the transmission data 10807 for the P1 symbol and the transmission data 10804 for the P2 symbol, and receives each symbol group (P1 Signaling data 10601, L1 Pre-Signalling data (10602), L1 Post-Signalling data (10603), Common PLP (10604), PLP#1 to #N (10605-1 to 10605-N)) transmission method (error correction code, code rate of error correction code) , modulation method, block length, frame configuration, selected transmission method including transmission method that regularly changes precoding matrix, pilot symbol insertion method, IFFT (Inverse Fast Fourier Transform)/FFT information, etc., PAPR reduction method information, information of the guard interval insertion method) is output as a control signal 10809.

The frame configuration unit 10810 receives the baseband signal 10812 of the PLP, the baseband signal 10806 of the P2 symbol, and the control signal 10809 as inputs, and receives a frequency, Stream 1's (orthogonal) baseband signal 10811-1 (a signal after mapping, i.e., a baseband signal based on the modulation method used), stream 2 ( orthogonal) a baseband signal 10811-2 (a signal after mapping, that is, a baseband signal based on the modulation method used) is output.

The signal processing unit 10812 receives the baseband signal 10811-1 of the stream 1, the baseband signal 10811-2 of the stream 2, and the control signal 10809 as inputs, and includes a transmission method included in the control signal 7609. A modulated signal 1 (10813-1) after signal processing and a modulated signal 2 (108313-2) after signal processing are outputted.

Note that the operation of the signal processing unit 10812 will be described in detail later.

The pilot inserting unit 10814-1 receives the modulated signal 1 10813-1 and the control signal 10809 after signal processing as inputs, and based on the information on the method of inserting the pilot symbol included in the control signal 10809, A pilot symbol is inserted into the modulated signal 1 10813-1 after signal processing, and the modulated signal 10815-1 after the pilot symbol insertion is output.

The pilot inserting unit 0814-2 receives the modulated signal 2 10813-2 and the control signal 10809 after signal processing as inputs, and based on the information on the method of inserting the pilot symbol included in the control signal 10809, A pilot symbol is inserted into the modulated signal 2 10813-2 after signal processing, and the modulated signal 10815-2 after the pilot symbol insertion is output.

The IFFT (Inverse Fast Fourier Transform) unit 10816-1 receives the modulated signal 10815-1 and the control signal 10809 after pilot symbol insertion as inputs, and receives the information of the IFFT method included in the control signal 10809. Based on the IFFT, the IFFT signal 10816-1 is output.

The IFFT unit 10816-2 receives the modulated signal 10815-2 and the control signal 10809 after pilot symbol insertion as inputs, and executes the IFFT based on the IFFT method information included in the control signal 10809. , the signal 10817-2 after IFFT is output.

The PAPR reduction unit 10818-1 receives the post-IFFT signal 10817-1 and the control signal 10809 as inputs, and based on the PAPR reduction information included in the control signal 10809, the post-IFFT signal 10817- In 1), processing for PAPR reduction is performed, and the signal 10819-1 after PAPR reduction is output.

The PAPR reduction unit 10818-2 receives the post-IFFT signal 10817-2 and the control signal 10809 as inputs, and based on the PAPR reduction information included in the control signal 10809, the post-IFFT signal 10817- In 2), processing for PAPR reduction is performed, and the signal 10819-2 after PAPR reduction is output.

The guard interval insertion unit 10820-1 receives the signal 10819-1 and the control signal 10809 after PAPR reduction as inputs, and based on the information on the method of inserting the guard interval included in the control signal 10809, the PAPR A guard interval is inserted into the reduced signal 10819-1, and the guard interval inserted signal 10821-1 is output.

The guard interval insertion unit 10820-2 receives the signal 10819-2 and the control signal 10809 after PAPR reduction as inputs, and based on the information on the method of inserting the guard interval included in the control signal 10809, the PAPR A guard interval is inserted into the reduced signal 10819-2, and the guard interval inserted signal 10821-2 is output.

The P1 symbol insertion unit 10822 receives the signal 10821-1 after guard interval insertion, the signal 10821-2 after guard interval insertion, and transmission data 10807 for the P1 symbol as inputs, and transmits data for the P1 symbol. A P1 symbol signal is generated from (10807), a P1 symbol is added to the signal 10821-1 after guard interval insertion, a signal 10823-1 after adding the P1 symbol, and a signal 10821 after a guard interval insertion -2), the signal 10823-2 after adding the P1 symbol is added. The signal of the P1 symbol may be added to both the signal 10823-1 after adding the P1 symbol and the signal 10823-2 after adding the P1 symbol, or may be added to either one. In the case where the added signal is added, a 0 (zero) signal exists as the baseband signal in the non-added signal in the section to which the added signal is added.

The radio processing unit 10824-1 receives the signal 10823-1 after adding the P1 symbol as input, performs frequency conversion and amplification processing, and outputs a transmission signal 10825-1. Then, the transmission signal 10825-1 is output as a radio wave from the antenna 10826-1.

The radio processing unit 10824-2 receives the signal 10823-2 after processing for the P1 symbol as input, performs frequency conversion, amplification, and other processing, and outputs a transmission signal 10825-2. Then, the transmission signal 10825-2 is output as a radio wave from the antenna 10826-2.

For example, it is assumed that the broadcasting station transmits each symbol according to the frame configuration shown in FIG. 106 . At this time, as an example, PLP (changed from #1 to #1 to avoid confusion) #1 and PLP$K, the broadcasting station transmits two modulated signals as described in Embodiments 1 to 11 through two antennas. The frame configuration on the frequency-time axis at the time is shown in FIG.

As shown in Fig. 109, in PLP#1, a slot (symbol) exists with time T and carrier 3 (10901 in Fig. 109) as the beginning of the slot, and time T+4 and carrier 4 as the end of the slot (10902 in Fig. 109). (refer to FIG. 109).

That is, in PLP$1, time T, carrier 3 is the first slot, the second slot is time T, carrier 4, the third slot is time T, carrier 5, ... , the seventh slot is time T+1, carrier 1, the eighth slot is time T+1, carrier 2, the ninth slot is time T+1, carrier 3, ... , the 14th slot is time T+1, carrier 8, the 15th slot is time T+2, carrier 0, ... becomes

Then, in PLP$K, a slot (symbol) exists with time S, carrier 4 (10903 in Fig. 109) as the beginning of the slot, and time S+8, carrier 4 as the end of the slot (10904 in Fig. 109) (Fig. 109).

That is, in PLP$K, time S, carrier 4 is the first slot, the second slot is time S, carrier 5, the third slot is time S, carrier 6, ... , the fifth slot is time S, carrier 8, the ninth slot is time S+1, carrier 1, the tenth slot is time S+1, carrier 2, ... , the 16th slot is time S+1, carrier 8, the 17th slot is time S+2, carrier 0, ... becomes

In addition, the slot information used by each PLP, including information on the first slot (symbol) and information on the last slot (symbol) of each PLP, is transmitted using control symbols such as P1 symbols, P2 symbols, and control symbol groups. becomes becoming

Next, the operation of the signal processing unit 10812 in FIG. 108 will be described. It is assumed that the signal processing unit 10812 includes an LDPC code encoding unit, a mapping unit, a precoding unit, a bit length adjustment unit, and a rearrangement unit (interleaver).

The signal processing unit 10812 receives a control signal 10809 as an input, and is included in the control signal 10809, for example, the code length (block length) of the LDPC code, information on the transmission method (SISO transmission, MIMO transmission, MISO transmission), the signal processing method is determined based on information on the modulation method. At this time, when MIMO transmission is selected as the transmission method, the signal is based on any one of the bit length adjustment methods described in Embodiments 1 to 11 based on the code length (block length) of the LDPC code and the set of modulation methods. The processing unit 10812 adjusts the bit length, and then performs interleaving, mapping, and, in some cases, precoding, so that the modulated signal 1 (10813-1) after signal processing and the modulated signal 2 (10813-) after signal processing are performed. 2) is printed.

As described above, a transmission method of each PLP by P1 symbol, P2 symbol, and control symbol group (for example, a transmission method of transmitting one stream, a transmission method using a space-time block code, a transmission method of transmitting two streams ) and information on the modulation method being used are transmitted to the terminal.

The operation of the terminal at this time will be described.

In FIG. 110, the P1 symbol detection and decoding unit 11011 receives the signal transmitted by the broadcasting station (FIG. 108), receives the signals 11004-X and 11004-Y after signal processing as input, and detects the P1 symbol to signal Detection and time frequency synchronization are performed, and control information included in the P1 symbol is obtained (by performing demodulation and error correction decoding), and P1 symbol control information 11012 is output.

The OFDM method related processing unit 11003-X receives the received signal 11002-X received from the antenna 11001-X as an input, performs signal processing on the receiving side for the OFDM method, and processes the signal 11004-X after signal processing. X) is printed. Similarly, the OFDM method related processing unit 11003-Y receives the received signal 11002-Y received from the antenna 11001-Y as an input, performs signal processing on the receiving side for the OFDM method, and performs signal processing on the signal 11004 -Y) is output.

The OFDM method related processing units 11003-X and 11003-Y receive P1 symbol control information 11012 as input, and change the signal processing method for the OFDM method based on this information (as described above, the broadcasting station This is because information on the transmission method of the signal to be transmitted is included in the P1 symbol).

The P2 symbol demodulation unit 11013 receives the signals 11004-X and 11004-Y after signal processing and the P1 symbol control information 11012 as inputs, performs signal processing based on the P1 symbol control information, and demodulates (errors). correction decoding is performed) to output P2 symbol control information 11014.

The control information generator 11015 receives the P1 symbol control information 11012 and the P2 symbol control information 11014 as inputs, bundles the control information (related to the reception operation) and outputs it as a control signal 11016 . Then, the control signal 11016 is input to each unit as shown in FIG. 110 .

The channel variation estimating unit 11005-1 of the modulated signal z ₁ (also as described in the modulated signal z ₁ embodiment A1) receives the signal 11004-X and the control signal 11016 after signal processing as inputs. , the transmission device estimates the channel variation between the antenna to which the modulated signal z ₁ has been transmitted and the reception antenna 11001-X using pilot symbols included in the signal 11004-X after signal processing, and the like, and the channel estimation signal 11006- 1) is printed.

The channel variation estimating unit 11005-2 of the modulated signal z ₂ (also as described in the modulated signal z ₂ embodiment A1) receives the signal 11004-X and the control signal 11016 after signal processing as inputs. , the channel estimation signal 11006-2 by estimating the channel variation between the antenna 11001-X from which the transmitter transmits the modulated signal z2 and the receiving antenna 11001-X using pilot symbols included in the signal 11004-X after signal processing. ) is output.

The channel variation estimating unit 11007-1 of the modulated signal z ₁ receives the signal 11004-Y and the control signal 11016 after signal processing (also as described in Embodiment A1 of the modulated signal z ₁ ) as inputs. , the channel estimation signal 11008-1 by estimating the channel variation between the antenna from which the transmitter transmits the modulated signal z ₁ and the receiving antenna 11001-Y using pilot symbols included in the signal 11004-Y after signal processing ) is output.

The channel variation estimating unit 11007-2 of the modulated signal z ₂ (also as described in the modulated signal z ₂ embodiment A1) receives the signal 11004-Y and the control signal 11016 after signal processing as inputs. , the channel estimation signal 11008-2 by estimating the channel variation between the antenna from which the transmitter transmits the modulated signal z ₂ and the receiving antenna 11001-Y using pilot symbols included in the signal 11004-Y after signal processing ) is output.

The signal processing unit 11009 receives the signals 11006-1, 11006-2, 11008-1, 11008-2, 11004-X, and 11004-Y and the control signal 11016 as inputs, and is included in the control signal 11016 The received data ( 11010) is output. In addition, the receiver extracts the required PLP from the slot information used by each PLP included in the control symbols such as the P1 symbol, the P2 symbol, and the control symbol group and demodulates it (including signal separation and signal detection). , error correction decoding is performed.

In the previous description, the configuration of a transmitting device to which a transmission method of performing precoding and phase change for a transmitting device of the DVB-T2 standard (for example, a broadcasting station) is applied and a receiving device receiving a signal transmitted by the transmitting device mainly explained.

However, when a broadcasting system using the DVB-T2 standard is operated and a receiving device capable of receiving a modulated signal of the DVB-T2 standard is already in use, when a new standard is introduced, it is possible to receive a modulated signal of the DVB-T2 standard. It is desirable not to affect the receiving device that can be used.

Therefore, in the following, a transmission method for transmitting one stream and a transmission method for transmitting two streams without affecting a receiving device capable of receiving a modulated signal of the DVB-T2 standard are introduced. ) and P2 symbols (L1 Pre-Signalling data and L1 Post-Signalling data) and P1 symbols (P1 Signaling data) and P2 symbols (L1 A method of configuring Pre-Signalling data and L1 Post-Signalling data) will be described.

First, in the DVB-T2 standard, the S1 field of the P1 symbol (P1 Signaling data) is stipulated as follows.

In addition, in Table 1, the SISO method is a method of transmitting one stream using one antenna or multiple antennas, and the MISO method is a space-time ( or frequency space) is a method of generating a plurality of modulated signals using a block code and transmitting the modulated signals using a plurality of antennas.

In 2 bits of PLP_FEC_TYPE of L1 Post-Signalling data of P2 symbol, the type of Forward Error Correction (FEC) used in PLP is prescribed.

Next, the configuration of the symbols P1 and P2 for realizing the bit length adjustment described in Embodiments 1 to 11 without affecting a receiving apparatus capable of receiving a modulated signal according to the DVB-T2 standard will be described. .

In the previous description, the S1 field of the P1 symbol (P1 Signaling data) in the DVB-T2 standard has been described. In addition, the DVB standard stipulates the S1 field of the P1 symbol (P1 Signaling data) as follows.

In addition, in Tables 3 and 4, the SISO method is a method of transmitting one stream using one antenna or multiple antennas, and the MISO method is described in Non-Patent Document 5, Non-Patent Document 7, and Non-Patent Document 8, It is a method of generating a plurality of modulated signals using a space-time (or frequency space) block code and transmitting the modulated signals using a plurality of antennas.

And for the new standard, the definition when the value of S1 is "111" in Tables 3 and 4 and S2 field 1 and S2 field 2 is set is as follows.

In addition, in Tables 5 to 8, "x" means negative (any value may be used), the SISO method is a method of transmitting one stream using one antenna or multiple antennas, and the MISO method is a non-patented method. A method of generating a plurality of modulated signals using a space-time (or frequency space) block code described in Document 5, Non-Patent Document 7, and Non-Patent Document 8 and transmitting the modulated signal using a plurality of antennas, the MIMO method is an example For example, it is a method of transmitting two streams that have been subjected to real precoding and the like described above.

As described above, by the P1 symbol transmitted by the transmitter,

"Which transmission method was used, a transmission method of transmitting one stream and a transmission method of transmitting two streams?"

can be known by the receiving device.

As described above, the transmission method for transmitting one stream, the SISO method (a method for transmitting one stream using one antenna or multiple antennas), or the MISO method (non-patent document X1, non-patent document X2) L1 Post-Signalling data of P2 symbols when a plurality of modulated signals are generated by the described space-time (or frequency space) block code and the modulated signals are transmitted using a plurality of antennas) or MIMO transmission method is selected 2 bits of PLP_FEC_TYPE are defined as follows (in addition, the method of setting S1 and S2 of the P1 symbol is as Table 3, Table 4, Tables 5 to 8).

In addition, 3 bits of PLP_NUM_PER_CHANNEL_USE of L1 Post-Signalling data of P2 symbol are defined as follows, for example.

Note that the "value of X+Y", s1, and s2 are the same as those described in the first to third embodiments described above.

Therefore, when the Ω standard MIMO transmission method is specified by the P1 symbol, the block length of the LDPC code specified by the 2-bit value of PLP_FEC_TYPE of the L1 Post-Signalling data of the P2 symbol and the PLP_NUM_PER_CHANNEL_USE of the L1 Post-Signalling data of the P2 symbol With the modulation method of s1 and the modulation method of s2 designated by 3 bits, the signal processing unit 10812 of FIG. 108 adjusts the bit length based on any one of the bit length adjustment methods described in the first to eleventh embodiments. (Adjustment of the number of bits in the adjustment bit string), and then interleaving, mapping, and, in some cases, precoding, the modulated signal 1 (10813-1) after signal processing and the modulated signal 2 (10813-) after signal processing 2) is printed.

Embodiments 1 to 11 describe specific numerical examples of bit length adjustment (adjustment of the number of bits in an adjustment bit string). However, it is only an example.

In addition, in the terminal receiving apparatus of FIG. 110, PLP_FEC_TYPE of L1 Post-Signalling data of P1 and P2 symbols and L1 Post-Signalling of P2 symbols by P1 symbol detection and demodulation unit 11011 and P2 symbol demodulator 11013 Obtaining data of PLP_NUM_PER_CHANNEL_USE of data, the control signal generating unit 11015 estimates the bit length adjustment method used by the transmitter based on the obtained data, and the signal processing unit 11009 signal processing based on the estimated bit length adjusting method will run In addition, the details of signal processing are the same as those described in the operation examples of the receiving apparatuses of the first to eleventh embodiments.

By implementing as described above, the transmitter can efficiently transmit the modulated signal of the new standard in addition to the modulated signal based on the DVB-T2 standard, that is, the effect that the control information by the P1 symbol and P2 symbol can be reduced. can get In addition, the effects described in the first to eleventh embodiments can also be obtained when the modulated signal of the new standard is transmitted.

Further, the receiving apparatus can determine whether the received signal is a signal of the DVB-T2 standard or a signal of a new standard based on the P1 symbol and the P2 symbol, and the effects described in the first to eleventh embodiments can be obtained.

Further, when the broadcasting station transmits the modulated signal by performing the bit length adjustment described in the first to eleventh embodiments, the terminal receiving apparatus clearly identifies the symbols constituting each block of the block code such as the LDPC code (data of a plurality of blocks) Since there is no symbol composed of information needs to be added).

Note that the configuration of the P1 symbol and the configuration of the P2 symbol described in the present embodiment are examples, and may be realized by other configuration methods. However, it is also possible to add a symbol for transmitting control information to the transmission frame while transmitting the control information using the P1 symbol and the P2 symbol.

(Supplementary 1)

Of course, you may implement by combining two or more embodiment demonstrated in this specification.

And, in this specification, "∀" indicates a universal quantifier, and "∃" indicates an existential quantifier.

Incidentally, in the present specification, the unit of phase, for example, declination in the complex plane, is "radian".

If the complex plane is used, the complex number can be displayed in polar form in terms of polar coordinates. When a point (a, b) on the complex plane is mapped to a complex number z = a + jb (a, b are both real numbers, and j is an imaginary unit), if this point is expressed as [r, θ] in polar coordinates,

a=r×cosθ,

b=r×sinθ

holds, r is the absolute value of z (r = |z|), and θ is the argument. And z = a + jb is expressed as r×e ^jθ .

In the description of the present invention, the baseband signals, s1, s2, z1, and z2, are complex signals. However, in the case of the complex signal, when the in-phase signal is I and the quadrature signal is Q, the complex signal is I + jQ (j is an imaginary unit). ) will be displayed. At this time, I may be set to zero, and Q may be set to zero.

Further, for example, a program for executing the communication method may be stored in advance in a ROM (Read Only Memory), and the program may be operated by a CPU (Central Processor Unit).

Further, the program for executing the communication method may be stored in a computer-readable storage medium, and the program stored in the storage medium may be recorded in a computer's RAM (Random Access Memory), and the computer may be operated according to the program.

In addition, each configuration of each of the above embodiments and the like may be realized as LSI (Large Scale Integration), which is typically an integrated circuit. These may be individually formed into one chip, or may be formed into one chip so as to include all or some of the structures of each embodiment. Although LSI is used here, it is sometimes called IC (Integrated Circuit), system LSI, super LSI, and ultra LSI depending on the difference in the degree of integration. Incidentally, the method of forming an integrated circuit is not limited to the LSI, and may be realized by a dedicated circuit or a general-purpose processor. A field programmable gate array (FPGA) that can be programmed after the LSI is manufactured or a reconfigurable processor that can reconfigure the connection and settings of circuit cells inside the LSI may be used.

In addition, if an integrated circuit technology capable of replacing the LSI emerges due to advances in semiconductor technology or other derived technologies, of course, functional blocks may be integrated using the technology. Adaptation of biotechnology may be a possibility.

In Embodiments 1 to 11, the bit length adjustment method has been described. Further, in the twelfth embodiment, the case where the bit length adjustment method of the first to eleventh embodiments is applied to the DVB standard has been described. Among these embodiments, a case in which 16QAM, 64QAM, and 256QAM are applied as modulation schemes is described.

Instead of 16QAM in Embodiments 1 to 12, a modulation scheme having 16 signal points in the in-phase I-orthogonal Q plane may be used. Similarly, in Embodiments 1 to 12, a modulation scheme having 64 signal points in the in-phase I-quadrature Q plane instead of 64QAM, and a modulation scheme having 256 signal points in the in-phase I-quadrature Q plane instead of 256QAM You can use it.

In this specification, one antenna may be constituted by a plurality of antennas.

In this specification, a configuration in which the receiving device and the antenna are separate may be used. For example, the receiving device is provided with an interface for inputting a signal received from the antenna or a signal obtained by performing frequency conversion on a signal received from the antenna through a cable, and the receiving device performs subsequent processing.

In addition, the data and information obtained by the receiving device are then converted into images or sounds, and displayed on a display (monitor) or sound is output from a speaker. In addition, the data/information obtained by the receiving device is subjected to image or sound signal processing (signal processing may not be added), and the RCA terminal (video terminal, audio terminal) and USB (Universal Serial) provided by the receiving device are performed. Bus), HDMI (High-Definition Multimedia Interface), a digital terminal, or the like.

(Supplementary 2)

In Embodiments 1 to 11, the bit length adjustment method has been described. Further, in the twelfth embodiment, the case in which the first to eleventh embodiment of the bit length adjustment method is applied to the DVB standard has been described. Among these embodiments, a case in which 16QAM, 64QAM, and 256QAM are applied as modulation schemes is described. In addition, a specific mapping method for 16QAM, 64QAM, and 256QAM is described in (Configuration Example R1).

Hereinafter, a configuration method such as a mapping method of 16QAM, 64QAM, and 256QAM different from (configuration example R1) will be described. In addition, 16QAM, 64QAM, and 256QAM described below may be applied to the first to twelfth embodiments, and the effects described in the first to twelfth embodiments can be obtained at this time.

A case in which 16QAM is extended will be described.

A mapping method of 16QAM will be described. 111 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 111, 16 circles denote 16QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q. In Fig. 111, it is assumed that f>0 (f is a real number greater than 0), f≠3, and f≠1.

The respective coordinates of the 16 signal points of 16QAM (“○” in FIG. 111 are the signal points) in the in-phase I-orthogonal Q plane are,

(3×w _16a , 3×w _16a ), (3×w _16a , f×w _16a ), (3×w _16a ,-f×w _16a ), (3×w _16a ,-3×w _16a ), (f×w _16a , 3×w _16a ), (f×w _16a , f×w _16a ), (f×w _16a ,-f×w _16a ), (f×w _16a ,-3×w _16a ), (-f×w _16a , 3×w _16a ), (-f×w _16a , f×w _16a ), (-f×w _16a ,-f×w _16a ), (-f×w _16a ,-3× w _16a ), (-3×w _16a , 3×w _16a ), (-3×w _16a , f×w _16a ), (-3×w _16a ,-f×w _16a ), (-3×w _16a ) , -3×w _16a ) (w _16a is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 11101 in FIG. 111, and the in-phase component of the baseband signal after mapping is I, If the orthogonal component is Q, (I, Q) = (3×w _16a , 3×w _16a ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in Fig. 111)

(3×w _16a , 3×w _16a ), (3×w _16a , f×w _16a ), (3×w _16a ,-f×w _16a ), (3×w _16a ,-3×w _16a ), (f×w _16a , 3×w _16a ), (f×w _16a , f×w _16a ), (f×w _16a ,-f×w _16a ), (f×w _16a ,-3×w _16a ), (-f×w _16a , 3×w _16a ), (-f×w _16a , f×w _16a ), (-f×w _16a ,-f×w _16a ), (-f×w _16a ,-3× w _16a ), (-3×w _16a , 3×w _16a ), (-3×w _16a , f×w _16a ), (-3×w _16a ,-f×w _16a ), (-3×w _16a ) ,-3×w _16a )

The values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown just below. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000-1111) and the coordinates of the signal point in 16QAM is not limited to FIG. 111 .

In the 16 signal points in FIG. 111, "signal point 1", "signal point 2"... It is called "signal point 15" and "signal point 16" (since there are 16 signal points, "signal point 1" to "signal point 16" exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _16a is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2.

In addition, in the previous description, the case equivalent to (configuration example R1) is called uniform-16QAM, and the case other than that is called non-uniform 16QAM.

The 64QAM mapping method will be described. 112 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. In Fig. 112, 64 circles denote 64QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q. 112, g ₁ >0 (g ₁ is a real number greater than 0), g ₂ >0 (g ₂ is a real number greater than 0), and g ₃ >0 (g ₃ is a real number greater than 0) ego,

{{{g ₁ ≠ 7, and g ₂ ≠ 7, and g ₃ ≠ 7} holds},

Also, {{(g ₁ , g ₂ , g ₃ )≠(1, 3, 5), and (g ₁ , g ₂ , g ₃ )≠(1, 5, 3), and (g ₁ , g ₂ , g ₃ )≠(3, 1, 5), and (g ₁ , g ₂ , g ₃ )≠(3, 5, 1), and (g ₁ , g ₂ , g ₃ )≠(5, 1, 3), and (g ₁ , g ₂ , g ₃ )≠(5, 3, 1)} holds},

Also, {{{g ₁ ≠ g ₂ , g ₁ ≠ g ₃ , and g ₂ ≠ g _3} holds}.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 112 are signal points) in the in-phase I-orthogonal Q plane are,

(7×w _64a , 7×w _4a ), (7×w _64a , g ₃ ×w _64a ), (7×w _64a , g ₂ ×w _64a ), (7×w _64a , g ₁ ×w _64a ) , (7×w _64a ,-g ₁ ×w _64a ), (7×w _64a ,-g ₂ ×w _64a ), (7×w _64a ,-g ₃ ×w _64a ), (7×w _64a ,- 7×w _4a )

(g ₃ ×w _64a , 7×w _4a ), (g ₃ ×w _64a , g ₃ ×w _64a ), (g ₃ ×w _64a , g ₂ ×w _64a ), (g ₃ ×w _64a , g ₁ ×w _64a ), (g ₃ ×w _64a ,-g ₁ ×w _64a ), (g ₃ ×w _64a ,-g ₂ ×w _64a ), (g ₃ ×w _64a ,-g ₃ ×w _64a ), (g ₃ ×w _64a ,-7×w _64a )

(g ₂ ×w _64a , 7×w _64a ), (g ₂ ×w _64a , g ₃ ×w _64a ), (g ₂ ×w _64a , g ₂ ×w _64a ), (g ₂ ×w _64a , g ₁ ×w _64a ), (g ₂ ×w _64a ,-g ₁ ×w _64a ), (g ₂ ×w _64a ,-g ₂ ×w _64a ), (g ₂ ×w _64a ,-g ₃ ×w _64a ), (g ₂ ×w _64a ,-7×w _64a )

(g ₁ ×w _64a , 7×w _64a ), (g ₁ ×w _64a , g ₃ ×w _64a ), (g ₁ ×w _64a , g ₂ ×w _64a ), (g ₁ ×w _64a , g ₁ ×w _64a ), (g ₁ ×w _64a ,-g ₁ ×w _64a ), (g ₁ ×w _64a ,-g ₂ ×w _64a ), (g ₁ ×w _64a ,-g ₃ ×w _64a ), (g ₁ ×w _64a ,-7×w _64a )

(-g ₁ ×w _64a , 7×w _64a ), (-g ₁ ×w _64a , g ₃ ×w _64a ), (-g ₁ ×w _64a , g ₂ ×w _64a ), (-g ₁ ×w _64a , g ₁ ×w _64a ), (-g ₁ ×w _64a ,-g ₁ ×w _64a ), (-g ₁ ×w _64a ,-g ₂ ×w _64a ), (-g ₁ ×w _64a ,- g ₃ ×w _64a ), (-g ₁ ×w _64a ,-7×w _64a )

(-g ₂ ×w _64a , 7×w _64a ), (-g ₂ ×w _64a , g ₃ ×w _64a ), (-g ₂ ×w _64a , g ₂ ×w _64a ), (-g ₂ ×w _64a , g ₁ ×w _64a ), (-g ₂ ×w _64a ,-g ₁ ×w _64a ), (-g ₂ ×w _64a ,-g ₂ ×w _64a ), (-g ₂ ×w _64a ,- g ₃ ×w _64a ), (-g ₂ ×w _64a ,-7×w _64a )

(-g ₃ ×w _64a , 7×w _64a ), (-g ₃ ×w _64a , g ₃ ×w _64a ), (-g ₃ ×w _64a , g ₂ ×w _64a ), (-g ₃ ×w _64a , g ₁ ×w _64a ), (-g ₃ ×w _64a ,-g ₁ ×w _64a ), (-g ₃ ×w _64a ,-g ₂ ×w _64a ), (-g ₃ ×w _64a ,- g ₃ ×w _64a ), (-g ₃ ×w _64a ,-7×w _64a )

(-7×w _64a , 7×w _64a ), (-7×w _64a , g ₃ ×w _64a ), (-7×w _64a , g ₂ ×w _64a ), (-7×w _64a , g ₁ ×w _64a ), (-7×w _64a ,-g ₁ ×w _64a ), (-7×w _64a ,-g ₂ ×w _64a ), (-7×w _64a ,-g ₃ ×w _64a ), (-7×w _64a , -7×w _64a )

(w _64a is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, if the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 11201 in FIG. When the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7×w _64a , 7×w _64a ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, and b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in Fig. 112)

(7×w _64a , 7×w _64a ), (7×w _64a , g ₃ ×w _64a ), (7×w _64a , g ₂ ×w _64a ), (7×w _64a , g ₁ ×w _64a ) , (7×w _64a ,-g ₁ ×w _64a ), (7×w _64a ,-g ₂ ×w _64a ), (7×w _64a ,-g ₃ ×w _64a ), (7×w _64a ,- 7×w _64a )

(g ₃ ×w _64a , 7×w _64a ), (g ₃ ×w _64a , g ₃ ×w _64a ), (g ₃ ×w _64a , g ₂ ×w _64a ), (g ₃ ×w _64a , g ₁ ×w _64a ), (g ₃ ×w _64a ,-g ₁ ×w _64a ), (g ₃ ×w _64a ,-g ₂ ×w _64a ), (g ₃ ×w _64a ,-g ₃ ×w _64a ), (g ₃ ×w _64a ,-7×w _4a )

(g ₂ ×w _64a , 7×w _4a ), (g ₂ ×w _64a , g ₃ ×w _64a ), (g ₂ ×w _64a , g ₂ ×w _64a ), (g ₂ ×w _64a , g ₁ ×w _64a ), (g ₂ ×w _64a ,-g ₁ ×w _64a ), (g ₂ ×w _64a ,-g ₂ ×w _64a ), (g ₂ ×w _64a ,-g ₃ ×w _64a ), (g ₂ ×w _64a ,-7×w _4a )

(g ₁ ×w _64a , 7×w _4a ), (g ₁ ×w _64a , g ₃ ×w _64a ), (g ₁ ×w _64a , g ₂ ×w _64a ), (g ₁ ×w _64a , g ₁ ×w _64a ), (g ₁ ×w _64a ,-g ₁ ×w _64a ), (g ₁ ×w _64a ,-g ₂ ×w _64a ), (g ₁ ×w _64a ,-g ₃ ×w _64a ), (g ₁ ×w _64a ,-7×w _64a )

(-g ₁ ×w _64a , 7×w _64a ), (-g ₁ ×w _64a , g ₃ ×w _64a ), (-g ₁ ×w _64a , g ₂ ×w _64a ), (-g ₁ ×w _64a , g ₁ ×w _64a ), (-g ₁ ×w _64a ,-g ₁ ×w _64a ), (-g ₁ ×w _64a ,-g ₂ ×w _64a ), (-g ₁ ×w _64a ,- g ₃ ×w _64a ), (-g ₁ ×w _64a ,-7×w _64a )

(-g ₂ ×w _64a , 7×w _64a ), (-g ₂ ×w _64a , g ₃ ×w _64a ), (-g ₂ ×w _64a , g ₂ ×w _64a ), (-g ₂ ×w _64a , g ₁ ×w _64a ), (-g ₂ ×w _64a ,-g ₁ ×w _64a ), (-g ₂ ×w _64a ,-g ₂ ×w _64a ), (-g ₂ ×w _64a ,- g ₃ ×w _64a ), (-g ₂ ×w _64a ,-7×w _64a )

(-g ₃ ×w _64a , 7×w _64a ), (-g ₃ ×w _64a , g ₃ ×w _64a ), (-g ₃ ×w _64a , g ₂ ×w _64a ), (-g ₃ ×w _64a , g ₁ ×w _64a ), (-g ₃ ×w _64a ,-g ₁ ×w _64a ), (-g ₃ ×w _64a ,-g ₂ ×w _64a ), (-g ₃ ×w _64a ,- g ₃ ×w _64a ), (-g ₃ ×w _64a ,-7×w _64a )

(-7×w _64a , 7×w _64a ), (-7×w _64a , g ₃ ×w _64a ), (-7×w _64a , g ₂ ×w _64a ), (-7×w _64a , g ₁ ×w _64a ), (-7×w _64a ,-g ₁ ×w _64a ), (-7×w _64a ,-g ₂ ×w _64a ), (-7×w _64a ,-g ₃ ×w _64a ), (-7×w _64a , -7×w _64a )

The values of sets 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 112 .

In the 64 signal points in FIG. 112, "signal point 1", "signal point 2"... They are referred to as "signal point 63" and "signal point 64" (because 64 signal points exist, "signal point 1" to "signal point 64" exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _64a is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2.

In addition, in the previous description, the case equivalent to (configuration example R1) is called uniform-64QAM, and the case other than that is called non-uniform 64QAM.

A mapping method of 256QAM will be described. 113 shows an example of 256QAM signal point arrangement in the in-phase I-orthogonal Q plane. In Fig. 113, 256 ? denote 256QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q. 113, h ₁ >0 (h1 is a real number greater than 0), h ₂ >0 (h2 is a real number greater than 0), h ₃ >0 (h3 is a real number greater than 0), and , h ₄ >0 (h4 is a real number greater than 0), h ₅ >0 (h ₅ is a real number greater than 0), and h ₆ >0 (h ₆ is a real number greater than 0), and also , h ₇ >0 (h ₇ is a real number greater than 0),

{{h ₁ ≠ 15, h ₂ ≠ 15, h ₃ ≠ 15, h ₄ ≠ 15, h ₅ ≠ 15, and h ₆ ≠ 15, h ₇ ≠ 15} holds},

In addition,

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {when ax≠ay holds for all x and all y} (h _a1 , h _a2 , h _a3 , h _a4 , h _a5 , h _a6 , h _a7 )≠(1, 3, 5, 7, 9, 11, 13) holds}.

Also, {{h ₁ ≠h ₂ , h ₁ ≠h ₃ , h ₁ ≠h ₄ , and h ₁ ≠h ₅ ,

Also, h ₁ ≠h ₆ , and h ₁ ≠h ₇ ,

Further, h ₂ ≠ h ₃ , h ₂ ≠ h ₄ , h ₂ ≠ h ₅ , h ₂ ≠ h ₆ , and h ₂ ≠ h ₇ ,

Further, h ₃ ≠ h ₄ , h ₃ ≠ h ₅ , h ₃ ≠ h ₆ , and h ₃ ≠ h ₇ ,

Also, h ₄ ≠h ₅ , h ₄ ≠h ₆ , and h ₄ ≠h ₇ ,

Also, h ₅ ≠h ₆ , and h ₅ ≠h ₇ ,

Also, h ₆ ≠ h ₇ } holds}

be assumed to be

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 113 is the signal point) in the in-phase I-orthogonal Q plane are,

(15×w _256a , 15×w _256a ), (15×w _256a , h ₇ ×w _256a ), (15×w _256a , h ₆ ×w _256a ), (15×w _256a , h ₅ ×w _256a ) , (15×w _256a , h ₄ ×w _256a ), (15×w _256a , h ₃ ×w _256a ), (15×w _256a , h ₂ ×w _256a ), (15×w _256a , h ₁ ×w _256a ), (15×w _256a ,-15×w _256a ), (15×w _256a ,-h ₇ × _256a ), (15×w _256a ,-h ₆ ×w _256a ), (15×w _256a ,- h ₅ ×w _256a ), (15×w _256a ,-h ₄ ×w _256a ), (15×w _256a ,-h ₃ ×w _256a ), (15×w _256a ,-h ₂ ×w _256a ), ( 15×w _256a ,-h ₁ ×w _256a ),

(h ₇ ×w _256a , 15×w _256a ), (h ₇ ×w _256a , h ₇ ×w _256a ), (h ₇ ×w _256a , h ₆ ×w _256a ), (h ₇ ×w _256a , h ₅ ×w _256a ), (h ₇ ×w _256a , h ₄ ×w _256a ), (h ₇ ×w _256a , h ₃ ×w _256a ), (h ₇ ×w _256a , h ₂ ×w _256a ), (h ₇ ×w _256a , h ₁ ×w _256a ), (h ₇ ×w _256a ,-15×w _256a ), (h ₇ ×w _256a ,-h ₇ ×w _256a ), (h ₇ ×w _256a ,-h ₆ ×w _256a ), (h ₇ ×w _256a ,-h ₅ ×w _256a ), (h ₇ ×w _256a ,-h ₄ ×w _256a ), (h ₇ ×w _256a ,-h ₃ ×w _256a ), (h ₇ ×w _256a ,-h ₂ ×w _256a ), (h ₇ ×w _256a ,-h ₁ ×w _256a ),

(h ₆ ×w _256a , 15×w _256a ), (h ₆ ×w _256a , h ₇ ×w _256a ), (h ₆ ×w _256a , h ₆ ×w _256a ), (h ₆ ×w _256a , h ₅ ×w _256a ), (h ₆ ×w _256a , h ₄ ×w _256a ), (h ₆ ×w _256a , h ₃ ×w _256a ), (h ₆ ×w _256a , h ₂ ×w _256a ), (h ₆ ×w _256a , h ₁ ×w _256a ), (h ₆ ×w _256a ,-15×w _256a ), (h ₆ ×w _256a ,-h ₇ ×w _256a ), (h ₆ ×w _256a ,-h ₆ ×w _256a ), (h ₆ ×w _256a ,-h ₅ ×w _256a ), (h ₆ ×w _256a ,-h ₄ ×w _256a ), (h ₆ ×w _256a ,-h ₃ ×w _256a ), (h ₆ ×w _256a ,-h ₂ ×w _256a ), (h ₆ ×w _256a ,-h ₁ ×w _256a ),

(h ₅ ×w _256a , 15×w _256a ), (h ₅ ×w _256a , h ₇ ×w _256a ), (h ₅ ×w _256a , h ₆ ×w _256a ), (h ₅ ×w _256a , h ₅ ×w _256a ), (h ₅ ×w _256a , h ₄ ×w _256a ), (h ₅ ×w _256a , h ₃ ×w _256a ), (h ₅ ×w _256a , h ₂ ×w _256a ), (h ₅ ×w _256a , h ₁ ×w _256a ), (h ₅ ×w _256a ,-15×w _256a ), (h ₅ ×w _256a ,-h ₇ ×w _256a ), (h ₅ ×w _256a ,-h ₆ ×w _256a ), (h ₅ ×w _256a ,-h ₅ ×w _256a ), (h ₅ ×w _256a ,-h ₄ ×w _256a ), (h ₅ ×w _256a ,-h ₃ ×w _256a ), (h ₅ ×w _256a ,-h ₂ ×w _256a ), (h ₅ ×w _256a ,-h ₁ ×w _256a ),

(h ₄ ×w _256a , 15×w _256a ), (h ₄ ×w _256a , h ₇ ×w _256a ), (h ₄ ×w _256a , h ₆ ×w _256a ), (h ₄ ×w _256a , h ₅ ×w _256a ), (h ₄ ×w _256a , h ₄ ×w _256a ), (h ₄ ×w _256a , h ₃ ×w _256a ), (h ₄ ×w _256a , h ₂ ×w _256a ), (h ₄ ×w _256a , h ₁ ×w _256a ), (h ₄ ×w _256a ,-15×w _256a ), (h ₄ ×w _256a ,-h7×w _256a ), (h ₄ ×w _256a ,-h ₆ × w _256a ), (h ₄ ×w _256a ,-h ₅ w _256a ), (h ₄ ×w _256a ,-h ₄ ×w _256a ), (h ₄ ×w _256a ,-h ₃ w _256a ), (h ₄ ×w _256a ,-h ₂ w _256a ), (h ₄ ×w _256a ,-h ₁ w _256a ),

(h ₃ ×w _256a , 15×w _256a ), (h ₃ ×w _256a , h ₇ ×w _256a ), (h ₃ ×w _256a , h ₆ ×w _256a ), (h ₃ ×w _256a , h ₅ ×w _256a ), (h ₃ ×w _256a , h ₄ ×w _256a ), (h ₃ ×w _256a , h ₃ ×w _256a ), (h ₃ ×w _256a , h ₂ ×w _256a ), (h ₃ ×w _256a , h ₁ ×w _256a ), (h ₃ ×w _256a ,-15×w _256a ), (h ₃ ×w _256a ,-h ₇ ×w _256a ), (h ₃ ×w _256a ,-h ₆ ×w _256a ), (h ₃ ×w _256a ,-h ₅ ×w _256a ), (h ₃ ×w _256a ,-h ₄ ×w _256a ), (h ₃ ×w _256a ,-h ₃ ×w _256a ), (h ₃ ×w _256a ,-h ₂ ×w _256a ), (h ₃ ×w _256a ,-h ₁ ×w _256a ),

(h ₂ ×w _256a , 15×w _256a ), (h ₂ ×w _256a , h ₇ ×w _256a ), (h ₂ ×w _256a , h ₆ ×w _256a ), (h ₂ ×w _256a , h ₅ ×w _256a ), (h ₂ ×w _256a , h ₄ ×w _256a ), (h ₂ ×w _256a , h ₃ ×w _256a ), (h ₂ ×w _256a , h ₂ ×w _256a ), (h ₂ ×w _256a , h ₁ ×w _256a ), (h ₂ ×w _256a ,-15×w _256a ), (h ₂ ×w _256a ,-h ₇ ×w _256a ), (h ₂ ×w _256a ,-h ₆ ×w _256a ), (h ₂ ×w _256a ,-h ₅ ×w _256a ), (h ₂ ×w _256a ,-h ₄ ×w _256a ), (h ₂ ×w _256a ,-h ₃ ×w _256a ), (h ₂ ×w _256a ,-h ₂ ×w _256a ), (h ₂ ×w _256a ,-h ₁ ×w _256a ),

(h ₁ ×w _256a , 15×w _256a ), (h ₁ ×w _256a , h ₇ ×w _256a ), (h ₁ ×w _256a , h ₆ ×w _256a ), (h ₁ ×w _256a , h ₅ ×w _256a ), (h ₁ ×w _256a , h ₄ ×w _256a ), (h ₁ ×w _256a , h ₃ ×w _256a ), (h ₁ ×w _256a , h ₂ ×w _256a ), (h ₁ ×w _256a , h ₁ ×w _256a ), (h ₁ ×w _256a ,-15×w _256a ), (h ₁ ×w _256a ,-h ₇ ×w _256a ), (h ₁ ×w _256a ,-h ₆ ×w _256a ), (h ₁ ×w _256a ,-h ₅ ×w _256a ), (h ₁ ×w _256a ,-h ₄ ×w _256a ), (h ₁ ×w _256a ,-h ₃ ×w _256a ), (h ₁ ×w _256a ,-h ₂ ×w _256a ), (h ₁ ×w _256a ,-h ₁ ×w _256a ),

(-15×w _256a , 15×w _256a ), (-15×w _256a , h ₇ ×w _256a ), (-15×w _256a , h ₆ ×w _256a ), (-15×w _256a , h ₅ ×w _256a ), (-15×w _256a , h ₄ ×w _256a ), (-15×w _256a , h ₃ ×w _256a ), (-15×w _256a , h ₂ ×w _256a ), (-15 ×w _256a , h ₁ ×w _256a ), (-15×w _256a ,-15×w _256a ), (-15×w _256a ,-h ₇ ×w _256a ), (-15×w _256a ,-h ₆ ×w _256a ), (-15×w _256a ,-h ₅ ×w _256a ), (-15×w _256a ,-h ₄ ×w _256a ), (-15×w _256a ,-h ₃ ×w _256a ), (-15×w _256a ,-h ₂ ×w _256a ), (-15×w _256a ,-h ₁ ×w _256a ),

(-h ₇ ×w _256a , 15×w _256a ), (-h ₇ ×w _256a , h ₇ ×w _256a ), (-h ₇ ×w _256a , h ₆ ×w _256a ), (-h ₇ ×w _256a , h ₅ ×w _256a ), (-h ₇ ×w _256a , h ₄ ×w _256a ), (-h ₇ ×w _256a , h ₃ ×w _256a ), (-h ₇ ×w _256a , h ₂ × w _256a ), (-h ₇ ×w _256a , h ₁ ×w _256a ), (-h ₇ ×w _256a ,-15×w _256a ), (-h ₇ ×w _256a ,-h ₇ ×w _256a ), (-h ₇ ×w _256a ,-h ₆ ×w _256a ), (-h ₇ ×w _256a ,-h ₅ ×w _256a ), (-h ₇ ×w _256a ,-h ₄ ×w _256a ), (- h ₇ ×w _256a ,-h ₃ ×w _256a ), (-h ₇ ×w _256a ,-h ₂ ×w _256a ), (-h ₇ ×w _256a ,-h ₁ ×w _256a ),

(-h ₆ ×w _256a , 15×w _256a ), (-h ₆ ×w _256a , h ₇ ×w _256a ), (-h ₆ ×w _256a , h ₆ ×w _256a ), (-h ₆ ×w _256a , h ₅ ×w _256a ), (-h ₆ ×w _256a , h ₄ ×w _256a ), (-h ₆ ×w _256a , h ₃ ×w _256a ), (-h ₆ ×w _256a , h ₂ × w _256a ), (-h ₆ ×w _256a , h ₁ ×w _256a ),

(-h ₆ ×w _256a ,-15×w _256a ), (-h ₆ ×w _256a ,-h ₇ ×w _256a ), (-h ₆ ×w _256a ,-h ₆ ×w _256a ), (-h ₆ ×w _256a ,-h ₅ ×w _256a ), (-h ₆ ×w _256a ,-h ₄ ×w _256a ), (-h ₆ ×w _256a ,-h ₃ ×w _256a ), (-h ₆ × w _256a ,-h ₂ ×w _256a ), (-h ₆ ×w _256a ,-h ₁ ×w _256a ),

(-h ₅ ×w _256a , 15×w _256a ), (-h ₅ ×w _256a , h ₇ ×w _256a ), (-h ₅ ×w _256a , h ₆ ×w _256a ), (-h ₅ ×w _256a , h ₅ ×w _256a ), (-h ₅ ×w _256a , h ₄ ×w _256a ), (-h ₅ ×w _256a , h ₃ ×w _256a ), (-h ₅ ×w _256a , h ₂ × w _256a ), (-h ₅ ×w _256a , h ₁ ×w _256a ), (-h ₅ ×w _256a ,-15×w _256a ), (-h ₅ ×w _256a ,-h ₇ ×w _256a ), (-h ₅ ×w _256a ,-h ₆ ×w _256a ), (-h ₅ ×w _256a ,-h ₅ ×w _256a ), (-h ₅ ×w _256a ,-h ₄ ×w _256a ), (- h ₅ ×w _256a ,-h ₃ ×w _256a ), (-h ₅ ×w _256a ,-h ₂ ×w _256a ), (-h ₅ ×w _256a ,-h ₁ ×w _256a ),

(-h ₄ ×w _256a , 15×w _256a ), (-h ₄ ×w _256a , h ₇ ×w _256a ), (-h ₄ ×w _256a , h ₆ ×w _256a ), (-h ₄ ×w _256a , h ₅ ×w _256a ), (-h ₄ ×w _256a , h ₄ ×w _256a ), (-h ₄ ×w _256a , h ₃ ×w _256a ), (-h ₄ ×w _256a , h ₂ × w _256a ), (-h ₄ ×w _256a , h ₁ ×w _256a ),

(-h ₄ ×w _256a ,-15×w _256a ), (-h ₄ ×w _256a ,-h ₇ ×w _256a ), (-h ₄ ×w _256a ,-h ₆ ×w _256a ), (-h ₄ ×w _256a ,-h ₅ ×w _256a ), (-h ₄ ×w _256a ,-h ₄ ×w _256a ), (-h ₄ ×w _256a ,-h ₃ ×w _256a ), (-h ₄ × w _256a ,-h ₂ ×w _256a ), (-h ₄ ×w _256a ,-h ₁ ×w _256a ),

(-h ₃ ×w _256a , 15×w _256a ), (-h ₃ ×w _256a , h ₇ ×w _256a ), (-h ₃ ×w _256a , h ₆ ×w _256a ), (-h ₃ ×w _256a , h ₅ ×w _256a ), (-h ₃ ×w _256a , h ₄ ×w _256a ), (-h ₃ ×w _256a , h ₃ ×w _256a ), (-h ₃ ×w _256a , h ₂ × w _256a ), (-h ₃ ×w _256a , h ₁ ×w _256a ), (-h ₃ ×w _256a ,-15×w _256a ), (-h ₃ ×w _256a ,-h ₇ ×w _256a ), (-h ₃ ×w _256a ,-h ₆ ×w _256a ), (-h ₃ ×w _256a ,-h ₅ ×w _256a ), (-h ₃ ×w _256a ,-h ₄ ×w _256a ), (- h ₃ ×w _256a ,-h ₃ ×w _256a ), (-h ₃ ×w _256a ,-h ₂ ×w _256a ), (-h ₃ ×w _256a ,-h ₁ ×w _256a ),

(-h ₂ ×w _256a , 15×w _256a ), (-h ₂ ×w _256a , h ₇ ×w _256a ), (-h ₂ ×w _256a , h ₆ ×w _256a ), (-h ₂ ×w _256a , h ₅ ×w _256a ), (-h ₂ ×w _256a , h ₄ ×w _256a ), (-h ₂ ×w _256a , h ₃ ×w _256a ), (-h ₂ ×w _256a , h ₂ × w _256a ), (-h ₂ ×w _256a , h ₁ ×w _256a ), (-h ₂ ×w _256a ,-15×w _256a ), (-h ₂ ×w _256a ,-h ₇ ×w _256a ), (-h ₂ ×w _256a ,-h ₆ ×w _256a ), (-h ₂ ×w _256a , h ₅ ×w _256a ), (-h ₂ ×w _256a ,-h ₄ ×w _256a ), (-h ₂ ×w _256a ,-h ₃ ×w _256a ), (-h ₂ ×w _256a ,-h ₂ ×w _256a ), (-h ₂ ×w _256a ,-h ₁ ×w _256a ),

(-h ₁ ×w _256a , 15×w _256a ), (-h ₁ ×w _256a , h ₇ ×w _256a ), (-h ₁ ×w _256a , h ₆ ×w _256a ), (-h×w _256a ) , h ₅ ×w _256a ), (-h ₁ ×w _256a , h ₄ ×w _256a ), (-h ₁ ×w _256a , h ₃ ×w _256a ), (-h ₁ ×w _256a , h ₂ ×w _256a ), (-h ₁ ×w _256a , h ₁ ×w _256a ), (-h ₁ ×w _256a ,-15×w _256a ), (-h ₁ ×w _256a ,-h ₇ ×w _256a ), ( -h ₁ ×w _256a ,-h ₆ ×w _256a ), (-h ₁ ×w _256a ,-h ₅ ×w _256a ), (-h ₁ ×w _256a ,-h ₄ ×w _256a ), (-h ₁ ×w _256a ,-h ₃ ×w _256a ), (-h ₁ ×w _256a ,-h ₂ ×w _256a ), (-h ₁ ×w _256a ,-h ₁ ×w _256a ),

(w _256a is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. It is mapped to point 11301, and if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (15×w _256a , 15×w _256a ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). In addition, an example of the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, b7 (00000000-11111111) and the coordinate of a signal point is as shown in FIG. 256 signal points of 256QAM (“○” in Fig. 113)

(15×w _256a , 15×w _256a ), (15×w _256a , h ₇ ×w _256a ), (15×w _256a , h ₆ ×w _256a ), (15×w _256a , h ₅ ×w _256a ) , (15×w _256a , h ₄ ×w _256a ), (15×w _256a , h ₃ ×w _256a ), (15×w _256a , h ₂ ×w _256a ), (15×w _256a , h ₁ ×w _256a ), (15×w _256a ,-15×w _256a ), (15×w _256a ,-h ₇ × _256a ), (15×w _256a ,-h ₆ ×w _256a ), (15×w _256a ,- h ₅ ×w _256a ), (15×w _256a ,-h ₄ ×w _256a ), (15×w _256a ,-h ₃ ×w _256a ), (15×w _256a ,-h ₂ ×w _256a ), ( 15×w _256a ,-h ₁ ×w _256a ),

(h ₇ ×w _256a , 15×w _256a ), (h ₇ ×w _256a , h ₇ ×w _256a ), (h ₇ ×w _256a , h ₆ ×w _256a ), (h ₇ ×w _256a , h ₅ ×w _256a ), (h ₇ ×w _256a , h ₄ ×w _256a ), (h ₇ ×w _256a , h ₃ ×w _256a ), (h ₇ ×w _256a , h ₂ ×w _256a ), (h ₇ ×w _256a , h ₁ ×w _256a ), (h ₇ ×w _256a ,-15×w _256a ), (h ₇ ×w _256a ,-h ₇ ×w _256a ), (h ₇ ×w _256a ,-h ₆ ×w _256a ), (h ₇ ×w _256a ,-h ₅ ×w _256a ), (h ₇ ×w _256a ,-h ₄ ×w _256a ), (h ₇ ×w _256a ,-h ₃ ×w _256a ), (h ₇ ×w _256a ,-h ₂ ×w _256a ), (h ₇ ×w _256a ,-h ₁ ×w _256a ),

(h ₆ ×w _256a , 15×w _256a ), (h ₆ ×w _256a , h ₇ ×w _256a ), (h ₆ ×w _256a , h ₆ ×w _256a ), (h ₆ ×w _256a , h ₅ ×w _256a ), (h ₆ ×w _256a , h ₄ ×w _256a ), (h ₆ ×w _256a , h ₃ ×w _256a ), (h ₆ ×w _256a , h ₂ ×w _256a ), (h ₆ ×w _256a , h ₁ ×w _256a ), (h ₆ ×w _256a ,-15×w _256a ), (h ₆ ×w _256a ,-h ₇ ×w _256a ), (h ₆ ×w _256a ,-h ₆ ×w _256a ), (h ₆ ×w _256a ,-h ₅ ×w _256a ), (h ₆ ×w _256a ,-h ₄ ×w _256a ), (h ₆ ×w _256a ,-h ₃ ×w _256a ), (h ₆ ×w _256a ,-h ₂ ×w _256a ), (h ₆ ×w _256a ,-h ₁ ×w _256a ),

(h ₅ ×w _256a , 15×w _256a ), (h ₅ ×w _256a , h ₇ ×w _256a ), (h ₅ ×w _256a , h ₆ ×w _256a ), (h ₅ ×w _256a , h ₅ ×w _256a ), (h ₅ ×w _256a , h ₄ ×w _256a ), (h ₅ ×w _256a , h ₃ ×w _256a ), (h ₅ ×w _256a , h ₂ ×w _256a ), (h ₅ ×w _256a , h ₁ ×w _256a ), (h ₅ ×w _256a ,-15×w _256a ), (h ₅ ×w _256a ,-h ₇ ×w _256a ), (h ₅ ×w _256a ,-h ₆ ×w _256a ), (h ₅ ×w _256a ,-h ₅ ×w _256a ), (h ₅ ×w _256a ,-h ₄ ×w _256a ), (h ₅ ×w _256a ,-h ₃ ×w _256a ), (h ₅ ×w _256a ,-h ₂ ×w _256a ), (h ₅ ×w _256a ,-h ₁ ×w _256a ),

(h ₄ ×w _256a , 15×w _256a ), (h ₄ ×w _256a , h ₇ ×w _256a ), (h ₄ ×w _256a , h ₆ ×w _256a ), (h ₄ ×w _256a , h ₅ ×w _256a ), (h ₄ ×w _256a , h ₄ ×w _256a ), (h ₄ ×w _256a , h ₃ ×w _256a ), (h ₄ ×w _256a , h ₂ ×w _256a ), (h ₄ ×w _256a , h ₁ ×w _256a ), (h ₄ ×w _256a ,-15×w _256a ), (h ₄ ×w _256a ,-h7×w _256a ), (h ₄ ×w _256a ,-h ₆ × w _256a ), (h ₄ ×w _256a ,-h ₅ w _256a ), (h ₄ ×w _256a ,-h ₄ ×w _256a ), (h ₄ ×w _256a ,-h ₃ w _256a ), (h ₄ ×w _256a ,-h ₂ w _256a ), (h ₄ ×w _256a ,-h ₁ w _256a ),

(h ₃ ×w _256a , 15×w _256a ), (h ₃ ×w _256a , h ₇ ×w _256a ), (h ₃ ×w _256a , h ₆ ×w _256a ), (h ₃ ×w _256a , h ₅ ×w _256a ), (h ₃ ×w _256a , h ₄ ×w _256a ), (h ₃ ×w _256a , h ₃ ×w _256a ), (h ₃ ×w _256a , h ₂ ×w _256a ), (h ₃ ×w _256a , h ₁ ×w _256a ), (h ₃ ×w _256a ,-15×w _256a ), (h ₃ ×w _256a ,-h ₇ ×w _256a ), (h ₃ ×w _256a ,-h ₆ ×w _256a ), (h ₃ ×w _256a ,-h ₅ ×w _256a ), (h ₃ ×w _256a ,-h ₄ ×w _256a ), (h ₃ ×w _256a ,-h ₃ ×w _256a ), (h ₃ ×w _256a ,-h ₂ ×w _256a ), (h ₃ ×w _256a ,-h ₁ ×w _256a ),

(h ₂ ×w _256a , 15×w _256a ), (h ₂ ×w _256a , h ₇ ×w _256a ), (h ₂ ×w _256a , h ₆ ×w _256a ), (h ₂ ×w _256a , h ₅ ×w _256a ), (h ₂ ×w _256a , h ₄ ×w _256a ), (h ₂ ×w _256a , h ₃ ×w _256a ), (h ₂ ×w _256a , h ₂ ×w _256a ), (h ₂ ×w _256a , h ₁ ×w _256a ), (h ₂ ×w _256a ,-15×w _256a ), (h ₂ ×w _256a ,-h ₇ ×w _256a ), (h ₂ ×w _256a ,-h ₆ ×w _256a ), (h ₂ ×w _256a ,-h ₅ ×w _256a ), (h ₂ ×w _256a ,-h ₄ ×w _256a ), (h ₂ ×w _256a ,-h ₃ ×w _256a ), (h ₂ ×w _256a ,-h ₂ ×w _256a ), (h ₂ ×w _256a ,-h ₁ ×w _256a ),

(h ₁ ×w _256a , 15×w _256a ), (h ₁ ×w _256a , h ₇ ×w _256a ), (h ₁ ×w _256a , h ₆ ×w _256a ), (h ₁ ×w _256a , h ₅ ×w _256a ), (h ₁ ×w _256a , h ₄ ×w _256a ), (h ₁ ×w _256a , h ₃ ×w _256a ), (h ₁ ×w _256a , h ₂ ×w _256a ), (h ₁ ×w _256a , h ₁ ×w _256a ), (h ₁ ×w _256a ,-15×w _256a ), (h ₁ ×w _256a ,-h ₇ ×w _256a ), (h ₁ ×w _256a ,-h ₆ ×w _256a ), (h ₁ ×w _256a ,-h ₅ ×w _256a ), (h ₁ ×w _256a ,-h ₄ ×w _256a ), (h ₁ ×w _256a ,-h ₃ ×w _256a ), (h ₁ ×w _256a ,-h ₂ ×w _256a ), (h ₁ ×w _256a ,-h ₁ ×w _256a ),

(-15×w _256a , 15×w _256a ), (-15×w _256a , h ₇ ×w _256a ), (-15×w _256a , h ₆ ×w _256a ), (-15×w _256a , h ₅ ×w _256a ), (-15×w _256a , h ₄ ×w _256a ), (-15×w _256a , h ₃ ×w _256a ), (-15×w _256a , h ₂ ×w _256a ), (-15 ×w _256a , h ₁ ×w _256a ), (-15×w _256a ,-15×w _256a ), (-15×w _256a ,-h ₇ ×w _256a ), (-15×w _256a ,-h ₆ ×w _256a ), (-15×w _256a ,-h ₅ ×w _256a ), (-15×w _256a ,-h ₄ ×w _256a ), (-15×w _256a ,-h ₃ ×w _256a ), (-15×w _256a ,-h ₂ ×w _256a ), (-15×w _256a ,-h ₁ ×w _256a ),

(-h ₇ ×w _256a , 15×w _256a ), (-h ₇ ×w _256a , h ₇ ×w _256a ), (-h ₇ ×w _256a , h ₆ ×w _256a ), (-h ₇ ×w _256a , h ₅ ×w _256a ), (-h ₇ ×w _256a , h ₄ ×w _256a ), (-h ₇ ×w _256a , h ₃ ×w _256a ), (-h ₇ ×w _256a , h ₂ × w _256a ), (-h ₇ ×w _256a , h ₁ ×w _256a ), (-h ₇ ×w _256a ,-15×w _256a ), (-h ₇ ×w _256a ,-h ₇ ×w _256a ), (-h ₇ ×w _256a ,-h ₆ ×w _256a ), (-h ₇ ×w _256a ,-h ₅ ×w _256a ), (-h ₇ ×w _256a ,-h ₄ ×w _256a ), (- h ₇ ×w _256a ,-h ₃ ×w _256a ), (-h ₇ ×w _256a ,-h ₂ ×w _256a ), (-h ₇ ×w _256a ,-h ₁ ×w _256a ),

(-h ₆ ×w _256a , 15×w _256a ), (-h ₆ ×w _256a , h ₇ ×w _256a ), (-h ₆ ×w _256a , h ₆ ×w _256a ), (-h ₆ ×w _256a , h ₅ ×w _256a ), (-h ₆ ×w _256a , h ₄ ×w _256a ), (-h ₆ ×w _256a , h ₃ ×w _256a ), (-h ₆ ×w _256a , h ₂ × w _256a ), (-h ₆ ×w _256a , h ₁ ×w _256a ),(-h ₆ ×w _256a ,-15×w _256a ), (-h ₆ ×w _256a ,-h ₇ ×w _256a ), (-h ₆ ×w _256a ,-h ₆ ×w _256a ), (-h ₆ ×w _256a ,-h ₅ ×w _256a ), (-h ₆ ×w _256a ,-h ₄ ×w _256a ), (- h ₆ ×w _256a ,-h ₃ ×w _256a ), (-h ₆ ×w _256a ,-h ₂ ×w _256a ), (-h ₆ ×w _256a ,-h ₁ ×w _256a ),

(-h ₅ ×w _256a , 15×w _256a ), (-h ₅ ×w _256a , h ₇ ×w _256a ), (-h ₅ ×w _256a , h ₆ ×w _256a ), (-h ₅ ×w _256a , h ₅ ×w _256a ), (-h ₅ ×w _256a , h ₄ ×w _256a ), (-h ₅ ×w _256a , h ₃ ×w _256a ), (-h ₅ ×w _256a , h ₂ × w _256a ), (-h ₅ ×w _256a , h ₁ ×w _256a ), (-h ₅ ×w _256a ,-15×w _256a ), (-h ₅ ×w _256a ,-h ₇ ×w _256a ), (-h ₅ ×w _256a ,-h ₆ ×w _256a ), (-h ₅ ×w _256a ,-h ₅ ×w _256a ), (-h ₅ ×w _256a ,-h ₄ ×w _256a ), (- h ₅ ×w _256a ,-h ₃ ×w _256a ), (-h ₅ ×w _256a ,-h ₂ ×w _256a ), (-h ₅ ×w _256a ,-h ₁ ×w _256a ),

(-h ₄ ×w _256a , 15×w _256a ), (-h ₄ ×w _256a , h ₇ ×w _256a ), (-h ₄ ×w _256a , h ₆ ×w _256a ), (-h ₄ ×w _256a , h ₅ ×w _256a ), (-h ₄ ×w _256a , h ₄ ×w _256a ), (-h ₄ ×w _256a , h ₃ ×w _256a ), (-h ₄ ×w _256a , h ₂ × w _256a ), (-h ₄ ×w _256a , h ₁ ×w _256a ),(-h ₄ ×w _256a ,-15×w _256a ), (-h ₄ ×w _256a ,-h ₇ ×w _256a ), (-h ₄ ×w _256a ,-h ₆ ×w _256a ), (-h ₄ ×w _256a ,-h ₅ ×w _256a ), (-h ₄ ×w _256a ,-h ₄ ×w _256a ), (- h ₄ ×w _256a ,-h ₃ ×w _256a ), (-h ₄ ×w _256a ,-h ₂ ×w _256a ), (-h ₄ ×w _256a ,-h ₁ ×w _256a ),

(-h ₃ ×w _256a , 15×w _256a ), (-h ₃ ×w _256a , h ₇ ×w _256a ), (-h ₃ ×w _256a , h ₆ ×w _256a ), (-h ₃ ×w _256a , h ₅ ×w _256a ), (-h ₃ ×w _256a , h ₄ ×w _256a ), (-h ₃ ×w _256a , h ₃ ×w _256a ), (-h ₃ ×w _256a , h ₂ × w _256a ), (-h ₃ ×w _256a , h ₁ ×w _256a ), (-h ₃ ×w _256a ,-15×w _256a ), (-h ₃ ×w _256a ,-h ₇ ×w _256a ), (-h ₃ ×w _256a ,-h ₆ ×w _256a ), (-h ₃ ×w _256a ,-h ₅ ×w _256a ), (-h ₃ ×w _256a ,-h ₄ ×w _256a ), (- h ₃ ×w _256a ,-h ₃ ×w _256a ), (-h ₃ ×w _256a ,-h ₂ ×w _256a ), (-h ₃ ×w _256a ,-h ₁ ×w _256a ),

(-h ₂ ×w _256a , 15×w _256a ), (-h ₂ ×w _256a , h ₇ ×w _256a ), (-h ₂ ×w _256a , h ₆ ×w _256a ), (-h ₂ ×w _256a , h ₅ ×w _256a ), (-h ₂ ×w _256a , h ₄ ×w _256a ), (-h ₂ ×w _256a , h ₃ ×w _256a ), (-h ₂ ×w _256a , h ₂ × w _256a ), (-h ₂ ×w _256a , h ₁ ×w _256a ), (-h ₂ ×w _256a ,-15×w _256a ), (-h ₂ ×w _256a ,-h ₇ ×w _256a ), (-h ₂ ×w _256a ,-h ₆ ×w _256a ), (-h ₂ ×w _256a , h ₅ ×w _256a ), (-h ₂ ×w _256a ,-h ₄ ×w _256a ), (-h ₂ ×w _256a ,-h ₃ ×w _256a ), (-h ₂ ×w _256a ,-h ₂ ×w _256a ), (-h ₂ ×w _256a ,-h ₁ ×w _256a ),

(-h ₁ ×w _256a , 15×w _256a ), (-h ₁ ×w _256a , h ₇ ×w _256a ), (-h ₁ ×w _256a , h ₆ ×w _256a ), (-h×w _256a ) , h ₅ ×w _256a ), (-h ₁ ×w _256a , h ₄ ×w _256a ), (-h ₁ ×w _256a , h ₃ ×w _256a ), (-h ₁ ×w _256a , h ₂ ×w _256a ), (-h ₁ ×w _256a , h ₁ ×w _256a ), (-h ₁ ×w _256a ,-15×w _256a ), (-h ₁ ×w _256a ,-h ₇ ×w _256a ), ( -h ₁ ×w _256a ,-h ₆ ×w _256a ), (-h ₁ ×w _256a ,-h ₅ ×w _256a ), (-h ₁ ×w _256a ,-h ₄ ×w _256a ), (-h ₁ ×w _256a ,-h ₃ ×w _256a ), (-h ₁ ×w _256a ,-h ₂ ×w _256a ), (-h ₁ ×w _256a ,-h ₁ ×w _256a ),

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 113 .

In the 256 signal points in FIG. 113, "signal point 1", "signal point 2"... It is called "signal point 255" and "signal point 256". (Since there are 256 signal points, "signal point 1" to "signal point 256" exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _256a is given as follows.

Then, the average power _of the baseband signal after mapping becomes z2.

In addition, the case equivalent to (configuration example R1) in the previous description is called uniform-256QAM, and the case other than this is called non-uniform 256QAM.

(Supplementary 3)

In Embodiments 1 to 11, the bit length adjustment method has been described. Further, in the twelfth embodiment, the case where the bit length adjustment method of the first to eleventh embodiments is applied to the DVB standard has been described. Among these embodiments, a case in which 16QAM, 64QAM, and 256QAM are applied as modulation schemes is described. In addition, a specific mapping method for 16QAM, 64QAM, and 256QAM is described in (Configuration Example R1).

Hereinafter, configuration methods such as 16QAM, 64QAM, and 256QAM mapping methods different from (Configuration Example R1) and (Supplementary 2) will be described. Further, 16QAM, 64QAM, and 256QAM described below may be applied to the first to twelfth embodiments, and at this time, the effects described in the first to twelfth embodiments can be obtained.

A mapping method of 16QAM will be described. 114 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In addition, in Fig. 114, 16 circles denote 16QAM signal points, the abscissa denotes I and the ordinate denotes Q. 114, f ₁ >0 (f ₁ is a real number greater than 0), f ₂ >0 (f ₂ is a real number greater than 0), f ₁ ≠ 3, and f ₂ ≠ 3 , and also f ₁ ≠ f ₂ .

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 114 is the signal point) in the in-phase I-orthogonal Q plane are,

(3×w _16b , 3×w _16b ), (3×w _16b , f ₂ ×w _16b ), (3×w _16b ,-f ₂ ×w _16b ), (3×w _16b ,-3×w _16b ) ), (f ₁ ×w _16b , 3×w _16b ), (f ₁ ×w _16b , f ₂ ×w _16b ), (f ₁ ×w _16b ,-f ₂ ×w _16b ), (f1×w _16b , -3×w _16b ), (-f ₁ ×w _16b , 3×w _16b ), (-f ₁ ×w _16b , f ₂ ×w _16b ), (-f ₁ ×w _16b ,-f ₂ ×w _16b ) ), (-f ₁ ×w _16b ,-3×w _16b ), (-3×w _16b , 3×w _16b ), (-3×w _16b , f ₂ ×w _16b ), (-3×w _16b ) ,-f ₂ ×w _16b ), (-3×w _16b ,-3×w _16b ),

(w _16b is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, when the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 11401 in FIG. 114, and the in-phase component of the baseband signal after mapping is I , when the orthogonal component is Q, (I, Q) = (3×w _16b , 3×w _16b ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in Fig. 114)

(3×w _16b , 3×w _16b ), (3×w _16b , f ₂ ×w _16b ), (3×w _16b ,-f ₂ ×w _16b ), (3×w _16b ,-3×w _16b ) ), (f ₁ ×w _16b , 3×w _16b ), (f ₁ ×w _16b , f ₂ ×w _16b ), (f ₁ ×w _16b ,-f ₂ ×w _16b ), (f1×w _16b , -3×w _16b ), (-f ₁ ×w _16b , 3×w _16b ), (-f ₁ ×w _16b , f ₂ ×w _16b ), (-f ₁ ×w _16b ,-f ₂ ×w _16b ) ), (-f ₁ ×w _16b ,-3×w _16b ), (-3×w _16b , 3×w _16b ), (-3×w _16b , f ₂ ×w _16b ), (-3×w _16b ) ,-f ₂ ×w _16b ), (-3×w _16b ,-3×w _16b ),

The values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown just below. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000-1111) and the coordinates of the signal points in 16QAM is not limited to FIG. 114 .

In the 16 signal points in Fig. 114, "signal point 1", "signal point 2"... It is called "signal point 15" and "signal point 16". (Since there are 16 signal points, &quot;signal point 1&quot; to &quot;signal point 16&quot; exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _16b is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2. In addition, the effect of 16QAM described above will be described later. The 64QAM mapping method will be described. 115 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. In Fig. 115, 64 circles denote 64QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

115, g ₁ >0 (g1 is a real number greater than 0), g ₂ >0 (g ₂ is a real number greater than 0), and g ₃ >0 (g ₃ is a real number greater than 0) Also, g ₄ >0 (g ₄ is a real number greater than 0), g ₅ >0 (g ₅ is a real number greater than 0), and g ₆ >0 (g ₆ is a real number greater than 0) ) and

{g ₁ ≠ 7, g ₂ ≠ 7, g ₃ ≠ 7, g ₁ ≠ g ₂ , g ₁ ≠ g ₃ , and g ₂ ≠ g 3}

In addition,

{g ₄ ≠ 7, g ₅ ≠ 7, g ₆ ≠ 7, g ₄ ≠ g ₅ , g ₄ ≠ g ₆ , and g ₅ ≠ g _6}

In addition,

{{g ₁ ≠g ₄ , or g ₂ ≠g ₅ , or g ₃ ≠g ₆ } holds}.

The respective coordinates of 64 signal points of 64QAM (“○” in FIG. 115 are signal points) in the in-phase I-orthogonal Q plane are,

(7×w _64b , 7×w _64b ), (7×w _64b , g6×w _64b ), (7×w _64b , g5×w _64b ), (7×w _64b , g4×w _64b ), (7 ×w _64b ,-g4×w _64b ), (7×w _64b ,-g5×w _64b ), (7×w _64b ,-g6×w _64b ), (7×w _64b ,-7×w _64b )

(g ₃ ×w _64b , 7×w _64b ), (g ₃ ×w _64b , g ₆ ×w _64b ), (g ₃ ×w _64b , g ₅ ×w _64b ), (g ₃ ×w _64b , g ₄ ×w _64b ), (g ₃ ×w _64b ,-g ₄ ×w _64b ), (g ₃ ×w _64b ,-g ₅ ×w _64b ), (g ₃ ×w _64b ,-g ₆ ×w _64b ), (g ₃ ×w _64b ,-7×w _64b )

(g ₂ ×w _64b , 7×w _64b ), (g ₂ ×w _64b , g ₆ ×w _64b ), (g ₂ ×w _64b , g ₅ ×w _64b ), (g ₂ ×w _64b , g ₄ ×w _64b ), (g ₂ ×w _64b ,-g ₄ ×w _64b ), (g ₂ ×w _64b ,-g ₅ ×w _64b ), (g ₂ ×w _64b ,-g ₆ ×w _64b ), (g ₂ ×w _64b ,-7×w _64b )

(g ₁ ×w _64b , 7×w _64b ), (g ₁ ×w _64b , g ₆ ×w _64b ), (g ₁ ×w _64b , g ₅ ×w _64b ), (g ₁ ×w _64b , g ₄ ×w _64b ), (g ₁ ×w _64b ,-g ₄ ×w _64b ), (g ₁ ×w _64b ,-g ₅ ×w _64b ), (g ₁ ×w _64b ,-g ₆ ×w _64b ), (g ₁ ×w _64b ,-7×w _64b )

(-g ₁ ×w _64b , 7×w _64b ), (-g ₁ ×w _64b , g ₆ ×w _64b ), (-g ₁ ×w _64b , g ₅ ×w _64b ), (-g ₁ ×w _64b , g ₄ ×w _64b ), (-g ₁ ×w _64b ,-g4×w _64b ), (-g ₁ ×w _64b ,-g5×w _64b ), (-g ₁ ×w _64b ,-g6× w _64b ), (-g ₁ ×w _64b ,-7×w _64b )

(-g ₂ ×w _64b , 7×w _64b ), (-g ₂ ×w _64b , g ₆ ×w _64b ), (-g ₂ ×w _64b , g ₅ ×w _64b ), (-g ₂ ×w _64b , g ₄ ×w _64b ), (-g ₂ ×w _64b ,-g ₄ ×w _64b ), (-g ₂ ×w _64b ,-g ₅ ×w _64b ), (-g ₂ ×w _64b ,- g ₆ ×w _64b ), (-g ₂ ×w _64b ,-7×w _64b )

(-g ₃ ×w _64b , 7×w _64b ), (-g ₃ ×w _64b , g ₆ ×w _64b ), (-g ₃ ×w _64b , g ₅ ×w _64b ), (-g ₃ ×w _64b , g ₄ ×w _64b ), (-g ₃ ×w _64b ,-g ₄ ×w _64b ), (-g ₃ ×w _64b ,-g ₅ ×w _64b ), (-g ₃ ×w _64b ,- g ₆ ×w _64b ), (-g ₃ ×w _64b ,-7×w _64b )

(-7×w _64b , 7×w _64b ), (-7×w _64b , g ₆ ×w _64b ), (-7×w _64b , g ₅ ×w _64b ), (-7×w _64b , g ₄ ×w _64b ), (-7×w _64b ,-g ₄ ×w _64b ), (-7×w _64b ,-g ₅ ×w _64b ), (-7×w _64b ,-g ₆ ×w _64b ), (-7×w _64b , -7×w _64b )

(w _64b is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to signal point 11501 in FIG. When the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (7×w _64b , 7×w _64b ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). In addition, an example of the relationship between the set (000000-111111) of b0, b1, b2, b3, b4, b5, and the coordinate of a signal point is as shown in FIG. 64 signal points of 64QAM (“○” in Fig. 115)

(7×w _64b , 7×w _64b ), (7×w _64b , g6×w _64b ), (7×w _64b , g5×w _64b ), (7×w _64b , g4×w _64b ), (7 ×w _64b ,-g4×w _64b ), (7×w _64b ,-g5×w _64b ), (7×w _64b ,-g6×w _64b ), (7×w _64b ,-7×w _64b )

(g ₃ ×w _64b , 7×w _64b ), (g ₃ ×w _64b , g ₆ ×w _64b ), (g ₃ ×w _64b , g ₅ ×w _64b ), (g ₃ ×w _64b , g ₄ ×w _64b ), (g ₃ ×w _64b ,-g ₄ ×w _64b ), (g ₃ ×w _64b ,-g ₅ ×w _64b ), (g ₃ ×w _64b ,-g ₆ ×w _64b ), (g ₃ ×w _64b ,-7×w _64b )

(g ₂ ×w _64b , 7×w _64b ), (g ₂ ×w _64b , g ₆ ×w _64b ), (g ₂ ×w _64b , g ₅ ×w _64b ), (g ₂ ×w _64b , g ₄ ×w _64b ), (g ₂ ×w _64b ,-g ₄ ×w _64b ), (g ₂ ×w _64b ,-g ₅ ×w _64b ), (g ₂ ×w _64b ,-g ₆ ×w _64b ), (g ₂ ×w _64b ,-7×w _64b )

(g ₁ ×w _64b , 7×w _64b ), (g ₁ ×w _64b , g ₆ ×w _64b ), (g ₁ ×w _64b , g ₅ ×w _64b ), (g ₁ ×w _64b , g ₄ ×w _64b ), (g ₁ ×w _64b ,-g ₄ ×w _64b ), (g ₁ ×w _64b ,-g ₅ ×w _64b ), (g ₁ ×w _64b ,-g ₆ ×w _64b ), (g ₁ ×w _64b ,-7×w _64b )

(-g ₁ ×w _64b , 7×w _64b ), (-g ₁ ×w _64b , g ₆ ×w _64b ), (-g ₁ ×w _64b , g ₅ ×w _64b ), (-g ₁ ×w _64b , g ₄ ×w _64b ), (-g ₁ ×w _64b ,-g4×w _64b ), (-g ₁ ×w _64b ,-g5×w _64b ), (-g ₁ ×w _64b ,-g6× w _64b ), (-g ₁ ×w _64b ,-7×w _64b )

(-g ₂ ×w _64b , 7×w _64b ), (-g ₂ ×w _64b , g ₆ ×w _64b ), (-g ₂ ×w _64b , g ₅ ×w _64b ), (-g ₂ ×w _64b , g ₄ ×w _64b ), (-g ₂ ×w _64b ,-g ₄ ×w _64b ), (-g ₂ ×w _64b ,-g ₅ ×w _64b ), (-g ₂ ×w _64b ,- g ₆ ×w _64b ), (-g ₂ ×w _64b ,-7×w _64b )

(-g ₃ ×w _64b , 7×w _64b ), (-g ₃ ×w _64b , g ₆ ×w _64b ), (-g ₃ ×w _64b , g ₅ ×w _64b ), (-g ₃ ×w _64b , g ₄ ×w _64b ), (-g ₃ ×w _64b ,-g ₄ ×w _64b ), (-g ₃ ×w _64b ,-g ₅ ×w _64b ), (-g ₃ ×w _64b ,- g ₆ ×w _64b ), (-g ₃ ×w _64b ,-7×w _64b )

(-7×w _64b , 7×w _64b ), (-7×w _64b , g ₆ ×w _64b ), (-7×w _64b , g ₅ ×w _64b ), (-7×w _64b , g ₄ ×w _64b ), (-7×w _64b ,-g ₄ ×w _64b ), (-7×w _64b ,-g ₅ ×w _64b ), (-7×w _64b ,-g ₆ ×w _64b ), (-7×w _64b , -7×w _64b )

The values of sets 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 115 .

In the 64 signal points in Fig. 115, "signal point 1", "signal point 2"... It is called "signal point 63" and "signal point 64". (Since there are 64 signal points, &quot;signal point 1&quot; to &quot;signal point 64&quot; exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _64b is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2. In addition, the effect is demonstrated next.

A mapping method of 256QAM will be described. 116 shows an example of the arrangement of signal points of 256QAM in the in-phase I-orthogonal Q plane. In Fig. 116, 256 ? denote 256QAM signal points, the horizontal axis denotes I, and the vertical axis denotes Q.

116, h ₁ >0 (h ₁ is a real number greater than 0), h ₂ >0 (h ₂ is a real number greater than 0), and h ₃ >0 (h ₃ is a real number greater than 0) , h ₄ >0 (h ₄ is a real number greater than 0), h ₅ >0 (h ₅ is a real number greater than 0), and h ₆ >0 (h ₆ is a real number greater than 0) ), h ₇ >0 (h ₇ is a real number greater than 0), h ₈ >0 (h ₈ is a real number greater than 0), and h ₉ >0 (h ₉ is a real number greater than 0) real number), h ₁₀ >0 (h ₁₀ is a real number greater than 0), h ₁₁ >0 (h ₁₁ is a real number greater than 0), and h ₁₂ >0 (h ₁₂ is a real number greater than 0) big real number), and h ₁₃ >0 (h ₁₃ is a real number greater than 0), and h ₁₄ >0 (h ₁₄ is a real number greater than 0),

{h ₁ ≠ 15, h ₂ ≠ 15, h ₃ ≠ 15, h ₄ ≠ 15, h ₅ ≠ 15, h ₆ ≠ 15, and h ₇ ≠ 15,

Further, h ₁ ≠ h ₂ , h ₁ ≠ h ₃ , h ₁ ≠ h ₄ , h ₁ ≠ h ₅ , h ₁ ≠ h ₆ , and h ₁ ≠ h ₇ , h ₂ ≠ h ₃ , h ₂ ≠ h ₄ , h ₂ ≠ h ₅ , h ₂ ≠ h ₆ , and h ₂ ≠ h ₇ , and , h ₃ ≠h ₄ , h ₃ ≠ h ₅ , h ₃ ≠ h ₆ , h ₃ ≠ h ₇ , h ₄ ≠ h ₅ , and h ₄ ≠ h ₆ , and h ₄ ≠h ₇ , h ₅ ≠h ₆ , and h ₅ ≠h ₇ , and further h ₆ ≠h ₇ },

In addition,

{h ₈ ≠ 15, h ₉ ≠ 15, h ₁₀ ≠ 15, h ₁₁ ≠ 15, h ₁₂ ≠ 15, h ₁₃ ≠ 15, and h ₁₄ ≠ 15, h ₈ ≠ h ₉ , h ₈ ≠ h ₁₀ , h ₈ ≠ h ₁₁ , h ₈ ≠ h ₁₂ , h ₈ ≠ h ₁₃ , Further, h ₈ ≠ h ₁₄ , h ₉ ≠ h ₁₀ , h ₉ ≠ h ₁₁ , h ₉ ≠ h ₁₂ , h ₉ ≠ h ₁₃ , and h ₉ ≠ h ₁₄ , h ₁₀ ≠h ₁₁ , h ₁₀ ≠ h ₁₂ , h ₁₀ ≠ h ₁₃ , h ₁₀ ≠ h ₁₄ , h ₁₁ ≠ h ₁₂ , and , h ₁₁ ≠h ₁₃ , h ₁₁ ≠ h ₁₄ , h ₁₂ ≠ h ₁₃ , h ₁₂ ≠ h ₁₄ , and h ₁₃ ≠ h ₁₄ },

In addition,

{h ₁ ≠h ₈ , or h ₂ ≠h ₉ , or h ₃ ≠h ₁₀ , or h ₄ ≠h ₁₁ , or h ₅ ≠h ₁₂ , or h ₆ ≠h ₁₃ , or h ₇ ≠h ₁₄ } come true

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 116 is the signal point) in the in-phase I-orthogonal Q plane are,

(15×w _256b , 15×w _256b ), (15×w _256b , h ₁₄ ×w _256b ), (15×w _256b , h ₁₃ ×w _256b ), (15×w _256b , h ₁₂ ×w _256b ) , (15×w _256b , h ₁₁ ×w _256b ), (15×w _256b , h ₁₀ ×w _256b ), (15×w _256b , h ₉ ×w _256b ), (15×w _256b , h ₈ ×w _256b ), (15×w _256b , -15×w _256b ), (15×w _256b ,-h ₁₄ ×w _256b ), (15×w _256b ,-h ₁₃ ×w _256b ), (15×w _256b ) -h ₁₂ ×w _256b ), (15×w _256b ,-h ₁₁ ×w _256b ), (15×w _256b ,-h ₁₀ ×w _256b ), (15×w _256b ,-h ₉ ×w _256b ), (15×w _256b ,-h ₈ ×w _256b ),

(h ₇ ×w _256b , 15×w _256b ), (h ₇ ×w _256b , h ₁₄ ×w _256b ), (h ₇ ×w _256b , h ₁₃ ×w _256b ), (h ₇ ×w _256b , h ₁₂ ×w _256b ), (h ₇ ×w _256b , h ₁₁ ×w _256b ), (h ₇ ×w _256b , h ₁₀ ×w _256b ), (h ₇ ×w _256b , h ₉ ×w _256b ), (h ₇ ×w _256b , h ₈ ×w _256b ), (h ₇ ×w _256b , -15×w _256b ), (h ₇ ×w _256b ,-h ₁₄ ×w _256b ), (h ₇ ×w _256b ,-h ₁₃ ×w _256b ), (h ₇ ×w _256b ,-h ₁₂ ×w _256b ), (h ₇ ×w _256b ,-h ₁₁ ×w _256b ), (h ₇ ×w _256b ,-h ₁₀ ×w _256b ), (h ₇ ×w _256b ,-h ₉ ×w _256b ), (h ₇ ×w _256b ,-h ₈ ×w _256b ),

(h ₆ ×w _256b , 15×w _256b ), (h ₆ ×w _256b , h ₁₄ ×w _256b ), (h ₆ ×w _256b , h ₁₃ ×w _256b ), (h ₆ ×w _256b , h ₁₂ ×w _256b ), (h ₆ ×w _256b , h ₁₁ ×w _256b ), (h ₆ ×w _256b , h ₁₀ ×w _256b ), (h ₆ ×w _256b , h ₉ ×w _256b ), (h ₆ ×w _256b , h ₈ ×w _256b ), (h ₆ ×w _256b , -15×w _256b ), (h ₆ ×w _256b ,-h ₁₄ ×w _256b ), (h ₆ ×w _256b ,-h ₁₃ ×w _256b ), (h ₆ ×w _256b ,-h ₁₂ ×w _256b ), (h ₆ ×w _256b ,-h ₁₁ ×w _256b ), (h ₆ ×w _256b ,-h ₁₀ ×w _256b ), (h ₆ ×w _256b ,-h ₉ ×w _256b ), (h ₆ ×w _256b ,-h ₈ ×w _256b ),

(h ₅ ×w _256b , 15×w _256b ), (h ₅ ×w _256b , h ₁₄ ×w _256b ), (h ₅ ×w _256b , h ₁₃ ×w _256b ), (h ₅ ×w _256b , h ₁₂ ×w _256b ), (h ₅ ×w _256b , h ₁₁ ×w _256b ), (h ₅ ×w _256b , h ₁₀ ×w _256b ), (h ₅ ×w _256b , h ₉ ×w _256b ), (h ₅ ×w _256b , h ₈ ×w _256b ), (h ₅ ×w _256b , -15×w _256b ), (h ₅ ×w _256b ,-h ₁₄ ×w _256b ), (h ₅ ×w _256b ,-h ₁₃ ×w _256b ), (h ₅ ×w _256b ,-h ₁₂ ×w _256b ), (h ₅ ×w _256b ,-h ₁₁ ×w _256b ), (h ₅ ×w _256b ,-h ₁₀ ×w _256b ), (h ₅ ×w _256b ,-h ₉ ×w _256b ), (h ₅ ×w _256b ,-h ₈ ×w _256b ),

(h ₄ ×w _256b , 15×w _256b ), (h ₄ ×w _256b , h ₁₄ ×w _256b ), (h ₄ ×w _256b , h ₁₃ ×w _256b ), (h ₄ ×w _256b , h ₁₂ ×w _256b ), (h ₄ ×w _256b , h ₁₁ ×w _256b ), (h ₄ ×w _256b , h ₁₀ ×w _256b ), (h ₄ ×w _256b , h ₉ ×w _256b ), (h ₄ ×w _256b , h ₈ ×w _256b ), (h ₄ ×w _256b , -15×w _256b ), (h ₄ ×w _256b ,-h ₁₄ ×w _256b ), (h ₄ ×w _256b ,-h ₁₃ ×w _256b ), (h ₄ ×w _256b ,-h ₁₂ ×w _256b ), (h ₄ ×w _256b ,-h ₁₁ ×w _256b ), (h ₄ ×w _256b ,-h ₁₀ ×w _256b ), (h ₄ ×w _256b ,-h ₉ ×w _256b ), (h ₄ ×w _256b ,-h ₈ ×w _256b ),

(h ₃ ×w _256b , 15×w _256b ), (h ₃ ×w _256b , h ₁₄ ×w _256b ), (h ₃ ×w _256b , h ₁₃ ×w _256b ), (h ₃ ×w _256b , h ₁₂ ×w _256b ), (h ₃ ×w _256b , h ₁₁ ×w _256b ), (h ₃ ×w _256b , h ₁₀ ×w _256b ), (h ₃ ×w _256b , h ₉ ×w _256b ), (h ₃ ×w _256b , h ₈ ×w _256b ), (h ₃ ×w _256b , -15×w _256b ), (h ₃ ×w _256b ,-h ₁₄ ×w _256b ), (h ₃ ×w _256b ,-h ₁₃ ×w _256b ), (h ₃ ×w _256b ,-h ₁₂ ×w _256b ), (h ₃ ×w _256b ,-h ₁₁ ×w _256b ), (h ₃ ×w _256b ,-h ₁₀ ×w _256b ), (h ₃ ×w _256b ,-h ₉ ×w _256b ), (h ₃ ×w _256b ,-h ₈ ×w _256b ),

(h ₂ ×w _256b , 15×w _256b ), (h ₂ ×w _256b , h ₁₄ ×w _256b ), (h ₂ ×w _256b , h ₁₃ ×w _256b ), (h ₂ ×w _256b , h ₁₂ ×w _256b ), (h ₂ ×w _256b , h ₁₁ ×w _256b ), (h ₂ ×w _256b , h ₁₀ ×w _256b ), (h ₂ ×w _256b , h ₉ ×w _256b ), (h ₂ ×w _256b , h ₈ ×w _256b ), (h ₂ ×w _256b , -15×w _256b ), (h ₂ ×w _256b ,-h ₁₄ ×w _256b ), (h ₂ ×w _256b ,-h ₁₃ ×w _256b ), (h ₂ ×w _256b ,-h ₁₂ ×w _256b ), (h ₂ ×w _256b ,-h ₁₁ ×w _256b ), (h ₂ ×w _256b ,-h ₁₀ ×w _256b ), (h ₂ ×w _256b ,-h ₉ ×w _256b ), (h ₂ ×w _256b ,-h ₈ ×w _256b ),

(h ₁ ×w _256b , 15×w _256b ), (h ₁ ×w _256b , h ₁₄ ×w _256b ), (h ₁ ×w _256b , h ₁₃ ×w _256b ), (h ₁ ×w _256b , h ₁₂ ×w _256b ), (h ₁ ×w _256b , h ₁₁ ×w _256b ), (h ₁ ×w _256b , h ₁₀ ×w _256b ), (h ₁ ×w _256b , h ₉ ×w _256b ), (h ₁ ×w _256b , h ₈ ×w _256b ),

(h ₁ ×w _256b ,-15×w _256b ), (h ₁ ×w _256b ,-h ₁₄ ×w _256b ), (h ₁ ×w _256b ,-h ₁₃ ×w _256b ), (h ₁ ×w _256b ) ,-h ₁₂ ×w _256b ), (h ₁ ×w _256b ,-h ₁₁ ×w _256b ), (h ₁ ×w _256b ,-h ₁₀ ×w _256b ), (h ₁ ×w _256b ,-h ₉ × w _256b ), (h ₁ ×w _256b ,-h ₈ ×w _256b ), (-15×w _256b , 15×w _256b ), (-15×w _256b , h ₁₄ ×w _256b ), (-15× w _256b , h ₁₃ ×w _256b ), (-15×w _256b , h ₁₂ ×w _256b ), (-15×w _256b , h ₁₁ ×w _256b ), (-15×w _256b , h ₁₀ ×w _256b ) ), (-15×w _256b , h ₉ ×w _256b ), (-15×w _256b , h ₈ ×w _256b ),

(-15×w _256b ,-15×w _256b ), (-15×w _256b ,-h ₁₄ ×w _256b ), (-15×w _256b ,-h ₁₃ ×w _256b ), (-15×w _256b ) ,-h ₁₂ ×w _256b ), (-15×w _256b ,-h ₁₁ ×w _256b ), (-15×w _256b , h ₁₀ ×w _256b ), (-15×w _256b ,-h ₉ ×w _256b ), (-15×w _256b ,-h ₈ ×w _256b ),

(-h ₇ ×w _256b , 15×w _256b ), (-h ₇ ×w _256b , h ₁₄ ×w _256b ), (-h ₇ ×w _256b , h ₁₃ ×w _256b ), (-h ₇ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₇ ×w _256b , h ₁₁ ×w _256b ), (-h ₇ ×w _256b , h ₁₀ ×w _256b ), (-h ₇ ×w _256b , h ₉ × w _256b ), (-h ₇ ×w _256b , h ₈ ×w _256b ), (-h ₇ ×w _256b ,-15×w _256b ), (-h ₇ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₇ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₇ ×w _256b ,-h ₉ ×w _256b ), (-h ₇ ×w _256b , h ₈ ×w _256b ),

(-h ₆ ×w _256b , 15×w _256b ), (-h ₆ ×w _256b , h ₁₄ ×w _256b ), (-h ₆ ×w _256b , h ₁₃ ×w _256b ), (-h ₆ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₆ ×w _256b , h ₁₁ ×w _256b ), (-h ₆ ×w _256b , h ₁₀ ×w _256b ), (-h ₆ ×w _256b , h ₉ × w _256b ), (-h ₆ ×w _256b , h ₈ ×w _256b ), (-h ₆ ×w _256b ,-15×w _256b ), (-h ₆ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₆ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₆ ×w _256b ,-h ₉ ×w _256b ), (-h ₆ ×w _256b , h ₈ ×w _256b ),

(-h ₅ ×w _256b , 15×w _256b ), (-h ₅ ×w _256b , h ₁₄ ×w _256b ), (-h ₅ ×w _256b , h ₁₃ ×w _256b ), (-h ₅ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₅ ×w _256b , h ₁₁ ×w _256b ), (-h ₅ ×w _256b , h ₁₀ ×w _256b ), (-h ₅ ×w _256b , h ₉ × w _256b ), (-h ₅ ×w _256b , h ₈ ×w _256b ),

(-h ₅ ×w _256b ,-15×w _256b ), (-h ₅ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₁ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₅ × w _256b ,-h ₉ ×w _256b ), (-h ₅ ×w _256b ,-h ₈ ×w _256b ),

(-h ₄ ×w _256b , 15×w _256b ), (-h ₄ ×w _256b , h ₁₄ ×w _256b ), (-h ₄ ×w _256b , h ₁₃ ×w _256b ), (-h ₄ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₄ ×w _256b , h ₁₁ ×w _256b ), (-h ₄ ×w _256b , h ₁₀ ×w _256b ), (-h ₄ ×w _256b , h ₉ × w _256b ), (-h ₄ ×w _256b , h ₈ ×w _256b ), (-h ₄ ×w _256b ,-15×w _256b ), (-h ₄ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₄ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₄ ×w _256b ,-h ₉ ×w _256b ), (-h ₄ ×w _256b ,-h ₈ ×w _256b ),

(-h ₃ ×w _256b , 15×w _256b ), (-h ₃ ×w _256b , h ₁₄ ×w _256b ), (-h ₃ ×w _256b , h ₁₃ ×w _256b ), (-h ₃ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₃ ×w _256b , h ₁₁ ×w _256b ), (-h ₃ ×w _256b , h ₁₀ ×w _256b ), (-h ₃ ×w _256b , h ₉ × w _256b ), (-h ₃ ×w _256b , h ₈ ×w _256b ), (-h ₃ ×w _256b ,-15×w _256b ), (-h ₃ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₃ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₃ ×w _256b ,-h ₉ ×w _256b ), (-h ₃ ×w _256b ,-h ₈ ×w _256b ),

(-h ₂ ×w _256b , 15×w _256b ), (-h ₂ ×w _256b , h ₁₄ ×w _256b ), (-h ₂ ×w _256b , h ₁₃ ×w _256b ), (-h ₂ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₂ ×w _256b , h ₁₁ ×w _256b ), (-h ₂ ×w _256b , h ₁₀ ×w _256b ), (-h ₂ ×w _256b , h ₉ × w _256b ), (-h ₂ ×w _256b , h ₈ ×w _256b ), (-h ₂ ×w _256b ,-15×w _256b ), (-h ₂ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₂ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₂ ×w _256b ,-h ₉ ×w _256b ), (-h ₂ ×w _256b ,-h ₈ ×w _256b ),

(-h ₁ ×w _256b , 15×w _256b ), (-h ₁ ×w _256b , h ₁₄ ×w _256b ), (-h ₁ ×w _256b , h ₁₃ ×w _256b ), (-h ₁ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₁ ×w _256b , h ₁₁ ×w _256b ), (-h ₁ ×w _256b , h ₁₀ ×w _256b ), (-h ₁ ×w _256b , h ₉ × w _256b ), (-h ₁ ×w _256b , h ₈ ×w _256b ), (-h ₁ ×w _256b ,-15×w _256b ), (-h ₁ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₁ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₁ ×w _256b ,-h ₉ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₈ ×w _256b ),

(w _256b is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. It is mapped to point 11601, and if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (15×w _256b , 15×w _256b ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). In addition, an example of the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, b7 (00000000-11111111) and the coordinate of a signal point is as shown in FIG. 256 signal points of 256QAM (“○” in Fig. 116)

(15×w _256b , 15×w _256b ), (15×w _256b , h ₁₄ ×w _256b ), (15×w _256b , h ₁₃ ×w _256b ), (15×w _256b , h ₁₂ ×w _256b ) , (15×w _256b , h ₁₁ ×w _256b ), (15×w _256b , h ₁₀ ×w _256b ), (15×w _256b , h ₉ ×w _256b ), (15×w _256b , h ₈ ×w _256b ), (15×w _256b , -15×w _256b ), (15×w _256b ,-h ₁₄ ×w _256b ), (15×w _256b ,-h ₁₃ ×w _256b ), (15×w _256b ) -h ₁₂ ×w _256b ), (15×w _256b ,-h ₁₁ ×w _256b ), (15×w _256b ,-h ₁₀ ×w _256b ), (15×w _256b ,-h ₉ ×w _256b ), (15×w _256b ,-h ₈ ×w _256b ),

(h ₇ ×w _256b , 15×w _256b ), (h ₇ ×w _256b , h ₁₄ ×w _256b ), (h ₇ ×w _256b , h ₁₃ ×w _256b ), (h ₇ ×w _256b , h ₁₂ ×w _256b ), (h ₇ ×w _256b , h ₁₁ ×w _256b ), (h ₇ ×w _256b , h ₁₀ ×w _256b ), (h ₇ ×w _256b , h ₉ ×w _256b ), (h ₇ ×w _256b , h ₈ ×w _256b ), (h ₇ ×w _256b , -15×w _256b ), (h ₇ ×w _256b ,-h ₁₄ ×w _256b ), (h ₇ ×w _256b ,-h ₁₃ ×w _256b ), (h ₇ ×w _256b ,-h ₁₂ ×w _256b ), (h ₇ ×w _256b ,-h ₁₁ ×w _256b ), (h ₇ ×w _256b ,-h ₁₀ ×w _256b ), (h ₇ ×w _256b ,-h ₉ ×w _256b ), (h ₇ ×w _256b ,-h ₈ ×w _256b ),

(h ₆ ×w _256b , 15×w _256b ), (h ₆ ×w _256b , h ₁₄ ×w _256b ), (h ₆ ×w _256b , h ₁₃ ×w _256b ), (h ₆ ×w _256b , h ₁₂ ×w _256b ), (h ₆ ×w _256b , h ₁₁ ×w _256b ), (h ₆ ×w _256b , h ₁₀ ×w _256b ), (h ₆ ×w _256b , h ₉ ×w _256b ), (h ₆ ×w _256b , h ₈ ×w _256b ), (h ₆ ×w _256b , -15×w _256b ), (h ₆ ×w _256b ,-h ₁₄ ×w _256b ), (h ₆ ×w _256b ,-h ₁₃ ×w _256b ), (h ₆ ×w _256b ,-h ₁₂ ×w _256b ), (h ₆ ×w _256b ,-h ₁₁ ×w _256b ), (h ₆ ×w _256b ,-h ₁₀ ×w _256b ), (h ₆ ×w _256b ,-h ₉ ×w _256b ), (h ₆ ×w _256b ,-h ₈ ×w _256b ),

(h ₅ ×w _256b , 15×w _256b ), (h ₅ ×w _256b , h ₁₄ ×w _256b ), (h ₅ ×w _256b , h ₁₃ ×w _256b ), (h ₅ ×w _256b , h ₁₂ ×w _256b ), (h ₅ ×w _256b , h ₁₁ ×w _256b ), (h ₅ ×w _256b , h ₁₀ ×w _256b ), (h ₅ ×w _256b , h ₉ ×w _256b ), (h ₅ ×w _256b , h ₈ ×w _256b ), (h ₅ ×w _256b , -15×w _256b ), (h ₅ ×w _256b ,-h ₁₄ ×w _256b ), (h ₅ ×w _256b ,-h ₁₃ ×w _256b ), (h ₅ ×w _256b ,-h ₁₂ ×w _256b ), (h ₅ ×w _256b ,-h ₁₁ ×w _256b ), (h ₅ ×w _256b ,-h ₁₀ ×w _256b ), (h ₅ ×w _256b ,-h ₉ ×w _256b ), (h ₅ ×w _256b ,-h ₈ ×w _256b ),

(h ₄ ×w _256b , 15×w _256b ), (h ₄ ×w _256b , h ₁₄ ×w _256b ), (h ₄ ×w _256b , h ₁₃ ×w _256b ), (h ₄ ×w _256b , h ₁₂ ×w _256b ), (h ₄ ×w _256b , h ₁₁ ×w _256b ), (h ₄ ×w _256b , h ₁₀ ×w _256b ), (h ₄ ×w _256b , h ₉ ×w _256b ), (h ₄ ×w _256b , h ₈ ×w _256b ), (h ₄ ×w _256b , -15×w _256b ), (h ₄ ×w _256b ,-h ₁₄ ×w _256b ), (h ₄ ×w _256b ,-h ₁₃ ×w _256b ), (h ₄ ×w _256b ,-h ₁₂ ×w _256b ), (h ₄ ×w _256b ,-h ₁₁ ×w _256b ), (h ₄ ×w _256b ,-h ₁₀ ×w _256b ), (h ₄ ×w _256b ,-h ₉ ×w _256b ), (h ₄ ×w _256b ,-h ₈ ×w _256b ),

(h ₃ ×w _256b , 15×w _256b ), (h ₃ ×w _256b , h ₁₄ ×w _256b ), (h ₃ ×w _256b , h ₁₃ ×w _256b ), (h ₃ ×w _256b , h ₁₂ ×w _256b ), (h ₃ ×w _256b , h ₁₁ ×w _256b ), (h ₃ ×w _256b , h ₁₀ ×w _256b ), (h ₃ ×w _256b , h ₉ ×w _256b ), (h ₃ ×w _256b , h ₈ ×w _256b ), (h ₃ ×w _256b , -15×w _256b ), (h ₃ ×w _256b ,-h ₁₄ ×w _256b ), (h ₃ ×w _256b ,-h ₁₃ ×w _256b ), (h ₃ ×w _256b ,-h ₁₂ ×w _256b ), (h ₃ ×w _256b ,-h ₁₁ ×w _256b ), (h ₃ ×w _256b ,-h ₁₀ ×w _256b ), (h ₃ ×w _256b ,-h ₉ ×w _256b ), (h ₃ ×w _256b ,-h ₈ ×w _256b ),

(h ₂ ×w _256b , 15×w _256b ), (h ₂ ×w _256b , h ₁₄ ×w _256b ), (h ₂ ×w _256b , h ₁₃ ×w _256b ), (h ₂ ×w _256b , h ₁₂ ×w _256b ), (h ₂ ×w _256b , h ₁₁ ×w _256b ), (h ₂ ×w _256b , h ₁₀ ×w _256b ), (h ₂ ×w _256b , h ₉ ×w _256b ), (h ₂ ×w _256b , h ₈ ×w _256b ), (h ₂ ×w _256b , -15×w _256b ), (h ₂ ×w _256b ,-h ₁₄ ×w _256b ), (h ₂ ×w _256b ,-h ₁₃ ×w _256b ), (h ₂ ×w _256b ,-h ₁₂ ×w _256b ), (h ₂ ×w _256b ,-h ₁₁ ×w _256b ), (h ₂ ×w _256b ,-h ₁₀ ×w _256b ), (h ₂ ×w _256b ,-h ₉ ×w _256b ), (h ₂ ×w _256b ,-h ₈ ×w _256b ),

(h ₁ ×w _256b , 15×w _256b ), (h ₁ ×w _256b , h ₁₄ ×w _256b ), (h ₁ ×w _256b , h ₁₃ ×w _256b ), (h ₁ ×w _256b , h ₁₂ ×w _256b ), (h ₁ ×w _256b , h ₁₁ ×w _256b ), (h ₁ ×w _256b , h ₁₀ ×w _256b ), (h ₁ ×w _256b , h ₉ ×w _256b ), (h ₁ ×w _256b , h ₈ ×w _256b ),(h ₁ ×w _256b ,-15×w _256b ), (h ₁ ×w _256b ,-h ₁₄ ×w _256b ), (h ₁ ×w _256b ,-h ₁₃ ×w _256b ), (h ₁ ×w _256b ,-h ₁₂ ×w _256b ), (h ₁ ×w _256b ,-h ₁₁ ×w _256b ), (h ₁ ×w _256b ,-h ₁₀ ×w _256b ), (h ₁ ×w _256b ,-h ₉ ×w _256b ), (h ₁ ×w _256b ,-h ₈ ×w _256b ),

(-15×w _256b , 15×w _256b ), (-15×w _256b , h ₁₄ ×w _256b ), (-15×w _256b , h ₁₃ ×w _256b ), (-15×w _256b , h ₁₂ ×w _256b ), (-15×w _256b , h ₁₁ ×w _256b ), (-15×w _256b , h ₁₀ ×w _256b ), (-15×w _256b , h ₉ ×w _256b ), (-15 ×w _256b , h ₈ ×w _256b ), (-15×w _256b ,-15×w _256b ), (-15×w _256b ,-h ₁₄ ×w _256b ), (-15×w _256b ,-h ₁₃ ×w _256b ), (-15×w _256b ,-h ₁₂ ×w _256b ), (-15×w _256b ,-h ₁₁ ×w _256b ), (-15×w _256b , h ₁₀ ×w _256b ), ( -15×w _256b ,-h ₉ ×w _256b ), (-15×w _256b ,-h ₈ ×w _256b ),

(-h ₇ ×w _256b , 15×w _256b ), (-h ₇ ×w _256b , h ₁₄ ×w _256b ), (-h ₇ ×w _256b , h ₁₃ ×w _256b ), (-h ₇ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₇ ×w _256b , h ₁₁ ×w _256b ), (-h ₇ ×w _256b , h ₁₀ ×w _256b ), (-h ₇ ×w _256b , h ₉ × w _256b ), (-h ₇ ×w _256b , h ₈ ×w _256b ), (-h ₇ ×w _256b ,-15×w _256b ), (-h ₇ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₇ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₇ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₇ ×w _256b ,-h ₉ ×w _256b ), (-h ₇ ×w _256b , h ₈ ×w _256b ),

(-h ₆ ×w _256b , 15×w _256b ), (-h ₆ ×w _256b , h ₁₄ ×w _256b ), (-h ₆ ×w _256b , h ₁₃ ×w _256b ), (-h ₆ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₆ ×w _256b , h ₁₁ ×w _256b ), (-h ₆ ×w _256b , h ₁₀ ×w _256b ), (-h ₆ ×w _256b , h ₉ × w _256b ), (-h ₆ ×w _256b , h ₈ ×w _256b ), (-h ₆ ×w _256b ,-15×w _256b ), (-h ₆ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₆ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₆ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₆ ×w _256b ,-h ₉ ×w _256b ), (-h ₆ ×w _256b , h ₈ ×w _256b ),

(-h ₅ ×w _256b , 15×w _256b ), (-h ₅ ×w _256b , h ₁₄ ×w _256b ), (-h ₅ ×w _256b , h ₁₃ ×w _256b ), (-h ₅ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₅ ×w _256b , h ₁₁ ×w _256b ), (-h ₅ ×w _256b , h ₁₀ ×w _256b ), (-h ₅ ×w _256b , h ₉ × w _256b ), (-h ₅ ×w _256b , h ₈ ×w _256b ), (-h ₅ ×w _256b ,-15×w _256b ), (-h ₅ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₅ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₅ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₅ ×w _256b ,-h ₉ ×w _256b ), (-h ₅ ×w _256b ,-h ₈ ×w _256b ),

(-h ₄ ×w _256b , 15×w _256b ), (-h ₄ ×w _256b , h ₁₄ ×w _256b ), (-h ₄ ×w _256b , h ₁₃ ×w _256b ), (-h ₄ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₄ ×w _256b , h ₁₁ ×w _256b ), (-h ₄ ×w _256b , h ₁₀ ×w _256b ), (-h ₄ ×w _256b , h ₉ × w _256b ), (-h ₄ ×w _256b , h ₈ ×w _256b ), (-h ₄ ×w _256b ,-15×w _256b ), (-h ₄ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₄ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₄ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₄ ×w _256b ,-h ₉ ×w _256b ), (-h ₄ ×w _256b ,-h ₈ ×w _256b ),

(-h ₃ ×w _256b , 15×w _256b ), (-h ₃ ×w _256b , h ₁₄ ×w _256b ), (-h ₃ ×w _256b , h ₁₃ ×w _256b ), (-h ₃ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₃ ×w _256b , h ₁₁ ×w _256b ), (-h ₃ ×w _256b , h ₁₀ ×w _256b ), (-h ₃ ×w _256b , h ₉ × w _256b ), (-h ₃ ×w _256b , h ₈ ×w _256b ), (-h ₃ ×w _256b ,-15×w _256b ), (-h ₃ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₃ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₃ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₃ ×w _256b ,-h ₉ ×w _256b ), (-h ₃ ×w _256b ,-h ₈ ×w _256b ),

(-h ₂ ×w _256b , 15×w _256b ), (-h ₂ ×w _256b , h ₁₄ ×w _256b ), (-h ₂ ×w _256b , h ₁₃ ×w _256b ), (-h ₂ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₂ ×w _256b , h ₁₁ ×w _256b ), (-h ₂ ×w _256b , h ₁₀ ×w _256b ), (-h ₂ ×w _256b , h ₉ × w _256b ), (-h ₂ ×w _256b , h ₈ ×w _256b ), (-h ₂ ×w _256b ,-15×w _256b ), (-h ₂ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₂ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₂ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₂ ×w _256b ,-h ₉ ×w _256b ), (-h ₂ ×w _256b ,-h ₈ ×w _256b ),

(-h ₁ ×w _256b , 15×w _256b ), (-h ₁ ×w _256b , h ₁₄ ×w _256b ), (-h ₁ ×w _256b , h ₁₃ ×w _256b ), (-h ₁ ×w ) _256b , h ₁₂ ×w _256b ), (-h ₁ ×w _256b , h ₁₁ ×w _256b ), (-h ₁ ×w _256b , h ₁₀ ×w _256b ), (-h ₁ ×w _256b , h ₉ × w _256b ), (-h ₁ ×w _256b , h ₈ ×w _256b ), (-h ₁ ×w _256b ,-15×w _256b ), (-h ₁ ×w _256b ,-h ₁₄ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₃ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₂ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₁ ×w _256b ), (- h ₁ ×w _256b ,-h ₁₀ ×w _256b ), (-h ₁ ×w _256b ,-h ₉ ×w _256b ), (-h ₁ ×w _256b ,-h ₁₈ ×w _256b ),

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 116 .

In the 256 signal points in Fig. 116, "signal point 1", "signal point 2"... It is called "signal point 255" and "signal point 256". (Since there are 256 signal points, "signal point 1" to "signal point 256" exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _256b is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2. In addition, the effect is demonstrated next.

Next, the effect of using the QAM described above will be described.

First, the configuration of the transmitting apparatus and the receiving apparatus will be described.

117 is an example of the structure of a transmitter. The error correction encoding unit 11702 receives the information 11701 as input, performs error correction encoding such as an LDPC code or a turbo code, and outputs the data 11703 after error correction encoding.

The interleaving unit 11704 receives the data 11703 after error correction encoding, rearranges the data, and outputs the interleaved data 11705.

The mapping unit 11706 receives the interleaved data 11705 as input, performs mapping based on the modulation method set by the transmitter, and outputs an orthogonal baseband signal (in-phase I component and quadrature Q component) 11707 .

The radio unit 11708 receives the quadrature baseband signal 11707 as an input, performs processing such as quadrature modulation, frequency conversion, and amplification, and outputs a transmission signal 11709. And the transmission signal 11709 is output from the antenna 11710 as a radio wave.

FIG. 118 is an example of the configuration of a receiving device that receives a modulated signal transmitted by the transmitting device of FIG. 117 .

The radio unit 11803 receives the received signal 11802 received from the antenna 11801 as an input, performs frequency conversion, orthogonal demodulation, and the like, and outputs an orthogonal baseband signal 11804.

The demapping unit 11805 receives the orthogonal baseband signal 11804 as an input to estimate and remove the frequency offset and to estimate the channel variation (transmission path variation), and at the same time, the log-likelihood of each bit in the data symbol, for example. A log-likelihood ratio signal 11806 is output by estimating the ratio.

The deinterleaving unit 11807 receives the log-likelihood ratio signal 11806 as an input, performs rearrangement, and outputs the de-interleaved log-likelihood ratio signal 11808.

The decoding unit 11809 receives the deinterleaved log-likelihood ratio signal 11808 as an input, decodes the error correction code, and outputs the received data 11810 .

In explaining the effect, the case of 16QAM will be described as an example. The following two cases (<16QAM#1> and <16QAM#12>) are compared.

<16QAM#1> This is the 16QAM described in Supplementary 2, and the arrangement of signal points in the in-phase I-orthogonal Q plane is as shown in FIG.

<16QAM#2> The arrangement of the signal points in the in-phase I-orthogonal Q plane is as shown in FIG. 114, and as described above, f ₁ >0 (f ₁ is a real number greater than 0), and f ₂ > It is assumed that 0 (f ₂ is a real number greater than 0), f ₁ ≠ 3, f ₁ ≠ 3, and f ₁ ≠ f ₂ .

In 16QAM, 4 bits of b0, b1, b2, and b3 are transmitted as described above. In the case of <16QAM#1>, when the log-likelihood ratio of each bit is calculated in the receiving apparatus, 4 bits are divided into "2-bit high-definition bits and 2-bit low-definition bits". On the other hand, when <16QAM#2> is set, "f ₁ >0 (f ₁ is a real number greater than 0), and f ₂ >0 (f ₂ is a real number greater than 0), f ₁ ≠ 3, Also, it is assumed that f ₁ ≠ 3 and f ₁ ≠ f ₂ ”, “2-bit high-definition bit, 1-bit medium-quality bit, 1-bit low-quality bit” is divided As described above, the distribution of quality of 4 bits differs according to <16QAM#1> and <16QAM#12>. In such a situation, when the error correction code is decoded by the decoding unit 11809 of FIG. 118, it is possible to obtain a high data reception quality in the receiving apparatus by setting it to <16QAM#2> depending on the error correction code used. There is this.

In addition, when the signal points are arranged in the in-phase I-orthogonal Q plane in 64QAM as shown in FIG. 115, as described above, there is a possibility that high data reception quality can be obtained in the receiving apparatus. In this case, as previously described,

"g ₁ >0 (g ₁ is a real number greater than 0), g ₂ >0 (g ₂ is a real number greater than 0), and g ₃ >0 (g ₃ is a real number greater than 0), Also, g ₄ >0 (g ₄ is a real number greater than 0), g ₅ >0 (g ₅ is a real number greater than 0), and g ₆ >0 (g ₆ is a real number greater than 0) ,

{g ₁ ≠ 7, g ₂ ≠ 7, g ₃ ≠ 7, g ₁ ≠ g ₂ , g ₁ ≠ g ₃ , g ₂ ≠ g ₃ }

In addition,

{g ₄ ≠ 7, g ₅ ≠ 7, g ₆ ≠ 7, g ₄ ≠ g 5, g ₄ ≠ g ₆ , and g ₅ ≠ g ₆ }

In addition,

{g ₁ ≠g ₄ , or g ₂ ≠g ₅ , or g ₃ ≠g ₆ } holds.”

is an important condition, which is different from the signal point arrangement described in Supplementary 2.

Similarly, in 256QAM, when the signal points are arranged in the in-phase I-orthogonal Q plane as shown in FIG. 116, as described above, there is a possibility that high data reception quality can be obtained in the receiving apparatus. In this case, as previously described,

"h ₁ >0 (h ₁ is a real number greater than 0), h ₂ >0 (h ₂ is a real number greater than 0), and h ₃ >0 (h ₃ is a real number greater than 0), Also, h ₄ >0 (h ₄ is a real number greater than 0), h ₅ >0 (h ₅ is a real number greater than 0), and h ₆ >0 (h ₆ is a real number greater than 0) , h ₇ >0 (h ₇ is a real number greater than 0), h ₈ >0 (h ₈ is a real number greater than 0), and h ₉ >0 (h ₉ is a real number greater than 0) Also, h ₁₀ >0 (h ₁₀ is a real number greater than 0), h ₁₁ >0 (h ₁₁ is a real number greater than 0), and h ₁₂ >0 (h ₁₂ is a real number greater than 0) ), and h ₁₃ >0 (h ₁₃ is a real number greater than 0), and h ₁₄ >0 (h ₁₄ is a real number greater than 0),

{h ₁ ≠ 15, h ₂ ≠ 15, h ₃ ≠ 15, h ₄ ≠ 15, h ₅ ≠ 15, h ₆ ≠ 15, and h ₇ ≠15, h ₁ ≠h ₂ , h ₁ ≠ h ₃ , h ₁ ≠ h ₄ , h ₁ ≠ h ₅ , h ₁ ≠ h ₆ , and , h ₁ ≠h ₇ , h ₂ ≠h ₃ , h ₂ ≠h ₄ , h ₂ ≠h ₅ , h ₂ ≠h ₆ , and h ₂ ≠h ₇ , h ₃ ≠ h ₄ , h ₃ ≠ h ₅ , h ₃ ≠ h ₆ , h ₃ ≠ h ₇ , h ₄ ≠ h ₅ , and h ₄ ≠ h ₆ , and h ₄ ≠h ₇ , further h ₅ ≠ h ₆ , and h ₅ ≠h ₇ , and h ₆ ≠h ₇ },

In addition,

{h ₈ ≠ 15, h ₉ ≠ 15, h ₁₀ ≠ 15, h ₁₁ ≠ 15, h ₁₂ ≠ 15, h ₁₃ ≠ 15, and h ₁₄ ≠15, h ₈ ≠h ₉ , h ₈ ≠h ₁₀ , h ₈ ≠h ₁₁ , h ₈ ≠h ₁₂ , h ₈ ≠h ₁₃ , and , h ₈ ≠h ₁₄ , h ₉ ≠h ₁₀ , h ₉ ≠ h ₁₁ , h ₉ ≠ h ₁₂ , h ₉ ≠ h ₁₃ , and h ₉ ≠ h ₁₄ , h ₁₀ ≠ h ₁₁ , h ₁₀ ≠ h ₁₂ , h ₁₀ ≠ h ₁₃ , h ₁₀ ≠ h ₁₄ , further h ₁₁ ≠ h ₁₂ , and h ₁₁ ≠ h ₁₃ , and h ₁₁ ≠h ₁₄ , further h ₁₂ ≠h ₁₃ , and h ₁₂ ≠h ₁₄ , and h ₁₃ ≠h ₁₄ },

In addition,

{h ₁ ≠h ₈ , or h ₂ ≠h ₉ , or h ₃ ≠h ₁₀ , or h ₄ ≠h ₁₁ , or h ₅ ≠h ₁₂ , or h ₆ ≠h ₁₃ , or h ₇ ≠h ₁₄ } accomplished.”

is an important condition, which is different from the signal point arrangement described in Supplementary 2.

Note that, although detailed configuration is omitted in Figs. 117 and 118, it can be implemented similarly in the case of transmitting and receiving modulated signals using the OFDM method and spread spectrum communication method described in other embodiments.

In addition, the MIMO transmission method described in the first to twelfth embodiments and space-time codes such as space-time block codes (however, the symbols may be arranged on the frequency axis), precoding In the MIMO transmission method that does not execute or precoding, there is a possibility that data reception quality can be improved even if 16QAM, 64QAM, and 256QAM described above are used.

(Supplementary 4)

In Embodiments 1 to 11, the bit length adjustment method has been described. Further, in the twelfth embodiment, the case where the bit length adjustment method of the first to eleventh embodiments is applied to the DVB standard has been described. Among these embodiments, a case in which 16QAM, 64QAM, and 256QAM are applied as modulation schemes is described. In addition, a specific mapping method for 16QAM, 64QAM, and 256QAM is described in (Configuration Example R1).

Hereinafter, configuration methods such as 16QAM, 64QAM, and 256QAM mapping methods different from (Configuration Example R1) and (Supplementary 2) (Supplementary 3) will be described. In addition, 16QAM, 64QAM, and 256QAM described below may be applied to the first to twelfth embodiments, and in this case, the effects described in the first to twelfth embodiments can be obtained.

A mapping method of 16QAM will be described. 119 shows an example of arrangement of signal points of 16QAM in the in-phase I-orthogonal Q plane. In Fig. 119, 16 circles denote 16QAM signal points, the abscissa denotes I and the ordinate denotes Q.

119, k ₁ >0 (k ₁ is a real number greater than 0), k ₂ >0 (k ₂ is a real number greater than 0), k ₁ ≠ 1, and k ₂ ≠ 1 , and further, k ₁ ≠ k ₂ .

The coordinates of the 16 signal points of 16QAM (“○” in FIG. 119 is the signal point) in the in-phase I-orthogonal Q plane are,

(k ₁ ×w _16c , k ₂ ×w _16c ), (k ₁ ×w _16c , 1×w _16c ), (k ₁ ×w _16c ,-1×w _16c ), (k ₁ ×w _16c ,-k ₂ ×w _16c ), (1×w _16c , k2×w _16c ), (1×w _16c , 1×w _16c ), (1×w _16c ,-1×w _16c ), (1×w _16c ,- k ₂ ×w _16c ), (-1×w _16c , k ₂ ×w _16c ), (-1×w _16c , 1×w _16c ), (-1×w _16c ,-1×w _16c ), (- 1×w _16c ,-k ₂ ×w _16c ), (-k ₁ ×w _16c , k ₂ ×w _16c ), (-k ₁ ×w _16c , 1×w _16c ), (-k ₁ ×w _16c , -1×w _16c ), (-k ₁ ×w _16c ,-k ₂ ×w _16c ),

(w _16c is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, and b3. For example, if the transmitted bit is (b0, b1, b2, b3) = (0, 0, 0, 0), it is mapped to the signal point 11901 in FIG. 119, and the in-phase component of the baseband signal after mapping is I , if the orthogonal component is Q, (I, Q)=(k ₁ ×w _16c , k ₂ ×w _16c ).

That is, the in-phase component I and the quadrature component Q of the mapped baseband signal (in the case of 16QAM) are determined based on the transmitted bits (b0, b1, b2, b3). In addition, an example of the relationship between the set (0000-1111) of b0, b1, b2, b3, and the coordinate of a signal point is as shown in FIG. 16 signal points of 16QAM (“○” in Fig. 119)

(k ₁ ×w _16c , k ₂ ×w _16c ), (k ₁ ×w _16c , 1×w _16c ), (k ₁ ×w _16c ,-1×w _16c ), (k ₁ ×w _16c ,-k ₂ ×w _16c ), (1×w _16c , k2×w _16c ), (1×w _16c , 1×w _16c ), (1×w _16c ,-1×w _16c ), (1×w _16c ,- k ₂ ×w _16c ), (-1×w _16c , k ₂ ×w _16c ), (-1×w _16c , 1×w _16c ), (-1×w _16c ,-1×w _16c ), (- 1×w _16c ,-k ₂ ×w _16c ), (-k ₁ ×w _16c , k ₂ ×w _16c ), (-k ₁ ×w _16c , 1×w _16c ), (-k ₁ ×w _16c , -1×w _16c ), (-k ₁ ×w _16c ,-k ₂ ×w _16c ),

The values of sets 0000 to 1111 of b0, b1, b2, and b3 are shown just below. The in-phase component I and the quadrature component Q of the baseband signal after mapping each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 0000 to 1111 of b0, b1, b2, and b3 are do. Note that the relationship between the sets of b0, b1, b2, and b3 (0000 to 1111) and the coordinates of the signal points in 16QAM is not limited to FIG. 119 .

In the 16 signal points in Fig. 119, "signal point 1", "signal point 2"... It is called "signal point 15" and "signal point 16". (Since there are 16 signal points, &quot;signal point 1&quot; to &quot;signal point 16&quot; exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _16c is given as follows.

Then, the average power of the baseband signal after mapping becomes z ² . In addition, the effect of 16QAM described above will be described next.

A mapping method of 64QAM will be described. 120 shows an example of the arrangement of the signal points of 64QAM in the in-phase I-orthogonal Q plane. In Fig. 120, 64 ? denotes a 64QAM signal point, and the horizontal axis denotes I, and the vertical axis denotes Q.

In Figure 120,

"m ₁ >0 (m ₁ is a real number greater than 0), m ₂ >0 (m ₂ is a real number greater than 0), and m ₃ >0 (m ₃ is a real number greater than 0), Also, m ₄ >0 (m ₄ is a real number greater than 0), m ₅ >0 (m ₅ is a real number greater than 0), and m ₆ >0 (m ₆ is a real number greater than 0) , also, m ₇ >0 (m ₇ is a real number greater than 0), and m ₈ >0 (m ₈ is a real number greater than 0),

{m ₁ ≠m ₂ , m ₁ ≠m ₃ , m ₁ ≠m ₄ , m ₂ ≠m ₃ , m ₂ ≠m ₄ , and m ₃ ≠m ₄ }, and

In addition,

{m ₅ ≠m ₆ , m ₅ ≠m ₇ , m ₅ ≠m ₈ , m ₆ ≠m ₇ , m ₆ ≠m ₈ , and m ₇ ≠m ₈ },

In addition,

{m ₁ ≠m ₅ , or m ₂ ≠m ₆ , or m ₃ ≠m ₇ , or m ₄ ≠m ₈ } holds.”

or,

"m ₁ >0 (m ₁ is a real number greater than 0), m ₂ >0 (m ₂ is a real number greater than 0), and m ₃ >0 (m ₃ is a real number greater than 0), Also, m ₄ >0 (m ₄ is a real number greater than 0), m ₅ >0 (m ₅ is a real number greater than 0), and m ₆ >0 (m ₆ is a real number greater than 0) , also, m ₇ >0 (m ₇ is a real number greater than 0), and m ₈ >0 (m ₈ is a real number greater than 0),

{m ₁ ≠m ₂ , m ₁ ≠m ₃ , m ₁ ≠m ₄ , m ₂ ≠m ₃ , m ₂ ≠m ₄ , and m ₃ ≠m ₄ }, and

In addition,

{m ₅ ≠m ₆ , m ₅ ≠m ₇ , m ₅ ≠m ₈ , m ₆ ≠m ₇ , m ₆ ≠m ₈ , and m ₇ ≠m ₈ },

In addition,

{So that m ₁ ≠m ₅ , or m ₂ ≠m ₆ , or m ₃ ≠m ₇ , or m ₄ ≠m ₈ holds}

In addition,

{m ₁ =m ₅ , or m ₂ =m ₆ , or m ₃ =m ₇ , or m ₄ =m ₈ holds}

is established.”

do it with

Each coordinate of 64 signal points of 64QAM (“○” in FIG. 120 is a signal point) in the in-phase I-orthogonal Q plane is,

(m ₄ ×w _64c , m8×w _64c ), (m ₄ ×w _64c , m ₇ ×w _64c ), (m ₄ ×w _64c , m ₆ ×w _64c ), (m ₄ ×w _64c , m ₅ ×w _64c ), (m ₄ ×w _64c ,-m ₅ ×w _64c ), (m ₄ ×w _64c ,-m ₆ ×w _64c ), (m ₄ ×w _64c ,-m ₇ ×w _64c ), (m ₄ ×w _64c ,-m ₈ ×w _64c )

(m ₃ ×w _64c , m ₈ ×w _64c ), (m ₃ ×w _64c , m ₇ ×w _64c ), (m ₃ ×w _64c , m ₆ ×w _64c ), (m ₃ ×w _64c , m ₅ ×w _64c ), (m ₃ ×w _64c ,-m ₅ ×w _64c ), (m ₃ ×w _64c ,-m ₆ ×w _64c ), (m ₃ ×w _64c ,-m ₇ ×w _64c ) , (m ₃ ×w _64c ,-m ₈ ×w _64c )

(m ₂ ×w _64c , m ₈ ×w _64c ), (m ₂ ×w _64c , m ₇ ×w _64c ), (m ₂ ×w _64c , m ₆ ×w _64c ), (m ₂ ×w _64c , m ₅ ×w _64c ), (m ₂ ×w _64c ,-m ₅ ×w _64c ), (m ₂ ×w _64c ,-m ₆ ×w _64c ), (m ₂ ×w _64c ,-m ₇ ×w _64c ) , (m ₂ ×w _64c ,-m ₈ ×w _64c )

(m ₁ ×w _64c , m ₈ ×w _64c ), (m ₁ ×w _64c , m ₇ ×w _64c ), (m ₁ ×w _64c , m ₆ ×w _64c ), (m ₁ ×w _64c , m ₅ ×w _64c ), (m ₁ ×w _64c ,-m ₅ ×w _64c ), (m ₁ ×w _64c ,-m ₆ ×w _64c ), (m ₁ ×w _64c ,-m ₇ ×w _64c ) , (m ₁ ×w _64c ,-m ₈ ×w _64c )

(-m ₁ ×w _64c , m ₈ ×w _64c ), (-m ₁ ×w _64c , m ₇ ×w _64c ), (-m ₁ ×w _64c , m ₆ ×w _64c ), (-m ₁ × w _64c , m ₅ ×w _64c ), (-m ₁ ×w _64c ,-m ₅ ×w _64c ), (-m ₁ ×w _64c ,-m ₆ ×w _64c ), (-m ₁ ×w _64c , -m ₇ ×w _64c ), (-m ₁ ×w _64c ,-m ₈ ×w _64c )

(-m ₂ ×w _64c , m ₈ ×w _64c ), (-m ₂ ×w _64c , m ₇ ×w _64c ), (-m ₂ ×w _64c , m ₆ ×w _64c ), (-m ₂ × w _64c , m ₅ ×w _64c ), (-m ₂ ×w _64c ,-m ₅ ×w _64c ), (-m ₂ ×w _64c ,-m ₆ ×w _64c ), (-m ₂ ×w _64c , -m ₇ ×w _64c ), (-m ₂ ×w _64c ,-m ₈ ×w _64c )

(-m ₃ ×w _64c , m ₈ ×w _64c ), (-m ₃ ×w _64c , m ₇ ×w _64c ), (-m ₃ ×w _64c , m ₆ ×w _64c ), (-m ₃ × w _64c , m ₅ ×w _64c ), (-m ₃ ×w _64c ,-m ₅ ×w _64c ), (-m ₃ ×w _64c ,-m ₆ ×w _64c ), (-m ₃ ×w _64c , -m ₇ ×w _64c ), (-m ₃ ×w _64c ,-m ₈ ×w _64c )

(-m ₄ ×w _64c , m ₈ ×w _64c ), (-m ₄ ×w _64c , m ₇ ×w _64c ), (-m ₄ ×w _64c , m ₆ ×w _64c ), (-m ₄ × w _64c , m ₅ ×w _64c ), (-m ₄ ×w _64c ,-m ₅ ×w _64c ), (-m ₄ ×w _64c ,-m ₆ ×w _64c ), (-m ₄ ×w _64c , -m ₇ ×w _64c ), (-m ₄ ×w _64c ,-m ₈ ×w _64c )

(w _64c is a real number greater than 0).

Here, the bits to be transmitted (input bits) are referred to as b0, b1, b2, b3, b4, and b5. For example, if the transmitted bit is (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), it is mapped to the signal point 12001 in FIG. When the in-phase component of the baseband signal is I and the quadrature component is Q, (I, Q) = (m ₄ ×w _64c , m ₈ ×w _64c ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5). An example of the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal point is as shown in FIG. 120 . 64 signal points of 64QAM (“○” in Fig. 120)

(m ₄ ×w _64c , m8×w _64c ), (m ₄ ×w _64c , m ₇ ×w _64c ), (m ₄ ×w _64c , m ₆ ×w _64c ), (m ₄ ×w _64c , m ₅ ×w _64c ), (m ₄ ×w _64c ,-m ₅ ×w _64c ), (m ₄ ×w _64c ,-m ₆ ×w _64c ), (m ₄ ×w _64c ,-m ₇ ×w _64c ), (m ₄ ×w _64c ,-m ₈ ×w _64c )

(m ₃ ×w _64c , m ₈ ×w _64c ), (m ₃ ×w _64c , m ₇ ×w _64c ), (m ₃ ×w _64c , m ₆ ×w _64c ), (m ₃ ×w _64c , m ₅ ×w _64c ), (m ₃ ×w _64c ,-m ₅ ×w _64c ), (m ₃ ×w _64c ,-m ₆ ×w _64c ), (m ₃ ×w _64c ,-m ₇ ×w _64c ) , (m ₃ ×w _64c ,-m ₈ ×w _64c )

(m ₂ ×w _64c , m ₈ ×w _64c ), (m ₂ ×w _64c , m ₇ ×w _64c ), (m ₂ ×w _64c , m ₆ ×w _64c ), (m ₂ ×w _64c , m ₅ ×w _64c ), (m ₂ ×w _64c ,-m ₅ ×w _64c ), (m ₂ ×w _64c ,-m ₆ ×w _64c ), (m ₂ ×w _64c ,-m ₇ ×w _64c ) , (m ₂ ×w _64c ,-m ₈ ×w _64c )

(m ₁ ×w _64c , m ₈ ×w _64c ), (m ₁ ×w _64c , m ₇ ×w _64c ), (m ₁ ×w _64c , m ₆ ×w _64c ), (m ₁ ×w _64c , m ₅ ×w _64c ), (m ₁ ×w _64c ,-m ₅ ×w _64c ), (m ₁ ×w _64c ,-m ₆ ×w _64c ), (m ₁ ×w _64c ,-m ₇ ×w _64c ) , (m ₁ ×w _64c ,-m ₈ ×w _64c )

(-m ₁ ×w _64c , m ₈ ×w _64c ), (-m ₁ ×w _64c , m ₇ ×w _64c ), (-m ₁ ×w _64c , m ₆ ×w _64c ), (-m ₁ × w _64c , m ₅ ×w _64c ), (-m ₁ ×w _64c ,-m ₅ ×w _64c ), (-m ₁ ×w _64c ,-m ₆ ×w _64c ), (-m ₁ ×w _64c , -m ₇ ×w _64c ), (-m ₁ ×w _64c ,-m ₈ ×w _64c )

(-m ₂ ×w _64c , m ₈ ×w _64c ), (-m ₂ ×w _64c , m ₇ ×w _64c ), (-m ₂ ×w _64c , m ₆ ×w _64c ), (-m ₂ × w _64c , m ₅ ×w _64c ), (-m ₂ ×w _64c ,-m ₅ ×w _64c ), (-m ₂ ×w _64c ,-m ₆ ×w _64c ), (-m ₂ ×w _64c , -m ₇ ×w _64c ), (-m ₂ ×w _64c ,-m ₈ ×w _64c )

(-m ₃ ×w _64c , m ₈ ×w _64c ), (-m ₃ ×w _64c , m ₇ ×w _64c ), (-m ₃ ×w _64c , m ₆ ×w _64c ), (-m ₃ × w _64c , m ₅ ×w _64c ), (-m ₃ ×w _64c ,-m ₅ ×w _64c ), (-m ₃ ×w _64c ,-m ₆ ×w _64c ), (-m ₃ ×w _64c , -m ₇ ×w _64c ), (-m ₃ ×w _64c ,-m ₈ ×w _64c )

(-m ₄ ×w _64c , m ₈ ×w _64c ), (-m ₄ ×w _64c , m ₇ ×w _64c ), (-m ₄ ×w _64c , m ₆ ×w _64c ), (-m ₄ × w _64c , m ₅ ×w _64c ), (-m ₄ ×w _64c ,-m ₅ ×w _64c ), (-m ₄ ×w _64c ,-m ₆ ×w _64c ), (-m ₄ ×w _64c , -m ₇ ×w _64c ), (-m ₄ ×w _64c ,-m ₈ ×w _64c )

The values of sets 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. Each coordinate in the in-phase I- orthogonal Q plane of the signal point (“○”) immediately above the sets 000000 to 111111 of b0, b1, b2, b3, b4, b5 is the in-phase component I and It becomes the orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in 64QAM is not limited to FIG. 120 .

In the 64 signal points in Fig. 120, "signal point 1", "signal point 2"... It is called "signal point 63" and "signal point 64". (Since there are 64 signal points, &quot;signal point 1&quot; to &quot;signal point 64&quot; exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _64c is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2. In addition, the effect is demonstrated next.

A mapping method of 256QAM will be described. 121 shows an example of the arrangement of signal points of 256QAM in the in-phase I-orthogonal Q plane. In Fig. 121, 256 ? denote 256QAM signal points, and the horizontal axis denotes I, and the vertical axis denotes Q.

121,

"n ₁ >0 (n ₁ is a real number greater than 0), n ₂ >0 (n ₂ is a real number greater than 0), and n ₃ >0 (n ₃ is a real number greater than 0), Also, n ₄ >0 (n ₄ is a real number greater than 0), n ₅ >0 (n ₅ is a real number greater than 0), and n ₆ >0 (n ₆ is a real number greater than 0) , also, n ₇ >0 (n ₇ is a real number greater than 0), and also n ₈ >0 (n ₈ is a real number greater than 0),

Also, n ₉ >0 (n ₉ is a real number greater than 0), n ₁₀ >0 (n ₁₀ is a real number greater than 0), and n ₁₁ >0 (n ₁₁ is a real number greater than 0) , also n ₁₂ >0 (n ₁₂ is a real number greater than 0), n ₁₃ >0 (n ₁₃ is a real number greater than 0), and n ₁₄ >0 (n ₁₄ is a real number greater than 0) , and n ₁₅ >0 (n ₁₅ is a real number greater than 0),

Also, n ₁₆ >0 (n ₁₆ is a real number greater than 0),

{n ₁ ≠n ₂ , n ₁ ≠n ₃ , n ₁ ≠n ₄ , n ₁ ≠n ₅ , n ₁ ≠n ₆ , and n ₁ ≠n ₇ and also, n ₁ ≠n ₈ ,

Further, n ₂ ≠ n ₃ , n ₂ ≠ n ₄ , n ₂ ≠ n ₅ , n ₂ ≠ n ₆ , and n ₂ ≠ n 7 , and further, n ₂ ≠ n ₇ , n ₈ ,

Further, n ₃ ≠ n ₄ , and further, n ₃ ≠ n ₅ , and further, n ₃ ≠ n ₆ , and further, n ₃ ≠ n ₇ , and further, n ₃ ≠ n ₈ ,

Further, n ₄ ≠ n ₅ , and further, n ₄ ≠ n ₆ , and further, n ₄ ≠ n ₇ , and further, n ₄ ≠ n ₈ ,

Further, n ₅ ≠ n ₆ , and n ₅ ≠ n ₇ , and further, n ₅ ≠ n ₈ ,

Also, n ₆ ≠ n ₇ , and n ₆ ≠ n ₈ ,

Also, n ₇ ≠ n ₈ }

In addition,

{n ₉ ≠n ₁₀ , n ₉ ≠n ₁₁ , n ₉ ≠n ₁₂ , n ₉ ≠n ₁₃ , n ₉ ≠n ₁₄ , and n ₉ ≠ n ₁₅ , and also, n ₉ ≠ n ₁₆ ,

Further, n ₁₀ ≠ n ₁₁ , further n ₁₀ ≠ n ₁₂ , further n ₁₀ ≠ n ₁₃ , further n ₁₀ ≠ n ₁₄ , further n ₁₀ ≠ n ₁₅ , and further, n ₁₀ ≠ n 15 , n ₁₆ ,

Further, n ₁₁ ≠ n ₁₂ , and n ₁₁ ≠ n ₁₃ , and further, n ₁₁ ≠ n ₁₄ , and further, n ₁₁ ≠ n ₁₅ , and further, n ₁₁ ≠ n ₁₆ ,

Further, n ₁₂ ≠ n ₁₃ , and further, n ₁₂ ≠ n ₁₄ , and further, n ₁₂ ≠ n ₁₅ , and further, n ₁₂ ≠ n ₁₆ ,

Further, n ₁₃ ≠ n ₁₄ , and further, n ₁₃ ≠ n ₁₅ , and further, n ₁₃ ≠ n ₁₆ ,

Also, n ₁₄ ≠n ₁₅ , and n ₁₄ ≠n ₁₆ ,

Also, n ₁₅ ≠ n ₁₆ }

In addition,

{n ₁ ≠n ₉ , or n ₂ ≠n ₁₀ , or n ₃ ≠n ₁₁ , or n ₄ ≠n ₁₂ , or n ₅ ≠n ₁₃ , or n ₆ ≠n ₁₄ , or n ₇ ≠n ₁₅ , or n ₈ ≠ n ₁₆ holds}

is established.”

or,

"n ₁ >0 (n ₁ is a real number greater than 0), n ₂ >0 (n ₂ is a real number greater than 0), and n ₃ >0 (n ₃ is a real number greater than 0), Also, n ₄ >0 (n ₄ is a real number greater than 0), n ₅ >0 (n ₅ is a real number greater than 0), and n ₆ >0 (n ₆ is a real number greater than 0) , also, n ₇ >0 (n ₇ is a real number greater than 0), and also n ₈ >0 (n ₈ is a real number greater than 0),

Also, n ₉ >0 (n ₉ is a real number greater than 0), n ₁₀ >0 (n ₁₀ is a real number greater than 0), and n ₁₁ >0 (n ₁₁ is a real number greater than 0) , also n ₁₂ >0 (n ₁₂ is a real number greater than 0), n ₁₃ >0 (n ₁₃ is a real number greater than 0), and n ₁₄ >0 (n ₁₄ is a real number greater than 0) , and n ₁₅ >0 (n ₁₅ is a real number greater than 0), and n ₁₆ >0 (n ₁₆ is a real number greater than 0),

{n ₁ ≠n ₂ , n ₁ ≠n ₃ , n ₁ ≠n ₄ , n ₁ ≠n ₅ , n ₁ ≠n ₆ , and n ₁ ≠n ₇ and also, n ₁ ≠n ₈ ,

Further, n ₂ ≠ n ₃ , n ₂ ≠ n ₄ , n ₂ ≠ n ₅ , n ₂ ≠ n ₆ , and n ₂ ≠ n 7 , and further, n ₂ ≠ n ₇ , n ₈ ,

Further, n ₃ ≠ n ₄ , and further, n ₃ ≠ n ₅ , and further, n ₃ ≠ n ₆ , and further, n ₃ ≠ n ₇ , and further, n ₃ ≠ n ₈ ,

Further, n ₄ ≠ n ₅ , and further, n ₄ ≠ n ₆ , and further, n ₄ ≠ n ₇ , and further, n ₄ ≠ n ₈ ,

Further, n ₅ ≠ n ₆ , and n ₅ ≠ n ₇ , and further, n ₅ ≠ n ₈ ,

Also, n ₆ ≠ n ₇ , and n ₆ ≠ n ₈ ,

Also, n ₇ ≠ n ₈ }

In addition,

{n ₉ ≠n ₁₀ , n ₉ ≠n ₁₁ , n ₉ ≠n ₁₂ , n ₉ ≠n ₁₃ , n ₉ ≠n ₁₄ , and n ₉ ≠ n ₁₅ , and also, n ₉ ≠ n ₁₆ ,

Further, n ₁₀ ≠ n ₁₁ , further n ₁₀ ≠ n ₁₂ , further n ₁₀ ≠ n ₁₃ , further n ₁₀ ≠ n ₁₄ , further n ₁₀ ≠ n ₁₅ , and further, n ₁₀ ≠ n 15 , n ₁₆ ,

Further, n ₁₁ ≠ n ₁₂ , and n ₁₁ ≠ n ₁₃ , and further, n ₁₁ ≠ n ₁₄ , and further, n ₁₁ ≠ n ₁₅ , and further, n ₁₁ ≠ n ₁₆ ,

Further, n ₁₂ ≠ n ₁₃ , and further, n ₁₂ ≠ n ₁₄ , and further, n ₁₂ ≠ n ₁₅ , and further, n ₁₂ ≠ n ₁₆ ,

Further, n ₁₃ ≠ n ₁₄ , and further, n ₁₃ ≠ n ₁₅ , and further, n ₁₃ ≠ n ₁₆ ,

Also, n ₁₄ ≠n ₁₅ , and n ₁₄ ≠n ₁₆ ,

Also, n ₁₅ ≠ n ₁₆ }

In addition,

{n ₁ ≠n ₉ , or n ₂ ≠n ₁₀ , or n ₃ ≠n ₁₁ , or n ₄ ≠n ₁₂ , or n ₅ ≠n ₁₃ , or n ₆ ≠n ₁₄ , or n ₇ ≠n ₁₅ , or n ₈ ≠ n ₁₆ holds}

Meanwhile,

{n ₁ =n ₉ , or n ₂ =n ₁₀ , or n ₃ =n ₁₁ , or n ₄ =n ₁₂ , or n ₅ =n ₁₃ , or n ₆ =n ₁₄ , or n ₇ =n ₁₅ , or n ₈ = n ₁₆ holds}

is established.”

do it with

The respective coordinates of the 256 signal points of 256QAM (“○” in FIG. 121 is the signal point) in the in-phase I-orthogonal Q plane are,

(n ₈ ×w _256c , n ₁₆ ×w _256c ), (n ₈ ×w _256c , n ₁₅ ×w _256c ), (n ₈ ×w _256c , n ₁₄ ×w _256c ), (n ₈ ×w _256c , n ₁₃ ×w _256c ), (n ₈ ×w _256c , n ₁₂ ×w _256c ), (n ₈ ×w _256c , n ₁₁ ×w _256c ), (n ₈ ×w _256c , n ₁₀ ×w _256c ), (n ₈ ×w _256c , n ₉ ×w _256c ), (n ₈ ×w _256c ,-n ₁₆ ×w _256c ), (n ₈ ×w _256c ,-n ₁₅ ×w _256c ), (n ₈ ×w _256c ,- n ₁₄ ×w _256c ), (n ₈ ×w _256c ,-n ₁₃ ×w _256c ), (n ₈ ×w _256c ,-n ₁₂ ×w _256c ), (n ₈ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₈ ×w _256c ,-n ₁₀ ×w _256c ), (n ₈ ×w _256c ,-n ₉ ×w _256c ),

(n ₇ ×w _256c , n ₁₆ ×w _256c ), (n ₇ ×w _256c , n ₁₅ ×w _256c ), (n ₇ ×w _256c , n ₁₄ ×w _256c ), (n ₇ ×w _256c , n ₁₃ ×w _256c ), (n ₇ ×w _256c , n ₁₂ ×w _256c ), (n ₇ ×w _256c , n ₁₁ ×w _256c ), (n ₇ ×w _256c , n ₁₀ ×w _256c ), (n ₇ ×w _256c , n ₉ ×w _256c ), (n ₇ ×w _256c ,-n ₁₆ ×w _256c ), (n ₇ ×w _256c ,-n ₁₅ ×w _256c ), (n ₇ ×w _256c ,- n ₁₄ ×w _256c ), (n ₇ ×w _256c ,-n ₁₃ ×w _256c ), (n ₇ ×w _256c ,-n ₁₂ ×w _256c ), (n ₇ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₇ ×w _256c ,-n ₁₀ ×w _256c ), (n ₇ ×w _256c ,-n ₉ ×w _256c ),

(n ₆ ×w _256c , n ₁₆ ×w _256c ), (n ₆ ×w _256c , n ₁₅ ×w _256c ), (n ₆ ×w _256c , n ₁₄ ×w _256c ), (n ₆ ×w _256c , n ₁₃ ×w _256c ), (n ₆ ×w _256c , n ₁₂ ×w _256c ), (n ₆ ×w _256c , n ₁₁ ×w _256c ), (n ₆ ×w _256c , n ₁₀ ×w _256c ), (n ₆ ×w _256c , n ₆ ×w _256c ), (n ₆ ×w _256c ,-n ₁₆ ×w _256c ), (n ₆ ×w _256c ,-n ₁₅ ×w _256c ), (n ₆ ×w _256c ,- n ₁₄ ×w _256c ), (n ₆ ×w _256c ,-n ₁₃ ×w _256c ), (n ₆ ×w _256c ,-n ₁₂ ×w _256c ), (n ₆ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₆ ×w _256c ,-n ₁₀ ×w _256c ), (n ₆ ×w _256c ,-n ₉ ×w _256c ),

(n ₅ ×w _256c , n ₁₆ ×w _256c ), (n ₅ ×w _256c , n ₁₅ ×w _256c ), (n ₅ ×w _256c , n ₁₄ ×w _256c ), (n ₅ ×w _256c , n ₁₃ ×w _256c ), (n ₅ ×w _256c , n ₁₂ ×w _256c ), (n ₅ ×w _256c , n ₁₁ ×w _256c ), (n ₅ ×w _256c , n ₁₀ ×w _256c ), (n ₅ ×w _256c , n ₉ ×w _256c ), (n ₅ ×w _256c ,-n ₁₆ ×w _256c ), (n ₅ ×w _256c ,-n ₁₅ ×w _256c ), (n ₅ ×w _256c ,- n ₁₄ ×w _256c ), (n ₅ ×w _256c ,-n ₁₃ ×w _256c ), (n ₅ ×w _256c ,-n ₁₂ ×w _256c ), (n ₅ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₅ ×w _256c ,-n ₁₀ ×w _256c ), (n ₅ ×w _256c ,-n ₉ ×w _256c ),

(n ₄ ×w _256c , n ₁₆ ×w _256c ), (n ₄ ×w _256c , n ₁₅ ×w _256c ), (n ₄ ×w _256c , n ₁₄ ×w _256c ), (n ₄ ×w _256c , n ₁₃ ×w _256c ), (n ₄ ×w _256c , n ₁₂ ×w _256c ), (n ₄ ×w _256c , n ₁₁ ×w _256c ), (n ₄ ×w _256c , n ₁₀ ×w _256c ), (n ₄ ×w _256c , n ₉ ×w _256c ), (n ₄ ×w _256c ,-n ₁₆ ×w _256c ), (n ₄ ×w _256c ,-n ₁₅ ×w _256c ), (n ₄ ×w _256c ,- n ₁₄ ×w _256c ), (n ₄ ×w _256c ,-n ₁₃ ×w _256c ), (n ₄ ×w _256c ,-n ₁₂ ×w _256c ), (n ₄ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₄ ×w _256c ,-n ₁₀ ×w _256c ), (n ₄ ×w _256c ,-n ₉ ×w _256c ),

(n ₃ ×w _256c , n ₁₆ ×w _256c ), (n ₃ ×w _256c , n ₁₅ ×w _256c ), (n ₃ ×w _256c , n ₁₄ ×w _256c ), (n ₃ ×w _256c , n ₁₃ ×w _256c ), (n ₃ ×w _256c , n ₁₂ ×w _256c ), (n ₃ ×w _256c , n ₁₁ ×w _256c ), (n ₃ ×w _256c , n ₁₀ ×w _256c ), (n ₃ ×w _256c , n ₉ ×w _256c ), (n ₃ ×w _256c ,-n ₁₆ ×w _256c ), (n ₃ ×w _256c ,-n ₁₅ ×w _256c ), (n ₃ ×w _256c ,- n ₁₄ ×w _256c ), (n ₃ ×w _256c ,-n ₁₃ ×w _256c ), (n ₃ ×w _256c ,-n ₁₂ ×w _256c ), (n ₃ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₃ ×w _256c ,-n ₁₀ ×w _256c ), (n ₃ ×w _256c ,-n ₉ ×w _256c ),

(n ₂ ×w _256c , n ₁₆ ×w _256c ), (n ₂ ×w _256c , n ₁₅ ×w _256c ), (n ₂ ×w _256c , n ₁₄ ×w _256c ), (n ₂ ×w _256c , n ₁₃ ×w _256c ), (n ₂ ×w _256c , n ₁₂ ×w _256c ), (n ₂ ×w _256c , n ₁₁ ×w _256c ), (n ₂ ×w _256c , n ₁₀ ×w _256c ), (n ₂ ×w _256c , n ₉ ×w _256c ), (n ₂ ×w _256c ,-n ₁₆ ×w _256c ), (n ₂ ×w _256c ,-n ₁₅ ×w _256c ), (n ₂ ×w _256c ,- n ₁₄ ×w _256c ), (n ₂ ×w _256c ,-n ₁₃ ×w _256c ), (n ₂ ×w _256c ,-n ₁₂ ×w _256c ), (n ₂ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₂ ×w _256c ,-n ₁₀ ×w _256c ), (n ₂ ×w _256c ,-n ₉ ×w _256c ),

(n ₁ ×w _256c , n ₁₆ ×w _256c ), (n ₁ ×w _256c , n ₁₅ ×w _256c ), (n ₁ ×w _256c , n ₁₄ ×w _256c ), (n ₁ ×w _256c , n ₁₃ ×w _256c ), (n ₁ ×w _256c , n ₁₂ ×w _256c ), (n ₁ ×w _256c , n ₁₁ ×w _256c ), (n ₁ ×w _256c , n ₁₀ ×w _256c ), (n ₁ ×w _256c , n ₉ ×w _256c ), (n ₁ ×w _256c ,-n ₁₆ ×w _256c ), (n ₁ ×w _256c ,-n ₁₅ ×w _256c ), (n ₁ ×w _256c ,- n ₁₄ ×w _256c ), (n ₁ ×w _256c ,-n ₁₃ ×w _256c ), (n ₁ ×w _256c ,-n ₁₂ ×w _256c ), (n ₁ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₁ ×w _256c ,-n ₁₀ ×w _256c ), (n ₁ ×w _256c ,-n ₉ ×w _256c ),

(-n ₈ ×w _256c , n ₁₆ ×w _256c ), (-n ₈ ×w _256c , n ₁₅ ×w _256c ), (-n ₈ ×w _256c , n ₁₄ ×w _256c ), (-n ₈ × w _256c , n ₁₃ ×w _256c ), (-n ₈ ×w _256c , n ₁₂ ×w _256c ), (-n ₈ ×w _256c , n ₁₁ ×w _256c ), (-n ₈ ×w _256c , n ₁₀ ×w _256c ), (-n ₈ ×w _256c , n ₉ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₈ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₈ ×w _256c ,-n ₉ ×w _256c ),

(-n ₇ ×w _256c , n ₁₆ ×w _256c ), (-n ₇ ×w _256c , n ₁₅ ×w _256c ), (-n ₇ ×w _256c , n ₁₄ ×w _256c ), (-n ₇ × w _256c , n ₁₃ ×w _256c ), (-n ₇ ×w _256c , n ₁₂ ×w _256c ), (-n ₇ ×w _256c , n ₁₁ ×w _256c ), (-n ₇ ×w _256c , n ₁₀ ×w _256c ), (-n ₇ ×w _256c , n ₉ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₇ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₇ ×w _256c ,-n ₉ ×w _256c ),

(-n ₆ ×w _256c , n ₁₆ ×w _256c ), (-n ₆ ×w _256c , n ₁₅ ×w _256c ), (-n ₆ ×w _256c , n ₁₄ ×w _256c ), (-n ₆ × w _256c , n ₁₃ ×w _256c ), (-n ₆ ×w _256c , n ₁₂ ×w _256c ), (-n ₆ ×w _256c , n ₁₁ ×w _256c ), (-n ₆ ×w _256c , n ₁₀ ×w _256c ), (-n ₆ ×w _256c , n ₆ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₆ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₆ ×w _256c ,-n ₉ ×w _256c ),

(-n ₅ ×w _256c , n ₁₆ ×w _256c ), (-n ₅ ×w _256c , n ₁₅ ×w _256c ), (-n ₅ ×w _256c , n ₁₄ ×w _256c ), (-n ₅ × w _256c , n ₁₃ ×w _256c ), (-n ₅ ×w _256c , n ₁₂ ×w _256c ), (-n ₅ ×w _256c , n ₁₁ ×w _256c ), (-n ₅ ×w _256c , n ₁₀ ×w _256c ), (-n ₅ ×w _256c , n ₉ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₅ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₅ ×w _256c ,-n ₉ ×w _256c ),

(-n ₄ ×w _256c , n ₁₆ ×w _256c ), (-n ₄ ×w _256c , n ₁₅ ×w _256c ), (-n ₄ ×w _256c , n ₁₄ ×w _256c ), (-n ₄ × w _256c , n ₁₃ ×w _256c ), (-n ₄ ×w _256c , n ₁₂ ×w _256c ), (-n ₄ ×w _256c , n ₁₁ ×w _256c ), (-n ₄ ×w _256c , n ₁₀ ×w _256c ), (-n ₄ ×w _256c , n ₉ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₄ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₄ ×w _256c ,-n ₉ ×w _256c ),

(-n ₃ ×w _256c , n ₁₆ ×w _256c ), (-n ₃ ×w _256c , n ₁₅ ×w _256c ), (-n ₃ ×w _256c , n ₁₄ ×w _256c ), (-n ₃ × w _256c , n ₁₃ ×w _256c ), (-n ₃ ×w _256c , n ₁₂ ×w _256c ), (-n ₃ ×w _256c , n ₁₁ ×w _256c ), (-n ₃ ×w _256c , n ₁₀ ×w _256c ), (-n ₃ ×w _256c , n ₉ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₃ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₃ ×w _256c ,-n ₉ ×w _256c ),

(-n ₂ ×w _256c , n ₁₆ ×w _256c ), (-n ₂ ×w _256c , n ₁₅ ×w _256c ), (-n ₂ ×w _256c , n ₁₄ ×w _256c ), (-n ₂ × w _256c , n ₁₃ ×w _256c ), (-n ₂ ×w _256c , n ₁₂ ×w _256c ), (-n ₂ ×w _256c , n ₁₁ ×w _256c ), (-n ₂ ×w _256c , n ₁₀ ×w _256c ), (-n ₂ ×w _256c , n ₉ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₂ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₂ ×w _256c ,-n ₉ ×w _256c ),

(-n ₁ ×w _256c , n ₁₆ ×w _256c ), (-n ₁ ×w _256c , n ₁₅ ×w _256c ), (-n ₁ ×w _256c , n ₁₄ ×w _256c ), (-n ₁ × w _256c , n ₁₃ ×w _256c ), (-n ₁ ×w _256c , n ₁₂ ×w _256c ), (-n ₁ ×w _256c , n ₁₁ ×w _256c ), (-n ₁ ×w _256c , n ₁₀ ×w _256c ), (-n ₁ ×w _256c , n ₉ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₁ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₁ ×w _256c ,-n ₉ ×w _256c ),

(w _256c is a real number greater than 0).

Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, b5, b6, and b7. For example, when the transmitted bit is (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), the signal in FIG. 121 It is mapped to point 12101, and if the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, (I, Q) = (n ₈ × w _256c , n ₁₆ × w _256c ).

That is, the in-phase component I and the quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the transmitted bits (b0, b1, b2, b3, b4, b5, b6, b7). In addition, an example of the relationship between the set (00000000-11111111) of b0, b1, b2, b3, b4, b5, b6, b7, and the coordinate of a signal point is as shown in FIG. 256 signal points of 256QAM (“○” in Fig. 121)

(n ₈ ×w _256c , n ₁₆ ×w _256c ), (n ₈ ×w _256c , n ₁₅ ×w _256c ), (n ₈ ×w _256c , n ₁₄ ×w _256c ), (n ₈ ×w _256c , n ₁₃ ×w _256c ), (n ₈ ×w _256c , n ₁₂ ×w _256c ), (n ₈ ×w _256c , n ₁₁ ×w _256c ), (n ₈ ×w _256c , n ₁₀ ×w _256c ), (n ₈ ×w _256c , n ₉ ×w _256c ), (n ₈ ×w _256c ,-n ₁₆ ×w _256c ), (n ₈ ×w _256c ,-n ₁₅ ×w _256c ), (n ₈ ×w _256c ,- n ₁₄ ×w _256c ), (n ₈ ×w _256c ,-n ₁₃ ×w _256c ), (n ₈ ×w _256c ,-n ₁₂ ×w _256c ), (n ₈ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₈ ×w _256c ,-n ₁₀ ×w _256c ), (n ₈ ×w _256c ,-n ₉ ×w _256c ),

(n ₇ ×w _256c , n ₁₆ ×w _256c ), (n ₇ ×w _256c , n ₁₅ ×w _256c ), (n ₇ ×w _256c , n ₁₄ ×w _256c ), (n ₇ ×w _256c , n ₁₃ ×w _256c ), (n ₇ ×w _256c , n ₁₂ ×w _256c ), (n ₇ ×w _256c , n ₁₁ ×w _256c ), (n ₇ ×w _256c , n ₁₀ ×w _256c ), (n ₇ ×w _256c , n ₉ ×w _256c ), (n ₇ ×w _256c ,-n ₁₆ ×w _256c ), (n ₇ ×w _256c ,-n ₁₅ ×w _256c ), (n ₇ ×w _256c ,- n ₁₄ ×w _256c ), (n ₇ ×w _256c ,-n ₁₃ ×w _256c ), (n ₇ ×w _256c ,-n ₁₂ ×w _256c ), (n ₇ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₇ ×w _256c ,-n ₁₀ ×w _256c ), (n ₇ ×w _256c ,-n ₉ ×w _256c ),

(n ₆ ×w _256c , n ₁₆ ×w _256c ), (n ₆ ×w _256c , n ₁₅ ×w _256c ), (n ₆ ×w _256c , n ₁₄ ×w _256c ), (n ₆ ×w _256c , n ₁₃ ×w _256c ), (n ₆ ×w _256c , n ₁₂ ×w _256c ), (n ₆ ×w _256c , n ₁₁ ×w _256c ), (n ₆ ×w _256c , n ₁₀ ×w _256c ), (n ₆ ×w _256c , n ₆ ×w _256c ), (n ₆ ×w _256c ,-n ₁₆ ×w _256c ), (n ₆ ×w _256c ,-n ₁₅ ×w _256c ), (n ₆ ×w _256c ,- n ₁₄ ×w _256c ), (n ₆ ×w _256c ,-n ₁₃ ×w _256c ), (n ₆ ×w _256c ,-n ₁₂ ×w _256c ), (n ₆ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₆ ×w _256c ,-n ₁₀ ×w _256c ), (n ₆ ×w _256c ,-n ₉ ×w _256c ),

(n ₅ ×w _256c , n ₁₆ ×w _256c ), (n ₅ ×w _256c , n ₁₅ ×w _256c ), (n ₅ ×w _256c , n ₁₄ ×w _256c ), (n ₅ ×w _256c , n ₁₃ ×w _256c ), (n ₅ ×w _256c , n ₁₂ ×w _256c ), (n ₅ ×w _256c , n ₁₁ ×w _256c ), (n ₅ ×w _256c , n ₁₀ ×w _256c ), (n ₅ ×w _256c , n ₉ ×w _256c ), (n ₅ ×w _256c ,-n ₁₆ ×w _256c ), (n ₅ ×w _256c ,-n ₁₅ ×w _256c ), (n ₅ ×w _256c ,- n ₁₄ ×w _256c ), (n ₅ ×w _256c ,-n ₁₃ ×w _256c ), (n ₅ ×w _256c ,-n ₁₂ ×w _256c ), (n ₅ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₅ ×w _256c ,-n ₁₀ ×w _256c ), (n ₅ ×w _256c ,-n ₉ ×w _256c ),

(n ₄ ×w _256c , n ₁₆ ×w _256c ), (n ₄ ×w _256c , n ₁₅ ×w _256c ), (n ₄ ×w _256c , n ₁₄ ×w _256c ), (n ₄ ×w _256c , n ₁₃ ×w _256c ), (n ₄ ×w _256c , n ₁₂ ×w _256c ), (n ₄ ×w _256c , n ₁₁ ×w _256c ), (n ₄ ×w _256c , n ₁₀ ×w _256c ), (n ₄ ×w _256c , n ₉ ×w _256c ), (n ₄ ×w _256c ,-n ₁₆ ×w _256c ), (n ₄ ×w _256c ,-n ₁₅ ×w _256c ), (n ₄ ×w _256c ,- n ₁₄ ×w _256c ), (n ₄ ×w _256c ,-n ₁₃ ×w _256c ), (n ₄ ×w _256c ,-n ₁₂ ×w _256c ), (n ₄ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₄ ×w _256c ,-n ₁₀ ×w _256c ), (n ₄ ×w _256c ,-n ₉ ×w _256c ),

(n ₃ ×w _256c , n ₁₆ ×w _256c ), (n ₃ ×w _256c , n ₁₅ ×w _256c ), (n ₃ ×w _256c , n ₁₄ ×w _256c ), (n ₃ ×w _256c , n ₁₃ ×w _256c ), (n ₃ ×w _256c , n ₁₂ ×w _256c ), (n ₃ ×w _256c , n ₁₁ ×w _256c ), (n ₃ ×w _256c , n ₁₀ ×w _256c ), (n ₃ ×w _256c , n ₉ ×w _256c ), (n ₃ ×w _256c ,-n ₁₆ ×w _256c ), (n ₃ ×w _256c ,-n ₁₅ ×w _256c ), (n ₃ ×w _256c ,- n ₁₄ ×w _256c ), (n ₃ ×w _256c ,-n ₁₃ ×w _256c ), (n ₃ ×w _256c ,-n ₁₂ ×w _256c ), (n ₃ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₃ ×w _256c ,-n ₁₀ ×w _256c ), (n ₃ ×w _256c ,-n ₉ ×w _256c ),

(n ₂ ×w _256c , n ₁₆ ×w _256c ), (n ₂ ×w _256c , n ₁₅ ×w _256c ), (n ₂ ×w _256c , n ₁₄ ×w _256c ), (n ₂ ×w _256c , n ₁₃ ×w _256c ), (n ₂ ×w _256c , n ₁₂ ×w _256c ), (n ₂ ×w _256c , n ₁₁ ×w _256c ), (n ₂ ×w _256c , n ₁₀ ×w _256c ), (n ₂ ×w _256c , n ₉ ×w _256c ), (n ₂ ×w _256c ,-n ₁₆ ×w _256c ), (n ₂ ×w _256c ,-n ₁₅ ×w _256c ), (n ₂ ×w _256c ,- n ₁₄ ×w _256c ), (n ₂ ×w _256c ,-n ₁₃ ×w _256c ), (n ₂ ×w _256c ,-n ₁₂ ×w _256c ), (n ₂ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₂ ×w _256c ,-n ₁₀ ×w _256c ), (n ₂ ×w _256c ,-n ₉ ×w _256c ),

(n ₁ ×w _256c , n ₁₆ ×w _256c ), (n ₁ ×w _256c , n ₁₅ ×w _256c ), (n ₁ ×w _256c , n ₁₄ ×w _256c ), (n ₁ ×w _256c , n ₁₃ ×w _256c ), (n ₁ ×w _256c , n ₁₂ ×w _256c ), (n ₁ ×w _256c , n ₁₁ ×w _256c ), (n ₁ ×w _256c , n ₁₀ ×w _256c ), (n ₁ ×w _256c , n ₉ ×w _256c ), (n ₁ ×w _256c ,-n ₁₆ ×w _256c ), (n ₁ ×w _256c ,-n ₁₅ ×w _256c ), (n ₁ ×w _256c ,- n ₁₄ ×w _256c ), (n ₁ ×w _256c ,-n ₁₃ ×w _256c ), (n ₁ ×w _256c ,-n ₁₂ ×w _256c ), (n ₁ ×w _256c ,-n ₁₁ ×w _256c ) ), (n ₁ ×w _256c ,-n ₁₀ ×w _256c ), (n ₁ ×w _256c ,-n ₉ ×w _256c ),

(-n ₈ ×w _256c , n ₁₆ ×w _256c ), (-n ₈ ×w _256c , n ₁₅ ×w _256c ), (-n ₈ ×w _256c , n ₁₄ ×w _256c ), (-n ₈ × w _256c , n ₁₃ ×w _256c ), (-n ₈ ×w _256c , n ₁₂ ×w _256c ), (-n ₈ ×w _256c , n ₁₁ ×w _256c ), (-n ₈ ×w _256c , n ₁₀ ×w _256c ), (-n ₈ ×w _256c , n ₉ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₈ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₈ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₈ ×w _256c ,-n ₉ ×w _256c ),

(-n ₇ ×w _256c , n ₁₆ ×w _256c ), (-n ₇ ×w _256c , n ₁₅ ×w _256c ), (-n ₇ ×w _256c , n ₁₄ ×w _256c ), (-n ₇ × w _256c , n ₁₃ ×w _256c ), (-n ₇ ×w _256c , n ₁₂ ×w _256c ), (-n ₇ ×w _256c , n ₁₁ ×w _256c ), (-n ₇ ×w _256c , n ₁₀ ×w _256c ), (-n ₇ ×w _256c , n ₉ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₇ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₇ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₇ ×w _256c ,-n ₉ ×w _256c ),

(-n ₆ ×w _256c , n ₁₆ ×w _256c ), (-n ₆ ×w _256c , n ₁₅ ×w _256c ), (-n ₆ ×w _256c , n ₁₄ ×w _256c ), (-n ₆ × w _256c , n ₁₃ ×w _256c ), (-n ₆ ×w _256c , n ₁₂ ×w _256c ), (-n ₆ ×w _256c , n ₁₁ ×w _256c ), (-n ₆ ×w _256c , n ₁₀ ×w _256c ), (-n ₆ ×w _256c , n ₆ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₆ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₆ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₆ ×w _256c ,-n ₉ ×w _256c ),

(-n ₅ ×w _256c , n ₁₆ ×w _256c ), (-n ₅ ×w _256c , n ₁₅ ×w _256c ), (-n ₅ ×w _256c , n ₁₄ ×w _256c ), (-n ₅ × w _256c , n ₁₃ ×w _256c ), (-n ₅ ×w _256c , n ₁₂ ×w _256c ), (-n ₅ ×w _256c , n ₁₁ ×w _256c ), (-n ₅ ×w _256c , n ₁₀ ×w _256c ), (-n ₅ ×w _256c , n ₉ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₅ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₅ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₅ ×w _256c ,-n ₉ ×w _256c ),

(-n ₄ ×w _256c , n ₁₆ ×w _256c ), (-n ₄ ×w _256c , n ₁₅ ×w _256c ), (-n ₄ ×w _256c , n ₁₄ ×w _256c ), (-n ₄ × w _256c , n ₁₃ ×w _256c ), (-n ₄ ×w _256c , n ₁₂ ×w _256c ), (-n ₄ ×w _256c , n ₁₁ ×w _256c ), (-n ₄ ×w _256c , n ₁₀ ×w _256c ), (-n ₄ ×w _256c , n ₉ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₄ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₄ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₄ ×w _256c ,-n ₉ ×w _256c ),

(-n ₃ ×w _256c , n ₁₆ ×w _256c ), (-n ₃ ×w _256c , n ₁₅ ×w _256c ), (-n ₃ ×w _256c , n ₁₄ ×w _256c ), (-n ₃ × w _256c , n ₁₃ ×w _256c ), (-n ₃ ×w _256c , n ₁₂ ×w _256c ), (-n ₃ ×w _256c , n ₁₁ ×w _256c ), (-n ₃ ×w _256c , n ₁₀ ×w _256c ), (-n ₃ ×w _256c , n ₉ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₃ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₃ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₃ ×w _256c ,-n ₉ ×w _256c ),

(-n ₂ ×w _256c , n ₁₆ ×w _256c ), (-n ₂ ×w _256c , n ₁₅ ×w _256c ), (-n ₂ ×w _256c , n ₁₄ ×w _256c ), (-n ₂ × w _256c , n ₁₃ ×w _256c ), (-n ₂ ×w _256c , n ₁₂ ×w _256c ), (-n ₂ ×w _256c , n ₁₁ ×w _256c ), (-n ₂ ×w _256c , n ₁₀ ×w _256c ), (-n ₂ ×w _256c , n ₉ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₂ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₂ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₂ ×w _256c ,-n ₉ ×w _256c ),

(-n ₁ ×w _256c , n ₁₆ ×w _256c ), (-n ₁ ×w _256c , n ₁₅ ×w _256c ), (-n ₁ ×w _256c , n ₁₄ ×w _256c ), (-n ₁ × w _256c , n ₁₃ ×w _256c ), (-n ₁ ×w _256c , n ₁₂ ×w _256c ), (-n ₁ ×w _256c , n ₁₁ ×w _256c ), (-n ₁ ×w _256c , n ₁₀ ×w _256c ), (-n ₁ ×w _256c , n ₉ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₆ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₅ ×w _256c ) ), (-n ₁ ×w _256c ,-n ₁₄ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₃ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₂ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₁ ×w _256c ), (-n ₁ ×w _256c ,-n ₁₀ ×w _256c ), (-n ₁ ×w _256c ,-n ₉ ×w _256c ),

The values of 00000000 to 11111111 in sets of b0, b1, b2, b3, b4, b5, b6, and b7 are shown immediately below. Each coordinate in the in-phase I-orthogonal Q plane of the signal point (“○”) immediately above the sets 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, b7 corresponds to the baseband signal after mapping. It becomes an in-phase component I and an orthogonal component Q. Note that the relationship between the sets of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points at 256QAM is not limited to FIG. 121 .

In the 256 signal points in Fig. 121, "signal point 1", "signal point 2"... It is called "signal point 255" and "signal point 256". (Since there are 256 signal points, "signal point 1" to "signal point 256" exist). Let Di be the distance between the "signal point i" and the origin in the in-phase I-orthogonal Q plane. At this time, w _256c is given as follows.

Then, the average power ^of the baseband signal after mapping becomes z2. In addition, the effect is demonstrated next.

Next, the effect of using the QAM described above will be described.

First, the configuration of the transmitting apparatus and the receiving apparatus will be described.

117 is an example of the structure of a transmitter. The error correction encoding unit 11702 receives the information 11701 as an input, performs error correction encoding such as an LDPC code or a turbo code, and outputs the data 11703 after error correction encoding.

The interleaving unit 11704 receives the data 11703 after error correction encoding, rearranges the data, and outputs the interleaved data 11705.

The mapping unit 11706 receives the interleaved data 11705 as input, performs mapping based on the modulation method set by the transmitter, and outputs an orthogonal baseband signal (in-phase I component and quadrature Q component) 11707 .

The radio unit 11708 receives the quadrature baseband signal 11707 as an input, performs processing such as quadrature modulation, frequency conversion, and amplification, and outputs a transmission signal 11709. And the transmission signal 11709 is output from the antenna 11710 as a radio wave.

FIG. 118 is an example of the configuration of a receiving device that receives a modulated signal transmitted by the transmitting device of FIG. 117 .

The radio unit 11803 receives the received signal 11802 received from the antenna 11801 as an input, performs frequency conversion, orthogonal demodulation, and the like, and outputs an orthogonal baseband signal 11804.

The demapping unit 11805 receives the orthogonal baseband signal 11804 as an input to estimate and remove the frequency offset and estimate the channel variation (transmission path variation), and at the same time estimate the log-likelihood ratio of each bit in the data symbol, for example. , and output a log-likelihood ratio signal 11806.

The de-interleave unit 11807 receives the log-likelihood ratio signal 11806 as an input, performs rearrangement, and outputs the log-likelihood ratio signal 11808 after deinterleaving.

The decoding unit 11809 receives the deinterleaved log-likelihood ratio signal 11808 as input, decodes the error correction code, and outputs the received data 11810 .

In explaining the effect, the case of 16QAM will be described as an example. The following two cases (<16QAM#3> and <16QAM#4>) are compared.

<16QAM#3> This is the 16QAM described in Supplementary 2, and the arrangement of the signal points in the in-phase I-orthogonal Q plane is as shown in FIG.

<16QAM#4>The arrangement of the signal points in the in-phase I-orthogonal Q plane is as shown in FIG. 119, as described above, k ₁ >0 (k ₁ is a real number greater than 0), and k ₂ > It is assumed that 0 (k ₂ is a real number greater than 0), k ₁ ≠ 1, k ₂ ≠ 1, and k ₁ ≠ k ₂ .

In 16QAM, 4 bits of b0, b1, b2, and b3 are transmitted as described above. In the case of <16QAM#3>, when the log-likelihood ratio of each bit is calculated in the receiving apparatus, 4 bits are divided into "2-bit high-definition bits and 2-bit low-definition bits". On the other hand, when <16QAM #4>, "k ₁ >0 (k ₁ is a real number greater than 0), and k ₂ >0 (k ₂ is a real number greater than 0), k ₁ ≠ 1, Also, it is assumed that k ₂ ≠ 1 and k ₁ ≠ k ₂ ”, “1 bit high-definition bit, 2-bit medium-quality bit, 1-bit low-quality bit” is divided As described above, the distribution of the quality of 4 bits differs according to <16QAM#3> and <16QAM#4>. In this situation, when the error correction code is decoded by the decoding unit 11809 of FIG. 118, it is better to use <16QAM#4> depending on the error correction code used to obtain high data reception quality in the receiving device. there is a possibility

In addition, in 64QAM, when the arrangement of signal points on the in-phase I-orthogonal Q plane is as shown in Fig. 120, as described above, there is a possibility that high data reception quality can be obtained in the receiving apparatus. In this case, as previously described,

"m ₁ >0 (m ₁ is a real number greater than 0), m ₂ >0 (m ₂ is a real number greater than 0), and m ₃ >0 (m ₃ is a real number greater than 0), Also, m ₄ >0 (m ₄ is a real number greater than 0), m ₅ >0 (m ₅ is a real number greater than 0), and m ₆ >0 (m ₆ is a real number greater than 0) , also, m ₇ >0 (m ₇ is a real number greater than 0), and m ₈ >0 (m ₈ is a real number greater than 0),

{m ₁ ≠m ₂ , m ₁ ≠m ₃ , m ₁ ≠m ₄ , m ₂ ≠m ₃ , m ₂ ≠m ₄ , and m ₃ ≠m ₄ }

In addition,

{m ₅ ≠m ₆ , m ₅ ≠m ₇ , m ₅ ≠m ₈ , m ₆ ≠m ₇ , m ₆ ≠m ₈ , and m ₇ ≠m ₈ }

In addition,

{So that m ₁ ≠m ₅ , or m ₂ ≠m ₆ , or m ₃ ≠m ₇ , or m ₄ ≠m ₈ holds}

is established.”

or,

"m ₁ >0 (m ₁ is a real number greater than 0), m ₂ >0 (m ₂ is a real number greater than 0), and m ₃ >0 (m ₃ is a real number greater than 0), Also, m ₄ >0 (m ₄ is a real number greater than 0), m ₅ >0 (m ₅ is a real number greater than 0), and m ₆ >0 (m ₆ is a real number greater than 0) , also, m ₇ >0 (m ₇ is a real number greater than 0), and m ₈ >0 (m ₈ is a real number greater than 0),

{m ₁ ≠m ₂ , m ₁ ≠m ₃ , m ₁ ≠m ₄ , m ₂ ≠m ₃ , m ₂ ≠m ₄ , and m ₃ ≠m ₄ }

In addition,

{m ₅ ≠m ₆ , m ₅ ≠m ₇ , m ₅ ≠m ₈ , m ₆ ≠m ₇ , m ₆ ≠m ₈ , and m ₇ ≠m ₈ }

In addition,

{So that m ₁ ≠m ₅ , or m ₂ ≠m ₆ , or m ₃ ≠m ₇ , or m ₄ ≠m ₈ holds}

In addition,

{m ₁ =m ₅ , or m ₂ =m ₆ , or m ₃ =m ₇ , or m ₄ =m ₈ holds}

is established.”

do it with

is an important condition, which is different from the signal point arrangement described in Supplementary 2.

Similarly, in 256QAM, when the signal points are arranged in the in-phase I-orthogonal Q plane as shown in FIG. 121, as described above, there is a possibility that high data reception quality can be obtained in the receiving apparatus. In this case, as previously described,

"n ₁ >0 (n ₁ is a real number greater than 0), n ₂ >0 (n ₂ is a real number greater than 0), and n ₃ >0 (n ₃ is a real number greater than 0), Also, n ₄ >0 (n ₄ is a real number greater than 0), n ₅ >0 (n ₅ is a real number greater than 0), and n ₆ >0 (n ₆ is a real number greater than 0) , also, n ₇ >0 (n ₇ is a real number greater than 0), and also n ₈ >0 (n ₈ is a real number greater than 0),

Also, n ₉ >0 (n ₉ is a real number greater than 0), n ₁₀ >0 (n ₁₀ is a real number greater than 0), and n ₁₁ >0 (n ₁₁ is a real number greater than 0) , also n ₁₂ >0 (n ₁₂ is a real number greater than 0), n ₁₃ >0 (n ₁₃ is a real number greater than 0), and n ₁₄ >0 (n ₁₄ is a real number greater than 0) , and n ₁₅ >0 (n ₁₅ is a real number greater than 0), and n ₁₆ >0 (n ₁₆ is a real number greater than 0),

{n ₁ ≠n ₂ , n ₁ ≠n ₃ , n ₁ ≠n ₄ , n ₁ ≠n ₅ , n ₁ ≠n ₆ , and n ₁ ≠n ₇ and also, n ₁ ≠n ₈ ,

Further, n ₂ ≠ n ₃ , n ₂ ≠ n ₄ , n ₂ ≠ n ₅ , n ₂ ≠ n ₆ , and n ₂ ≠ n 7 , and further, n ₂ ≠ n ₇ , n ₈ ,

Further, n ₃ ≠ n ₄ , and further, n ₃ ≠ n ₅ , and further, n ₃ ≠ n ₆ , and further, n ₃ ≠ n ₇ , and further, n ₃ ≠ n ₈ ,

Further, n ₄ ≠ n ₅ , and further, n ₄ ≠ n ₆ , and further, n ₄ ≠ n ₇ , and further, n ₄ ≠ n ₈ ,

Further, n ₅ ≠ n ₆ , and n ₅ ≠ n ₇ , and further, n ₅ ≠ n ₈ ,

Also, n ₆ ≠ n ₇ , and n ₆ ≠ n ₈ ,

Also, n ₇ ≠ n ₈ }

In addition,

{n ₉ ≠n ₁₀ , n ₉ ≠n ₁₁ , n ₉ ≠n ₁₂ , n ₉ ≠n ₁₃ , n ₉ ≠n ₁₄ , and n ₉ ≠ n ₁₅ , and also, n ₉ ≠ n ₁₆ ,

Further, n ₁₀ ≠ n ₁₁ , further n ₁₀ ≠ n ₁₂ , further n ₁₀ ≠ n ₁₃ , further n ₁₀ ≠ n ₁₄ , further n ₁₀ ≠ n ₁₅ , and further, n ₁₀ ≠ n 15 , n ₁₆ ,

Further, n ₁₁ ≠ n ₁₂ , and n ₁₁ ≠ n ₁₃ , and further, n ₁₁ ≠ n ₁₄ , and further, n ₁₁ ≠ n ₁₅ , and further, n ₁₁ ≠ n ₁₆ ,

Further, n ₁₂ ≠ n ₁₃ , and further, n ₁₂ ≠ n ₁₄ , and further, n ₁₂ ≠ n ₁₅ , and further, n ₁₂ ≠ n ₁₆ ,

Further, n ₁₃ ≠ n ₁₄ , and further, n ₁₃ ≠ n ₁₅ , and further, n ₁₃ ≠ n ₁₆ ,

Also, n ₁₄ ≠n ₁₅ , and n ₁₄ ≠n ₁₆ ,

Also, n ₁₅ ≠ n ₁₆ }

In addition,

{n ₁ ≠n ₉ , or n ₂ ≠n ₁₀ , or n ₃ ≠n ₁₁ , or n ₄ ≠n ₁₂ , or n ₅ ≠n ₁₃ , or n ₆ ≠n ₁₄ , or n ₇ ≠n ₁₅ , or n ₈ ≠ n ₁₆ holds}

is established.”

or,

"n ₁ >0 (n ₁ is a real number greater than 0), n ₂ >0 (n ₂ is a real number greater than 0), and n ₃ >0 (n ₃ is a real number greater than 0), Also, n ₄ >0 (n ₄ is a real number greater than 0), n ₅ >0 (n ₅ is a real number greater than 0), and n ₆ >0 (n ₆ is a real number greater than 0) , also, n ₇ >0 (n ₇ is a real number greater than 0), and also n ₈ >0 (n ₈ is a real number greater than 0),

Also, n ₉ >0 (n ₉ is a real number greater than 0), n ₁₀ >0 (n ₁₀ is a real number greater than 0), and n ₁₁ >0 (n ₁₁ is a real number greater than 0) , also, n ₁₂ >0 (n ₁₂ is a real number greater than 0), n ₁₃ >0 (n ₁₃ is a real number greater than 0), and n ₁₄ >0 (n ₁₄ is a real number greater than 0) , and n ₁₅ >0 (n ₁₅ is a real number greater than 0), and n ₁₆ >0 (n ₁₆ is a real number greater than 0),

{n ₁ ≠n ₂ , n ₁ ≠n ₃ , n ₁ ≠n ₄ , n ₁ ≠n ₅ , n ₁ ≠n ₆ , and n ₁ ≠n ₇ and also, n ₁ ≠n ₈ ,

On the other hand, n ₂ ≠ n ₃ , n ₂ ≠ n ₄ , n ₂ ≠ n ₅ , n ₂ ≠ n ₆ , and n ₂ ≠ n 7 , and further, n ₂ ≠ n ₇ , n ₈ ,

Further, n ₃ ≠ n ₄ , and further, n ₃ ≠ n ₅ , and further, n ₃ ≠ n ₆ , and further, n ₃ ≠ n ₇ , and further, n ₃ ≠ n ₈ ,

Further, n ₄ ≠ n ₅ , and further, n ₄ ≠ n ₆ , and further, n ₄ ≠ n ₇ , and further, n ₄ ≠ n ₈ ,

Further, n ₅ ≠ n ₆ , and n ₅ ≠ n ₇ , and further, n ₅ ≠ n ₈ ,

Also, n ₆ ≠ n ₇ , and n ₆ ≠ n ₈ ,

Also, n ₇ ≠ n ₈ }

In addition,

{n ₉ ≠n ₁₀ , n ₉ ≠n ₁₁ , n ₉ ≠n ₁₂ , n ₉ ≠n ₁₃ , n ₉ ≠n ₁₄ , and n ₉ ≠ n ₁₅ , and also, n ₉ ≠ n ₁₆ ,

Further, n ₁₀ ≠ n ₁₁ , further n ₁₀ ≠ n ₁₂ , further n ₁₀ ≠ n ₁₃ , further n ₁₀ ≠ n ₁₄ , further n ₁₀ ≠ n ₁₅ , and further, n ₁₀ ≠ n 15 , n ₁₆ ,

Further, n ₁₁ ≠ n ₁₂ , and n ₁₁ ≠ n ₁₃ , and further, n ₁₁ ≠ n ₁₄ , and further, n ₁₁ ≠ n ₁₅ , and further, n ₁₁ ≠ n ₁₆ ,

Further, n ₁₂ ≠ n ₁₃ , and further, n ₁₂ ≠ n ₁₄ , and further, n ₁₂ ≠ n ₁₅ , and further, n ₁₂ ≠ n ₁₆ ,

Further, n ₁₃ ≠ n ₁₄ , and further, n ₁₃ ≠ n ₁₅ , and further, n ₁₃ ≠ n ₁₆ ,

Also, n ₁₄ ≠n ₁₅ , and n ₁₄ ≠n ₁₆ ,

Also, n ₁₅ ≠ n ₁₆ }

In addition,

{n ₁ ≠n ₉ , or n ₂ ≠n ₁₀ , or n ₃ ≠n ₁₁ , or n ₄ ≠n ₁₂ , or n ₅ ≠n ₁₃ , or n ₆ ≠n ₁₄ , or n ₇ ≠n ₁₅ , or n ₈ ≠ n ₁₆ holds}

In addition,

{n ₁ =n ₉ , or n ₂ =n ₁₀ , or n ₃ =n ₁₁ , or n ₄ =n ₁₂ , or n ₅ =n ₁₃ , or n ₆ =n ₁₄ , or n ₇ =n ₁₅ , or n ₈ = n ₁₆ holds}

is established.”

is an important condition, which is different from the arrangement of the signal points described in Supplementary 2.

In addition, although the detailed configuration is omitted in Figs. 117 and 118, the same implementation can be performed even in the case of transmitting and receiving a modulated signal using the OFDM method and the spread spectrum communication method described in the other embodiments.

In addition, the MIMO transmission method described in the first to twelfth embodiments and space-time codes such as space-time block codes (however, the symbols may be arranged on the frequency axis), precoding In the MIMO transmission method with or without precoding, even if 16QAM, 64QAM, and 256QAM described above are used, there is a possibility that the data reception quality can be improved.

(Supplementary 5)

Here, a configuration example of a communication/broadcasting system using QAM described in (Supplementary 2), (Supplementary 3), and (Supplementary 4) will be described.

Fig. 122 is an example of a transmission device, and the same numbers are assigned to those that operate in the same manner as in Fig. 117 .

The transmission method instruction unit 12202 receives the input signal 12201 as an input, and generates an information signal 12203 regarding an error correction code (eg, an error correction code for generating a data symbol based on the input signal 12201). coding rate, block length of the error correction code, etc.), the information signal 12204 regarding the modulation method (eg, the modulation method), and the information signal 12205 of the parameter regarding the modulation method (eg, the amplitude of the QAM information about the value). Moreover, the user who uses the input signal 12201 may generate|occur|produce the input signal 12201, and when using it in a communication system, it is good also considering the feedback information of a communication partner as the input signal 12201.

The error correction coding unit 11702 receives the information 11701 and the information signal 12203 related to the error correction code as inputs, and performs error correction coding based on the information signal 12203 related to the error correction code to perform error correction coding. The subsequent data 11703 is output.

The mapping unit 11706 receives the interleaved data 11705, the information signal 12204 related to the modulation method, and the information signal 12205 of the parameter related to the modulation method as inputs, and the information signal 12204 related to the modulation method and the modulation method. Mapping is performed based on the information signal 12205 of the parameter related to the method, and an orthogonal baseband signal 11707 is output.

The control information symbol generating unit 12207 receives the information signal 12203 regarding the error correction code, the information signal 12204 regarding the modulation method, the information signal 12205 of the parameter regarding the modulation method, and the control data 12206 as inputs. Thus, the control information symbol signal 12208 is output by executing, for example, error correction coding processing and modulation processing such as BPSK or QPSK.

The radio unit 11703 receives the orthogonal baseband signal 11707, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210, and receives the frame composition signal 12210 based on the frame composition signal 12210. A transmission signal 11709 based on the output is output. In addition, the frame structure is the same as that shown in FIG.

Fig. 123 is an example of a frame configuration in frequency on the vertical axis and time on the horizontal axis. 123, 12301 is a pilot symbol, 12302 is a control information symbol, and 12303 is a data symbol. The pilot symbol 12301 corresponds to the pilot symbol signal 12209 of FIG. 122, the control information symbol 12302 corresponds to the control information symbol signal 12208 of FIG. 122, and the data symbol 12303 is orthogonal to that of FIG. It corresponds to the baseband signal 11707.

124 is a receiving device that receives a modulated signal transmitted by the transmitting device of FIG. 122, and the same numbers are assigned to those operating in the same manner as in FIG.

The synchronization unit 12405 receives the orthogonal baseband signal 11804 as an input and performs frequency synchronization, time synchronization, and frame synchronization by detecting and using, for example, the pilot symbol 12301 in FIG. ) as output.

The control information demodulator 12401 receives the orthogonal baseband signal 12403 and the synchronization signal 12406 as inputs, performs demodulation (and error correction decoding) of the control information symbol 12302 in FIG. (12402) is output.

The frequency offset/path estimation unit 12403 receives the orthogonal baseband signal 12403 and the synchronization signal 12406 as inputs, and uses, for example, the pilot symbol 12301 in FIG. By estimating the fluctuation of the transmission path, a frequency offset and fluctuation estimation signal 12404 of the transmission path are output.

The demapping unit 11805 receives an orthogonal baseband signal 12403, a control information signal 12402, a frequency offset and transmission path variation estimation signal 12404, and a synchronization signal 12406 as inputs, and receives a control information signal 12402 ) determines the modulation method of the data symbol 12303 in FIG. to output the log-likelihood ratio signal 11806.

The deinterleave unit 11807 receives the log-likelihood ratio signal 11808 and the control information signal 12402 as inputs, and transmits the information on the transmission method such as the modulation method and the error correction encoding method included in the control information signal 12402. The apparatus executes the processing of the deinterleave method corresponding to the interleave method used, and outputs the log-likelihood ratio signal 11808 after deinterleaving.

The decoding unit 11809 receives the log-likelihood ratio signal 11808 and the control information signal 12402 after deinterleaving as inputs, and performs error correction decoding based on the code from the error correction encoding method information included in the control information. and outputting the received data 11810.

Hereinafter, an embodiment using the QAM described in (Supplementary 2), (Supplementary 3) and (Supplementary 4) will be described.

<Example 1>

It is assumed that it is possible for the transmitter in FIG. 122 to transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #1>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #1>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described in FIG. 111 is used in the transmitter of FIG. 122 . In this case, it is assumed that f=f _#1 of FIG. 111 is set when the transmitter of FIG. 122 uses <error correction method #1>, and f=f _# 1 of FIG. 111 is set when <error correction method #12> is used. It is supposed to be set to At this time,

<Condition #H1>

It is sufficient that f _#1 ≠1, f _#12 ≠1, and f _#1 ≠f _# 1 hold. In this way, the possibility that the receiving device can obtain high data reception quality is increased in any of <Error Correction Method #1><Error Correction Method #1> Because the family register value of f is different).

It is assumed that the transmitter of FIG. 122 uses the 64QAM described with reference to FIG. 112 . At this time, when the transmitter of FIG. 122 uses <error correction method #1>, g ₁ =g ₁ , _#1 , g ₂ =g ₂ , _#1 , g ₃ =g ₃ , _#1 of FIG. 112 is set as It is assumed that, when <error correction method #2> is used, g ₁ =g ₁ , _#2 , g ₂ =g ₂ , _#2 , g ₃ =g ₃ , _#2 in FIG. 112 is set. Then, it is good if the following is satisfied.

<Condition #H2>

{(g _1,#11 , g2, _# 11, g3 _,#11 )≠(1,3,5), and (g1, _# 11, g2 _,#11 , g3 _,#11 ) )≠(1, 5, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(3,1,5), and (g1 _,#11 ) , g _{2,#11 ,} g3 _,#11 )≠(3, 5, 1), and (g1 _,# 11, g2,#11, g3 _,#11 )≠(5, 1, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(5, 3, 1)}

In addition,

{(g _{1,#2 ,} g2,#2, g3 _,#2 )≠(1, 3, 5), and (g1 _,#2 , g2 _,#2 , g3 _,#2 ) ) ≠ (1, 5, 3), and (g _1,#2 , g _2,#2 , g _3,#2 )≠(3, 1, 5), and (g _1,#2 ) , g _{2,#2, g3 ,#} 2)≠(3, 5, 1), and (g1 _,# 2, g2,#2, g3 _,#2 )≠(5, 1, 3) and (g _{1,#2 ,} g2,#2 , g3 _,#2 )≠(5, 3, 1)}

In addition,

{{{g _1,#1 ≠g _1,#2 , or g _2,#11 ≠g _2,#2 , or g _3,#11 ≠g _3,#2 } holds}

is established

In this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <Error Correction Method #1><Error Correction Method #1>(<Error Correction Method #1><Error Correction Method #12>) as the suitable sets of g ₁ , g ₂ , and g ₃ are different).

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 113 . At this time, when the transmitter of FIG. 122 uses the <error correction method #1>, h ₁ =h ₁ , _#1 , h ₂ =h _{2 , #1} , h ₃ =h _{3, #1} , h ₄ of FIG. 113 . =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11 , even when <error correction method #12> is used h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#2 , h ₆ = It is assumed that h6 _,#12 , _h7 =h7 _,#2 is set. Then, it is good if the following is satisfied.

<Condition #H3>

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {for all x and all y, ax≠ay holds}, (h _a1,#11 , h _{a2,# 1} , h _a3,#11 , h _a4,#11 , h _a5,#11 , h _a6,#11 , h _a7,#11 )≠(1, 3, 5, 7, 9, 11, 13) holds true do}

In addition,

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {with all x and all y, ax≠ay holds} (h _a1,#2 , h _a2,#2 , h _a3,#2 , h _a4,#2 , h _a5,#2 , h _a6,#2 , h _a7,#2 )≠(1, 3, 5, 7, 9, 11, 13) holds }

In addition,

{{h _1,#1 ≠h _1,#12 , or h _2,#11 ≠h _2,#12 , or h _3,#11 ≠h _3,#12 , or h _4,#11 ≠h _{4 ,} } holds true for _{# 2} , or h5 _{,#11 ≠} h5,#12, or h6,#11 ≠h6 _,#12 , or h7 _,#11 ≠h7 _,#12 }.

In this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <Error Correction Method #1><Error Correction Method #1>(<Error Correction Method #1><Error Correction Method #12>) (since the suitable sets of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ are different).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #1*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #2*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do).

In addition, it is assumed that the 16QAM described in FIG. 111 is used in the transmitter of FIG. 122 . At this time, it is assumed that f=f _#1 of FIG. 111 is set when the transmitter of FIG. 122 uses <error correction method #1*>, and f=f of FIG. 111 when <error correction method #2*> is used Suppose it is set to _#2 . At this time, it is sufficient if <condition #H1> is satisfied.

It is assumed that the transmitter of FIG. 122 uses the 64QAM described with reference to FIG. 112 . At this time, when the transmitter of FIG. 122 uses the <error correction method #1*>, g ₁ =g _{1,#11 , g2} =g2 _,# 11, _g3 =g3,#11 of FIG. When the <error correction method #2*> is used, it is assumed that g ₁ =g _{1, #2} , g ₂ =g _{2, #2} , g ₃ =g _{3, #2} in FIG. 112 is set. At this time, it is sufficient if <condition #H2> is satisfied.

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 113 . At this time, when the transmitter of FIG. 122 uses <error correction method #1*>, h ₁ =h _1,#11 , _h2 =h2 _,#11 , _h3 =h3 _,#11 , ₄ =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11, and use <error correction method #2*> When h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#2 , h in FIG. 112 , It is assumed that ₆ =h _6,#12 , _h7 =h7 _,#12 are set. At this time, it is sufficient if <condition #H3> is satisfied.

<Example 2>

It is assumed that it is possible for the transmitter in FIG. 122 to transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #3>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #4>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described in FIG. 114 is used in the transmitter of FIG. 122 . At this time, it is assumed that f ₁ =f _1,#11 , f2=f2 _, # ₁₁ of FIG. 114 is set when the transmitter of FIG. 122 uses <error correction method #13>, and <error correction method #14> When > is used, it is assumed that f ₁ =f _1,#12 , f2=f2, _{#12 in} FIG. 114 is set. At this time,

<Condition #H4>

{f _1,#11 ≠f1 _,#12 , or f2 _,#11 ≠f2 _,#12 } may hold. By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <Error Correction Method #1> and <Error Correction Method #1> increases (<Error Correction Method #1><Error Correction Method #4>) Since the suitable sets of f ₁ , f ₂ are different in >).

It is assumed that the transmitter of FIG. 122 uses the 64QAM described with reference to FIG. 115 . At this time, when the transmitter of FIG. 122 uses the <error correction method # ₃ >, g ₁ =g _{1,#11 , g2} =g2, _# 11, g3=g3,# ₁₁ , g4 in FIG. =g _4,#11 , _g5 =g5 _,#11 , _g6 =g6 _,#11 , and when <error correction method #4> is used, g1=g1 _{,# 1} in FIG. By setting ₂ , g ₂ =g _2,#2 , g ₃ =g _3,#2 , g ₄ =g _4,#2 , g ₅ =g _5,#2 , g ₆ =g _6,#2 do. Then, it is good if the following is satisfied.

<Condition #H5>

{

{{g _1,#1 ≠g _1,#2 , and g _1,#1 ≠g _2,#2 , and g _1,#1 ≠g _3,#2 }, or {g _{2 ,#1} ≠g _1,#2 , and g _2,#1 ≠g _2,#2 , and g _2,#11 ≠g _3,#2 }, or {g _3,#1 ≠ g _1,#12 , and g3 _,#11 ≠g2 _,#2 , and g3 _,#11 ≠g3 _,#12 } holds},

or,

{{g _4,#1 ≠g _4,#2 , and g _4,#1 ≠g _5,#2 , and g _4,# 1 ≠g _6,#2 }, or {g _{5 ,#1} ≠g _4,#2 , and g _5,#1 ≠g _5,#2 , and g _5,#11 ≠g _6,#2 }, or {g _6,#1 ≠ g _4,#2 , and g6 _,#1 ≠g _5,#2 , and g6 _,#11 ≠g _6,#2 } holds.}

}

is established

By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <Error Correction Method #1> and <Error Correction Method #1> increases (<Error Correction Method #1><Error Correction Method #4>) Since the suitable sets of g ₁ , g ₂ , g ₃ , g ₄ , g ₅ , and g ₆ are different).

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 116 . At this time, when the transmitter of FIG. 122 uses the <error correction method # ₃ >, h ₁ =h _1,#11 , _h2 =h2 _,#11 , h3=h3 _{,#11 ,} h4 =h _4,#11 , h ₅ =h _5,#11 , h ₆ =h _6,#11 , h ₇ =h _7,#11 , h ₈ =h _8,#11 , h ₉ =h _9,# 1 ₁ , h ₁₀ =h _{10,# 11 , h11} =h11 _{,#11 ,} h12 =h12,#11 , h13 =h13,#11 , _h14 = _h14 , _{# 11} and when <error correction method #4> is used, h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 in FIG. , h ₅ =h _5,#2 , h ₆ =h _6,#12 , h ₇ =h _7,#12 , h ₈ =h _8,#12 , h ₉ =h _9,#12 , h ₁₀ =h _{10,#2 ,} h ₁₁ =h _{11,# 12} , h12 =h12 _{,#12 ,} h13 =h13,#12 , _h14 =h14, _{# 12} . Then, it is good if the following is satisfied.

<Condition #H6>

{

{k is an integer greater than or equal to 1 and less than or equal to 7, and h _1,#11 ≠h _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer of 1 or more and 7 or less, and h _2,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _3,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _4,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _5,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h6 _,#11 ≠ _hk,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 7, and h _7,#11 ≠h _k,#2 holds for all k that satisfy it}

}

or,

{

{k is an integer between 8 and 14, and h _8,#11 ≠h _k,# 2 holds for all k satisfying this},

Alternatively, {k is an integer of 8 or more and 14 or less, and h _9,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _10,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _11,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _12,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _13,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _14,#11 ≠h _k,#2 holds for all k that satisfy it}

}

By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <Error Correction Method #1> and <Error Correction Method #1> increases (<Error Correction Method #1><Error Correction Method #4>) As the suitable set of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ , h ₈ , h ₉ , h ₁₀ , h ₁₁ , h ₁₂ , h ₁₃ , h ₁₄ is different in > ).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #3*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #4*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do)

In addition, it is assumed that the 16QAM described in FIG. 114 is used in the transmitter of FIG. 122 . At this time, when the transmitter of FIG. 122 uses the <error correction method #3*>, it is assumed that f ₁ =f _1,#11 , f2 =f2 _, # ₁₁ of FIG. 114 is set, and the <error correction method #1 When 4*> is used, it is assumed that f ₁ =f _1,#12 , f2=f2, _{#12 in} FIG. 114 is set. At this time, it is sufficient if <condition #H4> is satisfied.

It is assumed that the transmitter of FIG. 122 uses the 64QAM described with reference to FIG. 115 . At this time, when the transmitter of FIG. 122 uses the <error correction method # ₃ *>, g ₁ =g _1,#11 , _g2 =g2 _,#11 , g3=g3 _,#11 ,g _{4 =} g _4,#11 , _g5 =g5 _,#11 , _g6 =g6 _,#11 , and when <error correction method # ₄ *> is used, g1=g1 in FIG. 115 _,#2 , g ₂ =g _2,#2 , g ₃ =g _3,#2 , g ₄ =g _4,#2 , g ₅ =g _5,#2 , g ₆ =g _6,#2 do it by doing At this time, it is sufficient if <condition #H5> is satisfied.

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 116 . At this time, when the transmitter of FIG. 122 uses the <error correction method # ₃ *>, h ₁ =h _1,#11 , _h2 =h2 _,#11 , h3=h3 _,#11 ,h ₄ =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11 , using <error correction method #4*> When h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#2 , h in FIG. 116 , It is assumed that ₆ =h _6,#12 , _h7 =h7 _,#12 are set. At this time, it is sufficient if <condition #H6> is satisfied.

<Example 3>

It is assumed that the transmitting apparatus in Fig. 122 can transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #5>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #6>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described with reference to FIG. 119 is used in the transmitter of FIG. 122 . At this time, when the transmitter of FIG. 122 uses the <error correction method #5>, it is assumed that k ₁ =k _1,#11 , k2=k2 _, # ₁₁ of FIG. 119 is set, and the <error correction method #16> When > is used, it is assumed that k ₁ =k _1,#12 , k2=k2, _{#12 in} FIG. 119 is set. At this time,

<Condition #H7>

{k _1,#1 ≠k _1,#2 , or k _2,#11 ≠k _2,#2 } holds

good to go In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > in k ₁ , k ₂ because the suitable sets are different).

It is assumed that the transmitter of FIG. 122 uses the 64QAM described with reference to FIG. 120 . At this time, when the transmitter of FIG. 122 uses the <error correction method #5>, m ₁ =m _{1,#11 ,} m2=m2 _,#11 , _m3 =m3 _{,#11 ,} m4 =m _4,#11 , m ₅ =m _5,#11 , m ₆ =m _6,#11 , m ₇ =m _7,#11 , m8 =m _{8 ,#11} When correction method #6> is used, m ₁ =m _{1,#12 ,} m2 =m2 _,#12 , _m3 =m3 _,#12 , _m4 =m4 _{,#12 ,} m5 = It is assumed that m _5,#2 , m ₆ =m _6,#2 , m ₇ =m _7,#2 , m ₈ =m _8,#2 are set. Then, it is good if the following is satisfied.

<Condition #H8>

{

{{m _1,#1 ≠m _1,#2 , and m _1,#1 ≠m _2,#2 , and m _1,#1 ≠m _3,#2 , and m _{1, #1} ≠m _4,#2 }, or {m _2,#1 ≠m _1,#2 , and m _2,#1 ≠m _2,#2 , and m _2,#1 ≠m _3,#2 , and m _2,#1 ≠m _4,#2 }, or {m _3,#1 ≠m _1,#2 , and m _3,#11 ≠m _2,#2 Also, m _3,#1 ≠m _3,#2 , and m _3,#1 ≠m _4,#2 } or {m _4,#1 ≠m _1,#2 , and m _4,#11 ≠m2 _,#12 , and m4 _,#11 ≠m3 _,#12 , and m4 _,#11 ≠m4 _,#2 } holds},

or,

{{m _5,#1 ≠m _5,#2 , m _5,#1 ≠m _6,#2 , m _5,#11 ≠m _7,#2 , and m _{5, #1} ≠m _8,#2 }, or {m _6,#1 ≠m _5,#2 , and m _6,#1 ≠m _6,#2 , and m _6,#1 ≠m _7,#2 , and m _6,#1 ≠m _8,#2 }, or {m _7,#1 ≠m _5,#2 , and m _7,#11 ≠m _6,#2 and m _7,#11 ≠m _7,#2 , and m _7,#11 ≠m _8,#2 } or {m _8,#11 ≠m _5,#12 , and m _8,#11 ≠m _6,#2 , and m8 _,#11 ≠m7 _,#12, and m8 _,#11 ≠m8 _,#2 } holds.}

}

is established

In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > in m ₁ , m ₂ , m ₃ , m ₄ , m ₅ , m ₆ , m ₇ , m ₈ are different suitable sets).

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 121 . At this time, when the transmitter of FIG. 122 uses <error correction method # ₅ >, n ₁ =n _1,#11 , n2=n2 _,#11 , _n3 =n3 _,#11 , _n4 =n _4,#11 , n ₅ =n _5,#11 , n ₆ =n _6,#11 , n ₇ =n _7,#11 , n ₈ =n _8,#11 , n ₉ =n _9,# 1 ₁ , n ₁₀ =n _10,# 11 , n ₁₁ =n _11,#11 , n ₁₂ =n _12,#11 , n ₁₃ =n _13,#11 , n ₁₄ =n _14,#11 , n ₁₅ = It is assumed that n _15,#11 , _n16 = n16 _,#11 is set, and when <error correction method #6> is used, n ₁ =n _1,#12 , n2=n2, _{# 12} in FIG. , n ₃ =n _3,#2 , n ₄ =n _4,#2 , n ₅ =n _5,#2 , n ₆ =n _6,#2 , n ₇ =n _7,#2 , n ₈ =n _8,#2 , n ₉ =n _9,#2 , n ₁₀ =n _10,#12 , n ₁₁ =n _11,# 12 , n ₁₂ =n _12,#12 , n ₁₃ =n _13,#12 , It is assumed that n ₁₄ = n _{14, #2} , n ₁₅ =n _{15, #2} , n ₁₆ =n _{16, #2} is set. Then, it is good if the following is satisfied.

<Condition #H9>

{

{k is an integer greater than or equal to 1 and less than or equal to 8, and n _1,#11 ≠n _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _2,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _3,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _4,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _5,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _6,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _7,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _8,#11 ≠n _k,#2 holds for all k that satisfy it}

}

or,

{

{ _k is an integer greater than or equal to ₉ and less than or equal to 16;

Alternatively, {k is an integer of 9 or more and 16 or less, and n _10,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _11,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 9 and less than or equal to 16, and n _12,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _13,#1 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _14,#11 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _15,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _16,#11 ≠n _k,#2 holds for all k satisfying it}

}

In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > from n ₁ , n ₂ , n ₃ , n ₄ , n ₅ , n ₆ , n ₇ , n ₈ , n ₉ , n ₁₀ , n ₁₁ , n ₁₂ , n ₁₃ , n ₁₄ , n ₁₅ , n ₁₆ Because the suitable set is different).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #5*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #6*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do).

In addition, it is assumed that the 16QAM described with reference to FIG. 119 is used in the transmitter of FIG. 122 . At this time, when the transmitter of FIG. 122 uses the <error correction method #5*>, it is assumed that k ₁ =k _1,#11 , k ₂ =k2 _, #11 of FIG. 119 is set, and the <error correction method #1 When 6*> is used, it is assumed that k ₁ =k _1,#12 , k2=k2, _{#12 in} FIG. 119 is set. At this time, it is sufficient if <condition #H7> is satisfied.

It is assumed that the transmitter of FIG. 122 uses the 256QAM described with reference to FIG. 121 . _At this time, when the transmitter of FIG. ₁₂₂ uses _the <error correction method _{# 5 *} > ₄ =n _4,#11 , n ₅ =n _5,#11 , n ₆ =n _6,#11 , n ₇ =n _7,#11 , n ₈ =n _8,#11 , n ₉ =n _{9, #1} , n ₁₀ =n _10,# 11 , n ₁₁ =n _11,#11 , n ₁₂ =n _12,#11 , n ₁₃ =n _13,#11 , n ₁₄ =n _14,#11 , n ₁₅ =n _15,#11 , _n16 =n16 _,#11 , and when <error correction method #16*> is used, n ₁ =n _1,#2 , n ₂ =n _{2 in #2} , n ₃ =n _3,#2 , n ₄ =n _4,#12 , n ₅ =n _5,#12 , n ₆ =n _6,#2 , n ₇ =n _7,#12 , n ₈ =n _8,#2 , n ₉ =n _9,#12 , n ₁₀ =n _10,#12 , n ₁₁ =n _11,# 12 , n ₁₂ =n _12,#12 , n ₁₃ =n _{13,#1 2} , n ₁₄ =n _14,#12 , _n15 =n15 _,#12 , _n16 =n16 _,#12 . At this time, it is sufficient if <condition #H9> is satisfied.

In addition, although detailed configuration is omitted in Figs. 122 and 124, it can be implemented similarly when transmitting and receiving a modulated signal by using the OFDM method and spread spectrum communication method described in other embodiments.

In addition, the MIMO transmission method described in the first to twelfth embodiments and space-time codes such as space-time block codes (however, the symbols may be arranged on the frequency axis), precoding In the MIMO transmission method in which , or precoding is not performed, there is a possibility that data reception quality may be improved even if 16QAM, 64QAM, and 256QAM described above are used.

And as described above, when the transmitting device modulates (by executing mapping) and transmits a modulated signal, the transmitting device transmits control information that enables the receiving device to identify the modulation method and parameters of the modulation method, and the receiving device (Fig. 124) obtains this information to enable de-mapping (demodulation).

(Supplementary 6)

Here, the configuration of the communication/broadcasting system using QAM described in (Supplementary 2), (Supplementary 3), and (Supplementary 4), in particular, an example when the MIMO transmission method is used will be described.

125 is an example of a transmitter, and the same numbers are assigned to those operating in the same manner as in FIG. 122 .

The transmission method instruction unit 12202 receives the input signal 12201 as an input, and an information signal 12203 regarding an error correction code for generating a data symbol based on the input signal 12201 (eg, encoding of an error correction code). rate, the block length of the error correction code, etc.), the information signal 12204 about the modulation method (for example, the modulation method), the information signal 12205 of the parameter about the modulation method (for example, the amplitude value in QAM) ) and a transmission method information signal 12505 (information on MIMO transmission, single stream transmission, MISO transmission (transmission using space-time block code), etc.) are output. In addition, the user who uses the input signal 12201 may generate|occur|produce the input signal 12201, and when using it in a communication system, it is good also considering the feedback information of a communication partner as the input signal 12201. In addition, in the present description, MIMO transmission, single stream transmission, and MISO transmission (transmission using space-time block code) can be specified as the transmission method, and the precoding and phase change described in Embodiments 1 to 12 are performed by MIMO transmission. The transmission method is assumed to be handled.

The error correction encoding unit 11702 receives the information 11701 and the information signal 12203 regarding the error correction code as inputs, and performs error correction encoding based on the information signal 12203 on the error correction code to perform error correction encoding. The subsequent data 11703 is output.

The signal processing unit 12501 receives the data after error correction coding 11703, the information signal 12204 related to the modulation method, the information signal 12205 of the parameter related to the modulation method, and the information signal 12505 related to the transmission method as inputs. , on the basis of these signals, interleaving, mapping, precoding, phase change, power change, etc. are executed on the data 11703 after error correction encoding, and the processed baseband signals 12502A and 12502B are output.

The control information symbol generating unit 12207 includes an error correction code information signal 12203, a modulation method information signal 12204, a modulation method parameter information signal 12205, control data 12206, and a transmission method. A control information symbol signal 12208 is outputted by inputting an information signal 12505 regarding

The radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504A based on . In addition, the frame structure is the same as that described with reference to FIG. 126 .

The radio unit 12503B receives the processed baseband signal 12502B, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504B based on . In addition, the frame structure is the same as that described with reference to FIG. 126 .

Next, the operation of the signal processing unit 12501 of FIG. 125 will be described with reference to FIG. 126 .

Fig. 126 is an example of a frame configuration in the vertical axis frequency and horizontal axis time, Fig. 126 (A) is a frame structure of a signal transmitted from antenna #1 (12505A) in Fig. 125, and Fig. 126 (B) is an antenna #1 in Fig. 125. The frame structure of the signal transmitted from 2 (12505B) is shown.

First, the operation of the transmitter in the case of transmitting the pilot symbol 12601, the control information symbol 12602, and the data symbol 12603 in FIG. 126 will be described.

At this time, as a transmission method, one stream of a modulated signal is transmitted from the transmitter of FIG. 125 . In this case, for example, the following first method and second method are conceivable.

Method 1 :

The signal processing unit 12501 receives the data after error correction coding 11703, the information signal 12204 related to the modulation method, the information signal 12205 of the parameter related to the modulation method, and the information signal 12505 related to the transmission method as inputs. , determines a modulation method according to at least the information signal 12204 regarding the modulation method and the information signal 12205 of the parameter regarding the modulation method, performs mapping according to the modulation method, and outputs the processed baseband signal 12502A do. At this time, it is assumed that the processed baseband signal 12502B is not output (in addition, it is assumed that the signal processing unit 12501 also performs processing such as interleaving, for example).

The radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504A based on . In addition, it is assumed that the radio unit 12503B does not operate, and therefore no radio waves are output from the antenna #2 12505B.

As the transmission method, the second method in which a modulated signal of one stream is transmitted from the transmitter of FIG. 125 will be described.

Second method:

The signal processing unit 12501 receives the data after error correction coding 11703, the information signal 12204 related to the modulation method, the information signal 12205 of the parameter related to the modulation method, and the information signal 12505 related to the transmission method as inputs. , determines a modulation method according to at least the information signal 12204 regarding the modulation method and the information signal 12205 of the parameter regarding the modulation method, and performs mapping according to the modulation method to generate a signal after mapping.

Then, the signal processing unit 12501 generates two signals based on the signal after mapping and outputs them as the processed baseband signal 12502A and the processed baseband signal 12502B. In addition, although it is described as "generating two signals based on the signal after mapping", by changing the phase or power to the signal after mapping, two signals based on the signal after mapping are generated. (As described above, the signal processing unit 12501 also performs processing such as interleaving, for example).

The radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504A based on . The radio unit 12503B receives the processed baseband signal 12502B, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504B based on .

Next, in Fig. 126, the operation of the transmitting apparatus when transmitting the pilot symbols 12604A and 12604B, the control information symbols 12605A and 12605B, and the data symbols 12606A and 12606B will be described.

The pilot symbols 12604A and 12604B are symbols transmitted from the transmitter at time Y1 using the same frequency (common frequency).

Similarly, the control information symbols 12505A and 12605B are symbols transmitted using the same frequency (common frequency) from the transmitter at time Y2.

The data symbols 12606A and 12606B are symbols transmitted from the transmitter at times Y3 to Y10 using the same frequency (common frequency).

The signal processing unit 12501 includes space-time codes such as the MIMO transmission method or space-time block codes described in the first to twelfth embodiments (however, the symbols may be arranged on the frequency axis). ), precoding is performed or signal processing is performed according to the MIMO transmission method in which precoding is not performed. In particular, when performing precoding, phase change, and power change, the signal processing unit 12501 includes at least, for example, FIGS. do.

The signal processing unit 12501 receives the data after error correction coding 11703, the modulation method information signal 12204, the modulation method parameter information signal 12205, and the transmission method information signal 12505 as inputs. . In addition, when the information signal 12505 regarding the transmission method is information indicating that "precoding, phase change and power change are performed", the signal processing unit 12501 performs , 98, (or a portion excluding the encoding unit in FIGS. 5, 6, and 7 ) is performed. Accordingly, the signal processing unit 12501 outputs the processed baseband signals 12502A and 12502B (it is assumed that the signal processing unit 12501 also performs interleaving, for example).

The radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504A based on .

The radio unit 12503B receives the processed baseband signal 12502B, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504B based on .

In addition, the structure in the case where the signal processing part 12501 implements the transmission method using space-time block codes (Space-Time BlockCodes) is demonstrated using FIG.

The mapping unit 12802 receives the data signal (data after error correction encoding) 12801 and the control signal 12806 as inputs, and performs mapping based on the information related to the modulation method included in the control signal 12806, A signal 12803 after mapping is output. For example, the signal 12803 after mapping is s0, s1, s2, s3, ... s(2i), s(2i+1), ... It is assumed that they are arranged in the order of (i is an integer greater than or equal to 0).

The MISO (Multiple Input Multiple Output) processing unit 12804 receives the mapped signal 12803 and the control signal 12806 as inputs, and instructs that the control signal 12806 be transmitted in the MISO (Multiple Input Multiple Output) method. In this case, signals 12805A and 12805B after MISO processing are output. For example, the signal 12805A after MISO processing is s0, s1, s2, s3, ... , s(2i), s(2i+1), ... , and the signal 12805B after MISO processing is -s1*, s0*, -s3*, s2*... , -s(2i+1)*, s(2i)*, ... becomes In addition, "*" means a complex conjugate.

At this time, the signals 12805A and 12805B after MISO processing correspond to the baseband signals 12502A and 12502B after processing in Fig. 125, respectively. In addition, the method of the space-time block code is not limited to the above description.

Then, the radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and based on the frame composition signal 12210, A frame-based transmission signal 12504A is output, and the frame-based transmission signal 12504A is output as a radio wave from the antenna #1 12505A.

The radio unit 12503B receives the processed baseband signal 12502B, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504B based on .

127 is a receiving device that receives the modulated signal transmitted by the transmitting device of FIG. 125, and the same numbers are assigned to those operating in the same manner as in FIG.

The synchronization unit 12405 receives the orthogonal baseband signal 11804 as an input and performs frequency synchronization, time synchronization, and frame synchronization by detecting and using, for example, pilot symbols 12601, 12604A, 12604B in FIG. It is output as a synchronization signal 12406.

The control information demodulator 12401 receives the orthogonal baseband signal 12403 and the synchronization signal 12406 as inputs, and performs demodulation (and error correction decoding) of the control information symbols 12602, 12605A, and 1605B in FIG. Thus, a control information signal 12402 is output.

The frequency offset/path estimation unit 12403 receives the orthogonal baseband signal 12403 and the synchronization signal 12406 as inputs, and uses, for example, the pilot symbols 12601, 12604A, and 12604B in FIG. 126 to offset the frequency. and estimating the variation of the transmission path due to radio waves, and outputting a frequency offset and variation estimation signal 12404 of the transmission path.

The radio unit 12703X receives the received signal 12702X received from the antenna #1 12701X as input, performs processing such as frequency conversion, orthogonal demodulation (and Fourier transform), and outputs an orthogonal baseband signal 12704X. do.

Similarly, the radio unit 12703Y receives the received signal 12702Y received from the antenna #2 12701Y as an input, and performs processing such as frequency conversion, orthogonal demodulation (and Fourier transform) to obtain an orthogonal baseband signal 12704Y. to output

The signal processing unit 12705 receives the orthogonal baseband signals 12704X and 12704Y, the control information signal 12402, the frequency offset and transmission path variation estimation signal 12404, and the synchronization signal 12406 as inputs, and receives the control information signal ( 12402) determines the modulation method and transmission method, performs signal processing and demodulation based on them, obtains the log-likelihood ratio of each bit in the data symbol, and outputs a log-likelihood ratio signal 12706 (in addition, the signal processing unit (12705) may perform de-interleaving processing).

The decoding unit 12707 receives the log-likelihood ratio signal 12706 and the control information signal 12402 as inputs, performs error-correction decoding based on the code from the information on the error-correction encoding method included in the control information, and receives it. Output data 12708 .

Hereinafter, an embodiment using the QAM described in (Supplementary 2), (Supplementary 3) and (Supplementary 4) will be described.

<Example 1>

It is assumed that the transmitter in FIG. 125 can transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #1>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #1>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described in FIG. 111 is used in the transmitter of FIG. 125 . At this time, it is assumed that f=f _#1 of FIG. 111 is set when the transmitter of FIG. 125 uses <error correction method #1>, and f=f _#2 of FIG. 111 when <error correction method #12> is used It is supposed to be set to At this time,

<Condition #H10>

In each transmission method corresponding to FIG. 125,

f _#1 ≠1, f _#12 ≠1, and f _#1 ≠f _# 1 hold,

good to do In this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <Error Correction Method #1> <Error Correction Method #1> (<Error Correction Method #1> <Error Correction Method #12>) Because the family register value of f is different in ).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 112 . At this time, when the transmitter of FIG. 125 uses <error correction method #1>, g ₁ =g _{1,#11 , g2} =g2 _,# 11, _g3 =g3,#11 in FIG. It is assumed that when <error correction method # ₂ > is used, g ₁ =g _{1,#12 ,} g2=g2 _,# 12, _g3 =g3,#12 in FIG. 112 are set. Then, it is good if the following is satisfied.

<Condition #H11>

In each transmission method corresponding to FIG. 125, the following holds.

{(g _1,#11 , g2, _# 11, g3 _,#11 )≠(1,3,5), and (g1, _# 11, g2 _,#11 , g3 _,#11 ) )≠(1, 5, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(3,1,5), and (g1 _,#11 ) , g _{2,#11 ,} g3 _,#11 )≠(3, 5, 1), and (g1 _,# 11, g2,#11, g3 _,#11 )≠(5, 1, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(5, 3, 1)}

In addition,

{(g _{1,#2 ,} g2,#2, g3 _,#2 )≠(1, 3, 5), and (g1 _,#2 , g2 _,#2 , g3 _,#2 ) ) ≠ (1, 5, 3), and (g _1,#2 , g _2,#2 , g _3,#2 )≠(3, 1, 5), and (g _1,#2 ) , g _2,#2 , g _3,#2 )≠(3, 5, 1), and (g _1,#2 , g _2,#2 , g _3,#2 )≠(5, 1, 3) and (g _{1,#2 ,} g2,#2 , g3 _,#2 )≠(5, 3, 1)}

In addition,

{{{g _1,#1 ≠g _1,#2 , or g _2,#11 ≠g _2,#2 , or g _3,#11 ≠g _3,#2 } holds}

is established

In this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <Error Correction Method #1><Error Correction Method #1>(<Error Correction Method #1><Error Correction Method #12>) as the suitable sets of g ₁ , g ₂ , and g ₃ are different).

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 113 . At this time, when the transmitter of FIG. 125 uses the <error correction method #1>, h ₁ =h _{1,#11 , h2} =h2 _,# 11, _h3 =h3,# ₁₁ , h4 of FIG. =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11 , even when <error correction method #12> is used h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#2 , h ₆ = It is assumed that h6 _,#12 , _h7 =h7 _,#2 is set. Then, it is good if the following is satisfied.

<Condition #H12>

In each transmission method corresponding to FIG. 125, the following holds.

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {with all x and all y, ax≠ay holds} (h _a1,#11 , h _a2,#11) , h _a3,#11 , h _a4,#11 , h _a5,#11 , h _a6,#11 , h _a7,#11 )≠(1, 3, 5, 7, 9, 11, 13) holds }

In addition,

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {with all x and all y, ax≠ay holds} (h _a1,#2 , h _a2,#2 , h _a3,#2 , h _a4,#2 , h _a5,#2 , h _a6,#2 , h _a7,#2 )≠(1, 3, 5, 7, 9, 11, 13) holds }

In addition,

{{h _1,#1 ≠h _1,#12 , or h _2,#11 ≠h _2,#12 , or h _3,#11 ≠h _3,#12 , or h _4,#11 ≠h _{4 , #2} , or h5 _,#11 ≠h5 _,#12 , or h6 _,#11 ≠h6 _,#12 , or h7 _,#11 ≠h7 _,#12 } holds.}

is established

In this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <Error Correction Method #1><Error Correction Method #1>(<Error Correction Method #1><Error Correction Method #12>) (since the suitable sets of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ are different).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #1*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #2*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do).

In addition, it is assumed that the 16QAM described in FIG. 111 is used in the transmitter of FIG. 125 . At this time, it is assumed that f=f _#1 of FIG. 111 is set when the transmitter of FIG. 125 uses <error correction method #1*>, and f=f of FIG. 111 when <error correction method #2*> is used Suppose it is set to _#2 . At this time, <condition #H10> may be satisfied.

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 112 . At this time, when the transmitter of FIG. 125 uses the <error correction method #1*>, g ₁ =g _{1,#11 , g2} =g2 _,# 11, _g3 =g3,#11 in FIG. When the <error correction method #2*> is used, it is assumed that g ₁ =g _{1, #2} , g ₂ =g _{2, #2} , g ₃ =g _{3, #2} in FIG. 112 is set. At this time, <condition #H11> may be satisfied.

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 113 . At this time, when the transmitter of FIG. 125 uses the <error correction method #1*>, h ₁ =h _1,#11 , _h2 =h2 _,#11 , _h3 =h3 _,#11 , h ₄ =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11, and use <error correction method #2*> When h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#2 , h in FIG. 112 , It is assumed that ₆ =h _6,#12 , _h7 =h7 _,#12 are set. At this time, it is sufficient if <condition #H12> is satisfied.

<Example 2>

It is assumed that the transmitter in FIG. 125 can transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #3>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #4>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described in FIG. 114 is used in the transmitter of FIG. 125 . At this time, it is assumed that f1 = f1, #1, f2 = f2, #1 of FIG. 114 is set when the transmitter of FIG. 125 uses <error correction method #3>, and when <error correction method #4> is used It is assumed that f1 = f1, #2 and f2 = f2, #2 in Fig. 114 are set. At this time,

<Condition #H13>

In each transmission method corresponding to FIG. 125, the following holds.

{f _1,#1 ≠f _1,#2 , or f _2,#11 ≠f _2,#2 } holds,

good to do By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <Error Correction Method #1> and <Error Correction Method #1> increases (<Error Correction Method #1><Error Correction Method #4>) Since the suitable sets of f ₁ , f ₂ are different in >).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 115 . At this time, when the transmitter of FIG. 125 uses <error correction method # ₃ >, g ₁ =g _{1,#11 , g2} =g2, _# 11, g3=g3,# ₁₁ , g4 in FIG. =g _4,#11 , _g5 =g5 _,#11 , _g6 =g6 _,#11 , and when <error correction method #4> is used, g1=g1 _{,# 1} in FIG. By setting ₂ , g ₂ =g _2,#2 , g ₃ =g _3,#2 , g ₄ =g _4,#2 , g ₅ =g _5,#2 , g ₆ =g _6,#2 do. Then, it is good if the following is satisfied.

<Condition #H14>

In each transmission method corresponding to FIG. 125, the following holds.

{

{{g _1,#1 ≠g _1,#2 , and g _1,#1 ≠g _2,#2 , and g _1,#1 ≠g _3,#2 }, or {g _{2 ,#1} ≠g _1,#2 , and g _2,#1 ≠g _2,#2 , and g _2,#11 ≠g _3,#2 }, or {g _3,#1 ≠ g _1,#12 , and g3 _,#11 ≠g2 _,#2 , and g3 _,#11 ≠g3 _,#2 } holds,

or,

{{g _4,#1 ≠g _4,#2 , and g _4,#1 ≠g _5,#2 , and g _4,#1 ≠g _6,#2 }, or {g _{5 ,#1} ≠g _4,#2 , and g _5,#1 ≠g _5,#2 , and g _5,#11 ≠g _6,#2 }, or {g _6,#1 ≠ g _4,#2 , and g6 _,#1 ≠g _5,#2 , and g6 _,#11 ≠g _6,#2 } holds.}

}

is established

By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality increases in either case of <error correction method #13> and <error correction method #14>. (<error correction method #3><error correction method #14> because the suitable set of g ₁ , g ₂ , g ₃ , g ₄ , g ₅ , g ₆ is different).

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 116 . At this time, when the transmitter of FIG. 125 uses the <error correction method # ₃ >, h ₁ =h _{1,#11 , h2} =h2 _,# 11, h3=h3,# ₁₁ , h4 of FIG. =h _4,#11 , h ₅ =h _5,#11 , h ₆ =h _6,#11 , h ₇ =h _7,#11 , h ₈ =h _8,#11 , h ₉ =h _9,# 1 ₁ , h ₁₀ =h _{10,# 11 , h11} =h11 _{,#11 ,} h12 =h12,#11 , h13 =h13,#11 , _h14 = _h14 , _{# 11} and when <error correction method #4> is used, h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 in FIG. , h ₅ =h _5,#2 , h ₆ =h _6,#12 , h ₇ =h _7,#12 , h ₈ =h _8,#12 , h ₉ =h _9,#12 , h ₁₀ =h _{10,#2 ,} h ₁₁ =h _{11,# 12} , h12 =h12 _{,#12 ,} h13 =h13,#12 , _h14 =h14, _{# 12} . Then, it is good if the following is satisfied.

<Condition #H15>

In each transmission method corresponding to FIG. 125, the following holds.

{

{k is an integer greater than or equal to 1 and less than or equal to 7, and h _1,#11 ≠h _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer of 1 or more and 7 or less, and h _2,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _3,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _4,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _5,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h6 _,#11 ≠ _hk,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 7, and h _7,#11 ≠h _k,#2 holds for all k that satisfy it}

}

or,

{{ _k is an integer greater than or equal to ₈ and less than or equal to 14;

Alternatively, {k is an integer of 8 or more and 14 or less, and h _9,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _10,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _11,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _12,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _13,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _14,#11 ≠h _k,#2 holds for all k that satisfy it}

}

By doing in this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <Error Correction Method #1> and <Error Correction Method #1> increases (<Error Correction Method #1><Error Correction Method #4>) As the suitable set of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ , h ₈ , h ₉ , h ₁₀ , h ₁₁ , h ₁₂ , h ₁₃ , h ₁₄ is different in > ).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #3*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #4*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do)

In addition, it is assumed that the 16QAM described in FIG. 114 is used in the transmitter of FIG. 125 . At this time, when the transmitter of FIG. 125 uses the <error correction method #13*>, it is assumed that f ₁ =f _1,#11 , f2=f2 _, # ₁₁ of FIG. 114 is set, and the <error correction method #1 When 4*> is used, it is assumed that f ₁ =f _1,#12 , f2=f2, _{#12 in} FIG. 114 is set. At this time, it is sufficient if <condition #H13> is satisfied.

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 115 . At this time, when the transmitter of FIG. 125 uses the <error correction method # ₃ *>, g ₁ =g _1,#11 , _g2 =g2 _,#11 , g3=g3 _,#11 ,g _{4 =} g _4,#11 , _g5 =g5 _,#11 , _g6 =g6 _,#11 , and when <error correction method # ₄ *> is used, g1=g1 in FIG. 115 _,#2 , g ₂ =g _2,#2 , g ₃ =g _3,#2 , g ₄ =g _4,#2 , g ₅ =g _5,#2 , g ₆ =g _6,#2 do it by doing At this time, it is sufficient if <condition #H14> is satisfied.

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 116 . At this time, when the transmitter of FIG. 125 uses <error correction method # ₃ *>, h ₁ =h _1,#11 , _h2 =h2 _,#11 , h3=h3 _,#11 , ₄ =h _4,#11 , _h5 =h5 _,#11 , _h6 =h6 _,#11 , _h7 =h7 _,#11 , using <error correction method #4*> When h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,# 2, h ₄ =h _4,#2 , h ₅ =h _5,#2 , h in FIG. 116 , It is assumed that ₆ =h _6,#12 , _h7 =h7 _,#12 are set. At this time, it is sufficient if <condition #H15> is satisfied.

<Example 3>

It is assumed that the transmitter in FIG. 125 can transmit a plurality of block lengths (code lengths) with the error correction code.

For example, by selecting either one of error correction encoding using an LDPC (block) code having a block length (code length) of 16200 bits and an error correction encoding using an LDPC (block) code having a block length (code length) of 64800 bits, as shown in FIG. The transmitter shall perform error correction encoding. Therefore, the following two error correction methods are considered.

<Error correction method #5>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 16200 bits (information: 10800 bits, parity: 5400 bits).

<Error correction method #6>

Encoding is performed using an LDPC (block) code with a coding rate of 2/3 and a block length (code length) of 64800 bits (information: 43200 bits, parity: 21600 bits).

In addition, it is assumed that the 16QAM described in FIG. 119 is used in the transmitter of FIG. 125 . At this time, when the transmitter of FIG. 125 uses <error correction method #5>, it is assumed that k ₁ =k _1,#11 , k2 =k2 _, # ₁₁ of FIG. 119 is set, and <error correction method #16> When > is used, it is assumed that k ₁ =k _1,#12 , k2=k2, _{#12 in} FIG. 119 is set. At this time,

<Condition #H16>

In each transmission method corresponding to FIG. 125, the following holds.

{k _1,#1 ≠k _1,#2 , or k _2,#11 ≠k _2,#2 } holds

it's good In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > in k ₁ , k ₂ because the suitable sets are different).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 120 . At this time, when the transmitter of FIG. 125 uses the <error correction method #5>, m ₁ =m _{1,#11 ,} m2=m2 _{,#11 , m3} =m3,# ₁₁ , m4 in FIG. =m _4,#11 , m ₅ =m _5,#11 , m ₆ =m _6,#11 , m ₇ =m _7,#11 , m8 =m _{8 ,#11} When correction method #6> is used, m ₁ =m _{1,#12 ,} m2 =m2 _,#12 , _m3 =m3 _,#12 , _m4 =m4 _{,#12 ,} m5 = It is assumed that m _5,#2 , m ₆ =m _6,#2 , m ₇ =m _7,#2 , m ₈ =m _8,#2 are set. Then, it is good if the following is satisfied.

<Condition #H17>

In each transmission method corresponding to FIG. 125, the following holds.

{

{{m _1,#1 ≠m _1,#2 , and m _1,#1 ≠m _2,#2 , and m _1,#1 ≠m _3,#2 , and m _{1, #1} ≠m _4,#2 }, or {m _2,#1 ≠m _1,#2 , and m _2,#1 ≠m _2,#2 , and m _2,#1 ≠m _3,#2 , and m _2,#1 ≠m _4,#2 }, or {m _3,#1 ≠m _1,#2 , and m _3,#11 ≠m _2,#2 Also, m _3,#1 ≠m _3,#2 , and m _3,#1 ≠m _4,#2 } or {m _4,#1 ≠m _1,#2 , and m _4,#11 ≠m2 _,#12 , and m4 _,#11 ≠m3 _,#12 , and m4 _,#11 ≠m4 _,#2 } holds},

or,

{{m _5,#1 ≠m _5,#2 , m _5,#1 ≠m _6,#2 , m _5,#11 ≠m _7,#2 , and m _{5, #1} ≠m _8,#2 }, or {m _6,#1 ≠m _5,#2 , and m _6,#1 ≠m _6,#2 , and m _6,#1 ≠m _7,#2 , and m _6,#1 ≠m _8,#2 }, or {m _7,#1 ≠m _5,#2 , and m _7,#11 ≠m _6,#2 and m _7,#11 ≠m _7,#2 , and m _7,#11 ≠m _8,#2 } or {m _8,#11 ≠m _5,#12 , and m _8,#1 ≠m _6,#2 , m _8,#1 ≠m _7,#2 , and m _8,#1 ≠m _8,#2 } holds},

}

is established

In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > in m ₁ , m ₂ , m ₃ , m ₄ , m ₅ , m ₆ , m ₇ , m ₈ are different suitable sets).

It is assumed that the 256QAM described in FIG. 121 is used in the transmitter of FIG. 125 . In this case, when the transmitter of FIG. 125 uses the <error correction method # ₅ >, n ₁ =n _1,#11 , n2=n2 _,#11 , _n3 =n3 _,#11 , _n4 =n _4,#11 , n ₅ =n _5,#11 , n ₆ =n _6,#11 , n ₇ =n _7,#11 , n ₈ =n _8,#11 , n ₉ =n _9,# 1 ₁ , n ₁₀ =n _10,# 11 , n ₁₁ =n _11,#11 , n ₁₂ =n _12,#11 , n ₁₃ =n _13,#11 , n ₁₄ =n _14,#11 , n ₁₅ = It is assumed that n _15,#11 , _n16 = n16 _,#11 is set, and when <error correction method #6> is used, n ₁ =n _1,#12 , n2=n2, _{# 12} in FIG. , n ₃ =n _3,#2 , n ₄ =n _4,#2 , n ₅ =n _5,#2 , n ₆ =n _6,#2 , n ₇ =n _7,#2 , n ₈ =n _8,#2 , n ₉ =n _9,#2 , n ₁₀ =n _10,#12 , n ₁₁ =n _11,# 12 , n ₁₂ =n _12,#12 , n ₁₃ =n _13,#12 , It is assumed that n ₁₄ = n _{14, #2} , n ₁₅ =n _{15, #2} , n ₁₆ =n _{16, #2} is set. Then, it is good if the following is satisfied.

<Condition #H18>

In each transmission method corresponding to FIG. 125, the following holds.

{

{k is an integer greater than or equal to 1 and less than or equal to 8, and n _1,#11 ≠n _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer of 1 or more and 8 or less, and n _2,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _3,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _4,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _5,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _6,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _7,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _8,#11 ≠n _k,#2 holds for all k that satisfy it}

}

or,

{

{ _k is an integer greater than or equal to ₉ and less than or equal to 16;

Alternatively, {k is an integer of 9 or more and 16 or less, and n _10,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _11,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 9 and less than or equal to 16, and n _12,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _13,#1 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _14,#11 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _15,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _16,#11 ≠n _k,#2 holds for all k satisfying it}

}

In this way, the possibility that the receiving apparatus can obtain high data reception quality in either case of <error correction method #15> and <error correction method #16> increases (<error correction method #5><error correction method #6>) > from n ₁ , n ₂ , n ₃ , n ₄ , n ₅ , n ₆ , n ₇ , n ₈ , n ₉ , n ₁₀ , n ₁₁ , n ₁₂ , n ₁₃ , n ₁₄ , n ₁₅ , n ₁₆ Because the suitable set is different).

Summarizing the above, it becomes as follows.

Consider the following two error correction methods.

<Error correction method #5*>

Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0).

<Error correction method #6*>

Encoding is performed using a block code with a coding rate A and block length (code length) of C bits (A is a real number, 0<A<1 holds, C is an integer greater than 0, and B≠C holds true) do)

In addition, it is assumed that the 16QAM described in FIG. 119 is used in the transmitter of FIG. 125 . At this time, when the transmitter of FIG. 125 uses <error correction method #5*>, it is assumed that k ₁ =k _1,#11 , k ₂ =k2 _, #11 of FIG. 119 is set, and <error correction method #1> When 6*> is used, it is assumed that k ₁ =k _1,#12 , k2=k2, _{#12 in} FIG. 119 is set. At this time, it is sufficient if <condition #H16> is satisfied.

It is assumed that the 256QAM described in FIG. 121 is used in the transmitter of FIG. 125 . _At this time, when the transmitter _of FIG. 125 uses _the <error correction method _{# 5 *} > ₄ =n _4,#11 , n ₅ =n _5,#11 , n ₆ =n _6,#11 , n ₇ =n _7,#11 , n ₈ =n _8,#11 , n ₉ =n _{9, #1} , n ₁₀ =n _10,# 11 , n ₁₁ =n _11,#11 , n ₁₂ =n _12,#11 , n ₁₃ =n _13,#11 , n ₁₄ =n _14,#11 , n ₁₅ =n _15,#11 , _n16 =n16 _,#11 , and when <error correction method #16*> is used, n ₁ =n _1,#2 , n ₂ =n _{2 in #2} , n ₃ =n _3,#2 , n ₄ =n _4,#12 , n ₅ =n _5,#12 , n ₆ =n _6,#2 , n ₇ =n _7,#12 , n ₈ =n _8,#2 , n ₉ =n _9,#12 , n ₁₀ =n _10,#12 , n ₁₁ =n _11,# 12 , n ₁₂ =n _12,#12 , n ₁₃ =n _{13,#1 2} , n ₁₄ =n _14,#12 , _n15 =n15 _,#12 , _n16 =n16 _,#12 . At this time, it is sufficient if <condition #H18> is satisfied.

In addition, although the detailed configuration is omitted in Figs. 125 and 127, it can be implemented similarly when transmitting and receiving a modulated signal by using the OFDM method and the spread spectrum communication method described in other embodiments.

<Example 4>

As described with reference to FIG. 126, the transmitter of FIG. 125 performs precoding, phase change, and power change when transmitting a signal of one stream using one or more antennas. Transmission method using TimeBlock Codes) is sometimes implemented. It is assumed that the transmitter in Fig. 125 performs the following encoding.

"Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0)."

And define the following.

Transmission method #1: One stream of signals is transmitted using one or more antennas.

Transmission method #2: Execute precoding, phase change and power change.

Transmission method #3: Use Space-Time Block Codes.

In addition, it is assumed that the 16QAM described in FIG. 111 is used in the transmitter of FIG. 125 . At this time, it is assumed that f=f _#1 of FIG. 111 is set when the transmitter of FIG. 125 uses the transmission method #X, and that f=f _# 12 of FIG. 111 is set when the transmission method #Y is used. At this time,

<Condition #H19>

f _#1 ≠1, f _#12 ≠1, and f _#1 ≠f _# 1 hold,

good to do However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Because the family register value of f is different).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 112 . At this time, it is assumed that g ₁ =g _{1,#11 , g2 =} g2,#11, g3=g3,# ₁₁ of FIG. 112 when the transmitter of FIG. 125 uses the transmission method #X, When the transmission method #Y is used, it is assumed that g ₁ =g _{1,#12 , g2 =} g2,#12, g3=g3,# ₁₂ in FIG. 112 is set. Then, it is good if the following is satisfied.

<Condition #H20>

{(g _1,#11 , g2, _# 11, g3 _,#11 )≠(1,3,5), and (g1, _# 11, g2 _,#11 , g3 _,#11 ) )≠(1, 5, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(3,1,5), and (g1 _,#11 ) , g _{2,#11 ,} g3 _,#11 )≠(3, 5, 1), and (g1 _,# 11, g2,#11, g3 _,#11 )≠(5, 1, 3), and (g _{1,#11 ,} g2,#11, g3 _,#11 )≠(5, 3, 1)}

In addition,

{(g _{1,#2 ,} g2,#2, g3 _,#2 )≠(1, 3, 5), and (g1 _,#2 , g2 _,#2 , g3 _,#2 ) ) ≠ (1, 5, 3), and (g _1,#2 , g _2,#2 , g _3,#2 )≠(3, 1, 5), and (g _1,#2 ) , g _2,#2 , g _3,#2 )≠(3, 5, 1), and (g _1,#2 , g _2,#2 , g _3,#2 )≠(5, 1, 3) and (g _{1,#2 ,} g2,#2 , g3 _,#2 )≠(5, 3, 1)}

In addition,

{{{g _1,#1 ≠g _1,#2 , or g _2,#11 ≠g _2,#2 , or g _3,#11 ≠g _3,#2 } holds}

is established However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Since the suitable sets of g ₁ , g ₂ , and g ₃ are different).

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 113 . At this time, when the transmitter of FIG. 125 uses the transmission method #X, h ₁ =h _1,#1 , h ₂ =h _2,#1 , h ₃ =h _3,#1 , h ₄ =h ₄ of FIG. 113 _,#11 , h5 =h5,# ₁₁ ,h6=h6 _{,#11,h7=h7,#11, and when} transmission method _#Y is used, h1 ₌ h _in FIG. _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h _5,#12 , h ₆ =h _6,#2 , It is assumed that h ₇ =h _{7, #2} is set. Then, it is good if the following is satisfied.

<Condition #H21>

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {for all x and all y, ax≠ay holds} (h _a1,#11 , h _a2,#11 , h _a3,#11 , h _a4,#11 , h _a5,#11 , h _a6,#11 , h _a7,#11 )≠(1, 3, 5, 7, 9, 11, 13) holds}

In addition,

{{a1 is an integer of 1 or more and 7 or less, a2 is an integer of 1 or more and 7 or less, a3 is an integer of 1 or more and 7 or less, and a4 is an integer of 1 or more and 7 or less, and a5 is an integer of 1 or more and 7 or less, a6 is an integer of 1 or more and 7 or less, and a7 is an integer of 1 or more and 7 or less}, {x is an integer of 1 or more and 7 or less, and y is an integer of 1 or more and 7 or less, and when x≠y} holds, {for all x and all y, ax≠ay holds} (h _a1,#2 , h _a2,#2 , h _a3,#2 , h _a4,#2 , h _a5,#2 , h _a6,#2 , h _a7,#2 )≠(1, 3, 5, 7, 9, 11, 13) holds}

In addition,

{{h _1,#1 ≠h _1,#12 , or h _2,#11 ≠h _2,#12 , or h _3,#11 ≠h _3,#12 , or h _4,#11 ≠h _{4 , #2} , or h5 _,#11 ≠h5 _,#12 , or h6 _,#11 ≠h6 _,#12 , or h7 _,#11 ≠h7 _,#12 } holds.}

is established However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Since the suitable sets of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ are different).

<Example 5>

When transmitting a signal of one stream using one or more antennas as described with reference to FIG. 126, the transmitter of FIG. 125 performs precoding, phase change, and power change. Space-TimeBlock Codes ) is used in some cases. It is assumed that the transmitter in Fig. 125 performs the following encoding.

"Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0)."

And define the following.

Transmission method #1: One stream of signals is transmitted using one or more antennas.

Transmission method #2: Execute precoding, phase change and power change.

Transmission method #3: Use Space-Time Block Codes.

In addition, it is assumed that the 16QAM described in FIG. 114 is used in the transmitter of FIG. 125 . At this time, it is assumed that f ₁ =f _1,#11 , f2=f2 _, # ₁₁ of FIG. 114 is set when the transmission apparatus of FIG. 125 uses the transmission method #X, and when the transmission method #Y is used, FIG. 114 It is assumed that f ₁ =f _{1,#12 ,} f2=f2 _,#12 is set. At this time,

<Condition #H22>

{f _1,#11 ≠f1 _,#12 , or f2 _,#11 ≠f2 _,#12 } may hold. However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Since the suitable sets of f ₁ and f ₂ are different).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 115 . At this time, when the transmitter of FIG. 125 uses the transmission method #X, g ₁ =g _{1,#11 , g2 =} g2,# ₁₁ , g3=g3, _{# 11} , g4=g4 in FIG. _{,#11 ,} g5=g5,#11,g6=g6,# ₁₁ , and when the transmission method #Y is used, g1=g1 _{, #12 ,} g2 ₌ g _in FIG. 115 It is assumed that 2,# ₂ , g3 =g3, _{# 2} , g4=g4, _{# 2} , g5=g5 _{,#2 , g6} =g6 _,#2 are set. Then, it is good if the following is satisfied.

<Condition #H23>

{{{g _1,#1 ≠g _1,#2 , and g _1,#1 ≠g _2,#2 , and g _1,#11 ≠g _3,#2 }, or {g _2,#11 ≠g _1,#12 , and g _2,#11 ≠g _2,#12 , and g2 _,#11 ≠g _3,#12 }, or {g _3,#1 ≠g _1,#2 , and g3 _,#11 ≠g2 _,#2 , and g3 _,#11 ≠g3 _,#2 } holds},

or,

{{g _4,#1 ≠g _4,#2 , and g _4,#1 ≠g _5,#2 , and g _4,#1 ≠g _6,#2 }, or {g _{5 ,#1} ≠g _4,#2 , and g _5,#1 ≠g _5,#2 , and g _5,#11 ≠g _6,#2 }, or {g _6,#1 ≠ g _4,#2 , and g6 _,#1 ≠g _5,#2 , and g6 _,#11 ≠g _6,#2 } holds.}}

but it works However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Since the suitable sets of g ₁ , g ₂ , g ₃ , g ₄ , g ₅ , and g ₆ are different).

It is assumed that the transmitter of FIG. 125 uses the 256QAM described with reference to FIG. 116 . At this time, when the transmitting apparatus of FIG. 125 uses the transmission method #X, h ₁ =h _{1,#11 , h2 =} h2,# ₁₁ , h3=h3, _{# 11} , h4=h4 of FIG. _,#11 , h ₅ =h _5,#11 , h ₆ =h _6,#11 , h ₇ =h _7,#11 , h ₈ =h _8,#11 , h ₉ =h _9,#11 , h ₁₀ =h _{10,# 11 , h11} =h11 _{,#11 ,} h12 =h12,#11 , h13 =h13,#11 , _h14 = _h14 , _{# 11} When method #Y is used, h ₁ =h _1,#2 , h ₂ =h _2,#2 , h ₃ =h _3,#2 , h ₄ =h _4,#2 , h ₅ =h ₅ in FIG. _,#2 , h ₆ =h _6,#2 , h ₇ =h _7,#2 , h ₈ =h _8,#2 , h ₉ =h _9,#2 , h ₁₀ =h _10,#2 , h ₁₁ =h _{11,# 12 ,} h12=h12 _,#12, h13=h13,#12, _h14 =h14, _{# 12} . Then, it is good if the following is satisfied.

<Condition #H24>

{

{k is an integer greater than or equal to 1 and less than or equal to 7, and h _1,#11 ≠h _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer of 1 or more and 7 or less, and h _2,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _3,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _4,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h _5,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 1 or more and 7 or less, and h6 _,#11 ≠ _hk,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 7, and h _7,#11 ≠h _k,#2 holds for all k that satisfy it}

}

or,

{

{ _k is an integer greater than or equal to ₈ and less than or equal to 14;

Alternatively, {k is an integer of 8 or more and 14 or less, and h _9,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _10,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _11,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _12,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _13,#11 ≠h _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 8 or more and 14 or less, and h _14,#11 ≠h _k,#2 holds for all k that satisfy it}

}

However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Because the suitable sets of h ₁ , h ₂ , h ₃ , h ₄ , h ₅ , h ₆ , h ₇ , h ₈ , h ₉ , h ₁₀ , h ₁₁ , h ₁₂ , h ₁₃ , h ₁₄ are different).

<Example 6>

When transmitting a signal of one stream using one or more antennas as described with reference to FIG. 126, the transmitter of FIG. 125 performs precoding, phase change, and power change. Space-TimeBlock Codes ) is used in some cases. It is assumed that the transmitter in Fig. 125 performs the following encoding.

"Encoding is performed using a block code with a coding rate A and block length (code length) B bits (A is a real number, 0<A<1 holds, and B is an integer greater than 0)."

And define the following.

Transmission method #1: One stream of signals is transmitted using one or more antennas.

Transmission method #2: Execute precoding, phase change and power change.

Transmission method #3: Use Space-Time Block Codes.

In addition, it is assumed that the 16QAM described in FIG. 119 is used in the transmitter of FIG. 125 . At this time, it is assumed that k ₁ =k _1,#1 , k ₂ =k _2,#11 of FIG. 119 is set when the transmitting apparatus of FIG. 125 uses the transmission method #X, and FIG. 119 when the transmission method #Y is used It is assumed that k ₁ =k _1,#2 , k ₂ =k _2,#2 is set. At this time,

<Condition #H25>

{k _1,#1 ≠k _1,#2 , or k _2,#11 ≠k _2,#2 } holds

good to do However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Since the suitable sets of k ₁ and k ₂ are different).

It is assumed that the transmitter of FIG. 125 uses the 64QAM described with reference to FIG. 120 . At this time, when the transmission apparatus of FIG. 125 uses the transmission method #X, m ₁ =m _1,#1, m ₂ =m _2,#11 , m ₃ =m _3,#11 , m ₄ =m ₄ of FIG. _,#11 , m ₅ =m _5,#11 , m ₆ =m _6,#11 , m ₇ =m _7,#11 , _m8 =m8 _,#11 When used, m ₁ =m _1,#2 , m ₂ =m _2,#2 , m ₃ =m _3,#2 , m ₄ =m _4,#2 , m ₅ =m _5,#2 in FIG. It is assumed that m ₆ =m _6,#2 , m ₇ =m _7,#2 , m ₈ =m _8,#2 is set. Then, it is good if the following is satisfied.

<Condition #H26>

{

{{m _1,#1 ≠m _1,#2 , and m _1,#1 ≠m _2,#2 , and m _1,#1 ≠m _3,#2 , and m _{1, #1} ≠m _4,#2 }, or {m _2,#1 ≠m _1,#2 , and m _2,#1 ≠m _2,#2 , and m _2,#1 ≠m _3,#2 , and m _2,#1 ≠m _4,#2 }, or {m _3,#1 ≠m _1,#2 , and m _3,#11 ≠m _2,#2 Also, m _3,#1 ≠m _3,#2 , and m _3,#1 ≠m _4,#2 } or {m _4,#1 ≠m _1,#2 , and m _4,#11 ≠m2 _,#12 , and m4 _,#11 ≠m3 _,#12 , and m4 _,#11 ≠m4 _,#2 } holds},

or,

{{m _5,#1 ≠m _5,#2 , m _5,#1 ≠m _6,#2 , m _5,#11 ≠m _7,#2 , and m _{5, #1} ≠m _8,#2 }, or {m _6,#1 ≠m _5,#2 , and m _6,#1 ≠m _6,#2 , and m _6,#1 ≠m _7,#2 , and m _6,#1 ≠m _8,#2 }, or {m _7,#1 ≠m _5,#2 , and m _7,#11 ≠m _6,#2 and m _7,#11 ≠m _7,#2 , and m _7,#11 ≠m _8,#2 } or {m _8,#11 ≠m _5,#12 , and m _8,#1 ≠m _6,#2 , m _8,#1 ≠m _7,#2 , and m _8,#1 ≠m _8,#2 } holds},

}

is established However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) Because the suitable sets of m ₁ , m ₂ , m ₃ , m ₄ , m ₅ , m ₆ , m ₇ , m ₈ are different).

It is assumed that the 256QAM described in FIG. 121 is used in the transmitter of FIG. 125 . At this time, when the transmitter of FIG. 125 uses the transmission method #X, n ₁ =n _{1,#11 , n2} =n2, _{# 11} , n3=n3,#11, _n4 = _n4 of FIG. _,#11 , n ₅ =n _5,#11 , n ₆ =n _6,#11 , n ₇ =n _7,#11 , n ₈ =n _8,#11 , n ₉ =n _9,#11 , n ₁₀ =n _10,# 11 , n ₁₁ =n _11,#11 , n ₁₂ =n _12,#11 , n ₁₃ =n _13,#11 , n ₁₄ =n _14,#11 , n ₁₅ =n _15, It is assumed that _#1 , n ₁₆ =n _{16, #1} is set, and when transmission method #Y is used, n ₁ =n _{1, #2} , n ₂ =n _{2, #2} , n ₃ =n ₃ in FIG. 121 _,#2 , n ₄ =n _4,#2 , n ₅ =n _5,#12 , n ₆ =n _6,#12 , n ₇ =n _7,#2 , n ₈ =n _8,#12 , n ₉ =n _9,#2 , n ₁₀ =n _10,#12 , n ₁₁ =n _11,# 12 , n ₁₂ =n _12,#12 , n ₁₃ =n _13,#12 , n ₁₄ =n _14, It is assumed that _#2 , n ₁₅ =n _{15, #2} , n ₁₆ =n _{16, #2} is set. Then, it is good if the following is satisfied.

<Condition #H27>

{

{k is an integer greater than or equal to 1 and less than or equal to 8, and n _1,#11 ≠n _k,#2 holds for all k that satisfy it},

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _2,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _3,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _4,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _5,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and _n6,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _7,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 1 and less than or equal to 8, and n _8,#11 ≠n _k,#2 holds for all k that satisfy it}

}

or,

{

{ _k is an integer greater than or equal to ₉ and less than or equal to 16;

Alternatively, {k is an integer of 9 or more and 16 or less, and n _10,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _11,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer greater than or equal to 9 and less than or equal to 16, and n _12,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _13,#1 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _14,#11 ≠n _k,#2 holds for all k satisfying it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _15,#11 ≠n _k,#2 holds for all k that satisfy it}

Alternatively, {k is an integer of 9 or more and 16 or less, and n _16,#11 ≠n _k,#2 holds for all k satisfying it}

}

However, (X, Y) = (1, 2) or (1, 3) or (2, 3).

In this way, the possibility that the receiving apparatus can obtain high data reception quality both when the transmission method #X is used and when the transmission method #Y is used increases (when the transmission method #1X is used and the transmission method #Y is used) suitable for n ₁ , n ₂ , n ₃ , n ₄ , n ₅ , n ₆ , n ₇ , n ₈ , n ₉ , n ₁₀ , n ₁₁ , n ₁₂ , n ₁₃ , n ₁₄ , n ₁₅ , n ₁₆ different sets).

In addition, although the detailed configuration is omitted in Figs. 125 and 127, it can be implemented similarly when transmitting and receiving a modulated signal by using the OFDM method and the spread spectrum communication method described in other embodiments.

And as described above, when the transmitting device modulates (by executing mapping) and transmits a modulated signal, the transmitting device transmits control information that enables the receiving device to identify the modulation method and parameters of the modulation method, and the receiving device (Fig. 127) enables signal detection and de-mapping (demodulation) by obtaining this information.

(Supplementary 7)

Of course, you may implement by combining the embodiment demonstrated in this specification, and a plurality of supplementary contents.

In addition, each embodiment and supplementary contents are examples to the last, and even if "modulation method, error correction encoding method (error correction code used, code length, encoding rate, etc.), control information, etc." are exemplified, for example. In the case of applying other "modulation method, error correction coding method (error correction code used, code length, coding rate, etc.), control information, etc.", the same configuration can be implemented.

As for the modulation method, the embodiment and supplementary contents described in this specification can be implemented even if a modulation method other than the modulation method described in this specification is used. For example, Amplitude Phase Shift Keying (APSK) (eg 16APSK, 64APSK, 128APSK, 256APSK, 1024APSK, 4096APSK, etc.), Pulse Amplitude Modulation (PAM) (eg 4PAM, 8PAM, 16PAM, 64PAM, 128PAM, 256PAM, 1024PAM, 4096 PAM, etc.), Phase Shift Keying (PSK) (eg BPSK, QPSK, 8PSK, 16PSK, 64PSK, 128PSK, 256PSK, 1024PSK, 4096 PSK, etc.), Quadrature Amplitude Modulation (QAM) (eg 4QAM, 8QAM, 16QAM, 64QAM, 128QAM, 256QAM, 1024QAM, 4096QAM, etc.) may be applied, or uniform mapping or non-uniform mapping may be used in each modulation method.

Also, the arrangement method of 2, 4, 8, 16, 64, 128, 256, 1024, etc. signal points in the I-Q plane (2, 4, 8, 16, 64) A modulation method having signal points (eg, 128, 256, 1024, etc.) may be switched according to time, frequency, or time and frequency.

In the present specification, a configuration for executing power change, precoding (weighted synthesis), phase change, power change, etc. processing for the modulated signal s1 according to the first modulation method and s2 according to the second modulation method (for example, FIG. 5 ) , 6, 7, 97, 98) have been described. Instead of these processes, the processes described below may be performed to implement each embodiment of the present specification. Hereinafter, the processing method will be described.

129 and 130 are "a configuration for executing power change, precoding, phase change, power change, etc. processing on the modulation signal s1 according to the first modulation method and s2 according to the second modulation method" described in this specification This is a variant example.

129 and 130 have a configuration in which a phase change unit is added before weighted synthesis (precoding). Incidentally, the same reference numerals are assigned to those operating in the same manner as in Figs. 5, 6, and 7, and the detailed operation is omitted.

The phase change unit 12902 of FIG. 129 performs a phase change process on the modulated signal 12901 output from the mapping unit 504 so that its phase is different from that of the other modulated signal 505A, and the modulated signal after the phase change s2(t) 505B is output to the power change unit 506B.

The phase change unit 13002 of FIG. 130 performs a phase change process on the modulated signal 13001 output from the mapping unit 504 so that the phase is different from that of the other modulated signal 505A, and the modulated signal s2 after the phase change (t) 505B is output to the power change unit 506B.

131 is a modified example of the configuration example of the transmitter shown in FIG. 132 is a modified example of the configuration example of the transmitter shown in FIG.

The phase change unit 13102 of FIG. 131 performs a second phase change process with respect to the first phase change process performed by the phase change unit 12902 on the modulated signal 13101 output from the mapping unit 504, The modulated signal s1(t) 505A after the phase change is output to the power change unit 506A.

The phase change unit 13202 of FIG. 132 performs a second phase change process with respect to the first phase change process performed by the phase change unit 13002 on the modulated signal 13201 output from the mapping unit 504, The modulated signal s1(t) 505A after the phase change is output to the power change unit 506A.

As shown in Figs. 131 and 132, the phase change may be performed not only on one of the modulated signals output from the mapping unit, but on both signals.

Incidentally, the phase change processing of the phase change units 12902, 13002, 13102, and 13202 can be expressed by the following equation.

Here, λ(i) is a phase, λ(i) is a function of i (eg time, frequency, slot), and I and Q are the in-phase I component and quadrature Q component of the input signal, respectively, and the phase change Sections 12902, 13002, 13102, 13202 output I', Q'.

Also, of course, the receiving device receiving the modulated signal transmitted using FIGS. 129, 130, 131, and 132 performs signal processing corresponding to the signal processing described above, and an example of each bit included in the modulated signal For example, the log-likelihood ratio is obtained.

Also, the arrangement method of 2, 4, 8, 16, 64, 128, 256, 1024, etc. signal points in the I-Q plane (2, 4, 8, 16, 64) A modulation method having signal points (eg, 128, 256, 1024, etc.) is not limited to the method of arranging signal points of the modulation method described in this specification. Accordingly, a function of outputting an in-phase component and a quadrature component based on a plurality of bits becomes a function in the mapping unit, and then performing precoding and phase change becomes one effective function of the present invention.

In this embodiment, the embodiment when the precoding weight and phase are changed on the time axis has been described, but as described in Embodiment 1, this embodiment can be implemented in the same way even when a multi-carrier transmission method such as OFDM transmission is used. have. In particular, when the precoding switching method is changed depending on the number of transmission signals, the reception apparatus can know the method of switching the precoding weight and phase by obtaining information on the number of transmission signals transmitted by the transmission apparatus.

In this specification, it is conceivable that communication and broadcasting equipment such as a broadcasting station, a base station, an access point, a terminal, and a mobile phone are provided with the transmitter in the present specification. , a radio, a terminal, a personal computer, a mobile phone, an access point, a communication device such as a base station can be considered. In addition, the transmitter and receiver in the present invention are devices equipped with a communication function, and the device is capable of deciphering and connecting an interface to a device for executing applications such as television, radio, personal computer, and mobile phone. The form can also be considered.

In this embodiment, symbols other than data symbols, for example, pilot symbols (preamble, unique word, postamble, reference symbol, etc.), control information symbols, etc. may be arranged in a frame. In addition, although it is called a pilot symbol and a symbol for control information here, it may be called whatever it is, and the function itself is important.

The pilot symbol may be, for example, an existing symbol modulated using PSK modulation in the transceiver (or the receiver may know the symbol transmitted by the transmitter by synchronizing the receiver), and the receiver uses this symbol to Frequency synchronization, time synchronization, channel estimation (of each modulated signal) (estimation of CSI (Channel State Information)), signal detection, and the like are performed.

In addition, the symbol for control information is information that needs to be transmitted to the communication partner for realizing communication other than data (such as application) (for example, the modulation method, error correction encoding method, error correction encoding used for communication). It is a symbol for transmitting the encoding rate of the method, setting information in the upper layer, etc.).

In addition, this invention is not limited to each embodiment, It can change and implement variously. For example, in each embodiment, the case of implementation as a communication device is described, but the present invention is not limited thereto, and this communication method can also be implemented as software.

In addition, in the above, the precoding switching method in the method of transmitting two modulated signals from two antennas has been described, but the present invention is not limited thereto. The same precoding weight (matrix) is changed in the method of generating and transmitting from 4 antennas, that is, performing precoding on N mapped signals to generate N modulated signals and transmitting from N antennas. It can be implemented similarly also as a precoding switching method.

Although terms such as "precoding" and "precoding weight" are used in this specification, the name itself may be any, and in the present invention, the signal processing itself is important.

Different data may be transmitted according to the streams s1(t) and s2(t), or the same data may be transmitted.

One antenna described in the drawings may be constituted by a plurality of antennas for both the transmitting antenna of the transmitting apparatus and the receiving antenna of the receiving apparatus.

In some embodiments, it is necessary to notify the transmitting apparatus and the receiving apparatus of the transmission method (MIMO, SISO, space-time block code, interleaved method), the modulation method, and the error-correction encoding method in the frame transmitted by the omitted transmitting apparatus. The receiving device that comes into existence will change its behavior by obtaining it.

In Embodiments 1 to 11, the bit length adjustment method has been described, and in Embodiment 12, the case where the bit length adjustment method of Embodiments 1 to 11 is applied to the DVB standard has been described. At this time, for the bit length adjustment method in the transmitting device, Figs. 57, 60, 73, 78, 79, 80, 83, 91, 93, etc. are used, and the operation in the receiving device is described in the first to twelfth embodiments using Figs. 85, 87, 88, 96, and the like. And the MIMO transmission method (using precoding (weighted synthesis), power change, phase change, etc.) will be described in Embodiments 1 to 12 using FIGS. 5, 6, 7, 97, 98, etc. are doing

At this time, after the bit length adjustment process described in Embodiments 1 to 12, the MIMO transmission method (precoding (weighted synthesis)) described in FIGS. 5, 6, 7, 97, and 98 as a transmission method, Instead of using power change, phase change, etc.), the space-time block code, space-frequency block code (which arranges symbols in the frequency direction), (the MISO transmission method, sometimes called transmit diversity) described in FIG. Embodiments 1 to 12 can be implemented also in the case. That is, a bit sequence (digital signal) whose bit length is adjusted using FIGS. 57, 60, 73, 78, 79, 80, 83, 91, 93, etc. corresponds to 1201 in FIG. 128 After that, mapping/MISO processing is performed as shown in FIG. 128 .

In addition, the methods of space-time block code, space-frequency block code (symbols are arranged in the frequency direction), and (MISO transmission method, sometimes called transmit diversity) are not limited to FIG. 128, but as shown in FIG. 133 You may send FIG. 133 will be described (in addition, since FIG. 133 operates in the same manner as in FIG. 128, the same numbers are assigned).

The mapping unit 12802 receives the data signal (data after error correction encoding) 12801 and the control signal 12806 as inputs, and performs mapping based on the information related to the modulation method included in the control signal 12806, A signal 12803 after mapping is output. For example, the signal 12803 after mapping is s0, s1, s2, s3, ... , s(2i), s(2i+1), ... It is assumed that they are arranged in the order of (i is an integer greater than or equal to 0).

The MISO (Multiple Input Multiple Output) processing unit 12804 receives the mapped signal 12803 and the control signal 12806 as inputs, and instructs the control signal 12806 to be transmitted in the MISO (Multiple Input Multiple Output) method. In this case, signals 12805A and 12805B after MISO processing are output. For example, the signal 12805A after MISO processing is s0, -s1*, s2, -s3*, ... , s(2i), -s(2i+1)*, ... , and the signal 12805B after MISO processing is s1, s0*, s3, s2*... , s(2i+1), s(2i)*, ... becomes In addition, "*" means a complex conjugate.

At this time, the signals 12805A and 12805B after MISO processing correspond to the baseband signals 12502A and 12502B after processing in Fig. 125, respectively. In addition, the method of the space-time block code is not limited to the above description. Then, the radio unit 12503A receives the processed baseband signal 12502A, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and based on the frame composition signal 12210, A frame-based transmission signal 12504A is output, and the frame-based transmission signal 12504A is output as a radio wave from the antenna #1 12505A.

The radio unit 12503B receives the processed baseband signal 12502B, the control symbol signal 12208, the pilot symbol signal 12209, and the frame composition signal 12210 as inputs, and receives a frame based on the frame composition signal 12210. A transmission signal 12504B based on .

Embodiments 1 to 11 describe the bit length adjustment method, and in Embodiment 12, the case where the bit length adjustment method of Embodiments 1 to 11 is applied to the DVB standard has been described. At this time, for the bit length adjustment method in the transmitting device, Figs. 57, 60, 73, 78, 79, 80, 83, 91, 93, etc. are used, and the operation in the receiving device is described in the first to twelfth embodiments using Figs. 85, 87, 88, 96, and the like. And the MIMO transmission method (using precoding (weighted synthesis), power change, phase change, etc.) will be described in Embodiments 1 to 12 using Figs. 5, 6, 7, 97, 98, etc. are doing

At this time, after the bit length adjustment process described in Embodiments 1 to 12, the MIMO transmission method (precoding (weighted synthesis)) described in FIGS. 5, 6, 7, 97, and 98 as a transmission method, Instead of using power change, phase change, etc.), it becomes possible to implement Embodiments 1 to 12 also in the case of single-stream transmission.

That is, the bit sequence (digital signal) whose bit length is adjusted using FIGS. 57, 60, 73, 78, 79, 80, 83, 91, 93, etc. is shown in FIGS. 5, 6, and It corresponds to the bit series 503 of 7 or the bit series 9701 of Figs. 97 and 98, and is input to the mapping unit 504 of Figs. do.

The modulation method α of s1(t) is a modulation method for transmitting x-bit data, and no data is transmitted in s2(t) (no modulation, y=0-bit data transmission). Therefore, x + y = x + 0 = x described in this specification. In Embodiments 1 to 12, if "x+y=x+0=x" is implemented, it becomes possible to implement Embodiments 1 to 12 also in the case of single-stream transmission.

(Supplementary 8)

Although the matrix F for weighting synthesis (precoding) is shown in this specification, each embodiment of this specification can be implemented also using the precoding matrix F (or F(i)) as described below.

or,

or,

or,

or,

or,

or,

or,

In addition, in formulas (H10), (H11), (H12), (H13), (F14), (H15), (H16), and (H17), α may be a real number or an imaginary number. good, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero).

or,

or,

or,

or,

or,

or,

or,

or,

Further, in the formulas (H18), (H20), (H22), and (H24), β may be a real number or an imaginary number. However, β is not 0 (zero).

or,

or,

or,

or,

or,

or,

or,

or,

or,

or,

or,

or,

However, θ ₁₁ (i), θ ₂₁ (i), and λ (i) are functions of i (time or frequency), λ is a fixed value, α may be a real number or an imaginary number, and β may be a real number good and imaginary is good However, α is not 0 (zero). And β is also not 0 (zero).

Moreover, each embodiment of this specification can be implemented also even if it uses precoding matrices other than these.

The present invention can be widely applied to a wireless system that transmits different modulated signals from a plurality of antennas. It is also applicable to the case of performing MIMO transmission in a wired communication system having multiple transmission points (eg, PLC (Power Line Communication) system, optical communication system, DSL (Digital SubscriberLine) system). have.

The present invention can be widely applied to a wireless system that transmits different modulated signals from a plurality of antennas. Also, it can be applied to the case of performing MIMO transmission in a wired communication system having multiple transmission points (eg, PLC (Power Line Communication) system, optical communication system, DSL (Digital SubscriberLine) system). have.

502, 502LA encoder
502BI bit interleaver
5701, 6001, 7301, 8001 bit length adjustment unit
504 mapping unit

Claims (1)

As a transmission method for data communication,
encoding the first information using the first encoding rate and the first code length to generate a first encoded data series;
generating a second encoded data series by encoding second information using the first encoding rate and a second code length different from the first code length;
A first modulation symbol sequence is generated by mapping the first encoded data sequence to 16 signal points determined by a first 16QAM (Quadrature Amplitude Modulation) scheme,
generating a second modulation symbol sequence by mapping the second encoded data sequence to 16 signal points determined by the second 16QAM scheme;
generating a first OFDM (Orthogonal Frequency Division Multiplexing) symbol based on the first modulation symbol sequence;
generating a second OFDM symbol based on the second modulation symbol sequence;
Transmitting a signal generated based on the first OFDM symbol and the second OFDM symbol,
The 16 signal points determined by the first 16QAM method and the 16 signal points determined by the second 16QAM method are within the first upper limit in the I/Q plane having real and imaginary axes. a plurality of first signal points adjacent to each other and a plurality of second signal points adjacent to each other, wherein a first distance between the first signal points and a second distance between the second signal points are different;
The 16 signal points determined by the first 16QAM scheme have a first arrangement pattern in the I/Q plane,
The 16 signal points determined by the second 16QAM scheme have a second configuration pattern different from the first configuration pattern in the I/Q plane.

Images