KR102264561B1 - Apparatus and method for controlling power of three phase dual active bridge converter - Google Patents

Abstract

And a comparator for comparing an output voltage (V _out) and a predetermined reference voltage (V _{out_ref)} provided from the output of the three-phase dual-active-bridge converter according to the invention, on the basis of the output voltage and output current, output power (P _o ), a mode selection unit for selecting one of a plurality of preset control modes as a voltage control mode based on the calculated output power (P _{o ), and charging according to the comparison result in the comparator} a control signal generator generating a control signal for controlling the output voltage based on the selected voltage control mode when the mode or the discharging mode is performed; and the three-phase dual active bridge converter based on the generated control signal and a power control device for a three-phase dual active bridge converter including a converter driver controlling output voltage generation in the .

Description

Power control device and method for 3-phase dual active bridge converter {APPARATUS AND METHOD FOR CONTROLLING POWER OF THREE PHASE DUAL ACTIVE BRIDGE CONVERTER}

The present invention relates to a technique for controlling the power of a three-phase dual active bridge converter, and more particularly, the efficiency of the converter in the DC microgrid application field based on power electronics technology. It relates to a power control apparatus and method for a three-phase dual active bridge converter that can be improved.

As is known, in the case of the conventional three-phase DAB (Dual Active Bridge) converter, the current is divided into three phases and flows, so compared to the conventional single-phase DAB converter, it is widely used in high-power and high-current bidirectional topology applications.

And, in the case of the conventional three-phase DAB converter, since it is a method of transferring power in both directions using a phase shift method, zero voltage switching is possible without an additional circuit, which can have an advantage in terms of switching loss.

However, according to the analysis of the existing three-phase DAB converter, the parasitic capacitor effect of the switch is not considered.

Considering the above points, if the conventional three-phase DAB converter uses the phase shift method, in theory, zero voltage switching is possible in all areas when the turn ratio is 1:1, but considering the effect of the parasitic capacitor, There is a problem in that zero voltage switching is not possible at a low load, and zero voltage switching is possible only at a certain load or higher.

In addition, the conventional three-phase DAB converter has a problem in that efficiency is lowered when only the phase shift method is used because zero voltage switching is more difficult when the turn ratio is not 1:1.

And, in the case of a conventional single-phase DAB converter, it is possible to reduce the low-load loss by using an extended phase shift (EPS) or a triangular control method (TRM), but in the case of a three-phase DAB converter, between the legs There is a problem in that it is difficult to use the existing method because the phase has already been shifted by 120 degrees and the zero vector also exists.

Korean Patent No. 10-1786904 (Announcement Date: 2017. 11. 15.)

The present invention is to provide a power control device and method for a three-phase dual active bridge converter capable of increasing a zero voltage switching area while enabling zero current switching by applying a technique for controlling a phase and a duty ratio. do.

An object of the present invention is to provide an apparatus and method for controlling power of a three-phase dual active bridge converter capable of improving low-load efficiency compared to the prior art using only an algorithm without an additional circuit.

The problem to be solved by the present invention is not limited to those mentioned above, and another problem to be solved that is not mentioned can be clearly understood by those of ordinary skill in the art to which the present invention belongs from the following description. will be.

_{According to one aspect, the present invention provides a comparator for comparing an output voltage (V out} ) provided from an output of a three-phase dual active bridge converter with a preset reference voltage (V _{out_ref} ), and based on the output voltage and the output current, the output power (P _o) the calculated power calculation unit and calculating said output power (P _o) and a plurality of control modes of the mode selector for selecting one of a voltage control mode part preset on the basis of, in said comparator a control signal generator generating a control signal for controlling the output voltage based on the selected voltage control mode when the charging mode or the discharging mode is performed according to the comparison result; It is possible to provide an apparatus for controlling power of a three-phase dual active bridge converter including a converter driver for controlling generation of an output voltage in the phase dual active bridge converter.

The control signal generator of the present invention performs the charging mode when the phase value output from the comparator is a positive value (+), and performs the discharging mode when the phase value is a negative value (-) can

The control signal generator of the present invention may generate a control signal for controlling the output voltage through duty control or phase control.

The control signal generator of the present invention, when the phase (φ) of _{the output voltage (V out ) is less than a preset minimum phase (φ min} ), a control signal for controlling the output voltage through duty control If the first PI (Proportional-Integral) controller for generating and the phase (φ) of _{the output voltage (V out ) is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is less than or equal to a preset reference , a second PI controller for generating a control signal for controlling the output voltage through duty control, and a phase (φ) of _{the output voltage (V out} ) is greater than the _{preset minimum phase (φ min )} , when the fertilization ratio (D) is greater than or equal to a preset reference value, a third PI controller that generates a control signal for controlling the output voltage through phase (φ) control, and the fertilization ratio (D) is at a preset maximum value Upon arrival, a single phase shift (SPS) PI controller that generates a control signal for controlling the output voltage through phase (φ) control may be included.

According to another aspect, the present invention includes _{the steps of measuring an output voltage (V out} ) of a three-phase dual active bridge converter and comparing it with a preset reference voltage (V _{out_ref} ), and output power based on the output voltage and output current Calculating , selecting one of a plurality of preset modes as an operation mode based on the calculated output power, and performing a charging mode or a discharging mode according to a comparison result between the output voltage and the reference voltage. At this time, it is possible to provide a power control method of a three-phase dual active bridge converter comprising the step of controlling the output voltage generation in the three-phase dual active bridge converter based on the selected operation mode.

In the controlling step of the present invention, the charging mode may be performed when the phase value of the comparison result is a positive value (+), and the discharging mode may be performed when the phase value is a negative value (-). have.

In the controlling of the present invention, output voltage generation in the three-phase dual active bridge converter may be controlled through duty control or phase control.

In the controlling step of the present invention, when the phase (φ) of the output voltage _{is smaller than a preset minimum phase (φ min} ), the output voltage generation is controlled through duty control, and the phase of the output voltage is When (φ) is _{greater than the preset minimum phase (φ min} ) and the fertilization ratio (D) is less than or equal to a preset reference value, the output voltage generation is controlled through the duty control, and the phase (φ) of the output voltage is the It is greater than the preset minimum phase (φ _min ), and when the fertilization ratio (D) is greater than or equal to a preset reference value, the voltage generation is controlled through the phase (φ) control, and the fertilization ratio (D) reaches a preset maximum value. When the phase (φ) control, it is possible to control the output voltage generation.

According to an embodiment of the present invention, by simultaneously applying the technique of controlling the phase and the time ratio, it is possible to achieve zero current switching and increase (extend) a zero voltage switching area (a range where zero voltage switching starts).

According to an embodiment of the present invention, it is possible to increase (improve) the low load efficiency compared to the existing one by using only an algorithm without an additional circuit, and to increase (improve) the energy density by reducing the switching loss and applying it to the application of high frequency switching. .

1 is a block diagram of a power control apparatus of a three-phase dual active bridge converter according to an embodiment of the present invention.
2A and 2B are exemplary views for explaining that mode II is changed to mode III due to a phase difference according to an embodiment of the present invention.
3 is a flowchart illustrating a main process of controlling output voltage generation in a three-phase dual active bridge converter according to an embodiment of the present invention.
4 is for explaining that modes for controlling an output voltage are divided according to an embodiment of the present invention, and is a steady-state waveform diagram in each mode.
5 is an exemplary view showing a change trajectory of each mode.
6 is a steady-state waveform diagram exemplarily showing that ZVS does not occur at about 100 W (left) and becomes ZVS at approximately 300 W (middle) as an example.

Advantages and features of the present invention and methods of achieving them will become apparent with reference to the embodiments described below in detail in conjunction with the accompanying drawings. However, the present invention is not limited to the embodiments disclosed below, but can be implemented in various forms, and only these embodiments allow the disclosure of the present invention to be complete, and those of ordinary skill in the art to which the present invention pertains. It is provided to fully inform the person of the scope of the invention, and the scope of the invention is only defined by the claims.

In describing the embodiments of the present invention, detailed descriptions of well-known functions or configurations will be omitted except when actually necessary in describing the embodiments of the present invention. In addition, the terms to be described later are terms defined in consideration of functions in an embodiment of the present invention, which may vary according to intentions or customs of users and operators. Therefore, the definition should be made based on the content throughout this specification.

Hereinafter, preferred embodiments of the present invention will be described in detail with reference to the accompanying drawings.

1 is a block diagram of a power control apparatus of a three-phase dual active bridge converter according to an embodiment of the present invention.

Referring to FIG. 1 , the power control device of this embodiment includes a comparator 102 , a power calculator 104 , a mode selector 106 , a control signal generator 108 , a converter driver 110 , and a three-phase DAB converter. 112 and a low pass filter (LPF) 114 .

In addition, the control signal generating unit 108 includes a first PI (Proportional-Integral) controller 1082 , a second PI controller 1084 , a third PI controller 1086 , and a Single Phase Shift (SPS) PI controller 1088 ). and the like.

First, the comparator 102 controls the output voltage using the difference between the _{actual output voltage, that is, the output voltage (V out} ) and the reference voltage (V _{out_ref} ) provided by removing the high frequency through the low-pass filter 120 to be described later. It can provide functions such as

Here, if the phase value output through the comparator 102 is a positive value (+), it means a charging mode, and if the phase value is a negative value (-), it may mean a discharging mode. A case in which an output occurs can be defined as a charging mode, and a case in which power transfer occurs from an output to an input can be defined as a discharge mode.

That is, in order to control the output voltage, the phase (Phase shift angle = φ) or the duty cycle (D: duty cycle) must be changed. In order to control the phase value, the output voltage passing through the low pass filter (LPF) is passed. (V _out ) and the reference voltage (V _{out_ref} ) are compared.

As a result of the comparison here, if the output voltage (V _{out ) is greater than the reference voltage (V out_ref} ), the phase value (φ) or the time ratio ( D) is reduced relatively small, and when the output voltage V _{out is smaller than the reference voltage V out_ref} , the phase value or the time ratio currently output from the corresponding controller in the control signal generator 108 is relatively increased. Here, the output voltage is changed according to the phase (φ) and the time ratio (D).

_{Then, the power calculation unit 104 receives the measurement value V out} of the output voltage provided by removing the high frequency through the low-pass filter 114 to be described later, and the measurement value of the output current from the low-pass filter 114 . used with (i _out), may provide such functions as to calculate the output power (P _o), the output power (P _o) calculated here is transmitted to only the mode selection unit 106 in the following.

In addition, the mode selection unit 106 selects one of a plurality of preset control modes as the voltage control mode (or operation mode) based _{on the calculated output power (P o ) provided from the power calculation unit 104, etc.} function can be provided.

Here, a plurality of modes, for example, when the phase (φ) of the _{output voltage (V out ) is smaller than the preset minimum phase (φ min} ), a mode I for controlling the output voltage through duty control, and the output voltage When the phase (φ) of (V _{out ) is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is less than or equal to a preset reference value, mode II and mode Ⅲ for controlling the output voltage through duty control , When the phase (φ) of the output voltage (V _{out ) is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is greater than or equal to a preset reference value, the mode IV of controlling the output voltage through phase (φ) control and , it may include an SPS mode for controlling the output voltage through the phase (φ) control when the fertilization ratio (D) reaches a maximum (eg, 0.5).

Next, the control signal generating unit 108 is a voltage control mode selected by the mode selection unit 106 to provide a function such as generating a control signal for controlling the output voltage in the charging mode or the discharging mode. For this purpose, the control signal generator 108 may include a first PI controller 1082 , a second PI controller 1084 , a third PI controller 1086 , and an SPS PI controller 1088 .

That is, the control signal generating unit 108 is configured to perform a charging mode (when the phase value of the comparator output is positive) or a discharging mode (when the phase value of the comparator output is negative) according to the comparison result from the comparator 102 . value (-)), a control signal for controlling the output voltage is generated based on the selected voltage control mode.

First, the first PI controller 1082 in the control signal generating unit 108 _{, based on the comparison result between the preset reference voltage (V out_ref} ) and the output voltage (V _out ) When the charging mode or the discharging mode is performed, When the phase (φ) of the output voltage (V _{out ) is smaller than the preset minimum phase (φ min} ), a control signal for controlling the output voltage through duty control is generated (execution of mode I), and the converter driving unit A function such as forwarding to 110 may be provided.

And, the second PI controller 1084, when the charging mode or the discharging mode is performed based on the comparison result between the _{preset reference voltage (V out_ref} ) and the output voltage (V _out ), the phase of the _{output voltage (V out )} When (φ) is _{greater than a preset minimum phase (φ min} ) and the fertilization ratio (D) is less than or equal to a preset reference value, a control signal for controlling the output voltage through duty control is generated (mode II and mode III) ) to provide a function such as transmission to the converter driving unit 110 .

Here, in the case of mode II and mode III, the same controller, that is, one second PI controller 1084 is used, and in mode II and mode III, only the duty is performed in a situation where the phase is fixed to the minimum phase. Because they change, you can use the same controller. That is, mode II and mode III are changed by the mathematically calculated power, but the controlling variable is the same as D.

On the other hand, in the case of mode I, since the phase and D change together, a controller different from that of mode II and mode III must be used.

In addition, the third PI controller 1086, when the charging mode or the discharging mode is performed based on the comparison result between the _{preset reference voltage (V out_ref} ) and the output voltage (V _out ), the phase of the _{output voltage (V out )} If (φ) is _{greater than the preset minimum phase (φ min} ) and the fertilization ratio (D) is greater than or equal to the preset reference value, a control signal for controlling the output voltage through phase (φ) control is generated (execution of mode IV) Thus, a function such as transmission to the converter driving unit 110 may be provided.

Finally, the SPS PI controller 1088, when the charging mode or the discharging mode is performed based on the comparison result between the _{preset reference voltage (V out_ref} ) and the output voltage (V _{out ), the irrigation ratio (D) is the maximum (} For example, when 0.5) is reached, a function such as generating a control signal for controlling the output voltage through phase (φ) control (execution of mode SPS) and transmitting it to the converter driving unit 110 may be provided.

More specifically, a process in which each mode performed by the control signal generator 108 is changed by D and a phase value is as follows.

That is, in the case of mode I, power may be defined as in Equation 1 below.

[Equation 1]

In Equation 1, n is a turn ratio, V _in is an input voltage, V _out is an output voltage, f = f _s is a switching frequency, L is a coupling inductance, and w is an angular frequency (2*pi) *f), D is the duty ratio, and Φ is the phase angle, respectively.

That is, in mode 1, power is transmitted by D, and the phase in mode I increases in proportion to the value of D.

At this time, the time of switching to mode II is when the phase (φ) increased in mode I _{reaches a preset minimum phase (φ min} ), and the preset phase (φ) is ZVS (zero voltage switching). The minimum phase to achieve (φ _min ) may be calculated through Equation 2 below.

[Equation 2]

In Equation 2, V _in is an input voltage, V _out is an output voltage, d is a voltage gain (n*V _in /V _out ), f = f _s is a switching frequency, and L is a coupling inductance. , w denotes angular frequency (2*pi*f), Φ denotes phase angle, π denotes normal pi (3.141592), and Z _o denotes resonance impedance, respectively.

At this time, after the phase (φ) in mode I _{reaches the minimum phase (φ min} ), it is changed to mode II. At this time, power can be calculated through Equation 3 below.

[Equation 3]

In Equation 3, n is the turn ratio, V _in is the input voltage, V _out is the output voltage, L is the coupling inductance, w is the angular frequency (2*pi*f), and Φ _min is Each represents the minimum phase.

And, as D gradually increases in mode II, when each “phase difference”, that is, the phase-side phase difference of the three-phase DAB converter becomes “phase (φ _min )”, as shown in FIGS. 2A and 2B as an example, the mode II (FIG. 2A) is changed to Mode III (Mode 2B).

2A and 2B are exemplary views for explaining that mode II is changed to mode III due to a phase difference according to an embodiment of the present invention.

That is, referring to FIGS. 2A and 2B , when the interval between green and green [= phase difference between phases] in mode II2 becomes the minimum phase φ(φ _min ), it is changed to mode III, which can be calculated through Equation 4 below. can

[Equation 4]

In Equation 4, n is a turn ratio, V _in is an input voltage, V _out is an output voltage, f = f _s is a switching frequency, L is a coupling inductance, and w is an angular frequency (2*pi) *f), D is duty, Φ is phase angle, and Φ _min is minimum phase, respectively.

Finally, in the case of mode IV and mode SPS, the output power Po may be calculated as in Equation 5 below.

[Equation 5]

In Equation 5, n represents a turn ratio, V _in represents an input voltage, V _out represents an output voltage, f = f _s represents a switching frequency, L represents a coupling inductance, and Φ represents a phase angle, respectively.

In other words, since the power of mode SPS and mode IV have the same mathematical calculation, each mode can be changed by setting the power of the SPS according to the design specification and setting the mode IV so that D becomes 0.5 when it becomes SPS. have.

Accordingly, according to the embodiment of the present invention, power representing each mode can be mathematically calculated through each of the above-described equations, and it can be clearly seen that the mode is changed when the power is reached.

Again, referring to FIG. 1 , the converter driving unit 110 controls the driving of the three-phase DAB converter 112 based on the control signals selectively generated from each control unit in the control signal generating unit 108 (output voltage generation). control) can be provided.

_{In addition, the three-phase DAB converter 112 may provide a function of generating an output voltage (V out} ) according to the driving control provided from the converter driver 110 , and the output voltage generated here is a low-pass filter It is transmitted (negative feedback) to the comparator 102 and the power calculation unit 104 through (114).

Here, the low-pass filter 114 may _{provide a function of removing noise included in the output voltage V out} , for example, a high-frequency component such as a switching frequency.

3 is a flowchart illustrating a main process of controlling output voltage generation in a three-phase dual active bridge converter according to an embodiment of the present invention.

Referring to FIG. 3 , the comparator 102 compares the output voltage (V _out ) provided by removing the high frequency through the low-pass filter 120 and the reference voltage (V _{out_ref} ), and as a result of the comparison, a positive value ( A phase value having a positive value or a negative value (-) is output (step 302). Here, the output of the comparator 102 is provided as one input of the first PI controller 1082 , the second PI controller 1084 , the third PI controller 1086 , and the SPS PI controller 1088 .

In addition, if the phase value output through the comparator 102 is a positive value (+), the charging mode may be performed, and if the phase value is a negative value (-), the discharge mode may be performed.

_{In addition, the power calculator 104 receives the measured value (V out} ) of the output voltage provided by removing the high frequency through the low-pass filter 114 , and uses the measured value (i _out ) of the output current together to output power After calculating (P _o ) (step 304 ), the calculation result is provided to the control signal generating unit 108 .

Next, in the control signal generating unit 108, an operation mode (or voltage) for controlling the output voltage generation of the three-phase DAB converter 112 based on the phase (φ) and the time ratio (D) of _{the output voltage (V out )} control mode).

First, when step 306 the phase of the output voltage (V _out) (φ) is a group to check whether or not smaller than a minimum phase (φ _min) is set, the check result of the herein φ <φ _min the conditions are met, the process proceeds to step 308, and the first PI controller 1082 controls the output voltage generation in the three-phase DAB converter 112 through duty control by performing mode I.

And, as a result of the check in step 306 , _{if the condition φ<φ min} is not satisfied, in step 310 , the phase φ of the _{output voltage V out is greater than the preset minimum phase φ min} , and the fertilization ratio It is checked whether (D) is less than or equal to a preset reference value.

As a result of the check in step 310, if the _{condition φ>φ min} and the fertilization rate < reference value condition are satisfied, the process proceeds to step 312, and the second PI controller 1084 performs Mode II and Mode III by The output voltage generation in the three-phase DAB converter 112 is controlled through duty control.

In addition, as a result of the check in step 310 , if the _{condition φ>φ min} and the fertilization rate < reference value condition are not satisfied, in step 314 _{, the phase φ of the output voltage V out} is set to a preset minimum phase φ _min ), and it is checked whether the fertilization ratio (D) is greater than or equal to a preset reference value.

As a result of the check in step 314 , if the _{condition φ>φ min} and the fertilization ratio > reference value condition are satisfied, the process proceeds to step 316 , in which the third PI controller 1086 performs mode IV to ) to control the output voltage generation in the three-phase DAB converter 112 through the control.

Again, as a result of the check in step 314 , if the _{condition of φ>φ min and the} condition of fertilization rate > reference value are not satisfied, in step 318 , it is checked whether or not the fertilization ratio D has reached a preset maximum value.

As a result of the check in step 318, if the condition ratio = pre-set maximum value is satisfied, the process proceeds to step 320, and the SPS PI controller 1088 performs the SPS mode through phase (φ) control. Controls the output voltage generation in the three-phase DAB converter (112).

That is, according to the embodiment of the present invention, it is possible to actively control the output voltage generation of the three-phase DAB converter 112 based on the phase (φ) and the time ratio (D) of the _{output voltage (V out ).}

4 is for explaining that modes for controlling an output voltage are divided according to an embodiment of the present invention, and is a steady-state waveform diagram in each mode.

Referring to FIG. 4 , it can be seen that, in the case of advantages and effects obtained as a result, zero current switching is possible using a technology for controlling the fertilization ratio, and the zero voltage-switching area can be increased compared to the conventional technology.

That is, it can be seen that an area capable of increasing the efficiency at a low load compared to the existing one can be expanded by using only an algorithm without an additional circuit.

5 is an exemplary diagram showing the change trajectory of each mode, and is an exemplary diagram showing that seamless switching control is possible when an algorithm for controlling the fertilization rate is applied. (Mode change from mode I to mode SPS is possible)

Here, non-stop is a term used when controlling a bidirectional converter in the field of power electronics, and in the case of non-stepless control, it is a word that means continuous control. change) is used. In many topologies, when power is transferred from the forward direction to the reverse direction, it is difficult to instantaneously change the direction of power transfer, and interruption in power transfer occurs such as stopping and controlling. However, in the case of a three-phase DAB converter, since the power is controlled by phase, the phase change can be smoothly changed from positive to negative, which enables seamless control during bidirectional power conversion, which is defined as seamless transfer control. can do.

Referring to FIG. 5 , the proportion of mode change can be determined by setting the minimum phase shift value. When the minimum phase setting value is increased, the regions of mode I and mode III are enlarged, whereas the regions of mode II, mode IV and mode SPS are increased. It can be seen that the area is reduced.

6 is a steady-state waveform diagram exemplarily showing that ZVS does not occur at about 100 W (left) and becomes ZVS at approximately 300 W (middle) as an example.

Referring to FIG. 6 , it is shown that the part that does not become ZVS becomes ZVS in all conventional cases, which indicates that the switching loss is reduced in efficiency at low load, which is advantageous for high-frequency switching applications and at low load. It can be seen that the efficiency is improved.

The above description is merely illustrative of the technical idea of the present invention, and those of ordinary skill in the art to which the present invention pertains may make various substitutions, modifications, and changes within the scope not departing from the essential characteristics of the present invention. It will be easy to see that this is possible. That is, the embodiments disclosed in the present invention are not intended to limit the technical spirit of the present invention, but to explain, and the scope of the technical spirit of the present invention is not limited by these embodiments.

Accordingly, the protection scope of the present invention should be construed by the claims described below, and all technical ideas within the scope equivalent thereto should be construed as being included in the scope of the present invention.

102: comparator
104: power calculation unit
106: mode selection unit
108: control signal generator
110: converter driving unit
112: 3-phase DAB converter
114: low-pass filter
1082: first PI controller
1084: second PI controller
1086: third PI controller
1088: SPS PI controller

Claims (8)

A comparator for comparing the _{output voltage (V out} ) provided from the output of the three-phase dual active bridge converter with a preset reference voltage (V _{out_ref );}
a power calculation unit for calculating _{the output power (P o} ) based on the output voltage and the output current;
a mode selection unit for selecting one of a plurality of preset control modes as a voltage control mode based on the calculated output power (P _{o );}
a control signal generator for generating a control signal for controlling the output voltage based on the selected voltage control mode when a charging mode or a discharging mode is performed according to the comparison result in the comparator;
and a converter driver for controlling output voltage generation in the three-phase dual active bridge converter based on the generated control signal,
The control signal generator,
When the phase φ of the output voltage Vout is smaller than a preset minimum phase φmin, a first PI (Proportional-Integral) that generates a control signal for controlling the output voltage through duty control controller and
When the phase (φ) of the output voltage (V _{out ) is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is less than or equal to a preset reference value, to control the output voltage through duty control a second PI controller for generating a control signal for
If the phase (φ) of the output voltage (V _{out ) is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is greater than or equal to a preset reference value, the output voltage is controlled through the phase (φ) control A third PI controller that generates a control signal for
When the fertilization ratio (D) reaches a preset maximum value, comprising a SPS (Single Phase Shift) PI controller for generating a control signal for controlling the output voltage through phase (φ) control
Power control unit of 3-phase dual active bridge converter. The method of claim 1,
The control signal generator,
performing the charging mode when the phase value output from the comparator is a positive value (+), and performing the discharging mode when the phase value is a negative value (-)
Power control unit of 3-phase dual active bridge converter. The method of claim 1,
The control signal generator,
generating a control signal for controlling the output voltage through duty control or phase control
Power control unit of 3-phase dual active bridge converter. delete _{Measuring the output voltage (V out} ) of the three-phase dual active bridge converter and comparing it with a preset reference voltage (V _{out_ref );}
calculating output power based on the output voltage and output current;
selecting one of a plurality of preset modes as an operation mode based on the calculated output power;
When a charging mode or a discharging mode is performed according to a result of comparison between the output voltage and the reference voltage, controlling generation of an output voltage in the three-phase dual active bridge converter based on the selected operation mode,
The controlling step is
When the phase (φ) of the output voltage _{is smaller than a preset minimum phase (φ min} ), the output voltage generation is controlled through duty control,
When the phase (φ) of the output voltage _{is greater than the preset minimum phase (φ min} ) and the fertilization ratio (D) is less than or equal to a preset reference value, the output voltage generation is controlled through the duty control,
When the phase (φ) of the output voltage _{is greater than the preset minimum phase (φ min} ), and the fertilization ratio (D) is greater than or equal to a preset reference value, the output voltage generation is controlled through the phase (φ) control,
Controlling the output voltage generation through the phase (φ) control when the fertilization ratio (D) reaches a preset maximum value
Power control method of 3-phase dual active bridge converter. 6. The method of claim 5,
The controlling step is
performing the charging mode when the phase value of the comparison result is a positive value (+), and performing the discharging mode when the phase value is a negative value (-)
Power control method of 3-phase dual active bridge converter. 6. The method of claim 5,
The controlling step is
Controlling the output voltage generation in the three-phase dual active bridge converter through duty control or phase control
Power control method of 3-phase dual active bridge converter. delete

Images