CN212278126U - Frequency conversion phase shift modulation device of double-active-bridge series resonant converter circuit - Google Patents
Frequency conversion phase shift modulation device of double-active-bridge series resonant converter circuit Download PDFInfo
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Abstract
The utility model discloses a two active bridge series resonance converter circuit's frequency conversion phase shift modulation device, wherein two active bridge series resonance converter circuit include once side H bridge circuit, resonance capacitor, auxiliary inductance, a transformer, secondary side H bridge circuit and once side voltage-stabilizing capacitor, secondary side voltage-stabilizing capacitor, frequency conversion phase shift modulation device based on this circuit includes direct power control unit, segmentation linearization frequency conversion phase shift modulation unit and pulse width generating unit, be used for gathering the output voltage of converter respectively, and according to the error of the output voltage who gathers and expectation voltage, obtain the per unit transmission power instruction; obtaining a combination of a switching frequency ratio and a phase shift angle according to a per unit transmission power instruction and a voltage gain of a converter and a piecewise linearization method; and controlling the on and off of the switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit. The utility model discloses make the converter obtain near the highest efficiency according to the principle of efficiency optimization.
Description
Technical Field
The utility model belongs to direct current power supply transform field, more specifically relates to a frequency conversion phase shift modulation device of two active bridge series resonance converter circuits.
Background
The dual-active-bridge series resonant converter (DB-SRC) has the advantages of bidirectional energy flow, easiness in realizing soft switching, high power density and the like, wherein the resonant capacitor has the function of isolating direct current, and when a load is in short circuit, the resonant inductor and the high-frequency transformer can be effectively protected. The converter is widely applied to the fields of new energy electric automobiles, large-scale energy storage systems, renewable energy sources and the like. In addition, the DB-SRC has flexible control modes, such as: frequency conversion modulation mode, phase shift modulation mode, etc.
When the DB-SRC adopts frequency conversion modulation, soft switching of all switching tubes is easy to realize. However, for a wide voltage variation range application scenario, the converter requires a very wide operating frequency. This makes the design of the magnetic elements such as transformers and inductors difficult, and also increases the overall cost of the converter. In addition, when frequency conversion modulation is adopted, because the LC resonant tank and the output end are in a series structure, when the impedance of the LC resonant tank reaches the minimum, the voltage gain is only 1 at the maximum, and the output voltage is difficult to control under light load or no-load conditions. If a phase-shift modulation mode is adopted, the switching frequency is fixed, various problems existing in frequency conversion modulation can be effectively solved, meanwhile, the voltage regulation range is wide, and the voltage gain can be larger than 1 or smaller than 1. Phase shift control has various modes such as single phase shift control, double phase shift control, triple phase shift control, etc., but Single Phase Shift (SPS) modulation has some problems, such as: soft switching range is limited, backflow power is large, etc. Therefore, the optimal design can be performed by a Double Phase Shift (DPS) modulation mode and a Triple Phase Shift (TPS) modulation mode, but the DPS modulation mode and the TPS modulation mode are both complex.
Aiming at the defects of the DB-SRC in frequency conversion modulation or phase shift modulation, the frequency conversion modulation and the phase shift modulation can be combined to form a frequency conversion phase shift modulation mode. However, on the premise that the transmission power and the voltage gain are fixed, if the operating frequency and the phase shift angle are not properly selected, the effective current value of the resonant tank and the current stress of the switching tube are both increased rapidly, which leads to a serious decrease in the operating efficiency of the converter. Therefore, it is necessary to select the optimized operating frequency and phase shift angle from the viewpoint of efficiency optimization.
Disclosure of Invention
To prior art's defect, the utility model aims to provide a two active bridge series resonance converter circuit's frequency conversion phase shift modulation device aims at according to efficiency optimization's principle, moves the DB-SRC of phase modulation to the frequency conversion, at the in-process of adjusting output voltage, confirms optimal operating frequency and phase shift angle to make the converter obtain and be close the highest efficiency.
In order to achieve the above object, the present invention provides a frequency conversion phase shift modulation device of a dual active bridge series resonant converter circuit, which includes a primary side H bridge circuit, a resonant capacitor Cr, an auxiliary inductor Lr, a transformer, a secondary side H bridge circuit, a primary side voltage-stabilizing capacitor C1, and a secondary side voltage-stabilizing capacitor C2;
the direct current side of the primary side H-bridge circuit is connected with a primary side voltage source, and the alternating current side of the primary side H-bridge circuit is connected with the primary side of the transformer through a resonant capacitor Cr and an auxiliary inductor Lr; the alternating current side of the secondary side H-bridge circuit is connected with the secondary side of the transformer, and the direct current side of the secondary side H-bridge circuit is connected with a secondary side load;
the primary side voltage-stabilizing capacitor C1 and the secondary side voltage-stabilizing capacitor C2 are respectively connected in parallel with the primary side H-bridge circuit and the secondary side H-bridge circuit.
The frequency conversion phase shift modulation device comprises a direct power control unit, a piecewise linearization frequency conversion phase shift modulation unit and a pulse width generation unit. The input end of the direct power control unit is connected with a primary side direct current bus and a secondary side direct current bus of a main circuit of the double-active-bridge series resonant converter, and the output end of the direct power control unit is connected with the piecewise linearization frequency conversion phase shift modulation unit; the output end of the piecewise linearization frequency conversion phase shift modulation unit is connected with the pulse width generation units of the primary side H-bridge circuit and the secondary side H-bridge circuit;
the direct power control unit is used for acquiring the actual output voltage of the converter and obtaining an instruction value of per unit transmission power according to the error between the acquired actual output voltage and the expected voltage;
and the piecewise linearization frequency conversion phase shift modulation unit is used for determining the switching frequency and the phase shift angle according to the per unit transmission power instruction and the voltage gain and a piecewise linearization method and sending the switching frequency and the phase shift angle to the pulse width generation unit. The pulse width generating unit is used for controlling the on-off of the switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit, so that the effective value of the resonant current and the stress of the switching current are optimized, and the efficiency of the converter is further optimized;
the pulse width generating unit is used for generating two groups of square wave signals with adjustable frequency and 50% duty ratio and adjusting the phase difference between the two groups of square wave signals;
the piecewise linearization method is to obtain the switching frequency and the phase shift angle according to the principle of minimizing the effective value of the resonant current and minimizing the current stress. The specific determination method is that a frequency conversion modulation mode or a phase shift modulation mode is selected according to the value of the per unit transmission power instruction, and then the switching frequency ratio and the phase shift angle are determined. When the per unit transmission power instruction is smaller than a set demarcation value 1, a phase shift modulation mode is adopted, the frequency is set to be a maximum allowable switching frequency ratio in a fixed and unchangeable mode, and a phase shift angle is determined according to the transmission power instruction; when the per unit transmission power instruction is between the boundary value 1 and the boundary value 2, adopting variable frequency modulation, fixing the phase shift angle, and determining the switching frequency ratio according to the transmission power instruction; when the per unit transmission power instruction is larger than the demarcation value 2, phase shift modulation is adopted, the frequency is fixedly and invariably set as the minimum allowable switching frequency ratio, and the phase shift angle is determined according to the transmission power instruction.
Wherein the voltage gain is M ═ nV2/V1N is the turn ratio of the primary side and the secondary side of the transformer, V1For connection to primary side H-bridge circuitsDC input voltage, V2Is a direct current output voltage connected with a secondary side H-bridge circuit;
further, the primary side H-bridge circuit includes: four switching devices, respectively: the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the corresponding anti-parallel diode and the voltage stabilizing capacitor on the primary side; the primary side voltage stabilizing capacitor is connected in parallel with the primary side H-bridge circuit.
Further, the secondary side H-bridge circuit includes: four switching devices, respectively: a fifth switching tube, a sixth switching tube, a seventh switching tube, an eighth switching tube, a corresponding anti-parallel diode and a voltage stabilizing capacitor on the secondary side; and the voltage stabilizing capacitor on the secondary side is connected with the single-phase H-bridge circuit on the secondary side in parallel.
The utility model provides two control variables: a switching frequency ratio Fn defined as a ratio of the switching frequency to the resonance frequency; the phase shift angle theta is defined as the phase angle that the driving signal of the fifth switching tube in the secondary side H-bridge circuit lags behind the driving signal of the first switching tube in the primary side H-bridge circuit;
wherein the resonant frequency is
Cr is a resonance capacitor, and Lr is an auxiliary inductor.
Through the utility model discloses above technical scheme who thinks, compare with prior art, the beneficial effect that can obtain as follows:
(1) the utility model discloses a frequency conversion phase-shifting modulation device realizes the closed loop control of two active bridge series resonance converters, synthesizes frequency modulation and phase-shifting control's advantage, and the converter has the soft switching range of nimble voltage gain control ability, broad in full load range.
(2) The utility model provides a DB-SRC has higher transmission efficiency; when the transmission power is small (less than a certain transmission power boundary value 1), the converter adopts phase-shifting control, and the frequency is fixed to a maximum allowable value; when the transmission power is gradually increased, a frequency modulation mode is adopted for the converter, the phase shift angle is fixed, and a lower current effective value and current stress can be obtained, so that the efficiency of the converter is improved. When the DB-SRC works in a heavy load, the phase shift modulation is adopted for the converter, the switching frequency of the converter is low, and the full-range ZVS can be obtained to obtain high efficiency.
Drawings
Fig. 1 is a block diagram of a frequency conversion phase shift modulation apparatus of a dual-active-bridge series resonant converter circuit provided in an embodiment of the present invention;
fig. 2 is a schematic structural diagram of a main circuit topology and a frequency conversion phase shift modulation method of a dual-active-bridge series resonant converter provided in an embodiment of the present invention;
fig. 3(a) is a per-unit current effective value and a per-unit current stress optimization control trajectory when the voltage gain M is 0.75 according to an embodiment of the present invention;
fig. 3(b) is a two-dimensional plan view of a piecewise linearization optimization control track when the voltage gain M is 0.75 provided by the embodiment of the present invention;
fig. 4 is a graph of the relationship between the voltage gain M and the phase shift angles A, A1 and a2 according to the embodiment of the present invention;
fig. 5 is a graph of the relationship between the voltage gain M and the boundary power Po1 and Po 2;
FIG. 6 is a ZVS range diagram under the condition that Fn is more than or equal to 1.1 and less than or equal to 1.6;
FIG. 7 is a waveform of the phase shift control operation under light load;
fig. 8 is an operating waveform of the present invention under control of Po1< p < Po2 down conversion phase shift.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more clearly understood, the present invention is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention. Furthermore, the technical features mentioned in the embodiments of the present invention described below can be combined with each other as long as they do not conflict with each other.
Referring to fig. 1, it is a block diagram of the frequency conversion phase shift modulation apparatus of the dual active bridge series resonant converter circuit provided by the present invention, including the dual active bridge series resonant converter circuit and the frequency conversion phase shift modulation apparatus, the dual active bridge series resonant converter circuit mainly comprises a primary side single-phase H-bridge circuit, a resonant capacitor Cr, an auxiliary inductor Lr, a transformer T, a secondary side single-phase H-bridge circuit, a primary side voltage-stabilizing capacitor C1, and a secondary side voltage-stabilizing capacitor C2; the control part comprises a direct power control unit and a piecewise linearization frequency conversion phase shift modulation unit;
the direct current side of the primary side H bridge is connected with a primary side voltage source, and the alternating current side of the primary side H bridge is connected with the primary side of a transformer T through a resonant capacitor Cr and an auxiliary inductor Lr; the alternating current side of the secondary side H bridge is connected with the secondary side of the transformer T, and the direct current side of the secondary side H bridge is connected with a secondary side load; the input end of the direct power control unit is respectively connected with a primary side voltage source V1 and a secondary side voltage source V of the DB-SRC main circuit2The output end of the phase-shifting unit is connected with the phase-shifting unit; the primary side voltage-stabilizing capacitor C1 and the secondary side voltage-stabilizing capacitor C2 are respectively connected with the primary side H bridge circuit in parallel and the secondary side H bridge circuit in parallel; the output end of the frequency conversion phase shift modulation unit is respectively connected with the pulse width generation units of the primary side H-bridge circuit and the secondary side H-bridge circuit; a direct power control unit for sampling to obtain a real-time value V of the output voltage2And according to the collected actual output voltage and the expected output voltage VrefComparing to obtain an instruction value p of per unit transmission power; and the piecewise linearization frequency conversion phase shift modulation unit is used for determining the switching frequency and the phase shift angle according to the per unit transmission power instruction and the voltage gain and a piecewise linearization method and sending the switching frequency and the phase shift angle to the pulse width generation unit. The pulse width generating unit is used for controlling the on-off of the switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit, so that the effective value of the resonant current and the stress of the switching current are optimized, and the efficiency of the converter is further optimized; the pulse width generating unit is used for generating square wave signals with adjustable frequency and 50% duty ratio and adjusting the phase difference between the two groups of square wave signals. The pulse width generating unit is used for controlling the on-off of the switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit, so that the effective value of the resonant current and the stress of the switching current are optimized, and the efficiency of the converter is improvedOptimizing; the piecewise linearization method is to obtain the switching frequency and the phase shift angle according to the principle of minimizing the effective value of the resonant current and minimizing the current stress. The specific determination method is that a frequency conversion modulation mode or a phase shift modulation mode is selected according to the value of the per unit transmission power instruction, and then the switching frequency ratio and the phase shift angle are determined. When the per unit transmission power instruction is smaller than a set demarcation value 1, a phase shift modulation mode is adopted, the frequency is set to be a maximum allowable switching frequency ratio in a fixed and unchangeable mode, and a phase shift angle is determined according to the transmission power instruction; when the per unit transmission power instruction is between the boundary value 1 and the boundary value 2, adopting variable frequency modulation, fixing the phase shift angle, and determining the switching frequency ratio according to the transmission power instruction; when the per unit transmission power instruction is larger than the demarcation value 2, phase shift modulation is adopted, the frequency is fixedly and invariably set as the minimum allowable switching frequency ratio, and the phase shift angle is determined according to the transmission power instruction.
Wherein the voltage gain is M ═ nV2/V1N is the turn ratio of the primary side and the secondary side of the transformer, V1For the DC bus voltage, V, connected to the primary side H-bridge2The direct current bus voltage is connected with the secondary side H-bridge circuit;
specifically, as shown in fig. 2, the primary-side H-bridge circuit includes: four switching devices, respectively: first switch tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4And a corresponding anti-parallel diode D1、D2、D3、D4And a primary side voltage stabilizing capacitor C1(ii) a Primary side voltage stabilizing capacitor C1Connected in parallel with the primary side H-bridge circuit; the secondary side H-bridge circuit includes: four switching devices, respectively fifth switching tube S5The sixth switching tube S6Seventh switching tube S7The eighth switching tube S8And a corresponding anti-parallel diode D5、D6、D7、D8And a secondary side voltage stabilizing capacitor C2(ii) a Secondary side voltage stabilizing capacitor C2And is connected with the secondary side H-bridge circuit in parallel.
The utility model discloses a two control variables: a switching frequency ratio Fn defined as a ratio of the switching frequency to the resonance frequency, Fn being 1.1 or more and 1.6 or less; the phase shift angle theta is defined as the phase angle of a driving signal of a fifth switching tube in the secondary side H-bridge circuit lagging behind a driving signal of a first switching tube in the primary side H-bridge circuit, and theta is more than or equal to 0 and less than or equal to 0.5 pi;
wherein the resonant frequency is
Cr is a resonance capacitor, and Lr is an auxiliary inductor.
In the modulation process of frequency conversion phase shift of the double-active-bridge series resonant converter, the method specifically comprises the following steps:
step 1: direct power control unit collects output voltage V of converter2And according to the collected output voltage and the expected voltage VrefObtaining per unit transmission power instruction p;
step 2: the piecewise linearization frequency conversion phase shift modulation unit obtains the combination of a switching frequency ratio Fn and a phase shift angle theta according to a per unit transmission power instruction p and a converter voltage gain M by a piecewise linearization method;
and step 3: the pulse width generating unit controls the on and off of switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit according to the combination of the switching frequency ratio Fn and the phase shift angle theta;
specifically, in step 2, according to the per unit transmission power command and the voltage gain of the converter, the combination of the switching frequency ratio Fn and the phase shift angle θ is obtained by a piecewise linearization method, and the specific process includes:
(1) calculating the transmission power of the converter according to the transformer transformation ratio, the input voltage at the direct current side of the primary side H bridge circuit, the output voltage at the direct current side of the secondary side H bridge circuit, the switching frequency ratio Fn and the voltage gain M, and obtaining the per-unit transmission power of the converter according to the reference transmission power of the converter;
the per-unit transmission power of the converter is:
wherein the reference power of the converter is
V1Cr is a resonance capacitor, and Lr is an auxiliary inductor.
(2) According to the maximum allowable switching frequency ratio Fnmax1.6, minimum allowed switching frequency ratio Fnmin1.1, respectively obtaining an optimal control track of the effective value of the current and an optimal control track of the stress of the switching current according to the principles of minimizing the effective value of the resonant current and minimizing the stress of the current, and finally obtaining a fixed phase shift angle A at a frequency conversion boundary;
obtaining a control track with minimized current effective value and a control track with minimized switch current stress, and the specific steps are as follows:
1) obtaining an effective value of the current of the resonant tank of the converter according to the transformer transformation ratio, the input voltage at the direct current side of the primary side H-bridge circuit, the output voltage at the direct current side of the secondary side H-bridge circuit, the switching frequency ratio Fn and the voltage gain M, and obtaining a per-unit effective value of the current of the resonant tank by using the reference current;
the effective value of the per-unit resonance tank current of the converter is as follows:
in the formula:
wherein the reference current is
V1Cr is a resonance capacitor and Lr is an auxiliary inductor.
2) Obtaining current stress of the converter according to the transformer transformation ratio, the input voltage at the direct current side of the primary side H-bridge circuit, the output voltage at the direct current side of the secondary side H-bridge circuit, the switching frequency ratio Fn and the voltage gain M, and obtaining per-unit current stress by using reference current;
the per unit current stress of the converter is:
wherein the reference current is
V1Cr is a resonance capacitor and Lr is an auxiliary inductor.
3) Under the condition that the per-unit transmission power instruction is determined, the effective value of the resonant tank current is optimized and solved according to the constraint condition, and an optimized control track of combination of Fn and theta for minimizing the effective value of the per-unit current is obtained;
taking the voltage gain M equal to 0.75 as an example, the optimization objective function is formula (2), and the modal boundary constraint conditions are:
4) under the condition of a per-unit transmission power instruction, optimally solving the current stress of the resonance tank according to a constraint condition to obtain a combined control track of Fn and theta for minimizing the per-unit current stress;
taking the example that the voltage gain M is 0.75, the optimization objective function is formula (3), and the modal boundary constraint conditions are:
as shown in fig. 3(a), the curves of the trajectories of the current effective value minimization and the current stress minimization and the control combinations Fn and θ are obtained, and it can be seen that, under different given per unit transmission power commands, the trajectories of the current effective value optimization and the current stress optimization are close to each other, so that the optimization control effect is equivalent.
5) A piecewise function is adopted, the current effective value minimization and the current stress minimization control trajectory are fitted in a linear mode to be the only piecewise optimization control trajectory, and as shown in a figure 3(b), a phase shift angle theta and a switch resonance frequency ratio Fn control combination curve are obtained; as can be seen from fig. 3, if the per unit transmission power command p is smaller than the threshold Po1, the switching frequency ratio is fixed to Fn equal to 1.6, and the phase shift angle is determined according to equation (8); when the per-unit transmission power command is: selecting a frequency conversion modulation mode when Po1< P < Po2, keeping a phase shift angle as a turning point phase shift angle A, and determining a switching frequency ratio Fn according to a formula (8); when P > Po1, the switching frequency ratio Fn is 1.1, and the phase shift angle is determined according to equation (8).
In the same way, the optimized control trajectory under other different voltage gains M can be analyzed, fig. 4 is the utility model provides a relation curve of different voltage gains M and phase shift angle A, A1, a2, a1 is the turning point phase shift angle when Fn is 1.6 for the linearization fitting control trajectory, a2 is the turning point phase shift angle when Fn is 1.1, wherein a is (a is) 1.11+A2) And/2, the mathematical expression is as follows:
according to the formulas (6) and (7), the boundary value of the transmission power can be determined, fig. 5 is the relationship curves of Po1 and Po2 under different voltage gain M conditions of the present invention, and with reference to fig. 5, Po1 and Po2 under different voltage gains M can be obtained, and the corresponding calculation process can be easily derived by those skilled in the art according to the technical solution.
And (3) combining the formula (8) and the piecewise optimization control track shown in the figure 3(b) to realize the frequency conversion phase shift modulation of the DB-SRC.
Fig. 6 shows the ZVS range of the present invention under the condition that Fn is not less than 1.1 and not more than 1.6, and under the condition of different voltage gains M, the corresponding full ZVS operating region can be obtained for the given per unit transmission power p, and it can be seen that the ZVS range is significantly smaller than the ZVS range when Fn is 1.6. Meanwhile, in order to obtain higher power transmission efficiency, when the per-unit effective current value and current stress are analyzed and optimized, ZVS constraint can be preferentially considered when a full ZVS range is obtained.
Fig. 7 is the utility model discloses work oscillogram under light load, when series resonance converter work at light load or no-load state, switch resonant frequency's fixed Fn of ratio is 1.6, adopts phase shift control to DB-SRC to realize the stable output of light load or voltage under the no-load, effectively solve the problem that series resonance converter voltage gain can not be adjusted in a flexible way. At the same time, ZVS is easily implemented to achieve higher efficiency.
Fig. 8 is a waveform diagram of the operation of the present invention under transmission power command Po1< p < Po2, when DB-SRC operates in frequency modulation mode, the phase shift angle θ is fixed, and the lowest effective value of resonant current and current stress can be obtained, thereby improving the efficiency of the converter; while at the same time obtaining a wide range of voltage regulation capability.
It should be noted that all the data in the above embodiments are described as an example, the present invention is not limited to this, and the actual engineering may be set and calculated as needed.
It will be understood by those skilled in the art that the foregoing is merely a preferred embodiment of the present invention, and is not intended to limit the invention to the particular forms disclosed, but on the contrary, the intention is to cover all modifications, equivalents, and alternatives falling within the spirit and scope of the invention as defined by the appended claims.
Claims (5)
1. A frequency conversion phase shift modulation device of a double-active-bridge series resonant converter circuit comprises a primary side H-bridge circuit, a resonant capacitor, an auxiliary inductor, a transformer, a secondary side H-bridge circuit, a primary side voltage stabilizing capacitor and a secondary side voltage stabilizing capacitor, and is characterized by comprising a direct power control unit, a segmented linearization frequency conversion phase shift modulation unit and a pulse width generation unit; the input end of the direct power control unit is connected with a primary side direct current bus and a secondary side direct current bus of a main circuit of the double-active-bridge series resonant converter, and the output end of the direct power control unit is connected with the piecewise linearization frequency conversion phase shift modulation unit; the output end of the piecewise linearization frequency conversion phase shift modulation unit is connected with the pulse width generation units of the primary side H-bridge circuit and the secondary side H-bridge circuit;
the direct power control unit is used for acquiring the actual output voltage of the converter and obtaining an instruction value of per unit transmission power according to the error between the acquired actual output voltage and the expected voltage;
the piecewise linearization frequency conversion phase shift modulation unit is used for determining the switching frequency and the phase shift angle according to the per unit linearization method and the per unit linearization transmission power instruction and the voltage gain, and sending the switching frequency and the phase shift angle to the pulse width generation unit; the pulse width generating unit is used for controlling the on-off of the switching tubes in the primary side H-bridge circuit and the secondary side H-bridge circuit, so that the effective value of the resonant current and the stress of the switching current are optimized, and the efficiency of the converter is further optimized;
the pulse width generating unit is used for generating two groups of square wave signals with adjustable frequency and 50% duty ratio and adjusting the phase difference between the two groups of square wave signals.
2. The frequency-converting phase-shifting modulation apparatus according to claim 1, wherein the piecewise linear frequency-converting phase-shifting modulation unit is configured to obtain the switching frequency and the phase-shifting angle according to the principle of minimizing the effective value of the resonant current and minimizing the stress of the current.
3. The frequency-converting phase-shifting modulation device according to claim 2, wherein the principle of minimizing the effective value of the resonant current and minimizing the current stress is to select a frequency-converting modulation mode or a phase-shifting modulation mode according to the value of the per-unit transmission power command, and further determine the switching frequency ratio and the phase-shifting angle; when the per unit transmission power instruction is smaller than a set demarcation value 1, a phase shift modulation mode is adopted, the frequency is set to be a maximum allowable switching frequency ratio in a fixed and unchangeable mode, and a phase shift angle is determined according to the transmission power instruction; when the per unit transmission power instruction is between the boundary value 1 and the boundary value 2, adopting variable frequency modulation, fixing the phase shift angle, and determining the switching frequency ratio according to the transmission power instruction; when the per unit transmission power instruction is larger than the demarcation value 2, phase shift modulation is adopted, the frequency is fixedly and invariably set as the minimum allowable switching frequency ratio, and the phase shift angle is determined according to the transmission power instruction.
4. The apparatus according to claim 1, wherein the primary side H-bridge circuit has a dc side connected to a primary side voltage source and an ac side connected to the primary side of the transformer via a resonant capacitor and an auxiliary inductor; the alternating current side of the secondary side H-bridge circuit is connected with the secondary side of the transformer, and the direct current side of the secondary side H-bridge circuit is connected with a secondary side load;
the primary side voltage-stabilizing capacitor and the secondary side voltage-stabilizing capacitor are respectively connected with the primary side H-bridge circuit and the secondary side H-bridge circuit in parallel.
5. The apparatus according to claim 1, wherein the primary H-bridge circuit comprises four switching devices, respectively: the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the corresponding anti-parallel diode and the voltage stabilizing capacitor on the primary side;
the secondary side H-bridge circuit comprises four switching devices which are respectively: the fifth switching tube, the sixth switching tube, the seventh switching tube, the eighth switching tube, the corresponding anti-parallel diode and the voltage stabilizing capacitor on the secondary side.
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