KR102187750B1 - Motor driving apparatus and home appliance including the same - Google Patents

Abstract

The present invention relates to a motor driving device and a home appliance having the same. A motor driving apparatus and a home appliance having the same according to an embodiment of the present invention, a single-phase motor having an asymmetrical air gap, by switching operation, converts the dc power supply into AC power, and outputs the converted AC power to the single phase motor An inverter, an output current detector that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, and the control unit includes a high-frequency voltage and a DC voltage to detect an initial position of the motor. Is controlled to be applied to the motor, and the initial position of the motor is detected based on the output current detected by the output current detection unit. Accordingly, it is possible to accurately detect the initial position of the single-phase motor.

Description

Motor driving apparatus and home appliance including the same

The present invention relates to a motor driving device and a home appliance having the same, and more particularly, to a motor driving device capable of accurately detecting the initial position of a single-phase motor, and a home appliance having the same.

The motor driving device is a device for driving a motor having a rotor for rotational motion and a stator wound around a coil.

Motors can be classified into Samsung motors with three-phase windings and single-phase motors with single-phase windings.

In the three-phase motor, the rotation direction can be adjusted by a current applied to the three-phase or the like, but the single-phase motor cannot adjust the rotation direction.

Accordingly, when implementing a single-phase motor, there is a method of implementing a motor driving apparatus using a sensor method such as a Hall sensor, but according to this, there is a disadvantage in that additional cost is required.

Therefore, when driving a single-phase motor, a method of driving the motor in a sensorless method excluding the Hall sensor is being studied.

An object of the present invention is to provide a motor driving device capable of accurately detecting the initial position of a single-phase motor and a home appliance having the same.

An object of the present invention is to provide a motor driving device capable of reducing an error in a rotor position when driving a single-phase motor at high speed, and a home appliance including the same.

A motor driving device according to an embodiment of the present invention for achieving the above object and a home appliance having the same, a single-phase motor having an asymmetrical air gap, and by switching operation, converting the DC terminal power to AC power, and converted AC An inverter that outputs power to the single-phase motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, the control unit for detecting the initial position of the motor. , High-frequency voltage and DC voltage are applied to the motor, and the initial position of the motor is detected based on the output current detected by the output current detection unit.

On the other hand, the control unit of the motor driving apparatus according to an embodiment of the present invention integrates the output current detected by the output current detection unit based on the position angle of the frequency of the high frequency voltage to detect the magnitude of the current, and Based on the size, it is possible to detect the initial position of the motor.

Meanwhile, when the N pole of the magnet of the motor is positioned, the magnitude of the detected current may be greater than when the S pole of the motor magnet is positioned at the reference position of the motor.

In particular, when the N pole of the magnet of the motor is located, the magnitude of the detected DC current may be larger than when the S pole of the magnet of the motor is located at the reference position of the motor.

On the other hand, a motor driving device and a home appliance having the same according to another embodiment of the present invention for achieving the above object, by a single-phase motor having an asymmetrical air gap, and by a switching operation, converts DC power to AC power, An inverter that outputs the converted AC power to a single-phase motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, and the control unit includes an initial position of the motor. For detection, a high frequency voltage and a magnetic flux voltage command value are controlled to be applied to the motor, and the initial position of the motor is detected based on the output current detected by the output current detection unit.

A motor driving apparatus and a home appliance having the same according to an embodiment of the present invention, a single-phase motor having an asymmetrical air gap, by switching operation, converts the dc power supply into AC power, and outputs the converted AC power to the single phase motor An inverter, an output current detector that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, and the control unit includes a high-frequency voltage and a DC voltage to detect an initial position of the motor. Is controlled to be applied to the motor, and the initial position of the motor is detected based on the output current detected by the output current detection unit. Accordingly, it is possible to accurately detect the initial position of the single-phase motor. Accordingly, it is possible to drive the single-phase motor in a sensorless manner.

On the other hand, the control unit of the motor driving apparatus according to an embodiment of the present invention integrates the output current detected by the output current detection unit based on the position angle of the frequency of the high frequency voltage to detect the magnitude of the current, and Based on the size, it is possible to detect the initial position of the motor. Accordingly, accordingly, the initial position of the single-phase motor can be accurately detected.

On the other hand, a motor driving device and a home appliance having the same according to another embodiment of the present invention, a single-phase motor having an asymmetrical air gap, by switching operation, converts the DC power supply to AC power, and converts the converted AC power to single phase An inverter outputting to the motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, and the control unit includes a high-frequency voltage to detect the initial position of the motor. And a magnetic flux voltage command value is applied to the motor, and the initial position of the motor is detected based on the output current detected by the output current detection unit. Accordingly, it is possible to accurately detect the initial position of the single-phase motor. Accordingly, it is possible to drive the single-phase motor in a sensorless manner.

1 is a side elevation view showing a state of use of a cleaner according to an embodiment of the present invention.
FIG. 2 is a perspective view of a cleaner from which the nozzle module is removed from FIG. 1.
3 is a side elevation view of the cleaner of FIG. 2.
4A and 4B are views showing the suction motor of FIG. 3.
5 illustrates an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention.
6 is an example of an internal circuit diagram of the motor driving apparatus of FIG. 5.
7 is an internal block diagram of the inverter controller of FIG. 6.
8 is a diagram referred to for describing the operation of the motor.
9 to 12 are views referenced for explaining the operation of the motor driving apparatus according to the embodiment of the present invention.

Hereinafter, the present invention will be described in more detail with reference to the drawings.

The suffixes "module" and "unit" for the constituent elements used in the following description are given in consideration of only the ease of writing in the present specification, and do not impart a particularly important meaning or role by themselves. Therefore, the "module" and "unit" may be used interchangeably with each other.

The home appliance described herein refers to a home appliance that includes a single-phase motor and is driven according to an operation of the single-phase motor. For example, the home appliance may be variously exemplified such as a vacuum cleaner, a hair dryer, an electric fan, a washing machine, an air purifier, an air conditioner, a water purifier, a refrigerator, and a vehicle. Hereinafter, a vacuum cleaner among home appliances will be described.

1 is a side elevational view showing a state of use of a cleaner according to an embodiment of the present invention, FIG. 2 is a perspective view of a cleaner with a nozzle module removed from FIG. 1, and FIG. 3 is a side elevation view of the cleaner of FIG. 2.

1 to 3, the cleaner 100 according to an embodiment of the present invention includes a main body 10 and a main body 10 forming a flow path P for guiding suctioned air to be discharged to the outside. ), the handle 30 coupled to the rear side of the main body 10, the nozzle module 70 detachably connected to the suction unit 11 of the main body 10, a battery Bt for supplying power, and a battery Bt. A fan module 50 disposed on the battery housing 40 and the flow path P to move air in the flow path may be provided.

The nozzle module 70 may include a nozzle unit 71 provided to suck in external air and an extension pipe 73 extending from the nozzle unit 71.

The extension pipe 73 connects the nozzle part 71 and the suction part 11. The extension pipe 73 guides the air sucked in from the nozzle part 71 to flow into the suction flow path P. One end of the extension pipe 73 may be detachably coupled to the suction part 11 of the main body 10. The user can clean while holding the handle 30 and moving the nozzle 71 while placing the nozzle 71 on the floor.

The main body 10 includes an exhaust cover 12 forming an exhaust port 10a, a dust collecting unit 13 for storing separated dust, and a fan module housing 14 accommodating the fan module 50 therein. It may include.

The discharge cover 12 may form an upper surface of the main body 10. The exhaust cover 12 covers the upper side of the fan module housing 14.

The dust collection part 13 may be formed in a cylindrical shape. The dust collecting part 13 may be disposed under the fan module housing 14. Accordingly, a storage space for dust may be formed inside the dust collection unit 13.

The fan module housing 14 may be formed to extend upward from the dust collection unit 13. The fan module housing 14 is formed in a cylindrical shape. The extended portion 31 of the handle 30 may be disposed on the rear side of the fan module housing 14.

In the fan module housing 14, a fan module 50 may be disposed.

The fan module 50 includes a suction motor 230 that rotates the impeller 51. The suction motor 230 may be located above the dust separation unit 20.

The impeller 51 may be disposed under the suction motor 230. The impeller 51 is coupled with the suction motor 230 and rotates by the rotational force of the suction motor 230.

Meanwhile, the impeller 510 may pressurize the air by rotation so that the air in the flow path P is discharged through the exhaust port 10a.

Meanwhile, the cleaner 100 may include a motor driving unit 220 for controlling the suction motor 230. The motor driving unit 220 may be disposed between the suction motor 230 and the dust collecting unit 13. Meanwhile, the motor driving unit 220 may include circuit elements disposed on a PCB circuit board.

The handle 30 extends in the vertical direction and includes an additional extension 32. The additional extension part 32 may be spaced apart from the main body 10 in the front-rear direction. The user can use the vacuum cleaner 100 while holding the additional extension 32. The upper end of the additional extension 32 is connected to the rear end of the extension 31. The lower end of the additional extension 32 is connected to the battery housing 40.

The additional extension part 32 is provided with a movement limiting part 32a to prevent the hand from moving in the longitudinal direction (up and down direction) of the additional extension part 32 while the user holds the additional extension part 32 Can be. The movement limiting part 32a may protrude forward from the additional extension part 32.

The movement limiting part 32a is disposed to be spaced apart from the extension part 31 vertically. While the user holds the additional extension part 32, some fingers of the user's hand are positioned above the movement limiting part 32a, and the other fingers are provided to be located below the movement limiting part 32a.

The handle 30 may include an inclined surface 33 facing the direction between the upper side and the rear side. The inclined surface 33 may be positioned at the rear of the extension 31. The input unit 3 may be disposed on the inclined surface 33.

The battery Bt may supply power to the fan module 50. The battery Bt may supply power to the noise control module. The battery Bt may be detachably disposed inside the battery housing 40.

The battery housing 40 is coupled to the rear side of the main body 10. The battery housing 40 is disposed under the handle 30. The battery Bt is accommodated in the battery housing 40. A heat dissipation hole for discharging heat generated from the battery Bt to the outside may be formed in the battery housing 40.

Meanwhile, the exhaust port 10a may be disposed to face a specific direction (eg, upward direction). The plurality of exhaust ports 10a may be divided from each other in the circumferential direction by a plurality of exhaust guides 12a. The plurality of exhaust ports 10a may be arranged at predetermined intervals apart from each other along the circumferential direction.

4A and 4B are views showing the suction motor of FIG. 3.

Referring to the drawings, the suction motor 230 according to the embodiment of the present invention may include a rotor (ROT) and a stator (STA).

The rotor ROT may include a rotor core PCO and a magnet PM formed on the outer periphery of the rotor core PCO. The magnet (PM) is formed in a circular shape, and may be provided with an S pole (PMS) and an N pole (PMN), respectively.

Meanwhile, in FIG. 4A, it is illustrated that the S pole (PMS) faces upward, and in FIG. 4B, it is illustrated that the S pole (PMS) faces downward.

The stator STA may include a stator frame SFR formed on one side of the rotor ROT, and coils Cla and Clb respectively wound on the upper and lower sides of the stator frame SFR.

On the other hand, since the stator frame (SFR) is disposed on one side of the magnet (PM) of the rotor (ROT), an asymmetrical air gap (ARG) between the magnet (PM) of the rotor (ROT) and the stator frame (SFR) Can be formed.

As described above, the suction motor 230 according to an embodiment of the present invention may be a brushless DC (BLDC) single-phase motor in which an asymmetric air gap (ARG) is formed.

The motor driving apparatus described in this specification is capable of estimating the rotor position of the motor by a sensorless method, which does not include a position detection unit such as a hall sensor for sensing the rotor position of the motor. It is a possible motor drive. Hereinafter, a sensorless motor driving device will be described.

5 illustrates an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention, and FIG. 6 is an example of an internal circuit diagram of the motor driving apparatus of FIG. 5.

Referring to the drawings, the motor driving apparatus 220 according to an embodiment of the present invention is for driving the single-phase motor 230 and may include an inverter 420 and an inverter control unit 430.

In addition, the motor driving apparatus 220 according to an embodiment of the present invention may include a converter 410, a dc terminal voltage detection unit (B), a dc terminal capacitor (C), and an output current detection unit (E). In addition, the driving unit 220 may further include an input current detection unit A and the like.

Hereinafter, operations of each of the constituent units in the motor driving apparatus 220 of FIGS. 5 and 6 will be described.

The input current detection unit A may detect an input current i _s input from the battery BT. To this end, as the input current detection unit A, a current trnasformer (CT), a shunt resistor, or the like may be used. The detected input current i _s is a pulsed discrete signal and may be input to the inverter controller 430.

The converter 410 may convert the level of the battery power Vs from the battery BT to output the level-converted DC power. To this end, the converter 410 may include a switching element. Meanwhile, the converter 410 may be omitted.

The dc terminal capacitor C may store input power. In addition, the input power can be smoothed.

Meanwhile, since DC power is stored at both ends of the DC terminal capacitor C, this may be referred to as a dc terminal or a dc link terminal.

The dc terminal voltage detector B may detect the dc terminal voltage Vdc, which is both ends of the dc terminal capacitor C. To this end, the dc terminal voltage detection unit B may include a resistance element, an amplifier, and the like. The detected dc voltage Vdc may be input to the inverter controller 430 as a discrete signal in the form of a pulse.

The inverter 420 includes a plurality of inverter switching elements, and converts the DC power supply (Vdc) of the dc stage into a single phase AC power supply (va) of a predetermined frequency by an on/off operation of the switching element, and a single phase synchronous motor It can be output to 230.

In the inverter 420, a pair of upper-arm switching elements (Sa, Sb) and lower-arm switching elements (S'a, S'b) connected in series with each other, respectively, and a total of two pairs of upper and lower arm switching elements are parallel to each other ( It is connected to Sa&S'a,Sb&S'b). Diodes are connected in reverse parallel to each of the switching elements Sa, S'a, Sb, S'b.

The switching elements in the inverter 420 perform on/off operations of each switching element based on the inverter switching control signal Sic from the inverter controller 430. As a result, single-phase AC power having a predetermined frequency is output to the single-phase synchronous motor 230.

The inverter controller 430 may control a switching operation of the inverter 420 based on a sensorless method. To this end, the inverter control unit 430 may receive an output current i _o detected by the output current detection unit E.

The inverter controller 430 outputs an inverter switching control signal Sic to the inverter 420 in order to control the switching operation of the inverter 420. The inverter switching control signal Sic is a switching control signal of the pulse width modulation method (PWM), and is generated and output based on the output current i _o detected by the output current detection unit E. A detailed operation of the output of the inverter switching control signal Sic in the inverter control unit 430 will be described later with reference to FIG. 7.

The output current detection unit E detects an output current i _o flowing between the inverter 420 and the single-phase motor 230. That is, the current flowing through the motor 230 is detected.

The output current detection unit E may be located between the inverter 420 and the motor 230, and for current detection, a current trnasformer (CT), a shunt resistor, or the like may be used. Alternatively, the output current detection unit E may include a shunt resistor disposed between the dc terminal capacitor C and the inverter 420.

The detected output current i _o may be applied to the inverter control unit 430 as a discrete signal in the form of a pulse, and the inverter switching control signal Sic based on the detected output current i _o Is created. Hereinafter, it may be described in parallel that the detected output current i _o is the single-phase output current io.

Meanwhile, the single-phase motor 230 includes a stator and a rotor, and single-phase AC power having a predetermined frequency is applied to the coil of the single-phase stator, so that the rotor rotates.

Such a single-phase motor 230 is, for example, a surface-mounted permanent magnet synchronous motor (Surface-Mounted Permanent-Magnet Synchronous Motor; SMPMSM), a built-in permanent magnet synchronous motor (Interior Permanent Magnet Synchronous Motor; IPMSM), and synchronous It may include a reluctance motor (Synchronous Reluctance Motor; Synrm) or the like. Among them, SMPMSM and IPMSM are Permanent Magnet Synchronous Motor (PMSM), and Synrm is characterized by no permanent magnet.

7 is an internal block diagram of the inverter controller of FIG. 6.

Referring to FIG. 7, the inverter control unit 430 includes an axis conversion unit 310, a speed calculation unit 320, a current command generation unit 330, a voltage command generation unit 340, an axis conversion unit 350, and A switching control signal output unit 360 may be included.

The axis conversion unit 310 receives the single-phase output current io or ia detected by the output current detection unit E and converts it into two-phase currents iα and iβ of the stationary coordinate system.

Meanwhile, the axis conversion unit 310 may convert the two-phase currents iα and iβ of the stationary coordinate system into the two-phase currents id and iq of the rotational coordinate system.

)와 연산된 속도(

)를 출력할 수 있다.The speed calculation unit 320 is based on the two-phase current (iα, iβ) of the stationary coordinate system axis-changed by the axis conversion unit 310,

) And calculated speed (

) Can be printed.

)와 속도 지령치(ω^* _r)에 기초하여, 전류 지령치(i^* _q)를 생성한다. 예를 들어, 전류 지령 생성부(330)는, 연산 속도(

)와 속도 지령치(ω^* _r)의 차이에 기초하여, PI 제어기(335)에서 PI 제어를 수행하며, 전류 지령치(i^* _q)를 생성할 수 있다. 도면에서는, 전류 지령치로, q축 전류 지령치(i^* _q)를 예시하나, 도면과 달리, d축 전류 지령치(i^* _d)를 함께 생성하는 것도 가능하다. 한편, d축 전류 지령치(i^* _d)의 값은 0으로 설정될 수도 있다. On the other hand, the current command generation unit 330, the calculation speed (

) And the speed command value (ω ^* _r ), the current command value (i ^* _q ) is generated. For example, the current command generation unit 330, the calculation speed (

) And the speed command value (ω ^* _r ), the PI controller 335 performs PI control, and a current command value (i ^* _q ) can be generated. In the drawing, the q-axis current command value (i ^* _q ) is illustrated as the current command value, but unlike the drawing, it is also possible to generate the d-axis current command value (i ^* _d ) together. Meanwhile, the value of the d-axis current command value (i ^* _d ) may be set to 0.

Meanwhile, the current command generation unit 330 may further include a limiter (not shown) that limits the level so that the current command value i ^* _q does not exceed the allowable range.

Next, the voltage command generation unit 340 includes the d-axis and q-axis currents (i _d , i _q ) that have been axially transformed from the axis conversion unit into a two-phase rotational coordinate system, and a current command value in the current command generation unit 330, etc. Based on i ^* _d ,i ^* _q ), the d-axis and q-axis voltage command values (v ^* _d ,v ^* _q ) are generated. For example, the voltage command generation unit 340 performs PI control in the PI controller 344 based on the difference between the q-axis current (i _q ) and the q-axis current command value (i ^* _q ), and q It is possible to generate the axis voltage command value (v ^* _q ). In addition, the voltage command generation unit 340 performs PI control in the PI controller 348 based on the difference between the d-axis current (i _d ) and the d-axis current command value (i ^* _d ), and the d-axis voltage You can create a setpoint (v ^* _d ). Meanwhile, the voltage command generation unit 340 may further include a limiter (not shown) that limits the level of the d-axis and q-axis voltage command values (v ^* _d , v ^* _q ) to not exceed the allowable range. .

On the other hand, the generated d-axis and q-axis voltage command values (v ^* _d and v ^* _q ) are input to the axis conversion unit 350.

)와, d축, q축 전압 지령치(v^* _d,v^* _q)를 입력받아, 축변환을 수행한다.The axis conversion unit 350 is a position calculated by the speed calculation unit 320 (

) And the d-axis and q-axis voltage command values (v ^* _d ,v ^* _q ) and perform axis transformation.

)가 사용될 수 있다.First, the axis conversion unit 350 converts from a two-phase rotation coordinate system to a two-phase stationary coordinate system. At this time, the position calculated by the speed calculating unit 320 (

) Can be used.

In addition, the axis conversion unit 350 converts from a two-phase stationary coordinate system to a single-phase stationary coordinate system. Through this conversion, the axis conversion unit 1050 outputs a single-phase output voltage command value (v ^* a).

The switching control signal output unit 360 generates and outputs a switching control signal Sic for an inverter according to a pulse width modulation (PWM) method based on a single-phase output voltage command value (v ^* a).

The output inverter switching control signal Sic may be converted into a gate driving signal by a gate driver (not shown) and may be input to the gate of each switching element in the inverter 420. Accordingly, each of the switching elements Sa, S'a, Sb, S'b in the inverter 420 performs a switching operation.

8 is a diagram referred to for describing the operation of the motor.

Referring to the drawings, the single-phase motor 230 may be divided into an alignment section (Pon), an open loop section (Pop), and a closed loop section (Pcl) to operate.

During the alignment period Pon, the inverter controller 430 may control the rotor of the motor 230 to be aligned at a certain position by flowing a certain current to the motor 230. Here, the constant current may be a magnetic flux current.

Accordingly, during the alignment period Pon, the rotational speed of the motor 230 becomes 0, as shown in the figure.

Next, after the alignment period Pon, the inverter controller 430 may control the open loop period Pop to be performed while the rotational speed of the motor 230 continuously increases.

During the open loop period (Pop), as in FIG. 7, the speed command value (ω ^* _r ) continuously rises, but without feedback on the output current (io) detected by the output current detector (E), the speed command value Based only on (ω ^* _r ), the motor 230 is driven.

Next, after the open loop period Pop, the inverter controller 430 may control the closed loop period Pcl to be performed while the rotational speed of the motor 230 continuously increases.

During the closed loop period (Pcl), as shown in FIG. 7, the speed command value (ω ^* _r ) is continuously rising or variable, and the inverter control unit 430 is the output current detected by the output current detection unit (E) (io ) Is fed back, and the motor 230 can be driven based on the difference between the detected output current io and the speed command value ω ^* _r .

On the other hand, the mechanical average output of the single-phase motor 230 includes a DC component and an AC component.

This is made by the product of the current flowing through the stator of the single-phase motor 230 and the counter electromotive force, and the product of the cos component of the phase difference between these two elements. Therefore, as the phase difference between the current flowing through the stator of the single-phase motor 230 and the back electromotive force decreases, the mechanical average output increases.

In order to efficiently control the single-phase motor 230, a vector control method of instantaneously controlling the phase of the back EMF and the phase of the current is required.

Accordingly, in the present invention, it is assumed that vector control for instantaneously controlling the phase of the back EMF and the phase of the current is performed.

Meanwhile, in order to perform vector control in a sensorless manner, it is important to accurately grasp the position of the rotor of the motor 230. In particular, when the motor 230 is initially started, it is important to determine the position of the rotor of the motor 230.

On the other hand, in the case of a three-phase motor having an asymmetrical air gap, a constant magnetic field is formed when a high-frequency signal is injected, and magnetic saturation may occur, but in the case of the single-phase motor 230 having an asymmetrical air gap as shown in Figs. During injection, an alternating magnetic field is generated, so magnetic saturation may not occur.

Accordingly, in the present invention, it is assumed that the rotor position of the motor 230 is grasped at the initial start-up by using high-frequency signal injection. This will be described with reference to FIG. 9 below.

9 to 12 are views referenced for explaining the operation of the motor driving apparatus according to the embodiment of the present invention.

First, FIG. 9 is a diagram referred to for explaining injection of a high frequency voltage in the inverter control unit 430.

Referring to the drawings, the high-frequency voltage injection unit 805 in the inverter control unit 430 adds the high-frequency voltage Vinj and the DC voltage Voffset at the initial start-up to obtain the switching control signal output unit 560. Through this, the switching control signal Sic may be controlled to be output to the inverter 230.

Accordingly, the high frequency voltage Vinj and the DC voltage Voffset may be applied to the motor 230. In Equation 1 below, the inverter output voltage is illustrated.

Here, Vs_initial denotes the inverter output voltage and θinj denotes the phase angle of the high-frequency voltage signal.

The output current detection unit E can detect the output current io flowing through the motor 230.

In this case, the output current io flowing through the motor 230 may be divided into a high-frequency current Is_ing and a direct current Ioffset, as shown in the figure.

Meanwhile, the result of the multiplication operator 807 in the drawing may be expressed as Equation 2 below.

Here, Ids_inj denotes a current including high frequency and direct current.

Meanwhile, based on the output of the multiplication operator 807, the integrator 809 may detect the initial position of the motor 230 as shown in Equation 3.

Here, Im represents the magnitude of the current flowing through the motor, and Ioffset represents the direct current.

That is, the inverter control unit 430 may detect the initial position of the motor 230 based on the output current io detected by the output current detection unit E.

In particular, the inverter control unit 430 detects the magnitude of the current by integrating the output current io detected by the output current detection unit E based on the position angle of the frequency of the high-frequency voltage, and detects the magnitude of the detected current. Based on, the initial position of the motor 230 may be detected. Accordingly, it is possible to accurately detect the initial position of the single-phase motor 230. Accordingly, it is possible to drive the single-phase motor 230 in a sensorless manner.

On the other hand, as shown in the figure, the N of the magnet of the motor 230 than the current magnitude (Ssd) when the S pole (PMS) of the magnet of the motor 230 is located at the reference position of the motor 230 When the pole PMN is located, the magnitude of the detected current Sns becomes larger.

In particular, when the N pole (PMN) of the magnet of the motor 230 is located, compared to the case where the S pole (PMS) of the magnet of the motor 230 is located at the reference position of the motor 230, the detected direct current Becomes larger in size.

FIG. 10A corresponds to FIG. 4B, and when the N-pole (PMN) of the magnet of the motor 230 is positioned on the upper side, a high-frequency voltage having a magnitude of Vm and a waveform of a DC voltage having a magnitude of Voffset (Vsi ) Is applied to the motor 230.

Accordingly, as shown in (b) of FIG. 10A, an output current (Iinj + Ioffet) having a peak value of Pka may be detected. The output current may include a high-frequency current of the size of Iinj and a direct current of the size of Ioffet.

FIG. 10B corresponds to FIG. 4A, and when the S-pole (PMS) of the magnet of the motor 230 is located on the upper side, a high-frequency voltage having a magnitude of Vm and a waveform of a DC voltage having a magnitude of Voffset (Vsi ) Is applied to the motor 230.

Accordingly, as shown in (b) of FIG. 10B, an output current (Iinj + Ioffet) having a peak value of Pkb smaller than Pka may be detected. The output current may include a high-frequency current of the size of Iinj and a direct current of the size of Ioffet.

Accordingly, the inverter control unit 430 controls to apply a high-frequency voltage and a DC voltage to the motor 230 in order to detect the initial position of the motor 230, and the output current io detected by the output current detection unit E ), the initial position of the motor 230 may be detected.

Meanwhile, according to another embodiment of the present invention, the inverter control unit 430 controls to apply a high-frequency voltage and a magnetic flux voltage command value to the motor 230 to detect the initial position of the motor 230, and the output current detection unit Based on the output current io detected in (E), the initial position of the motor 230 is detected. This will be described with reference to FIG. 11.

Referring to the drawings, the voltage command generation unit 540 in the inverter control unit 430, based on the magnetic flux current command value (I ^* _d ) and the direct current (Ioffset), at the initial start-up, the magnetic flux voltage command value ( v ^* _d ) can be created.

The DC current Ioffset at this time may be a DC current in which the high frequency current is increased through the high frequency removal unit 811 from the output current io detected by the output current detection unit E.

In addition, the inverter control unit 430 sums the magnetic flux voltage command value (v ^* _d ) and the high frequency voltage (Vinj), and transmits the switching control signal Sic to the inverter 230 through the switching control signal output unit 560. ) Can be controlled.

Accordingly, the high frequency voltage Vinj and the DC voltage Voffset may be applied to the motor 230. The inverter output voltage as in Equation 1 above is illustrated.

The output current detection unit E can detect the output current io flowing through the motor 230.

In this case, the output current io flowing through the motor 230 may be divided into a high-frequency current Is_ing and a direct current Ioffset, as shown in the figure.

Meanwhile, a result of the multiplication operator 807 in the drawing may be expressed as in Equation 2 above.

On the other hand, based on the output of the multiplication operator 807, the integrator 809 may detect the initial position of the motor 230 as shown in Equation 3 above.

That is, the inverter control unit 430 may detect the initial position of the motor 230 based on the output current io detected by the output current detection unit E.

In particular, the inverter control unit 430 detects the magnitude of the current by integrating the output current io detected by the output current detection unit E based on the position angle of the frequency of the high frequency voltage, and detects the magnitude of the detected current. Based on, the initial position of the motor 230 may be detected. Accordingly, it is possible to accurately detect the initial position of the single-phase motor 230. Accordingly, it is possible to drive the single-phase motor 230 in a sensorless manner.

On the other hand, as shown in the figure, the N of the magnet of the motor 230 than the current magnitude (Ssd) when the S pole (PMS) of the magnet of the motor 230 is located at the reference position of the motor 230 When the pole PMN is located, the magnitude of the detected current Sns becomes larger.

In particular, when the N pole (PMN) of the magnet of the motor 230 is located, compared to the case where the S pole (PMS) of the magnet of the motor 230 is located at the reference position of the motor 230, the detected direct current Becomes larger in size.

On the other hand, after the additional start by the high-frequency injection described above, in the closed loop section, in order to determine the position of the rotor of the motor 230, a magnetic flux estimation technique using the magnetic flux of the motor 230 may be used.

For example, the magnetic flux estimating unit (not shown) in the inverter control unit 430 calculates a back EMF (es) based on a voltage command value (v ^* _d ) for the magnetic flux, and based on the back EMF (es), the motor ( 230), the magnetic flux can be estimated.

The magnetic flux voltage command value (v ^* _d ) is generated by the voltage command generation unit 540 of FIG. 7, and may be generated based on the current output current io.

)을 추정할 수 있다.And, the magnetic flux estimation unit (not shown), based on the calculated back electromotive force (es) and the magnetic flux voltage command value (v ^* _d ), the magnetic flux of the motor 230 (

) Can be estimated.

)을 추정하면, 모터(230)의 자속(λd)을 추정할 수 있게 된다.In this way, the magnetic flux corresponding to the magnetic flux of the motor 230 (

When) is estimated, the magnetic flux (λd) of the motor 230 can be estimated.

Eventually, the magnetic flux estimation unit 580 in the inverter control unit 430 calculates the voltage command value for the magnetic flux (v ^* _d ) based on the output current (io), and based on the voltage command value for the magnetic flux (v ^* _d ). , The back EMF (es) is calculated, and the magnetic flux (λd) of the motor 230 can be estimated based on the back EMF (es). Accordingly, it is possible to accurately estimate the magnetic flux of the motor.

)에 기초하여, 모터의 회전자 위치(

)를 연산할 수 있다.Next, the inverter control unit 430, the magnetic flux of the motor 230 estimated by the magnetic flux estimation unit (not shown) (

), based on the motor's rotor position (

) Can be calculated.

)과, 모터(230)의 속도 지령치(w^*)에 기초하여, 모터(230)의 회전자(ROT)의 위치(

)를 연산할 수 있다. 이에 따라, 단상 모터(230) 구동시 자속 추정에 기반하여 센서리스 방식으로 구동할 수 있게 된다.Specifically, the inverter control unit 430, the magnetic flux corresponding to the magnetic flux of the motor 230 (

), and the position of the rotor (ROT) of the motor 230 based on the speed command value (w ^* ) of the motor 230 (

) Can be calculated. Accordingly, when the single-phase motor 230 is driven, it can be driven in a sensorless manner based on magnetic flux estimation.

The motor driving device and the home appliance having the same according to an embodiment of the present invention are not limited to the configuration and method of the embodiments described as described above, but the above embodiments are each so that various modifications can be made. All or some of the embodiments may be selectively combined and configured.

Meanwhile, the motor driving method or the home appliance operating method of the present invention may be implemented as a code readable by the processor on a recording medium readable by a processor provided in the motor driving apparatus or the home appliance. The processor-readable recording medium includes all types of recording devices that store data that can be read by the processor.

In addition, although the preferred embodiments of the present invention have been illustrated and described above, the present invention is not limited to the specific embodiments described above, and the technical field to which the present invention belongs without departing from the gist of the present invention claimed in the claims. In addition, various modifications are possible by those of ordinary skill in the art, and these modifications should not be individually understood from the technical spirit or prospect of the present invention.

Claims (10)

A single-phase motor having an asymmetric air gap;
An inverter converting a dc terminal power into an AC power source by a switching operation and outputting the converted AC power to the single-phase motor;
An output current detector for detecting an output current flowing through the motor;
Includes; a control unit for controlling the inverter based on the detected output current,
The control unit,
For detecting the initial position of the motor, controlling to apply a high frequency voltage and a DC voltage to the motor, based on the output current detected by the output current detection unit, detects the initial position of the motor,
The control unit,
Integrating the output current detected by the output current detection unit based on the position angle of the frequency of the high-frequency voltage to detect the magnitude of the current, and detecting the initial position of the motor based on the magnitude of the detected current. Motor drive device, characterized in that. delete The method of claim 1,
The motor driving apparatus, characterized in that the magnitude of the detected current is larger when the N-pole of the magnet of the motor is positioned than the S-pole of the magnet of the motor at the reference position of the motor. The method of claim 1,
The motor driving apparatus, wherein the detected DC current has a larger magnitude when the N pole of the magnet of the motor is positioned than when the S pole of the magnet of the motor is positioned at the reference position of the motor. A single-phase motor having an asymmetric air gap;
An inverter converting a dc terminal power into an AC power source by a switching operation and outputting the converted AC power to the single-phase motor;
An output current detector for detecting an output current flowing through the motor;
Includes; a control unit for controlling the inverter based on the detected output current,
The control unit,
In order to detect the initial position of the motor, control to apply a high frequency voltage and a magnetic flux voltage command value to the motor, and detect the initial position of the motor based on the output current detected by the output current detection unit. Motor-drive unit. The method of claim 5,
The control unit,
And removing a high-frequency current from the output current detected by the output current detection unit, and generating the magnetic flux voltage command value based on the output current from which the high frequency current has been removed and the magnetic flux current command value. The method of claim 5,
The control unit,
Integrating the output current detected by the output current detection unit based on the position angle of the frequency of the high-frequency voltage to detect the magnitude of the current, and detecting the initial position of the motor based on the magnitude of the detected current. Motor drive device, characterized in that. The method of claim 7,
The motor driving apparatus, characterized in that the magnitude of the detected current is larger when the N-pole of the magnet of the motor is positioned than the S-pole of the magnet of the motor at the reference position of the motor. The method of claim 7,
The motor driving apparatus, wherein the detected DC current has a larger magnitude when the N pole of the magnet of the motor is positioned than when the S pole of the magnet of the motor is positioned at the reference position of the motor. A home appliance comprising the motor drive device of any one of claims 1 and 3 to 9.

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