KR102184546B1 - Motor driving apparatus and home appliance including the same - Google Patents

Abstract

The present invention relates to a motor driving device and a home appliance having the same. A motor driving apparatus and a home appliance having the same according to an embodiment of the present invention, a single-phase motor having a symmetrical air gap, by switching operation, converts the dc-stage power into AC power, and outputs the converted AC power to the single-phase motor And a control unit for controlling the inverter, based on the detected output current, an output current detection unit that detects an output current flowing through the motor, and the control unit includes a DC current to the motor for alignment of the motor Control to apply to. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical air gap is started.

Description

Motor driving apparatus and home appliance including the same

The present invention relates to a motor driving device and a home appliance having the same, and more particularly, to a motor driving device capable of stably performing initial alignment when starting a single-phase motor having a symmetrical air gap, and a home appliance having the same. will be.

The motor driving device is a device for driving a motor having a rotor for rotational motion and a stator wound around a coil.

Motors can be classified into Samsung motors with three-phase windings and single-phase motors with single-phase windings.

In the three-phase motor, the rotation direction can be adjusted by a current applied to the three-phase or the like, but the single-phase motor cannot adjust the rotation direction.

Accordingly, when implementing a single-phase motor, there is a method of implementing a motor driving apparatus using a sensor method such as a Hall sensor, but according to this, there is a disadvantage in that an additional cost is required.

Therefore, when driving a single-phase motor, a method of driving the motor in a sensorless method excluding the Hall sensor is being studied.

It is an object of the present invention to provide a motor driving device capable of stably performing initial alignment when starting a single-phase motor having a symmetrical air gap, and a home appliance having the same.

Another object of the present invention is to provide a motor driving apparatus capable of driving in a sensorless manner based on magnetic flux estimation when driving a single-phase motor, and a home appliance having the same.

A motor driving apparatus and a home appliance having the same according to an embodiment of the present invention to achieve the above object, a single-phase motor having a symmetrical air gap, by switching operation, converting the DC power supply into AC power, and converted AC An inverter that outputs power to the single-phase motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, the control unit, at the initial start-up, performs motor alignment. For this purpose, it controls to apply a direct current to the motor.

On the other hand, the control unit of the motor driving apparatus according to the embodiment of the present invention controls to apply a positive DC current to the motor for motor alignment during initial startup, and when the motor alignment is not performed even when the positive DC current is applied , It can be controlled to apply a negative direct current to the motor.

On the other hand, the control unit of the motor driving apparatus according to the embodiment of the present invention may control to drive the motor based on the first level of magnetic flux current command value for motor alignment during initial startup.

On the other hand, the control unit of the motor driving apparatus according to the embodiment of the present invention may control to drive the motor by setting the level of the current command value for torque to zero for motor alignment during initial startup.

Meanwhile, the control unit of the motor driving apparatus according to an exemplary embodiment of the present invention may calculate a back EMF based on a voltage command value for a magnetic flux, and estimate a magnetic flux for a motor based on the back EMF.

On the other hand, the control unit of the motor driving apparatus according to an embodiment of the present invention may calculate the back EMF based on the voltage command value for the magnetic flux and the output current, and estimate the magnetic flux for the motor based on the back EMF.

Meanwhile, the control unit of the motor driving apparatus according to an exemplary embodiment of the present invention may calculate the position of the rotor of the motor based on the estimated magnetic flux of the motor and the speed command value of the motor.

On the other hand, a motor driving apparatus and a home appliance having the same according to another embodiment of the present invention for achieving the above object, a single-phase motor having a symmetrical air gap, by switching operation, converts the DC terminal power to AC power, An inverter that outputs the converted AC power to the single-phase motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, and the control unit includes: For motor alignment, control is performed to drive the motor based on the current command value for the magnetic flux at the first level.

A motor driving apparatus and a home appliance having the same according to an embodiment of the present invention, a single-phase motor having a symmetrical air gap, by switching operation, converts the dc-stage power into AC power, and outputs the converted AC power to the single-phase motor And a control unit for controlling the inverter, based on the detected output current, an output current detection unit that detects an output current flowing through the motor, and the control unit includes a DC current to the motor for alignment of the motor Control to apply to. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical air gap is started.

Particularly, at the initial start-up, by applying a DC current instead of applying a DC voltage to align the motor, accurate alignment is possible and an overcurrent shape does not occur, so that stable alignment is possible.

On the other hand, the control unit of the motor driving device controls to apply a positive DC current to the motor for motor alignment during initial start-up, and when the motor alignment is not performed even when the positive DC current is applied, the negative DC current is applied. It can be controlled to apply to the motor. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical air gap is started.

On the other hand, the control unit of the motor driving apparatus may control to drive the motor based on the first level magnetic flux current command value for motor alignment during initial startup. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical air gap is started.

On the other hand, the control unit of the motor driving apparatus may control to drive the motor by setting the level of the current command value for torque to zero for motor alignment during initial startup. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical air gap is started.

On the other hand, the control unit of the motor driving apparatus may calculate the back electromotive force based on the voltage command value for the magnetic flux and estimate the magnetic flux for the motor based on the back electromotive force. Accordingly, it is possible to drive the single-phase motor in a sensorless manner based on magnetic flux estimation.

Meanwhile, the control unit of the motor driving apparatus may calculate a back EMF based on a voltage command value for a magnetic flux and an output current, and estimate a magnetic flux for the motor based on the back EMF. Accordingly, it is possible to drive the single-phase motor in a sensorless manner based on magnetic flux estimation.

Meanwhile, the control unit of the motor driving apparatus may calculate the position of the rotor of the motor based on the estimated magnetic flux of the motor and the speed command value of the motor. Accordingly, it is possible to drive the single-phase motor in a sensorless manner based on magnetic flux estimation.

On the other hand, the motor driving device and the home appliance having the same according to another embodiment of the present invention, a single-phase motor having a symmetrical air gap, by switching operation, converts the dc power supply to AC power, and converts the converted AC power to single phase An inverter that outputs to the motor, an output current detection unit that detects an output current flowing through the motor, and a control unit that controls the inverter based on the detected output current, the control unit, at the time of initial startup, to align the motor, It controls to drive a motor based on the current command value for magnetic flux of 1 level. Accordingly, it is possible to stably perform initial alignment when the single-phase motor having a symmetrical gap is started.

1 is a side elevation view showing a state of use of a cleaner according to an embodiment of the present invention.
FIG. 2 is a perspective view of a cleaner from which the nozzle module is removed from FIG. 1.
3 is a side elevation view of the cleaner of FIG. 2.
4A and 4B are views showing the suction motor of FIG. 3.
5 illustrates an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention.
6 is an example of an internal circuit diagram of the motor driving apparatus of FIG. 5.
7 is an internal block diagram of the inverter controller of FIG. 6.
8 is a diagram referred to for describing the operation of the motor.
9 to 12 are views referenced for explaining the operation of the motor driving apparatus according to the embodiment of the present invention.

Hereinafter, the present invention will be described in more detail with reference to the drawings.

The suffixes "module" and "unit" for the constituent elements used in the following description are given in consideration of only the ease of writing in the present specification, and do not impart a particularly important meaning or role by themselves. Therefore, the "module" and "unit" may be used interchangeably with each other.

The home appliance described herein refers to a home appliance that includes a single-phase motor and is driven according to an operation of the single-phase motor. For example, the home appliance may be variously exemplified such as a vacuum cleaner, a hair dryer, an electric fan, a washing machine, an air purifier, an air conditioner, a water purifier, a refrigerator, and a vehicle. Hereinafter, a vacuum cleaner among home appliances will be described.

1 is a side elevational view showing a state of use of a cleaner according to an embodiment of the present invention, FIG. 2 is a perspective view of a cleaner with a nozzle module removed from FIG. 1, and FIG. 3 is a side elevation view of the cleaner of FIG. 2.

1 to 3, the cleaner 100 according to an embodiment of the present invention includes a main body 10 and a main body 10 forming a flow path P for guiding suctioned air to be discharged to the outside. ), the handle 30 coupled to the rear side of the main body 10, the nozzle module 70 detachably connected to the suction unit 11 of the main body 10, a battery Bt for supplying power, and a battery Bt. A fan module 50 disposed on the battery housing 40 and the flow path P to move air in the flow path may be provided.

The nozzle module 70 may include a nozzle unit 71 provided to suck in external air and an extension pipe 73 extending from the nozzle unit 71.

The extension pipe 73 connects the nozzle part 71 and the suction part 11. The extension pipe 73 guides the air sucked in from the nozzle part 71 to flow into the suction flow path P. One end of the extension pipe 73 may be detachably coupled to the suction part 11 of the main body 10. The user can clean while holding the handle 30 and moving the nozzle 71 while placing the nozzle 71 on the floor.

The main body 10 includes an exhaust cover 12 forming an exhaust port 10a, a dust collecting unit 13 for storing separated dust, and a fan module housing 14 accommodating the fan module 50 therein. It may include.

The discharge cover 12 may form an upper surface of the main body 10. The exhaust cover 12 covers the upper side of the fan module housing 14.

The dust collection part 13 may be formed in a cylindrical shape. The dust collecting part 13 may be disposed under the fan module housing 14. Accordingly, a storage space for dust may be formed inside the dust collection unit 13.

The fan module housing 14 may be formed to extend upward from the dust collection unit 13. The fan module housing 14 is formed in a cylindrical shape. The extended portion 31 of the handle 30 may be disposed on the rear side of the fan module housing 14.

In the fan module housing 14, a fan module 50 may be disposed.

The fan module 50 includes a suction motor 230 that rotates the impeller 51. The suction motor 230 may be located above the dust separation unit 20.

The impeller 51 may be disposed under the suction motor 230. The impeller 51 is coupled with the suction motor 230 and rotates by the rotational force of the suction motor 230.

Meanwhile, the impeller 510 may pressurize the air by rotation so that the air in the flow path P is discharged through the exhaust port 10a.

Meanwhile, the cleaner 100 may include a motor driving unit 220 for controlling the suction motor 230. The motor driving unit 220 may be disposed between the suction motor 230 and the dust collecting unit 13. Meanwhile, the motor driving unit 220 may include circuit elements disposed on a PCB circuit board.

The handle 30 extends in the vertical direction and includes an additional extension 32. The additional extension part 32 may be spaced apart from the main body 10 in the front-rear direction. The user can use the vacuum cleaner 100 while holding the additional extension 32. The upper end of the additional extension 32 is connected to the rear end of the extension 31. The lower end of the additional extension 32 is connected to the battery housing 40.

The additional extension part 32 is provided with a movement limiting part 32a to prevent the hand from moving in the longitudinal direction (up and down direction) of the additional extension part 32 while the user holds the additional extension part 32 Can be. The movement limiting part 32a may protrude forward from the additional extension part 32.

The movement limiting part 32a is disposed to be spaced apart from the extension part 31 vertically. While the user holds the additional extension part 32, some fingers of the user's hand are positioned above the movement limiting part 32a, and the other fingers are provided to be located below the movement limiting part 32a.

The handle 30 may include an inclined surface 33 facing the direction between the upper side and the rear side. The inclined surface 33 may be positioned at the rear of the extension 31. The input unit 3 may be disposed on the inclined surface 33.

The battery Bt may supply power to the fan module 50. The battery Bt may supply power to the noise control module. The battery Bt may be detachably disposed inside the battery housing 40.

The battery housing 40 is coupled to the rear side of the main body 10. The battery housing 40 is disposed under the handle 30. The battery Bt is accommodated in the battery housing 40. A heat dissipation hole for discharging heat generated from the battery Bt to the outside may be formed in the battery housing 40.

Meanwhile, the exhaust port 10a may be disposed to face a specific direction (eg, upward direction). The plurality of exhaust ports 10a may be divided from each other in the circumferential direction by a plurality of exhaust guides 12a. The plurality of exhaust ports 10a may be arranged at predetermined intervals apart from each other along the circumferential direction.

4A and 4B are views showing the suction motor of FIG. 3.

Referring to the drawings, the suction motor 230 according to the embodiment of the present invention may include a rotor (ROT) and a stator (STA).

The rotor ROT may include a rotor core PCO and a magnet PM formed on the outer periphery of the rotor core PCO. The magnet (PM) is formed in a circular shape, and may be provided with an S pole (PMS) and an N pole (PMN), respectively.

Meanwhile, in FIG. 4A, it is illustrated that the S pole (PMS) faces upward, and in FIG. 4B, it is illustrated that the S pole (PMS) faces downward.

The stator (STA) includes stator frames (SFRa, SFRb) formed on both sides (upper and lower sides) of the rotor (ROT), and coils (CLa, CLb) wound around the stator frames (SFRa, SFRb), respectively. can do.

On the other hand, since the stator frames (SFRa, SFRb) are arranged on the upper and lower sides of the rotor (ROT), between the magnet (PM) of the rotor (ROT) and the stator frames (SFRa, SFRb), a symmetrical air gap (ARG) ) Can be formed.

As described above, the suction motor 230 according to an embodiment of the present invention may be a brushless DC (BLDC) single-phase motor having a symmetrical air gap.

The motor driving apparatus described in this specification is capable of estimating the rotor position of the motor by a sensorless method, which does not include a position detection unit such as a hall sensor for sensing the rotor position of the motor. It is a possible motor drive. Hereinafter, a sensorless motor driving device will be described.

5 illustrates an example of an internal block diagram of a motor driving apparatus according to an embodiment of the present invention, and FIG. 6 is an example of an internal circuit diagram of the motor driving apparatus of FIG. 5.

Referring to the drawings, the motor driving apparatus 220 according to an embodiment of the present invention is for driving the single-phase motor 230 and may include an inverter 420 and an inverter control unit 430.

In addition, the motor driving apparatus 220 according to an embodiment of the present invention may include a converter 410, a dc terminal voltage detection unit (B), a dc terminal capacitor (C), and an output current detection unit (E). In addition, the driving unit 220 may further include an input current detection unit A and the like.

Hereinafter, operations of each of the constituent units in the motor driving apparatus 220 of FIGS. 5 and 6 will be described.

The input current detection unit A may detect an input current i _s input from the battery BT. To this end, as the input current detection unit A, a current trnasformer (CT), a shunt resistor, or the like may be used. The detected input current i _s is a pulsed discrete signal and may be input to the inverter controller 430.

The converter 410 may convert the level of the battery power Vs from the battery BT to output the level-converted DC power. To this end, the converter 410 may include a switching element. Meanwhile, the converter 410 may be omitted.

The dc terminal capacitor C may store input power. In addition, the input power can be smoothed.

Meanwhile, since DC power is stored at both ends of the DC terminal capacitor C, this may be referred to as a dc terminal or a dc link terminal.

The dc terminal voltage detector B may detect the dc terminal voltage Vdc, which is both ends of the dc terminal capacitor C. To this end, the dc terminal voltage detection unit B may include a resistance element, an amplifier, and the like. The detected dc voltage Vdc may be input to the inverter controller 430 as a discrete signal in the form of a pulse.

The inverter 420 includes a plurality of inverter switching elements, and converts the DC power supply (Vdc) of the dc stage into a single phase AC power supply (va) of a predetermined frequency by an on/off operation of the switching element, and a single phase synchronous motor It can be output to 230.

In the inverter 420, a pair of upper-arm switching elements (Sa, Sb) and lower-arm switching elements (S'a, S'b) connected in series with each other, respectively, and a total of two pairs of upper and lower arm switching elements are parallel to each other ( It is connected to Sa&S'a,Sb&S'b). Diodes are connected in reverse parallel to each of the switching elements Sa, S'a, Sb, S'b.

The switching elements in the inverter 420 perform on/off operations of each switching element based on the inverter switching control signal Sic from the inverter controller 430. As a result, single-phase AC power having a predetermined frequency is output to the single-phase synchronous motor 230.

The inverter controller 430 may control a switching operation of the inverter 420 based on a sensorless method. To this end, the inverter control unit 430 may receive an output current i _o detected by the output current detection unit E.

The inverter controller 430 outputs an inverter switching control signal Sic to the inverter 420 in order to control the switching operation of the inverter 420. The inverter switching control signal Sic is a switching control signal of the pulse width modulation method (PWM), and is generated and output based on the output current i _o detected by the output current detection unit E. A detailed operation of the output of the inverter switching control signal Sic in the inverter control unit 430 will be described later with reference to FIG. 7.

The output current detection unit E detects an output current i _o flowing between the inverter 420 and the single-phase motor 230. That is, the current flowing through the motor 230 is detected.

The output current detection unit E may be located between the inverter 420 and the motor 230, and for current detection, a current trnasformer (CT), a shunt resistor, or the like may be used. Alternatively, the output current detection unit E may include a shunt resistor disposed between the dc terminal capacitor C and the inverter 420.

The detected output current i _o may be applied to the inverter control unit 430 as a discrete signal in the form of a pulse, and the inverter switching control signal Sic based on the detected output current i _o Is created. Hereinafter, it may be described in parallel that the detected output current i _o is the single-phase output current io.

Meanwhile, the single-phase motor 230 includes a stator and a rotor, and single-phase AC power having a predetermined frequency is applied to the coil of the single-phase stator, so that the rotor rotates.

Such a single-phase motor 230 is, for example, a surface-mounted permanent magnet synchronous motor (Surface-Mounted Permanent-Magnet Synchronous Motor; SMPMSM), a built-in permanent magnet synchronous motor (Interior Permanent Magnet Synchronous Motor; IPMSM), and synchronous It may include a reluctance motor (Synchronous Reluctance Motor; Synrm) or the like. Among them, SMPMSM and IPMSM are Permanent Magnet Synchronous Motor (PMSM), and Synrm is characterized by no permanent magnet.

7 is an internal block diagram of the inverter controller of FIG. 6.

Referring to FIG. 7, the inverter control unit 430 includes an axis conversion unit 310, a speed calculation unit 320, a current command generation unit 330, a voltage command generation unit 340, an axis conversion unit 350, and A switching control signal output unit 360 may be included.

The axis conversion unit 310 receives the single-phase output current io or ia detected by the output current detection unit E and converts it into two-phase currents iα and iβ of the stationary coordinate system.

Meanwhile, the axis conversion unit 310 may convert the two-phase currents iα and iβ of the stationary coordinate system into the two-phase currents id and iq of the rotational coordinate system.

)와 연산된 속도(

)를 출력할 수 있다.The speed calculation unit 320 is based on the two-phase current (iα, iβ) of the stationary coordinate system axis-changed by the axis conversion unit 310, the calculated position (

) And calculated speed (

) Can be printed.

)와 속도 지령치(ω^* _r)에 기초하여, 전류 지령치(i^* _q)를 생성한다. 예를 들어, 전류 지령 생성부(330)는, 연산 속도(

)와 속도 지령치(ω^* _r)의 차이에 기초하여, PI 제어기(335)에서 PI 제어를 수행하며, 전류 지령치(i^* _q)를 생성할 수 있다. 도면에서는, 전류 지령치로, q축 전류 지령치(i^* _q)를 예시하나, 도면과 달리, d축 전류 지령치(i^* _d)를 함께 생성하는 것도 가능하다. 한편, d축 전류 지령치(i^* _d)의 값은 0으로 설정될 수도 있다. On the other hand, the current command generation unit 330, the calculation speed (

) And the speed command value (ω ^* _r ), the current command value (i ^* _q ) is generated. For example, the current command generation unit 330, the calculation speed (

) And the speed command value (ω ^* _r ), the PI controller 335 performs PI control, and a current command value (i ^* _q ) can be generated. In the drawing, the q-axis current command value (i ^* _q ) is illustrated as the current command value, but unlike the drawing, it is also possible to generate the d-axis current command value (i ^* _d ) together. Meanwhile, the value of the d-axis current command value (i ^* _d ) may be set to 0.

Meanwhile, the current command generation unit 330 may further include a limiter (not shown) that limits the level so that the current command value i ^* _q does not exceed the allowable range.

Next, the voltage command generation unit 340 includes the d-axis and q-axis currents (i _d , i _q ) that have been axially transformed from the axis conversion unit into a two-phase rotational coordinate system, and a current command value in the current command generation unit 330, etc. Based on i ^* _d ,i ^* _q ), the d-axis and q-axis voltage command values (v ^* _d ,v ^* _q ) are generated. For example, the voltage command generation unit 340 performs PI control in the PI controller 344 based on the difference between the q-axis current (i _q ) and the q-axis current command value (i ^* _q ), and q It is possible to generate the axis voltage command value (v ^* _q ). In addition, the voltage command generation unit 340 performs PI control in the PI controller 348 based on the difference between the d-axis current (i _d ) and the d-axis current command value (i ^* _d ), and the d-axis voltage You can create a setpoint (v ^* _d ). Meanwhile, the voltage command generation unit 340 may further include a limiter (not shown) that limits the level of the d-axis and q-axis voltage command values (v ^* _d , v ^* _q ) to not exceed the allowable range. .

On the other hand, the generated d-axis and q-axis voltage command values (v ^* _d and v ^* _q ) are input to the axis conversion unit 350.

)와, d축, q축 전압 지령치(v^* _d,v^* _q)를 입력받아, 축변환을 수행한다.The axis conversion unit 350 is a position calculated by the speed calculation unit 320 (

) And the d-axis and q-axis voltage command values (v ^* _d ,v ^* _q ) and perform axis transformation.

)가 사용될 수 있다.First, the axis conversion unit 350 converts from a two-phase rotation coordinate system to a two-phase stationary coordinate system. At this time, the position calculated by the speed calculating unit 320 (

) Can be used.

In addition, the axis conversion unit 350 converts from a two-phase stationary coordinate system to a single-phase stationary coordinate system. Through this conversion, the axis conversion unit 1050 outputs a single-phase output voltage command value (v ^* a).

The switching control signal output unit 360 generates and outputs a switching control signal Sic for an inverter according to a pulse width modulation (PWM) method based on a single-phase output voltage command value (v ^* a).

The output inverter switching control signal Sic may be converted into a gate driving signal by a gate driver (not shown) and may be input to the gate of each switching element in the inverter 420. Accordingly, each of the switching elements Sa, S'a, Sb, S'b in the inverter 420 performs a switching operation.

8 is a diagram referred to for describing the operation of the motor.

Referring to the drawings, the single-phase motor 230 may be divided into an alignment section (Pon), an open loop section (Pop), and a closed loop section (Pcl) to operate.

During the alignment period Pon, the inverter controller 430 may control the rotor of the motor 230 to be aligned at a certain position by flowing a certain current to the motor 230. Here, the constant current may be a magnetic flux current.

Accordingly, during the alignment period Pon, the rotational speed of the motor 230 becomes 0, as shown in the figure.

Next, after the alignment period Pon, the inverter controller 430 may control the open loop period Pop to be performed while the rotational speed of the motor 230 continuously increases.

During the open loop period (Pop), as in FIG. 7, the speed command value (ω ^* _r ) continuously rises, but without feedback on the output current (io) detected by the output current detection unit (E), the speed command value Based only on (ω ^* _r ), the motor 230 is driven.

Next, after the open loop period Pop, the inverter controller 430 may control the closed loop period Pcl to be performed while the rotational speed of the motor 230 continuously increases.

During the closed loop period (Pcl), as shown in FIG. 7, the speed command value (ω ^* _r ) is continuously rising or variable, and the inverter control unit 430 is the output current detected by the output current detection unit (E) (io ) Is fed back, and the motor 230 can be driven based on the difference between the detected output current io and the speed command value ω ^* _r .

On the other hand, the mechanical average output of the single-phase motor 230 includes a DC component and an AC component.

This is made by the product of the current flowing through the stator of the single-phase motor 230 and the counter electromotive force, and the product of the cos component of the phase difference between these two elements. Therefore, as the phase difference between the current flowing through the stator of the single-phase motor 230 and the back electromotive force decreases, the mechanical average output increases.

In order to efficiently control the single-phase motor 230, a vector control method of instantaneously controlling the phase of the back EMF and the phase of the current is required.

Accordingly, in the present invention, it is assumed that vector control for instantaneously controlling the phase of the back EMF and the phase of the current is performed.

Meanwhile, in order to perform vector control in a sensorless method, it is important to align the rotor of the motor 230 to a predetermined position during initial startup.

On the other hand, in the case of the single-phase motor 230 having a symmetrical void, since it is not an asymmetrical void, a high-frequency injection technique or the like cannot be utilized.

Meanwhile, in the single-phase motor 230 having a symmetrical air gap, when a DC voltage is applied for motor alignment, an accurate alignment operation is impossible and an overcurrent phenomenon occurs, thereby increasing the possibility of starting failure.

Accordingly, in the present invention, in the single-phase motor 230 having a symmetrical air gap, for motor alignment, a popular technique of direct current is used. This will be described with reference to FIG. 9 below.

9 to 12 are views referenced for explaining the operation of the motor driving apparatus according to the embodiment of the present invention.

First, FIG. 9 is a diagram illustrating an internal block diagram of the voltage command generation unit 540 in the inverter control unit 430.

Referring to the drawings, the voltage command generation unit 540 may include a PI controller 544 for generating a q-axis voltage command and a PI controller 548 for generating a d-axis voltage command.

The inverter control unit 430 according to an embodiment of the present invention may control to apply a DC current to the motor 230 for alignment of the motor 230 during initial startup.

In particular, the voltage command generation unit 540 in the inverter control unit 430 drives the motor 230 based on the current command value for the magnetic flux of the first level Spu to align the motor 230 during initial startup. Can be controlled to do.

At this time, the voltage command generation unit 540 in the inverter control unit 430 controls to drive the motor 230 by setting the level of the current command value for torque to zero for alignment of the motor 230 during initial startup. I can. According to this, by setting the level of the current command value for torque to zero, it is possible to control so as to minimize the movement of the rotor position of the motor during motor alignment.

FIG. 10A illustrates that the boundary between the S-pole PMS and the N-pole PMN of the rotor ROT of the motor coincides with the axis.

On the other hand, FIG. 10A illustrates that the axis, which is the boundary between the S-pole PMS and the N-pole PMN, of the rotor ROT of the motor coincides with the reference ref.

On the other hand, FIG. 10(b) shows that a direct current, in particular a magnetic flux current, is applied to the motor 230 for motor alignment, so that the S pole (PMS) and the N pole (PMN) of the rotor (ROT) of the motor are applied. ), the axis, which is the boundary, is moved by θ to the left to maintain θ, which is a constant angle from the reference (ref). Accordingly, the initial alignment can be stably performed when the single-phase motor 230 having a symmetrical gap is started.

Particularly, at the initial start-up, by applying a DC current instead of applying a DC voltage for alignment of the motor 230, accurate alignment is possible and an overcurrent shape does not occur, so that stable alignment is possible.

Meanwhile, the inverter control unit 430 of the motor driving device 220 controls to apply a positive DC current to the motor 230 for alignment of the motor 230 at the initial start-up, and even when the positive DC current is applied, the motor (230) When the alignment is not performed, it may be controlled to apply a negative direct current to the motor 230. This will be described with reference to FIGS. 11A to 11B.

11A illustrates that a positive direct current iana is applied to the motor 230 for alignment of the motor 230 during initial startup.

When the motor alignment is completed by application of a positive direct current iana, an instantaneous current change occurs during alignment.

The inverter control unit 430 may detect an instantaneous current change during alignment based on the output current io detected by the output current detection unit E and determine that alignment is complete.

On the other hand, when motor alignment is not completed due to the application of a positive direct current iana, there may be no current change.

The inverter control unit 430 may determine that alignment is not completed when there is no current change, based on the output current io detected by the output current detection unit E.

Accordingly, as shown in FIG. 11B, the inverter control unit 430 may control to apply a negative direct current inb to the motor 230 after the positive direct current iana.

In this way, by applying a direct current of negative polarity opposite to the positive polarity, a magnetic field is formed in the opposite direction, and thus, initial alignment of the motor 230 can be stably performed.

After such initial alignment, as shown in FIG. 8, the motor 230 can operate through an open loop and a closed loop section. In particular, in the closed loop section, the motor 230 may be driven by a sensorless vector control.

At this time, for vector control in a sensorless method, in the present invention, it is assumed that the rotor position calculation of the motor 230 based on magnetic flux estimation is performed. This will be described with reference to the contents of FIG. 12.

12 is a diagram illustrating an internal block diagram of the magnetic flux estimating unit 580 in the inverter control unit 430.

Referring to the drawings, the inverter control unit 430 calculates the voltage command value (v ^* _d ) for the magnetic flux based on the current command value for the magnetic flux and the output current (ia), and calculates the voltage command value for the magnetic flux (v ^* _d ). Based on the switching control signal output unit 550, the inverter switching control signal Sic may be output to the inverter 420.

On the other hand, the magnetic flux estimating unit 580 in the inverter control unit 430 calculates the back EMF (es) based on the voltage command value (v ^* _d ) for the magnetic flux, and based on the back EMF (es), the motor 230 The magnetic flux can be estimated.

Specifically, the magnetic flux estimating unit 580 in the inverter control unit 430 is based on the magnetic flux voltage command value (v ^* _d ) and the output current (ia or io) detected by the output current detection unit E, the back electromotive force ( es) is calculated, and the magnetic flux of the motor 230 can be estimated based on the back electromotive force (es).

The magnetic flux voltage command value (v ^* _d ) is generated by the voltage command generation unit 540 of FIG. 7, and may be generated based on the current output current io.

Meanwhile, Rs in FIG. 12 represents the stator resistance of the motor 230, and Ls represents the stator inductance of the motor 230.

The first calculator 581 in the magnetic flux estimating unit 580 is obtained by multiplying the magnetic flux voltage command value (v ^* _d ) and the magnetic flux voltage command value (v ^* _d ) by the stator resistance Rs of the motor 230. Based on the difference in values, back electromotive force (es) may be calculated.

)을 추정할 수 있다.And, the magnetic flux estimating unit 580, based on the calculated back electromotive force (es) and the magnetic flux voltage command value (v ^* _d ), the magnetic flux of the motor 230 (

) Can be estimated.

)을 추정할 수 있다.Specifically, the back electromotive force calculation unit 582 in the magnetic flux estimating unit 580 calculates using a proportional gain factor, an integral gain factor, and the like, and the second calculator 581 is the output of the back EMF calculation unit 582 and the magnetic flux. Based on the difference in the value obtained by multiplying the voltage command value (v ^* _d ) by the stator inductance (Ls) of the motor 230, the magnetic flux corresponding to the magnetic flux of the motor 230 (

) Can be estimated.

)을 추정하면, 모터(230)의 자속(λd)을 추정할 수 있게 된다.In this way, the magnetic flux corresponding to the magnetic flux of the motor 230 (

When) is estimated, the magnetic flux (λd) of the motor 230 can be estimated.

Eventually, the magnetic flux estimation unit 580 in the inverter control unit 430 calculates the voltage command value for the magnetic flux (v ^* _d ) based on the output current (io), and based on the voltage command value for the magnetic flux (v ^* _d ). , The back EMF (es) is calculated, and the magnetic flux (λd) of the motor 230 can be estimated based on the back EMF (es). Accordingly, it is possible to accurately estimate the magnetic flux of the motor.

Meanwhile, a graph representing the magnetic flux λa of the motor 230 estimated by the magnetic flux estimating unit 580 is illustrated as shown in the drawing. In this case, in some regions 1010, the level of the magnetic flux λa may be uneven.

)에 기초하여, 모터의 회전자 위치(

)를 연산할 수 있다.Next, the inverter control unit 430, the magnetic flux of the motor 230 estimated by the magnetic flux estimating unit 580 (

), based on the motor's rotor position (

) Can be calculated.

)과, 모터(230)의 속도 지령치(w^*)에 기초하여, 모터(230)의 회전자(ROT)의 위치(

)를 연산할 수 있다. Specifically, the inverter control unit 430, the magnetic flux corresponding to the magnetic flux of the motor 230 (

), and the position of the rotor (ROT) of the motor 230 based on the speed command value (w ^* ) of the motor 230 (

) Can be calculated.

Meanwhile, the position calculation of the rotor ROT may be performed by the position calculation unit 520 of FIG. 7.

)과, 모터(230)의 속도 지령치(w^*)에 기초하여, 토크분 자속(

)을 연산할 수 있다. Inverter control unit 430, the magnetic flux (

) And, based on the speed command value (w ^* ) of the motor 230, the magnetic flux (

) Can be calculated.

)과, 토크분 자속(

)에 대한 아크탄젠트 연산을 통해, 모터(230)의 회전자(ROT)의 위치(

)를 연산할 수 있다. 이에 따라, 단상 모터(230) 구동시 자속 추정에 기반하여 센서리스 방식으로 안정적으로 구동할 수 있게 된다.And, the position calculating unit 520, the calculated magnetic flux magnetic flux (

) And magnetic flux for torque (

) Through the arc tangent operation, the position of the rotor (ROT) of the motor 230 (

) Can be calculated. Accordingly, it is possible to stably drive the single-phase motor 230 in a sensorless manner based on magnetic flux estimation when driving the single-phase motor 230.

The motor driving device and the home appliance having the same according to an embodiment of the present invention are not limited to the configuration and method of the embodiments described as described above, but the above embodiments are each so that various modifications can be made. All or some of the embodiments may be selectively combined and configured.

Meanwhile, the motor driving method or the home appliance operating method of the present invention may be implemented as a code readable by the processor on a recording medium readable by a processor provided in the motor driving apparatus or the home appliance. The processor-readable recording medium includes all types of recording devices that store data that can be read by the processor.

In addition, although the preferred embodiments of the present invention have been illustrated and described above, the present invention is not limited to the specific embodiments described above, and the technical field to which the present invention belongs without departing from the gist of the present invention claimed in the claims. In addition, various modifications are possible by those of ordinary skill in the art, and these modifications should not be individually understood from the technical spirit or prospect of the present invention.

Claims (10)

A single-phase motor having a symmetrical air gap;
An inverter converting a dc terminal power into an AC power source by a switching operation and outputting the converted AC power to the single-phase motor;
An output current detector for detecting an output current flowing through the motor;
Includes; a control unit for controlling the inverter based on the detected output current,
The control unit,
At initial start-up, for motor alignment, control to apply a direct current to the motor,
The control unit,
At initial start-up, for motor alignment, when controlling to apply a positive DC current to the motor for a first period, and when an instantaneous current change occurs in the output current flowing through the motor by the application of the positive DC current, After the first period, control not to apply a negative direct current,
When an instantaneous current change does not occur in the output current flowing through the motor due to the application of the positive direct current during the first period, the negative direct current is applied to the negative direct current during a second period after the first period. A motor driving device, characterized in that the control is applied to the motor. delete The method of claim 1,
The control unit,
At the time of initial start-up, for motor alignment, the motor driving apparatus is controlled to drive the motor based on a current command value for magnetic flux at the first level. The method of claim 3,
The control unit,
At initial start-up, for motor alignment, the motor driving apparatus is controlled to drive the motor by setting the level of the current command value for torque to zero. The method of claim 1,
The control unit,
A motor driving apparatus comprising: calculating a back electromotive force based on a voltage command value corresponding to a magnetic flux, and estimating a magnetic flux corresponding to the magnetic flux of the motor based on the back electromotive force. The method of claim 1,
The control unit,
A motor driving apparatus comprising: calculating a back electromotive force based on a voltage command value for a magnetic flux and the output current, and estimating a magnetic flux corresponding to the magnetic flux of the motor based on the back electromotive force. The method of claim 5,
The control unit,
And calculating the position of the rotor of the motor based on the estimated magnetic flux of the motor and the speed command value of the motor. A single phase motor having a symmetrical air gap;
An inverter converting a DC terminal power source into an AC power source by a switching operation and outputting the converted AC power source to the single-phase motor;
An output current detector for detecting an output current flowing through the motor;
Includes; a control unit for controlling the inverter based on the detected output current,
The control unit,
At the time of initial startup, for motor alignment, based on a first level magnetic flux current command value of positive polarity for a first period, control to drive the motor, and based on the first level magnetic flux current command value of positive polarity , When an instantaneous current change occurs in the output current flowing through the motor, after the first period, control not to drive the motor based on a magnetic flux current command value of a second level of negative polarity,
When an instantaneous current change does not occur in the output current flowing through the motor by the first level magnetic flux current command value of the positive polarity during the first period, during a second period after the first period, the negative A motor driving apparatus comprising controlling to drive the motor based on a current command value for the magnetic flux of the second level of polarity. The method of claim 8,
The control unit,
At initial start-up, for motor alignment, the motor driving apparatus is controlled to drive the motor by setting the level of the current command value for torque to zero. A home appliance comprising the motor drive device of any one of claims 1 and 3 to 9.

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