JPWO2016163027A1 - Radar equipment - Google Patents

Abstract

A pulse modulator (203) that generates a pulse signal, a transmitter (101) that generates a transmission signal from the pulse signal, an antenna element (102) that radiates the transmission signal into the air, and a reception signal reflected by the target A plurality of antenna elements (204) for receiving, a phase shifter (205) for converting received received signals to different frequencies, and an adder (adding each converted received signal to generate a received video signal) 206), an A / D converter (208) for A / D converting the added received video signal, a frequency domain converter (301) for converting the A / D converted received video signal into a frequency domain, A target candidate detection unit (302) that detects a target candidate from the signal power of the converted received video signal, and a target candidate direction calculation unit (303) that calculates the direction of the target candidate from the detection result.

Description

  The present invention relates to a radar apparatus that searches for a target to be observed.

  Conventionally, a radar apparatus using DBF (Digital Beam Forming) that performs signal processing by forming a plurality of antenna patterns by digital signal processing is known (see, for example, Non-Patent Document 1). In this radar apparatus, an A / D converter is installed for each antenna element. Thereby, the reception signal received by each antenna element can be input to the digital signal processor, and a plurality of antenna patterns can be formed by the digital signal processor. Therefore, it is possible to perform signal processing when a plurality of directions are directed, and it is possible to detect a target of the directions.

IEICE, “Revised Radar Technology”, 11.5.2

  Thus, in the conventional radar apparatus, an A / D converter is installed for each antenna element. Therefore, there is a problem that the H / W scale increases. Further, when searching for a plurality of directions, there is a problem that the amount of calculation when forming an antenna pattern of a plurality of directions by digital signal processing becomes enormous.

  The present invention has been made in order to solve the above-described problems, and provides a radar apparatus that can reduce the H / W scale and can search for a plurality of directions with a low calculation amount compared to the conventional configuration. It is intended to provide.

  A radar apparatus according to the present invention includes a pulse signal generator that generates a pulse signal, a transmitter that generates a transmission signal from the pulse signal generated by the pulse signal generator, and the transmission signal generated by the transmitter in the air. Radiating transmit antenna elements, multiple receive antenna elements that receive signals radiated from the transmit antenna elements and reflected by the target as received signals, and convert received signals received by the respective receive antenna elements to different frequencies A frequency converter that adds the received signals converted by the frequency converter to generate a received video signal, and an A / D converter that A / D converts the received video signal added by the adder A frequency domain converter that converts the received video signal A / D converted by the A / D converter into a frequency domain, and a frequency domain converter. A target candidate detection unit that detects a target candidate from the signal power of the received video signal, and a target candidate direction calculation unit that calculates the direction of the target candidate from the detection result by the target candidate detection unit. is there.

  According to this invention, since it comprised as mentioned above, a H / W scale can be reduced with respect to a conventional structure, and a several azimuth | direction can be searched with low computational complexity.

It is a figure which shows the structural example of the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure which shows the hardware structural example of the radar apparatus which concerns on Embodiment 1 of this invention. It is a flowchart which shows the example of transmission operation | movement of the transmission signal of the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure which shows an example of the relationship between the pulse repetition period calculated by the parameter calculator in Embodiment 1 of this invention, and a pulse width. It is a figure explaining an example of the influence on the discrete Fourier transform result by the relationship between a pulse repetition period and a pulse width, (a) It is a figure which shows the case where a pulse repetition period is an integral multiple of a pulse width, (b) It is a figure which shows the case where a pulse repetition period is not an integral multiple of a pulse width. It is a flowchart which shows the example of receiving operation of the received signal of the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure which shows an example of the relationship of the phase of the received signal received by each antenna element in Embodiment 1 of this invention. It is a figure which shows an example of the space | interval of the received signal frequency-converted with the phase shifter in Embodiment 1 of this invention, (a) It is a figure which shows the case of an angular frequency domain, (b) The case of a time domain FIG. It is a figure which shows an example of the received video signal added by the adder in Embodiment 1 of this invention, (a) It is a figure which shows the case where there is no addition of a load, (b) Addition of a load (Humming window) It is a figure which shows the case where there exists. It is a flowchart which shows the signal processing operation example by the signal processor in Embodiment 1 of this invention. It is a figure which shows an example of the relationship between the angular frequency and directivity direction in the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure explaining an example of the time division antenna pattern formation in the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure explaining an example of the influence on the distance measurement performance by the relationship between the period of an angular frequency, and a pulse width. It is a figure which shows an example of the processing result of the radar apparatus which concerns on Embodiment 1 of this invention. It is a figure which shows the structural example of the radar apparatus which concerns on Embodiment 2 of this invention. It is a figure explaining an example of the influence on the discrete Fourier-transform result by the relationship between a pulse repetition period and a pulse width.

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.
Embodiment 1 FIG.
1 is a diagram showing a configuration example of a radar apparatus according to Embodiment 1 of the present invention.
As shown in FIG. 1, the radar apparatus includes a transmitter 1, a receiver 2, a signal processor 3, and a display 4.

  The transmission unit 1 includes a transmitter 101 and an antenna element (transmission antenna element) 102.

  The transmitter 101 generates a transmission signal using a pulse signal from a pulse modulator 203 (described later) of the reception unit 2. A transmission signal generated by the transmitter 101 is output to the antenna element 102.

  The antenna element 102 radiates a transmission signal (radio wave) from the transmitter 101 into the air.

  The receiving unit 2 includes a local oscillator 201, a parameter calculator 202, a pulse modulator (pulse signal generator) 203, a plurality of antenna elements (receiving antenna elements) 204 (204-1 to 204-M), and a plurality of phase shifters. (Frequency conversion unit) 205 (205-1 to 205-M), an adder 206, a mixer 207, and a single A / D converter 208 are included.

  The local oscillator 201 generates a local oscillation signal. The local oscillation signal generated by the local oscillator 201 is output to the pulse modulator 203 and the mixer 207.

  The parameter calculator 202 calculates a pulse repetition period (PRI) and a pulse width, which are parameters of the pulse signal generated by the pulse modulator 203. The parameter calculator 202 calculates an angular frequency used by the phase shifter 205 from the calculated pulse width. Information indicating the pulse repetition period and pulse width calculated by the parameter calculator 202 is output to the pulse modulator 203, and information indicating the calculated angular frequency is output to each phase shifter 205. Information indicating the pulse repetition period is also output to a frequency domain converter 301 (to be described later) of the signal processor 3.

  The pulse modulator 203 performs pulse modulation on the local oscillation signal from the local oscillator 201 according to the information indicating the pulse repetition period and pulse width from the parameter calculator 202, and generates a pulse signal. The pulse signal generated by the pulse modulator 203 is output to the transmitter 101 of the transmitter 1.

The antenna element 204 receives a signal radiated from the transmitter 101 of the transmission unit 1 and reflected by a target to be observed as a reception signal. The received signal received by the antenna element 204 is output to the corresponding phase shifter 205.
Note that, here, the antenna element 102 that radiates a transmission signal and the antenna element 204 that receives a reception signal are separated, but may be integrated. That is, a common antenna element may be used to radiate a transmission signal when performing transmission and receive a reception signal when performing reception.

  The phase shifter 205 is provided for each antenna element 204, and converts the received signals from the corresponding antenna elements 204 into different frequencies between the antenna elements 204 by shifting the phase. At this time, the phase shifter 205 calculates a phase shift amount (frequency change amount) from the information indicating the angular frequency from the parameter calculator 202, and performs phase shift of the received signal according to the phase shift amount. The received signal frequency-converted by the phase shifter 205 is output to the adder 206.

  The adder 206 adds the received signals from the phase shifters 205 to generate a received video signal. In addition, when reducing the side lobe of the antenna pattern, the adder 206 performs addition after adding a load corresponding to the corresponding antenna element 204 to the received signal from each phase shifter 205. . The received video signal generated by the adder 206 is output to the mixer 207.

  The mixer 207 uses the local oscillation signal from the local oscillator 201 to down-convert the received video signal from the adder 206. The received video signal down-converted by the mixer 207 is output to the A / D converter 208.

  The A / D converter 208 performs phase detection on the received video signal from the mixer 207 to perform A / D conversion. The received video signal subjected to A / D conversion by the A / D converter 208 is output to a frequency domain conversion unit 301 (to be described later) of the signal processor 3.

  The signal processor 3 includes a frequency domain conversion unit 301, a target candidate detection unit 302, a target candidate azimuth calculation unit 303, a target candidate relative speed calculation unit 304, and a target candidate relative distance calculation unit 305.

  The frequency domain converting unit 301 converts the received video signal from the A / D converter 208 of the receiving unit 2 into the frequency domain based on information indicating the pulse repetition period from the parameter calculator 202 of the receiving unit 2. is there. The received video signal converted into the frequency domain by the frequency domain converting unit 301 is output to the target candidate detecting unit 302. The received video signal is also output to the display 4 via the target candidate detection unit 302, the target candidate orientation calculation unit 303, the target candidate relative speed calculation unit 304, and the target candidate relative distance calculation unit 305.

  The target candidate detection unit 302 detects a target candidate based on the signal power of the received video signal from the frequency domain conversion unit 301. Information indicating the target candidates detected by the target candidate detection unit 302 is output to the target candidate orientation calculation unit 303, the target candidate relative speed calculation unit 304, and the target candidate relative distance calculation unit 305.

  The target candidate azimuth calculation unit 303 calculates the target candidate azimuth based on the information indicating the target candidates from the target candidate detection unit 302. Information indicating the azimuth of the target candidate calculated by the target candidate azimuth calculation unit 303 is output to the display 4 via the target candidate relative speed calculation unit 304 and the target candidate relative distance calculation unit 305.

  The target candidate relative speed calculation unit 304 calculates the relative speed of the target candidate based on the information indicating the target candidate from the target candidate detection unit 302. Information indicating the relative speed of the target candidate calculated by the target candidate relative speed calculation unit 304 is output to the display 4 via the target candidate relative distance calculation unit 305.

  The target candidate relative distance calculation unit 305 calculates the relative distance of the target candidates based on the information indicating the target candidates from the target candidate detection unit 302. Information indicating the relative distance of the target candidate calculated by the target candidate relative distance calculation unit 305 is output to the display 4.

  The display 4 outputs information from the signal processor 3 on the screen as a processing result.

Next, an example of a hardware configuration for realizing the radar apparatus configured as described above will be described with reference to FIG.
The hardware configuration of the radar apparatus includes a transmitting apparatus 51, a receiving apparatus 52, a processor 53, a memory 54, and a display 55 as shown in FIG.

  In FIG. 2, the transmission unit 1 shown in FIG. 1 is realized by a transmission device 51. Also, the receiving unit 2 shown in FIG. Further, the display 4 shown in FIG. The signal processor 3 shown in FIG. 1 is realized by a processor 53 that executes a program stored in the memory 54. In addition, a plurality of processors 53 and a plurality of memories 54 may cooperate to execute the above function.

ここで、ｔは時刻であり、Ｔ_ｏｂｓはレーダ装置の観測時間であり、ｆ_０は局部発振信号Ｌ_０（ｔ）の周波数であり、Ａ_Ｌは局部発振信号Ｌ_０（ｔ）の振幅である。この局部発振器２０１により生成された局部発振信号Ｌ_０（ｔ）はパルス変調器２０３及びミキサ２０７に出力される。Next, the operation of the radar apparatus according to the first embodiment will be described.
First, the transmission operation of the transmission signal will be described with reference to FIG.
In the transmission operation of the transmission signal, as shown in FIG. 3, first, the local oscillator 201 generates a local oscillation signal L ₀ (t) from the following equation (1) (step ST301).

Here, t is the time, _Tobs is the observation time of the radar device, f ₀ is the frequency of the local oscillation signal L ₀ (t), and A _L is the amplitude of the local oscillation signal L ₀ (t). is there. The local oscillation signal L ₀ (t) generated by the local oscillator 201 is output to the pulse modulator 203 and the mixer 207.

ここで、Ｎ_ＩＮＴは正の整数である。このパラメータ算出器２０２により算出されたパルス繰り返し周期Ｔ_ＰＲＩ及びパルス幅Ｔ_ｐｌｓを示す情報はパルス変調器２０３に出力される。また、パルス繰り返し周期Ｔ_ＰＲＩを示す情報は信号処理器３の周波数領域変換部３０１にも出力される。The parameter calculator 202 calculates a pulse repetition period T _PRI and a pulse width T _pls that are parameters of the pulse signal (step ST302). In the first embodiment, as shown in FIG. 4, the pulse repetition period T _{PRI is set} to an integral multiple of the pulse width T _pls from the following equation (2).

Here, N _INT is a positive integer. Information indicating the pulse repetition period T _PRI and the pulse width T _pls calculated by the parameter calculator 202 is output to the pulse modulator 203. Information indicating the pulse repetition period T _PRI is also output to the frequency domain conversion unit 301 of the signal processor 3.

ここで、Δｆは移相器２０５による周波数変換後の受信信号間の周波数間隔である。このパラメータ算出器２０２により算出された角周波数ωを示す情報は各移相器２０５に出力される。The parameter calculator 202 calculates the angular frequency ω from the calculated pulse width T _pls (step ST303). At this time, the angular frequency ω at which the time T in which the phase is one cycle becomes the pulse width T _pls is calculated from the following equation (3).

Here, Δf is a frequency interval between received signals after frequency conversion by the phase shifter 205. Information indicating the angular frequency ω calculated by the parameter calculator 202 is output to each phase shifter 205.

Thus, by calculating the pulse repetition period T _PRI and the pulse width T _pls that satisfy Expression (2) and the angular frequency ω that satisfies Expression (3), each phase shifter 205 sets each received signal to a different frequency. Even if converted to, as shown in FIG. 5A, it becomes coherent at the pulse repetition period interval (interval between a ₁ and a _{2 in} FIG. 5) and faces the same direction. Therefore, when the received signal is subjected to discrete Fourier transform at the pulse repetition period T _PRI in the frequency domain transform unit 301, it is integrated coherently with the Doppler frequency (relative speed) of the target candidate. FIG. 5 is a diagram showing the relationship between the pulse signal and the received signal after frequency conversion. In FIG. 5, the alternate long and short dash line indicates a received signal converted to a frequency of 1ω, and the broken line indicates a received signal converted to a frequency of 2ω.

On the other hand, when the expressions (2) and (3) are not satisfied at the same time, as shown in FIG. Therefore, even if the received signal is discrete Fourier transformed at the pulse repetition period T _PRI in the frequency domain transform unit 301, it is not coherently integrated with the target candidate Doppler frequency (relative velocity), and other components are also integrated. End up. As a result, it becomes difficult to calculate the relative speed of the target candidate.

ここで、ｈはヒット番号であり、Ｈはヒット数である。このパルス変調器２０３により生成されたパルス信号Ｌ_ｐｌｓ（ｔ）は送信部１の送信機１０１に出力される。Next, based on the information indicating the pulse repetition period T _PRI and the pulse width T _pls from the parameter calculator 202, the pulse modulator 203 calculates the local oscillation signal from the local oscillator 201 from the following equations (4) and (5). Pulse modulation is performed on L ₀ (t) to generate a pulse signal L _pls (t) (step ST304).

Here, h is a hit number and H is the number of hits. The pulse signal L _pls (t) generated by the pulse modulator 203 is output to the transmitter 101 of the transmitter 1.

Next, transmitter 101 generates a transmission signal using pulse signal L _pls (t) from pulse modulator 203 of reception unit 2 (step ST305). A transmission signal generated by the transmitter 101 is output to the antenna element 102.
Next, antenna element 102 radiates the transmission signal from transmitter 101 into the air (step ST306).

ここで、Ｒｘ_０（ｔ）は基準点にあるアンテナ素子２０４の受信信号であり、Ｍはアンテナ素子２０４の数であり、ｍはアンテナ素子２０４の番号であり、ｄは各アンテナ素子２０４の間隔であり、ｃは光速である。Next, the reception operation of the reception signal will be described with reference to FIG.
In the reception operation of the reception signal, as shown in FIG. 6, first, each antenna element 204 receives the signal radiated from the transmitter 101 of the transmission unit 1 and reflected by the target as a reception signal (step ST601). . Here, an equally spaced linear array is assumed as the plurality of antenna elements 204. The target is assumed that the azimuth is θ, the relative distance is R ₀ , and the relative speed is v. Further, the received signal Rx _m (t) received by the antenna element 204 is expressed by the following expression (6).

Here, Rx ₀ (t) is the received signal of the antenna element 204 at the reference point, M is the number of the antenna elements 204, m is the number of the antenna elements 204, and d is the interval between the antenna elements 204. And c is the speed of light.

ここで、Ａ_Ｒｘは受信信号Ｒｘ_０（ｔ）の振幅である。各アンテナ素子２０４により受信された受信信号の位相の関係を図７に示す。
この各アンテナ素子２０４により受信された受信信号Ｒｘ_ｍ（ｔ）は対応する移相器２０５に出力される。In addition, the received signal Rx ₀ (t) of the antenna element 204 at the reference point is expressed by the following expression (7).

Here, A _Rx is the amplitude of the received signal Rx ₀ (t). FIG. 7 shows the phase relationship of the received signal received by each antenna element 204.
The reception signal Rx _m (t) received by each antenna element 204 is output to the corresponding phase shifter 205.

ここで、Ａ_Ｃは移相量Ｃ_φ，ｍ（ｔ）の振幅であり、ωは式（３）に示す受信信号間の角周波数（図８）である。Next, each phase shifter 205 performs a phase shift on the received signal Rx _m (t) from the corresponding antenna element 204 to convert the antenna elements 204 to different frequencies (step ST602). At this time, each phase shifter 205 calculates the phase shift amount C _{φ, m} (t) from the information indicating the angular frequency ω from the parameter calculator 202 by the following equation (8), and receives the received signal Rx _m (t ).

Here, A _C is phase shift amount C _phi, the amplitude of _{m (t),} is ω is the angular frequency between the received signal shown in Equation (3) (Fig. 8).

ここで、＊は複素共役である。
この移相器２０５により周波数変換された受信信号Ｒｘ_φ，ｍ（ｔ）は加算器２０６に出力される。The frequency-converted received signal Rx _{φ, m} (t) is expressed by the following equation (9).

Here, * is a complex conjugate.
The received signal Rx _{φ, m} (t) frequency-converted by the phase shifter 205 is output to the adder 206.

Next, adder 206 adds reception signals Rx _{φ, m} (t) from each phase shifter 205 to generate a reception video signal (step ST603). The received video signal Rx _{φ, sum} (t) added by the adder 206 is expressed by the following equation (10).

図９（ａ）に示す荷重ｗ_ｍを付加しない場合に対し、受信信号Ｒｘ_φ，ｍ（ｔ）に荷重ｗ_ｍを付加した上で加算を行うことで、図９（ｂ）に示すように、アンテナパターンのサイドローブを低減する効果がある。
この加算器２０６により生成された受信ビデオ信号Ｒｘ_{φ，ｓｕｍ}（ｔ）はミキサ２０７に出力される。Further, when reducing the side lobes of the antenna pattern, the adder 206 applies the load w _m corresponding to the corresponding antenna element 204 to the received signal Rx _{φ, m} (t) from each phase shifter 205. Addition is performed after adding. Note that the load w _m sets a Hamming window or the like according to the side lobe level or the signal-to-noise ratio. The received video signal Rx _{φ, sum} (t) in this case is expressed by the following equation (11).

To when not adding the load w _m shown in FIG. 9 (a), the received signal Rx _phi, by performing the addition in terms of added load w _m to _{m (t),} as shown in FIG. 9 (b) There is an effect of reducing the side lobe of the antenna pattern.
The received video signal Rx _{φ, sum} (t) generated by the adder 206 is output to the mixer 207.

ここで、Ａ_Ｖは受信ビデオ信号Ｖ（ｔ）の振幅である。このミキサ２０７によりダウンコンバートされた受信ビデオ信号Ｖ（ｔ）はＡ／Ｄ変換器２０８に出力される。Next, mixer 207 down-converts received video signal Rx _{φ, sum} (t) from adder 206 using local oscillation signal L ₀ (t) from local oscillator 201 (step ST604). The received video signal V (t) down-converted by the mixer 207 is expressed by the following equation (12).

Here, _AV is the amplitude of the received video signal V (t). The received video signal V (t) down-converted by the mixer 207 is output to the A / D converter 208.

ここで、Ｎはパルス繰り返し周期内のサンプリング数であり、ｎはパルス繰り返し周期内のサンプリング番号であり、ΔＴはパルス繰り返し周期内のサンプリング間隔である。このＡ／Ｄ変換器２０８によりＡ／Ｄ変換された受信ビデオ信号Ｖ（ｈ，ｎ）は信号処理器３の周波数領域変換部３０１に出力される。Next, A / D converter 208 performs phase detection on received video signal V (t) from mixer 207 to perform A / D conversion (step ST605). The received video signal V (h, n) A / D converted by the A / D converter 208 is expressed by the following equation (13).

Here, N is the number of samplings within the pulse repetition period, n is the sampling number within the pulse repetition period, and ΔT is the sampling interval within the pulse repetition period. The received video signal V (h, n) A / D converted by the A / D converter 208 is output to the frequency domain converter 301 of the signal processor 3.

ここで、Ｈ_ＦＦＴは周波数領域の変換点数であり、ｋは周波数領域のサンプリング番号である。この周波数領域変換部３０１により周波数領域に変換された受信ビデオ信号ｆ_ｄ，Ｖ（ｋ，ｎ）は目標候補検出部３０２に出力され、また、目標候補検出部３０２、目標候補方位算出部３０３、目標候補相対速度算出部３０４及び目標候補相対距離算出部３０５を介して表示器４にも出力される。Next, the signal processing operation by the signal processor 3 will be described with reference to FIG.
In the signal processing operation by the signal processor 3, first, as shown in FIG. 10, the frequency domain conversion unit 301 first determines the A / _V of the reception unit 2 based on the information indicating the pulse repetition period T _PRI from the parameter calculator 202. Received video signal V (h, n) from D converter 208 is converted into the frequency domain (step ST1001). The received video signal f _{d, V} (k, n) converted into the frequency domain by the frequency domain converter 301 is expressed by the following equation (14).

Here, H _FFT is the number of transform points in the frequency domain, and k is a sampling number in the frequency domain. The received video signal f _{d, V} (k, n) converted into the frequency domain by the frequency domain transform unit 301 is output to the target candidate detection unit 302, and the target candidate detection unit 302, the target candidate azimuth calculation unit 303, The data is also output to the display 4 via the target candidate relative speed calculation unit 304 and the target candidate relative distance calculation unit 305.

Here, the frequency domain transform unit 301 performs discrete Fourier transform with the pulse repetition period T _PRI to transform into the frequency domain. Therefore, there is an effect of coherent integration of the received signal, and an effect of improving a signal-to-noise ratio (SNR: Signal To Noise Ratio). Here, the discrete Fourier transform is used as the frequency domain transform, but a fast Fourier transform may be used.

Further, when Expression (14) is expanded, it is expressed as Expression (15).

From this equation (15), terms relating to frequency conversion exist as in the following equations (16) and (17).

Here, Δf = 1 / T _pls from the equation (3), and the pulse repetition period T _PRI is an integer multiple N _INT of the pulse width, so the equation (17) is expressed as the equation (18). The Therefore, even if the hit number h or the antenna element number M, which is an integer, changes only to an integer multiple of 2π, it does not affect the result of the frequency domain transform (discrete Fourier transform). That is, by using the parameter calculator 202, the Doppler frequency (relative speed) can be accurately obtained even if the received signal from each antenna element 204 is converted to a different frequency. That is, as shown in FIG. 14, it is integrated into the relative speed of the target candidate and shows the maximum value.

Next, target candidate detecting section 302 detects a target candidate based on the signal power of received video signal f _{d, V} (k, n) from frequency domain transform section 301 (step ST1002). At this time, the target candidate detection unit 302 detects a target candidate by, for example, CFAR (Constant False Alarm Rate) processing. Information indicating the target candidate detected by the target candidate detection unit 302 (information indicating the sampling number k ′ in the frequency domain of the target candidate and the sampling number n ′ in the pulse repetition period of the target candidate) is the target. The information is output to the candidate orientation calculation unit 303, the target candidate relative speed calculation unit 304, and the target candidate relative distance calculation unit 305.

Here, the effect of the receiving unit 2 of the present invention will be described.
In the phase shifter 205 of the receiving unit 2, the received signal is frequency-converted to a different frequency for each angular frequency ω. This indicates that the phase between the received signals is controlled to change by an integral multiple of ωT as shown in the equations (8) and (9). That is, by converting the received signal to a different frequency for each angular frequency ω, the directivity of the antenna pattern can be changed in a time division manner as shown in FIGS. As a result, it is not necessary to form an antenna pattern for each azimuth as in the prior art, and multibeam data with a reduced amount of computation can be obtained. In FIG. 11, A is the in-phase wavefront at time t, A ′ is the in-phase wavefront at time t + Δt, D ₁ is the distance corresponding to phase ωt, and D _M−1 is the phase (M −1) is a distance corresponding to ωt, and D ′ _M−1 is a distance corresponding to the phase (M−1) ω (t + Δt). In FIG. 12, reference numeral 1201 denotes an antenna pattern.

In Expression (15), the term in the time direction within the pulse repetition period is as shown in Expression (19). When Expression (20) is satisfied, the beam (antenna pattern) can be directed to the azimuth θ. In the first embodiment, it is possible to form a beam in a time division manner by converting the received signal into different frequencies by the angular frequency ω (= 2πΔf). Therefore, as shown in FIG. 14, the relationship between the time t and the azimuth θ is clarified, and the azimuth θ of the beam (antenna pattern) at the time t can be calculated according to the equation (21).

この目標候補方位算出部３０３により算出された目標の候補の方位θ’を示す情報は目標候補相対速度算出部３０４及び目標候補相対距離算出部３０５を介して表示器４に出力される。Next, the target candidate azimuth calculation unit 303 calculates the target from the following equation (22) based on the information indicating the target candidate from the target candidate detection unit 302 (sampling number n ′ in the pulse repetition period of the target candidate). Is calculated (step ST1003).

Information indicating the target candidate azimuth θ ′ calculated by the target candidate azimuth calculation unit 303 is output to the display 4 via the target candidate relative speed calculation unit 304 and the target candidate relative distance calculation unit 305.

ここで、Δｖ_ｓａｍｐは速度サンプリング間隔である。この目標候補相対速度算出部３０４により算出された目標の候補の相対速度ｖ’を示す情報は目標候補相対距離算出部３０５を介して表示器４に出力される。The target candidate relative speed calculation unit 304 also uses the following equations (23) and (24) based on the information indicating the target candidate from the target candidate detection unit 302 (sampling number k ′ in the frequency domain of the target candidate). ) To calculate the relative velocity v ′ of the target candidate (step ST1004).

Here, Δv _samp is a speed sampling interval. Information indicating the relative speed v ′ of the target candidate calculated by the target candidate relative speed calculation unit 304 is output to the display 4 via the target candidate relative distance calculation unit 305.

ここで、ｆｌｏｏｒ（Ｚ）は変数Ｚ以下の最も近い整数である。この目標候補相対距離算出部３０５により算出された目標の候補の相対距離Ｒ_０’を示す情報は表示器４に出力される。Further, the target candidate relative distance calculation unit 305 is based on the information indicating the target candidate from the target candidate detection unit 302 (sampling number n ′ in the pulse repetition period of the target candidate) from the following equation (25): The relative distance R ₀ ′ of the target candidate is calculated (step ST1005).

Here, floor (Z) is the nearest integer less than or equal to variable Z. Information indicating the relative distance R ₀ ′ of the target candidate calculated by the target candidate relative distance calculation unit 305 is output to the display 4.

Here, the parameter calculator 202 _sets the time T during which the phase of the angular frequency ω is one cycle as the pulse width T _pls . Therefore, as shown in FIG. 13A, distance measurement and azimuth measurement are possible without distance ambiguity. Further, the target candidate number can be calculated without error. On the other hand, when the time T in which the phase of the angular frequency ω is one cycle is not the pulse width T _pls , the distance ambiguity is generated and the distance measurement performance is deteriorated. In the example of FIG. 13B, since the angular frequency ω increases, the sampling frequency also increases and the amount of calculation increases.

Thereafter, the display 4 displays information from the signal processor 3 (received video signal f _{d, V} (k, n), target candidate azimuth θ ′, target candidate relative speed v ′, and target candidate relative. The distance R ₀ ′) is output on the screen as a processing result.

  As described above, according to the first embodiment, since the reception signals received by the antenna element 204 are converted to different frequencies, the adder 206 is provided, and the A / D converter 208 is simply configured. Compared to the conventional configuration, the H / W scale can be reduced, and a plurality of directions can be searched with a low calculation amount.

  The pulse modulator 203 generates a pulse signal whose pulse repetition period is an integral multiple of the pulse width, and the phase shifter 205 uses the angular frequency whose time is the pulse width to shift the phase for one period. By calculating the phase amount and performing frequency conversion, the frequency domain conversion unit 301 performs conversion to the frequency domain at the pulse repetition period, thereby enabling calculation of the relative speed of the target candidate.

  In the above description, a plurality of phase shifters 205 are used to convert received signals received by the antenna element 204 into different frequencies. However, the frequency converter is not limited to this as long as it can convert the received signals received by the antenna elements 204 into different frequencies. For example, as the frequency converter, a plurality of local oscillators that are provided for each antenna element 204 and generate local oscillation signals having different frequencies, and a local oscillation signal that is provided for each antenna element 204 and is generated by a corresponding local oscillator And a plurality of mixers that perform frequency conversion by down-converting the received signal received by the corresponding antenna element 204.

  In the radar apparatus shown in FIG. 1, the case where the target candidate relative speed calculation unit 304 and the target candidate relative distance calculation unit 305 are provided is shown. However, the target candidate relative speed calculation unit 304 and the target candidate relative distance calculation unit 305 are not indispensable configurations, and are not provided when it is not necessary to calculate the target candidate relative speed and the target candidate relative distance. Also good.

Embodiment 2. FIG.
FIG. 15 is a diagram showing a configuration example of a radar apparatus according to Embodiment 2 of the present invention. In the radar device according to the second embodiment shown in FIG. 15, the receiving unit 2 of the radar device according to the first embodiment shown in FIG. 1 is changed to the receiving unit 2b, and the signal processor 3 is changed to the signal processor 3b. It is a thing. The receiving unit 2b is obtained by changing the parameter calculator 202 of the receiving unit 2 in the first embodiment shown in FIG. 1 to a parameter calculator 202b. Further, the signal processor 3b is obtained by changing the frequency domain conversion unit 301 of the signal processor 3 in the first embodiment shown in FIG. 1 to a frequency domain conversion unit 301b. Other configurations are the same, and the same reference numerals are given and description thereof is omitted.

  Similar to the parameter calculator 202 in the first embodiment, the parameter calculator 202b calculates a pulse signal parameter (pulse repetition period and pulse width) and an angular frequency. At this time, the pulse repetition period does not need to be an integral multiple of the pulse width. The parameter calculator 202b also calculates an interval that is the least common multiple of the pulse repetition period and the pulse width. Information indicating the pulse repetition period and pulse width calculated by the parameter calculator 202b is output to the pulse modulator 203, information indicating the calculated angular frequency is output to each phase shifter 205, and the calculated interval is calculated. The information shown is output to the frequency domain converter 301b of the signal processor 3b.

  Based on the information indicating the interval from the parameter calculator 202b, the frequency domain transform unit 301b performs Fourier transform (discrete Fourier transform or fast Fourier transform) on the received video signal from the A / D converter 208 of the receiver 2 at the above interval. ) To convert to the frequency domain. The received video signal converted into the frequency domain by the frequency domain conversion unit 301 b is output to the target candidate detection unit 302. The received video signal is also output to the display 4 via the target candidate detection unit 302, the target candidate orientation calculation unit 303, the target candidate relative speed calculation unit 304, and the target candidate relative distance calculation unit 305.

ここで、ＬＣＭ（Ａ，Ｂ）は変数Ａと変数Ｂの最小公倍数である。In the second embodiment, the parameter calculator 202b calculates the pulse repetition period T _PRI and the pulse width T _pls that satisfy the equation (2) and the angular frequency ω that satisfies the equation (3). Further, from the equation (26), Then, an interval T _LCM that is the least common multiple of the pulse repetition period T _PRI and the pulse width T _pls is calculated.

Here, LCM (A, B) is the least common multiple of variables A and B.

Then, the frequency domain transform unit 301b converts the received video signal V (h, n) from the A / D converter 208 of the receiving unit 2 into the frequency domain from the equation (14), and receives the received video signal _{fd, V} (k, n) is obtained. However, in the second embodiment, instead of the pulse repetition period _{T PRI,} the Fourier transform at intervals _{T LCM} as the least common multiple of the pulse repetition period _{T PRI} and the pulse width _{T pls} performed.

In the second embodiment, it is assumed that the pulse repetition period T _PRI is a non-integer multiple of the pulse width T _pls . In this case, as shown in FIG. 16, since the pulse repetition period interval (interval between a1 and a2 in FIG. 16) is not coherent, even if Fourier transform is performed with the pulse repetition period T _PRI , integration is performed only on the relative speed of the target candidate. Thus, the relative speed cannot be calculated correctly.
On the other hand, the interval T _LCM (interval between a1 and a3 in FIG. 16) that is the least common multiple of the pulse repetition period T _PRI and the pulse width T _pls is coherent. Therefore, in the second embodiment, by performing Fourier transform at this interval _TLCM , it is integrated only with the relative speed of the target candidate, and the relative speed can be calculated correctly.

  As described above, according to the second embodiment, since the received signal is Fourier-transformed at an interval that is the least common multiple of the pulse repetition period and the pulse width, the pulse repetition period is different from that of the first embodiment. Even if is a non-integer multiple of the pulse width, the relative speed of the target candidate can be calculated.

  In the present invention, within the scope of the invention, any combination of the embodiments, or any modification of any component in each embodiment, or omission of any component in each embodiment is possible. .

  The radar apparatus according to the present invention can reduce the H / W scale with respect to the conventional configuration, and can improve the target detection performance by searching each direction with a low calculation amount, and the like to search for a target. Suitable for use in.

  1 Transmitter, 2, 2b Receiver, 3, 3b Signal processor, 4 Display, 51 Transmitter, 52 Receiver, 53 Processor, 54 Memory, 55 Display, 101 Transmitter, 102 Antenna element (Transmit antenna element) , 201 local oscillator, 202, 202b parameter calculator, 203 pulse modulator (pulse signal generator), 204 antenna element (receiving antenna element), 205 phase shifter (frequency converter), 206 adder, 207 mixer, 208 A / D converter, 301, 301b Frequency domain converter, 302 Target candidate detector, 303 Target candidate azimuth calculator, 304 Target candidate relative speed calculator, 305 Target candidate relative distance calculator.

Claims (9)

A pulse signal generator for generating a pulse signal;
A transmitter for generating a transmission signal from the pulse signal generated by the pulse signal generator;
A transmitting antenna element that radiates the transmission signal generated by the transmitter into the air;
A plurality of receiving antenna elements for receiving, as a received signal, a signal radiated by the transmitting antenna element and reflected by a target;
A frequency converter that converts received signals received by each of the receiving antenna elements into different frequencies;
An adder for adding each reception signal converted by the frequency conversion unit to generate a reception video signal;
An A / D converter for A / D converting the received video signal added by the adder;
A frequency domain converter that converts the received video signal A / D converted by the A / D converter into a frequency domain;
A target candidate detection unit that detects the target candidate from the signal power of the received video signal converted by the frequency domain conversion unit;
A radar apparatus comprising: a target candidate azimuth calculating unit that calculates an azimuth of the target candidate from a detection result by the target candidate detecting unit. The pulse signal generator generates the pulse signal whose pulse repetition period is an integer multiple of a pulse width;
The frequency conversion unit performs the conversion of the frequency using an angular frequency in which the time during which the phase is one cycle is the pulse width,
The radar apparatus according to claim 1, wherein the frequency domain transform unit performs the transform to the frequency domain by performing a Fourier transform at the pulse repetition period. The frequency conversion unit performs the conversion of the frequency using an angular frequency that is a pulse width of the pulse signal when a phase period is one cycle,
The frequency domain transform unit performs transform to the frequency domain by performing Fourier transform at an interval that is a least common multiple of a pulse repetition period and a pulse width of the pulse signal. Radar device. The radar apparatus according to claim 2, wherein the frequency conversion unit converts each received signal into a frequency that is different by an integer multiple of the angular frequency. The radar apparatus according to claim 3, wherein the frequency conversion unit converts each received signal into a frequency that is different by an integer multiple of the angular frequency. The frequency converter is
The plurality of phase shifters that are provided for each of the reception antenna elements and perform the frequency conversion by performing phase shift of the reception signals received by the corresponding reception antenna elements. Radar equipment. The frequency converter is
A plurality of local oscillators that are provided for each of the receiving antenna elements and generate local oscillation signals having different frequencies;
A plurality of frequency conversions that are provided for each of the reception antenna elements, and that convert the frequency by down-converting the reception signal received by the corresponding reception antenna element using the local oscillation signal generated by the corresponding local oscillator. The radar apparatus according to claim 1, further comprising: The radar apparatus according to claim 1, further comprising: a target candidate relative speed calculation unit that calculates a relative speed of the target candidate from a detection result of the target candidate detection unit. The radar apparatus according to claim 1, further comprising: a target candidate relative speed calculation unit that calculates a relative distance of the target candidate from a detection result by the target candidate detection unit.

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