JPWO2016006068A1 - Wireless communication system, transmitter, and receiver - Google Patents

Abstract

In a wireless communication system, a transmitter includes a transmission information generation unit that generates transmission information, and a first code that repeats at a frequency fr, and an autocorrelation value between the same partial areas rather than a cross-correlation value between different partial areas. A first code generation unit that generates a first code having a high value, a second code generation unit that generates a second code that can detect whether or not two series of identical codes match on the time axis, and the transmission An encoding unit that encodes information with the first code and the second code, a transmission that superimposes a carrier wave on the encoded transmission information, generates a transmission signal whose polarization plane rotates at a frequency fr, and transmits the signal wirelessly A receiver that removes a carrier wave from the received signal, a synchronization detector that detects a starting point of the information signal using a second code for the information signal from which the carrier wave has been removed, and an information Corresponding to each partial area using the starting point of the signal Extracts the partial area information respectively that includes a partial region information extracting section for detecting the phase shift of the partial area information respectively.

Description

  The present invention relates to a wireless communication system that enables highly secure communication suitable for control and monitoring of social infrastructure equipment.

  With the advancement of wireless communication technology against the background of the explosive spread of mobile phones, the reliability of wireless communication has been remarkably improved, and communication technology related to social infrastructure equipment, which has been said to have no means other than wired communication, Application of wireless technology is under consideration. In recent years, there are great expectations for high-efficiency operation of social infrastructure equipment using information and communication technologies, and the creation of new energy-information fusion networks taking smart grids as an example is being studied around the world.

  In the operation of social infrastructure equipment using information and communication technologies, special attention should be paid not only to the reliability of communication, but also to the confidentiality of communication information and resistance to external intruders. As a result, the importance of increasing the security of communications is increasing.

  In highly secure communication for social infrastructure devices, wired communication, which is generally considered to be superior to wireless communication in terms of reliability, is difficult to prevent external intruder attacks because the communication path can be physically specified. . Therefore, great expectations are placed on wireless communication in which the communication path cannot be physically specified.

  In wireless communication in which transmission paths are automatically spread between transmission and reception points, a technique for multiplexing communication paths between transmission and reception points is called diversity. Diversity is a technology that multiplexes communication paths using multiple areas in the time and frequency axes, as well as spatial diversity that forms multiple transmission / reception points in the space by taking advantage of the characteristics of electromagnetic waves that serve as wireless communication media. And two physical multiplexing schemes of polarization diversity for forming a plurality of vector components in a space are known.

  The environment in which social infrastructure equipment is placed must resist physical external forces such as high voltage at power plants and transmission substations, and high impact at transportation facilities and construction machinery. It is not preferable to use many, and diversity with a small number of antennas is advantageous.

  As background techniques for improving communication reliability between transmission and reception points using polarized waves, there are Patent Document 1 (Japanese Patent Laid-Open No. 2007-36521) and Patent Document 2 (Japanese Patent Laid-Open No. WO 2009/069798). Patent Document 1 states that “circularly polarized radio waves are obliquely incident on the glass and become distorted and become elliptically polarized waves. However, the receiving units 210 and 220 receive linearly polarized components separately, 230 is optimally synthesized.At the time of transmission, elliptically polarized waves that have been compensated in advance so as to be circularly polarized after being distorted by glass are transmitted (see summary).

  Further, Patent Document 2 states that “a transmitter transmits signals in the same band using two orthogonally polarized waves of radio waves in addition to spatial multiplexing of MIMO as a signal transmitted from each antenna on the transmitting side. Both polarization transmissions for transmitting two independent signals are performed.The receiving unit has an interference compensator and a MIMO signal processing circuit connected to the interference compensator. "

  In these prior arts, signals are transmitted using two orthogonal polarizations, and the receiver unit combines two independent signals obtained with the two orthogonal polarizations with the same weight on the time axis. , The energy of the transmission signal is reflected in the reception signal as much as possible to improve the reception sensitivity.

JP 2007-36521 A JP 2009/069798 A

  An object of the present invention is to provide a wireless communication technique capable of distinguishing a transmission path through which a arrived information signal has passed.

The present application includes a plurality of means for solving the above-described problems. A typical configuration of the present invention is as follows. That is,
A wireless communication system comprising a transmitter and a receiver,
The transmitter is
A transmission information generator for generating transmission information;
A first code generation unit that generates a first code that repeats at a frequency fr, and in each partial region obtained by dividing the first code for one period on the time axis, than a cross-correlation value between different partial regions, A first code generation unit that generates the first code that is a code having a high autocorrelation value between the same partial regions;
A second code generation unit that generates a second code that is a code that can detect whether or not two series of identical codes match on the time axis;
An encoding unit that encodes the transmission information generated by the transmission information generation unit using the first code and the second code;
A transmission unit that superimposes a carrier wave on the transmission information encoded by the encoding unit, generates a transmission signal whose polarization plane rotates at a frequency fr, and wirelessly transmits the transmission signal;
The receiver
A receiver that receives a transmission signal from the transmitter and removes a carrier wave from the received signal;
A synchronization detection unit that detects a start point of the information signal using the second code with respect to the information signal from which the carrier wave is removed by the reception unit;
Using the starting point of the information signal, the partial area information corresponding to each partial area is extracted from the information signal, respectively, and a partial area information extracting unit for detecting a phase shift of the partial area information,
It is characterized by providing.

  According to the present invention, it is possible to distinguish the transmission path through which the arrived information signal has passed.

It is a block diagram of the radio | wireless communications system in embodiment of this invention. It is a block diagram of the transmitter in 1st Example of this invention. It is a block diagram of the receiver in 1st Example of this invention. It is a block diagram of the modification of the receiver in 1st Example of this invention. It is a block diagram of the transmitter in 2nd Example of this invention. It is a block diagram of the transmitter in 3rd Example of this invention. It is a block diagram of the transmitter in 4th Example of this invention. It is a block diagram of the receiver in 4th Example of this invention. It is a block diagram of the transmitter in 5th Example of this invention. It is a block diagram of the transmitter in 6th Example of this invention. It is a block diagram of the receiver in 7th Example of this invention. It is a block diagram of the transmitter in 8th Example of this invention. It is a block diagram of the transmitter in 9th Example of this invention. It is a block diagram of the receiver in 10th Example of this invention. It is a figure explaining the correlation in embodiment of this invention. It is a block diagram of the elevator system (11th Example) to which the radio | wireless communications system of this invention is applied. It is a block diagram of the substation equipment monitoring system (12th Example) to which the radio | wireless communications system of this invention is applied.

FIG. 1 is a configuration diagram of a wireless communication system according to an embodiment of the present invention.
The wireless communication system in the embodiment of the present invention is configured to include a transmitter 1000 and a receiver 2000.

  The transmitter 1000 includes a transmission information generation unit 4 that generates transmission information to be transmitted to the receiver 2000, a first code generation unit 1 that generates a first code that repeats at a frequency fr, and a second code that has a high autocorrelation value. A second code generation unit 2 to generate, a third code storage unit 3 to store a third code, a third encoding unit 5 to encode transmission information generated by the transmission information generation unit 4 with a third code, and The transmission information encoded by the third encoding unit 5 is encoded by the first code and the second code, the encoding unit 6, the carrier wave superimposing unit 7, the first transmission antenna 8, and the first Transmission antenna 8 and a second transmission antenna 9 spatially orthogonal to each other.

  The transmission unit 10 is configured to include a carrier wave superimposing unit 7, a first transmission antenna 8, and a second transmission antenna 9. As will be described later, the transmission unit 10 superimposes a carrier wave on the transmission information encoded by the encoding unit 6, generates a transmission signal whose polarization plane rotates at the frequency fr, and wirelessly transmits the transmission signal.

  The first code generation unit 1 generates first codes having different codes in each partial area in each partial area obtained by dividing the first code for one period on the time axis. Specifically, the first code generation unit 1 has an autocorrelation value between the same partial areas (between partial areas having the same code) rather than a cross-correlation value between different partial areas (between partial areas having different codes). A first code that is high is generated. In the present embodiment, each partial region is formed by equally dividing the first code for one period on the time axis, but may not be equally divided.

  The second code generation unit generates a code having a high autocorrelation value, that is, a second code that is a code that can detect whether or not two sequences of identical codes match on the time axis. The second code is, for example, a cyclic code. The length of the second code is preferably set longer than the length of the first code.

The third code is a code (encryption) for concealing transmission information, and is generated so as to reflect the characteristics of the transmission path between the transmitter 1000 and the receiver 2000. The third code is, for example, a code reflecting the state of the received signal due to reflection (reception power amplitude, signal quality, etc.). Details of the third code will be described later.
The carrier wave superimposing unit 7 superimposes the carrier wave on the transmission information encoded by the encoding unit 6 and then generates a cosine wave signal having a frequency fr and a sine wave signal having a frequency fr.

The operation outline of the transmitter 1000 is as follows.
The transmitter 1000 encodes the transmission information generated by the transmission information generation unit 4 by the third encoding unit 3 using the third code, and then uses the first code and the second code to encode the encoding unit 6. Encode with Thereafter, a carrier wave is superimposed on the transmission information encoded by the encoding unit 6 and the electromagnetic wave 15 is radiated from the first transmission antenna 8 and the second transmission antenna 9. That is, the carrier wave superimposing unit 7 superimposes the carrier wave, generates a cosine wave signal and a sine wave signal in which the envelope sine vibrates at the frequency fr, wirelessly transmits the cosine wave signal from the first transmission antenna 8, A sine wave signal is wirelessly transmitted from a second transmission antenna 9 that is spatially orthogonal to the first transmission antenna 8.

  The cosine wave signal radiated from the first transmitting antenna 8 and the sine wave signal radiated from the second transmitting antenna 9 are radiated as linearly polarized electromagnetic waves, respectively. Thus, the electromagnetic wave 15 radiated from the first transmission antenna 8 and the second transmission antenna 9 travels in space so that the amplitude of the sine wave is spatially orthogonal with a phase difference of 90 degrees. The electromagnetic wave 15 rotates at a frequency fr (that is, the direction of the electric field rotates at the frequency fr while changing the magnitude of the electric field) in a plane perpendicular to the traveling direction of the electromagnetic wave 15. Form polarization.

  The receiver 2000 includes a first receiving antenna 21, a second receiving antenna 22 that is spatially orthogonal to the first receiving antenna 21, a carrier wave removing unit 23, a synchronization detecting unit 24, and a partial area information extracting unit. 25, an information decoding unit 27, and an information processing unit 28.

  The reception unit 26 is configured to include a first reception antenna 21, a second reception antenna 22, and a carrier wave removal unit 23. As will be described later, the reception unit 26 receives a transmission signal from the transmitter 1000 and removes a carrier wave from the received reception signal.

  The first receiving antenna 21 and the second receiving antenna 22 are respectively transmitted from the radio signal from the transmitter 1000 (the cosine wave signal transmitted from the first transmitting antenna 8 and the second transmitting antenna 9). A composite signal with a sine wave signal). The carrier removal unit 23 removes the carrier from the radio signals received by the first reception antenna 21 and the second reception antenna 22. The synchronization detection unit 24 detects the start point of the received information signal using the second code for the information signal from which the carrier wave is removed by the carrier wave removal unit 23.

  The partial region information extraction unit 25 extracts partial region information corresponding to each partial region of the first code of the first code generation unit 1 of the transmitter 1000 from the information signal using the start point of the information signal. At the same time, a phase shift (shift on the time axis) of each partial area information is detected. This phase shift is caused when a polarization angle shift (polarization angle shift) corresponding to the polarization angle at the time of reflection occurs when the electromagnetic wave from the transmitter 1000 is reflected on the transmission path. Details of the polarization angle shift will be described later.

  The information decoding unit 27 decodes the information extracted by the partial region information extraction unit 25 using the third code. Further, the information decoding unit 27 notifies the information processing unit 28 of the phase shift of each partial region information.

  The information processing unit 28 performs various types of information processing on the information decoded by the information decoding unit 27. Further, the information processing unit 28 recognizes a phase shift in each partial area, that is, indirectly recognizes and distinguishes a transmission path through which the information signal has reached by the phase shift in each partial area.

An outline of the operation of the receiver 2000 is as follows.
The receiver 2000 uses the first receiving antenna 21 and the second receiving antenna 22 to receive the electromagnetic wave 15 (electromagnetic wave whose polarization vector rotates) from the transmitter 1000, that is, the cosine from the transmitter 1000. A composite signal of a wave signal and a sine wave signal is received. The polarization angle of this received signal is shifted due to the influence of reflection in the radio wave transmission path compared to when the transmitter 1000 transmits it. The amount of this polarization angle shift differs depending on the polarization angle at the time of reflection, that is, differs for each partial region. Next, in the receiver 2000, the carrier wave removing unit 23 removes the carrier wave from the received signal and extracts the information signal.

  Next, in the receiver 2000, the synchronization detection unit 24 detects the start point of the information signal using the second code. Then, based on the starting point of the information signal, the partial region information extraction unit 25 extracts information corresponding to each partial region from the information signal using the first code, and the phase shift in each partial region is detected. Extract. Next, the information extracted by the partial area information extraction unit 25 is decoded (decoded) by the information decoding unit 27 using the third code. Next, various types of information processing are performed by the information processing unit 28 on the information decoded by the information decoding unit 27. Further, the information processing unit 28 recognizes the amount of phase shift in each partial region.

  In addition, when it is not necessary to strictly conceal transmission information wirelessly transmitted from the transmitter 1000, it is not necessary to encode the transmission information generated by the transmission information generation unit 4 using the third code. That is, when it is not necessary to strictly conceal transmission information from the transmitter 1000, the third code storage unit 3 and the third encoding unit 5 of the transmitter 1000 and the information decoding unit 27 of the receiver 2000 are omitted. be able to.

(First embodiment)
Hereinafter, a first example of the present embodiment will be described with reference to FIGS. 2A and 2B.
FIG. 2A is a block diagram of a transmitter in the first embodiment of the present invention. FIG. 2B is a block diagram of the receiver in the first embodiment. 2A and 2B, the same components as those in FIG. 1 are denoted by the same reference numerals, and description thereof will be omitted as appropriate.

  As shown in FIG. 2A, the transmitter 1001 of the first embodiment generates a transmission information generation unit 4 that generates transmission information I, a first code generation unit 1 that generates a first code, and a second code. A second code generation unit 2, a third code storage unit 3 for storing a third code, a third encoding unit 5 configured by a multiplier, an encoding unit 6 as a first multiplier, and a carrier wave A carrier wave generation circuit 11 for generating the first transmission antenna 11, a second multiplier 12, a cosine weight circuit 13, a sine weight circuit 14, a first transmission antenna 8, and a first transmission antenna 8 that are spatially orthogonal to each other. And two transmission antennas 9.

  1 is configured to include a carrier wave generation circuit 11, a second multiplier 12, a cosine weight circuit 13, and a sine weight circuit 14.

  The first code generation unit 1 generates a first code that is a repetition code having a frequency fr, that is, a cycle Tr (Tr = 1 / fr). The first code is a code that maximizes the autocorrelation and minimizes the cross-correlation in a section (partial region) in which the period Tr is equally divided by the integer M. In the example of FIG. 2A, the period Tr is equally divided into four, and four sections A1 to A4 are generated. For example, the code of the section A1 is generated so that the autocorrelation is maximized and the cross-correlation with the codes of the other sections A2 to A4 is minimized. The code of the section A2 is generated so that the autocorrelation is maximized and the cross-correlation with the codes of the other sections A1, A3, A4 is minimized. The same applies to the signs of the sections A3 and A4.

  As described above, the second code is a code that can detect whether or not the two series of second codes match on the time axis. For example, a PN (Pseudo Noise) code is used. When the two PN codes coincide with each other on the time axis, the sum of the PN codes has a maximum value, and when the two PN codes do not match, the sum has a minimum value. For example, when two PN7 codes match on the time axis, the sum is 7, and when they do not match, the sum is 0. In the present embodiment, the length of the second code is set longer than the length of the first code.

  The third code storage unit 3 stores a third code that is a cipher for concealing the information I. As the third code, a commonly used encryption can be used, but it is preferable to use a code generated based on a state of a transmission path between the transmitter 1001 and the receiver 2001 (that is, a reflection state). The code generated based on the state of the transmission path is a code generated to reflect the characteristics of the transmission path of the received signal received by the receiver 2001. As will be described later, the received signal corresponding to each partial area of the first code passes through a different transmission path for each partial area depending on the state of the transmission path (that is, the reflection state).

  For example, the third code corresponds to a code that reflects a temporal change in received power amplitude or a signal quality of a received signal corresponding to each partial area of the first code in the receiver 2001, or corresponds to each partial area. It is a code reflecting the phase shift of the received signal.

  The third code is taken into the transmitter 1001 from the outside by an operator, for example, and stored in the third code storage unit 3. For example, when the transmitter 1001 is a transmitter / receiver that also has the function of the receiver 2001, the third code is a case where an information signal transmitted from the transmitter 1001 of the transmission partner is received via a transmission path. , It can be generated to reflect the characteristics of the transmission path. For example, in the partial area A1 to A4 of the partial area information extraction unit 25 of the receiver 2001 to be described later, the temporal change in the amplitude of the received power of the received signal and the temporal change in the signal quality such as the SN ratio (noise-to-signal ratio) The code reflecting the time change of the phase shift amount can be detected by the second demodulation circuit 54 and used as the third code.

  In this way, the third code includes information unique to the transmission path from the transmitter 1001 to the receiver 2001, that is, unique information reflecting the nature of the reflector in the transmission path. Therefore, when the third code is used, it becomes difficult for a third party in a different place on the transmission path to decode the third code.

In the example of this embodiment, the transmission information I to be created by the transmission information generating unit 4 has a much longer cycle T _I than the period Tr of the first code, that is, far more than the frequency fr of the first code having a low frequency _{f I.} In other words, the transmission information I generated by the transmission information generation unit 4 can be regarded as the same signal in the four sections A1 to A4 of the first code described above. For example, the frequency f _I is 10 kHz and the frequency fr is about 1 MHz. Note that the transmission information I generated by the transmission information generation unit 4 may be configured to be different from each other in the four sections A1 to A4 of the first code.

  The output of the transmission information generation unit 4 (transmission information I) is encoded by the third encoding unit 5 using the third code stored in the third code storage unit 3, and then output from the first code generation unit 1. And the output of the second code generation unit 2 and the encoding unit 6. At this time, for example, the second code is included in one bit of the first code. For example, if the first code is [b1, b2, b3, b4, b5...] (Bi = 1 or −1), the first code to which the second code (CODE2) is applied is [b1 ( CODE2), b2 (CODE2), b3 (CODE2), b4 (CODE2),. Note that, contrary to the above, the first code may be included in one bit of the second code.

  The output of the encoding unit 6 is superposed on the output of the carrier wave generation circuit 11 by the second multiplier 12 and then branched into two. One of the branched signals is given a cosine weight by the cosine weight circuit 13 having the frequency fr and is radiated from the first transmitting antenna 8 into the air. The other branched signal is given a sine weight by the sine weight circuit 14 having the frequency fr and is radiated from the second transmitting antenna 9 into the air. The cosine weight is applied, for example, by superimposing (that is, multiplying) the cosine wave (cos2πfrt) having the frequency fr, and the sine weight is applied, for example, by superimposing (that is, multiplying) the sine wave (sin2πfrt) having the frequency fr. )It is to be. For example, the frequency of the carrier wave is about 400 MHz.

  In this way, the transmitter 1001 radiates the same signal with a cosine weight and a sine weight from the first transmitting antenna 8 and the second transmitting antenna 9 that are spatially orthogonal to each other and radiates it to the space. Since the cosine weight and sine weight change at a constant frequency fr, the polarization vector of the electromagnetic wave radiated into space rotates (that is, the polarization plane rotates) at the frequency fr. That is, the electromagnetic waves radiated from the first transmitting antenna 8 and the second transmitting antenna 9 are spatially orthogonal in terms of the sinusoidal amplitude of the frequency fr with a phase difference of 90 degrees. In this way, an electromagnetic wave having a rotationally polarized wave whose polarization vector rotates at the frequency fr is formed and travels in space.

  As shown in FIG. 2B, the receiver 2001 of the first embodiment includes a first receiving antenna 21, a second receiving antenna 22 that is spatially orthogonal to the first receiving antenna 21, and a first mixer. 31a, a second mixer 31b, a local signal generation circuit 32, a first analog filter 33a, a second analog filter 33b, a first adder 34, a first variable delay circuit 35, A first exclusive OR (XROR) operation circuit 36, a synchronous code generation circuit 38 that generates the same code (second code) as the second code generation unit 2 of the transmitter 1001, and a first demodulation circuit 37 The second variable delay circuit 41a, the second exclusive OR operation circuit 42a, the third variable delay circuit 41b, the third exclusive OR operation circuit 42b, and 2M fourth Variable delay circuits 51 (1) to 51 (2M); M partial code generation circuits 53 (1) to 53 (2M), 2M fourth exclusive OR operation circuits 52 (1) to 52 (2M), and 2M second demodulation circuits 54 (1) -54 (2M), the information decoding part 27 (decoding circuit), and the information processing part 28 are provided.

  Fourth variable delay circuits 51 (1) to 51 (2M), fourth exclusive OR operation circuits 52 (1) to 52 (2M), partial code generation circuits 53 (1) to 53 (2M), When the second demodulation circuits 54 (1) to 54 (2M) are called as representatives, the fourth variable delay circuit 51, the fourth exclusive OR operation circuit 52, the partial code generation circuit 53, and the second, respectively. This is referred to as a demodulation circuit 54. In the example of FIG. 2B, the number of M corresponds to twice the number of partial areas of the first code generation unit 1, and M = 8.

  1 is configured to include a first mixer 31a, a second mixer 31b, a local signal generation circuit 32, a first analog filter 33a, and a second analog filter 33b. Is done.

  1 includes a first adder 34, a first variable delay circuit 35, a first exclusive OR operation circuit 36, a synchronous code generation circuit 38, and a first demodulation circuit 37. The synchronization detection unit 24 is configured.

  A second variable delay circuit 41a, a second exclusive OR operation circuit 42a, a third variable delay circuit 41b, a third exclusive OR operation circuit 42b, a fourth variable delay circuit 51, The partial area information extraction unit 25 of FIG. 1 is configured to include a fourth exclusive OR operation circuit 52, a partial code generation circuit 53, and a second demodulation circuit 54.

  The reception signal captured from the first reception antenna 21 is multiplied by the output of the local signal generation circuit 32 by the first mixer 31a, and then passes through the first analog filter 33a to remove the carrier frequency. The output of the first analog filter 33a becomes an input A of an FPGA (Field-Programmable Gate Array) 3001, and then branches at an internal point C of the FPGA 3001. One of the branched signals becomes the first input of the first adder 34. In the first embodiment, in FIG. 2B, the configuration other than the first reception antenna 21, the second reception antenna 22, and the carrier wave removal unit 23 is configured as an FPGA 3001.

  The reception signal captured from the second reception antenna 22 is multiplied by the output of the local signal generation circuit 32 by the second mixer 31b, and then passes through the second analog filter 33b to remove the carrier frequency. The output of the second analog filter 33b becomes the input B of the FPGA 3001, and then branches at an internal point D of the FPGA 3001. One branched signal becomes the second input of the first adder 34. The first input and the second input of the first adder 34 are added by the first adder 34 and output.

  The output of the first adder 34 passes through the first variable delay circuit 35, and then the output of the synchronous code generation circuit 38, the exclusive OR operation by the first exclusive OR operation circuit 36. Is given. The synchronous code generation circuit 38 outputs a second code (PN code). The first exclusive OR operation circuit 36 performs a multi-bit exclusive OR operation between the output of the synchronous code generation circuit 38 and the output of the first variable delay circuit 35.

  In this way, an exclusive OR operation is performed between the second code (PN code) that is the output of the synchronous code generation circuit 38 and the second code included in the output of the first variable delay circuit 35. The calculation result is input to the first demodulation circuit 37. The first demodulation circuit 37 performs a correlation detection calculation by adding the result of the exclusive OR calculation of a plurality of bits. As described above, the two series of PN codes are maximized when the time axes match, and are minimized when the time axes do not match. The first demodulation circuit 37 performs a correlation detection calculation based on the exclusive OR calculation result, generates a delay amount control signal for controlling the delay amount based on the correlation detection calculation result, and generates a first variable delay circuit. 35, the second variable delay circuit 41a, and the third variable delay circuit 41b.

  At this time, the first demodulation circuit 37 has a value of the correlation detection calculation result equal to or greater than a predetermined value (that is, with correlation detection), and the output of the first exclusive OR calculation circuit 36 (that is, the intensity of the received signal). ) Controls the delay amount of the first variable delay circuit 35 so that the timing at which becomes equal to or greater than a predetermined value is obtained. Thus, the first demodulation circuit 37 finds the start point of the code included in the transmission signal based on the timing at which the value of the correlation detection calculation result becomes equal to or greater than the predetermined value and the reception intensity becomes equal to or greater than the predetermined value. In addition, synchronization of the reception signal with respect to the transmission signal from the transmitter 1001 can be realized.

  Of the outputs of the first analog filter 33a, the other branched signal passes through the second variable delay circuit 41a, and is then input to the second exclusive OR operation circuit 42a. The exclusive OR operation is performed with the output of The output of the second exclusive OR operation circuit 42a from which the second code has been removed in this way is further branched into M pieces, which are the fourth variable delay circuit 51 as signals E (1) to E (M), respectively. (1) to 51 (M).

  Of the outputs of the second analog filter 33b, the other branched signal passes through the third variable delay circuit 41b, and is then input to the third exclusive OR operation circuit 42b. The exclusive OR operation is performed with the output of The output of the second exclusive OR operation circuit 42b from which the second code has been removed in this way is further branched into M pieces, which are the fourth variable delay circuit 51 as signals E (M + 1) to E (2M), respectively. (M + 1) to 51 (2M).

  At this time, the first demodulation circuit 37 controls the delay amounts of the second variable delay circuit 41 a and the third variable delay circuit 41 b to be the same as the delay amount of the first variable delay circuit 35.

  The signals E (1) to E (M) are delayed by the fourth variable delay circuits 51 (1) to 51 (M), respectively, and then output from the partial code generation circuits 53 (1) to 53 (M). Are subjected to an exclusive OR operation by the fourth exclusive OR operation circuits 52 (1) to 52 (M).

  E (M + 1) to E (2M) are respectively delayed by the fourth variable delay circuits 51 (M + 1) to 51 (2M), and then output from the partial code generation circuits 53 (M + 1) to 53 (2M). , Exclusive OR operation is performed by the fourth exclusive OR operation circuits 52 (M + 1) to 52 (2M).

  The plurality of partial code generation circuits 53 (1) to 53 (M) generate different partial codes corresponding to the partial areas of the first code generation unit 1 of the transmitter 1001. Similarly, the partial code generation circuits 53 (M + 1) to 53 (2M) generate different partial codes corresponding to the partial areas of the first code generation unit 1, respectively. As described above, the partial code generation circuits 53 (1) to 53 (M) each output the same code as the first code in each partial region similar to the first code generation unit 1. The partial code generation circuits 53 (M + 1) to 53 (2M) also output the same codes as the partial code generation circuits 53 (1) to 53 (M), respectively.

  For example, the partial code generation circuit 53 (1) and the partial code generation circuit 53 (M + 1), that is, the partial code generation circuit 53 (1) and the partial code generation circuit 53 (5), as shown in FIG. The first code corresponding to the area A1 of the first code generation unit 1 is output. The partial code generation circuit 53 (M) and the partial code generation circuit 53 (2M), that is, the partial code generation circuit 53 (4) and the partial code generation circuit 53 (8) are areas of the first code generation unit 1 in the transmitter 1001. The first code corresponding to A4 is output.

  The fourth exclusive OR operation circuits 52 (1) to 52 (2M) respectively output the partial code generation circuits 53 (1) to 53 (2M) and the fourth variable delay circuits 51 (1) to 51 (1). An exclusive OR operation is performed with the output of 51 (2M). The second demodulation circuits 54 (1) to 54 (2M) perform correlation detection calculations using the calculation results of the fourth exclusive OR calculation circuits 52 (1) to 52 (2M), respectively. For example, the second demodulation circuit 54 (1) adds each bit of the calculation result of the fourth exclusive OR operation circuit 52 (1) to perform the correlation detection calculation. At this time, if the code of the output of the fourth variable delay circuit 51 (1) matches the code of the output of the partial code generation circuit 53 (1), the value of the correlation detection calculation result is maximized.

FIG. 9 is a diagram illustrating the correlation in the embodiment of the present invention.
In the example of FIG. 9, the case where the correlation detection calculation of the repetition codes C _{1 to} C _M is performed is shown. As shown in FIG. 9, the correlation value between two series of repetition codes C _{1 to} C _M having the same content is, for example, an autocorrelation value a1 between C ₁ and C _{1 or} between C ₂ and C ₂ . and autocorrelation values a2, autocorrelation value aM between _{C M} and _{C M} becomes the maximum of. On the other hand, the cross-correlation value between C ₁ and C ₂ does not become a maximum.

Returning to FIG. 2B, the description will be continued.
For example, the signal E (1) passes through the fourth variable delay circuit 51 (1) and then passes through the fourth exclusive OR operation circuit 52 () with the output of the partial code generation circuit 53 (1). The exclusive OR operation according to 1) is performed. The result of the exclusive OR operation is input to the second demodulation circuit 54 (1). The second demodulation circuit 54 (1) performs a correlation detection calculation based on the exclusive OR calculation result, and sends a delay amount based on the correlation detection calculation result to the variable delay circuit 51 (1). At this time, the second demodulation circuit 54 (1) has a value of the correlation detection calculation result equal to or greater than a predetermined value, and the signal strength of the output of the fourth exclusive OR calculation circuit 52 is equal to or greater than a predetermined value. The delay amount of the variable delay circuit 51 (1) is controlled so that the signal intensity of the signal E (1) becomes a predetermined value or more.

  As described above, the second demodulation circuit 54 (1) is configured so that the value of the correlation detection calculation result is a predetermined value or more and the signal intensity of the signal E (1) is a predetermined value or more. The delay amount 51 (1) is controlled. This delay amount corresponds to the phase shift of the received signal received from the transmitter 1001, and is specific to the transmission path through which the electromagnetic wave from the transmitter 1001 has been transmitted (that is, the reflector in the transmission path). Information specific to the property).

  Similarly, each of the second demodulation circuits 54 (2) to 54 (M) sets the value of the correlation detection calculation result to a predetermined value or more and sets the signal intensity of the signals E (2) to E (M). The delay amounts of the variable delay circuits 51 (2) to 51 (M) are controlled so as to be equal to or greater than a predetermined value. Each of these delay amounts corresponds to a phase shift of the received signal received from the transmitter 1001, and information unique to the transmission path through which the electromagnetic wave from the transmitter 1001 is transmitted is reflected.

  When there are a plurality of reflectors in the transmission path, electromagnetic waves from the transmitter 1001 arrive via a plurality of paths having different path lengths due to a plurality of reflections by the plurality of reflectors. As described above, the electromagnetic wave from the transmitter 1001 undergoes a polarization angle shift corresponding to the polarization angle of the electromagnetic wave at the time of reflection, that is, a different polarization angle shift for each partial region.

  On the other hand, since the antennas 21 and 22 cannot receive electromagnetic waves having a certain polarization angle (that is, a polarization angle orthogonal to the reception polarization angle of the antenna), the signals received by the antennas 21 and 22 are The signal intensity differs depending on the polarization angle (that is, each partial region). That is, the signals E (1) to E (2M) have different signal strengths depending on each partial region.

  Then, the second demodulation circuit 54 has a correlation detection calculation value between the received signal (that is, the signal E) and the output of the partial code generation circuit 53 that is equal to or greater than a predetermined value, and the received signal (that is, the signal E). The delay amount of the variable delay circuit 51 is controlled so that the signal intensity of the signal becomes equal to or greater than a predetermined value. As a result, a reception signal (signal E) having a signal strength equal to or higher than a predetermined value is selected for each partial region. That is, a transmission path on which a received signal with a signal strength equal to or higher than a predetermined value is selected as a transmission path for information signals extracted in each partial region.

  Thus, the delay amounts of the variable delay circuits 51 (1) to 51 (2M) correspond to the phase shift of the received signal received from the transmitter 1001, respectively, and the transmission path through which the electromagnetic wave from the transmitter 1001 is transmitted. It will be reflected.

  Further, the second demodulation circuits 54 (1) to 54 (M) respectively have exclusive OR operation results (that is, first outputs) from the fourth exclusive OR operation circuits 52 (1) to 52 (M). The information I) corresponding to the partial areas A1 to A4 of the one code generation unit 1 is output as information F (1) to F (M) to the information decoding unit 27 (decoding circuit). Similarly, the second demodulation circuits 54 (M + 1) to 54 (2M) respectively receive exclusive OR operation results from the fourth exclusive OR operation circuits 52 (M + 1) to 52 (2M) (that is, The information I) corresponding to the partial areas A1 to A4 of the first code generation unit 1 is output as information F (M + 1) to F (2M) to the information decoding unit 27 (decoding circuit).

  The information decoding unit 27 performs, for example, a logical sum (OR) of the input information F (1) to F (M) and the information F (M + 1) to F (2M), and then uses the third code. Decrypt. The decrypted information is sent to the information processing unit 28. In addition, the information decoding unit 27 receives the phase shift amount in each of the partial areas A1 to A4 from the second demodulation circuit 54 and sends it to the information processing unit 28. The information processing unit 28 performs processing using the information decoded by the information decoding unit 27. In addition, the information processing unit 28 detects and recognizes the phase shift amount in each partial region.

  In this way, the receiver 2001 uses the second code of the synchronization code generation circuit 38 for detecting the synchronization of the received signal, and the first demodulation circuit 37 extracts the start timing of the entire received signal. Then, using the timing, the receiver 2001 uses the fourth exclusive OR circuit 54 to extract the reception signal start timing for each partial area and detect the phase shift amount in each partial area. To do.

The operation of the synchronization detection unit 24 will be further described.
As described above, an electromagnetic wave radiated in a different direction from the transmitter 1001 is reflected on the surfaces of a plurality of reflectors (electromagnetic wave scatterers) existing between transmission and reception, and when these are synthesized by the receiver 2001, a specific The received electromagnetic wave energy is greatly attenuated at the polarization angle of. In this case, the received electromagnetic wave energy is maximized at a polarization angle orthogonal to the polarization angle. Therefore, by obtaining received signals from electromagnetic waves having different polarization angles and orthogonal polarization angles and summing them, it is possible to receive all of the energy of the signals arriving at all polarization angles.

  The receiver 2001 receives a signal transmitted by an electromagnetic wave whose polarization vector is rotated by two antennas 21 and 22 that are spatially orthogonal to each other. Then, the synchronization detection unit 24 generates a sum signal of the two received signals, and sequentially changes the delay amount of the sum signal, while the delayed sum signal and the second code generated by the synchronization code generation circuit 38. And the starting point of the second code included in the transmission signal is found.

  In this way, the receiver 2001 performs the exclusive OR operation on the sum signal of the two signals received by the two antennas 21 and 22 using the second code, so that the receiver 2001 can transmit information transmitted from the transmitter 1001. In other words, the start timing of the second code that modulates the transmitted information can be easily found.

  Further, as described above, the second code of the synchronization code generation circuit 38 for detecting the synchronization of the received signal has a longer code length than the first code of the partial code generation circuit 53. Therefore, the extraction accuracy of the start timing of the entire received signal can be improved.

  However, since the second code of the synchronous code generation circuit 38 has a longer code length than the first code of the partial code generation circuit 53, the first exclusive OR operation circuit controlled by the first demodulation circuit 37 is used. The operation of 36 has a much larger calculation amount than the operation of the fourth exclusive OR operation circuit 52 controlled by the second demodulation circuit 54.

  Therefore, as described above, the first demodulation circuit 37 sets a constant threshold value for the correlation detection calculation result, and controls so that the correlation detection calculation result is equal to or greater than the threshold value. Then, the first demodulation circuit 37 aborts the operation of the first exclusive OR operation circuit 36, assuming that synchronization is achieved when the threshold value is exceeded. In this way, the amount of calculation of the first exclusive OR operation circuit 36 is greatly increased under conditions in which a rapid change in radio wave propagation environment does not easily occur over time, such as a wireless network for monitoring and controlling social infrastructure equipment. Can be reduced. The threshold value may be determined based on the previous calculation result.

  As described above, under the condition that the radio wave propagation environment does not easily change with time, the start timing of the entire received signal once determined by the first demodulation circuit 37 rarely changes greatly with time. Therefore, a change in the radio wave propagation environment that occurs rarely in time is dealt with by the processing by the first demodulation circuit 37 having a large calculation amount (processing for extracting the start timing of the entire received signal), and other small changes. It is efficient to deal with the above by processing by the second demodulation circuit 54 (extraction processing of start timing of each partial area). Thus, by performing the processing in two stages, the digital signal processing amount of the entire receiver 2001 can be significantly reduced, and the start timing extraction speed can be increased.

  Note that the synchronization detector 24 (the first adder 34, the first variable delay circuit 35, the first exclusive OR operation circuit 36, the synchronization code generation circuit 38, and the first demodulation circuit 37) is omitted. Although it is not impossible, if omitted, the accuracy regarding the start timing of the entire received signal extracted by a single calculation process is inferior, and the repetition time of the calculation process is increased due to the poor accuracy. The synchronization detection unit 24 uses the signal of the sum of the reception fields of the two antennas 21 and 22 orthogonal to each other, whereas the partial area information extraction unit 25 uses the signal of the reception field of a single antenna. For this reason, in the partial area information extraction unit 25, since the energy of the received signal is low, the SN ratio is deteriorated and the accuracy of detecting the synchronization of the received signal is lowered.

The operation of the partial area information extraction unit 25 will be further described.
As described above, when there are a plurality of reflectors between the transmitter 1001 and the receiver 2001, the electromagnetic wave radiated from the transmitter 1001 reaches the receiver 2001 through a plurality of reflections. When the electromagnetic wave is reflected, it undergoes a polarization angle shift (polarization angle shift) inherent to the polarization angle of the polarization vector on the reflection surface. The amount of this polarization angle shift differs for each polarization angle of the polarization vector. That is, the electromagnetic waves in the partial regions (A1 to A4) of the first code generation unit 1 are subjected to different polarization angle shifts because the polarization angles are different from each other.

  Electromagnetic waves that have passed through a plurality of transmission paths reach the receiver 2001, but each of the antennas 21 and 22 of the receiver 2001 has a certain polarization angle (that is, a polarization angle orthogonal to the reception polarization angle of the antenna). Cannot receive electromagnetic waves. Therefore, the signals received by the antennas 21 and 22 of the receiver 2001 lack a signal having a certain polarization angle, that is, a signal that has passed through a certain transmission path. In other words, the signals received by the antennas 21 and 22 of the receiver 2001 are obtained by combining signals that have passed through a plurality of transmission paths except for a certain transmission path.

  Therefore, in the receiver 2001, the received signals corresponding to the partial areas (A1 to A4) are signals that have passed through different transmission paths. For example, the reception signal corresponding to the partial area A1 and the reception signal corresponding to the partial area A2 are signals that have passed through different transmission paths. Then, the second demodulation circuit 54 selects a signal on a transmission path having a high reception intensity among signals that have passed through a plurality of transmission paths.

  More specifically, electromagnetic waves radiated from the transmitter 1001 reach the receiver 2001 via transmission paths having different path lengths due to the influence of reflection. For example, it is assumed that the electromagnetic wave radiated from the transmitter 1001 reaches the receiver 2001 via transmission paths L1, L2, L3, and L4 (path length: L1 <L2 <L3 <L4) having different path lengths. At this time, the electromagnetic waves that have arrived through the transmission lines L1, L2, L3, and L4 arrive in the order of the transmission lines L1, L2, L3, and L4, that is, are out of phase with each other.

  The electromagnetic wave that has reached the receiver 2001 is detected by the synchronization detection unit 24 at the starting point of the information signal. Specifically, when the condition C1 that the value of the correlation detection calculation result between the received signal and the second code of the synchronization code generation circuit 38 is equal to or greater than a predetermined value and the intensity of the received signal is equal to or greater than the predetermined value is satisfied In addition, the starting point of the information signal is detected.

  For example, when the received signal on the transmission line L1 satisfies the condition C1, the start point of the information signal is detected from the received signal on the transmission line L1. When the reception signal of the transmission line L1 does not satisfy the condition C1, it is checked whether or not the next arrival signal of the transmission line L2 satisfies the condition C1. When the reception signal on the transmission line L2 satisfies the condition C1, the start point of the information signal is detected from the reception signal on the transmission line L2.

  The received signal received by the first receiving antenna 21 passes through the second variable delay circuit 41a and the second exclusive OR operation circuit 42a as signals E (1) to E (4), respectively. Are input to the fourth variable delay circuits 51 (1) to 51 (4), and correlation detection calculation is performed with the partial code generation circuits 53 (1) to 53 (4). When the condition C2 that the value of the correlation detection calculation result is equal to or greater than the predetermined value and the intensity of the signals E (1) to E (4) is equal to or greater than the predetermined value is satisfied, the partial code generation circuit 53 is provided. Extracted as partial region information corresponding to partial regions A1 to A4 of (1) to 53 (4).

  Similarly, the received signal received by the second receiving antenna 22 passes through the third variable delay circuit 41b and the third exclusive OR operation circuit 42b, and becomes signals E (5) to E (8). Each is input to the fourth variable delay circuits 51 (5) to 51 (8), and correlation detection calculation is performed between the partial code generation circuits 53 (5) to 53 (8). When the condition C2 that the value of the correlation detection calculation result is equal to or greater than the predetermined value and the intensity of the signals E (5) to E (8) is equal to or greater than the predetermined value is satisfied, the partial code generation circuit 53 is provided. Extracted as partial area information corresponding to partial areas A1 to A4 of (5) to 53 (8).

  For example, whether or not the reception signal of the transmission line L1 satisfies the condition C2 is checked in the second demodulation circuit 54 (1). If the condition C2 is satisfied, the reception signal of the transmission line L1 is partially Extracted as partial area information corresponding to the partial area A1 of the code generation circuit 53 (1). In this case, there is no phase shift of the partial area information corresponding to the partial area A1 with respect to the start point of the information signal.

  Similarly, the received signal of the transmission line L1 is checked in the second demodulation circuits 54 (2) to 54 (4) whether or not the condition C2 is satisfied, and if the condition C2 is satisfied, the transmission line The received signal of L1 is extracted as partial area information corresponding to the partial areas A2 to A4 of the partial code generation circuits 53 (2) to 53 (4). In this case, there is no phase shift of the partial area information corresponding to the partial areas A2 to A4 with respect to the start point of the information signal.

  However, if the received signal on the transmission line L1 does not satisfy the condition C2 in the second demodulation circuit 54 (2), for example, the received signal on the transmission line L1 is a part of the partial code generation circuit 53 (2). It is not extracted as partial area information corresponding to the area A2. The reason why the received signal of the transmission line L1 does not satisfy the above condition C2 is that the reflected signal is reflected on the transmission line, which causes a polarization angle shift in the partial region A2, and as a result, the received signal received by the first receiving antenna 21 This is because the strength of is insufficient.

  For example, when the reception signal of the transmission line L2 satisfies the condition C2 in the second demodulation circuit 54 (2), the reception signal of the transmission line L2 is the partial region A2 of the partial code generation circuit 53 (2). Is extracted as partial region information corresponding to. In this case, the phase shift amount of the partial area information corresponding to the partial area A2 with respect to the start point of the information signal is a time difference between the reception signal of the transmission line L1 and the reception signal of the transmission line L2.

  Similarly, for example, when the reception signal of the transmission line L2 satisfies the condition C2 in the second demodulation circuit 54 (5), the reception signal of the transmission line L2 is a part of the partial code generation circuit 53 (5). Extracted as partial area information corresponding to the area A1. In this case, the phase shift amount of the partial area information corresponding to the partial area A1 with respect to the start point of the information signal is a time difference between the reception signal of the transmission line L1 and the reception signal of the transmission line L2.

  Similarly, for example, when the reception signal of the transmission line L4 satisfies the condition C2 in the second demodulation circuit 54 (8), the reception signal of the transmission line L4 is a part of the partial code generation circuit 53 (8). Extracted as partial area information corresponding to the area A4. In this case, the phase shift amount of the partial area information corresponding to the partial area A4 with respect to the start point of the information signal is a time difference between the reception signal of the transmission line L1 and the reception signal of the transmission line L4.

  Thus, the received signals (received signals with high received intensity) selected by the second demodulating circuit 54 in the partial areas (A1 to A4) are respectively signals that have passed through different transmission paths, and as a result, different phase shifts. Will be shown.

  In the above description, the condition that the intensity of the received signal is greater than or equal to the predetermined value is used in the conditions C1 and C2. Instead, the condition that the SN ratio is greater than or equal to the predetermined value, or It is also possible to use a condition that the strength and the SN ratio are each equal to or greater than a predetermined value.

Moreover, in this radio | wireless communications system, an external intruder can be detected as follows.
The transmitter 1001 corresponds to each partial area (A1 to A4) of the first code generation unit 1, that is, uses a different code string (partial code of the first code) corresponding to the polarization angle, and transmits the same information signal. Send. The receiver 2001 uses the code string (partial code of the first code), that is, the received information using the code string corresponding to each partial area (A1 to A4) of the partial code generation circuit 53. The signal is restored in each partial area, and the information signal of each restored partial area is compared by the information processing unit 28 of the receiver 2001.

  If there is a mismatch in the information of each restored partial area, the information processing unit 28 can recognize that information has been falsified by an external intruder on the transmission path corresponding to the partial area where the mismatch has occurred. . In this case, the information processing unit 28 may reject the information in the partial area where the information has been tampered with. In this way, it is possible to detect the presence of an external intruder and suppress impersonation by the external intruder. Impersonation by an outside intruder is mixing illegal information.

Further, in the present wireless communication system, communication reliability can be improved in addition to detection of an external intruder.
Also in this case, the transmitter 1001 transmits the same information signal by using different code sequences (partial codes of the first code) corresponding to the partial areas (A1 to A4) of the first code generation unit 1. The information processing unit 28 of the receiver 2001 determines the appropriate information from the result of the same information signal reaching the receiver 2001 from the transmitter 1001, that is, the information on each partial area (A1 to A4) of the partial area information extraction unit 25. Choose one. For example, the information processing unit 28 determines that the information of the partial areas (A1 to A4) having the same information content or the information having the largest number of pieces of information that are the same as the information transmitted from the transmitter 1001. Consider.

Moreover, in this radio | wireless communications system, the information signal to transmit can be concealed using a 3rd code | symbol as follows.
In this case, first, a known information signal is encoded by the transmitter 1001 with the first code and the second code and wirelessly transmitted. Then, the receiver 2001 checks the interrelationship of information signals in each partial area of the partial area information extraction unit 25. Then, a third code is generated using the mutual relationship. Using this third code, the transmitter 1001 encodes an information signal to be transmitted and wirelessly transmits it.

  Specifically, the interrelationship of information signals in each partial area of the partial area information extraction unit 25, for example, the interrelationship such as temporal change in received power amplitude, temporal change in signal quality, or phase shift amount in each partial area. Then, a known information signal is transmitted and checked, and a specific code string (third code) is created using the mutual relationship. Then, the transmitter 1001 superimposes the code string (third code) on the information signal to be transmitted and transforms and transmits the original signal (information signal to be transmitted).

  In this way, since the receiver 2001 can generate the above-described correlation (that is, the third code) from the received signal, the information signal can be restored using the third code. An intruder (for example, a wireless eavesdropper) cannot generate the interrelation (that is, the third code) from the received signal, and cannot restore the information signal. Thus, the third code functions as a secret code for concealing the information signal to be transmitted.

  For example, the information signal can be transmitted by transmitting the same information signal with a different code (partial code of the first code) corresponding to the polarization angle. Since the information signal undergoes different polarization angle shifts for different polarization angles in the transmission path, the synthetic relationship of these electromagnetic waves arriving at the receiver 2001 is due to the symmetry with respect to communication transmission and reception and the duality of the electromagnetic waves. Only the transmission point (transmitter 1001) and the reception point (receiver 2001) are unique. Therefore, an outside intruder who does not exist at the transmission point and the reception point has no means of knowing the combination relationship (that is, the mutual relationship of information signals in each partial area).

  FIG. 2C is a block diagram of a modification of the receiver in the first embodiment of the present invention. The modification of FIG. 2C is different from the example of FIG. 2B in the following points. That is, in the modification of FIG. 2C, the fourth variable delay circuits 51 (M + 1) to 51 (2M), the fourth exclusive OR operation circuits 52 (M + 1) to 52 (2M) in the example of FIG. The code generation circuits 53 (M + 1) to 53 (2M) and the second demodulation circuits 54 (M + 1) to 54 (2M) are deleted, and the switches 43 (1) to 43 (M) and the switches 44 (1) to 44 ( M) and second adders 45 (1) to 45 (M) are added. When the switches 43 (1) to 43 (M), the switches 44 (1) to 44 (M), and the second adders 45 (1) to 45 (M) are referred to as representatives, the switches 43, 44, referred to as a second adder 45. In the example of FIG. 2C, M = 4.

  The switch 43 is controlled by the first demodulation circuit 37 and the second demodulation circuit 54 to switch the output of the second exclusive OR operation circuit 42a in a time-sharing manner to the second adder 45. Output. Specifically, the switch 43 (1) is in an ON state in which the output of the second exclusive OR operation circuit 42a is output to the adder 45 (1) only during the period A1 of the partial area of the partial code generation circuit 53. . Similarly, the switches 43 (2) to 43 (4) respectively output the output of the second exclusive OR operation circuit 42a during the period A2 to A4 in the partial area of the partial code generation circuit 53. 2) to 45 (4), the output is turned on.

  The switch 44 performs the time-division switching for the period A1 to A4 of the partial area of the partial code generation circuit 53, and then the first demodulation circuit 37 and the second demodulation in the next period A1 to A4. Controlled by the circuit 54, the output of the third exclusive OR circuit 42 b is switched in a time-sharing manner and output to the second adder 45. Specifically, the switch 44 (1) outputs the output of the second exclusive OR circuit 42a to the adder 45 (4) only during the period A4 of the partial area, and then the partial code The output of the third exclusive OR circuit 42b is output to the adder 45 (1) only during the period A1 of the partial region of the generation circuit 53. Similarly, the switches 44 (2) to 44 (M) respectively output the output of the third exclusive OR operation circuit 42b during the period A2 to A4 in the partial area of the partial code generation circuit 53. 2) to 45 (4), the output is turned on.

  Specifically, the second demodulation circuits 54 (1) to 54 (4) turn on the switch 43 and the switch 44 during the period A 1 to A 4 in the partial area of the partial code generation circuit 53. The first demodulation circuit 37 turns on the switch 43 and the switch 44 during a period in which a predetermined time is added before and after each of the periods A1 to A4 in the partial area. For example, the first demodulation circuit 37 turns on the switch 43 (1) and the switch 44 (1) during a period in which a predetermined time is added before and after the period A1 of the partial area.

  In this way, in the example of FIG. 2C, the output of the second exclusive OR operation circuit 42a and the output of the third exclusive OR operation circuit 42b are respectively set to the periods A1 to A4 of the partial areas, By switching in a time division manner, the number of the fourth variable delay circuit 51, the fourth exclusive OR operation circuit 52, the partial code generation circuit 53, and the second demodulation circuit 54 is reduced.

According to the first embodiment, at least the following effects can be obtained.
(A1) The transmitter encodes the transmission information with the first code and the second code, then superimposes the carrier wave, generates a transmission signal whose polarization plane rotates at the frequency fr, and wirelessly transmits the signal. For the received signal received from the transmitter, the start point of the information signal is detected using the second code, and the partial area information corresponding to each partial area of the first code is respectively detected using the start point of the information signal. Since the wireless communication system is configured to extract and detect the phase shift of the partial area information, when the information signal arrives via a plurality of transmission paths between the transmission and reception, it corresponds to each partial area It becomes possible to identify a phase shift of information, that is, to distinguish a transmission path through which an information signal passes.
(A2) The transmitter further encodes the transmission information with a third code generated to reflect the characteristics of the transmission path when the partial area information is transmitted to the receiver. When the wireless communication system is configured so that information corresponding to each partial region extracted using the first code is decoded using the third code, transmission information acquisition by an external eavesdropper can be suppressed.
(A3) The transmission information is the same in each partial area, and the receiver extracts each partial area information, and then determines whether the extracted partial area information is the same. When configuring a wireless communication system, the reliability of communication can be improved, or the presence or absence of an external intruder can be detected.
(A4) The transmission information is identical to each other in each partial area, and the receiver obtains information having a larger number of pieces of identical information as transmission information from the transmitter among the partial area information. In the case of configuring a wireless communication system, it is possible to improve the reliability of communication or to suppress an impersonation act by an outside intruder.
(A5) The transmitter, after encoding the transmission information with the first code and the second code, generates a cosine wave signal and a sine wave signal with a frequency fr, wirelessly transmits the cosine wave signal from the first antenna, A sine wave signal is wirelessly transmitted from a second antenna that is spatially orthogonal to the first antenna, and the receiver uses a third antenna and a fourth antenna that is spatially orthogonal to the third antenna to generate a cosine wave. The signal and the sine wave signal are received, the start point of the information signal is detected using the second code, and the partial area information corresponding to each partial area of the first code is extracted based on the start point of the information signal. In addition, since the wireless communication system is configured to detect a phase shift of each partial area information, the functions of the transmitter and the receiver according to the present invention can be easily realized.
(A6) The receiver uses the second code superimposed on the third and fourth information signals based on the sum of the third information signal received by the third antenna and the fourth information signal received by the fourth antenna. Since the wireless communication system is configured so as to detect the synchronization of the signals, it is easy to receive all the energy of the signals arriving at all the polarization angles.
(A7) The receiver extracts partial region information based on the third information signal received by the third antenna, detects a phase shift of the partial region information, and receives the fourth information signal received by the fourth antenna. Based on the above, the wireless communication system is configured to extract the partial area information and detect the phase shift of the partial area information, so that when the information signal arrives via a plurality of transmission paths between transmission and reception, It becomes easy to identify the phase shift of the partial area information, that is, to distinguish the transmission path through which the information signal passes.
(A8) A change in the radio wave propagation environment that occurs rarely in time is handled by the processing by the first demodulation circuit 37 having a large amount of calculation (processing for extracting the start timing of the entire received signal), and other small Since the wireless communication system is configured to cope with the change by the processing by the second demodulation circuit 54 (extraction processing of the start timing of each partial area), the digital signal processing amount of the entire receiver is greatly reduced. In addition, the extraction speed of the start timing can be increased.

(Second embodiment)
Next, a second embodiment of the present invention will be described.
In the present embodiment, an example in which the configuration of the carrier wave superimposing unit 7 is changed in the transmitter 1001 of the first embodiment will be described.

  FIG. 3A is a configuration diagram of the transmitter 1002 of the second embodiment. In the transmitter 1002, the carrier wave superimposing unit 7 includes a carrier wave generating circuit 11, a second multiplier 12, a sine wave generator 301 having a frequency fr, a third multiplier 302, and 90 ° corresponding to the frequency fr. And a phase shift circuit 303. Other configurations are the same as those of the transmitter 1001 of the first embodiment. The same components as those in FIG. 2A already described are denoted by the same reference numerals and description thereof is omitted.

  The output of the sine wave generator 301 having the frequency fr is superimposed on the output of the second multiplier 12 via the third multiplier 302. The signal on which the sine wave of the frequency fr is superimposed is branched into two. One branched signal is radiated from the first transmitting antenna 8 into the air. The other branched signal is radiated from the second transmitting antenna 9 into the air via the 90 ° phase shift circuit 303 corresponding to the frequency fr.

  The envelope of the amplitude of the signal superimposed with a sine wave having a frequency fr different from the carrier frequency is a sine wave having the frequency fr. Therefore, a difference of 90 ° in terms of space and time is used by using two of them. By radiating into the air, an electromagnetic wave whose polarization vector rotates at the frequency fr can be generated as in the first embodiment.

  According to the second embodiment, compared with the transmitter 1001 of the first embodiment of FIG. 2A, the sine weight circuit 14 and the cosine weight circuit 13 which are generally nonlinear circuits can be reduced, and a simple phase shift circuit 303 is obtained. A transmitter can be realized by using. Therefore, it is effective in reducing the cost of the transmitter.

(Third embodiment)
Next, a third embodiment of the present invention will be described.
In this embodiment, another example in which the configuration of the carrier wave superimposing unit 7 is changed in the transmitter 1001 of the first embodiment will be described.

  FIG. 3B is a configuration diagram of the transmitter 1003 of the third embodiment. In the transmitter 1003, the carrier wave superimposing unit 7 includes a carrier wave generation circuit 11, a second multiplier 12, a sine wave generator 311 having a frequency fr, a third multiplier 302, and a cosine wave generator having a frequency fr. 312 and a fourth multiplier 313. Other configurations are the same as those of the transmitter 1001 of the first embodiment. The same components as those in FIGS. 2A and 3A described above are denoted by the same reference numerals and description thereof is omitted.

  The output of the second multiplier 12 is branched into two, and the output of the sine wave generator 311 having the frequency fr is superimposed on one of the branched signals via the third multiplier 302, Radiated from the transmitting antenna 8 into the air. The output of the cosine wave generator 312 having the frequency fr is superimposed on the other signal branched from the second multiplier 12 via the fourth multiplier 313 and is radiated from the second transmitting antenna 9 into the air. The

  As described in the second embodiment, since the envelope of the amplitude of the signal superimposed with the frequency fr different from the carrier frequency becomes a sine wave of the frequency fr, two of them are used spatially and temporally. By radiating in the air with a difference of 90 °, it is possible to generate an electromagnetic wave whose polarization vector rotates at the frequency fr as in the first embodiment.

  According to the third embodiment, since the 90 ° phase shift circuit 303 whose physical dimensions are large when the rotation frequency fr of the polarization vector is small is not used, the transmitter 1003 can be downsized as compared with the second embodiment. realizable.

(Fourth embodiment)
Next, a fourth embodiment of the present invention will be described.
In the transmitter 1004 of the present embodiment, an example in which the configuration of the carrier wave superimposing unit 7 is changed in the transmitter 1001 of the first embodiment will be described. In the receiver 2004 of this embodiment, an example in which the configuration of the carrier removal unit 23 is changed in the receiver 2001 of the first embodiment will be described.

  FIG. 4A is a configuration diagram of the transmitter 1004 of the fourth embodiment. In the transmitter 1004, the carrier wave superimposing unit 7 includes a first carrier wave generation circuit 401 having a frequency fc1, a second multiplier 12, a second carrier wave generation circuit 402 having a frequency fc2, and a third multiplier 302. The transmission composition circuit 403 and the 90 ° phase shift circuit 303 are included. Other configurations are the same as those of the transmitter 1001 of the first embodiment. The same components as those already described in FIGS. 2A, 3A, and 3B are denoted by the same reference numerals, and description thereof is omitted.

  FIG. 4B is a configuration diagram of the receiver 2004 of the fourth embodiment. In the receiver 2004, the carrier removal unit 23 includes a local signal generation circuit 32 having a frequency fc1, a first mixer 31a, a first analog filter 33a, a third local signal generation circuit 426 having a frequency fc2, and a first A third mixer 423, a third analog filter 428, a first reception synthesis circuit 421, a second local signal generation circuit 425 having a frequency fc1, a second mixer 31b, and a second analog filter 33b. , A fourth local signal generation circuit 427 having a frequency fc2, a fourth mixer 424, a fourth analog filter 429, and a second reception synthesis circuit 422. Other configurations are the same as those of the receiver 2001 of the first embodiment. The same components as those already described in FIG. 2B are denoted by the same reference numerals and description thereof is omitted.

  In the transmitter 1004, the output of the encoding unit 6 is branched into two. The second multiplier 12 superimposes the output of the first carrier wave generation circuit 401 having the frequency fc1 on one of the branched signals. The third multiplier 302 superimposes the output of the second carrier wave generation circuit 402 having the frequency fc2 on the other branched signal. The frequencies fc1 and fc2 have a relationship in which ½ of the difference between fc1 and fc2 is the frequency fr (fr = | fc1−fc2 | / 2). The outputs of the second multiplier 12 and the third multiplier 302 are combined by the transmission combining circuit 403 and then branched into two. One branched signal is radiated from the first transmitting antenna 8 into the air. The other branched signal is radiated from the second transmitting antenna 9 into the air via the 90 ° phase shift circuit 303 corresponding to the frequency fr = | fc1−fc2 | / 2.

  In the receiver 2004, the received signal taken from the first receiving antenna 21 is branched into two. One of the branched reception signals is multiplied by the output of the first local signal generating circuit 32 by the first mixer 31a, and then the carrier wave frequency is removed by the first analog filter 33a, and then the first reception signal is received. It becomes an input of the synthesis circuit 421.

  The other branched reception signal is multiplied by the output of the third local signal generation circuit 426 by the third mixer 423, and then the carrier wave frequency is removed by the third analog filter 428, and then the first reception signal is received. This becomes another input of the synthesis circuit 421. The output of the first reception synthesis circuit 421 becomes the input A of the FPGA 3001 shown in FIG. 2B.

  The received signal taken from the second receiving antenna 22 is branched into two. One of the branched reception signals is multiplied by the output of the second local signal generation circuit 425 by the second mixer 31b, and then the carrier frequency is removed by the second analog filter 33b, and then the second reception signal is received. This is input to the synthesis circuit 422.

  The other branched reception signal is multiplied by the output of the fourth local signal generation circuit 427 by the fourth mixer 424, and then the carrier frequency is removed by the fourth analog filter 429, and then the second reception signal is received. This becomes another input of the synthesis circuit 422. The output of the second reception synthesis circuit 422 becomes the input B of the FPGA 3001 shown in FIG. 2B.

  In the first embodiment, a high-frequency circuit using a frequency fr (frequency at which the polarization vector rotates) belonging to a frequency band (for example, 1 MHz) different from a carrier frequency (for example, 400 MHz) is required. On the other hand, in this embodiment, the transceiver need only include a high-frequency circuit using the frequencies (fc1, fc2) of two carriers belonging to the same frequency band, and does not need a high-frequency circuit using the frequency fr.

  As described above, in this embodiment, the transmitter is encoded with the first code and the second code using the frequency f1 and the frequency f2 in which ½ of the difference between the frequency f1 and the frequency f2 is the frequency fr. The transmitted information is branched, a first signal is generated by superimposing a carrier of frequency f1 on the one of the branched transmission information, and a carrier of frequency f2 is added to the other transmitted information. Is generated to generate a second signal, and the first signal and the second signal are combined to generate a cosine wave signal of frequency fr and a sine wave signal of frequency fr. The transmitter and the receiver do not include an oscillator having a frequency fr that is a frequency band different from the frequency band of the carrier wave. Therefore, this embodiment has not only the same effect as the first embodiment but also the effect of suppressing external radiation (spurious radiation) in the unnecessary frequency band generated by the radio.

(5th Example)
Next, a fifth embodiment of the present invention will be described.
In the transmitter 1005 of the present embodiment, another example in which the configuration of the carrier wave superimposing unit 7 is changed in the transmitter 1004 of the fourth embodiment will be described. The radio signal transmitted from the transmitter 1005 according to the present embodiment can be received by the receiver 2004 according to the fourth embodiment.

  FIG. 5 is a configuration diagram of the transmitter 1005 of the fifth embodiment. In the transmitter 1005, the carrier wave superimposing unit 7 includes a first carrier wave generation circuit 401 having a frequency fc1, a second multiplier 12, a second carrier wave generation circuit 402 having a frequency fc2, and a third multiplier 302. , Transmission synthesis circuit 403, third carrier generation circuit 501 with frequency fc1, second 90 ° phase shift circuit 505 corresponding to frequency fc1, fourth multiplier 313, and fourth carrier with frequency fc2 The generation circuit 502, a third 90 ° phase shift circuit 506 corresponding to the frequency fc2, a fifth multiplier 503, and a second transmission synthesis circuit 504 are configured. Other configurations are the same as those of the transmitter 1004 of the fourth embodiment. The same components as those already described in FIGS. 2A, 3A, 3B, and 4A are denoted by the same reference numerals, and description thereof is omitted.

  The output of the encoding unit 6 is branched into two systems, and one of the branched systems is further branched into B1 and B2. The second multiplier 12 superimposes the output of the first carrier wave generation circuit 401 having the frequency fc1 on one of the branched B1 signals. The third multiplier 302 superimposes the output of the second carrier wave generation circuit 402 having the frequency fc2 on the other branched B2 signal. The frequencies fc1 and fc2 have a relationship of frequency fr = | fc1−fc2 | / 2. The outputs of the second multiplier 12 and the third multiplier 302 are combined by the first transmission combining circuit 403 and then radiated from the first transmitting antenna 8 into the air.

  The other branch of the output of the encoding unit 6 is further branched to B3 and B4. The output of the third carrier wave generation circuit 501 having the frequency fc1 is superposed by the fourth multiplier 313 via the second 90 ° phase shift circuit 505 to one of the branched B3 signals. The output of the fourth carrier wave generation circuit 502 having the frequency fc2 is superimposed on the other branched B4 signal by the fifth multiplier 503 via the third 90 ° phase shift circuit 506. The outputs of the fourth multiplier 313 and the fifth multiplier 503 are combined by the second transmission combining circuit 504 and then radiated from the second transmitting antenna 9 into the air.

  According to the present embodiment, as in the fourth embodiment of FIG. 4A, the transmitter does not include an oscillator having a frequency fr that is a frequency band different from the frequency band of the carrier wave. Radiation).

  In the fourth embodiment shown in FIG. 4A, the phase shift circuit 303 needs a large amount of phase shift corresponding to the frequency fr of the rotational polarization. On the other hand, since the phase shift circuits 505 and 506 of the present embodiment are phase shift circuits having a carrier frequency higher than the frequency fr, the amount of phase shift is extremely small. The ratio of the amount of phase shift between the phase shift circuit of this embodiment and the phase shift circuit of the fourth embodiment is substantially the same as the ratio of the carrier frequency to the frequency fr of the rotational polarization. Therefore, in this embodiment, there is a great effect that the transmitter can be downsized.

(Sixth embodiment)
Next, a sixth embodiment of the present invention will be described.
In the transmitter 1006 of the present embodiment, another example in which the configuration of the carrier wave superimposing unit 7 is changed in the transmitter 1005 of the fifth embodiment will be described. The radio signal transmitted from the transmitter 1006 of the present embodiment can be received by the receiver 2004 of the fourth embodiment.

  FIG. 6 is a configuration diagram of the transmitter 1006 of the sixth embodiment. In the transmitter 1006, the carrier wave superimposing unit 7 includes a first digital cosine wave signal generation circuit 601 having a frequency fc1, a first transmission delta-sigma circuit 602, a first transmission digital filter 603, and a second multiplier. 12, a second digital cosine wave signal generation circuit 604 having a frequency fc2, a second transmission delta sigma circuit 605, a second transmission digital filter 606, a third multiplier 302, a transmission synthesis circuit 403, , A first digital sine wave signal generation circuit 611 having a frequency fc1, a third transmission delta-sigma circuit 612, a third transmission digital filter 613, a fourth multiplier 313, and a second digital having a frequency fc2. A sine wave signal generation circuit 614, a fourth transmission delta-sigma circuit 615, a fourth transmission digital filter 616, a fifth multiplier 503, and a second Configured to include a transmission synthesis circuit 504. Other configurations are the same as those of the transmitter 1005 of the fifth embodiment. The same components as those already described in FIGS. 2A, 3A, 3B, 4A, and 5 are denoted by the same reference numerals, and the description thereof is omitted.

  The output of the encoding unit 6 is branched into two systems, and one of the branched systems is further branched into B1 and B2. The second multiplier 12 superimposes the output C1 of the first transmission digital filter 603 on one of the branched B1 signals. The first digital cosine wave signal generation circuit 601, the first transmission delta sigma circuit 602, and the first transmission digital filter 603 that generate a carrier wave having the frequency fc1 are cascade-coupled, and the first digital cosine is generated. The output of the wave signal generation circuit 601 is input to the first transmission delta sigma circuit 602, and the output of the first transmission delta sigma circuit 602 is input to the first transmission digital filter 603.

  The third multiplier 302 superimposes the output C2 of the second transmission digital filter 606 on the other branched B2 signal. A second digital cosine wave signal generation circuit 604 that generates a carrier wave having a frequency fc2, a second transmission delta sigma circuit 605, and a second transmission digital filter 606 are cascade-coupled, and the second digital cosine. The output of the wave signal generation circuit 604 is input to the second transmission delta sigma circuit 605, and the output of the second transmission delta sigma circuit 605 is input to the second transmission digital filter 606.

  The outputs of the second multiplier 12 and the third multiplier 302 are combined by the first transmission combining circuit 403 and then radiated from the first transmitting antenna 8 into the air. The frequencies fc1 and fc2 have a relationship of frequency fr = | fc1−fc2 | / 2.

  The other branch of the output of the encoding unit 6 is further branched to B3 and B4. The fourth multiplier 313 superimposes the output C3 of the third transmission digital filter 613 on one of the branched B3 signals. The first digital sine wave signal generation circuit 611, the third transmission delta sigma circuit 612, and the third transmission digital filter 613 that generate a carrier wave having the frequency fc1 are cascade-coupled, and the first digital sine wave is generated. The output of the wave signal generation circuit 611 is input to the third transmission delta sigma circuit 612, and the output of the third transmission delta sigma circuit 612 is input to the third transmission digital filter 613.

  The fifth multiplier 503 superimposes the output C4 of the fourth transmission digital filter 616 on the other branched B4 signal. The second digital sine wave signal generation circuit 614 that generates the carrier wave having the frequency fc2, the fourth transmission delta sigma circuit 615, and the fourth transmission digital filter 616 are cascade-coupled, and the second digital sine wave is generated. The output of the wave signal generation circuit 614 is input to the fourth transmission delta sigma circuit 615, and the output of the fourth transmission delta sigma circuit 615 is input to the fourth transmission digital filter 616.

  The outputs of the fourth multiplier 313 and the fifth multiplier 503 are combined by the second transmission combining circuit 504 and then radiated from the second transmitting antenna 9 into the air. Except for the two transmitting antennas 8 and 9, the entire circuit of the transmitter 1006 is formed inside the FPGA 3006.

  In this embodiment, the transmitter is configured to generate a cosine wave signal having a frequency fr and a sine wave signal having a frequency fr using a discrete-time delta-sigma circuit, so that all circuits except the antennas 8 and 9 are configured. It can be implemented in the FPGA 3006. Therefore, the transmitter can be significantly reduced in size as compared with the transmitter 1005 of the fifth embodiment.

(Seventh embodiment)
Next, a seventh embodiment of the present invention will be described.
In the receiver 2007 of the present embodiment, an example in which the configuration of the carrier wave removal unit 23 is changed in the receiver 2001 of the first embodiment will be described. The receiver 2007 of the present embodiment can receive radio signals transmitted from the transmitter 1004 of the fourth embodiment, the transmitter 1005 of the fifth embodiment, and the transmitter 1006 of the sixth embodiment.

  FIG. 7 is a configuration diagram of a receiver 2007 according to the seventh embodiment. In the receiver 2007, the carrier removal unit 23 includes a first reception analog filter 33a, a first delta sigma addition circuit 716, a first delta sigma analog filter 715, a first delta sigma comparator 714, A second delta sigma adder circuit 726, a second delta sigma analog filter 725, a second delta sigma comparator 724, a second receive analog filter 33b, a third delta sigma adder circuit 736, Delta sigma analog filter 735, third delta sigma comparator 734, fourth delta sigma adder circuit 746, fourth delta sigma analog filter 745, fourth delta sigma comparator 744, and first internal clock 711, a first delta-sigma quantizer 712, Ruta sigma sample and hold circuit 713, second internal clock 721, second delta sigma quantizer 722, second delta sigma sample and hold circuit 723, synthesis circuit 727, and third internal clock 731 A third delta sigma quantizer 732, a third delta sigma sample and hold circuit 733, a fourth internal clock 741, a fourth delta sigma quantizer 742, and a fourth delta sigma sample and hold circuit 743 and a synthesis circuit 747. Other configurations are the same as those of the receiver 2001 of the first embodiment. The same components as those already described in FIG. 2B are denoted by the same reference numerals and description thereof is omitted.

  Of the configuration of the carrier removal unit 23, a first internal clock 711, a first delta sigma quantizer 712, a first delta sigma sample hold circuit 713, a second internal clock 721, A second delta-sigma quantizer 722, a second delta-sigma sample and hold circuit 723, a synthesis circuit 727, a third internal clock 731, a third delta-sigma quantizer 732, and a third delta A sigma sample and hold circuit 733, a fourth internal clock 741, a fourth delta sigma quantizer 742, a fourth delta sigma sample and hold circuit 743, and a synthesis circuit 747 are included in the FPGA 3007.

  In the receiver 2007, the reception signal taken from the first reception antenna 21 is branched into two via the first reception analog filter 33a. One of the branched reception signals is operated at the first delta sigma addition circuit 716, the first delta sigma analog filter 715 operating at the frequency fc1 (specifically, increasing the pass level of the frequency component of fc1), It is connected to the input A of the FPGA 3007 through a cascade connection with one delta-sigma comparator 714.

  The other branched reception signal is connected to the FPGA 3007 via a cascade connection of the second delta sigma addition circuit 726, the second delta sigma analog filter 725 operating at the frequency fc 2, and the second delta sigma comparator 724. To the input A ′.

  The received signal taken from the second receiving antenna 22 is branched into two via the second receiving analog filter 33b. One of the branched reception signals is connected to the FPGA 3007 through a cascade connection of the third delta sigma addition circuit 736, the third delta sigma analog filter 735 operating at the frequency fc1, and the third delta sigma comparator 734. Connected to input B.

  The other branched received signal is connected to the FPGA 3007 through a cascade connection of a fourth delta sigma adder circuit 746, a fourth delta sigma analog filter 745 operating at the frequency fc2, and a fourth delta sigma comparator 744. To the input B ′.

  The FPGA 3007 converts the signal of the input A into a discrete signal by the first delta sigma quantizer 712 combined with the first internal clock 711, and outputs it to the synthesis circuit 727. The FPGA 3007 adds the discrete signal to the input of the first delta sigma adder circuit 716 as a continuous signal via the first delta sigma sample hold circuit 713.

  Further, the FPGA 3007 converts the signal of the input A ′ into a discrete signal by the second delta sigma quantizer 722 coupled with the second internal clock 721 and outputs it to the synthesis circuit 727. The FPGA 3007 adds the discrete signal to the input of the second delta sigma addition circuit 726 as a continuous signal via the second delta sigma sample and hold circuit 723. The output of the synthesis circuit 727 reaches the internal point C of the FPGA 3007.

  Further, the FPGA 3007 converts the signal of the input B into a discrete signal by the third delta sigma quantizer 732 combined with the third internal clock 731, and outputs it to the synthesis circuit 747. The FPGA 3007 adds the discrete signal to the input of the third delta sigma adder circuit 736 as a continuous signal via the third delta sigma sample hold circuit 733.

  Further, the FPGA 3007 converts the signal of the input B ′ into a discrete signal by the fourth delta sigma quantizer 742 coupled with the fourth internal clock 741, and outputs it to the synthesis circuit 747. The FPGA 3007 adds the discrete signal to the input of the fourth delta sigma addition circuit 746 as a continuous signal via the fourth delta sigma sample hold circuit 743. The output of the synthesis circuit 747 reaches the internal point D of the FPGA 3007.

  The internal point C and the internal point D of the FPGA 3007 are the same positions as the internal point C and the internal point D of the FPGA 3001 in FIG. 2B. That is, the configuration of the FPGA 3007 after the internal point C and the internal point D is the same as the configuration after the internal point C and the internal point D of the FPGA 3001 in FIG. 2B. Note that the inputs A and B of the FPGA 3007 are different from the inputs A and B of the FPGA 3001 in FIG.

  In this embodiment, since the receiver is configured to remove the carrier wave from the radio signals received by the third antenna and the fourth antenna using the continuous time delta sigma circuit, the carrier of the signal input to the receiver The noise-to-noise ratio can be improved by the noise shaving function of the delta-sigma circuit (the above-described configurations 711 to 716, 721 to 726, 731 to 736, and 741 to 746), and the reception sensitivity of the receiver can be improved.

  Next, transmission having two systems of the first code generation unit 1, the second code generation unit 2, the third code storage unit 3, the transmission information generation unit 4, the third encoding unit 5 and the encoding unit 6 of FIG. Examples of the machine will be described in the eighth to ninth embodiments. An example of a receiver having two systems of the synchronization detection unit 24 and the partial region information extraction unit 25 of FIG. 1 will be described in the tenth embodiment.

(Eighth embodiment)
An eighth embodiment of the present invention will be described.
In the transmitter 1007 of the present embodiment, in the transmitter 1004 of the fourth embodiment, the first code generation unit 1, the second code generation unit 2, the third code storage unit 3, the transmission information generation unit 4, and the first of FIG. An example of a transmitter having two systems of three encoding units 5 and encoding units 6 will be described. The radio signal transmitted from the transmitter 1007 of this embodiment can be received by the receiver 2008 of the tenth embodiment described later.

FIG. 8A is a configuration diagram of the transmitter 1007 of the eighth embodiment. The same components as those in FIG. 4A already described are denoted by the same reference numerals, and description thereof is omitted.
In the transmitter 1007, the components 1 to 6 of the transmitter 1004 in FIG. 4A are duplicated. That is, the component elements 1 ′ to 6 ′ are provided separately from the component elements 1 to 6. The components 1 ′ to 6 ′ have the same functions as the components 1 to 6, respectively. However, the information I ′ generated by the component 4 ′ (transmission information generator) is different from the information I generated by the transmission information generator 4, and the frequency f _I 1 of the information signal of the component 4 ′ is The frequency f _I 2 of the information signal of the component 4 is different.

  The output from the component 6 is input to the third multiplier 302, and the output from the component 6 ′ is input to the second multiplier 12. Subsequent configuration of the transmitter 1007 (first carrier generation circuit 401, second multiplier 12, second carrier generation circuit 402, third multiplier 302, transmission synthesis circuit 403, 90 ° The phase shift circuit 303, the first transmission antenna 8, and the second transmission antenna 9) are the same as the configuration of the transmitter 1004 in FIG. 4A.

  According to the present embodiment, signal processing similar to that of the transmitter 1004 in FIG. 4A can be performed for different frequencies of the frequencies fc1 and fc2. In the transmitter 1007 in FIG. 8A, signals of different carrier frequencies fc1 and fc2 are generated for information signals in a low frequency region that can be regarded as being constant compared to the rotational polarization and the frequency fr of the first code or the frequency of the second code. It is superimposed. Since signals transmitted at different frequencies fc1 and fc2 are independent of each other, in the receiver 2008 of the tenth embodiment to be described later, the fc1 system (CD system) and the fc2 system (C′-D ′). The information decoded in the above system) is also independent of each other, and the information I and information I ′ transmitted from the transmitter 1007 in FIG. 8A can be easily reproduced by a digital filter on the receiver side. Therefore, according to this embodiment, the amount of information transmitted from the transmitter to the receiver can be doubled. Alternatively, when information I and information I ′ have the same content, communication quality between transmission and reception can be improved.

(Ninth embodiment)
Next, a ninth embodiment of the present invention will be described.
In the transmitter 1008 of the present embodiment, in the transmitter 1005 of the fifth embodiment, the first code generation unit 1, the second code generation unit 2, the third code storage unit 3, the transmission information generation unit 4, and the first of FIG. An example in which two systems of three encoding units 5 and encoding units 6 are provided will be described. The radio signal transmitted from the transmitter 1008 of this embodiment can be received by the receiver 2008 of the tenth embodiment described later.
FIG. 8B is a configuration diagram of the transmitter 1008 of the ninth embodiment. The same components as those already described with reference to FIG.

In the transmitter 1008 of FIG. 8B, the components 1 to 6 of the transmitter 1005 of FIG. 5 are duplicated. That is, the component elements 1 ′ to 6 ′ are provided separately from the component elements 1 to 6. The components 1 ′ to 6 ′ have the same functions as the components 1 to 6, respectively. However, the information I ′ generated by the component 4 ′ (transmission information generator) is different from the information I generated by the transmission information generator 4, and the frequency f _I 1 of the information signal of the component 4 ′ is The frequency f _I 2 of the information signal of the component 4 is different. Further, the frequencies f _I 1 and f _I 2 of the information signal are limited to be low enough to be considered constant compared to the carrier frequencies fc1 and fc2 and the frequency fr of the rotational polarization (that is, the frequency of the first code).

  The output from the component 6 is input to the third multiplier 302 and the fifth multiplier 503, and the output from the component 6 ′ is input to the second multiplier 12 and the fourth multiplier 313. The Subsequent configuration of the transmitter 1008 (first carrier generation circuit 401, second multiplier 12, second carrier generation circuit 402, third multiplier 302, transmission synthesis circuit 403, third Carrier wave generation circuit 501, second 90 ° phase shift circuit 505, fourth multiplier 313, fourth carrier wave generation circuit 502, third 90 ° phase shift circuit 506, and fifth multiplication The transmitter 503, the second transmission combining circuit 504, the first transmission antenna 8, and the second transmission antenna 9) are the same as the configuration of the transmitter 1005 in FIG.

  In this manner, the transmitter 1008 can wirelessly transmit the information I from the component 4 and the information I ′ from the component 4 ′ simultaneously from the antenna 8 and the antenna 9.

  According to the present embodiment, signal processing similar to that of the transmitter 1005 in FIG. 5 can be performed for different frequencies fc1 and fc2. In the transmitter 1008 of FIG. 8B, as in the transmitter 1007 of FIG. 8A, the information signal in the low frequency region that can be regarded as constant compared to the rotational polarization and the frequency fr of the first code or the frequency of the second code. , Signals of different carrier frequencies fc1 and fc2 are superimposed. Since signals transmitted at different frequencies fc1 and fc2 are independent of each other, in the receiver 2008 of the tenth embodiment to be described later, the fc1 system (CD system) and the fc2 system (C′-D ′). The information decoded in the above system) is also independent of each other, and the information I and information I ′ transmitted from the transmitter 1008 in FIG. 8B can be easily reproduced by a digital filter on the receiver side. Therefore, according to the present embodiment, the amount of information transmitted from the transmitter to the receiver can be doubled, or the communication quality between transmission and reception can be improved.

  In the transmitter 1006 of the sixth embodiment, the first code generation unit 1, the second code generation unit 2, the third code storage unit 3, the transmission information generation unit 4, the third encoding unit 5, and the encoding unit 6 are used. Can be configured to provide two systems. The radio signal transmitted from the transmitter 1009 configured as described above can be received by the receiver 2008 of the tenth embodiment described later.

  In this case, in the transmitter 1008 of the ninth embodiment, in the transmitter 1009, the output from the component 6 and the output from the component 6 ′ are connected to the carrier wave superimposing unit 7 in FIG. The output from the element 6 and the output from the component 6 ′ are connected to the carrier wave superimposing unit 7 in FIG. That is, the output from the component 6 is input to the third multiplier 302 and the fifth multiplier 503, and the output from the component 6 ′ is input to the second multiplier 12 and the fourth multiplier 313. Entered. The subsequent configuration of the transmitter 1009 is the same as the configuration of the transmitter 1006 of FIG.

  Also in this case, as in the ninth embodiment, the information I and information I ′ transmitted from the transmitter 1009 can be easily reproduced by a digital filter on the receiver side. Therefore, the amount of information transmitted from the transmitter to the receiver can be doubled, or the communication quality between transmission and reception can be improved.

(Tenth embodiment)
Next, a tenth embodiment of the present invention will be described.
In the receiver 2008 of the present embodiment, an example in which two systems of the synchronization detection unit 24 and the partial region information extraction unit 25 of FIG. 1 are provided in the receiver 2007 of the seventh embodiment will be described.
FIG. 8C is a configuration diagram of the receiver 2008 of the tenth embodiment. The same components as those already described with reference to FIG.

  The FPGA 3008 included in the receiver 2008 has two functions of the synchronization detection unit 24 and the partial area information extraction unit 25 in FIG. 1 and these functions operate in parallel. That is, the first adder 34, the first variable delay circuit 35, the first exclusive OR operation circuit 36, the first demodulation circuit 37, the synchronous code generation circuit 38, and the second variable in the FPGA 3007 of FIG. The delay circuit 41a, the third variable delay circuit 41b, and the like have two systems, and these functions operate in parallel.

  In the FPGA 3008, the configurations 711 to 716, the configurations 721 to 726, the configurations 731 to 736, and the configurations 741 to 746 are the same as the configurations with the same reference numerals in the FPGA 3007 in FIG. 7, and these operations are also the same as the operations in the FPGA 3007. However, in the FPGA 3008, the synthesis circuit 727 and the synthesis circuit 747 in the FPGA 3007 do not exist, and the connection destination of the output of the first delta-sigma quantizer 712 and the connection destination of the output of the second delta-sigma quantizer 722. The connection destination of the output of the third delta sigma quantizer 732 and the connection destination of the output of the fourth delta sigma quantizer 742 are different from those in the FPGA 3007.

  That is, in the FPGA 3008, the output of the first delta-sigma quantizer 712 branches after reaching the internal point C of the FPGA 3007, and is input to the first adder 34 and the second variable delay circuit 41a. . The output of the second delta sigma quantizer 722 branches after reaching the internal point C ′ and is input to the first adder 34 ′ and the second variable delay circuit 41 a ′. The output of the third delta sigma quantizer 732 branches after reaching the internal point D, and is input to the first adder 34 and the third variable delay circuit 41b. Further, the output of the fourth delta sigma quantizer 742 branches after reaching the internal point D ′ and is input to the first adder 34 ′ and the third variable delay circuit 41 b ′.

  According to the present embodiment, signal processing similar to that of the receiver 2004 of FIG. 4B and the receiver 2007 of FIG. 7 can be performed for different frequencies fc1 and fc2. Since signals transmitted at different frequencies fc1 and fc2 from the transmitter 1007 in FIG. 8A and the transmitter 1008 in FIG. 8B are independent of each other, the fc1 system (CD system) in FIG. Information decoded in the system (system C′-D ′) is also independent of each other, and the information I and the information I ′ transmitted from the transmitter 1007 in FIG. 8A and the transmitter 1008 in FIG. Can be easily reproduced with a filter. Therefore, according to the present embodiment, the amount of information transmitted from the transmitter to the receiver can be doubled, or the communication quality between transmission and reception can be improved.

(Eleventh embodiment)
Next, an eleventh embodiment of the present invention will be described. In this embodiment, a configuration example of a communication system using a transceiver to which the wireless system of the present invention is applied will be described. FIG. 10 is an example of a configuration diagram of an elevator system to which the polarization angle division diversity radio according to the present invention is applied.

  In the elevator system 100 according to the present embodiment, the elevator cage 111 moves up and down inside the building 101. On the floor inside the building 101, a base station radio 103a according to the present invention and a base station 2 orthogonal polarization integrated antenna 102a are coupled and installed. A base station radio 103b according to the present invention and a base station 2 orthogonally polarized integrated antenna 102b are coupled and installed on a ceiling portion inside the building 101.

  Base station radios 103a and 103b include the functions of transmitter 1000 and receiver 2000 of FIG. 1, respectively. The base station 2 orthogonal polarization integrated antennas 102a and 102b include the first transmitting antenna 8, the second transmitting antenna 9, the first receiving antenna 21 and the second receiving antenna 22 of FIG.

  A terminal station 2 orthogonal polarization integrated antenna 112 a is installed on the outer floor surface of the lifting cage 111 and is coupled to the terminal radio 113 by a high-frequency cable 114. Further, a terminal station 2 orthogonal polarization integrated antenna 112 b is installed on the external ceiling of the lifting cage 111, and is coupled to the terminal radio 113 by a high-frequency cable 114.

  The terminal radio 113 includes the functions of the transmitter 1000 and the receiver 2000 of FIG. The terminal station 2 orthogonal polarization integrated antennas 112a and 112b include the first transmitting antenna 8, the second transmitting antenna 9, the first receiving antenna 21 and the second receiving antenna 22 of FIG.

  Since the base station radio 103 (103a, 103b) and the terminal station radio 113 use the inside of the building 101 as a radio transmission medium, the electromagnetic waves transmitted between the base station radio 103 and the terminal station radio 113 are Multiple reflections are received by the inner wall of the building 101 and the outer wall of the elevating cage 111 to form a multiwave interference environment.

  In the present embodiment, since the present invention is applied to the base station radio 103 and the terminal station radio 113, highly secure radio transmission can be realized even in a multi-wave interference environment. Therefore, the elevator cage 111 can be controlled and monitored remotely from the building 101 side by wireless connection means using the base station radio 103 and the terminal station radio 113. Therefore, it is not necessary to use a wired connection means such as a cable between the elevator cage 111 and the base station radio 103, and therefore the same transportation capacity can be realized with a smaller building volume. Alternatively, with the same building volume, it is possible to improve the transportation capacity without increasing the elevator dimensions.

(Twelfth embodiment)
Next, a twelfth embodiment of the present invention will be described. In this embodiment, a configuration example of a communication system using a transceiver to which the wireless system of the present invention is applied will be described. FIG. 11 is an example of a configuration diagram of a substation equipment monitoring system to which the polarization angle division diversity radio according to the present invention is applied.

  In the substation equipment monitoring system 120 of the present embodiment, a plurality (12 in the example of FIG. 11) of the substations 121 and a plurality (four in the example of FIG. 11) of base stations 124 that are smaller than the number of substations 121 are included. And are installed. Base station apparatus 124 is installed in the vicinity of a plurality of transformers 121.

  A terminal station radio 123 according to the present invention and a terminal station 2 orthogonal polarization integrated antenna 122 are coupled and installed in each of the transformers 121. In the base station device 124, a base station radio 126 according to the present invention and a base station 2 orthogonal polarization integrated antenna 125 are coupled and installed.

  Terminal station radio 123 and base station radio 126 include the functions of transmitter 1000 and receiver 2000 in FIG. 1, respectively. The terminal station 2 orthogonally polarized integrated antenna 122 and the base station 2 orthogonally polarized integrated antenna 125 are respectively the first transmitting antenna 8, the second transmitting antenna 9, the first receiving antenna 21 and the second antenna of FIG. And a receiving antenna 22.

  The size of the transformer is on the order of several meters (meters), and is overwhelmingly larger than the wavelength corresponding to the frequency (several hundred MHz to several GHz) of electromagnetic waves used by the terminal station radio 123 and the base station radio 126. Therefore, the electromagnetic waves between the transformation machine 121 and the base station apparatus 124 are subjected to multiple reflections by the plurality of transformation machines 121, and a multi-wave interference environment is formed.

  In this embodiment, since the present invention is applied to the terminal station radio 123 and the base station radio 126, highly secure radio transmission can be realized even in a multi-wave interference environment. Therefore, the control and monitoring of the transformer 121 can be performed remotely from the radio base station 124 by the wireless connection means using the terminal station radio 123 and the base station radio 126. Therefore, it is possible to solve the problem of high-voltage induction power that becomes a problem when a wired connection means such as a cable is used between the transformation machine 121 and the base station device 124, and the installation cost of the cable can be eliminated. It is effective in improving the safety and cost of the control / monitoring system.

  In addition, this invention is not limited to the above-mentioned embodiment, It cannot be overemphasized that it can change variously in the range which does not deviate from the summary.

  DESCRIPTION OF SYMBOLS 1 ... 1st code generation part, 2 ... 2nd code generation part, 3 ... 3rd code memory | storage part, 4 ... Transmission information generation part, 5 ... 3rd encoding part, 6 ... Encoding part (1st multiplier) , 7 ... Carrier wave superimposition unit, 8 ... First transmission antenna, 9 ... Second transmission antenna, 10 ... Transmission unit, 15 ... Electromagnetic wave, 11 ... Carrier wave generation circuit, 12 ... Second multiplier, 13 ... Cosine Weight circuit, 14 ... sine weight circuit, 21 ... first receiving antenna, 22 ... second receiving antenna, 23 ... carrier wave removing unit, 24 ... synchronization detecting unit, 25 ... partial area information extracting unit, 26 ... receiving unit, 27: Information decoding section (decoding circuit), 28: Information processing section, 31a: First mixer, 31b: Second mixer, 32: Local signal generating circuit, 33a: First analog filter, 33b: Second Analog filter, 34 ... first adder, 35 ... first variable delay circuit, 3 ... first exclusive OR operation circuit, 37 ... first demodulation circuit, 38 ... synchronous code generation circuit, 41a ... second variable delay circuit, 41b ... third variable delay circuit, 42a ... second exclusion Logical OR operation circuit, 42b ... third exclusive OR operation circuit, 43 ... switch, 44 ... switch, 45 ... second adder, 51 ... fourth variable delay circuit, 52 ... fourth exclusive OR operation circuit, 53 ... partial code generation circuit, 54 ... second demodulation circuit, 100 ... elevator system, 101 ... building, 102 ... base station 2 orthogonal polarization integrated antenna, 103 ... base station radio, 111 ... lift 112 ... Terminal station 2 orthogonal polarization integrated antenna, 113 ... Terminal radio, 114 ... High frequency cable, 120 ... Substation equipment monitoring system, 121 ... Substation, 122 ... Terminal station 2 orthogonal polarization integrated antenna, 123 ... Terminal Station radio 124 ... base station apparatus, 125 ... base station 2 orthogonal polarization integrated antenna, 126 ... base station radio, 301 ... sine wave generator, 302 ... third multiplier, 303 ... 90 ° phase shift circuit, 311 ... sine Wave generator, 312 ... cosine wave generator, 313 ... fourth multiplier, 401 ... first carrier generation circuit, 402 ... second carrier generation circuit, 403 ... transmission synthesis circuit, 421 ... first reception synthesis Circuit 422 second reception synthesis circuit 423 third mixer 424 fourth mixer 425 second local signal generation circuit 426 third local signal generation circuit 427 fourth Local signal generation circuit, 428, third analog filter, 429, fourth analog filter, 501, third carrier generation circuit, 502, fourth carrier generation circuit, 503, fifth multiplier, 50 2nd transmission synthesis circuit, 505 2nd 90 ° phase shift circuit, 506 3rd 90 ° phase shift circuit, 601 1st digital cosine wave signal generation circuit, 602 1st transmission delta-sigma Circuit 603... First transmission digital filter 604... Second digital cosine wave signal generation circuit 605... Second transmission delta sigma circuit 606... Second transmission digital filter 611. Signal generation circuit 612 ... third transmission delta sigma circuit, 613 ... third transmission digital filter, 614 ... second digital sine wave signal generation circuit, 615 ... fourth transmission delta sigma circuit, 616 ... fourth Transmission digital filter, 711, first internal clock, 712, first delta-sigma quantizer, 713, first delta-sigma sample and hold circuit, 71 ... first delta-sigma comparator, 715 ... first delta-sigma analog filter, 716 ... first delta-sigma adder, 721 ... second internal clock, 722 ... second delta-sigma quantizer, 723 ... first Second delta-sigma sample and hold circuit, 724 ... second delta-sigma comparator, 725 ... second delta-sigma analog filter, 726 ... second delta-sigma adder circuit, 727 ... synthesis circuit, 731 ... third internal clock, 732 ... third delta sigma quantizer, 733 ... third delta sigma sample and hold circuit, 734 ... third delta sigma comparator, 735 ... third delta sigma analog filter, 736 ... third delta sigma adder circuit , 741... Fourth internal clock, 742... Fourth delta sigma quantizer, 74 4th delta-sigma sample hold circuit, 744 ... 4th delta-sigma comparator, 745 ... 4th delta-sigma analog filter, 746 ... 4th delta-sigma addition circuit, 747 ... Synthesis circuit, 1000-1008 ... Transmitter 2000, 2001, 2004, 2007, 2008 ... Receiver, 3001, 3006, 3007, 3008 ... FPGA.

Claims (15)

A wireless communication system comprising a transmitter and a receiver,
The transmitter is
A transmission information generator for generating transmission information;
A first code generation unit that generates a first code that repeats at a frequency fr, and in each partial region obtained by dividing the first code for one period on the time axis, than a cross-correlation value between different partial regions, A first code generation unit that generates the first code that is a code having a high autocorrelation value between the same partial regions;
A second code generation unit that generates a second code that is a code that can detect whether or not two series of identical codes match on the time axis;
An encoding unit that encodes the transmission information generated by the transmission information generation unit using the first code and the second code;
A transmission unit that superimposes a carrier wave on the transmission information encoded by the encoding unit, generates a transmission signal whose polarization plane rotates at a frequency fr, and wirelessly transmits the transmission signal;
The receiver
A receiver that receives a transmission signal from the transmitter and removes a carrier wave from the received signal;
A synchronization detection unit that detects a start point of the information signal using the second code with respect to the information signal from which the carrier wave is removed by the reception unit;
Using the starting point of the information signal, the partial area information corresponding to each partial area is extracted from the information signal, respectively, and a partial area information extracting unit for detecting a phase shift of the partial area information,
A wireless communication system comprising: The wireless communication system of claim 1,
The transmitter is
A third encoding unit that encodes information using a third code generated to reflect the characteristics of the transmission path when the partial region information corresponding to each partial region is transmitted to the receiver; ,
The encoding unit and the third encoding unit encode the transmission information generated by the transmission information generation unit with the first code, the second code, and the third code,
The receiver
An information decoding unit that decodes the partial region information extracted by the partial region information extraction unit using the third code;
A wireless communication system. The wireless communication system of claim 1,
The transmission information generation unit of the transmitter generates transmission information that is the same in each partial region,
The receiver
An information processing unit for determining whether or not the plurality of partial region information extracted by the partial region information extraction unit are the same;
A wireless communication system. The wireless communication system of claim 3,
The information processing unit of the receiver acquires, as transmission information from the transmitter, information having the largest number of pieces of information that are identical to each other among the plurality of partial area information.
A wireless communication system. The wireless communication system of claim 1, comprising:
The transmitter is
A carrier wave superimposing unit that superimposes a carrier wave on the transmission information encoded by the encoding unit to generate a cosine wave signal having a frequency fr and a sine wave signal having a frequency fr;
A first antenna that wirelessly transmits the cosine wave signal;
A second antenna that is spatially orthogonal to the first antenna and wirelessly transmits the sine wave signal;
The receiver is
A third antenna for receiving a composite signal of the cosine wave signal and the sine wave signal;
A fourth antenna that is spatially orthogonal to the third antenna and receives the combined signal;
A carrier removal unit that removes a carrier from the combined signal received by the third antenna and the fourth antenna;
A wireless communication system. The wireless communication system of claim 5,
The synchronization detection unit of the receiver is
Based on the sum of the third information signal received by the third antenna and the fourth information signal received by the fourth antenna, synchronization of the second code superimposed on the third and fourth information signals is performed. Detect
The partial area information extraction unit of the receiver is
Based on the third information signal, the partial area information is extracted and a phase shift of the partial area information is detected. Based on the fourth information signal, the partial area information is extracted and the partial area information is extracted. Detect the phase shift of
A wireless communication system. The wireless communication system of claim 5,
The carrier wave superimposing unit of the transmitter is
Using the frequency f1 and the frequency f2 in which 1/2 of the difference between the frequency f1 and the frequency f2 is the frequency fr,
The transmission information encoded by the encoding unit is branched, a first signal is generated by superimposing a carrier wave of the frequency f1 on the branched transmission information, and the other branched signal is generated. A second signal is generated by superimposing the carrier wave having the frequency f2 on the transmission information, the first signal and the second signal are synthesized, and the cosine wave signal and the sine wave signal are combined. Generate,
A wireless communication system. The wireless communication system of claim 5,
The carrier wave superimposing unit of the transmitter generates the cosine wave signal and the sine wave signal using a discrete time delta-sigma circuit.
A wireless communication system. The wireless communication system of claim 5,
The carrier removal unit of the receiver removes a carrier from the combined signal received by the third antenna and the fourth antenna using a continuous time delta-sigma circuit.
A wireless communication system. An elevator control system using the wireless communication system according to claim 5,
The receiver is provided in an elevator car of the elevator control system, the third antenna and the fourth antenna of the receiver are provided in the upper part or the lower part of the elevator car,
The first antenna and the second antenna of the transmitter are provided at positions facing the third antenna and the fourth antenna,
A wireless communication system. A substation equipment monitoring system using the wireless communication system of claim 1,
The substation monitoring system is configured to include at least one base station and at least one substation,
The transmitter is provided in the base station, and the receiver is provided in the transformer.
A wireless communication system. A transmission information generator for generating transmission information;
A first code generation unit that generates a first code that repeats at a frequency fr, and in each partial region obtained by dividing the first code for one period on the time axis, than a cross-correlation value between different partial regions, A first code generation unit that generates the first code that is a code having a high autocorrelation value in the same partial region;
A second code generation unit that generates a second code that is a cyclic code, wherein the second code is a code that can detect whether or not two second codes match on a time axis. A code generator;
An encoding unit that encodes the transmission information generated by the transmission information generation unit using the first code and the second code;
A transmitter that superimposes a carrier wave on the transmission information encoded by the encoder, generates a transmission signal whose polarization plane rotates at a frequency fr, and wirelessly transmits the transmission signal;
A transmitter comprising: The transmitter of claim 12, wherein
A third encoding unit that encodes an information signal with a third code generated to reflect the characteristics of the transmission path when the partial region information corresponding to each partial region is transmitted to the receiver; ,
The encoding unit and the third encoding unit encode the transmission information generated by the transmission information generation unit using the first code, the second code, and the third code,
A transmitter characterized by that. An information signal including a first code that repeats at the frequency fr and a second code that is a code that can detect whether or not two series of identical codes coincide on the time axis is superimposed on the carrier wave, and the polarization plane is A receiving unit that receives a radio signal rotating at a frequency fr and removes a carrier wave from the radio signal;
A synchronization detection unit that detects a start point of the information signal using the second code with respect to the information signal from which the carrier wave is removed by the reception unit;
Using the starting point of the information signal, the partial information corresponding to each partial region obtained by dividing the first code for one period on the time axis is extracted from the information signal, and the partial region information A partial region information extraction unit for detecting each phase shift;
A receiver comprising: 15. A receiver according to claim 14, comprising:
Using the third code generated to reflect the characteristics of the transmission path when the partial area information corresponding to each partial area is transmitted from the transmitter that transmits the wireless signal to the receiver, An information decoding unit for decoding the information extracted by the partial area information extracting unit;
A receiver comprising:

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