JPS63289737A - Electromagnetic contactor - Google Patents

Abstract

(57) [Summary] This bulletin contains application data before electronic filing, so abstract data is not recorded.

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an electromagnetic contactor, and more particularly to an apparatus for controlling an electromagnetic contactor.

A magnetic contactor is known from U.S. Pat. No. 3,339,16-1. The electromagnetic contactor starts the motor,
This is a particularly useful switching device for lighting, switching, etc. A motor starting contactor with an overload relay system is called a motor controller. Contactors typically have a magnetic circuit that includes a fixed magnet and a movable magnet or armature that define an air gap therebetween when the contactor is open. By controlling the electromagnetic coil in response to commands, the main contact of the contactor interacts with the connectable power source to electromagnetically accelerate the gusset air toward the stationary magnet, reducing the air gap. be able to. The armature is provided with a pair of bridge contacts, the complementary elements of which are fixedly mounted within the contactor barrel housing and which engage when the magnetic circuit is energized and the armature moves. The load and its power source are connected to fixed contacts, and when the bridge contacts engage the fixed contacts, the load and its power source are connected to each other. Generally, when the armature is accelerated toward the magnet, two spring forces must be overcome. a first spring force is generated from a kickout spring;
This kickout spring is later used to separate the contacts by driving the armature in the opposite direction when the coil is deenergized. This occurs when the contacts open. The other spring begins to compress when the bridge contact abuts the stationary contact, but the armature continues to move towards the stationary contact as the air gap contracts to zero. The force of the contact spring determines the amount of current that can be carried by the closing contact,
Furthermore, it is determined how much contact friction is allowed as the contactor is repeatedly operated. It is typically desired that the contact spring be as strong as possible to increase the current carrying capacity of the contactor. However, this force must be overcome by the energy supplied to the electromagnet during the closing operation, so the stronger the contact spring, the greater the closing energy. The contactor electromagnet is often supplied with AC current and, as will be explained in more detail below, the magnetic attraction curve of the tVIi1 armature acceleration system is approximately constant in shape depending on the magnetic system utilized. In known contactors, the amount of energy supplied to the electromagnet is greater than the amount required to overcome the spring force resisting movement of the armature during acceleration. One reason for this is that when the contacts engage, they must overcome the action of relatively strong contact springs. However, excess energy is wasted, which is not desirable. However, a potentially more significant problem is the absorption of excess energy by the mechanical system as the armature completes its closing stroke. Such excess kinetic energy typically takes the form of heat, vibration, contact bounce, and shock.

Accordingly, it would be desirable to develop an electrical control system for an electromagnetic closing system that provides only the amount of energy necessary to overcome the forces resisting armature movement during the closing stroke.

It is also desirable to reduce the speed of the armature to a relatively low value, for example zero, at the point where it abuts the stationary magnet. The lower the speed, the less the movable contact bounces when it comes into contact with the fixed magnet.

The present invention includes: a first contact; a second contact driven into a position in electrical contact with the first contact; and a second contact mechanically coupled to the second contact so that current flows through the winding. an electromagnet with a movable armature responsive to drive the second contact into electrical contact with the first contact; and a mechanical resistance device arranged to resist movement of the movable armature. , wherein the amount of kinetic energy K applied to the movable armature is sufficient to overcome the resistance of the mechanical resistance device and bring the first contact and the second contact into abutment, A control element is provided for supplying a current to the winding of the electromagnet, and during the movement of the movable armature, the total amount of kinetic energy If supplied to the movable armature.

In order to further clarify the content of the invention, which proposes an electromagnetic contactor characterized in that half the current flows through the winding and is approximately equal to K, preferred embodiments shown in the accompanying drawings will be described below. .

Figures 1 and 2 in the margin below show a three-phase contactor or controller 1o. For convenience, the configuration of only one of the three poles will be explained, but the other two poles are also exactly the same. The contactor 10 has a housing 1 made of a suitable electrically insulating material such as a glass/nylon composition.
2 and controlled by the contactor 10;
Electrical load terminal 1 for connection with a circuit or system
4.16 are arranged in the housing 12. An example of such a system is schematically illustrated in FIG. Terminal 14.16
may each be configured to form a part of the three-phase terminals, the terminals 14, 16 are spaced apart from each other and
It connects internally with a conductor 20.24 extending into the center of 2.

Inside the housing, the ends of the conductors 20.24 each form suitably fixed contacts 22.26. Contact 22.2
6 are connected to each other, the terminals 14 and 16 are closed, and the contactor 10 becomes conductive. A separately manufactured coil control board 28 (as shown in FIGS. 8.9 and 10) is secured within the housing 12 in a manner to be described below, with the coil or solenoid 31 being integrated into the coil control board 28. Attach the coil or solenoid assembly 30 included as a part. A spring 32 is provided at a distance from the coil control panel 28 and forms one end of the coil assembly 30, and one end of a kickout spring 34 is fixed to this spring. kickout spring 3
At the other end of the spring 34, the support member 42 moves nine times as described later, and its lower part 42A picks up the spring 34 and holds it against the seat 32.
It is in contact with the portion 12A of the housing 12 until it is brought into pressure contact with the portion 12A of the housing 12. The pressure contact occurs in a plane outside the plane of FIG.

Spring 34 surrounds armature 40 and supports lower part 42
It is picked up by the lower part 42A at a position intersecting A. The dimension of member 42 in front of the plane of FIG.
A fixed magnet or a magnetic material slug 36 is arranged in an appropriate manner within the fixed magnet 36 in the same passage 38 with a position shifted from the fixed magnet 36 in the axial direction, and the fixed magnet 36 is arranged in the same passage 38 in the longitudinal direction (axial direction). ) is provided with a magnetic armature or magnetic flux conducting member 40 capable of 8wJ. An electrically insulating contact support member 42 that projects in the longitudinal direction is provided at the end of the armature 40 opposite to the fixed magnet 36, and an electrically conductive contact bridge 44 is attached to this. A contact 46 is mounted on one radial arm of the contact bridge 44, and a contact 48 is mounted on the other radial arm. It goes without saying that all three pairs of these contacts have the same configuration in a three-pole contactor. When the internal circuit is completed between the terminals 14 and 16 with the closing of the contactor 1o, the contact 46 comes into contact with the contact 22 (22-46), and the contact 48 comes into contact with the contact 26 (26-46). 48). Conversely, when contact 22 separates from contact 46 and contact 26 separates from contact 48, the internal circuit between terminals 14 and 16 opens, such an open circuit condition being illustrated in FIG. The provision of an arc box 50 surrounding the contact bridge 44 and the terminals 22, 26, 46.48 creates a partially enclosed space inside the housing in which the current flowing between the terminals 14.16 can be safely interrupted. ing. A recess 52 is provided in the center of the arc box 50, and the cross spar 54 of the contact support member 42 is inserted into this recess, and the crossbar 54 of the contact support member 42 is inserted while being fixed so that it does not bend laterally (radially) as shown in FIG. It is made to be able to move or slide in the longitudinal direction (@ direction) of the center line 38A of the passage 38. Contact bridge 44 is held to support member 42 by contact springs 56 . Contact 22-46.26-4
Contact spring 56 is compressed so that contact support member 42 continues to press against slug 36 even after contact 8 is in abutting or "closed" condition. Further compression of the contact spring 56 significantly increases the pressure on the closing contacts 22-46 and 26-48, increasing the current carrying capacity of the internal circuit between the terminals 14.16 and ensuring that the contacts remain in contact even after significant contact wear. Magnet 36 and movable armature 4
0 defines an air gap 58 in which magnetic flux is generated when coil 31 is energized.

The externally accessible terminals in the terminal block J1 are arranged on the coil control board 28 in such a way that they can be connected to the coil or solenoid 31, particularly via printed circuit paths or other conductors on the coil control board 28. Another terminal block JX (shown in FIG. 32) may also be provided on the printed circuit board 28 with another purpose. When the coil or solenoid 31 is energized via the externally accessible terminal in the terminal block J1, the stationary magnet or slug 36 is activated, for example in response to the generation of a contact closure signal in said externally accessible terminal block J1. , air gap 58 and armature 40 . As is well known, in this condition the armature 40 moves longitudinally within the passageway 38 to shorten the air gap 58 and eventually abut the magnet or slug 36. This movement is initially resisted by the compressive force of the kickout spring 34, and at the later stage of the movement stroke of the armature 4o, the contact points 22-46, 26-4
After contact 8 comes into contact, new resistance is applied due to the compressive force of the contact spring 56.

Also provided within the housing 12 of the contactor 10 (also shown in Figures 8.9 and 10) is an overload relay printed circuit board or card 60 (of which only 62B is shown in Figure 2). Ta)
Embodiments in which a current-voltage transducer 62 is provided are also possible. In embodiments of the invention that utilize overload relay board 60, conductor 24 is connected to annular opening 62T of current-to-voltage transducer 62B such that current flowing through conductor 24 can be sensed by current-to-voltage transducer 62B. It should be configured so that it passes through. By using the detected information in a manner described later, circuit information necessary for the contactor 10 can be obtained.

Another embodiment of the present invention is shown in FIGS. 30 and 31, in which a configuration in which a selector switch 64 accessible from the outside of the housing 12 is also provided at one end of the overload relay board 60 is also possible. Its configuration and operation will be described later.

FIG. 3 depicts four intersecting curves to illustrate the current technology: a magnetic solenoid, such as that shown at 31 in FIG. 2; a kick-out spring, such as that shown at 34; The relationship between force and distance is shown for a contact spring as shown at 56, and the relationship between instantaneous velocity and distance is shown for an armature as shown at 40 (curve 92).
). In both curves, the independent variable is distance,
Time, which is closely related to distance in the curve of FIG. 3, can also be an independent variable. For convenience of explanation, the components of the contactor 10 shown in FIG. 2 will be described as an example, but this does not mean that the components shown in FIG. 2 as a whole are included in the known technology. A first curve 70 shows the distance (or time) versus force relationship for a kickout spring (eg 34) as it begins to be compressed from point 72. 74 is spring 3
4 and the spring 34 resists compression with increasing force until a point 78 on the distance axis is reached.

Point 721 Point 749 Curve 701 Point 76, Point 78 and Point 72
The area bounded by the line connecting the armature 40 is the total amount required to compress the kickout spring and close the air gap 58 between the armature 40 and the fixed magnet 36 by movement of the armature 40 as the armature 40 is accelerated. Represents the amount of energy. This force resists movement of armature 40. At point 80 on the distance axis, for example, the second
When the contacts 22-42, 26-48 of the figures are brought into abutment and the armature 40 continues to move, the contact spring 56 is compressed, exerting an even greater force on the already abutting contacts for the reasons discussed above. Let it work.

Curve 79 represents the total force acting on movable armature 40 as it is accelerated towards closing air gap 58.

When the contacts 22-42, 26-48 make contact, the force increases in a step function between points 81 and 82. This force gradually increases until the combination of kickout spring 34 and contact spring 56 exerts a maximum force on the moving armature 40 at point 78. contact spring 56
The amount of supplementary energy that the moving armature must supply to overcome the resistance of points 81, 82.
It is represented by a region surrounded by a line connecting curve 793 points 84 and 76, curve 76A, and point 81.

Therefore, in the process of accelerating the armature 40 from the non-actuated position 72 to the abutment position 78 with the magnet 36, at least the coil or solenoid 31 moves at points 72, 74, 8
1, 82, 84, 713 and 72 must be supplied with the amount of energy represented by the lines 0. The positive slope of the curve 70 is such that the armature 4
must be made as small as possible so that the contactor is driven in the opposite direction and the contactor is opened again. The initial force that armature 4o has to overcome in the first phase of its movement is the force threshold represented by the difference between points 72, 74.

The armature must therefore provide at least a force corresponding to this force at this point. Therefore,
For purposes of explanation, assume that electromagnetic coil 31 provides the force 88 (FIG. 3) required by armature 40 at point 72. Also, the force provided by the coil or solenoid 31 at point 8 in FIG.
It must be greater than the force expressed by the distance between 0.82 and 0.82, otherwise the accelerating armature air 40 will stall midway and the contact between the contacts 22-46 and 26-48 will be extremely weak. This is a condition in which the contacts tend to weld and shunt, which is not preferable. Therefore, the force provided by coil 31 in accelerating armature 40 is
The force must be greater than the force shown in The magnetic attraction curve for a solenoid and its associated movable armature will vary depending on a variety of factors such as armature weight, magnetic field strength, air gap size, etc. Such a curve will have a relatively predictable shape. It is shown at 86 in Figure 3. The relative shape of the curve 86 and the constraints up to the point 80, i.e. the coil 3 at points 72 and 80 on the distance axis in FIG.
1 determines the entire magnetic attraction curve of the armature 40 and coil 31 shown in FIG. This curve ends at a force of 90. Note that the magnetic attraction curve is characterized in that the magnetic force increases significantly as the moving armature 40 approaches the fixed magnet 36 and the air gap 58 narrows. Therefore, force 90 is exhibited at point 78. It is at this point 78 that the armature 40 first abuts or contacts the stationary magnet 36. However, as a result, two inconvenient situations occur. First, as is clear from the drawing, points 72, 88 . The total energy supplied by the coil 31 to the magnetic system, represented by the line connecting curve 863 points 90.78 and 72, is much greater than the amount of energy required to overcome the various spring resistances; this energy difference is Point 74.88. Curve 869 points 90, 84, 82° 81
and is again represented by an area surrounded by a line connecting to point 74. This energy is wasted or unnecessary energy, and it would be extremely advantageous if this energy did not have to be generated. A second disadvantageous property or event is that the acceleration of armature 40 is at its maximum just before it abuts magnet 36, generating most of its kinetic energy. As shown in FIG. 3, a velocity curve 92 beginning at point 72 and ending at point 94 represents the velocity of armature 40 accelerating along the axial motion path due to the change in shape at point 80 as it engages kickout spring 34. I want to be noticed. Just before armature 40 contacts magnet 36, velocity v1 reaches its maximum value. This is extremely inconvenient because the speed at the moment when the armature 40 and the magnet 36 collide or abut each other is high, so a high kinetic energy is transmitted. This energy must be instantaneously dissipated or absorbed by other elements of the system. Typically, an instantaneous drop in energy is required to instantaneously reduce the armature velocity to zero at point 78. This kinetic energy is converted into impact sounds, heat, "bounces," vibrations, mechanical wear, etc. Armature 40 connects contact 4 on contact bridge 44
6-48 and contact spring 56, so that if it bounces, the mechanical system of these elements will vibrate, resulting in contact structure 22-42.26-
48 is likely to open and close rapidly and repeatedly. This is a highly disadvantageous property in electrical circuits. Therefore,
The energy delivered to coil 31 is carefully monitored and selected to provide only the exact amount of energy (or close to it) needed to overcome the resistance of kickout spring 34 and contact spring 56. It is desirable to utilize the contactor 10 of FIG. 2 in an embodiment. It is also desirable to significantly reduce the speed of the armature 40 when it comes into contact with the magnet 36 to effectively reduce the possibility of "bouncing". This is achieved by the present invention as graphically illustrated in FIG.

The explanation will be given below along with the margins and FIGS. 2.3 and 4. A family of curves related to the present invention, similar to the curves in FIG. 3 related to the prior art, is shown in FIG. In this case, the spring force curves 70.79 associated with kickout spring 34 and contact spring 56, respectively, are the same as in FIG. It is. In this N'FZs example of the invention, the magnetic attraction curve 86° representing the force supplied by the coil 31 starts at a point or force level 95 and appears at a distance 96 in order to overcome the critical force of the kickout spring. Or lasts up to power level 97. The electrical energy supplied to armature 40 by coil 31 dissipates at distance 1ii96 corresponding to force level 97. That is, the armature 40 disappears before it reaches the position of contact with the fixed magnet 36. The maximum speed Vm reached by the armature 40 at this point is shown at point 98 on the speed curve 92°. This is the maximum speed that the armature reaches while moving into contact with the magnet 36. In other words, when the supply of electrical energy from the coil 31 is cut off, the armature stops accelerating and begins to decelerate. Figure 4 1
00 is its deceleration curve, which spans the range from point 98 to point 78, and the slope changes at the position where it engages the kickout spring. This is accomplished by cutting off the flow of electrical energy to coil 31 early when distance 1i96 is reached. Only the amount of energy necessary to overcome the spring force is provided before the armature 40 completes its eight movements into abutment position with the fixed magnet 36, providing an energy efficient system. Solenoid 31
Points 96, 99, . Curve 701 points 81.82. This is an area surrounded by a line connecting curve 791 points 84 and 78 and point 96 again. This energy is applied to the armature coil 31 at a point 74.95. It is supplied over a portion represented by an area Z (not necessarily to scale) surrounded by a line connecting the curve 86°9 point 97.99 and point 74 again. Such energy balances are selected by any suitable method, such as empirical analysis of energy levels determined by experimentation. The energy represented by area Z' is utilized to compress kickout spring 34 during the initial movement of the armature, but is not utilized during the subsequent travel stroke. As discussed below, a microprocessor may be used to determine the amount of energy to be delivered. The amount of continued movement of armature 40 during the deceleration phase represented by curve 100 is determined by the kinetic energy level E reached by armature 40 at point 96 where electrical energy to coil 31 is cut off. This energy E is equal to % of the armature mass (M) multiplied by the square of the velocity (Vm) at point 98. In a system with perfect energy balance, armature 4 during deceleration
0 abuts fixed magnet 36 at zero velocity at point 78, no bouncing occurs and there is no need to absorb excess energy in the form of noise, wear, heat, etc. In addition,
It is difficult to realize the ideal as shown in Figure 4,
In fact, it goes without saying that there is no need to produce such a highly efficient system. Accordingly, FIG. 4 shows an ideal system for explaining the invention in detail, with armature 40 at exactly zero velocity and magnet 3 at point 78.
It is extremely difficult to make contact with 6. Small residual velocities are acceptable, especially when compared to the velocity 94 in known systems as shown in FIG.

2.4 and 5, which relates to a system in which the contact spring 56 is relatively strong and therefore the forces that the armature 40 has to overcome are also large. A group of curves similar to those shown in FIG. 4 was shown. In addition to the features of the embodiment described above, other features are also presented in FIG. For example, since the coil is powered for a longer time than in the embodiments described above, the speed of the movable armature 40 can reach higher values.

Higher velocity values are required because the spring force of the contact spring 56 is greater than in the embodiment shown in FIG. 4, and to overcome this it is necessary to increase the kinetic energy. The same reference symbols in FIGS. 4 and 5 represent corresponding points on the curves in both figures. In the embodiment of the invention shown in FIG. 5, kickout spring 34 and contact spring 56
The total energy required to compress points 82, 102.
Curve 79° 1 point 104, 84. Curve 79 and point 82 again
increases by the amount U represented by the area surrounded by the curve or line connecting . The remaining areas, namely points 72, 74 .
Curve 702 points 81.82. The area surrounded by the line connecting curve 79, points 84, 78 and 72 again is the same as the corresponding area in FIG. In order to obtain a larger energy U, a magnetic attraction curve 86'' is formed which is different from that shown in FIG. 4. This electric attraction curve has a slightly larger average slope;
It connects over a time represented by the distance difference between points 96 and 100, resulting in an incremental increase in energy U.

The new magnetic attraction curve 86'' is at point 9 as in Figure 4.
5 and ends at point 97', represented by the distance [100. This attraction curve produces a steeper and longer velocity curve 92'' for movable armature 40 than in FIG. 4. Peak velocity V2 is reached at point 98 DEG on velocity curve 92''. At this point, the kinetic energy (E2) of armature 40 is equal to MV2 squared. The instantaneous velocity then decreases to a curve of 100° with a clear breakpoint at velocity v1. This breakpoint represents the first contact between the armature and contact spring 56.

Increased velocity V2 and therefore increased energy E2
Since a portion of the curve 100'' is rapidly absorbed by the energy increase due to the strong, ie, high resistance, contact spring mentioned above, the curve 100'' theoretically becomes zero at the point 78 when the movable armature 40 abuts the fixed magnet 36. This will now be explained with reference to Figures 2.4 and 6. Figure 6 shows the voltage and current curves for the coil 31 and the relationship between these curves and the force curve of Figure 4. In a preferred embodiment of the invention, the coil current and voltage are controlled in the following four steps in the manner described in connection with the embodiment of FIG. 7: (1) Armature 40;
(7) ACCELERATION stage to accelerate, (2) CoAST stage to adjust the armature speed at the rear stage of the armature 8 before contact with the fixed magnet 36, (3) attenuate swing and bounce immediately after contact. Fix the armature 40 with magnet 3 to
(4) H-OLD stage to hold the armature. Please refer to Table 1 for supplementary explanation above and below. The information from Table 1 is stored in the microprocessor's memory as a menu, as described below. ACCELERATION
At step 7, time 7 is associated with point 72 on the distance axis of FIG.
Electrical energy is supplied to the coil or solenoid 31 at 2.degree. and the supply is cut off at 96.degree., associated with point 96 on the distance axis of FIG.

The energy represented by regions Z and Zo in FIG. 4 is obtained by appropriate selection of the voltage across the terminals of the coil 31 and the current flowing through the coil.

Apparatus and methods for controlling the voltages and currents are described in detail below with respect to FIG. Although suitable waveforms are shown in FIG. 6 for convenience, the apparatus for providing these waveforms will be described below. In the preferred embodiment of the invention, the voltage applied across the terminals of coil 31 has a waveform having a peak amplitude of 110. It may be an unfiltered full-wave rectified AC voltage represented by 106,
The current flowing through coil 31 is full-wave rectified, unfiltered,
An AC current pulse 108 with conduction angle control, which current flows through the coil 31 according to Table 1. Voltages may be applied to the coil 31 as shown at 106A, 106B, 106C and 106D in FIG. In one embodiment of the invention, the total power supplied to the coil 31 over a period of time from time 72° to time 96° is such that the combination of current and voltage that constitutes this is equal to or less than the time (72' - 96'). is obtained by adjusting the amplitude of the fully conducting current waveform in relation to the peak amplitude 110 of the voltage wave 106 to equal the mechanical energy required to close the contacts as described above. . However, in other embodiments of the present invention, Table 1
If a gated device, such as a triac, is connected in series with coil 31 as shown in FIG. 7 in more detail below, a predetermined portion α1 . The coil 31 is kept in a substantially non-conducting state over α2, etc., that is, in a substantially conducting state over parts β1, β2, etc., for a period of time (72' - 96').
The total amount of power supplied to the device can be adjusted. In the preferred embodiment of the invention, the number of current conduction angle control pulses is as described above, so that some coil current flows during a conduction interval due to the release of the energy magnetically stored during the previous conduction interval. Coil 3 in a manner
1 is determined by the length of time that the magnetic energy must be supplied. In an embodiment of the invention, the pulse 108 is suitably adjusted before the point 96°, yet the armature 40 is accelerated in the manner described above. It is also possible to provide an appropriate electrical energy supply to the coil 31 for this purpose. In other embodiments of the invention, sufficient energy cannot be obtained by simply adjusting the current conduction cycle at the appropriate time, and the necessary adjustments are made as described below. Note that, for example, the smooth curves or waves 106° and 108 are just ideal waveforms, and are not actually as shown. In the ideal state shown in FIG.
At point 78, the armature 40 is accelerated to an energy level E sufficient to continue to compress kickout spring 34 and contact spring 56, after which the armature decelerates and at time 78, armature 40 follows curve 100 as shown in FIG. Magnet 3 gently at zero speed to
Contact with 6. However, in reality, it is difficult to achieve such conditions. For example, a suitable time (72' −
96'), the amount of electrical energy provided by the combination of voltage waveform 106 and conduction control current waveform 108 is insufficient to provide armature 40 with the kinetic energy necessary to complete the contact closure cycle. . This state is represented by a speed curve 100A in FIG. 4, for example. That is, the armature 40 stops before contacting the fixed magnet 36. That is, zero velocity is reached. In this case, the combination spring 34-56 of the contact spring 56 and kickout spring 34 accelerates in the opposite direction of the armature 40 until it relaxes, preventing the closure of the contacts mechanically connected to the armature 40; It acts to disable the closing operation of the contactor 10. Although such a situation is inconvenient, a situation in which the armature 40 is about to come into contact with the fixed magnet 36 is even more inconvenient. This is because there is a risk that an arc will occur between the contacts and contact welding will significantly increase. Since there is not enough energy available to accelerate the armature within a reasonable time frame, the speed curve of the armature 40 can be "tweaked""on the way" based on new information.
Corrections will be necessary.

This modification is made in the CoAST portion of FIG.

In a preferred embodiment of the present invention, the armature 40 is connected to the fixed magnet 3 at a relatively low, if not zero, speed.
6, the armature deceleration curve is deflected from curve 100 to curve 100B in FIG.
The armature 40 is re-accelerated by applying a regulating current pulse 116 at l/1 at 18°. This adjustment pulse 116 sets, for example, a triac firing control angle α3 which is much larger than angles α1 and α2. In a preferred embodiment of the present invention, it is assumed that the angle α1=α2, but the angle is not necessarily limited to this condition and is selected depending on the control system used for the current conduction path to the coil 31. When the armature 40 abuts the stationary magnet 36 at a relatively low speed, the contactor 10 is in the "closed" state. Since factors such as vibration can induce extremely undesirable bouncing, the control circuit for the current in the coil 31 can be operated in a known manner as described below to reduce the number of forces acting on the abutting armature 40 and fixed magnet 36. generates a "seal in" or GRAB pulse. At least theoretically, the advancement of the armature 40 has already been stopped by contact with the magnet 36, or is about to stop;
The introduction of the contact pulse does not cause any acceleration of the armature, i.e. the bus of the armature is connected to the fixed magnet 3.
This is because it is physically blocked by the presence of 6. Rather than causing acceleration, all vibrations are damped to ensure that the contacts seal tightly. In a preferred embodiment of the invention, the contact or GRAB pulse 120 is generated by passing the coil current over a portion of the current half-wave represented by conduction angles β4, β5, and β6, and
AB step control is performed. ACCELERA
TION.

(:0AST and GRAB control operations are performed based on the principle of feedforward voltage control.The final control stage HO
In an LD, the mechanical system is almost stationary, but a certain amount of magnetism is required to keep the armature 40 in contact with the fixed magnet 36 and keep the contacts closed. There, to prevent the kickout spring 34 from accelerating the armature 40 in the opposite direction and opening the contact, a relatively small amount of current is applied, once every half-cycle, for the amount of time the contact must remain closed. , repeating the variable hold pulse 124. The amount of electrical energy required to hold armature 40 in contact with magnet 36 is necessary to accelerate armature 40 toward magnet 36 to overcome the forces of kickout spring 34 and contact spring 56 during the opening operation. much smaller than the amount. The nose 124 can be obtained by significantly increasing the fray back, retardation or firing angle, for example to α7. The angle α7 can be changed by the current pulse. That is, the next phase delay angle α8 may be larger or smaller than the angle α7. This is achieved by closed loop current control, i.e. coil 31
and readjust as necessary, as described below in connection with FIG.

FIGS. 7A to 7D are block diagrams of control circuits of the present invention. The coil control card 28 of FIGS. 2.8.9 and 10 is provided with a terminal board or strip J1 for connection with external control elements, such as the one shown in FIG. 11, for example. The terminal board J1 has terminals 1 to 5, respectively labeled with reference symbols, and terminal "2" has a resistive element R1.
One end of the resistance element R2, and the first AC input terminal of the full-wave bridge rectifier BRI are connected. The other end of resistance element R1 is connected to one end of capacitive element C1 and one end of resistance element R16. -i of resistance element R16 is set to "120 V"
The other end of resistive element R2 is shown as “AC” of bipolar linear custom analog integrated circuit module U1.
LINE" input terminal, the function of which will be described later. The "LINE" input terminal is also connected to the B40 terminal of the microprocessor U2 and one side of the capacitive element CX, and the other side of the capacitive element CX. is grounded.As the microprocessor U2, μPD75CG33E or μPD7533 manufactured by “NEC” is used.
can be adopted. The second of the bridge rectifier BRI
One side of the resistive element R6 and TRI are connected to the AC input terminal.
The anode of the gate control device Q1, such as AC, is connected, and the other side of the resistive element R6 is grounded. The other end of the capacitive element C1 is connected to the anode of the diode CRI, the cathode of the diode CR2, and the adjustment terminal of the Zener diode ZNI. The cathode of the diode CR1 is connected to one side of the capacitive element C2 and the "+■" terminal of the integrated circuit U1, and the other side of the capacitive element C2 is grounded. The "+■" terminal of integrated circuit U1 represents the supply voltage VY, which in the preferred embodiment of the invention is +10 VDC.

The anode of diode CR2 is connected to one side of capacitive element C7, and the other side of element C7 is grounded. The other terminal of Zener diode ZNI is connected to the non-regulated terminal of another Zener diode ZN2. The other side or adjustment terminal of Zener diode ZN2 is grounded. A supply voltage vX appears at the connection between the device CR2 and the anode of the capacitive element C7, which voltage is -7 VDC in the preferred embodiment of the invention.

Input terminal "1" on terminal board J1 is grounded.

Input terminal "3" on terminal board J1 is connected to one side of resistive element R3, and the other side of element R3 is connected to capacitive element C4.
is connected to one side of the linear integrated circuit U1 and the B41 terminal of the microprocessor U2.

The other side of capacitive element C4 is grounded. Terminal "4" of terminal board J1 is connected to one side of resistive element R4,
The other side of element R4 is connected to one side of capacitive element C5, the "5TART" input terminal of linear circuit U1, and the 842 terminal of microprocessor U2. The other side of capacitive element C5 is grounded. Input terminal of terminal board J1'
5'' is connected to one side of resistive element R5, and the other side of element R5 is connected to one side of capacitive element C6, linear integrated circuit U.
1 “RESET” input terminal and microprocessor U
Connect to the 843 terminal of 2. The other side of capacitive element C6 is grounded. Resistive element/capacitive element combination R3-
C4, R4-C5, and R5-C6 represent filter circuits respectively associated with input terminals "3", "4", and "5" of terminal board J1.

These filters are connected to the input “RUN” of the linear integrated circuit U1.
”, 5TART” and “RESET”, respectively.

Between the DC or output terminals of the full-wave bridge rectifier BRI,
Connect the solenoid coil 31 which has already been described and is used in the manner described in more detail below. The other main conductive terminal or cathode of gate control device Q1, such as a silicon controlled rectifier, is connected to one side of resistive element R7 and to the "CCI" terminal of device U1. The other side of resistive element R7 is grounded. The gate of the gate control device Q1, such as a silicon controlled rectifier, is connected to the linear integrated circuit U1.
Connect to the “GATE” output terminal of

The linear integrated circuit U1 is represented by the reference symbol ■Z and connected to the REF input terminal of the microprocessor U2.
V'' power supply terminal, and a resistive potentiometer element R8 for adjustment.The integrated circuit module U1 has a VDD input terminal of the microprocessor U2, a capacitive element C1.
6 and one side of resistive element R15, and the other side of element R15 is connected to one side of capacitive element C9 and the "VDDS" of linear analog module U1. ”Connect to the input terminal. The other side of capacitive elements C9 and C16 is grounded. The linear integrated circuit module U1 also includes a ground terminal "GND" for connection to a common system or ground. Integrated circuit U1 has a terminal "RS" which provides a "RES" signal to the RES input terminal of microprocessor U2. The linear integrated circuit module or chip U1 has terminals "DM" connected to one side of the capacitive element C8 and one side of the resistive element R14.
(DEADMAN). The other side of resistive element R14 is connected to the 022 terminal of microprocessor U2.

The other side of capacitive element C8 is grounded. The chip or circuit U1 has a "TRIG" input terminal which is supplied with the signal "TRIG" from the 852 terminal of the microprocessor U2. The integrated circuit U1 is the IN of the microprocessor U2.
It has a "■OK" output terminal that supplies the signal "VDDOK" to the To terminal. On the last side, the integrated circuit U1 sends a signal “C0ILCUR” to the A82 input terminal of the microprocessor U2.
It has a "CCO" output terminal that supplies Signal “Co”
ILCUR'' indicates the amount of coil current flowing through the coil 31.The internal operation of the bipolar linear integrated circuit U1 and the operation of various human forces will be described later.

Below, the other side of the margin resistance element R16 is connected to the anode of the diode CR4, and the cathode of the diode CR4 is connected to one side of the capacitive element C13, one side of the resistance element R17, and the AN3N3 of the microprocessor U2. . AN
3 input terminal is the signal “LV” which indicates the line voltage of the system under control.
The other side of the capacitive element C13 and the other side of the resistive element R17 are grounded.

The coil 1ldJ control board 28 has a signal or function “GND”.
” (ground), “MCUR” (input), “DELAY
” (input), “+5V” (power supply), “+10V”
A connector or terminal block J2 having terminals to which (power supply) and "-7v" (power supply) are supplied is separately provided. Control signals Z, A, B, C and SW are also formed here.

Terminals GND and A GND of microprocessor U2
is grounded. Terminal AN2 of microprocessor U2
is connected to the MCUR'' terminal of the terminal board J2, the terminal CL2 of the microprocessor U2 is connected to one side of the crystal Y1, and the other side of the crystal Y1 is connected to the terminal CLI of the microprocessor U2. It is also connected to one side of the terminal CL.
I is also connected to one side of the capacitive element C15. The other side of capacitive elements C14 and C15 is connected to the system ground. The terminal DVL of the microprocessor U2 is connected to the "+5V" terminal of the terminal board J2.

The linear analog circuit U1 has a built-in regulated power supply RP5, and its input is the “+■” input terminal, and its output is the “+5” input terminal.
V" output terminals. In the preferred embodiment of the present invention, the unregulated 10 volt value VY is converted into a highly regulated 5 volt signal vZ or +5V in the regulated power supply RPS. The internal output source COMP of the regulated power supply RPS is set to 3.2 volts in the preferred embodiment.
O is connected to the reference (-) of comparator COMP.

■DDS for one input (+) of comparator COMP
A signal is provided. The output of comparator COMP is VO
It is represented by K. Input terminal “LlNE”, “RUN”
, 5TART” and “RESET” are linear integrated circuit U
In the preferred embodiment of the present invention, the range of the signal supplied to the microprocessor U2 is increased by +4, regardless of whether the associated signal is a DC voltage signal or an AC voltage signal. .6 volts to -0,4
Restrict between bolts. Linear rotation 58U1 is “TRIG”
It has a built-in gate amplifier circuit GA that receives the human power and supplies the GATE output. Also, the DEADMAN signal "DM"
DEADMAN/reset circuit DMC which receives the reset signal RES and supplies the reset signal RES at “R3”
An inhibit signal is also provided to the gate amplifier GA at "I" so that the gate amplifier GA does not output the gate signal GATE when the DMAN function is performed. Further, it receives a coil current signal from terminal "CCI" and outputs an output signal C which is utilized by microprocessor U2 in a manner to be described below.
A coil current amplifier CCA is also provided which outputs o I LCUR from terminal CCO.

The functions provided by microprocessor U2 at the various input/output terminals will be discussed below.

A connector JIOI and a connector J are connected to the coil current control panel 28 via a cable 64 and have a complementary relationship therewith.
An overload relay board 6o including 102 is also provided. Above current -
Voltage transducer or transformer 62 may be represented by three transformers 62A, 62B, 62C for a three-phase electrical system dominated by overload relay board 6o. One side of each secondary winding of these current-voltage transducers 62A, 62B, 62C is grounded, and the other side is connected to a resistive element R101, R1, respectively.
02, connect to one side of R103. Resistance element R1o
t, terminals aOR and bOR connected to the other side of R102 and R103, respectively.

A triple two-channel analog multiplexer/demultiplexer or transmission gate U101 with cOR is also provided. Gate UIOI ay.

By and cy end terminals are grounded. The terminals ax, bx and CX of UIOl are electrically bundled and connected to one side of the integrating capacitor C1ot and to the anode of the rectifier CRIOI. The other side of the capacitor C101 is connected to the cathode of the rectifier CR102, and the anode of CR'102 is connected to the cathode of the rectifier CR101 and the differential amplifier U.
103 outputs and a second triple 2-channel analog
bOR1 of multiplexer/demultiplexer U102
Connect with child. The other side of the integrating capacitor C101 is also connected to the positive input terminal of a buffer amplifier containing a gain U105 and to the cOR output terminal of the second analog multiplexer/demultiplexer or transmission gate U102. The collective terminals ax, bx, and cx of the transmission gate U101 are also connected to the ay and CX terminals of the transmission gate UIO2. The CX terminal of transmission gate or analog multiplexer/demultiplexer U102 is grounded. Device U10
The aOR terminal of 2 is connected to one side of the capacitive element ClO2, and the other side of the element ClO2 is connected to the bx terminal of the multiplexer/demultiplexer U102 and the differential amplifier 01.
Connect to the negative input terminal of 03. The above differential amplifier U103
The positive input terminal of is grounded. The negative input terminal of differential amplifier U105 is connected to the wiper of potentiometer P101, one main terminal of potentiometer P101 is grounded, and the other main terminal is connected to terminal board J102, and the "MCUR" output signal is connected to one side of resistive element R103. The other side of resistive element R103 is supplied from the output of differential amplifier U105, the anode of diode CR104, and the diode CR
It is connected with 105 cathodes. Diode CR1
The anode of the diode CR104 is grounded, and the cathode of the diode CR104 is connected to the +5■ power supply terminal VZ. device UIOI,
U102 and U2O5 are supplied with power from the 17 power supply. +10
V power supply voltage is the gain amplifier U105 and the resistance element 10.
The other side of the resistive element 104 is connected to the power supply, the transmission gates U101, U2O5 and the anode of the diode CR106, and the other side of the resistive element 104 is connected to the anode of the diode CR106.
The cathode of 6 is connected to +5■ power supply voltage. The +5V power level Z of terminal board J102 is also supplied to one side of the filter capacitive element ClO3, whose other side is grounded, and to one main terminal of potentiometer P102, the other main terminal of potentiometer P102 is grounded. ing. The wiper of potentiometer P102 is on the terminal board J
A "DELAY" output signal is provided via 101 to terminal ANO of microprocessor U2. Control terminal A of the analog multiplexer/demultiplexer device U101.

B and C are parallel-serial 8-bit static shift registers U104
Connect to the A, B, and C signal terminals respectively. A word A,
B and C are terminals 032.031 of the microprocessor 42
．． 030 respectively.

An 8-pole switch 5WIOI is provided having poles AM, CO, CI, SP, HO, H1, H2, H3. One side of each switch pole is a parallel-series 8-bit static shift register U1.
5 volt power supply vZ via the PO to P7 input terminals of 04
The "COM" output terminal of the register U104 receives the "SW" signal from the terminal board J101 and the terminal 110 of the microprocessor U2. Reference symbol above “
HO" to "H3" indicate that the device controlled by the overload relay board 60 is a "heater" class. The 4iHO to H3 in the switch 5WIOI
By appropriately manipulating some or all of the above, a heater class device can be represented by the overload relay board 60.

The configuration of the printed circuit board used for manufacturing the coil control board 28 and overload relay board 60 will be explained with reference to FIGS. 2.8.9 and 10. Specifically, in addition to the terminal block J1, a coil assembly 30 is arranged on the coil control panel 28, and the coil of the coil assembly 30 is omitted from the illustration. The coil assembly 30 includes a spring seat 32 and a coil seat 31A. The coil control panel 28 is also provided with a connector J2, and one end of the flat cable 64 is inserted into the connector J2 by soldering or the like. The other end of the flat cable 64 reaches connectors J102 and J102 of the overload relay board 60. A three-phase current generator 62 is shown in Fig. 8 for three-phase current.
are shown as 62A, 62B, and 62C on the overload relay board 60. An 8-pole dip switch is provided as the switch 5W101. Also illustrated are potentiometers Plot and P102 used for factory calibration and delay adjustment, respectively.

In a preferred embodiment of the invention, the coil control board 28 and overload FJ electrical board 60 are formed on a single piece of preformed, soldered, and connected printed circuit board material. The single piece printed circuit board material is then separated in the region 100, for example by folding the neck portion 102, to form overload relay boards 60 which are hinged to each other at right angles, as is particularly apparent from FIGS. 2 and 10. and a coil control panel 28.

Next, an embodiment of a control circuit configuration using coil control≦28 and overload relay board 60 devices and electric elements will be described with reference to FIGS. 2 and 11. Specifically, three main power feed lines L1. L2. L3 is provided to provide three-phase AC power from a suitable three-phase power source. Each of these feeder lines is a contactor MA.

Power is supplied via MB and MC. Terminal block J1 includes terminals ``C'', ``E'', ``P'', 3'', ``R'', whose reference symbols represent the function or connection ``C0MM0N'', respectively.
”, “ACPOWER”.

“RUN PERMIT/5TOP”, “5TART”
-REQUEST” and “RESET”.

For example, as already apparent from FIG. 8.9.10, the coil control board 28 communicates with the overload relay board 60 via a multi-purpose cable 64. The overload relay board 60 includes a switch 5W101 that performs the above-mentioned functions, and has current transformers 62A to 6
A 2C secondary winding is connected to an overload relay board 60. Further, the secondary windings of the current transformers 62A to 62C are connected to the overload relay board 60. Current transformers 62A to 62C are connected to terminal T.
1. T2. Through T3 the lines Ll, L2 . The line L1. which is supplied to the motor is connected to L3. Instantaneous line current iL1. flowing through L2, L3. iL2. Monitor iL3. For example, the power is transmitted through the line L1. The current is supplied to the coil control panel 28 and the overload relay panel 60 via a current transformer CPT whose primary winding is connected between L2. The secondary winding of current transformer CPT connects to the "C" and "E" terminals of terminal block J1. Current transformer C
One side of the P7 secondary winding can be connected to one side of the normally closed 5TOP pushbutton and one side of the normally open RESET pushbutton. The other side of the 5TOP pushbutton connects to the "P" input terminal of terminal block J1 and one side of the normally open 5TART pushbutton. The other side of the normally open 5 TAR'T pushbutton is connected to the "3" input terminal of terminal block J1,
The other side of the RESET pushbutton is connected to the reset terminal R of terminal block J1. Control information can be supplied to the coil control panel 28 and the overload relay panel 60 by operating the push buttons in a known manner.

The configuration and operation of various current transformers 62 of the present invention will be discussed with reference to FIGS. 2, 7C, and 12-18. Conventional current sensing transformers create a secondary winding current that is proportional to the primary winding current. When the output current signal from this type of current transformer is supplied to a resistive current shunt and the shunt voltage is supplied to voltage sensing electronics such as that incorporated into the overload N1 electrical board 60, the A proportional relationship exists. An air core transformer, also called a linear coupler, can be used for current sensing by providing a secondary winding voltage that is proportional to the derivative of the current flowing through the primary winding. Conventional iron core current transformers and linear couplers have several drawbacks. One drawback is that the "turns ratio" of a conventional current transformer must be changed in order to vary the output voltage depending on the given current transformer design conditions. The rate of change of the magnetic flux appearing in the magnetic core over time is proportional to the current flowing through the primary winding in the absence of magnetic flux saturation in the magnetic core. Since an output voltage is generated that is proportional to the derivative of the current flowing through the primary winding, and the ratio between the output voltage and current changes easily, it can be applied to various current sensing applications. Iron core current transformers tend to be relatively large, but the current transformer of the present invention can be made smaller.

As is particularly clear from FIG. 12, the current transformer 62 of the present invention
X includes an annular magnetic core 110 having a substantially discontinuous air gap 111. Since the primary current iL1, ie, the current to be detected, passes through the center of the magnetic core 110, a single-turn input primary winding corresponding to the line L1 is formed. Secondary winding 112 of current transformer 62X includes multiple turns having a number of turns of N2 for convenience of explanation. Secondary winding 112 has a sufficient number of turns to output a voltage level sufficient to drive the electronic circuitry that monitors the current transformer. For convenience of explanation, the circumferential length of the magnetic core 110 is set to 11°, and the length of the air gap 111 is set to 1°.
Set it to 2.

Let the cross-sectional area of the magnetic core be A1, and the cross-sectional area of the air gap be A2. The output voltage of the current transformer is varied by varying the effective length of the air gap λ2.

This can be achieved either by inserting metal shims into the air gap 111 as shown in FIGS. 15 and 16, or by moving separate sections of the current transformer core structure eight times as shown in FIG. 111 may be made smaller or larger. Once the length of the air gap 111 is set,
A relatively compact current sensing current transformer is formed which outputs an output voltage eo(t) approximately proportional to the derivative of the input current iL1 flowing through the input winding of the current transformer. One advantage of this configuration is that it does not necessarily require the use of sinusoidal or periodic input currents.For example, the output voltage eo(t) from the secondary winding of current transformer 62X shown in FIG. It is given by (1).

N1・N2 d eO(t)= (ILlsin
cat) fll IL2 dt □+□ ... (1) μIA1 μ2A2 μm and μ2 are the magnetic permeabilities of the magnetic core 110 and the air gap 111, respectively. ω (omega) is the instantaneous current iL1
ILL is equal to the peak width of the instantaneous current iL1. If all parameters except the length of the air gap fL2 and the frequency ω remain unchanged, equation (1) simplifies to equation (2).

N 1 ・ N2 eO(t)−EωILICOS ωt] (2)k
2ffl to l+, and the term in parentheses is equivalent to the derivative part of equation (1).

The voltage eo(t) in equation (2) is 113 as shown in FIG.
In a preferred embodiment of the present invention, an integrator circuit such as
The output of is expressed by the following equation (3).

N1・N2 e'0(t) = ILlsin ωt
(3) kl+k12 When the length 12 of the air gap 111 changes, the output voltage e'0(t), which is directly proportional to the input terminal iL1, changes inversely proportional to the length 12 of the air gap 111. 14th
The figure is a graph showing the relationship between the change in the length fL2 of the air gap 111 and the value obtained by dividing the output voltage e'o(t) by the input current (for example, i Ll). In the special case where the first layer wavenumber ω is constant or is assumed to be constant, there is no need to use the integrator circuit 113 of FIG. ) can be rewritten as

eO(t) = ILlcos ωt
(4) kl+k2j22 Constant frequency term ω forms part of 4. In this case, the output eo(t) from the current transformer secondary winding 112 is equal to the input current IL
L and inversely proportional to the length 22 of the air gap 111.

With particular reference to Figure 15.16.17, if it is desired to sense several current ranges using the same current transformer, by effectively varying the length 12 of the air gap 111, the output The voltage eO(t) can be varied. To do this, it is sufficient to insert a shim of a predetermined width into the air gap of current transformer 62Y, depending on the range of the required output voltage eO(t), or insert a wedge-shaped shim into air gap 111 of current transformer 62Z. A semi-core 119 may also be inserted.

Furthermore, a similar result can be achieved in current transformer 62U of FIG. 17 by dividing its magnetic core into two portions 116A, 116B and forming two complementary air gaps 111A, 111B. Figures 12-17 illustrate a current-to-voltage transducer in which a primary winding is arranged on a magnetic core such that a magnetic flux is generated in the magnetic core that is approximately proportional to the amount of current flowing through the primary winding. The magnetic core has a discontinuous, but variable, air gap that has a first air gap that prevents magnetic saturation in the magnetic core at current values equal to or less than the value 11. Has magnetic resistance. Further, a secondary winding is arranged on the magnetic core so that a voltage V approximately proportional to the magnetic flux in the magnetic core appears at the output terminal. The voltage ■ is equal to or less than the voltage v2 for the first reluctance and for values of the current I equal to or less than 11.

The variable, but discontinuous air gap prevents magnetic saturation in the magnetic core for values of current equal to or less than 2 greater than 11. It can be changed to obtain a higher magnetoresistance value than the magnetoresistance. For a second air gap magnetoresistance value and a current value less than or equal to 2, the voltage 2 maintains a value of Vl or less.

In particular, as can be seen from FIG. 18, - there is no apparently wide discontinuous air gap 111, but the air gaps 124 are evenly distributed between the fine-grained magnetic core material 122, e.g. A homogeneous magnetic core 120 made of sintered or pressed powder metal such as ferrite is connected to a current transformer 62S.
It can also be used for. Said air gap 124 has the same effect as a discontinuous air gap such as 111 shown in FIG. 12, but reduces the effects of stray magnetic fields and allows the realization of extremely reliable compact current transformers. . This type of current transformer is made by compressing powder metal.
22 and a magnetic core with microscopic and uniformly distributed air gaps 124 around the metal grains. A magnetic core constructed in this manner does not require saturation and produces an output voltage proportional to the derivative of the excitation current. One embodiment of the invention places a non-magnetic insulating material in the air gap.

Next, the operating mode of the system will be explained in accordance with FIGS. 7A to 7D and FIGS. 11, 19, 20, and 21.
2 is represented by the LINE signal, which is used to synchronize the AC line voltage. This generates various supply voltages, eg vx, vy, vZ. Detmann circuit DMC also used as a power-on reset circuit
First, the 5 volt 10 millisecond reset signal RE
S to microprocessor U2.

This signal initializes microprocessor U2 by setting its output to a high impedance level and setting the internal program to memory location O. Switch inputs are read via inputs B41-B43. The algorithm is as shown in FIG. Under normal conditions, terminal B41. B42. B43 is an input terminal of the microprocessor U2, but is also configured as an output terminal that serves as a discharge path for the capacitor for discharging. The reason is as follows. That is, when the manual pushbutton is opened, C4, C5, and C6 may become charged as described above or due to leakage current from the microprocessor. Leakage current is mistakenly logic 1
Charge the capacitor to a voltage level that could be interpreted as Therefore, it is necessary to periodically discharge the capacitive elements C4, C5, and C6. The "READSWITC)IES" algorithm in logic block 152 in FIG. 19 asks the following questions: “Microprocessor U
Is the line voltage read from the line signal LINE at the 840 input terminal of 2 a positive half cycle? ”If the answer to this question is “yes”, the respective input terminals B41.
B42. A logic block 154 is utilized which checks whether the "5TART", "RUN" and "RESET" signals at B43 are digital 1s or digital 0s. Regardless of the answer, when the above question is asked, function block 1
In the next step of the algorithm shown in 56, the instruction "
DISC) IARGE CAPACITORS" is issued. At this point, terminals B41-B43 of microprocessor U2 are internally set to zero, discharging the capacitors as described above. This occurs during the positive half cycle of the line voltage. If the answer to the question posed in function block 152 is "no", then the line voltage is in the negative half cycle and it is in this half cycle that input terminals B41-B43 are released from capacitor discharge mode. , I explained about the motor control device, but
The invention can also be applied to devices that detect the presence of AC voltage signals.

After the margin initialization has been performed, the microprocessor U2 checks the input terminal INTO to monitor the state of the VOK output signal from the linear integrated circuit U1. If the voltage of the random access memory RAM contained in the microprocessor υ2 is high enough to guarantee the reliability of the already stored data, said signal becomes a digital O. Capacitive element C9 is a random access element.
The power supply voltage VDD to the memory is monitored and stored. For example, during a power outage, even if the voltage VDD is removed by cutting off the power supply to the entire system, the capacitive element C9 maintains the voltage VDD for a while, but eventually discharges. The voltage of capacitive element C9 is VDDS and is again supplied to linear integrated circuit U1 in the manner described above. Output signal VOK to voltage V
A digital 1 indicating that DD is too low, or a voltage V
Whether DD becomes digital 0 indicating that it is a safe value depends on this voltage VDDS.

Microprocessor U2 also receives an input signal LVOLT at its input terminal AN3.

This voltage between 0 and volts is proportional to the voltage on the control line LINE. Microprocessor U2 uses this information in three ways. (1) Used to select the contact closure profile of contactor 10 as already described in connection with FIG. The appropriate closure profile depends on the line voltage.

Signal LVOLT provides voltage information to microprocessor U2, which adjusts the firing phase or delay angle α1 . of gate control device Q1, such as a triac, in response to changes in line voltage. Change α2 etc. (2
) LVOLT (g is also used to determine whether the line voltage is high enough to close the contactor 10 (Table 1
reference). There is a lower limit of line voltage or control voltage for reliable closing operation to occur, often this lower limit is 65% of the nominal line voltage. In a preferred embodiment of the invention,
Select this to be 78VAC. (3) Finally, the microprocessor uses the LVOLT signal to determine if there is a lower voltage limit that will logically open the contacts at the appropriate time. This voltage is often 40% of the maximum voltage. When the line voltage signal LVOLT indicates that the line voltage is less than 50% of the maximum value, the microprosser U2 automatically opens the contacts to perform a fail-safe operation. In the preferred embodiment of the invention, this is chosen to be 48 VAC. Microprocessor U2 reads the LVOLT signal according to the "READ VOLTS" algorithm of FIG. 20. The LVOLT signal is utilized in the "READ VOLTS" algorithm of FIG. Decision block 162 asks, "Is this a positive voltage half cycle?" This question and its answer are similar to decision block 152 in District 19. If the answer to the question at decision block 162 is "no", the algorithm returns to its starting point. If the answer is "yes", instruction block 164 instructs the microprocessor to select the AN3 power of microprocessor U2 for analog-to-digital conversion of the signals present based on the determination of decision block 162. This information is stored in a memory location in microprocessor U2 under the instructions of instruction block 168 for use in the manner described above, and the algorithm returns to its starting point.

Again in Table 1, the next input to the microprocessor is designated C0LCUR. This is part of the closed loop coil current control system. Human CCI to linear circuit U1
is the coil 31 according to the voltage drop across the resistive element R7.
Measure the current flowing through the This information is scaled appropriately as described above and transmitted to microprocessor U2 by the Co I LCUR signal. Just as we must know the line voltage given by the LVOLT signal,
The coil current given by the COI LCUR signal must also be known.

The Co I LCUR signal is “CHOLD” shown in FIG.
First, the microprocessor is instructed to execute a captive conduction delay, as indicated in instruction block 172. Angle α7 is a constant conduction delay angle, e.g., 5 mm. The second is the sum of this captured amount.Then the microprocessor 0
Wait at a suitable time, ie, until angle α7 has passed, and fire the triac or silicon controller Q1 according to the instructions in instruction block 174. The microprocessor accomplishes this firing by issuing a "TRIG" signal from terminal B52, which connects the TRIG input of integrated circuit U1 via amplifier GA and its GATE output terminal in the manner described in connection with FIGS. 7A and 7B. terminal to operate the gate of a silicon controlled rectifier triac or similar gate controller Q1. Then instruction block 17
6, the current flowing through resistive element R7 and measured at the CCI input of semi-custom integrated circuit U1 fires COILCUR silicon controller Q1 to terminal AN2 of microprocessor U2 via amplifier OCA to CCO output. Microprocessor is terminal B5
This ignition is accomplished by issuing a TRIG" signal from the integrated circuit U1 via the amplifier GA and its GATE output terminal in the manner described in connection with FIGS. 7A and 7B.
0 to the TRIG input terminal of Semi-Custom Integrated Circuit U1 to actuate the gate of a silicon-controlled rectifier triac or similar gate control device Q1.
The current measured at the I input is provided via amplifier OCA to the CCO output as the C01LCUR signal to terminal AN2 of microprocessor U2. The microprocessor repeats this C0ILCUR signal and performs A/D conversion to find its maximum value. This maximum current is then compared in microprocessor U2 to the regulation point provided to microprocessor U2 as determined by decision block 178 to determine whether the maximum current is greater than the current determined by the regulation point. In a preferred embodiment of the invention, the regulation point peak current is set to have a DC component of 200 milliamps. This excitation level is maintained by varying angle α7 as required. If the answer to interpage at decision block 178 is "yes", the conduction delay is digitally incremented in the microprocessor up to the next highest value. This is done by incrementing the counter by at least one significant bit at a time.

As a result, the delay angle α7 in FIG. 6, for example, is larger and therefore the current pulse 124 is smaller, resulting in a smaller average half-cycle current flowing through the gate control device Q1, such as a triac.

Conversely, the answer to page spacing in decision block 178 is "
If no, the count in the microprocessor is decremented by at least one significant bit, thereby reducing the delay angle α7 and increasing the current pulse 124.Function Block 1
Regardless of the answer to the question at 78, once the increments required by instruction blocks 180 and 182 are completed, the algorithm returns to its starting point for subsequent periodic use.

By varying α7 every half cycle as needed, the coil current will be maintained at the regulated value throughout the HOLD phase regardless of changes in drive voltage or coil resistance.

Inputs LVOLT and C0ILCUR are important values that determine when the trigger signal TRIG is supplied from the output B52 of the microprocessor U2 to the trigger input TRIG of the linear circuit U1. The linear circuit U1 uses the trigger signal TRIG in the manner described above to supply the gate output signal GATE to the gate terminal of the thyristor Q1 in the manner described above.

Line current iL1. iL2. An apparatus and method for detecting and measuring i'L3 will be described with reference to FIGS. 22.23, 24.25, and 7A to 7B. As for transmission gate U101, its ax, bx and CX output terminals are collectively connected to one side of integrating capacitor C101. Microprocessor U2 controls the parameter selection in gate U101 by providing signals A, B, C to the relevant inputs of transmission gate U1 according to the digital arrangement shown in Table 2. This operation causes current transformers 62A, 62B, 62C
can be sampled sequentially in 32 half-cycle increments. Integrating capacitor C101 is charged in a manner described below. As already mentioned, current transformers 62A, 62B.

The secondary winding output voltage of 62C is determined by the line current iL1.62C flowing through the main feed lines A, B, and C, respectively. iL2. Associated with iL3 mathematical differences. This voltage is converted into a charging current by applying it to each of the resistive elements R101, R102 or R103, so the voltage of the integrating capacitor C101 V Cl0
I also changes every line cycle. The capacitor is discharged only after 32 line cycles of integration have been performed in the manner described below.

Margin table below 2 U101 logic input sensing current BA 1 1 0 i LA1 0
1 i LBo 1 1
i LCo 0 0
i Transmission gate U that operates in conjunction with the GRDZ input signal
102 changes the connection relationship of the integrating circuit and integrates the integrating capacitor C.
101 periodically activates circuit operation. This is z=
It happens when 0. The output voltage V CIQI of the integrating capacitor Cl01 is applied to a buffer amplifier U105 including a gain to form a signal MCUR, which is applied to the ANI input of the microprocessor U2. Microprocessor U2 digitizes the data provided by signal MCUR in the manner of the "RANGE" algorithm shown in FIG. Voltage signal MCUR is applied to microprocessor U2
It is provided as a car-to-analog input to an 8-bit, 5-volt A/D converter 200 built into the vehicle. A/D
Converter 200 is shown in FIG. It is desirable to use the system of the present invention in order to be able to measure line currents that vary over a wide range depending on the application. For example, depending on the stage, it may be necessary to measure line currents as high as 1.200 amperes, and there may be cases where it is desired to measure line currents of 10 amperes or less. To extend the dynamic range of the system, the microprocessor U
2 expands the 8-bit output, which is a predetermined bit of the built-in A/D converter 200, to 12 bits.

For convenience of explanation, the above-described operation will be explained in detail using an illustrated example related to the sensing current transformer 62A and the resistor R101. In addition,
Current transformer 62B and resistor R102° and current transformer 62C and resistor 103 can also be used in the same way. Furthermore, di(t) eo (t) ~□ dt holds true for all current functions. Air gap 11 in current transformer 62A
Assuming that the length 12 of 1 is constant for a particular application (or current transformer 62S of FIG. 18 is used), i
Assuming that (t) is a sine wave, i.e., I Ll sin ωt, the output voltage of the current transformer defined by equation (1) can be rewritten as shown in equation (5) below. Can be done.

K5 d (ILI sin ωt)eo (t
)=□ dt , , (5) The output voltage eo(t) is applied to the resistor R101 and the charging current i of the integrating capacitor C101 according to equation (6)
Converted to CH. This is expressed in unit amplitude (p, u, ) in a graph as shown in Figure 25B.

eO(t) K6 d (I Ll sin
ωt)ICH= −= (6)
RIOI dt The charging current iCH of the integrating capacitor C101 is proportional to the derivative of the line current iL1 rather than the line current itself. As a result, as is clear from equation (7), the voltage V C1 (11) of the capacitive element C101 present as a result of the charging current 1 CH (1) flowing during the negative half cycle can be expressed as:

Below margin 1 86 d (I Ll sin (JJ
t) dtv clot = --(7) CIOI RIOI dtV C1
01=-7 ILI sin ωt
(8) Equation (8) represents equation (7) in a simpler form. I Ll sin ωt ノ＼
-. Fig. 25A is a graph showing what is expressed in units (P, U,). The derivative of iLl sinωt after being integrated by capacitor C101, i.e. −7 1LI expressed in unit amplitude (p, u, )
FIG. 25C shows that sin ωt is incorporated. The charging current iCH of the capacitive element C101 is connected to the transmission gate U101.
comes from output terminal aX of. This current is supplied to the transmission gate U101 from the aOR input terminal, and the transmission gate U101
Similarly, the current from current transformer 62B is selected according to the corresponding signals at the 8 terminals A, B, and C of
It can be used by selecting the oR-bX terminal, and the current from the current transformer 62C can be used to select the cOR-cx terminal. The terminals ax, bx, and cx are connected to the car.
A lead is formed and a charging current is supplied to the integrating capacitor C101. The single lead is the ay of transmission gate U102.
and connect to the CX terminal. The ax end terminal of transmission gate U102 is grounded, and the aOR common terminal is connected to capacitor C10.
Connect to one side of 1. cOR terminal is capacitor C1
Connect to the other side of 01. bx of transmission gate U102
The end terminal is connected to the negative input terminal of the operational amplifier U103, and the associated bOR common terminal is connected to the output of the operational amplifier U103. Under normal conditions, the diode circuit CRIOI-CR10
3 is during the integration operation, the positive half cycle of the integration current ICH is connected to the diodes CR101, CR102 and the operational amplifier U10.
Integrating capacitor C through a bridge circuit containing the output of 3
101 and the negative half cycle is the capacitive element C1.
01 to the peak value of the corresponding half cycle. The capacitive element Cl01 is repeatedly charged to a gradually higher voltage value, and each charging voltage value corresponds to the peak value of the negative half cycle of the charging current.

It is not uncommon for a voltage as small as 0.25 millivolts to exist between the negative and positive input terminals of operational amplifier U103. Capacitive element C to form a zero net input offset voltage for amplifier U103, i.e. charging current iCH.
1O2 is periodically charged to the negative of the voltage value.

The "RANGE" algorithm performed in cooperation with the above integration circuit including the capacitive element C101 and the microprocessor U2 will be explained with reference to the examples shown in Figures H22, H23, and H25. It goes without saying that the dynamic range for detecting line current is important, but as is clear from Figure 23, the A/
The D-to-D converter 200 has an input voltage upper limit that guarantees the number of digital outputs to be detected. Input terminals up to +5 volts can be accepted to form the 8-bit signal provided to the first eight locations 204 of 202 . In this case, the 5 volt upper limit input is represented by decimal number 256, which corresponds to the digital number in all eight locations of section 204 of accumulator 202.

FIG. 25B is a typical graph showing the amplitude change over time of the current i Ll sin ωt. The graph in Figure 25A is the charging current iCH which is the derivative of the line current in Figure 25B.
shows. Also, Figure 25A shows that only the negative half cycle of the current is integrated. In FIG. 25B, appropriate amplitude standards 220, 230, and 240 are taken as three examples, and the differences between the 1-wheel amplitude, the y2-wheel amplitude, and the 2-wheel amplitude are illustrated. An amplitude of 220 A in the graph of FIG. 25A,
230A and 240A respectively correspond to the unit amplitude in the curve shown in FIG. 25B. Similarly, Example 1 and Example 2
Two songs 11230B and 220B are illustrated as follows. 246 in Figure 25C is the 5 volt maximum input terminal. The algorithm of FIG. 22 is performed for each half cycle over 32 consecutive half cycles. Each half cycle during this time interval is identified by a number stored as HCYCLE. Half-cycles 2, 4.8.16 and 32 each represent an integration interval twice as large as the previous half-cycle; it is at the end of these defined intervals that the algorithm re-evaluates the voltage VCIOI.

Assume that the input signal repeats every cycle in 32 intervals. In that case, HCYCLE=2.4.
The voltage VCIOI at the end of the interval denoted 8.16 or 32 will be twice the size at the end of the previous interval. Therefore, if the result of an A/D conversion in the previous interval is greater than or equal to 2.5 volts,
If it is 80H or more corresponding to the OI value, the VCIOI at the current interval will be 5 volts or more, and the A/D conversion result will be invalid. This is because the A/D converter cannot digitize values higher than 5 volts. Therefore, if the previous result is greater than or equal to 80H, the algorithm retains this result as the best possible A/D conversion.

Conversely, if the preceding A/D conversion is 80H or less, it may be considered that effective A/D conversion can be performed.

The current signal can be more than twice the previous value,
This is because it is still less than 5 volts. The current A/D conversion is advantageous in that the size of the converted signal is twice as large as that of the previous A/D conversion, and a resolution with a larger number of bits can be obtained.

If the result of the A/D conversion is found to be greater than or equal to 80H, the left shift operation 188 performs this function, which must be adjusted to take into account the interval in which the A/D conversion was performed. For example, the result obtained at the end of interval 4 is 80
H is the result of an input signal having twice the magnitude of the human input signal producing result 80H at the end of interval 8. Therefore, shifting the result of interval 4 to the left doubles this result by the end of interval 8. The 12 bit answer contained in accumulator 202 of FIG. 23 at the end of 32 half cycles represents at least an approximation of the value of the current flowing through the line being measured.

It is this value that the microprocessor U2 utilizes in order to control the contactor 10 in the manner already described and to be described in more detail below. At HCYCLE 33, the entire process is then reinitialized for use with current transformer 628B and then 62C. It goes without saying that this initialization is repeated periodically by the microprocessor U2 in a known manner.

Straight line 220B in FIG. 25C shows that voltage V Cl0I increases with integration of current iCH in FIG. 25A. Integration is not performed during the positive half cycle of the charging current iCH, but integration is performed to draw a negative CO3 curve every negative half cycle.

These integral values are accumulated to form voltage V 0101. Therefore, for 33 half cycles the capacitive element C10
1 increases with the value of the line current sampled over a period of time represented by 32 half cycles until it is discharged to zero.

Next, the embodiment of the accumulator according to Example 1 will be explained along with FIGS. 22, 24, 25 and 26. In order to charge the example C101 and generate the capacitor voltage VCIOI in the capacitor 1, a charging current 1cH230a having an amplitude in % is used. The 5th C is a summary of this voltage profile.
This is 230b in the figure. This voltage is sampled by the "RANGE" algorithm according to function block 184 of FIG. In “2”, “4”, 8”, “16” and “32” HCYCLE benchmarks, “RA”
NGE” algorithm is function block 186 of the East 22 map.
It is determined whether the preceding A/D conversion result is in class 80 or higher, as described in . The class to 80 is equal to the digital number 128. The answer to this question is “
If not, the analog voltage VCIOI present at input ANI of A/D converter 200 is digitized and stored as shown in functional block 192 of FIG. 22 and graphically in FIG. HCYCLE is 1
is incremented and the routine restarts. As long as the prior A/D conversion result is below the 80 class, there is no need to utilize the "left shift" technique of the present invention; therefore, Example 1 of FIG. 26 is a sampling method that does not require the use of the LI soft shift technique.・Show the routine. That is, in Example 1 of FIG. 26, when HCYCLE=2, the A/D converter 20
0.2 volts are obtained at the input terminal ANI of 0, which is 1
It is digitized into a binary number corresponding to the decimal number 10. This binary number has digital ones in the "2" and "8" positions of memory portion 204 and digital zeros in all other bit positions. “H'CYOLE, 4” digitizes the analog voltage 0.4 volts to a decimal 20 with digital 1s in the “16” and “4” bit positions of memory portion 204 and digital 0s in all other positions. form. “HC
Digitize 0.8 volts in YCLE8”,
A binary number corresponding to decimal number 40 is formed with digital 1's in locations "32" and "8" of memory portion 204.

In "HCYCLEI6" 1.6 volts is digitized to form a digital number representing 81 decimal numbers.

This digital number is “64” and “8” in the memory portion 204.
” has a digital 1 in the “HCY” position.
At CLE=32'', 3.2 volts is digitized to form a digital number equivalent to 163 decimal.

The digital number is 128” in the accumulator 204, 3
2”, “2” and “1” bit positions, at this point the “RANGE” algorithm for Example 1 is complete. As already mentioned, “R
The ANGE" algorithm does not proceed to function block 188 that requires a left shift. However, as discussed below in connection with Examples 2 and 3, a left shift may have to be utilized.

Next, with reference to Figures 22.24.25 and 27, Example 2 will be described in which a charging current of 1 cH220a with an amplitude of 1 degree is used to generate the voltage VCIOI in the capacitive element C1019. 220b in FIG. 25C depicts the generated voltage in comparison with HCYOLE. Again, the second
The RANGE" algorithm in Figure 2 is utilized. As in Example 1, 2", "4", "8", 16" and "3"
2” Memory location 202 in the HCYOLE sample
RANGE" algorithm is utilized so that the "2" Portion 204 has digital 1s in bit positions “16” and “4” and digital 0s in all other bit positions. Digitize 0°8 volts at HCYCLE=4 to give the digital number responsible for decimal number 40. This digital number has a digital 1 at the 32'' and 8'' bit positions of portion 204 of accumulator 202. At HCYOLE=8, 1.6 volts is digitized to form a digital number in portion 204 of accumulator 202 corresponding to 81 decimal digits. This digital number has digital or logical 1's in bit positions "64", "16" and "1". At HCYCLE=16, 3.2 volts is digitized and a digital number corresponding to decimal number 163 is stored in part 20 of accumulator 202.
Form into 4. This digital number has bit position “128”
, 32", "2" and "1" have digital 1s.H
At CLYCLE=32, the "RANGE" algorithm utilizes function block 186 to determine that a digital number greater than 80 px was formed as a result of the previous A/D conversion. Therefore, function block 188 is utilized for the first time to perform a "left shift". As a result, even though there is 6.4 volts as the voltage to be digitized in the human power of the A/D converter 200, the output of the A/D converter cannot be trusted if the analog number at the input is this large. For this reason, digitization is not performed, and the accumulator 200 during digitization of the preceding 3.2 volt analog signal.
By simply shifting the digital number stored in the portion 204 one digit to the left for each bit of the digital number, the decimal number 3
Form a new digital number corresponding to 26. This new digital number is stored in accumulator 2 as shown in Figure 27.
A part of the spill over part 206 of 02 is used. The new digital number is
256'', ``64'', ``4'' and ``2'' bit positions have digital 1's.The digital number at the 32''HCYOLE position in Figure 27 is the same as the digital number shown at HCYCLE location ``16'', but with 1 bit. Only the position has shifted to the left. This example shows the bad side of left shift technology.

Accumulator 20 at the end of the 32nd HCYCLE
The numbers stored in 2 are the line currents 22, 24, 25 and 28 measured in the overload of the contactor 1o and in the Pi brown system 1.
A third example of the left shift technique will be explained along the diagram. In Example 3, in order to obtain the voltage VC101, a charging current icH with an amplitude of about 21L is applied to the capacitor C101 as shown at 240a in FIG. 25B.
Integrate by. This voltage is % in relation to examples 1 and 2.
It exhibits an output profile similar to that shown in Figure 25C, but with a slope as outlined in Figure 25C as Example 3.

To avoid confusion, ignore the step relationships between electricians. However, in much the same way as in Examples 1 and 2, Example 3
However, in case 3 of 6 where there is a step voltage, “RA
NGE” algorithm is HCYCLE=”2”,’4”
and "8" and update portion 204 of accumulator 202 by performing appropriate A/D conversions. However, in HCYCLE samples “16” and 32, the portion of accumulator 202 is updated not by A/D conversion, but by two successive sequential left shifts of the prior information stored in location 204.

It is clear that A/D conversion does not provide reliable results for sampling at "16" and "32". Specifically, in HCYCLE=“2”,
Digitize 0.8 volts to form a digital number equivalent to 40 decimal. This digital number has a digital number one in the "32" and "8" bit positions of the portion 204 of the accumulator 202. In the “4” HCYCLE sample, 1.6 volts is digitized to decimal 8
Forms a digital number equivalent to 1. This digital number is "64" and "16" in the portion 204 of the accumulator 202.
” and has a digital number 1 in the “1” bit position.HC
At YCLE=8, 3.2 volts is digitized to form a digital number equivalent to 163 decimal. This digital number is stored in portion 204 of accumulator 202.
128", "32", "2" and "1" bit positions have digital 1s. At HCYCLE=16, "R
ANGE” algorithm has a leading A/D conversion result of 80 (corresponding to a digital number of 163), which is larger than the class.
Therefore, the accumulator 202 is the A/D converter 20
It is updated not by A/D converting the voltage at the 0 input, but by shifting the digital information already stored in accumulator 202 by one bit to the left as a result of the HCYOLE="8" sample completion. Recognize that. As a result, "16" HCYCLE samples form a digital number equivalent to 326 decimal numbers. This is accomplished by shifting the information already stored in the accumulator to the left by one bit. As a result, the above digital number is stored in the accumulator 20.
A portion of the spillover of 2 overflows to the 1-bit position of 206.

This new digital number is “25” in accumulator 202.
6”, “64”, “4” and “2” bit positions. At the HCYCLE=“3” sample, by left-shifting the number already stored in accumulator 202 once again in accumulator 202. , occupying two locations in spillover portion 206 and all eight locations in portion 204.

This new digital number corresponds to the decimal number 652.

It has a digital 1 at the 512" position, the 128" position, the 8" bit position, and the 4" bit position.Using this number, the line current measured through the overload relay board 60 is expressed. In addition, the values stored in accumulator 202 are utilized in the manner described above to cause functions to be performed by contactor or controller 10.

Referring again to Figures M7A-7D, the apparatus and methods associated with switch 5W101 and 8-bit static shift register U104 will now be described. Inputs HO through H4 of switch 5W101 represent a switch configuration that programs digital numbers that can be read by microprocessor U2 to make decisions and perform calculations regarding the ultimate value of the full load current sensed by the system. These switch values and the switch values associated with AM", co", C1" are sequentially processed by the microprocessor U2 as part of the signal appearing on line SW in response to the input information provided by the A, B, C human input signals. By utilizing the heater switch configuration, the four heater switches HO through H are programmed in a binary manner.
3 allows you to select 16 ultimate trip values. These switches replace known mechanical heaters to adjust the overload range of the motor. There are also two inputs CO and C1 used to power the motor class.
Also provided. A class 10 motor can withstand a rotor lock condition for 10 seconds without loss, a class 20 motor can withstand a rotor lock condition for 20 seconds, and a class 30 motor can withstand a rotor lock condition for 30 seconds. The current in the rotor locked condition is assumed to be six times the normal current.

Referring again to Figures 7A and 7B, and Figures 11 and 29,
An apparatus and method for discriminating true input signals from false input signals appearing at the "RUN", "5TART" and "RESET" inputs is described. FIG. 11 shows the distributed parasitic capacitance CLL between the power lines connecting the "E" and "P" terminals in the terminal block J1 of the relay board 28. This capacitance is believed to be caused by the presence of extremely long input lines between the pushbuttons "5TOP", "5TART" and "RESET" and the terminal block J1. Similar capacitances may exist between the other lines shown in FIG. Parasitic capacitance has the undesirable effect of coupling signals between the input lines, resulting in pushbuttons "5TOP", "5TART" and "RES"
The microprocessor U2 is used as a true signal to indicate as if the "ET" is in the closed state when it is actually open.
A false signal that is misidentified occurs. Therefore, the purpose of the device described below is to distinguish between true and false signals appearing on the input line. A capacitive current i CL L flowing through the distributed parasitic capacitance CLL precedes the voltage in said capacitance, i.e. between terminals "E" and P.
FIG. 9(a) shows a truncated VLINE received by microprocessor U2. In FIG. 29(C), the pseudo current 1CLL is connected to the resistive element R3, the capacitive element c4, and the circuit U.
1 shows the voltage appearing at, for example, terminal B41 of microprocessor U2 as a result of flowing through the internal impedance at the RUN input terminal of microprocessor U2. This voltage VR which is a false indication of voltage
UN (F) is the voltage Vl.

Leads INE by the value γ. If capacitive element cX, C4
are different from each other, specifically, if the capacitive element CX is larger than the capacitive element C4, the true VRUN signal VRUN
(T), that is, the signal generated by closing the 5TOP switch as shown in FIG. 11 is approximately in phase with the voltage VLINE.

The only difference between the two is due to the difference in capacitance between the capacitive elements cX and C4. If the capacitive element CX is smaller than the capacitive element c4, this difference will cause the true voltage VRU to
N (T) is VL by the amount Δ as shown in FIG. 29(b).
It lags behind INE. Therefore, the microprocessor U2 detects that the voltage VLINE changes state, i.e., FIG.
), the voltage VLINE must be compared with the voltage at input terminal B41 within a short time of Δ or less after passing through the changing points "JP" and "DOWN" of terminal B4.
If the digital value of the voltage appearing at VLINE 1 is a digital signal of opposite polarity to the digital value associated with the voltage VLINE at this point in time, this signal is a true signal as shown in FIG. 29(b). If the polarities are the same, it is a false signal as shown in FIG. 29(C). That is, for example, the voltage VLIN
E after time “UP” (measured within time Δ, terminal B4
1, and if the voltage at terminal B41 is digital O, then the voltage signal at terminal B41 is a true signal. However, if the voltage signal is a digital 1, the voltage signal appearing at terminal B41 is a false signal. By appropriately setting the values of the capacitive elements CX and C4, it is possible to change the amount by which the true signal precedes the line voltage, that is, the amount of delay Δ. Δ
Since the value of is smaller than the value γ, it is also impossible that the sign of the spurious signal differs from the sign of the reference voltage during the sampling or comparison interval.

FIG. 30 shows an alternative embodiment of the printed circuit card also shown in FIGS. 8.9 and 10. In the embodiment of FIG. 30,
Elements that are the same as those of the apparatus shown in Figures 8.9 and 10 are given the same reference symbols with a dash (°). In the apparatus of Figures 8.9 and 10, connect solder connector J2 to Jl.
A flat connector 64 is used to connect the OL and J102, but in the embodiment shown in FIG.
Instead, an electrically insulating base 300 is provided, on which a male plug connector 303 is placed. Connector 303 is shown 60 degrees above the overload relay board. A female connector 302 corresponding to the male connector 300 of the relay board 60° is provided above the printed circuit board 28°. Female connector 302 has a recess or hole 304 that is complementary to male plug 303 of connector 300. As will be described later in connection with FIGS. 31 and 32, the bobbin 32 is soldered to the bobbin 32 through the pin 318 inserted into a suitable hole formed in the circuit board 28' to more securely support the circuit board 28. ” is connected to the circuit board 28°. As in the case of the embodiment shown in Figures 8.9 and 10, after assembly, the entire circuit board is folded at 100° and the third
Connector 302 corresponds to connector 303 in the manner shown in and described in connection with Figures 1 and 32. There is also a separate internal communication circuit (IUCOM) that allows communication between the contactor and the remote control communication element.
Separately install a terminal block JX to connect to.

31 and 32 show an embodiment of the invention similar to that shown in FIGS. 1 and 2. In this embodiment, elements identical or similar to elements of the apparatus shown in FIGS. 1 and 2 are given the same reference numerals with a dash (''). The apparatus of FIGS. 1 and 2 comprises: For the cooperation, function and operation of the elements of Figures 31 and 32 which are identical or similar to the elements shown in Figures 31 and 32, reference is made to the descriptions associated with Figures 1 and 2.Relay board 6Q' and printed circuit board 28' shows the assembled state in which the plug 303 is connected to the female connector 302 in the manner described above. That is, by inserting the male connector 303 into the female connector 302 and making electrical contact therewith, 1. !The elements of the switchboard 60' are connected to the elements of the flint circuit board 28°.Also, the switchboards 60', shown for example in numbers 31 and 32, are connected to the elements of the flint circuit board 28°. In the embodiment shown in FIGS. 31 and 32, the contactors include terminal straps 20', 24°, and terminal lugs 14'.

16°, and includes a one-piece thermoplastic insulating base 12' holding fixed contacts 22', 26'. Appropriate screw 40
0 to secure the fixed contact and terminal strap to the base. Base 12° also serves as a positioning/guiding system for movable contacts 46', 48°, crossbar 44°, spacer or carrier 42', and armature 40°, which will be described in more detail below. The overload 11 electrical board 60' and the coil control board 28' are uniquely supported within the base 12'. Specifically, (as is particularly clear from FIG.
29, which is pressed against a corresponding lip 330 on the base 12' under the action of a retaining spring or member 316. This retaining spring is a slug or permanent magnet 36
is coupled to the base 12''. The slug or permanent magnet 36° has a second lip 314 (as is particularly apparent in FIG. The bobbin 317 is provided with a retaining pin 318, which is fixed to the coil control panel 28' by soldering or the like, and the coil control panel 28', which includes a visible electrical insulating material, is attached to the center of the bobbin 317. Fixed support.

The 28° corner of the coil control board is supported directly on the base 12', for example at 320. Overload relay board 60' is supported vertically above coil control board 28' by the interaction of bins and connectors 300, 302, 303 and 304. The coil assembly 30' has the other end connected to the kickout spring 3.
4° and thus the bobbin 317 is supported by the spring 3
The lip 31 of the magnet 36 due to the compressive force of 4
4 and the base 12°. 32, the top of the spring 34' is anchored to the bottom lip 340 of the carrier or spacer 42°, the movable contact 46", the 48° spacer 42' and the armature 4.
During the movement of the movable system, including zero movement, it moves together with the carrier or spacer.

FIG. 32 shows magnetic members 36° and 4 which are approximately E-shaped.
The configuration and interactions of 0' are illustrated. The movable armature 40' has a central leg 322 and two outer legs 330, 33.
Contains 1. In order to obtain the function of tightening the magnet at 40°, the legs 330 and 331 may have cross-sectional areas that are slightly different from each other. This is because, during repeated use, the front surface of the magnetic disk outer legs 330, 331 repeatedly collides with the front surface of the magnetic slug or permanent magnet 36', which is in a complementary relationship with the magnetic slug, thereby forming a wear pattern. Therefore,
Magnetic member 40゛ for maintenance purposes etc.

If the 36' is removed periodically, it is desirable to reassemble it in its exact original orientation so that the existing wear pattern remains intact. It is undesirable to assemble both members 40° and 36° in orientations opposite to their original orientations because new wear patterns will occur. If the sum of the cross-sectional areas of the legs 3-30 and 331 is set to be approximately equal to the cross-sectional area of the legs 332, effective conduction of magnetic flux can be achieved. In a preferred embodiment of the invention, a large portion of the face of the central leg 332 is cut to form a projection or nipple 326 and two effective air gap areas 327, 328. When the armature 40' comes into contact with the slug or permanent magnet 36°, the complementary outer plate legs 331, 330 come into surface contact, and the front part of the nip, hole or protrusion 326 of the central leg 322 is in the area 327, 328 of both magnets. The surfaces are brought into contact with each other leaving a wide air gap. The presence of the air gap acts to reduce the residual magnetism of the magnetic circuit formed by the abutting armature 40" and permanent magnet 36". This means that during the contact opening action the kickout spring 34° It is known that magnetic noise can be introduced in magnetic structures subjected to alternating or periodic HOLD pulses, which are desirable to separate the magnetic members and open the contacts.Nipple 326 must be present. Ba, HO
Under the action of the LD pulse, the central leg 322 of the movable armature 40' vibrates in the same way that the magnetic core of a radio speaker vibrates in the presence of a drive signal. Furthermore, under the action of the periodic HOLD pulse, the rear protrusion 333 of the armature 40° is distorted towards the center, and the movable armature 40° leg 330° 331 displaces the front surface of the complementary leg 330, 331 of the permanent magnet 36°. Move as if rubbing. As a result, undesirable surface wear increases. A nipple or protrusion 326 is formed to prevent the distortion and wear and to ensure an air gap. This prevents the leg 322 from shifting under the action of the HOLD pulse, yet reduces the residual magnetism to a level that does not interfere with the operation of the kickout spring 34°. The operation of the current transformer 62S shown in FIG. 18 will be explained. This description applies to electrical devices such as contactors, meters, relay systems, etc.
By using 2S, the voltage output ■ proportional to the time derivative of the current i flowing through the primary winding can be expressed as
This is extremely useful in understanding the manner in which this occurs in the next winding. By utilizing this, it is possible to measure or detect a wide range of current i, and the error in the output voltage V for a wide range of current i is extremely small. For example, from 0.1 amp to 20
Output voltage V for current range varying up to 00 amps
is a relatively faithful representation of the magnitude of the derivative of current i with an error of no more than 1%. (R, M, Bozort
“Ferro-magnetism” p. 489
No. 11-1111q, as shown in No. 34
If iron powder is used for the magnetic core 120 shown in the figure, the magnetic permeability μ depending on the magnetic field strength H remains approximately constant over a relatively wide known magnetic field strength range in a region called the Rayleigh region or Rayleigh range. Take the value μ0. The Rayleigh constant count equal to the slope (λ) of the magnetization curve is approximately equal to zero over the Rayleigh range of iron powder; examples of slope values for ferromagnetic materials other than iron powder are AA, BB, CC; Here the gradient λ is not equal to zero, and Equation (9) describes the relationship between the magnetic field strength H in the Rayleigh constant count, the Rayleigh constant count, and the magnetic field strength H, depending on the initial permeability μ0, regardless of the type of ferromagnetic material. show.

μ=μ0+Input Hm-...(9) NI H=□...(10) Equation (
10) shows the relationship between the magnetic field strength H and the current i.

μNli ΦA=β=μH=□ (11)λ Equation (11) shows the relationship among magnetic flux (φ), magnetic flux density (β), and magnetic field strength H).

dφ V = N 2− −・・・・・・・・・・(12
) dt Equation (12) shows the relationship between the output voltage according to the magnetic flux appearing in the secondary winding of the current/voltage transducer 62S and the number of turns N2 of the secondary winding.

NlN2A dμ1 V==□ □ ・・・・・・・・・(13) u
dt Equation (13) i Express equation (12) in a form in which its constant values are bundled.

Below Margin NlN2A d(μ0+Input H)i ■Fully dt... (14) Equation (14) shows the form obtained by substituting equation (9) into equation (13).

NlN2A di If λ=0, then V; □μO□・−(15)u
dt Equation (15) shows equation (14) for the special case where μO is constant.

If di λ=0, ■;□ (16) dt Equation (16) is a simplified form of equation (15) and is within the excitation or non-saturation region of the magnetic core, for example magnetic core 120.

[Brief explanation of drawings]

Figure 1 is a perspective view of the electromagnetic contactor; Figure 2 is Figure 1 II-
A vertical cross-section of the contactor in line II; Figure 3 is a graph showing the force and armature velocity curves of a known contactor with electromagnetic armature velocity curve, kickout spring and contact spring; Figure 4 shows the curves of Figure 3 and Figure 6 is a graph showing a family of curves similar to the curves of Figures 3 and 4, but for another embodiment of the invention; The figure is a graph showing a group of curves corresponding to the electrical and current waveforms, respectively, in the device embodiment corresponding to FIGS. 4 and 5; FIGS. 7A to 7D are graphs showing the electrical control in the contactor shown in FIGS. 1 and 2. A circuit diagram partially showing the system as a block diagram; FIG. 8 is a plan view of a printed circuit board including the circuit elements of FIG. 7 and the contactor coil, current transformer, and transformer of FIG. 2; FIG. 8 is an elevation view of the circuit board shown in FIG. 8; FIG. 10 is a perspective view showing the circuit board of FIGS. 8 and 9 attached to the contactor of FIG. 2; FIG. 11 is a perspective view of the circuit board shown in FIG.
The figure is a partial block diagram of the circuit/wiring diagram showing how the contactors of Figures 2 and 7 are used in conjunction with the motor controlled by them; Figure 12 is the current/voltage used in the embodiment of the present invention; Transducer block diagram: Figure 13 is a block diagram schematically illustrating the transducer of Figure 12 together with the integrator circuit; Figure 14 shows the air gap length and voltage/current ratio of the transducer of Figures 12 and 13. Figure 15 is a block diagram showing an embodiment of a current-voltage transducer using magnetic shims; Figure 16 is an embodiment of a current-voltage transducer using adjustable protruding members. Fig. 17 is a block diagram showing an embodiment of a current-voltage transducer using a flexible wJ magnetic core: 1st
Fig. 8 is a block diagram showing an embodiment of a current-voltage transducer using a powder metal magnetic core; Fig. 19 is a microcomputer for reading the input circuit switch and discharging the capacitor in the 8 m coil system shown in Fig. 7. A block diagram showing the algorithm "READSWITCHES" used by the processor; Figure 20 is an algorithm for reading the line voltage in the coil control panel shown in Figure 7.
Block diagram showing “READVOLTS”;
Figure 21 is a block diagram showing the algorithm "CHOLD" for reading the coil current in the coil control panel shown in Figure 7; Figure 22 is the line current determined by the overload relay board shown in Figure 7. Plotter diagram showing the algorithm “RANGE” for reading;
FIG. 23 is a simplified diagram showing the A/D converter and memory location that cooperate with line current reading by the microprocessor in the coil control panel of the present invention; FIG. 24 is a simplified diagram showing the coil control triac in the coil control panel shown in FIG. Algorithm “F” used by the microprocessor to start
Block tire gram showing “IRE TRIAC”;
FIG. 25A is a graph showing the derivative of the line current shown in FIG. 25B; FIG. 25B is a graph showing the line current of a device controlled by the present invention in vertical, one and two vertical amplitude sinusoids:
Figure 25C is a graph showing the relationship between A/D converter input terminals and half-cycle sampling interval (time) corresponding to the three line current amplitudes shown in Figure 25A; Figure 26 is in % line cycle; RANG in Figure 22
The six samplings performed according to the E-sampling routine result in the two samples corresponding to the first example of A/D conversion being stored in the microprocessor memory location shown in FIG.
Arrangement diagram of base numbers; FIG. 27 shows the A/D stored in the microprocessor memory location shown in FIG. 23 by six samplings performed according to the RANGE sampling routine of FIG. 22 in one position line cycle. Conversion 2nd
Binary sequence diagram corresponding to the example: Figure 28 shows the 23rd line cycle with six samplings performed according to the RANGE sampling routine of Figure 22 in a two-position line cycle.
An array diagram of binary numbers corresponding to the third example of A/D conversion stored in the memory location of the microprocessor shown in the figure: Figure 29 shows VLINE and VR in the microprocessor's manual power.
FIG. 30 is a plan view of a printed circuit board similar to that shown in FIGS. 8 and 9 used in another embodiment of the invention: M311
1Z is a vertical section blade of a contactor similar to that shown in FIGS. 1 and 2 in another embodiment of the invention; FIG.
33 is a perspective view, partially in section, of a compressed powder iron current-voltage transducer having a magnetic core as shown in FIG. 18. FIG. 34 is a graph showing the relationship between magnetic field strength and magnetic permeability of various magnetic materials.

Claims (1)

[Scope of Claims] 1. A first contact; a second contact driven to a position in electrical contact with the first contact; mechanically coupled to the second contact, and a current flows through the winding. an electromagnet having a movable armature for driving said second contact into electrical contact with said first contact in response to said flow; a mechanical resistance device disposed to resist movement of said movable armature; and wherein the amount of kinetic energy K applied to the movable armature is sufficient to overcome the resistance of the mechanical resistance device and bring the first contact and the second contact into contact. a control element is provided for supplying a current to the winding of the electromagnet, and during movement of the movable armature, the total amount of kinetic energy supplied to the movable armature is a result of the current flowing through the winding. 1. An electromagnetic contactor characterized in that the electromagnetic contactor generates an electric current approximately equal to K. 2. The contactor according to claim 1, wherein the mechanical resistance device is a spring that is compressed while resisting movement of the armature. 3. said spring responds to a command to move said second contact to said first contact point;
The contactor according to claim 2, characterized in that the contactor is a kick-out spring that separates from the contact and opens the electric circuit. 4. The contactor according to claim 2, wherein the spring is a contact spring that acts to press the first and second contacts in the electrical contact state. 5. said spring in response to a command to move said second contact to said first contact;
5. The contactor according to claim 4, wherein the contactor is a kick-out spring that separates from the contact and opens the electric circuit. 6. A fixed armature cooperates with said movable armature to initially define an air gap therebetween, and said control element for supplying said electric current causes said movable armature to first define an air gap therebetween before bringing said movable armature into contact with said fixed armature. said movable armature then continues to move toward said fixed armature at said first velocity in response to said kinetic energy applied thereto, and abuts said fixed armature at substantially zero velocity; A contactor according to claim 1. 7. After the electrical energy K is supplied, the movement of the movable armature to the contact position with the fixed armature is directly connected by the kinetic energy corresponding to the speed V1 imparted to the movable armature by the electrical energy; Contactor according to claim 1, characterized in that the movable armature then abuts the fixed armature at approximately zero speed V2. 8. The contactor of claim 7, wherein the mechanical resistance device is a combination of a contactor kickout spring and a contactor contact spring.