JPS63217703A - Frequency converter - Google Patents
Frequency converterInfo
- Publication number
- JPS63217703A JPS63217703A JP4890987A JP4890987A JPS63217703A JP S63217703 A JPS63217703 A JP S63217703A JP 4890987 A JP4890987 A JP 4890987A JP 4890987 A JP4890987 A JP 4890987A JP S63217703 A JPS63217703 A JP S63217703A
- Authority
- JP
- Japan
- Prior art keywords
- frequency
- input signal
- local oscillation
- diode
- line
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
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- 230000010355 oscillation Effects 0.000 claims abstract description 31
- 230000005540 biological transmission Effects 0.000 claims abstract description 4
- 230000008878 coupling Effects 0.000 abstract description 7
- 238000010168 coupling process Methods 0.000 abstract description 7
- 238000005859 coupling reaction Methods 0.000 abstract description 7
- 238000006243 chemical reaction Methods 0.000 abstract description 6
- 230000005672 electromagnetic field Effects 0.000 abstract description 2
- 239000000758 substrate Substances 0.000 description 4
- 230000006866 deterioration Effects 0.000 description 2
- 238000012545 processing Methods 0.000 description 2
- PNEYBMLMFCGWSK-UHFFFAOYSA-N aluminium oxide Inorganic materials [O-2].[O-2].[O-2].[Al+3].[Al+3] PNEYBMLMFCGWSK-UHFFFAOYSA-N 0.000 description 1
- 239000003795 chemical substances by application Substances 0.000 description 1
- 230000001010 compromised effect Effects 0.000 description 1
- 239000004020 conductor Substances 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000002474 experimental method Methods 0.000 description 1
- 238000003780 insertion Methods 0.000 description 1
- 230000037431 insertion Effects 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 230000001629 suppression Effects 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
（産業上の利用分野）
本発明は周波数変換器に係り、特にストリップ線路、マ
イクロストリップ線路などの平面回路を用いたマイクロ
波帯からミリ波帯の周波数領域で用いられる周波数変換
器に関するものである。[Detailed Description of the Invention] (Industrial Application Field) The present invention relates to a frequency converter, and is particularly used in the frequency range from the microwave band to the millimeter wave band using a planar circuit such as a strip line or a microstrip line. It relates to frequency converters.
（従来の技術）
従来の平面回路を用いた周波数変換器の構成を第５図に
示す。この変換器は誘電体基板上分布定数線路を用いた
入力信号周波数帯域通過濾波器３４、局部発振周波数帯
域通過濾波器３５、中間周波数帯域通過濾波器３７およ
びミキサーダイオード３６から構成されている。ダイオ
ード３６は濾波器３４および３５の間にあり、入力信号
および局部発振に対してダイオード３６のインピーダン
スと整合のとれる位置に配置されている。(Prior Art) FIG. 5 shows the configuration of a frequency converter using a conventional planar circuit. This converter is composed of an input signal frequency bandpass filter 34 using a distributed constant line on a dielectric substrate, a local oscillation frequency bandpass filter 35, an intermediate frequency bandpass filter 37, and a mixer diode 36. Diode 36 is located between filters 34 and 35, and is positioned to match the impedance of diode 36 with respect to the input signal and local oscillation.
一般的に入力信号の整合は局部発振側の濾波器３５とダ
イオード３６との間にある線路の長さＬｌを調整して行
ない、局部発振の整合は入力信号側の濾波器３４とダイ
オード３６との間にある線路の長さＬ２を調整して行な
う。この結果長さり、、Ｌ２は一意的に決定される。一
方ミキサ回路において雑音指数を最小にするためには、
イメージ周波数（イメージ周波数をｆｌ、局部発振周波
数をｆｐ、入力信号周波数をｆ５とするとｆ。＝２ｆ、
−ｆｓ）に対するインピーダンス処理が必要となる。長
さＬ、とＬ２でダイオードの両端から見たイメージ周波
数ｆ。に対するインピーダンス（以下イメージインピー
ダンスと称す）は決定されるが、上述のように入力信号
および局部発振の整合条件から長さり、、Ｌ、が決定さ
れているため、イメージインピーダンスは必ずしも適切
な値に選択ちれているとは限らず雑音指数の劣化となる
。In general, input signal matching is performed by adjusting the length Ll of the line between the filter 35 and diode 36 on the local oscillation side; This is done by adjusting the length L2 of the line between them. As a result, the length L2 is uniquely determined. On the other hand, in order to minimize the noise figure in the mixer circuit,
Image frequency (if the image frequency is fl, the local oscillation frequency is fp, and the input signal frequency is f5, then f. = 2f,
-fs) is required. The image frequency f seen from both ends of the diode with length L, and L2. The impedance (hereinafter referred to as image impedance) is determined, but as mentioned above, the length, L, is determined from the matching conditions of the input signal and local oscillation, so the image impedance is not necessarily selected at an appropriate value. This does not necessarily mean that the noise figure is degraded, but rather that the noise figure is degraded.
逆にイメージインピーダンスが適切な値となるように長
さり、とＬ２とを調整すると、入力信号および局部発振
に対する整合条件が損なわれて、これがまた雑音指数の
劣化を伴なう。Conversely, if the length and L2 are adjusted so that the image impedance is at an appropriate value, the matching conditions for the input signal and local oscillation are compromised, which is also accompanied by a deterioration of the noise figure.
（発明が解決しようとする問題点）
以上述べてきたように従来構成の周波数変換器では、周
波数変換器の雑音指数を低減するためのイメージインピ
ーダンスの処理と、入力信号および局部発振のインピー
ダンスの整合を同時に行なうことができず、また整合が
とれたとしてもかなり手間のかかる欠点を有していた。(Problems to be Solved by the Invention) As described above, in the conventional frequency converter, image impedance processing is required to reduce the noise figure of the frequency converter, and impedance matching of the input signal and local oscillation is required. It is not possible to do both at the same time, and even if matching is achieved, it has the drawback of requiring considerable effort.
従って本発明の目的は、マイクロ波帯からミリ波帯の平
面回路の周波数変換器において、比較的簡単な構成で上
述の欠点を除去し得る変換器を提供せんとするものであ
る。Therefore, an object of the present invention is to provide a planar circuit frequency converter from a microwave band to a millimeter wave band, which can eliminate the above-mentioned drawbacks with a relatively simple configuration.
（問題点を解決するための手段）
この目的を達成するため本発明周波数変換器は、平面回
路を用いた周波数変換器において、周波数変調用ダイオ
ードを接続した伝送線路に近接して、誘電体共振器によ
る入力信号周波数帯域通過濾波器と、誘電体共振器によ
る局部発振周波数帯域通過濾波器とを配置し、２つの前
記濾波器を介してそれぞれ入力される前記入力信号およ
び前記局部発振を前記伝送線路に電磁界結合して前記ダ
イオードに印加し、両周波数差信号を前記ダイオードか
ら取出すようにしたことを特徴とするものである。(Means for solving the problem) In order to achieve this object, the frequency converter of the present invention uses a planar circuit, in which a dielectric resonance An input signal frequency band-pass filter using a device and a local oscillation frequency band-pass filter using a dielectric resonator are arranged, and the input signal and the local oscillation inputted through the two filters are transmitted. The present invention is characterized in that an electromagnetic field is coupled to the line and applied to the diode, and both frequency difference signals are extracted from the diode.
（実施例）
以下添付図面を参照し実施例により本発明の詳細な説明
する。(Examples) The present invention will be described in detail below by way of examples with reference to the accompanying drawings.
第１図に本発明周波数変換器構成の一実施例を示す。第
１図でこの変換器は、誘電体基板１上に入力信号用入力
マイクロストリップ線路２、局部発振用入力マイクロス
トリップ線路３を構成し、これらの間に１個から複数個
の誘電体共振器１１゜１２、１３による入力信号周波数
帯域通過濾波器４および局部発振周波数帯域通過濾波器
５を配置している。またこれら濾波器４および５の間に
は結合用マイクロストリップ線路６を配置している。こ
の結合用マイクロストリップ線路６の一端にはミキサダ
イオード７の一端を接続し、このダイオード７の他端に
接続した中間周波数帯域通過濾波器１４を介して中間周
波数出力端子８から中間周波数成分をとり出すようにす
る。FIG. 1 shows an embodiment of the structure of a frequency converter according to the present invention. In FIG. 1, this converter comprises an input microstrip line 2 for input signals and an input microstrip line 3 for local oscillation on a dielectric substrate 1, and one to a plurality of dielectric resonators are arranged between them. An input signal frequency band-pass filter 4 and a local oscillation frequency band-pass filter 5 are arranged. Further, a coupling microstrip line 6 is arranged between these filters 4 and 5. One end of a mixer diode 7 is connected to one end of this coupling microstrip line 6, and an intermediate frequency component is extracted from an intermediate frequency output terminal 8 via an intermediate frequency band pass filter 14 connected to the other end of this diode 7. Let's put it out.
以下本実施例周波数変換器の動作を詳細に説明する。The operation of the frequency converter of this embodiment will be explained in detail below.
まず、マイクロストリップ線路６の長さは所要のイメー
ジインピーダンスとなるように選択される。例えばイメ
ージ周波数に対してλ／４（λはイメージ周波数の波長
）長の先端開放線路の場合インピーダンスは零となる。First, the length of the microstrip line 6 is selected so as to provide a required image impedance. For example, in the case of an open-ended line with a length of λ/4 relative to the image frequency (λ is the wavelength of the image frequency), the impedance is zero.
この線路の左右には入力信号および局部発振に共振した
誘電体共振器１２、１３が置かれているが、共振器のＱ
が高くイメージ周波数に対して完全離調状態であるため
双方の共振器の影響を受けることなく、線路の長さだけ
でイメージインピーダンスが決定される。Dielectric resonators 12 and 13 that resonate with the input signal and local oscillation are placed on the left and right sides of this line, but the Q of the resonators is
Since the impedance is high and completely detuned with respect to the image frequency, the image impedance is determined only by the length of the line without being affected by both resonators.
次に入力信号とダイオードの整合は、入力信号周波数帯
域通過濾波器４に用いられる誘電体共振器１２と線路６
との結合位置を調整することで行なう。この場合線路６
の反対側にある局部発振周波数帯域通過濾波器５に用い
る誘電体共振器１３とは共振周波数が異なるため、これ
の影響を受けることなく独立して信号の整合が可能とな
る。Next, matching between the input signal and the diode is performed using the dielectric resonator 12 and the line 6 used in the input signal frequency bandpass filter 4.
This is done by adjusting the bonding position. In this case track 6
Since the resonant frequency is different from that of the dielectric resonator 13 used in the local oscillation frequency band pass filter 5 on the opposite side, signal matching can be performed independently without being affected by this.
また局部発振の整合についても同じ理由で共振器１３と
線路６の結合位置を調整するのみで、共振器１２の位置
に影響されることなく独立して行なうことができる。Also, for the same reason, local oscillation matching can be performed independently without being affected by the position of the resonator 12 by simply adjusting the coupling position between the resonator 13 and the line 6.
次に以上のことを等価回路を用いて説明する。Next, the above will be explained using an equivalent circuit.
第２図（ａ）は第１図を入力信号、局部発振およびイメ
ージ周波数帯域における等価回路で示したものである。FIG. 2(a) shows an equivalent circuit of FIG. 1 in the input signal, local oscillation, and image frequency bands.
入力信号および局部発振に共振した誘電体共振器２３．
２４は、イメージ周波数に対しては離調状態にあり、か
つ誘電体共振器のＱが高いために、イメージ周波数に対
しては第２図（ｂ）のようにダイオード２６に長さＬ４
のストリップ線路２５だけが接続されたものと見做され
、ダイオードの両端から見たインピーダンスは鈍りアク
タンスとなる。線路Ｌ４をイメージ周波数に対してλ／
４に選べばインピーダンスは零となる。Dielectric resonator 23 that resonates with the input signal and local oscillation.
24 is in a detuned state with respect to the image frequency, and since the Q of the dielectric resonator is high, the diode 26 has a length L4 as shown in FIG.
Only the strip line 25 is considered to be connected, and the impedance seen from both ends of the diode becomes dull and actance. The line L4 is λ/ with respect to the image frequency.
If you select 4, the impedance will be zero.
入力信号周波数に対してはこの信号に共振した誘電体共
振器２３は線路２５に結合し、局部発振周波数に共振し
た誘電体共振器２４は離調状態となるので等価回路は第
２図（ｃ）のように表わされ、入力信号電力は共振器２
４の影響を受けることなくダイオード２６に注入される
。同様の理由で局部発振周波数電力は共振器２３の影響
を受けることなくダイオード２６に注入される。For the input signal frequency, the dielectric resonator 23 that resonates with this signal is coupled to the line 25, and the dielectric resonator 24 that resonates with the local oscillation frequency becomes detuned, so the equivalent circuit is shown in Figure 2 (c). ), and the input signal power is expressed as
4 is injected into the diode 26 without being affected by the current. For the same reason, the local oscillation frequency power is injected into the diode 26 without being affected by the resonator 23.
共振器２３．２４に分布定数線路を用いて構成した場合
には、共振器のＱは誘電体共振器に比べて低く、共振器
の抵抗損失が線路に加わるため入力信号および局部発振
周波数の電力の一部がこれに吸収され雑音特性の劣化と
なる。When the resonators 23 and 24 are configured using distributed constant lines, the Q of the resonator is lower than that of a dielectric resonator, and the resistance loss of the resonator is added to the line, so the power of the input signal and local oscillation frequency is reduced. A part of the noise is absorbed by this, resulting in deterioration of the noise characteristics.
上記構成の変換器を厚さ０．３８ｍｍのアルミナ基板上
で試作し、入力信号帯域で十分カットオフとなるような
ケースに入れ実験を行なった。使用した誘電体共振器（
比誘電率約３１、直径２．８ｍｍ）の２２ＧＨｚ帯にお
ける無負荷Ｑは約３０００程度であった。A converter with the above configuration was prototyped on an alumina substrate with a thickness of 0.38 mm, and an experiment was conducted by placing it in a case that provided a sufficient cutoff in the input signal band. The dielectric resonator used (
The no-load Q in the 22 GHz band with a dielectric constant of about 31 and a diameter of 2.8 mm was about 3000.
入力信号周波数帯域通過濾波器の特性を第３図に示すが
、挿入損失は０．４ ｄＢ以下、イメージ周波数帯（１
９，８〜２０．３ＧＨｚ ）における減衰量は４５ｄＢ
以上が得られている。The characteristics of the input signal frequency bandpass filter are shown in Figure 3, and the insertion loss is 0.4 dB or less, and the image frequency band (1
9.8~20.3GHz) attenuation is 45dB
The above has been obtained.
また試作した変換器の変換損失２８および総合雑音指数
２７を第４図に示した。測定には利得４０ｄＢ雑音指数
１．２ ｄＢ以下のＩＰ増幅器を用いた。２２．５〜２
３．０ＧＨｚの入力信号に対し変換損失２８は５．６〜
６．５ ｄＢ、総合雑音指数２７は６．５〜７．６ ｄ
Ｂであった。Furthermore, the conversion loss 28 and overall noise figure 27 of the prototype converter are shown in FIG. For the measurements, an IP amplifier with a gain of 40 dB and a noise figure of 1.2 dB or less was used. 22.5~2
Conversion loss 28 is 5.6~ for 3.0GHz input signal
6.5 dB, total noise figure 27 is 6.5-7.6 d
It was B.
なおイメージ抑圧比は５６ｄＢ以上であった。Note that the image suppression ratio was 56 dB or more.
（発明の効果）
以上説明してきたように本発明による周波数変換器によ
れば、イメージインピーダンスの処理および入力信号回
路、局部発振回路との整合をそれぞれ独立に行なえる自
由度を有するので、雑音特性のすぐれた周波数変換器を
得ることができ、かつ調整が簡易な極めて実用性の高い
マイクロ波およびミリ波周波数変換器を提供することが
可能となった。(Effects of the Invention) As explained above, the frequency converter according to the present invention has the degree of freedom to perform image impedance processing and matching with the input signal circuit and the local oscillation circuit independently, so noise characteristics It has become possible to obtain an excellent frequency converter, and to provide an extremely practical microwave and millimeter wave frequency converter that is easy to adjust.
第１図は、本発明に関わる周波数変換器実施例の構成を
示し、
第２図（ａ）は第１図示構成の等価回路を、同図（ｂ）
、 （ｃ）および（ｄ）はそれぞれイメージ周波数、
入力信号周波数および局部発振周波数に対する等価回路
を示し、
第３図は本発明実施例装置に使用された入力信号周波数
帯域通過濾波器の特性を示し、第４図は、試作した本発
明変換器の変換損失および総合雑音指数の特性を示し、
第５図は、従来例の構成を示す。
１・・・誘電体基板
２・・・入力信号用入力マイクロストリップ線路３・・
・局部発振用入力マイクロストリップ線路４．２３．３
４・・・入力信号周波数帯域通過濾波器５．２４．３５
・・・局部発振周波数帯域通過濾波器６・・・結合用マ
イクロストリップ線路７．２６．３６・・・ミキサダイ
オード８．３３・・・中間周波数出力端子
９．２１．３１・・・入力信号入力端子１０、２２．３
２・・・局部発振入力端子１１．１２．１３・・・誘電
体共振器
１４．３７・・・中間周波数帯域通過濾波器１５・・・
ダイオード用直流リターン回路１６．３８・・・接地導
体部
２５・・・マイクロストリップ線路
２７・・・総合雑音指数 ２８・・・変換損失２９
・・・ＩＦ増幅器の雑音指数
第１図
第３図
第２図
（ａ）
２．１
（ｂ）
（Ｃ）
（ｄ）
第４図
第５図
手 続 補 正 書
昭和６２年 ４月１６日
特許庁長官 黒 １） 明 雄 殿１、事件の
表示
昭和６２年特許願第４８９０９号
２、発明の名称
周波数変換器
３、補正をする者
事件との関係 特許出願人
（４３５）日本放送協会
４、代理人
■、明細書の特許請求の範囲を下記の通りに訂正する。
「２、特許請求の範囲
■、 平面回路を用いた周波数変換器において、周波数
変換器ダイオードを接続した伝送線路に近接して、誘電
体共振器による入力信号周波数帯域通過濾波器と、誘電
体共振器による局部発振周波数帯域通過濾波器とを配置
し、２つの前記濾波器を介してそれぞれ入力される前記
入力信号および前記局部発振を前記伝送線路に電磁界結
合して前記ダイオードに印加し、両周波数差信号を前記
ダイオードから取出すようにしたことを特徴とする周波
数変換器。」
２、明細書第３頁第６行の「選択つれて」を「選択され
て」に訂正する。
３、同第４頁第６行の「変調用ダイオード」を「変換用
ダイオード」に訂正する。FIG. 1 shows the configuration of an embodiment of a frequency converter according to the present invention, FIG. 2(a) shows an equivalent circuit of the configuration shown in FIG.
, (c) and (d) are the image frequencies, respectively,
The equivalent circuit for the input signal frequency and the local oscillation frequency is shown, FIG. 3 shows the characteristics of the input signal frequency bandpass filter used in the device according to the embodiment of the present invention, and FIG. 4 shows the characteristics of the prototype converter of the present invention. The characteristics of conversion loss and total noise figure are shown, and FIG. 5 shows the configuration of a conventional example. 1... Dielectric substrate 2... Input microstrip line for input signal 3...
・Input microstrip line for local oscillation 4.23.3
4...Input signal frequency band pass filter 5.24.35
... Local oscillation frequency band pass filter 6 ... Microstrip line for coupling 7.26.36 ... Mixer diode 8.33 ... Intermediate frequency output terminal 9.21.31 ... Input signal input Terminal 10, 22.3
2... Local oscillation input terminal 11.12.13... Dielectric resonator 14.37... Intermediate frequency band pass filter 15...
DC return circuit for diode 16.38...Ground conductor section 25...Microstrip line 27...Total noise figure 28...Conversion loss 29
...Noise figure of IF amplifier Figure 1 Figure 3 Figure 2 (a) 2.1 (b) (C) (d) Figure 4 Figure 5 Procedures Amendment Book April 16, 1988 Commissioner of the Patent Office Kuro 1) Akio Yu 1, Indication of the case Patent Application No. 48909 of 1989 2, Name of the invention Frequency converter 3, Person making the amendment Relationship to the case Patent applicant (435) Japan Broadcasting Corporation 4 , Agent ■, amend the claims in the specification as follows. "2. Claim ■. In a frequency converter using a planar circuit, an input signal frequency bandpass filter using a dielectric resonator and a dielectric resonance A local oscillation frequency band-pass filter by a filter is arranged, and the input signal and the local oscillation, which are respectively inputted through the two filters, are electromagnetically coupled to the transmission line and applied to the diode. A frequency converter, characterized in that a frequency difference signal is extracted from the diode.'' 2. In the specification, page 3, line 6, ``selected'' is corrected to ``selected''. 3. Correct "modulation diode" in line 6 of page 4 to "conversion diode".
Claims (1)
調用ダイオードを接続した伝送線路に近接して、誘電体
共振器による入力信号周波数帯域通過濾波器と、誘電体
共振器による局部発振周波数帯域通過濾波器とを配置し
、２つの前記濾波器を介してそれぞれ入力される前記入
力信号および前記局部発振を前記伝送線路に電磁界結合
して前記ダイオードに印加し、両周波数差信号を前記ダ
イオードから取出すようにしたことを特徴とする周波数
変換器。1. In a frequency converter using a planar circuit, an input signal frequency bandpass filter using a dielectric resonator and a local oscillation frequency bandpass filter using a dielectric resonator are installed close to the transmission line connected to the frequency modulation diode. The input signal and the local oscillation, which are respectively input through the two filters, are electromagnetically coupled to the transmission line and applied to the diode, and the frequency difference signal is output from the diode. A frequency converter characterized in that it can be taken out.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP62048909A JPH0770928B2 (en) | 1987-03-05 | 1987-03-05 | Frequency converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP62048909A JPH0770928B2 (en) | 1987-03-05 | 1987-03-05 | Frequency converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS63217703A true JPS63217703A (en) | 1988-09-09 |
| JPH0770928B2 JPH0770928B2 (en) | 1995-07-31 |
Family
ID=12816384
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP62048909A Expired - Fee Related JPH0770928B2 (en) | 1987-03-05 | 1987-03-05 | Frequency converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0770928B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6169511B1 (en) | 1998-08-18 | 2001-01-02 | Uniden Corporation | Radar detector |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS53101914A (en) * | 1977-02-18 | 1978-09-05 | Hitachi Ltd | Mixer circuit |
| JPS56152305A (en) * | 1980-04-25 | 1981-11-25 | Nec Corp | Frequency converter |
| JPS6294002A (en) * | 1985-10-19 | 1987-04-30 | Sanyo Electric Co Ltd | Microwave receiver |
-
1987
- 1987-03-05 JP JP62048909A patent/JPH0770928B2/en not_active Expired - Fee Related
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS53101914A (en) * | 1977-02-18 | 1978-09-05 | Hitachi Ltd | Mixer circuit |
| JPS56152305A (en) * | 1980-04-25 | 1981-11-25 | Nec Corp | Frequency converter |
| JPS6294002A (en) * | 1985-10-19 | 1987-04-30 | Sanyo Electric Co Ltd | Microwave receiver |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6169511B1 (en) | 1998-08-18 | 2001-01-02 | Uniden Corporation | Radar detector |
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0770928B2 (en) | 1995-07-31 |
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