JPS6236470B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a constant voltage power supply device using a series resonant DC-DC converter that stabilizes the output DC voltage.

Conventional switching regulators generally use the PWM method, which stabilizes the output DC voltage by controlling the duty ratio of the on/off operation of the switching element. However, the disadvantage of the above method is that there is a period in which the direct current and voltage change sharply when the switching element is turned on and off, resulting in large switching losses and large unnecessary radiation noise. Therefore,
If we consider the above switching regulator as a power supply for audio equipment, we would insert a filter in the input/output section to greatly attenuate unnecessary radiation noise, and
Since noise countermeasures such as a completely sealed shield are required, there are problems such as increased costs and decreased reliability.

As a means to solve the above drawbacks, a series resonant DC-DC converter using a series resonant circuit composed of a capacitor and a coil has been proposed.
In this series resonant DC-DC converter, due to the series resonant circuit, the current waveform when the switching element is conducting becomes a sine wave, and the current and voltage intersect at zero when the switching element is turned on and off. Therefore, switching loss and unnecessary radiation noise are significantly reduced. However, in the above series resonant DC-DC converter, it is difficult to control input/output fluctuations to stabilize the output DC voltage without impairing the above characteristics.

Based on the above points, the circuit configuration and operation of a conventionally used series resonant DC-DC converter will be explained.

FIG. 1 is a basic circuit configuration diagram of a conventional series resonant DC-DC converter, and FIGS. 2a, b, and c are its operating waveform diagrams. In FIG. 1, switching elements (for example, transistors, thyristors, etc.) 3 and 4 that perform on/off operations are connected in series between both terminals of two input DC power supplies 1 and 2 connected in series. A resonance capacitor 7 and a primary winding 5 of a conversion transformer 5 are connected in series between the input DC power supplies 1 and 2 and the switching elements 3 and 4.
A is connected. Further, a rectifier circuit 8 and a smoothing capacitor 9 are connected to the secondary winding 5b of the conversion transformer 5, and a load 10 is connected to its output terminals a and b. Here, it is assumed that the resonant current flowing through the series resonant circuit composed of the resonant capacitor 7 and the effective leakage inductance of the conversion transformer 5 is i, and the charging voltage of the resonant capacitor 7 is _Vc . FIGS. 2a, b, and c show the on/off states of the switching elements 3 and 4, and operational waveform diagrams of the resonance current i and charging voltage _Vc . In FIG. ₂ , the switching element 3 is turned on at time t1, and the resonant current i is a sinusoidal current whose period is determined by the capacitance of the resonant capacitor 7 and the effective leakage inductance between time _t1 and time _t2 . becomes. During the above period, the charging voltage V _c changes from the initial charging voltage -V _c1 to V _c1 due to the resonance current i.

Next, at time _t2 , switching element 3 is turned off. During time t ₂ ≦ t ≦ t ₃ , both switching elements 3 and 4 are off, so the resonant current i becomes zero, and the charging voltage V _c1 of the resonant capacitor 7 also remains constant because there is no discharge path. . time t ₃
Then, when switching element 4 is turned on, time t ₁
The operating waveform is opposite in polarity to the operating waveform during ≦t≦t ₃ , and thereafter, when the switching element 3 is turned on again, the same operation is repeated. In addition, the resonant current i is
It is transmitted to the secondary side via the conversion transformer 5, and after rectification and smoothing, it is applied to the load 10 as a predetermined output DC voltage.
supplied to

The above is the circuit configuration and operation of a conventional series resonant DC-DC converter. Above series resonant DC
-As means for controlling the DC converter, it has been proposed to control the capacitance value of the resonance capacitor 7 and to control the period during which both the switching elements 3 and 4 are in the OFF state, that is, the switching frequency. However, in either case, control was difficult because the amount of resonance current i did not change.

The present invention aims to provide a constant voltage power supply device that stabilizes the output DC voltage over a wide range of input/output fluctuations without impairing the characteristics of the resonance system of the above-mentioned series resonant DC-DC converter. It is something to do.

The present invention will be described below, but first a control transformer having a variable inductance function used in the present invention will be described. Figure 3 is a schematic configuration diagram showing an example, Figure 4 is its characteristic diagram, and Figure 5 is a diagram showing its characteristics.
The figure shows the equivalent symbols. Third
In the figure, AC windings Na, Nb, Nc, and Nd are provided on each leg of a combination of an E-type core and an I-type core, or a combination of two E-type cores, and a DC winding Ne is provided on the center leg. A control terminal E of the DC winding Ne is provided,
A DC current source I is connected between F and F. Also,
A and B are input terminals, and C and D are output terminals. The AC windings Na and Nb are connected in series to form a first winding, and are wound in such a way that the magnetic flux induced in the center leg by the AC currents from the input terminals A and B is canceled out. In other words, the magnetic fluxes φ ₂ and φ' ₂ induced by the AC windings Na and Nb are equal.
Furthermore, the AC windings Nc and Nd are connected in series to form a second winding and are connected to the output terminals C and D, with a certain turns ratio to the AC windings Na and Nb. It is formed.

Here, by flowing a DC power from the DC power supply I, a magnetic flux φ ₁ is generated in the DC winding Ne, and the inductance between the input terminals A and B changes. Figure 4 shows the change in inductance between input terminals A and B due to direct current. Therefore, the inductance between the input terminals A and B can be controlled in a decreasing direction by applying a direct current between the control terminals E and F. Equivalent symbols for the control transformer described above are shown in FIG. 5, and embodiments of the present invention using this will be described below with reference to FIG. 6 and subsequent drawings. FIG. 6 is a circuit diagram of the first embodiment of the present invention, in which components having the same functions as those explained in FIG. 1 are given the same reference numerals. Further, FIGS. 7a, b, c, d, e, and f are operational waveform diagrams in FIG. 6.

In FIG. 6, 11 is a control transformer as illustrated in FIG. 3, 12 is a rectifier circuit, 13 is a comparison circuit, 14 is a DC current control circuit, and 15 is a distribution circuit. Input terminal A of the control transformer 11,
B is the output terminal C,
D is connected to the input side of the rectifier circuit 12, and control terminals E and F are connected to the output side of the DC current control circuit 14. Further, the output side of the rectifier circuit 12 is connected to the input DC power supply 2. The comparator circuit 13 compares the DC output voltages of the output terminals a and b applied to its input terminals with the value of a predetermined reference voltage _Es , and sends the difference signal to the DC current control circuit 14 and the distribution circuit 15. supply to. DC current control circuit 14
input terminals A, F of the control transformer 11 by supplying direct current according to the output signal from the comparison circuit 13 to the control terminals E, F of the control transformer 11.
This constitutes a first control means for changing the inductance between B (first winding). Further, the distribution circuit 15 generates a frequency-modulated pulse train according to the output signal from the comparison circuit 13, distributes and supplies this to the switching elements 3 and 4, and performs a second control to alternately turn them on and off. constitutes a means.

Next, the principle of operation of the embodiment shown in FIG. 6 will be explained with reference to FIG. 7. However, explanations that overlap with those of the conventional example will be omitted. The period of the resonant current i flowing through the resonant circuit is determined by the effective leakage inductance of the conversion transformer 5 and the inductance between the input terminals A and B of the resonant capacitor 7 and the control transformer 11. In addition, the control transformer 11
The control current i _L1 flowing between the input terminals A and B of is a continuous sine wave, and is synchronized with the resonant current i. The charging voltage of the resonant capacitor 7 increases in proportion to the sum of the resonant current i and the control current i _L1 . The above state is from time _t1 when switching element 3 is turned on to time _t'1 . At time t' ₁ , the voltage induced at the output terminals C and D of the control transformer 11 reaches the input DC power supply 2.
The charging energy stored in the resonance capacitor 7 is transmitted as discharge energy to the input DC power supply 2 of the DC-DC converter via the control transformer 11. This state is the time
From t′ ₁ to time t′ ₂ . Further, the output current i _L2 of the control transformer 11 flowing during the above period becomes a sine wave, and its period is determined by the capacitance of the resonance capacitor 7 and the inductance of the control transformer 11. As a result of the above phenomenon, the charging voltage V _c of the resonant capacitor 7 decreases to V _c4 (time t' ₂ o'clock) due to the flow of the output current i _L2 of the control transformer 11, and the time when the next switching element 4 turns on. t ₃
up to V _c2 by the control current i _L1 . Thereafter, the polarity is reversed as a phenomenon from time _t3 to time _t5 , and when the switching element 3 is turned on at time _t5 , the waveform becomes exactly the same from then on, and the same phenomenon is repeated.

Also, the factors that determine the amount of resonance current i are:
Since this is the initial charging voltage V _c of the resonance capacitor 7, changing the value of the initial charging voltage changes the amount of current transmitted to the secondary side via the conversion transformer 5, and the output terminal of the DC-DC converter changes. The energy supplied to a and b can be controlled.
The initial charging voltage V _c is − at time t ₁ in FIG.
V _c2 and V _c2 at time t ₃ . The above initial charging voltage (-V _c2 , V _c2 ) is the control transformer 1 as described above.
The amount of output current i _L2 of the control transformer ₁₁ is also related to the control current i _L1 . Therefore, in order to change the output DC voltage, it is sufficient to control the current amount of the control current i _L1 to be changed. In other words, the present invention utilizes the fact that the amount of control current i _L1 is inversely proportional to the inductance between the input terminals A and B of the control transformer 11, and is also inversely proportional to the switching frequency of the switching elements 3 and 4. be.

FIG. 8 shows a second embodiment of the present invention, and FIG.
The figure shows the operating waveforms. In this embodiment as well, parts having the same functions as those explained in FIG. 6 are given the same reference numerals. In this embodiment, the diodes 16 and 17 are connected in parallel to the switching elements 3 and 4 so as to conduct in the opposite direction to the conduction direction of the switching elements 3 and 4, that is, to be reverse biased with respect to the input DC power supplies 1 and 2. By connecting them, the charging energy stored in the resonance capacitor 7 is transferred to the input DC power source 1 or 2 through the diode 16 or 17 as regenerative energy. The operation will be explained below with reference to FIG. Note that the operation of flowing the output current i _L2 from the control transformer 11 is exactly the same as that in the first embodiment shown in FIG. 6, so a description thereof will be omitted here.
In FIG. 9, at time _t2 when the switching element 3 is turned off, the charging energy stored in the resonance capacitor 7 is transferred from the resonance capacitor 7 to the input DC power supply 1 via the conversion transformer 5 and the diode 16 as a regenerative current. be regenerated. The above phenomenon occurs during the period from time t ₂ to time t″ ₂ in the waveform diagram of the resonant current i shown in FIG. 9c. Therefore, the initial charging voltage V _c5 ( Time t ₃ ) varies greatly depending on the output current i _L2 of the control transformer 11 and the regenerative current. After that, the phenomenon of polarity reversal is repeated during the period from time t ₃ when the switching element 4 is turned on to time t ₅ , and further, When the switching element 3 is turned on at time _t5 , the operating waveform becomes the same as that from time _t1.The control operation is performed in exactly the same manner as in the embodiment shown in FIG. The connection points are not limited to those shown in the figure, and include a series connection circuit between the switching element 3 and the primary winding 5a of the conversion transformer 5, and a series connection circuit between the switching element 4 and the primary winding 5a of the conversion transformer 5. On the other hand, they may be connected in parallel, and similar effects can be obtained even in this case.

FIG. 10 shows a third embodiment of the present invention. Also in FIG. 10, parts having the same functions as those explained in FIG. 3 are given the same reference numerals. In FIG. 10, 18 and 19 are diodes, and 20 and 21 are the diodes 18 and 21, respectively.
The regenerative coil connected in series to 19 connects the primary winding 5a of the conversion transformer 5 and the switching elements 3 and 4.
are connected in parallel to the series connected circuits. The diodes 18 and 19 are connected so as to conduct in the direction opposite to the conduction direction of the switching elements 3 and 4, that is, to be reverse biased to the input DC power supplies 1 and 2. The operating principle of this embodiment is the same as that of utilizing the regenerative current from the resonant capacitor 7 described in the second embodiment shown in FIG.
Since _d1 and i _d2 are regenerated to the input DC power supply 1 or 2 through the series-connected diode and regeneration coil (18 and 20 or 19 and 21) without going through the conversion transformer 5, the DC-DC converter The difference is that the output energy is not the same. Furthermore, by changing the inductance of the regenerative coil 20 or 21, the periods of the regenerative currents i _d1 and i _d2 can be arbitrarily changed. The control operation is completely similar to the embodiments shown in FIGS. 6 and 8.

In each of the embodiments of the present invention described above, a configuration has been described in which the charging energy of the resonant capacitor 7 is fed back to one of the input DC power sources 2 using the control transformer 11. A similar effect can be obtained by feeding back to the entire input DC power supplies 1 and 2 connected to the input DC power supplies 1 and 2. Furthermore, in each of the embodiments of the present invention described above, two switching elements are used.
Although a half-bridge configuration using four switching elements is used, a full-bridge configuration using four switching elements can also be used, and similar effects can be obtained. Furthermore, although the effective leakage inductance of the resonant capacitor and the conversion transformer is used to form the series resonant circuit in the present invention, a resonant coil is connected in series with the primary winding of the resonant capacitor and the conversion transformer. It is also possible to create a series resonant circuit using the inductance of the resonant coil.
It goes without saying that it is included in the present invention.

As described above, according to the present invention, the output DC voltage can be stabilized over a wide range of input/output fluctuations with a simple circuit configuration while taking advantage of the features of the series resonant DC-DC converter. , its industrial value is extremely high.

[Brief explanation of the drawing]

Fig. 1 is a circuit configuration diagram of a conventional series resonant DC-DC converter, Fig. 2 a, b, and c are its operating waveform diagrams, and Fig. 3 is a schematic diagram showing an example of the configuration of a control transformer used in the present invention. , FIG. 4 is its characteristic diagram, FIG. 5 is its equivalent symbol diagram, FIG. 6 is a circuit configuration diagram of the first embodiment of the present invention, and FIG. 7 is a, b, c, d, e, f.
8 is a circuit diagram of the second embodiment of the present invention, and FIG. 9 is a, b, c, d, e, f.
10 is an operating waveform diagram thereof, and FIG. 10 is a circuit configuration diagram of a third embodiment of the present invention. 1, 2... Input DC power supply, 3, 4... Switching element, 5... Conversion transformer, 5a... Primary winding, 5b
... Secondary winding, 7... Resonance capacitor, 8... Rectifier circuit, 9... Smoothing capacitor, 10... Load, 11...
Control transformer, 12... Rectifier circuit, 13... Comparison circuit, 14... DC current control circuit, 15... Distribution circuit, 16, 17, 18, 19... Diode, 2
0,21...Regeneration coil.

Claims (1)

[Claims] 1. At least a switching element and a conversion transformer that operate on and off with respect to an input DC power source.
A series connection circuit including a secondary winding and a resonant capacitor is connected, and a first rectifier circuit and a smoothing circuit are connected to the secondary winding of the conversion transformer to obtain a DC output voltage at an output terminal. DC
- a DC converter, a first winding connected in parallel to the resonance capacitor, and a second winding for output extraction; and the inductance of the first winding is controlled by the supplied electric signal a second rectifier circuit that rectifies a signal voltage obtained from a second winding of the control transformer and supplies it to the input DC power supply;
first control means for controlling the inductance of the control transformer as a function of the DC output voltage available at the output terminal of the DC-DC converter;
A constant voltage power supply device comprising second control means for controlling the switching frequency (or period) of the switching element as a function of the DC output voltage obtained at the output terminal of the DC converter. 2. A constant voltage power supply device according to claim 1, characterized in that a unidirectional element is connected in parallel to the switching element so as to conduct in a direction opposite to the conduction direction of the switching element. 3 In the statement of claim 1, a circuit in which a coil and a unidirectional element that conducts in a direction opposite to the conduction direction of the switching element are connected in series is defined as a circuit in which a coil and a unidirectional element that conducts in a direction opposite to the conduction direction of the switching element are connected in series.
A constant voltage power supply device characterized in that it is connected in parallel to the series connection circuit of the next winding.