JPS6216031Y2 - - Google Patents
Info
- Publication number
- JPS6216031Y2 JPS6216031Y2 JP7355181U JP7355181U JPS6216031Y2 JP S6216031 Y2 JPS6216031 Y2 JP S6216031Y2 JP 7355181 U JP7355181 U JP 7355181U JP 7355181 U JP7355181 U JP 7355181U JP S6216031 Y2 JPS6216031 Y2 JP S6216031Y2
- Authority
- JP
- Japan
- Prior art keywords
- signal
- resistor
- frequency
- tone squelch
- amplifies
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 239000003990 capacitor Substances 0.000 description 10
- 230000008878 coupling Effects 0.000 description 6
- 238000010168 coupling process Methods 0.000 description 6
- 238000005859 coupling reaction Methods 0.000 description 6
- 238000000034 method Methods 0.000 description 4
- 238000004891 communication Methods 0.000 description 3
- 230000005540 biological transmission Effects 0.000 description 2
- 230000015572 biosynthetic process Effects 0.000 description 2
- 238000010586 diagram Methods 0.000 description 2
- 230000010355 oscillation Effects 0.000 description 2
- 230000005236 sound signal Effects 0.000 description 2
- 238000003786 synthesis reaction Methods 0.000 description 2
- 230000003321 amplification Effects 0.000 description 1
- 238000007796 conventional method Methods 0.000 description 1
- 239000013078 crystal Substances 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000010295 mobile communication Methods 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 230000002194 synthesizing effect Effects 0.000 description 1
Landscapes
- Transmitters (AREA)
Description
【考案の詳細な説明】
本考案は送信変調用の入力信号の信号合成器に
関するものである。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a signal synthesizer for input signals for transmission modulation.
従来、移動無線にはノイズスケルチ方式とトー
ンスケルチ方式があり、トーンスケルチ方式の送
信機の構成例を第1図に示す。同図において、1
は水晶発振器や周波数シンセサイザー等の安定な
周波数発振源を用いた原発振器で、その発振周波
数(o)は送信周波数(i)の(1/逓倍
数)である。2は位相変調器、3,4はそれぞれ
逓倍数がmよびnの周波数逓倍器、5は電力増幅
器、6はアンテナ、7は信号合成器、8はIDC
(瞬時偏移調節回路)、9はマイクロホン、10は
トーンスケルチ発振器、11はその起動スイツチ
である。 Conventionally, mobile radio has a noise squelch method and a tone squelch method, and an example of the configuration of a tone squelch transmitter is shown in FIG. In the same figure, 1
is an original oscillator using a stable frequency oscillation source such as a crystal oscillator or a frequency synthesizer, and its oscillation frequency (o) is a (1/multiply) of the transmission frequency (i). 2 is a phase modulator, 3 and 4 are frequency multipliers with multipliers of m and n, respectively, 5 is a power amplifier, 6 is an antenna, 7 is a signal combiner, and 8 is an IDC.
(instantaneous deviation adjustment circuit), 9 is a microphone, 10 is a tone squelch oscillator, and 11 is a start switch thereof.
70は電源入力端子、71はIDCからの音声周
波数入力端子、81はトーンスケルチ信号の入力
端子、R1〜R4は抵抗器、C1〜C2はコンデンサで
ある。 70 is a power input terminal, 71 is an audio frequency input terminal from the IDC, 81 is an input terminal for a tone squelch signal, R 1 to R 4 are resistors, and C 1 to C 2 are capacitors.
上記構成において、マイクロホン9の音声と、
トーンスケルチ発振器10の出力は信号合成器7
で合成の上、原発振器1の出力位相変調器2によ
り変調を掛けた上で、逓倍器3,4によりm×n
倍に逓倍されて、電力増幅後アンテナ6により送
信される。このように第1図で示したトーンスケ
ルチ方式は通話音声信号とその通信系個有の信号
を同時に送出し、受信側でこの信号を受信したと
き通話回路をスピーカに接続するようにしたもの
である。トーンスケル用の周波数には2つの異な
る系列があるが、一般に67Hz〜250.3Hzが使用さ
れている。 In the above configuration, the audio of the microphone 9,
The output of the tone squelch oscillator 10 is sent to the signal synthesizer 7
After synthesizing it, it is modulated by the output phase modulator 2 of the original oscillator 1, and then m×n
The signal is multiplied twice and transmitted by the antenna 6 after power amplification. In this way, the tone squelch method shown in Figure 1 simultaneously sends out a voice signal and a signal unique to the communication system, and when the receiving side receives this signal, it connects the communication circuit to the speaker. . There are two different series of frequencies for tone scales, but 67Hz to 250.3Hz are commonly used.
これに対して通話音声帯域は300〜3000Hzであ
るから、これをフイルターで切分けするには信号
周波数の上限と音声帯域の下限が接近し、周波数
が低いため、これに使用するフイルター容積は大
きくなり、移動通信機器等への組込みは適当でな
い。このため、第1図に示した合成器7において
R1,C1アームにはIDC出力を、R2,C2アームに
はトーン信号出力が接続されるが、R2,C2アー
ムの負荷インピーダンスの変動によりIDC出力が
変化する。電波法で周波数偏移は厳しく規定され
ており、所定レベルを超過しないように内輪目に
レベル設定され、S/Nの点で損失となつてい
る。 On the other hand, the telephone voice band ranges from 300 to 3000Hz, so in order to separate this using a filter, the upper limit of the signal frequency and the lower limit of the voice band are close to each other, and since the frequency is low, the volume of the filter used for this is large. Therefore, it is not appropriate to incorporate it into mobile communication equipment, etc. Therefore, in the combiner 7 shown in FIG.
The IDC output is connected to the R 1 and C 1 arms, and the tone signal output is connected to the R 2 and C 2 arms, but the IDC output changes due to fluctuations in the load impedance of the R 2 and C 2 arms. Frequency deviation is strictly regulated under the Radio Law, and the level is set at an inner level so as not to exceed a predetermined level, resulting in a loss in terms of S/N.
また、調整の際は無線機部分と信号器部分は別
個に組立てられるが、この際、便宜的に信号器と
似かよつたダミー抵抗を負荷してレベル調整後、
両者を結合することを行つているが、本来、厳し
い規格の無線機ではどうしても変調レベルの設定
が内輪になるだけでなく、厳密には変調信号の周
波数特性にも、信号系のインピーダンスが悪い影
響を与える点で問題があつた。 Also, when making adjustments, the radio part and the signal part are assembled separately, but at this time, for convenience, a dummy resistor similar to the signal part is loaded, and after adjusting the level,
Although we are trying to combine the two, in radio equipment that meets strict standards, not only is it inevitable to set the modulation level, but strictly speaking, the impedance of the signal system has a negative effect on the frequency characteristics of the modulated signal. There was a problem in giving .
本考案はこれらの欠点を除いて、IDCを付加し
た音声信号およびトーンスケルチの信号のレベル
の設定に当つて、入力信号源のインピーダンスの
影響を全く受けないようにし、機器調整をより簡
単、確実に行ない易くし、音声通信の変調特性に
変化のない信号合成器を提供することを目的とす
るものである。 The present invention eliminates these drawbacks and makes it possible to set the level of the IDC-added audio signal and tone squelch signal without being affected by the impedance of the input signal source, making equipment adjustment easier and more reliable. It is an object of the present invention to provide a signal synthesizer that is easy to perform and that does not change the modulation characteristics of voice communication.
以下にその実施例と共に説明する。第2図は本
考案になるトーンスケル信号の信号合成回路の一
実施例である。 This will be explained below along with examples. FIG. 2 shows an embodiment of a signal synthesis circuit for tone scale signals according to the present invention.
第2図において、符号1〜6,8〜11,7
0,71,81はそれぞれ第1図における同符号
のものに対応する。21,22は変調器動作点を
決めるバイアス電圧用分圧器、72は結合コンデ
ンサー、73は入力調整器、74,75は分圧抵
抗、76は帰還抵抗、78は直列抵抗、79は結
合コンデンサー、82は結合コンデンサー、83
は入力調整器、84,85は分圧抵抗、86,8
7は帰還用抵抗とコンデンサー、88は直列抵
抗、89は結合コンデンサー、90,91はオペ
アンプである。 In Fig. 2, symbols 1 to 6, 8 to 11, 7
0, 71, and 81 correspond to the same reference numerals in FIG. 1, respectively. 21 and 22 are voltage dividers for bias voltage that determine the modulator operating point, 72 is a coupling capacitor, 73 is an input regulator, 74 and 75 are voltage dividing resistors, 76 is a feedback resistor, 78 is a series resistor, 79 is a coupling capacitor, 82 is a coupling capacitor, 83
is an input regulator, 84, 85 are voltage dividing resistors, 86, 8
7 is a feedback resistor and capacitor, 88 is a series resistor, 89 is a coupling capacitor, and 90 and 91 are operational amplifiers.
次にこの実施例の動作を説明する。音声周波数
入力端子71からの音声入力は帰還増幅器90で
増幅され、直列抵抗78、結合コンデンサー79
を介して変調器2に加えられる。変調器2は入力
レベルに対して位相変化を与えるものであるか
ら、一定レベルの信号に対しては△F=nmm
となり、変調周波数(m)により6dB/Octの
周波数特性を有する位相変調を与える。変調レベ
ルの設定は第2図の接続状態にて可変抵抗73で
行なう。オペアンプ90,91をそれぞれの出力
端子a,bからみたインピーダンスはほぼ0であ
るから、直列抵抗78とし抵抗21,22,88
の並列抵抗インピーダーで分割された電圧が変調
器2の入力となる。 Next, the operation of this embodiment will be explained. The audio input from the audio frequency input terminal 71 is amplified by a feedback amplifier 90, which is connected to a series resistor 78 and a coupling capacitor 79.
is applied to modulator 2 via. Since the modulator 2 gives a phase change to the input level, △F=nmm for a signal at a constant level.
The modulation frequency (m) gives phase modulation with a frequency characteristic of 6 dB/Oct. The modulation level is set using the variable resistor 73 in the connection state shown in FIG. Since the impedance of the operational amplifiers 90 and 91 when viewed from their respective output terminals a and b is approximately 0, the series resistor 78 is used as the resistor 21, 22, 88.
The voltage divided by the parallel resistance impeders becomes the input to the modulator 2.
トーンスケルチの信号はオペアンプ91で増幅
されるが、抵抗86、コンデンサ87により積分
回路を形成しており、変調入力67〜250を−
6dB/octでレベル傾斜させて出力する。この場
合、前述のオペアンプ90の場合と同様に信号は
直列抵抗88と抵抗78,21,22の並列抵抗
で分割されて変調器2に加えられるが、この場合
には変調周波数に無関係の△Fを与え等価的な
FM変調とする。 The tone squelch signal is amplified by the operational amplifier 91, but the resistor 86 and capacitor 87 form an integrating circuit, and the modulation inputs 67 to 250 are -
Outputs with a level gradient of 6dB/octave. In this case, as in the case of the operational amplifier 90 described above, the signal is divided by the series resistor 88 and the parallel resistors 78, 21, and 22 and is applied to the modulator 2. giving the equivalent
FM modulation.
直列抵抗78,88を抵抗21,22に対して
充分小さく選び、結合コンデンサー79,89を
充分に大きな容量とすれば、オペアンプ90に対
しては直列抵抗88が、またオペアンプ91に対
しては抵抗78が負荷インピーダンスとして安定
に動作する。 If the series resistors 78, 88 are selected to be sufficiently small compared to the resistors 21, 22 and the coupling capacitors 79, 89 are selected to have a sufficiently large capacitance, the series resistor 88 for the operational amplifier 90 and the resistor 78 for the operational amplifier 91 operate stably as a load impedance.
また、トーンスケルチの信号レベルは音声に対
して一般に低く選ぶので、この場合には直列抵抗
88を抵抗78に対し大きくして分割比を変える
ようにしてもよいことになる。 Further, since the tone squelch signal level is generally selected to be low compared to the voice, in this case, the series resistor 88 may be made larger than the resistor 78 to change the division ratio.
なお、この信号合成は同一周波数帯域の複数の
信号を干渉なく合成できるので応用分野も広い。 Note that this signal synthesis can be applied to a wide range of fields because multiple signals in the same frequency band can be synthesized without interference.
以上、説明したように本考案によれば、2つの
増幅器の出力側からみたインピーダンスはほぼ0
であるから、音声信号とトーンスケルチ信号の2
つの信号をフイルター等を用いずにしかも干渉な
く合成することができ、そのレベル調整に当つて
も各個独立して行ない得るので、従来のように互
いのインピーダンスを想定した負荷状態でレベル
設定をする必要がないので調整を各ブロツク毎に
行ない、これを接続するだけで所要の特性が得ら
れるので、量産機器の調整に当つて工程を分割
し、独立して行なわせることができるのでその工
業的価値は大きい。 As explained above, according to the present invention, the impedance seen from the output side of the two amplifiers is almost 0.
Therefore, there are two signals: the audio signal and the tone squelch signal.
It is possible to combine two signals without using a filter or the like and without interference, and the level adjustment can be done independently for each signal, so the level can be set under a load condition assuming each other's impedance as in the conventional method. Since this is not necessary, adjustments can be made for each block and the desired characteristics can be obtained by simply connecting them. This allows the process to be divided into parts and performed independently when adjusting mass-produced equipment, thereby improving industrial efficiency. Great value.
第1図は従来の無線機の信号合成器の結線図、
第2図は本考案の一実施例による信号合成器の結
線図である。
90,91……オペアンプ、78,88……直
列抵抗、76,86……抵抗、87……コンデン
サ、2……変調器。
Figure 1 is a wiring diagram of a conventional radio signal synthesizer.
FIG. 2 is a wiring diagram of a signal synthesizer according to an embodiment of the present invention. 90, 91... operational amplifier, 78, 88... series resistor, 76, 86... resistor, 87... capacitor, 2... modulator.
Claims (1)
る第1のオペアンプ、負帰還が施され、通話音声
信号を増幅する第2のオペアンプ、抵抗により構
成され、上記第1、第2のオペアンプの出力を合
成する合成回路、およびこの合成出力が加えられ
る位相変調器を備え、上記第1のオペアンプで構
成され、トーンスケルチ信号を増幅する増幅部を
積分特性として、トーンスケルチ信号の周波数に
対して周波数偏移一定の等価FM変調特性を与え
たことを特徴とする信号合成器。 A first operational amplifier that is subjected to negative feedback and amplifies the tone squelch signal, a second operational amplifier that is subjected to negative feedback and amplifies the call voice signal, and a resistor, and synthesizes the outputs of the first and second operational amplifiers. and a phase modulator to which the synthesized output is added, and the amplifying section that amplifies the tone squelch signal has an integral characteristic, and has a constant frequency deviation with respect to the frequency of the tone squelch signal. A signal synthesizer characterized by providing equivalent FM modulation characteristics.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7355181U JPS6216031Y2 (en) | 1981-05-20 | 1981-05-20 |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP7355181U JPS6216031Y2 (en) | 1981-05-20 | 1981-05-20 |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS57185240U JPS57185240U (en) | 1982-11-25 |
JPS6216031Y2 true JPS6216031Y2 (en) | 1987-04-23 |
Family
ID=29869316
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP7355181U Expired JPS6216031Y2 (en) | 1981-05-20 | 1981-05-20 |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS6216031Y2 (en) |
-
1981
- 1981-05-20 JP JP7355181U patent/JPS6216031Y2/ja not_active Expired
Also Published As
Publication number | Publication date |
---|---|
JPS57185240U (en) | 1982-11-25 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
JPH08274559A (en) | Output power controller | |
KR970013809A (en) | Radio transmitter and high frequency power amplifier | |
EP0476908B1 (en) | Amplifying circuit | |
JPH06505138A (en) | High dynamic range closed circuit automatic gain control circuit and method | |
JPH0923119A (en) | Prior strain circuit and mobile machine using this circuit | |
EP0823779A2 (en) | High-frequency amplifier | |
US4110692A (en) | Audio signal processor | |
US4947141A (en) | Oscillator network for radio receiver | |
US4064462A (en) | Acoustic feedback peak elimination unit | |
JPS6216031Y2 (en) | ||
US4403201A (en) | Bandpass filter circuit | |
JP2000165146A (en) | Transmitter and modulator for mobile station | |
GB2209642A (en) | Active filter / equaliser | |
US6118991A (en) | Device including a broadband amplifier circuit | |
US5625698A (en) | Loudspeaker and design methodology | |
AU745842B2 (en) | Signal processing system | |
US6928170B1 (en) | Wireless microphone having a split-band audio frequency companding system that provides improved noise reduction and sound quality | |
CA1246151A (en) | Autodyne receiver | |
KR970004548A (en) | Hearing Aid with Voice Amplification and Frequency Filtering | |
JPH08130428A (en) | Variable gain amplifier | |
JP2712923B2 (en) | SAT phase shift circuit | |
JPS5631235A (en) | Active antenna system | |
JPS6223139Y2 (en) | ||
US5705951A (en) | Method for correction of error signals in a signal amplification system and an apparatus used for that purpose | |
JPH062397Y2 (en) | Loudspeaker |