JPS5990471A - Signal processing circuit - Google Patents
Signal processing circuitInfo
- Publication number
- JPS5990471A JPS5990471A JP57201322A JP20132282A JPS5990471A JP S5990471 A JPS5990471 A JP S5990471A JP 57201322 A JP57201322 A JP 57201322A JP 20132282 A JP20132282 A JP 20132282A JP S5990471 A JPS5990471 A JP S5990471A
- Authority
- JP
- Japan
- Prior art keywords
- output
- amplifier
- signal
- controlled oscillator
- video
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
- H04N5/60—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals
Landscapes
- Engineering & Computer Science (AREA)
- Multimedia (AREA)
- Signal Processing (AREA)
- Processing Of Color Television Signals (AREA)
Abstract
Description
【発明の詳細な説明】
〔発明の技術分野〕
この発明は、例えばテレビジョン受像機の映像検波及び
音声中間周波数（以下ＳＩＦ；５ＯＵＮＤ ＩＮＴ−
ＥＲＦＲＥＱＵＥＮＣＹと称す。）検波方式に関するも
ので、映像信号と音声信号の相互防害を減らし、良好な
映書信号と音声信号を提供するものである。[Detailed Description of the Invention] [Technical Field of the Invention] The present invention relates to, for example, video detection and audio intermediate frequency (hereinafter referred to as SIF) of a television receiver.
It is called ERFREQUENCY. ) It is related to a detection method that reduces mutual interference between video and audio signals and provides good video and audio signals.
従来、この種の検波方式として大きく分けてインターキ
ャリア方式とスプリットキャリア方式の２つがあった。Conventionally, there have been two main types of detection methods of this type: an intercarrier method and a split carrier method.
インターキャリア方式の例として以下に示すものがある
。第１図において（１）はチューナー、（２）はチュー
ナーの出力に接続されたバンドパスフィルター、（３）
はバンドパスフィルタ（２）につながれた増幅器、（４
）は増幅器の出力につながれた狭帯域増幅器、（５）は
掛算器、（６）は出力端子である。チューナー（１）よ
り中間周波数に周波数変換された信号は第２図に示す周
波数特性をもつバンドパスフィルター（２）を通り増幅
器（３）で増幅される。Examples of intercarrier systems include the following. In Figure 1, (1) is a tuner, (2) is a bandpass filter connected to the output of the tuner, and (3) is a tuner.
is an amplifier connected to a bandpass filter (2), (4
) is a narrowband amplifier connected to the output of the amplifier, (5) is a multiplier, and (6) is an output terminal. The signal frequency-converted to an intermediate frequency by the tuner (1) passes through a band-pass filter (2) having frequency characteristics shown in FIG. 2, and is amplified by an amplifier (3).
第２図で、ｆｐは映像信号搬送波、ｆｃ は色信号搬送
波、ｆｓは音声信号搬送波を示す、増幅器（３）で増幅
された信号は帯域増幅器（４）で映像信号搬送波付近の
み増幅され、掛算器（５）において増幅器（３）の出力
と掛算され、出力端子（６）に検波出力を出す。In Figure 2, fp is a video signal carrier wave, fc is a color signal carrier wave, and fs is an audio signal carrier wave.The signal amplified by the amplifier (3) is amplified only near the video signal carrier wave by the band amplifier (4), and multiplied by The signal is multiplied by the output of the amplifier (3) in the detector (5), and a detected output is output to the output terminal (6).
第１図に示す回路は最とも簡単に構成できるインターキ
ャリア方式の一つで擬似同期検波と呼ばれているが、帯
域増幅器（４）の周波数選択度が十分とれないため、色
信号搬送波ｆｃと音声信号搬送波ｆｓの差の成分９２０
ｋ）ｌｘがビー°トとなり、映像に９２０ｋＨｚビー
トと呼ばれる妨害を生ずる。それを防ぐため（２）のバ
ンドパスフィルターにおいて音声信号搬送波ｆｓの減衰
量を大きくすれば良いが逆に出力端子（６）に出力され
る４、５ Ｍ ＨｚのＳＩＦ Ｈ号が小さくなり、バズ
と呼ばれる音声における映像の妨害音が大きくなる。The circuit shown in Figure 1 is one of the easiest intercarrier systems to configure and is called pseudo-synchronous detection, but because the frequency selectivity of the band amplifier (4) is not sufficient, the chrominance signal carrier fc Difference component 920 of audio signal carrier fs
k) lx becomes a beat and causes a disturbance called 920kHz beat in the video. To prevent this, the amount of attenuation of the audio signal carrier fs can be increased in the bandpass filter (2), but conversely, the SIF H signal of 4 or 5 MHz output to the output terminal (6) becomes smaller, causing a buzz. The sound that interferes with the video in the audio becomes louder.
第８図は第１図における欠点を改良したもので、（１）
から（６）は第１図と同じものである。（７）は第４図
に示すような音声信号搬送波のみ減衰させるトラップで
、（８）は増幅器（３）の出力を包絡線検波する検波器
で、（６ａ）はその出力端子である。掛算器（５）で掛
算された信号は、トラップ（７）で音声搬送波が減衰し
ているので、９２０ｋｌＩＺビートが小さくなる。出力
端子（６）は映像信号の出力端子として、出力端子（６
ａ）はＳＩＦ信号の出力端子として用られる。（８）の
検波器として包絡線検波の他に擬似同期検波が使われる
こともある。第８図の回路では第１図における回路より
９２０ｋｌｈビート、バズが小さくなるが増幅器（３）
の非直線性により生ずるビート成分と、検波器（８）で
生ずる直交歪によるバズは減らすことができず、音声多
重などの音声の高品質化には性能が十分ではない。Figure 8 is an improved version of the defects in Figure 1, (1)
to (6) are the same as in FIG. (7) is a trap that attenuates only the audio signal carrier as shown in FIG. 4, (8) is a detector that performs envelope detection of the output of the amplifier (3), and (6a) is its output terminal. In the signal multiplied by the multiplier (5), the audio carrier wave is attenuated by the trap (7), so the 920klIZ beat becomes smaller. The output terminal (6) is used as an output terminal for video signals.
a) is used as an output terminal for the SIF signal. In addition to envelope detection, pseudo-synchronous detection may be used as the detector in (8). The circuit in Figure 8 has a 920klh beat and smaller buzz than the circuit in Figure 1, but the amplifier (3)
The beat component caused by the nonlinearity of the signal and the buzz caused by the orthogonal distortion caused by the detector (8) cannot be reduced, and the performance is not sufficient for high quality audio such as audio multiplexing.
第５図に示す回路は第８図の回路の欠点を補うものでＰ
ＬＬ （Ｐｈａｓｅ Ｌｏｃｋｅｄ Ｌｏｏｐ ）検波
を応用したものである。第５図において、（１）から（
６）は第１図と同一で、（９）は位相比較器、００は、
電圧制御発振器、θυは位相比較器（９）の出力電圧を
平滑するためのローパスフィルタ、（１２はＰＬＬと呼
ばれる領域を示す。ＰＬＬ （１３は増幅器（３）より
出力された信号のうちの映像信号搬送波と、電圧制御発
振器０１ｌ）の発振周波数との位相を一致させる。検波
器（５）は電圧制御発振器００の出力と、増幅器（３）
の出力を掛算するため理想に近い同期検波をすることが
でき、直交歪によるバズ、やビートを減らすことができ
る。The circuit shown in Fig. 5 compensates for the drawbacks of the circuit shown in Fig. 8.
This is an application of LL (Phase Locked Loop) detection. In Figure 5, from (1) to (
6) is the same as in Figure 1, (9) is a phase comparator, and 00 is
A voltage controlled oscillator, θυ is a low-pass filter for smoothing the output voltage of the phase comparator (9), (12 indicates a region called PLL. PLL (13 is an image of the signal output from the amplifier (3) Match the phase of the signal carrier wave and the oscillation frequency of the voltage controlled oscillator 01l).The detector (5) detects the output of the voltage controlled oscillator 00 and the amplifier (3).
By multiplying the outputs of , nearly ideal synchronous detection can be performed, and buzz and beats caused by orthogonal distortion can be reduced.
しかしながら、増幅器（３）の非直線性で発生するビー
ト成分はそのまま検波されてしまうため、バンドパスフ
ィルタ（２）において、音声信号搬送波を第２図におけ
るように減衰させなければならない。However, since the beat component generated by the nonlinearity of the amplifier (3) is detected as is, the audio signal carrier must be attenuated in the bandpass filter (2) as shown in FIG.
このため、弱電界における音声の信号対雑音比が悪化す
る。この欠点は、第１図、第３図に示す回路にも共通で
、これらインターキャリア方式のもつ欠点である。Therefore, the signal-to-noise ratio of audio in a weak electric field deteriorates. This drawback is common to the circuits shown in FIGS. 1 and 3, and is a drawback of these intercarrier systems.
第６図は、スプリットキャリア方式の従来例を示す。（
１）〜（６）は第１図と同一である。（２ａ）は第７図
に示す周波数特性をもつバンドパスフィルタ、（２ｂ）
は第８図に示す周波数特性をもつバンドパスフィルタ、
０３は音声搬送波ｆｓをＳＩＦ信号に周波数変換するた
めの掛算器、Ｑ４１はＳＩＦ信号のみ通すバンドパスフ
ィルタ、０時は振幅制限増幅器、０ゆはＦＭ検波器、α
力は音声出力端子、ａ樽はＦＭ検波器の出力の直流電圧
を得るためのローパスフィルタ、０呻は局部発振器であ
る。掛算器ａ場によりバンドパスフィルタ（２ｂ）から
入力される信号と局部発振器萌の発振周波数の差がＳＩ
Ｆ信号となり、その周波数はＦＭ検波器ＯＱの出力直流
電圧として検知され、局部発振周波数がいつも、音声信
号搬送波ｆｓよりＳＩＦ信号周波数だけ低くなるように
帰還がかけられている。第６図の回路では、ＳＩＦ信号
への周波数変換の際、バンドパスフィルタ（２ｂ）によ
り映像信号成分がいっさい除かれているため、バズがほ
とんど発生しない。又、映像検波もバンドパスフィルタ
（２ａ）により音声信号搬送波ｆｓが除かれているため
、９２０ ｋｌｂビートも生じない。第６図のスプリッ
トキャリア方式における欠点は、局部発振器０呻の周波
数安定度の高さが要求されることと、チューナー（１）
の内部の局部発振周波数がずれた時、バンドパスフィル
タ（２ｂ）を通過する音声信号搬送波のレベルが急激に
減衰するため、局部発振器α１が音声信号搬送波よすＳ
ＩＦ信号の周波数分だけ低い周波数に引き込むことがで
きなくなるということである。FIG. 6 shows a conventional example of the split carrier system. (
1) to (6) are the same as in FIG. (2a) is a bandpass filter with the frequency characteristics shown in Figure 7; (2b)
is a bandpass filter with the frequency characteristics shown in Figure 8,
03 is a multiplier for converting the frequency of the audio carrier wave fs into an SIF signal, Q41 is a band pass filter that passes only the SIF signal, 0 is an amplitude limiting amplifier, 0 is an FM detector, α
Power is an audio output terminal, barrel a is a low-pass filter for obtaining the DC voltage output from the FM detector, and zero is a local oscillator. The difference between the signal input from the bandpass filter (2b) and the oscillation frequency of the local oscillator Moe by the multiplier a field is SI
F signal, whose frequency is detected as the output DC voltage of the FM detector OQ, and feedback is applied so that the local oscillation frequency is always lower than the audio signal carrier fs by the SIF signal frequency. In the circuit shown in FIG. 6, during frequency conversion to an SIF signal, the band pass filter (2b) removes all video signal components, so almost no buzz occurs. Also, since the audio signal carrier fs is removed by the bandpass filter (2a) in video detection, no 920 klb beat occurs. The disadvantages of the split carrier system shown in Figure 6 are that high frequency stability is required for the local oscillator (0), and that the tuner (1)
When the internal local oscillation frequency shifts, the level of the audio signal carrier wave passing through the bandpass filter (2b) is rapidly attenuated, so that the local oscillator α1
This means that it becomes impossible to pull in a frequency as low as the frequency of the IF signal.
この発明は、従来のインターキャリア方式及びスプリッ
トキャリア方式での上で述べた欠点を除去するためのも
のであり、簡単な回路で、良好な映像信号とＳＩＦ信号
を得ることのできる回路を提供することを目的としたも
のである。The present invention is intended to eliminate the above-mentioned drawbacks of the conventional intercarrier system and split carrier system, and provides a circuit that can obtain good video signals and SIF signals with a simple circuit. It is intended for this purpose.
第９図に本発明の一実施例を示す。第９図において第１
図、第５図、第６図における同一番号は同一部品を示す
。（ホ）はバンドパスフィルタ（２ｂ）より入力された
音声信号搬送波を増幅するための増幅器で、０１）は、
ＰＬＬ （ｌの中の電圧制御発振器００の出力と、増幅
器翰の出力信号を掛算するための掛算器である。FIG. 9 shows an embodiment of the present invention. In Figure 9, the first
The same numbers in the figures, FIG. 5, and FIG. 6 indicate the same parts. (E) is an amplifier for amplifying the audio signal carrier input from the bandpass filter (2b), and 01) is
This is a multiplier for multiplying the output of the voltage controlled oscillator 00 in the PLL (l) by the output signal of the amplifier.
チューナー（１）より出力された信号は、各々、第７図
と第８図に示される周波数特性を持つバンドパスフィル
タ（２ａ）と（２ｂ）により映像信号系と音声信号系に
分けられる。バンドパスフィルタ（２ａ）により音声信
号搬送波ｆｓが十分減衰させられた信号は増幅器（３）
で増幅され、位相比較器（９）と掛算器（５）とに入る
。位相比較器（９）は、電圧制御発振器ＯＱの出力と、
増幅器（３）の出力を位相比較し、ローパスフィルタα
つに出力し、ローパスフィルタ０］）の出力電圧によす
電圧制御発振器００の発振周波数を変化させる。このよ
うなＰＬＬ Ｏａの働きにより、電圧制御発振器００の
出力は、増幅器（３）の出力の映像信号搬送波ｆｐと、
一定位相、同一周波数になる。掛算器（５）は、増幅器
（３）の出力と電圧制御発振器０１の出力を同期検波し
て端子（６）に映像出力を出す。一方バンドパスフィル
タ（２ｂ）により出力された音声信号搬送波ｆｓは、増
幅器翰により増幅される。掛算器１ｊｌ）は、増幅器（
１）の出力と、電圧制御発振器ａ０の出力とを掛算し、
それらの差の周波数成分、すなわちＳＩＦ信号が端子（
６ａ）に得られる。The signals output from the tuner (1) are divided into a video signal system and an audio signal system by bandpass filters (2a) and (2b) having frequency characteristics shown in FIGS. 7 and 8, respectively. The signal whose audio signal carrier fs has been sufficiently attenuated by the bandpass filter (2a) is sent to the amplifier (3).
The signal is amplified by the phase comparator (9) and multiplier (5). The phase comparator (9) is connected to the output of the voltage controlled oscillator OQ,
The output of the amplifier (3) is phase-compared, and the low-pass filter α
The oscillation frequency of the voltage controlled oscillator 00 is changed depending on the output voltage of the low-pass filter 0]. Due to such a function of PLL Oa, the output of the voltage controlled oscillator 00 is the video signal carrier wave fp of the output of the amplifier (3),
Constant phase and same frequency. A multiplier (5) synchronously detects the output of the amplifier (3) and the output of the voltage controlled oscillator 01 and outputs a video output to a terminal (6). On the other hand, the audio signal carrier wave fs output by the bandpass filter (2b) is amplified by an amplifier. Multiplier 1jl) is an amplifier (
Multiply the output of 1) by the output of voltage controlled oscillator a0,
The frequency component of their difference, that is, the SIF signal, is the terminal (
6a).
以上のように本発明を用いれば、バンドパスフィルタ（
２ａ）で音声信号搬送波を減衰させたことにヨリ、９２
０ｋＩｈヒートを大幅に減らすことがで劃、又、ＰＬＬ
検波により直交歪の極めて少ない映像信号を得ることが
できる。またバンドパスフィルタ（２ｂ）で映像信号搬
送波を除去し、音声信号搬送波と電圧制御発振器員の出
力と掛算しているためバズが少ない。しかも、音声信号
搬送波ｆｓを減衰させていないので音声の信号／雑音比
が悪化しない。If the present invention is used as described above, the bandpass filter (
In addition to attenuating the audio signal carrier wave in 2a), 92
0kIh heat can be significantly reduced, and PLL
Through detection, a video signal with extremely low orthogonal distortion can be obtained. Furthermore, since the video signal carrier wave is removed by the band pass filter (2b) and the audio signal carrier wave is multiplied by the output of the voltage controlled oscillator, there is little buzz. Moreover, since the audio signal carrier wave fs is not attenuated, the audio signal/noise ratio does not deteriorate.
その上、チューナーの局部発振周波数がずれても、バン
ドパスフィルタ（２ａ）の帯域がバンドパスフィルタ（
２ｂ）の帯域に比べ広いので電圧制御発振器Ｃ１，）の
引込み範囲が、第６図のスプリットキャリア方式に比べ
て大きい。それゆえ、端子（６ａ）に出力されるＳＩＦ
信号も、チューナーの局部発振周波数のズレに対して強
いという効果がある。Moreover, even if the local oscillation frequency of the tuner shifts, the band of the band-pass filter (2a)
Since the band is wider than the band of 2b), the pull-in range of the voltage controlled oscillator C1,) is larger than that of the split carrier method shown in FIG. Therefore, the SIF output to terminal (6a)
The signal also has the effect of being resistant to deviations in the tuner's local oscillation frequency.
なお、上記実施例では、バンドパスフィルタ（２ｂ）の
周波数特性を第８図で説明したが、第１０図のように音
声に妨害を与えやすい映像成分を減衰させても同様の効
果が得られる。In the above embodiment, the frequency characteristics of the bandpass filter (2b) were explained using FIG. 8, but the same effect can be obtained by attenuating video components that tend to interfere with audio as shown in FIG. 10. .
第１図は、従来の擬似同期検波によるブロック回路図、
第２図はバンドパスフィルタの周波数特性を示す図、第
８図は買似同期検波の発展させたブロック回路図、第４
図はトラップの周波数特性図、第５図はＰＬＬを使った
同期検波回路を示すブロック回路図、第６図はスプリッ
トキャリア方式による検波回路を示すブロック回路図、
第７図はバンドパスフィルタの周波数特性図、第８図は
バンドパスフィルタ（２ｂ）の周波数特性図、第９図は
、本発明の一実施例を示すブロック回路図、第１０図は
本発明に用いるバンドパスフィルタの周波数特性の他の
例を示す図である。
図において、（１）はチューナー、（２）、 （２ａ
）、 （２ｂ ）はバンドパスフィルタ、（３） （４
） （１時（ホ）は増幅器、（５） （９） （１→Ｑ
◇は掛算器、（６）（６ａ ）は出力端子、（７）はト
ラップ、（８）は包絡線検波器、０１３．Ｏ’）は発振
器、０］）湖はローパスフィルタを示す。
なお、図中同一符号は同一または相当部分を示す。
代理人 葛野信−
第１図
第２図
第３図
第４図
第５図
第６図
第７図
第８図
第９図
第１０図
手続補正書（自発）
特許庁長官殿
１、事件の表示 特願昭５７−２０１８２２号２
、発明の名称
信号処理回路
３、補正をする者
事件との関係 特許出願人
住 所 東京都千代田区丸の内二丁目２番３号
名 称（６０１） 三菱電機株式会社代表者片山仁
八部
４、代理人
住 所 東京都千代田区丸の内二丁目２番３号
三菱電機株式会社内
５、補丁の対象
明細書の特許請求の範囲および発明の詳細な説明の欄６
、補正の内容
（１）明細書の特許請求の範囲を別紙のとおり訂正する
。
（２）明細書をつぎのとおり訂正する。
（２）
２、特許請求の範囲
（１）チューナーの出力端子に出力される信号のうち音
声信号搬送波を減衰して映像搬送波と色信号搬送波を通
す第１のバンドパスフィルタと、色信号搬送波と映像信
号搬送波の一部又は全部を減衰させ音声信号搬送波を通
す第２のバンドパスフィルタと、上記第１のバントパス
フィルタに接続された第１の増幅器と、上記第１の増幅
器の出力の映像信号搬送波と同一周波数で発振する電圧
制御発振器と、上２の増幅器と、上記電圧制御発振器の
出力と、上記第２の増幅器の出力とを掛算する掛算器と
を備えたことを特徴とする信号処理回路。
（２）前記電圧制御発振器の出力は、前記第１の増幅器
の出力の映像搬送波と同一周波数でかつ位相が一定であ
ることを特徴とする特許請求の範囲第１項記載の信号処
理回路。Figure 1 is a block circuit diagram of conventional pseudo-synchronous detection.
Figure 2 is a diagram showing the frequency characteristics of a bandpass filter, Figure 8 is a block circuit diagram of an advanced synchronous detection system, and Figure 4 is a diagram showing the frequency characteristics of a bandpass filter.
The figure is a frequency characteristic diagram of a trap, Figure 5 is a block circuit diagram showing a synchronous detection circuit using PLL, Figure 6 is a block circuit diagram showing a detection circuit using a split carrier method,
FIG. 7 is a frequency characteristic diagram of the band pass filter, FIG. 8 is a frequency characteristic diagram of the band pass filter (2b), FIG. 9 is a block circuit diagram showing an embodiment of the present invention, and FIG. 10 is a diagram of the present invention. FIG. 3 is a diagram showing another example of the frequency characteristics of a bandpass filter used in the present invention. In the figure, (1) is a tuner, (2), (2a
), (2b) are bandpass filters, (3) (4
) (1 o'clock (E) is the amplifier, (5) (9) (1→Q
◇ is a multiplier, (6) (6a) is an output terminal, (7) is a trap, (8) is an envelope detector, 013. O') is an oscillator, and 0]) is a low-pass filter. Note that the same reference numerals in the figures indicate the same or corresponding parts. Agent Makoto Kuzuno - Figure 1 Figure 2 Figure 3 Figure 4 Figure 5 Figure 6 Figure 7 Figure 8 Figure 9 Figure 10 Procedural amendment (voluntary) Commissioner of the Japan Patent Office 1, Indication of the case Patent Application No. 57-201822 2
, Name of the invention Signal processing circuit 3, Relationship to the case of the person making the amendment Patent applicant Address 2-2-3 Marunouchi, Chiyoda-ku, Tokyo Name (601) Mitsubishi Electric Corporation Representative Jinhachibe Katayama 4; Agent address: 5, Mitsubishi Electric Corporation, 2-2-3 Marunouchi, Chiyoda-ku, Tokyo, Column 6 for claims and detailed description of the invention in the subject specification of supplementary copy
, Contents of amendment (1) The scope of claims in the specification is corrected as shown in the attached sheet. (2) The specification shall be amended as follows. (2) 2. Claims (1) A first bandpass filter that attenuates the audio signal carrier of the signal output to the output terminal of the tuner and passes the video carrier and the color signal carrier; a second bandpass filter that attenuates part or all of the video signal carrier wave and passes the audio signal carrier wave; a first amplifier connected to the first bandpass filter; and an image of the output of the first amplifier. A signal comprising: a voltage controlled oscillator that oscillates at the same frequency as a signal carrier; a second amplifier; and a multiplier that multiplies the output of the voltage controlled oscillator by the output of the second amplifier. processing circuit. (2) The signal processing circuit according to claim 1, wherein the output of the voltage controlled oscillator has the same frequency and constant phase as the video carrier wave output from the first amplifier.
Claims (2)
声信号搬送波を減衰して映像搬送波と色信号搬送波を通
す第１のバンドパスフィルタと、色信号搬送波と映像信
号搬送波の一部又は全部を減衰させ音声信号搬送波を通
す第２のバンドパスフィルタと、上記第１のバンドパス
フィルタに接続された第１の増幅器と、上記第１の増幅
器の出力の映像信号搬送波と同一周波数で発振する電圧
制御発振器と、上記第２の帯域Ｐ波器に接続された第２
の増幅器と、上記電圧制御発振器の出力と、上記第２の
増幅器の出力とを掛算する掛算器とを備えたことを特徴
とする信号処理回路。(1) A first bandpass filter that attenuates the audio signal carrier of the signal output to the output terminal of the tuner and passes the video carrier and the color signal carrier; a second bandpass filter that attenuates and passes an audio signal carrier wave; a first amplifier connected to the first bandpass filter; and a voltage that oscillates at the same frequency as the video signal carrier output from the first amplifier. a controlled oscillator, and a second P-wave generator connected to the second band P-wave generator.
A signal processing circuit comprising: an amplifier; and a multiplier that multiplies the output of the voltage controlled oscillator by the output of the second amplifier.
の出力の映像搬送波と同一周波数でかつ位相が一定であ
ることを特徴とする特許請求の範囲第１項記載の信号処
理回路。(2) The signal processing circuit according to claim 1, wherein the output of the voltage controlled oscillator has the same frequency and constant phase as the video carrier wave of the output of the amplifier of the first tube.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57201322A JPS5990471A (en) | 1982-11-15 | 1982-11-15 | Signal processing circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57201322A JPS5990471A (en) | 1982-11-15 | 1982-11-15 | Signal processing circuit |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPS5990471A true JPS5990471A (en) | 1984-05-24 |
Family
ID=16439082
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP57201322A Pending JPS5990471A (en) | 1982-11-15 | 1982-11-15 | Signal processing circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS5990471A (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0715457A3 (en) * | 1994-11-30 | 1996-07-10 | Sony Corp |
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| JPH10220653A (en) * | 1997-02-02 | 1998-08-21 | Bridgestone Corp | Water and hot water supply hose |
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| JP2005146679A (en) * | 2003-11-17 | 2005-06-09 | Matsushita Electric Works Ltd | Private parts washing device |
| JP2006316607A (en) * | 2005-04-13 | 2006-11-24 | Inax Corp | Stainproof equipment and ultraviolet rays irradiation device |
| JP2012067442A (en) * | 2010-09-21 | 2012-04-05 | Toto Ltd | Sanitary washing device |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH057767U (en) * | 1991-02-22 | 1993-02-02 | 松下電工株式会社 | Local cleaning device |
| JPH09144110A (en) * | 1995-11-17 | 1997-06-03 | Matsushita Electric Ind Co Ltd | Sanitary washing device |
| JPH10220653A (en) * | 1997-02-02 | 1998-08-21 | Bridgestone Corp | Water and hot water supply hose |
| JP2001132057A (en) * | 1999-07-01 | 2001-05-15 | Toto Ltd | Nozzle-attached construction of washing device for private parts and private parts washing apparatus |
| JP2002206679A (en) * | 2001-01-11 | 2002-07-26 | Inax Corp | Hose assembly |
| JP2003213740A (en) * | 2002-01-16 | 2003-07-30 | Toto Ltd | Piping system |
| JP2004300864A (en) * | 2003-03-31 | 2004-10-28 | Toto Ltd | Exterior facing material and its munufacturing method |
| JP2005146679A (en) * | 2003-11-17 | 2005-06-09 | Matsushita Electric Works Ltd | Private parts washing device |
| JP2006316607A (en) * | 2005-04-13 | 2006-11-24 | Inax Corp | Stainproof equipment and ultraviolet rays irradiation device |
| JP2012067442A (en) * | 2010-09-21 | 2012-04-05 | Toto Ltd | Sanitary washing device |
| JP2013167061A (en) * | 2012-02-14 | 2013-08-29 | Toto Ltd | Toilet device |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0715457A3 (en) * | 1994-11-30 | 1996-07-10 | Sony Corp | |
| US5644368A (en) * | 1994-11-30 | 1997-07-01 | Sony Corporation | Composite signal detecting apparatus having associated filter |
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