JPS5842301A - Distributed constant filter - Google Patents
Distributed constant filterInfo
- Publication number
- JPS5842301A JPS5842301A JP14079481A JP14079481A JPS5842301A JP S5842301 A JPS5842301 A JP S5842301A JP 14079481 A JP14079481 A JP 14079481A JP 14079481 A JP14079481 A JP 14079481A JP S5842301 A JPS5842301 A JP S5842301A
- Authority
- JP
- Japan
- Prior art keywords
- lines
- adjacent
- line
- distributed constant
- capacitance
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/203—Strip line filters
- H01P1/2039—Galvanic coupling between Input/Output
Landscapes
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
Description
【発明の詳細な説明】 この発明はマイクロ波帯に使用されるフィンタ。[Detailed description of the invention] This invention is a finter used in the microwave band.
例えばマイクロ・ストリップ線路等の分布定数線路によ
って構成される楕円関数形の分布定数フィルタに関する
ものである。For example, the present invention relates to an elliptic function-type distributed constant filter constituted by a distributed constant line such as a microstrip line.
近年、マイクロ波帯のフィルタとして1例えば。In recent years, one example is a microwave band filter.
マイクロ・ストリップ線路等の分布定数線路が活用され
ている。この種のマイクロ・ストリップ線路は、これを
変形することによって等価的にリアクタンス素子が形成
され、そのリアクタンス素子の組合せによって選択度の
優れた楕円関数形分布定数フィルタの得られることがよ
く知られている。Distributed constant lines such as micro-strip lines are used. It is well known that by deforming this type of microstrip line, a reactance element is equivalently formed, and by combining the reactance elements, an elliptic function distributed constant filter with excellent selectivity can be obtained. There is.
第1図は、上記従来の方法によるマイクロ・ストリップ
線路に適用される楕円関数形低域通過フィルタの構造を
平面図によシ示したものである。FIG. 1 is a plan view showing the structure of an elliptic function low-pass filter applied to a microstrip line according to the above-mentioned conventional method.
図に於て、1は誘導電体基板、2,3.4は広幅線路、
5,6は狭幅線路、7,8は入出力線路である。図に示
すように広幅線路2.3.4と狭幅線路5.6は交互に
接続され、かつ互いに隣接した2個の広幅線路2と3及
び3と4は近接して配置されている。また1図には示し
ていないが、基板1の裏面には接地導体が存在する。也
のように構成することによシ、広幅線路2,3.4は並
列にキヤi?シタンスが、狭幅線路5,6は直列にイン
ダクタンスが挿入されたものと等価になる。更に、互に
隣接する2個の広幅線路2と3及び3と4が近接してい
るため、それぞれ2個の間に線路の電磁波進行方向の結
合によって生じる容量性の結合が存在し、これによって
直列にキャノ9シタンスが挿入されたものと等価になる
。In the figure, 1 is an inductive electric board, 2, 3.4 is a wide line,
5 and 6 are narrow lines, and 7 and 8 are input/output lines. As shown in the figure, the wide lines 2.3.4 and the narrow lines 5.6 are connected alternately, and two mutually adjacent wide lines 2 and 3 and 3 and 4 are arranged close to each other. Although not shown in FIG. 1, there is a ground conductor on the back surface of the substrate 1. By configuring it like this, the wide lines 2, 3, and 4 are connected in parallel. The narrow-width lines 5 and 6 are equivalent to having an inductance inserted in series. Furthermore, since the two adjacent wide lines 2 and 3 and 3 and 4 are close to each other, there is capacitive coupling between the two lines due to coupling in the direction of electromagnetic wave propagation. It is equivalent to inserting a cano-9 sitance in series.
第2図は、第1図の実施例の等価回路を示した図である
。上述で明らかなよりに、広幅線路2゜3.4はキャパ
シタシス13,14.15に、狭幅線路5,6はインダ
クタンス16.17に対応する。更に広幅線路2と3,
3と4の間に存在する結合容量はそれぞれキヤ/(’シ
タンス18.19に、入出力線路7,8は端子9,10
に、そして基板lの裏面の接地導体は端子11.12に
それぞれ対応する。このことから、第1図の分布定数フ
ィルタが、楕円関数形の低域通過フィルタを構成してい
ることが判る。FIG. 2 is a diagram showing an equivalent circuit of the embodiment of FIG. 1. As is clear from the above, the wide line 2°3.4 corresponds to the capacitor sis 13, 14.15, and the narrow line 5, 6 corresponds to the inductance 16.17. Furthermore, wide tracks 2 and 3,
The coupling capacitance existing between 3 and 4 is capacitance 18.19, and input/output lines 7 and 8 are connected to terminals 9 and 10
and the ground conductors on the back side of the substrate l correspond to terminals 11 and 12, respectively. From this, it can be seen that the distributed constant filter of FIG. 1 constitutes an elliptic function type low-pass filter.
上述のような楕円関数形低域通過フィルタを。An elliptic function low-pass filter as described above.
周波数が高い場合に適用する場合、線路の実現寸法に大
きさの面からの制限が加わシ、必要な周波数特性を得る
ことが困難になる。特に隣接する広幅線路2と3,3と
4の結合によるキャパシタンス18.19に関しては、
必要とする特性を得るためキャパシタンス18.19に
要求される値を得るには広幅線路2と3,3と4の間り
間隙を狭くしなければならないが、その間隙をある程度
以上狭くすることは実現上殆ど不可能である。例えば、
キャパシタンス18.19として、それに必要な大きさ
の容量を得る為、広幅線路2.3.4の対向幅を長くす
ることも考えられるが、キャパシタンス13.14.1
5が正しい値からずれてしまうことになり、使用にたえ
ない。このように。When applied to high frequencies, restrictions are imposed on the actual dimensions of the line, making it difficult to obtain the necessary frequency characteristics. Especially regarding the capacitance 18.19 due to the coupling between the adjacent wide lines 2 and 3, and 3 and 4,
In order to obtain the required value for capacitance 18.19 in order to obtain the required characteristics, the gaps between the wide lines 2 and 3, and between 3 and 4 must be narrowed, but it is not possible to narrow the gaps beyond a certain level. This is almost impossible in terms of implementation. for example,
In order to obtain the necessary capacitance for capacitance 18.19, it is possible to increase the facing width of wide line 2.3.4, but capacitance 13.14.1
5 will deviate from the correct value, making it unusable. in this way.
第1図のような分布定数フィルタを高い周波数に適用す
ると、キャパシタンス18.19が所要の値にならない
為、希望する阻止特性が得られなくなる。If a distributed constant filter as shown in FIG. 1 is applied to high frequencies, the capacitance 18.19 will not reach the required value, making it impossible to obtain desired blocking characteristics.
第3図は、上記従来のフィルタの周波数特性例を示した
グラフである。図に於・て、縦軸は通過減衰量、横軸は
周波数である。またf+が通過周波数で+fz〜f4は
2例えばhの高調波であシ、いずれも阻止されるべき周
波数域fある。ここで。FIG. 3 is a graph showing an example of the frequency characteristics of the conventional filter. In the figure, the vertical axis is the amount of passing attenuation, and the horizontal axis is the frequency. Further, f+ is a passing frequency, and +fz to f4 are harmonics of 2, for example, h, and there is a frequency range f in which all of them should be blocked. here.
実@20が、必要とされる特性を示している。しかしな
がら、上述したように高い周波数に於て第1図の低域通
過フィルタを使用すると、破線21のような特性になり
、被阻止周波数fv、f+では充分な減衰量を得ること
ができない。上記のような問題点は、マイクロ・ストリ
ップ線路以外の他の分布定数線路で楕円関数形フィルタ
を構成した場合でも全く同様である。Actual @20 shows the required properties. However, as described above, when the low-pass filter shown in FIG. 1 is used at high frequencies, the characteristics shown by the broken line 21 occur, and sufficient attenuation cannot be obtained at the blocked frequencies fv and f+. The above-mentioned problems are exactly the same even when an elliptic function filter is constructed using a distributed constant line other than a microstrip line.
この発明の目的は、上記のような問題点を解決する為、
高い周波数に適用して優れた選択度を備この発明の分布
定数フィルタは1等価的に分布定数線路にキヤ・ぐシタ
ンスが連列に挿入された容量性線路と1等価的にインダ
クタンスが直列に挿−人された誘導性線路とが交互に接
続され、かつ互いに隣接した2個の上記容量性線路が近
接して配置された構造を有し、その近接部分の形状が非
直線形状をなしていることを特徴とする。The purpose of this invention is to solve the above problems,
The distributed parameter filter of the present invention, which has excellent selectivity when applied to high frequencies, has a capacitive line in which a capacitance is inserted in series in a distributed constant line, and an inductance in series in an equivalent manner. It has a structure in which the inserted inductive lines are alternately connected, and the two capacitive lines adjacent to each other are arranged closely, and the shape of the adjacent part is non-linear. It is characterized by the presence of
以下この発明を、マイクロ・ストリップ線路に適用し、
第1図と同様に楕円関数形の低域通過フィルタを構成し
た場合の実施例につき1図面を参第4図は、この発明の
一実施例を示した平面図である。図に於て、第1図と同
一符号は同じ構造。Hereinafter, this invention will be applied to a micro strip line,
Refer to one drawing for an embodiment in which an elliptic function type low-pass filter is constructed in the same manner as in FIG. 1. FIG. 4 is a plan view showing an embodiment of the present invention. In the figure, the same symbols as in Figure 1 indicate the same structure.
機能を持つと理解されたい。22.23.24は広幅線
路である。広幅線路22,23.24に於て、隣接する
それぞれ2個の広幅線路22と23及び23と24の近
接部分が波形になっている。I want it to be understood as having a function. 22, 23, and 24 are wide lines. In the wide lines 22, 23, and 24, the proximate portions of the two adjacent wide lines 22 and 23 and 23 and 24 are corrugated.
この為、隣接するそれぞれ2個の線路22と23゜23
と24の電磁波進行方向の結合長を充分にとることがで
き、大きな結合が得られる。従って。For this reason, each of the two adjacent lines 22 and 23°23
A sufficient coupling length in the direction of electromagnetic wave propagation between and 24 can be obtained, and a large coupling can be obtained. Therefore.
キャパシタンス18.19として、必要な大きさの容量
が容易に得られる。一方、広幅線路22゜23.24の
幅の大きさにはl?!とんど変化がないので、キャパシ
タンス13,14.15の選定ニは影響はない。また、
上記互いに隣接した広幅線路22と23.23と24の
近接部分の波形の形状は、線路幅に較べて充分小さい一
為、線路の特性インピーダンス等の変化も無視できるほ
ど小さい。As a capacitance of 18.19, the required amount of capacitance can be easily obtained. On the other hand, the width of the wide line 22°23.24 is l? ! Since there is almost no change, the selection of capacitances 13, 14, and 15 has no effect. Also,
The shape of the waveform in the vicinity of the mutually adjacent wide lines 22 and 23, and 23 and 24 is sufficiently small compared to the line width, so that changes in the characteristic impedance of the line etc. are negligibly small.
従って、この実施例に見られる楕円関数形低域通過フィ
ルタの等価回路は、第2図と同じであり。Therefore, the equivalent circuit of the elliptic function low-pass filter seen in this embodiment is the same as that shown in FIG.
がiZlられる。それによって1周波数特性も第3図の
実線20のようになり、初期の目的を達成できる0
第5図は、この発明の他の実施例の構成を示した平面図
である。図に於いて、25,26.27は広幅線路であ
シ、隣接するそれぞれ2個の広幅線路25と26及び2
6と27の近接部分が凹凸形になっている。従って、こ
の実施例によれば。is iZl. As a result, the single frequency characteristic becomes like the solid line 20 in FIG. 3, and the initial objective can be achieved. FIG. 5 is a plan view showing the configuration of another embodiment of the present invention. In the figure, 25, 26, and 27 are wide lines, and two adjacent wide lines 25, 26, and 2 are connected to each other.
The adjacent portions of 6 and 27 are uneven. Therefore, according to this embodiment.
キャパシタンス18.19は第4図の実施例と庇べて一
層大きな値をもち、これによって、更に特性の巾広い要
求に応することができる。The capacitances 18 and 19 have a larger value than in the embodiment shown in FIG. 4, thereby making it possible to meet demands for a wider range of characteristics.
上記第1および第2の実施例においては、隣接するそれ
ぞれ2個の広幅線路の近接部分の形状が波形の場合と凹
凸形の場合を例にとって説明したが、その近接部分の形
状がそれら以外の他の非直線形状をなしている場合に於
ても1本実施例の場合と全く同様の効果が得られること
は勿論である1また。この発明の実施例としてマイクロ
・ストリップ線路を用いた場合を例にとって説明したが
他の分布定数線路でフィルタを構成する場合に於ても、
楕円関数形のフィルタを構成している限り。In the first and second embodiments described above, the cases where the shape of the adjacent portions of two adjacent wide lines are wavy and the shape of convexes and convexes are explained as examples. It goes without saying that the same effects as in the present embodiment can also be obtained with other non-linear shapes. Although the embodiment of this invention has been explained using a micro-strip line as an example, it is also possible to construct a filter using other distributed constant lines.
As long as you are constructing an elliptic function filter.
全く同様の効果が得られることも明白である。上記他の
分布定数線路としては1例えば、トリプレート線路やス
ロットラインが考えられ、また、広幅線路として太い金
属棒、狭幅線路として金属線を用いることができる。It is also clear that exactly the same effect can be obtained. For example, a triplate line or a slot line can be considered as the other distributed constant line, and a thick metal rod can be used as the wide line, and a metal wire can be used as the narrow line.
尚、上記実施例においては、広幅線路3個、狭幅線路2
個で構成されるフィルタを例にとって説明らかである。In the above embodiment, three wide lines and two narrow lines are used.
The explanation is clear by taking a filter made up of two as an example.
以上の説明で明らかなように、この発明による分布定数
フィルタは、高い周波数に適用して優れp た選択度
を備え、かつ阻止域に於ても充分な減衰量が得られるの
で、よシ周波数の高いマイクロ波帯の回路に適用してそ
の性能を向上すべく得られる効果は大きい。As is clear from the above explanation, the distributed constant filter according to the present invention has excellent selectivity when applied to high frequencies, and also provides sufficient attenuation in the stop band. When applied to circuits in the high microwave band, the effect of improving their performance is significant.
第1図は従来の分布定数フィルタの構成例を示す平面−
1第2図は、第1図の従来例の等何回路。
第3図は、第1図の従来例の周波数特性図、第4図はこ
の発明による一実施例の構成を示す平面図。
第5図はこの発明の他の実施例の構成を示す平面図であ
る。
図に於て、1は誘電体基板、 2 、3 、4 、22
゜23.24.25.26.27は広幅線路、5゜6は
狭幅線路、’7 、8は入出力線路、9.10は入出力
端子、11.12は接地端子、13,14゜15.18
.19はキャパシタンス、16.17はインダクタンス
である。
」
第1図
竿2凶
周波数
第3図
第4図
第5図Figure 1 is a plane showing an example of the configuration of a conventional distributed constant filter.
1. Figure 2 shows the conventional circuit shown in Figure 1. 3 is a frequency characteristic diagram of the conventional example shown in FIG. 1, and FIG. 4 is a plan view showing the configuration of an embodiment according to the present invention. FIG. 5 is a plan view showing the configuration of another embodiment of the invention. In the figure, 1 is a dielectric substrate, 2, 3, 4, 22
゜23.24.25.26.27 are wide lines, 5゜6 are narrow lines, '7 and 8 are input/output lines, 9.10 are input/output terminals, 11.12 are ground terminals, 13, 14゜15.18
.. 19 is a capacitance, and 16.17 is an inductance. ” Figure 1 Rod 2 Bad Frequency Figure 3 Figure 4 Figure 5
Claims (1)
に挿入された容量性線路と1等価的にインダクタンスが
直列に挿入された誘導性線路とが交互に接続され、かつ
互いに隣接した2個の前記容量性線路が近接して配置さ
れてなる分布定数フィルタに於いて、前記近接部分の形
状が非直線形状をなしていることを特徴とする分布定数
フィルタ。1. Equivalently to the distributed constant line! Capacitive lines in which capacitances are inserted in parallel and inductive lines in which inductances are equivalently inserted in series are alternately connected, and the two capacitive lines adjacent to each other are arranged closely. A distributed constant filter characterized in that the shape of the adjacent portion is non-linear.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP14079481A JPS5842301A (en) | 1981-09-07 | 1981-09-07 | Distributed constant filter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP14079481A JPS5842301A (en) | 1981-09-07 | 1981-09-07 | Distributed constant filter |
Publications (1)
Publication Number | Publication Date |
---|---|
JPS5842301A true JPS5842301A (en) | 1983-03-11 |
Family
ID=15276888
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP14079481A Pending JPS5842301A (en) | 1981-09-07 | 1981-09-07 | Distributed constant filter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS5842301A (en) |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5055809A (en) * | 1988-08-04 | 1991-10-08 | Matsushita Electric Industrial Co., Ltd. | Resonator and a filter including the same |
JPH066110A (en) * | 1992-06-16 | 1994-01-14 | Nippon Dengiyou Kosaku Kk | Branching filter |
US5955931A (en) * | 1995-01-09 | 1999-09-21 | Murata Manufacturing Co., Ltd. | Chip type filter with electromagnetically coupled resonators |
JP2000022480A (en) * | 1998-06-29 | 2000-01-21 | Taiyo Yuden Co Ltd | Laminated filter |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS4829174A (en) * | 1971-08-19 | 1973-04-18 | ||
JPS5494258A (en) * | 1978-01-09 | 1979-07-25 | Nec Corp | High frequency filter |
-
1981
- 1981-09-07 JP JP14079481A patent/JPS5842301A/en active Pending
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS4829174A (en) * | 1971-08-19 | 1973-04-18 | ||
JPS5494258A (en) * | 1978-01-09 | 1979-07-25 | Nec Corp | High frequency filter |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US5055809A (en) * | 1988-08-04 | 1991-10-08 | Matsushita Electric Industrial Co., Ltd. | Resonator and a filter including the same |
JPH066110A (en) * | 1992-06-16 | 1994-01-14 | Nippon Dengiyou Kosaku Kk | Branching filter |
US5955931A (en) * | 1995-01-09 | 1999-09-21 | Murata Manufacturing Co., Ltd. | Chip type filter with electromagnetically coupled resonators |
JP2000022480A (en) * | 1998-06-29 | 2000-01-21 | Taiyo Yuden Co Ltd | Laminated filter |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US5357227A (en) | Laminated high-frequency low-pass filter | |
EP0444948A2 (en) | Dielectric resonator and a filter using same | |
JPH07273502A (en) | Low pass filter | |
JPS63258101A (en) | Microwave filter | |
JPS6284601A (en) | Ultra high frequency band filter | |
US6323745B1 (en) | Planar bandpass filter | |
US4114120A (en) | Stripline capacitor | |
EP0438149B1 (en) | Dielectric filter with attenuation poles | |
US4011528A (en) | Semi-lumped element coupler | |
US5136269A (en) | High-frequency band-pass filter having multiple resonators for providing high pass-band attenuation | |
US5376908A (en) | Interdigital strip line filter having a plurality of different width resonant electrodes | |
US4288761A (en) | Microstrip coupler for microwave signals | |
JPS5842301A (en) | Distributed constant filter | |
US6762660B2 (en) | Compact edge coupled filter | |
KR100392341B1 (en) | Band pass filter using DGS | |
KR20210021736A (en) | Low pass filter with transmission zero | |
EP1806841A2 (en) | Resonant circuit, filter circuit, and multilayered substrate | |
US6194981B1 (en) | Slot line band reject filter | |
JP5454222B2 (en) | Low pass filter | |
KR102054503B1 (en) | Band pass filter and design method thereof | |
Rius et al. | Theoretical and experimental study of various types of compensated dielectric bridges for millimeter-wave coplanar applications | |
JPH0671162B2 (en) | Micro strip band pass filter | |
US5317291A (en) | Microstrip filter with reduced ground plane | |
WO1999018630A9 (en) | Slot line band pass filter | |
CN115412043B (en) | Symmetrical lumped parameter low-pass filter for improving far-end rejection performance |