JPS5812022A - Phase controlling circuit - Google Patents
Phase controlling circuitInfo
- Publication number
- JPS5812022A JPS5812022A JP9274081A JP9274081A JPS5812022A JP S5812022 A JPS5812022 A JP S5812022A JP 9274081 A JP9274081 A JP 9274081A JP 9274081 A JP9274081 A JP 9274081A JP S5812022 A JPS5812022 A JP S5812022A
- Authority
- JP
- Japan
- Prior art keywords
- trigger
- resistor
- voltage
- control element
- capacitor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M5/25—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M5/257—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Electrical Variables (AREA)
Abstract
Description
【発明の詳細な説明】
本発明は、位相制御出力を出力する操作部により制御す
る位相制御回路に関するもので、その目的とするところ
は、主制御素子の半波完全導通による誤動作を防止する
とともに操作部の位相制御角を調整する可蜜抵抗の回転
角と負荷の位相制御出力との関係ｔ［４！的に費化でき
るようにして使用勝手を向上することにある。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a phase control circuit that is controlled by an operation unit that outputs a phase control output, and its purpose is to prevent malfunctions due to half-wave complete conduction of a main control element, and to Relationship between the rotation angle of the flexible resistor that adjusts the phase control angle of the operating unit and the phase control output of the load t[4! The objective is to improve usability by making it more cost effective.
従来の位相制御回路は、第１図のように、制御素子Ｑ４
により位相制御出力を出力する抄作部口）と制御部（り
′とにより構成され、制御部１！１′は負荷（３）に主
制御素子Ｑ、を直列接続して位相制御するようにし、操
作部（りの出力により抵抗Ｒ８を介して充電されるトリ
ガコニ／９−ＪすＣの充電電圧によりトリガ素子ＴＶ）
リガして補助制御素子Ｑ、ｔオシにし、補助制御素子Ｑ
、に直列接続した抵抗Ｒ１の両喘會主制御素子Ｑ、のゲ
ート、Ｔ、電極間に接続して主制御素子Ｑｍｔ位相制御
するようにしていた。（４＋は補助制卿素子９１に電圧
を印加するためのトラシスであり、（Ｉｌは電源である
。The conventional phase control circuit has a control element Q4 as shown in FIG.
The main control element Q is connected in series to the load (3) and the control part 1!1' is configured to perform phase control. , operation unit (trigger element TV charged by the charging voltage of the trigger controller/9-JSC charged via the resistor R8 by the output of the trigger)
Trigger and set the auxiliary control element Q and t to the auxiliary control element Q.
, the resistor R1 is connected in series between the gate, T, and electrode of both the main control elements Q, so as to control the phase of the main control element Qmt. (4+ is a trasis for applying voltage to the auxiliary control element 91, (Il is a power supply.
今、第２図（ａ）のような電源（５）の電圧、を印加し
、トリガ素子Ｔ、にトリガして補助制御素子Ｑ＋にオシ
すると抵抗Ｒ１の両端に第２図（ｂ）の電圧ｖＲ１が生
じて主制御素子Ｑ律オンにする。この電圧ＶＲｌは電源
電圧が０になるまでは図示のように電位が残っているた
め、トリガコシデシサＣの電位はトリガ素子Ｔのオシ電
圧ｖｓ、補助制御素子Ｑ１のゲート、Ｔ、電極間電圧、
および抵抗Ｒ１の電圧ＶＲ，の和の電圧＝最毒着４−−
−４→鴫４■μｍが存在する。その後、電源ＩＩＩが反
転又は補助制御素子Ｑｓの電流が保持電流以下になって
補助制御素子Ｑｔがオフになると、補助制御素子Ｑ１の
アノード電流による抵抗Ｒ１の電圧降下分がなくなり、
トリガコシデシサＣの電荷は第２図（ｅ）のように微弱
な電流として放電される。この電流により電源（藝）の
反転後のサイクシで補助制御素子Ｑ１を全導通させてし
まい、抵抗Ｒ３の両端の電圧ＶＲ，は第２ｅＶ（ｄ）の
ようになって主制御素子Ｑｌも中波全導通になり、負荷
Ｉｌｌは非対称制御されることになる。したがって、負
荷（３）が照明装置の場合、ちらつきが生じるという欠
点を有していた。又、操作部（１）Ｋよ鉄負荷（１１’
を調光する場合には、操作部（１）の可変抵抗ＶＲに対
する光出力が第３図のように８字カーブとなり、操作性
が悪いという欠点を有していた。Now, when the voltage of the power supply (5) as shown in Fig. 2(a) is applied and the trigger element T is triggered and the auxiliary control element Q+ is turned on, the voltage shown in Fig. 2(b) is applied across the resistor R1. vR1 occurs and turns on the main control element Q-rhythm. Since this voltage VRl remains at a potential as shown in the figure until the power supply voltage becomes 0, the potential of the trigger cosidecisor C is the oscillator voltage vs of the trigger element T, the gate of the auxiliary control element Q1, the inter-electrode voltage,
and the voltage VR of the resistor R1, the sum of the voltages = the most poisonous point 4--
-4 → 4μm exists. After that, when the power supply III is reversed or the current of the auxiliary control element Qs becomes less than the holding current and the auxiliary control element Qt is turned off, the voltage drop across the resistor R1 due to the anode current of the auxiliary control element Q1 disappears.
The charge of the trigger sensor C is discharged as a weak current as shown in FIG. 2(e). This current makes the auxiliary control element Q1 fully conductive after the power supply is reversed, and the voltage VR, across the resistor R3 becomes 2 eV (d), and the main control element Ql also becomes medium-wavelength. Full conduction will occur, and the load Ill will be asymmetrically controlled. Therefore, when the load (3) is a lighting device, there is a drawback that flickering occurs. In addition, the operating part (1) K and the iron load (11'
When controlling the light, the light output to the variable resistor VR of the operating section (1) forms a figure-eight curve as shown in FIG. 3, which has the drawback of poor operability.
本発明はかかる点に鑑みてなされたもので、以下実施例
によシ詳細に説明する。The present invention has been made in view of this point, and will be explained in detail below using examples.
第４図において、（１）は操作部、（！）は制御部で、
トランス（４）の２次側に抵抗Ｒｓとトリガコンデシサ
Ｃとの直列回路管接続し、トリ力コシデンサＣに並゛列
に補助制御素子Ｑ１と抵抗Ｒ１の直列回路を接続し、補
助制御素子Ｑ１のゲートと抵抗Ｒ３の一噛との間にトリ
ガ素子ＴＶ接続しておく、トリガ素子Ｔのトリガ電圧は
トラシス（４）の２次電圧の波高値より高くしておく、
操作部（１）の出力を抵抗Ｒｔｒ介してトリガコシヂシ
サＣに接続してオく。In Fig. 4, (1) is the operation section, (!) is the control section,
A series circuit tube of a resistor Rs and a trigger capacitor C is connected to the secondary side of the transformer (4), and a series circuit of an auxiliary control element Q1 and a resistor R1 is connected in parallel to the trigger capacitor C. Trigger element TV is connected between the gate of Q1 and one end of resistor R3.The trigger voltage of trigger element T is set higher than the peak value of the secondary voltage of transmission (4).
The output of the operating section (1) is connected to a trigger sensor C via a resistor Rtr.
今、負荷（３）にランプを使用し、電源（６）に接続さ
れた操作部口）からは可変抵抗ＶＲとコシデシサＣＩと
スイッチシフ素子ＱｓＫよって決まる位相角で制御素子
Ｑ、が点弧され、制御部１りには可変抵抗ＶＲの値が大
きく、ランプ（負荷（ｉ））が暗く調光されたときには
第５図（ｂ）のような出力電圧ｖｓが与えられ、又、可
変抵抗ＶＲの値が小さく、明るく点灯するときには第５
図（ｅ）のような出力電圧ｖｓが与えられる。尚、第５
図（＆）は電源偵）の電圧波形である。このとき、繰作
５１１）の可、臂抵抗ＶＲの値【同じ値だけ蜜化させる
と、通常、第５ ’Ｗ （ｂ） 、 （ｃ）の（イ）、
（Ｑ）のようにその時間軸の変化中が同じになるため
、第５図ｒｂ＞の場合の電圧変化分は第５因（ｅ）の場
合の電圧変化分より大きくなる。しかるに、制御部偉）
はトうシス（４）の２次電圧Ｖ、によりトリガコシダシ
サＣは、抵抗Ｒｓ′ｇｒ介してトリガ素子Ｔのトリカガ
コンデンサＣには前述のように、第５図（ｅ）のような
電圧ＶＣが存在する０点弧角θ１より少し遅ｎた点で補
助制御素子Ｑ１が点弧するから、その時点で低くなり、
トリガ素子Ｔのオシ電圧ＶｏＮとなる、このとき、実際
には操作部１１＋からの出力電圧Ｖ。Now, using a lamp as the load (3), the control element Q is ignited from the operating part port connected to the power supply (6) at a phase angle determined by the variable resistor VR, cosidecisor CI, and switch shift element QsK. , the value of the variable resistor VR is large in the control unit 1, and when the lamp (load (i)) is dimmed, the output voltage vs as shown in FIG. 5(b) is given, and the variable resistor VR When the value of is small and the light is lit brightly, the fifth
An output voltage vs as shown in figure (e) is given. Furthermore, the fifth
The figure (&) is the voltage waveform of the power supply. At this time, the value of the arm resistance VR of the repetition 511) [If the same value is condensed, normally the 5th W (b), (c) (a),
Since the changes in the time axis are the same as in (Q), the voltage change in the case of rb> in FIG. 5 is larger than the voltage change in the case of the fifth factor (e). However, the control department
Due to the secondary voltage V of the output system (4), the trigger voltage sensor C generates a voltage VC as shown in FIG. 5(e) to the trigger capacitor C of the trigger element T via the resistor Rs'gr. Since the auxiliary control element Q1 fires at a point a little later than the zero firing angle θ1 at which
At this time, the oscillation voltage VoN of the trigger element T is actually the output voltage V from the operating section 11+.
により第５図（ｆ）のように点弧角＃１から破線のよう
にＶｃは急激に上昇し、トリガ素子Ｔのトリガ電圧ＶＢ
Ｏに達すると、トリガ素子Ｔがオンし、電荷を放出して
前述のＶＯＲに落ちつく、シたがって、補助制御素子Ｑ
１は位相角α１で点弧し、主制御素子Ｑ、も同時に点弧
してランプ（負荷（Ｓ））は暗（調光点灯する。電＃（
ｉ）の半サイクルが終り、逆向きの半サイクルになると
、ＶＣはその半サイクル中、抵抗Ｒ１の電圧降下とは関
係なしにトリガ素子ＴのＶｏｌｔで低下しており、その
値は殆んどＯｖであり、補助制御素子Ｑｌのゲートトリ
ガ電流が流れることなく、正常に途切れてトリガコシデ
シサＣは逆方向に充電を始めることに’＆り、ちらつき
がなくなる。As a result, as shown in FIG. 5(f), Vc rises rapidly from firing angle #1 as shown by the broken line, and the trigger voltage VB of the trigger element T increases.
0, the trigger element T turns on, discharges the charge and settles at the aforementioned VOR, therefore, the auxiliary control element Q
1 is lit at a phase angle α1, the main control element Q is also lit at the same time, and the lamp (load (S)) is dimmed (lit.
When the half cycle of i) ends and the reverse half cycle begins, VC has decreased by the Volt of the trigger element T during that half cycle, regardless of the voltage drop of the resistor R1, and its value is almost Ov, the gate trigger current of the auxiliary control element Ql does not flow and is interrupted normally, and the trigger detector C starts charging in the reverse direction, and the flicker disappears.
つぎに、第５図（ｇ）のように、操作部＋１１の出力電
圧Ｖ、の点弧角θ、が小さいとき、トリ力コシデシサＣ
の電圧Ｖｃは第５図（転）のように、トラシス（４）の
２次電圧ｖＩによ−る充電分は低く、Ｖ＋とｖ、、の合
成によるＶｃの波形はｖｓのθ■付近の瞬時電圧も低い
次め、第５図（１）の破線のようにゆるやかな立上りを
有しており、位相角α８で補助制御素子Ｑ、およ、び主
制御素子Ｑｚが点弧する。したがって、α１−θ〈α■
−＃１の関係が成立ち、操作ｆｉＡ＋１１での点弧角が
小さいときは主制御素子Ｑ、の点弧費化分は大きく、操
作部（１）の点弧位相角が９００付近では主制御素子Ｑ
１の点弧費化分は小さく、又、１５０°付近でも主制御
素子Ｑｍの変化分は大きくなる。以上によりラシプ（９
Ｉｉ荷（３））の調光特性は第６図のように直線的な調
光特性を示し、可賢抵抗ＶＲの回転角と光出力が比例し
て操作が容易になる。Next, as shown in FIG. 5(g), when the firing angle θ of the output voltage V of the operating part +11 is small,
As shown in Fig. 5 (translation), the voltage Vc is charged by the secondary voltage vI of the transmission (4) is low, and the waveform of Vc due to the combination of V+ and v is around θ■ of vs. Since the instantaneous voltage is low, it has a gradual rise as shown by the broken line in FIG. 5(1), and the auxiliary control element Q and the main control element Qz are fired at a phase angle α8. Therefore, α1−θ〈α■
-#1 relationship is established, when the firing angle at the operation fiA+11 is small, the starting cost of the main control element Q is large, and when the firing phase angle of the operation part (1) is around 900, the main control element Element Q
The ignition cost of 1 is small, and the change in main control element Qm becomes large even near 150°. As a result of the above, Lasip (9
The dimming characteristic of item Ii (3)) shows a linear dimming characteristic as shown in FIG. 6, and the rotation angle of the flexible resistor VR is proportional to the light output, making the operation easy.
第７図は本発明の他の実施例で、トランス（４）の２次
側に抵抗ＲｓとトリガコンデンサＣの直列回路を接続し
、トリガコンデンサＣに並列にトリガ素子Ｔと主制御素
子Ｑ、のゲート、ＴＩ電極を接続し、操作部（１）の出
力で抵抗Ｒｍｋ介してトリガコンデンサＣに充電するよ
うにしたもので、トリガ素子Ｔのトリガ電圧はトラシス
＋４１の２次電圧により充電格れるトリガコンデンサＣ
の電圧Ｖｃより高くし′Ｃシ＜、シたがって、トラシス
（４）の２次電圧によりトリガコンデンサＣにトリガ素
子Ｔのトリガ電圧ＶＢＯより低い電圧まで充電し、操作
部（１１の出力電圧Ｖ、により抵抗Ｒ１ｋ通してトリガ
コニ／Ｊ５！−Ｊ寸Ｃ１に充電させ、前述のＶＢＯに達
せしめて負荷（組の電圧変化分を前述の第４図のものと
同様に直線的にできる。FIG. 7 shows another embodiment of the present invention, in which a series circuit of a resistor Rs and a trigger capacitor C is connected to the secondary side of a transformer (4), and a trigger element T and a main control element Q are connected in parallel to the trigger capacitor C. The gate and TI electrodes are connected, and the output of the operating section (1) charges the trigger capacitor C via the resistor Rmk, and the trigger voltage of the trigger element T is charged by the secondary voltage of trasis +41. Trigger capacitor C
Therefore, the secondary voltage of the transmission (4) charges the trigger capacitor C to a voltage lower than the trigger voltage VBO of the trigger element T, and the output voltage V of the operating section (11) is increased. , through the resistor R1k to charge the trigger voltage /J5!-J dimension C1 to reach the above-mentioned VBO, and the voltage change of the load (set) can be made linear as in the case of Fig. 4 above.
第８図は、第１図に示す従来例の補助制御素子Ｑ１のゲ
ートとトリガコンデンサＣの負端子との間に抵抗Ｈａｉ
ｒ接続したものである。このものにあっては、トリガコ
ンデンサＣの放電は、トリガ素子Ｔおよび抵抗Ｒ，の直
列回路のシーづと、トリカ累子Ｔ、補助制御嵩子Ｑ１の
ゲート、Ｔ８電極および抵抗Ｒ１の直列回路のループと
に分力ζｎる。抵抗Ｒ８を通って放電する場合、補助制
御素子Ｑ、のアノード電流による電圧降下が抵抗Ｒ，の
両端には発生しないので、電源（−）の反転によりゲー
トトリガ電流が次のサイクルへ流ｎ込むことがなく、補
助制御素子Ｑ１および主制御素子Ｑｍの誤動作、即ち、
半波全導通音完全に防止できる。FIG. 8 shows a resistor Hai connected between the gate of the auxiliary control element Q1 and the negative terminal of the trigger capacitor C in the conventional example shown in FIG.
r connection. In this case, the discharge of the trigger capacitor C is caused by the series circuit of the trigger element T and the resistor R, the trigger resistor T, the gate of the auxiliary control element Q1, the T8 electrode, and the series circuit of the resistor R1. The component force ζn is in the loop. When discharging through the resistor R8, the voltage drop due to the anode current of the auxiliary control element Q does not occur across the resistor R, so the gate trigger current flows into the next cycle due to the reversal of the power supply (-). There is no malfunction of the auxiliary control element Q1 and the main control element Qm, that is,
Half-wave full conduction sound can be completely prevented.
叙上のように本発明は、１次側ｔ−１１８に接続されト
リガ素子のトリガ電圧より低い２次電圧を出力するトラ
シスの２次側を抵抗を介してトリガコンデンサに接続し
たから、主制御素子の半波完全導通による誤動作會防止
できる上％操作部の位相制御角を調整する可愛抵抗の回
転角と負荷の位相制御出力との関係管直綜的に費化でき
るようにできて使い勝手を向上でき、又、補助制御素子
のゲートとトリガコンデンサの負端子との間に抵抗會接
続したから、主制御素子の半波完全導通による誤動作を
防止できるという効果ヲ実するものである。As described above, in the present invention, the secondary side of the trasys, which is connected to the primary side t-118 and outputs a secondary voltage lower than the trigger voltage of the trigger element, is connected to the trigger capacitor via a resistor. The half-wave complete conduction of the element prevents malfunctions.The relationship between the rotation angle of the resistor and the phase control output of the load adjusts the phase control angle of the operating section.The relationship between the rotation angle of the resistor and the phase control output of the load can be directly calculated for ease of use. Furthermore, since a resistor is connected between the gate of the auxiliary control element and the negative terminal of the trigger capacitor, malfunctions due to half-wave complete conduction of the main control element can be prevented.
第１図は従来の位相制御回路の回路図、第２図（＆）〜
（ｄ）は同上の要部電圧電流波形図、第３因は同上の特
性図、第４図は本発明の一実施例の回路図、第！Ｓ図（
ａ）〜（１）は同上の要部電圧波形内、第６図は同上の
特性図、第７図および第８図はそれぞｎ本発明の他の実
施例の回路図である。
１１）・・・操作部、 １１１・・・制御部、（３）・
・・負荷、（４）・・・トラシスｓ Ｑ＋・・・補助制
御素子、Ｑ、・・・主制御素子、Ｃ・・・トリガコンデ
ンサ、Ｔ・・・トリガ素子％ Ｒａ・・・抵抗、Ｒ６・
・・抵抗。
代理人 弁理士 石 １）長 七Figure 1 is a circuit diagram of a conventional phase control circuit, Figure 2 (&) ~
(d) is the main voltage and current waveform diagram of the same as above, the third factor is the characteristic diagram of the same as above, and FIG. 4 is a circuit diagram of an embodiment of the present invention. S diagram (
a) to (1) are voltage waveforms of the main parts of the same as above, FIG. 6 is a characteristic diagram of the same as above, and FIGS. 7 and 8 are circuit diagrams of other embodiments of the present invention. 11)...Operation unit, 111...Control unit, (3).
... Load, (4) ... Trasis s Q+ ... Auxiliary control element, Q, ... Main control element, C ... Trigger capacitor, T ... Trigger element % Ra ... Resistance, R6・
··resistance. Agent Patent Attorney Ishi 1) Choshichi
Claims (1)
部のトリガコンデンサ會充電し、前記トリガコンデンサ
の充電電圧によりトリガ素子をトリガして主制御素子を
オシせしめ、前記主制御素子により負荷を位相制御する
如くした位相制御回路において、１次側を電源に接続さ
れトリガ素子のトリガ電圧より低い２次電圧を出力する
トラシスの３次側を抵抗を介して前記トリガコンデンサ
に接続して成ることを特徴とする位相制御回路。 悸） 位相制御出力を出力する操作部の出力により制御
部のトリガコンデンサを充電し、前記トリガコンデンサ
の充電電圧によりトリガ素子をトリガして補助制御素子
を介して主制御素子をオンせしめ、前記主制御素子によ
り負荷を位相制御する如くした位相制御回路において、
補助制御素子のゲートとトリガコンデンサの負端子との
間に抵抗ｔ−接続して成ることを特徴とする位相制御回
路。(1) The trigger capacitor of the control unit is charged by the output of the operation unit that outputs the phase control output, the trigger element is triggered by the charging voltage of the trigger capacitor, and the main control element is turned on, and the load is controlled by the main control element. In a phase control circuit that performs phase control, the tertiary side of a trasys whose primary side is connected to a power source and which outputs a secondary voltage lower than the trigger voltage of the trigger element is connected to the trigger capacitor via a resistor. A phase control circuit featuring: A trigger capacitor of the control unit is charged by the output of the operation unit that outputs the phase control output, and the charging voltage of the trigger capacitor triggers the trigger element to turn on the main control element via the auxiliary control element. In a phase control circuit in which the phase of a load is controlled by a control element,
A phase control circuit comprising a resistor T-connected between the gate of the auxiliary control element and the negative terminal of the trigger capacitor.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP9274081A JPS5812022A (en) | 1981-06-15 | 1981-06-15 | Phase controlling circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP9274081A JPS5812022A (en) | 1981-06-15 | 1981-06-15 | Phase controlling circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5812022A true JPS5812022A (en) | 1983-01-24 |
| JPH0321925B2 JPH0321925B2 (en) | 1991-03-25 |
Family
ID=14062807
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP9274081A Granted JPS5812022A (en) | 1981-06-15 | 1981-06-15 | Phase controlling circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS5812022A (en) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5074159A (en) * | 1973-10-29 | 1975-06-18 | ||
| JPS5120752U (en) * | 1974-07-31 | 1976-02-16 | ||
| JPS5268947A (en) * | 1975-12-05 | 1977-06-08 | Matsushita Electric Ind Co Ltd | Remote control apparatus |
| JPS5313066U (en) * | 1976-07-14 | 1978-02-03 |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5313066B2 (en) * | 1973-07-02 | 1978-05-08 |
-
1981
- 1981-06-15 JP JP9274081A patent/JPS5812022A/en active Granted
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5074159A (en) * | 1973-10-29 | 1975-06-18 | ||
| JPS5120752U (en) * | 1974-07-31 | 1976-02-16 | ||
| JPS5268947A (en) * | 1975-12-05 | 1977-06-08 | Matsushita Electric Ind Co Ltd | Remote control apparatus |
| JPS5313066U (en) * | 1976-07-14 | 1978-02-03 |
Also Published As
| Publication number | Publication date |
|---|---|
| JPH0321925B2 (en) | 1991-03-25 |
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