JPH10322136A - High-frequency circuit - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a high-frequency circuit in which circuit constitution is simple, and frequency characteristic is high. SOLUTION: A Wilkinson-type amplifier 15 is constituted of a Wilkinson-type distributor/synthesizer 4 for distributing an input signal with the same phase, and outputting a distributed signal, unit amplifiers 12a and 12b for amplifying the distributed signal, and outputting an amplified signal, Wilkinson-type distributor/synthesizer 5 for synthesizing the two amplified signals with the same phase, and outputting it, DC bias supplying circuit 9 for supplying a DC bias through the Wilkinson-type distributor/synthesizer 4 to the bases of transistors 1a and 1b, DC bias supplying circuit 10 for supplying DC bias through the Wilkinson-type distributor/synthesizer 5 to the collectors of the transistors 1a and 1b, and capacitor 8 for interrupting a DC voltage for interrupting a DC voltage.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a high-frequency circuit, and more particularly to a high-frequency circuit such as an amplifier and a frequency converter used for a microwave or millimeter-wave wireless communication receiver.

[0002]

2. Description of the Related Art Bipolar transistors or FETs
(Field effect transistors) and passive elements make up a unit amplifier or unit mixer. The input signal is distributed in parallel to the unit amplifier or unit mixer by a distributor, and signal amplification or frequency conversion is performed. There is a high-frequency circuit that combines the outputs of the mixers and outputs a combined signal.

[0003] In a frequency converter, which is a kind of high-frequency circuit, several unit mixers are operated in parallel so that desired output signals are combined in phase and unnecessary output signals are combined in opposite phase to cancel out. ing. Various methods have been devised for such a distribution / synthesis method. For example, there are an image rejection mixer for canceling an image component and a signal converted by a local transmission signal, a local transmission signal suppressing single balance mixer, a balance mixer, and the like, which are disclosed in Japanese Patent Application Laid-Open No. 6-29749.

Some examples of conventional high-frequency circuits will be described below. [Prior Art 1] Referring to FIG. 7, a Wilkinson amplifier 72 splits an input signal into two signals having the same phase (a phase difference of 0 degree) and outputs a divided signal. And unit amplifiers 70a and 70b respectively connected to the output of the Wilkinson divider / combiner 4 for amplifying the divided signal and outputting the amplified signals, respectively, and connected to the outputs of the unit amplifiers 70a and 70b so that the amplified signals are in phase. And a Wilkinson distributor / combiner 5 for combining and outputting.

The Wilkinson divider / combiner 4 includes 90-degree phase delay lines 14a and 14b for delaying an input phase by 90 degrees and outputting the same, and a resistor 13a.

[0006] The Wilkinson divider / combiner 5 includes 90-degree phase delay lines 14c and 14d for delaying the input phase by 90 degrees and outputting the same, and a resistor 13b.

The unit amplifier 70a includes a transistor 1a
DC bias supply circuits 9a and 10a respectively connected to the base and collector of transistor 1a for supplying a DC bias (DC bias), matching circuits 2a and 3a, and a DC voltage cutoff for cutting off a DC voltage And a capacitor 8.

The main components of the unit amplifier 70b are the same as those of the unit amplifier 70a described above.
The description will not be repeated here.

Next, the operation of the Wilkinson amplifier 72 will be described. The Wilkinson divider / combiner 4 is
The input signal is divided into two signals with the same phase, and a divided signal is output. Unit amplifiers 70a and 70b respectively receive and amplify the two divided signals, and then output amplified signals. The Wilkinson divider / combiner 5 receives the two amplified signals, combines them at the same phase, and outputs them.

The Wilkinson divider / combiner 4 distributes an input signal into two parts. The two divided signals are output after being respectively delayed by 90 degrees in phase by the 90-degree phase delay line.

The unit amplifiers 70a and 70b receive the distributed signals and output amplified signals, respectively.

The Wilkinson divider / combiner 5 receives amplified signals output from the unit amplifiers 70a and 70b, respectively. The respective amplified signals are combined and output after their phases are delayed by 90 degrees in the 90-degree phase delay lines 14c and 14d, respectively.

The Wilkinson amplifier 72 can be regarded as a unit amplifier and can be further combined in parallel. Similarly, 2 ⁿ (n = 1, 2,...) Parallel compositions can be performed. With the Wilkinson amplifier 72, the power of the input signal can be doubled. [Prior Art 2] Referring to FIG.
4 is a 90-degree hybrid 80 for dividing an input signal into two signals with a phase difference of 90 degrees and outputting a divided signal;
Unit amplifier 70a connected to the output of the hybrid 80 to amplify the distribution signal and output the respective amplified signals
And 70b, and a 90-degree hybrid 82 connected to the outputs of the unit amplifiers 70a and 70b for combining and outputting an amplified signal having a phase difference of 90 degrees to a phase difference of 0 degrees and outputting the combined signal.

The 90-degree hybrid 80 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting the delayed signal.
4e, 14f, 14g and 14y, and a terminating resistor 17.

The 90-degree hybrid 82 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting the delayed signal.
4h, 14i, 14j, and 14z, and a terminating resistor 17.

Main components of unit amplifiers 70a and 70b are the same as those described with reference to FIG. 7, and therefore, description thereof will not be repeated here.

Next, the operation of the balanced amplifier 84 will be described. The 90-degree hybrid 80 distributes an input signal and outputs two distribution signals having different phases by 90 degrees.
Unit amplifiers 70a and 70b receive the two divided signals, respectively, and after amplification, output the amplified signals.
The 90-degree hybrid 82 receives the two amplified signals, returns them to the same phase, combines them, and outputs them.

The 90-degree hybrid 80 converts the input signal to 2
Distribute into two. One of the divided signals is output after the 90-degree phase is delayed by the 90-degree phase delay line 14e. The other distribution signal is provided by phase delay circuits 14y and 14y.
The signals are output after the phases are delayed by 90 degrees at f respectively. Therefore, the other distribution signal is 180 degrees behind the input signal. Therefore, the phase difference between one distribution signal and the other distribution signal is 90 degrees.

The unit amplifiers 70a and 70b receive the respective divided signals and output the respective amplified signals. The distribution signal input to the unit amplifier 70b has a phase delayed by 90 degrees from the distribution signal input to the unit amplifier 70a. Therefore, the same relationship is maintained between the respective amplified signals.

The 90-degree hybrid 82 has a unit amplifier 7
Input amplified signals output from 0a and 70b.
The amplified signal output from the unit amplifier 70a (the phase is delayed by 90 degrees from the input signal) is delayed by 90 degrees in the 90-degree phase delay lines 14h and 14z. The amplified signal output from the unit amplifier 70b (the phase is delayed by 180 degrees from the input signal) is delayed in phase by the 90-degree phase delay line 14j. The two phased amplified signals are combined and output. The phase difference between the two amplified signals is 270 degrees from the input signal, so that the phase difference between the two amplified signals is 0.
Degree.

It is to be noted that the balanced amplifier 84 can be regarded as a unit amplifier and further combined in parallel. Similarly,
2 ⁿ (n = 1, 2,...) Parallel compositions can be performed.

The power of the input signal can be doubled by the balanced amplifier 84. In the balanced amplifier 84, the reflected powers output from the unit amplifiers 70a and 70b are all 90-degree hybrids 80 and 82.
Are respectively absorbed by the respective terminating resistors 17 included in.
Therefore, even when the input / output impedance of unit amplifiers 70a and 70b deviates from 50Ω, the input / output impedance of balanced amplifier 84 is almost 50Ω.
There is an advantage that it is kept at Ω. The numerical value of 50Ω is an input / output impedance used for a commercially available measuring device, amplifier, mixer, and the like. [Related Art 3] Referring to FIG. 9, an image rejection mixer 96 includes a Wilkinson-type distributing / combining unit 4 for distributing an LO signal (locally transmitted signal) into two in-phase and outputting the same, and an RF signal. A 90-degree hybrid 80 for distributing the (high-frequency signal) into two signals with a phase difference of 90 degrees and outputting a divided signal; and one output of the Wilkinson divider / combiner 4 and one output of the 90-degree hybrid 80 Unit mixer 90 for outputting IF signals (intermediate frequency signals) after frequency-synthesizing the respective outputs.
A unit mixer 92 connected to the other output of the Wilkinson divider / combiner 4 and the other output of the 90-degree hybrid 80 for frequency-synthesizing the respective outputs and outputting an IF signal; For outputting an in-phase output and a phase difference output by combining
And a temperature synthesizer 94.

The Wilkinson divider / combiners 4 and 90
The main components of degree hybrid 80 are the same as those described with reference to FIGS. 7 and 8, respectively, and therefore, description thereof will not be repeated here.

The unit mixer 90 includes a transistor 1b,
DC bias supply circuits 9b and 10b connected to the base and the collector of transistor 1b to supply a DC bias, matching circuits 2b and 3b,
Includes matching circuit IF filter 11b and DC voltage blocking capacitor 8 for blocking DC voltage.

The main components of unit mixer 92 are the same as those of unit mixer 90 described above, and the description of these components will not be repeated here.

Next, an image rejection mixer 96
Will be described. First, the frequency of the LO signal is R
Consider a case where the frequency is lower than the frequency of the F signal. The LO signal is split into two in-phase by a Wilkinson splitter / combiner 4. The RF signal is 90
It is split into two with a phase difference of degrees. Unit mixer 92 performs frequency synthesis of one output signal output from Wilkinson divider / combiner 4 and one output signal output from 90-degree hybrid 80, and outputs an IF signal.
The unit mixer 90 performs frequency synthesis of the other output signal output from the Wilkinson divider / combiner 4 and the other output signal output from the 90-degree hybrid 80,
Outputs IF signal. The two IF signals have a phase difference of 90 degrees. Therefore, the two IF signals are combined into a 90-degree combiner 94.
, The combined signal of the LO signal and the RF signal is output as the phase difference output. Nothing is output to the in-phase output. This is because two IFs with a 90 degree phase difference
Since the signals are converted by the 90-degree combiner 94 into two IF signals having a phase difference of 180 degrees and then combined, the 2
This is because two IF signals cancel each other and no output occurs.

Next, consider the case where the frequency of the LO signal is higher than the frequency of the RF signal. In this case, the unit mixer 90
The relationship between the phase difference between the two IF signals output from the and IF 92 is opposite to the relationship between the phase difference between the two IF signals when the frequency of the LO signal is lower than the frequency of the RF signal. Therefore, a composite signal of the LO signal and the RF signal is output to the in-phase output of the 90-degree synthesizer 94, and nothing is output to the phase difference output.

With such an image rejection mixer 96, the output terminal can be determined depending on whether the frequency of the LO signal is higher or lower than the frequency of the RF signal. [Prior Art 4] Referring to FIG. 10, single-balanced mixer 104 splits an input signal of frequency f1 into two signals in opposite phases (a phase difference of 180 degrees) to output a split signal, and outputs frequency signal f2. A 180 degree hybrid 60 for distributing the LO signal in phase and outputting a distributed signal, and frequency combining and amplifying one of the distributed signal of the input signal of frequency f1 and one of the LO signal of frequency f2. Frequency f
A unit amplifier 70a for outputting an amplified signal of 1-f2
A unit amplifier 70b for synthesizing and amplifying the other distributed signal of the input signal of frequency f1 and the other distributed signal of the LO signal of frequency f2 to output an amplified signal of frequency f1-f2; It includes a 180-degree hybrid 62 for receiving the signal, setting the phase difference between the two amplified signals to 0 degree, and then combining and outputting the resultant signal, and the terminating resistor 17.

The 180-degree hybrid 60 has 90-degree phase delay lines 14k, 141, 14m, 14n, 14p, and 14q for delaying the input phase by 90 degrees and outputting the delayed output.
including.

The 180-degree hybrid 62 has 90-degree phase delay lines 14r, 14s, 14u, 14v, 14w, and 14x for delaying the input phase by 90 degrees and outputting the delayed signals.
including.

The main components of unit amplifiers 70a and 70b are the same as those described with reference to FIG. 7, and therefore, description thereof will not be repeated here.

Next, the operation of the single balance mixer 104 will be described. The input signal having the frequency f1 is distributed by the 180-degree hybrid 60, and two distributed signals having phases different from each other by 180 degrees are output. In addition, L of frequency f2
The O signal is distributed by the 180-degree hybrid 60, and two distributed signals in phase are output. Unit amplifier 70a
Is one distribution signal of the input signal of the frequency f1 and the frequency f
After performing the frequency synthesis of the two LO signals with one of the distribution signals and amplifying the same, an amplified signal of the frequency f1-f2 is output.
The unit amplifier 70b synthesizes and amplifies the other distribution signal of the input signal of the frequency f1 and the other distribution signal of the LO signal of the frequency f2, and then outputs an amplified signal of the frequency f1-f2. These two signals are 180 degrees out of phase. The two amplified signals are phase-converted by the 180-degree hybrid 62 so that the signal components of the frequencies f1 and f2 have the same phase, and are combined to output a combined signal.

The amplified signals output from the unit amplifiers 70a and 70b each include an LO signal component. However, this signal component is a 180 degree hybrid 6
2, the two phases are oppositely synthesized, so that they are not mutually canceled and output. [Prior Art 5] Referring to FIG. 11, a double balance mixer 110 includes a Wilkinson type divider / combiner 4 for dividing an input signal into two in phase and outputting a divided signal,
1 for distributing the LO signal in reverse phase and outputting a distribution signal
80 degree hybrid 60 and 180 degree hybrid 60
One of the divided signals and the Wilkinson divider / combiner 4
And a single balance mixer 104a for outputting a synthesized signal after frequency conversion.
A single balance mixer 104b for receiving the other output of the 80-degree hybrid 60 and the other output of the Wilkinson divider / combiner 4 and outputting a synthesized signal after frequency conversion, and outputs from the single balance mixers 104a and 104b, respectively. Receiving the synthesized signal
It includes a 180-degree hybrid 62 for returning the two combined signals to the same phase and combining and outputting the combined signals, and a terminating resistor 17.

Main components of 180-degree hybrids 60 and 62 are similar to those of 180-degree hybrids 60 and 62 described with reference to FIG. 10, and therefore, description thereof will not be repeated.

Main components of Wilkinson divider / combiner 4 are the same as those of Wilkinson divider / combiner 4 described with reference to FIG. 7, and therefore, description thereof will not be repeated. Single balance mixers 104a and 10
Main components of 4b are the same as those of single balance mixer 104 described with reference to FIG. 10, and therefore, description thereof will not be repeated.

Next, the operation of the double balance mixer 110 will be described. The input signal of the frequency f1 is divided into two in-phase by the Wilkinson divider / combiner 4, and the divided signal is output. The LO signal of the frequency f2 is distributed by the 180-degree hybrid 60 into two distribution signals so that the phase difference becomes 180 degrees. Single balance mixer 104a
Receives one of the input signals of the frequency f1 and one of the LO signals of the frequency f2, and receives the frequency f1-
The composite signal of f2 is output. Single balance mixer 1
04b receives the other distribution signal of the input signal of the frequency f1 and the other distribution signal of the LO signal of the frequency f2, and outputs a composite signal of the frequencies f1 to f2. 180 degrees phase difference 2
The phase difference between the two synthesized signals is 0
Then, the combined signal is output.

Single balance mixers 104a and 1
The operation of 04b is the same as that of single balance mixer 104 described with reference to FIG. 10, and therefore, description thereof will not be repeated.

Transistors 1a, 1b, 1a constituting unit amplifiers 70a, 70b, 70c and 70d, respectively.
For the base and collector of c and 1d respectively,
One DC bias supply circuit is attached to each. Therefore, eight DC bias supply circuits are required as the double balance mixer 110.

[0039]

However, the conventional high-frequency circuit has the following problems. In order to operate a bipolar transistor or FET constituting a unit amplifier or a unit mixer, it is usually necessary to supply two types of DC bias. For example, GaAs (gallium arsenide)
When a system-based hetero bipolar transistor (HBT) is grounded at the emitter, it is necessary to apply a DC voltage of about 1.3 to 1.5 V to the base and about 3 V to the collector. Therefore, a DC is connected to each contact of the transistor or the FET.
Bias was being supplied. When two unit amplifiers or mixers are arranged in parallel to constitute a parallel amplifier or a frequency converter, a total of four DC bias supply circuits are required. Similarly, a unit amplifier or a unit mixer
^{When n} pieces are arranged in parallel, 2 × 2 ⁿ DC bias supply circuits are required. On the other hand, if the frequency used is 1G
As the frequency increases from about Hz (gigahertz) to about 10 GHz, a so-called MMIC (monolithic microwave integrated circuit) for integrating a high-frequency circuit on one semiconductor chip has been actively developed. When these parallel amplifiers and frequency converters are formed into MMICs, the layout becomes complicated, and the area occupied by the bias supply line and the DC voltage supply pad increases, which causes an increase in cost. Further, when the number of unit amplifiers and unit mixers is four or more, the number of intersections between the high-frequency signal line and the DC bias supply circuit increases. Usually, at these intersections, one track is bridged over the other track,
A so-called air bridge is formed to reduce the influence of each other's lines. However, as the frequency increases, the capacitance between the two lines at the intersection becomes not negligible, and the mutual influence between the two lines increases. This causes the characteristics of the high frequency circuit to deteriorate.

The present invention has been made to solve these problems, and the invention according to any one of the first to ninth aspects provides a high-frequency circuit having a simple circuit configuration and high frequency characteristics. The purpose is to provide.

[0041]

According to a first aspect of the present invention, there is provided a high frequency circuit comprising: a first high frequency component passing means for passing only a high frequency component of an input signal; and a first high frequency component passing means. A distributor connected to the output, for dividing and outputting the output of the first high-frequency component passing means into a plurality of parts with a certain phase difference, and connected to the output of the distributor, respectively, for amplifying the output of the distributor. A plurality of amplifying means for outputting, connected to outputs of the plurality of amplifying means, a combining means for combining and outputting the outputs of the plurality of amplifying means with a certain phase difference, and connected to an output of the combining means, A second high-frequency component passing means for passing only the high-frequency component of the output of the synthesizing means, and a plurality of amplifiers connected to the distributing means and / or the synthesizing means, respectively, A and a DC bias supply means for supplying direct current bias, respectively.

The high-frequency circuit according to the first aspect of the present invention supplies a DC bias to a plurality of amplifying units via the distribution unit and / or the synthesizing unit, so that the number of DC bias supply units is minimized. be able to. Therefore, the circuit configuration can be simplified, and the time required for layout design can be reduced. Further, since there is no mutual influence between the line of the high-frequency signal and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal.

In the high frequency circuit according to the second aspect of the present invention, in addition to the configuration of the first aspect, the distribution means is connected to an output of the first high frequency component passing means,
And an in-phase distributor for distributing the output of the high-frequency component passing means into a plurality with a phase difference of 0 degrees and outputting the divided output. Includes an in-phase combiner for combining and outputting with a phase difference of 0 degrees.

According to a third aspect of the present invention, in addition to the configuration of the first aspect, the distribution means is connected to an output of the first high frequency component passing means,
A 90-degree splitter for splitting the output of the high-frequency component passing means into two with a phase difference of 90 degrees and outputting the same, the plurality of amplifying means includes two amplifying means, and the combining means includes two amplifying means. And a 90-degree combiner for combining and outputting the outputs of the two amplifying means having a phase difference of 90 degrees with a phase difference of 0 degrees.

The high-frequency circuit according to the fourth aspect of the present invention is connected to a plurality of high-frequency component passing means for passing only high-frequency components of a plurality of input signals, respectively, and to outputs of the plurality of high-frequency component passing means. A plurality of distributing means for distributing the output of the high-frequency component passing means into a plurality with a certain phase difference, and outputting the plurality of distributing means; and A plurality of mixers for frequency synthesizing and outputting, a synthesizing means connected to outputs of the plurality of mixers for synthesizing and outputting the outputs of the plurality of mixers with a certain phase difference, and a plurality of distributing means or synthesizing means DC bias supply means for respectively supplying a DC bias to the plurality of mixers via the plurality of distribution means or the synthesis means.

In the high-frequency circuit according to the fourth aspect of the present invention, a DC bias is supplied to a plurality of mixers via a plurality of distributing means or synthesizing means, so that the number of DC bias supplying means is minimized. Can be. For this reason,
The circuit configuration can be simplified, and the time required for layout design can be reduced. Further, since there is no mutual influence between the line of the high-frequency signal and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal.

According to a fifth aspect of the present invention, in addition to the configuration of the fourth aspect, the plurality of input signals include an input signal of a frequency f1 and an input signal of a frequency f2. , A plurality of high frequency component passing means, the frequency f1
A first high-frequency component passing means for passing only the high-frequency component of the input signal having a frequency f2, and a second high-frequency component passing means for passing only the high-frequency component of the input signal having the frequency f2. Is connected to the output of the first high-frequency component passing means, distributes the output of the first high-frequency component passing means into two with a phase difference of 90 degrees, and outputs the two. The output of the second high frequency component passing means is connected to the output of the
A plurality of mixers connected to one output of the first distribution means and one output of the second distribution means; A first unit mixer for frequency-synthesizing and outputting one output and one output of the second distribution means, and connected to the other output of the first distribution means and the other output of the second distribution means; A second unit mixer for frequency-synthesizing and outputting the other output of the first distribution unit and the other output of the second distribution unit, wherein the synthesizing unit includes an output of the first unit mixer. And the output of the first unit mixer and the output of the second unit mixer having a phase difference of 90 degrees are respectively connected to the outputs of | f1-f2 | with a phase difference of 0 degree. Includes a 90 degree combiner for combining and outputting.

According to a sixth aspect of the present invention, in addition to the configuration of the fourth aspect, the plurality of input signals include an input signal of a frequency f1 and an input signal of a frequency f2. , A plurality of high frequency component passing means, the frequency f1
A first high-frequency component passing means for passing only the high-frequency component of the input signal having a frequency f2, and a second high-frequency component passing means for passing only the high-frequency component of the input signal having the frequency f2. Is connected to the output of the first high-frequency component passing means, distributes the output of the first high-frequency component passing means into two with a phase difference of 180 degrees, and outputs the two. The output of the second high frequency component passing means is connected to the output of the
And a plurality of mixers are connected to one output of the first distribution means and one output of the second distribution means, and are connected to one of the first distribution means. And a first unit mixer for frequency-synthesizing the output of the first distributing means and one output of the second distributing means, and being connected to the other output of the first distributing means and the other output of the second distributing means. A second output for synthesizing and outputting the other output of the first distributor and the other output of the second distributor.
The unit mixer is connected to the output of the first unit mixer and the output of the second unit mixer, and the output of the first unit mixer and the output of the second unit mixer having a phase difference of 180 degrees. And a negative-phase combiner for combining and outputting the signal components of | f1-f2 | with a phase difference of 0 degree.

The high frequency circuit according to the present invention is connected to a plurality of high frequency component passing means for passing only the high frequency signals of the plurality of input signals, and to the outputs of the plurality of high frequency component passing means, respectively. A plurality of distribution means for distributing the output of the high-frequency component passing means into a plurality with a certain phase difference and respectively outputting the outputs, and being connected to an output of each of the plurality of distribution means and an output of each of the plurality of distribution means Receiving a plurality of frequency conversion means for performing frequency conversion, respectively outputting the plurality of frequency conversion means, and outputting the combined output of the plurality of frequency conversion means with a certain phase difference. A DC bias is connected to the synthesizing means and the plurality of distributing means or the synthesizing means, and is supplied to the plurality of frequency converting means via the plurality of distributing means or the synthesizing means. And a DC bias supply means for.

In the high frequency circuit according to the present invention, a DC bias is supplied to a plurality of frequency converting means via a plurality of distributing means or synthesizing means, so that the number of DC bias supplying means is minimized. Can be held down. Therefore, the circuit configuration can be simplified, and the time required for layout design can be reduced. Further, since there is no mutual influence between the line of the high-frequency signal and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal.

In the high-frequency circuit according to the eighth aspect, in addition to the configuration of the seventh aspect, the plurality of input signals include an input signal having a frequency f1 and an input signal having a frequency f2. , A plurality of high frequency component passing means, the frequency f1
A first high-frequency component passing means for passing only the high-frequency component of the input signal having a frequency f2, and a second high-frequency component passing means for passing only the high-frequency component of the input signal having the frequency f2. Is connected to the output of the first high-frequency component passing means, distributes the output of the first high-frequency component passing means into two with a certain phase difference, and outputs the two signals; The output of the second high-frequency component passing means is connected to the output of the
Second distributing means for distributing and outputting the two
The plurality of frequency conversion means are connected to one output of the first distribution means and one output of the second distribution means, and connect one output of the first distribution means and one output of the second distribution means. A first frequency converting means for receiving, performing frequency conversion and outputting, and connected to the other output of the first distributing means and the other output of the second distributing means, Second frequency converting means for receiving the output and the other output of the second distribution means, performing frequency conversion and outputting the output, and the synthesizing means includes an output of the first frequency converting means and a second frequency converting means. Connected to the output of the conversion means,
A phase difference synthesizing means for synthesizing the output of the first frequency converting means and the output of the second frequency converting means with a certain phase difference and outputting the result.

According to a ninth aspect of the present invention, in addition to the configuration of the eighth aspect, the first distribution means is connected to an output of the first high frequency component passing means,
An in-phase distributor for dividing the output of the first high-frequency component passing means into two with a phase difference of 0 degree and outputting the same is provided, and the second distribution means is connected to the output of the second high-frequency component passing means. ,
The output of the second high frequency component passing means is set to 2
And a phase difference synthesizing means connected to the output of the first frequency converting means and the output of the second frequency converting means, and having a phase difference of 180 degrees. And an antiphase synthesizer for synthesizing the output of the frequency conversion means and the output of the second frequency conversion means with a phase difference of 0 degree and outputting the result.

[0053]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Hereinafter, high-frequency circuits according to various embodiments of the present invention will be described with reference to the drawings. In the following description, the same parts are denoted by the same reference numerals. Since their names and functions are the same, repeated description is omitted as appropriate. [First Embodiment] Referring to FIG. 1, a Wilkinson amplifier 15 of a first embodiment includes a Wilkinson divider / combiner 4 for dividing an input signal into two in-phase and outputting a divided signal; Unit amplifiers 12a and 12b respectively connected to the output of the Wilkinson divider / combiner 4 for amplifying the divided signal and outputting the amplified signals, respectively, and connected to the unit amplifiers 12a and 12b to combine and output the amplified signals in the same phase. Wilkinson-type distributor / synthesizer 5
A DC bias supply circuit 9 for supplying a DC bias to the bases of transistors 1a and 1b to be described later via a Wilkinson divider / combiner 4, and a transistor 1 via a Wilkinson divider / combiner 5.
It includes a DC bias supply circuit 10 for supplying a DC bias to the collectors a and 1b, respectively, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The Wilkinson divider / combiner 4 includes 90-degree phase delay lines 14a and 14b for delaying an input phase by 90 degrees and outputting the same, and a resistor 13a. The Wilkinson divider / combiner 5 includes 90-degree phase delay lines 14c and 14d for delaying an input phase by 90 degrees and outputting the same, and a resistor 13b. 90 degree phase delay line 1
Reference numerals 4a, 14b, 14c, and 14d each include a microstrip line, a coplanar line, or the like. Unit amplifier 12a includes a transistor 1a and matching circuits 2a and 3a.

The unit amplifier 12b includes the transistor 1b
And matching circuits 2b and 3b.

Next, the operation of the Wilkinson amplifier 15 will be described. The input signal is split into two by the Wilkinson splitter / combiner 4 with the same phase. The two distribution signals are input to unit amplifiers 12a and 12b, respectively, and are amplified respectively. The two amplified signals are input to the Wilkinson divider / combiner 5, where they are combined and output at the same phase.

The Wilkinson divider / combiner 4 distributes an input signal into two parts. The two split signals are respectively 90 degrees by 90 degree phase delay lines 14a and 14b.
It is output after the phase has been delayed.

Each of unit amplifiers 12a and 12b receives a divided signal and outputs an amplified signal.

The Wilkinson divider / combiner 5 receives the amplified signals output from the unit amplifiers 12a and 12b. Each amplified signal is a 90-degree phase delay line 14c.
After the phases are respectively delayed by 90 degrees in steps 14 and 14d, they are combined and output.

The transistors 1a and 1b constituting the unit amplifiers 12a and 12b, respectively, are supplied with a DC bias from DC bias supply circuits 9 and 10 connected to the Wilkinson type divider / combiners 4 and 5, respectively. Further, the DC voltage is cut off by the DC voltage cut-off capacitor 8 provided at the input / output port, and only the high frequency signal can be passed.

In the Wilkinson amplifier 15, by supplying a DC bias before and after distributing a high-frequency signal, the number of DC bias supply circuits conventionally required four becomes two. Therefore, the circuit configuration can be simplified, and the time required for the layout design can be reduced. Also,
Since the mutual influence between the high-frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal. [Second Embodiment] Referring to FIG. 2, a balanced amplifier 24 according to a second embodiment has a 90-degree hybrid 20 for dividing an input signal into two signals with a phase difference of 90 degrees and outputting a divided signal. Unit amplifiers 12a and 12b connected to the two outputs of the 90-degree hybrid 20 to amplify the divided signal and output the amplified signals, respectively;
a 90-degree hybrid 22 connected to the outputs of a and 12b for returning an amplified signal having a phase difference of 90 degrees to 0-degree and combining and outputting the amplified signal; and 90-degree hybrid 20 via unit amplifiers 12a and 12b. DC bias supply circuit 9 for supplying a DC bias to the bases of transistors 1a and 1b as respective components.
And the transistor 1 via the 90-degree hybrid 22
It includes a DC bias supply circuit 10 for supplying a DC bias to the collectors a and 1b, respectively, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The 90-degree hybrid 20 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees for output.
4e, 14f, 14g and 21a, and the terminating resistor 17. The DC bias supply circuit 9 is connected to the 90-degree phase delay line 21a.

The 90-degree hybrid 82 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees for output.
4h, 14i, 14j and 21b, and the terminating resistor 17.

DC bias supply circuits 9 and 10 are connected to the 90-degree phase delay lines 21a and 21b, respectively. 90-degree phase delay lines 14e, 14f, 14
g, 14h, 14i, 14j, 21a and 21b are:
It is composed of a microstrip line, a coplanar line and the like.

Next, the operation of the balanced amplifier 24 will be described. The input signal is distributed by the 90-degree hybrid 20 into two distribution signals having different phases by 90 degrees. 2
The two distribution signals are input to the unit amplifiers 12a and 12b, respectively, amplified, and output as amplified signals. The two amplified signals are 90 degree hybrid 22
And are returned to the same phase and then combined.

The 90-degree hybrid 20 converts the input signal to 2
Distribute into two. The operation is the same as that of 90-degree hybrid 80 described with reference to FIG. 8, and therefore, description thereof will not be repeated here.

Each of unit amplifiers 12a and 12b receives a distribution signal and outputs an amplified signal. The distribution signal input to the unit amplifier 12b is
Has a phase lag of 90 degrees from the distribution signal input to.
Therefore, the same relationship is maintained between the respective amplified signals.

The 90-degree hybrid 22 is a unit amplifier 1
The amplified signals output from 2a and 12b are input, and after the respective signals have the same phase, they are combined and output. The operation has been described with reference to FIG.
Since it is similar to 0-degree hybrid 82, its description will not be repeated here.

The transistors 1a and 1b constituting the unit amplifiers 12a and 12b are supplied with DC bias from DC bias supply circuits 9 and 10 connected to the 90-degree hybrids 20 and 22, respectively. Further, the DC voltage is cut off by the DC voltage cut-off capacitor 8 provided at the input / output port, and only the high frequency signal can be passed. In addition, termination resistor 1
Due to the DC voltage blocking capacitor 8 provided between the terminal 7 and the ground, the terminating resistor 17 functions as a resistance for a high-frequency signal and functions as an open for a DC current.

In the balanced amplifier 24, by supplying a DC bias before and after distributing a high-frequency signal, the number of DC bias supply circuits conventionally required four becomes two. Therefore, the circuit configuration can be simplified, and the time required for the layout design can be reduced. Further, since there is no mutual influence between the high-frequency signal line and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal. Third Embodiment Referring to FIG. 3, image rejection mixer 36 according to a third embodiment includes a Wilkinson divider / combiner 4 for dividing an LO signal into two in-phase and outputting the same, and an RF signal. 90-degree hybrid 20 for dividing a signal into two signals with a phase difference of 90 degrees and outputting a divided signal
A unit mixer 30a connected to one output of the Wilkinson divider / combiner 4 and one output of the 90-degree hybrid 20 for frequency-synthesizing the respective outputs and outputting an IF signal (intermediate frequency signal). Are connected to the other output of the Wilkinson-type distributor / synthesizer 4 and the other output of the 90-degree hybrid 20. After the respective outputs are frequency-synthesized, a unit mixer 30b for outputting an IF signal, and A 90-degree synthesizer 34 for synthesizing and outputting 90-degrees, and a 90-degree hybrid 2
0, a DC bias supply circuit 9 for supplying a DC bias to the bases of the transistors 1a and 1b of the respective components of the unit mixers 30a and 30b via the 90-degree hybrid 20, and a Wilkinson-type distribution circuit. The transistors 1a and 1a are connected to the combiner 4 and pass through the Wilkinson-type distributor / synthesizer 4.
b includes a DC bias supply circuit 10 for supplying a DC bias to each of the collectors, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The main components of 90-degree hybrid 20 have been described with reference to FIG. 2, and therefore description thereof will not be repeated here.

The main components of Wilkinson divider / combiner 4 have been described with reference to FIG. 7, and thus description thereof will not be repeated here.

The unit mixer 30a includes the transistor 1a
And matching circuits 2a and 3a, a matching circuit IF filter 32a, and a DC voltage blocking capacitor 8 for blocking DC voltage. Unit mixer 30b includes transistor 1b, matching circuits 2b and 3b, matching circuit IF filter 32b, and DC voltage blocking capacitor 8 for blocking DC voltage.

The matching circuits 2a, 2b, 3a and 3b have a circuit configuration having direct current conduction between input and output. Unit mixer 3
0a and 30b, matching circuits 2a, 2b,
Although an example in which only 3a and 3b are arranged is shown, various configurations such as a filter and a phase shifter other than the matching circuit can be considered.

Next, the image rejection mixer 36
Will be described. The LO signal is split into two split signals in phase by the Wilkinson splitter / combiner 4. The RF signal is divided by the 90-degree hybrid 20 into two distribution signals with a phase difference of 90 degrees. Unit mixer 3
0a performs a frequency conversion between one of the divided signals output from the Wilkinson divider / combiner 4 and one of the divided signals of the 90-degree hybrid 20, and outputs an IF signal. The unit mixer 30b synthesizes the frequency of the other distributed signal output from the Wilkinson-type distributor / synthesizer 4 and the other distributed signal output from the 90-degree hybrid 20.
Outputs F signal. The 90-degree combiner 34 receives the two IF signals, combines them by 90 degrees, and outputs a combined signal.

The transistors 1a and 1b constituting the unit mixers 30a and 30b respectively have bias supply lines 10 and 9 connected to the Wilkinson divider / combiner 4 and the 90-degree hybrid 20, respectively.
A DC bias is supplied via the Wilkinson divider / combiner 4 and the 90-degree hybrid 20, respectively. Further, the DC bias is cut off by the DC voltage cut-off capacitors 8 provided at the two input ports,
Only high frequency signals can be passed. Furthermore, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 acts as a resistor for high-frequency signals and acts as an open for DC current.

In the image rejection mixer 36,
By supplying a DC bias before and after distributing the high-frequency signal, the number of DC bias supply circuits conventionally required four becomes two. Therefore, the circuit configuration can be simplified, and the time required for the layout design can be reduced. Further, since there is no mutual influence between the high-frequency signal line and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal. [Fourth Embodiment] Referring to FIG. 4, an image rejection mixer 38 according to a fourth embodiment includes a Wilkinson divider / combiner 4 for distributing an RF signal into two in-phase and outputting the same, and an LO. 90-degree hybrid 20 for dividing a signal into two signals with a phase difference of 90 degrees and outputting a divided signal
A unit mixer 30a connected to one output of the Wilkinson divider / combiner 4 and one output of the 90-degree hybrid 20 for frequency-synthesizing the respective outputs, and then outputting an IF signal; The other output of the device 4 and the other output of the 90-degree hybrid 20 are connected to each other.
A unit mixer 30b for outputting an IF signal, a 90-degree synthesizer 34 for synthesizing and outputting each IF signal at 90 degrees, and a 90-degree hybrid 20 are connected.
A DC bias supply circuit 10 for supplying a DC bias to the bases of the transistors 1a and 1b of the component mixers of the unit mixers 30a and 30b, respectively, and a Wilkinson divider / combiner 4 via the hybrid 20. , Via the Wilkinson divider / combiner 4 to the collectors of the transistors 1a and 1b.
It includes a DC bias supply circuit 9 for supplying a C bias and a DC voltage blocking capacitor 8 for blocking a DC voltage.

Main components of 90-degree hybrid 20 have been described with reference to FIG. 2, and therefore description thereof will not be repeated here.

The main components of the Wilkinson divider / combiner 4 have been described with reference to FIG. 7, and the description thereof will not be repeated here.

The main components of the unit mixers 30a and 30b have been described with reference to FIG.
Here, the description will not be repeated.

Next, the image rejection mixer 38
Will be described. The RF signal is split into two split signals in phase by the Wilkinson splitter / combiner 4. The LO signal is distributed by the 90-degree hybrid 20 into two distribution signals with a phase difference of 90 degrees. Unit mixer 3
0a synthesizes the frequency of one of the divided signals output from the Wilkinson splitter / combiner 4 and the other distributed signal output from the 90-degree hybrid 20, and outputs an IF signal. The unit mixer 30b synthesizes the frequency of the other distribution signal output from the Wilkinson distribution / combiner 4 and the other distribution signal output from the 90-degree hybrid 20, and outputs an IF signal. 90 degree synthesizer 34
Receives two IF signals, combines them by 90 degrees, and outputs a combined signal.

The transistors 1a and 1b constituting the unit mixers 30a and 30b respectively include bias supply lines 10 and 9 connected to the 90-degree hybrid 20 and the Wilkinson divider / combiner 4, respectively.
A DC bias is supplied via the 90-degree hybrid 20 and the Wilkinson divider / combiner 4, respectively. Further, the DC bias is cut off by the DC voltage cut-off capacitors 8 provided at the two input ports,
Only high frequency signals can be passed. Furthermore, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 acts as a resistor for high-frequency signals and acts as an open for DC current.

In the image rejection mixer 38,
By supplying a DC bias before and after distributing the high-frequency signal, the number of DC bias supply circuits conventionally required four becomes two. Therefore, the circuit configuration can be simplified, and the time required for the layout design can be reduced. Further, since there is no mutual influence between the high-frequency signal line and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal. [Fifth Embodiment] Referring to FIG. 5, a single balance mixer 54 according to a fifth embodiment distributes an input signal of frequency f1 into two signals in opposite phases to output a divided signal, and outputs a divided signal of frequency f2. A 180-degree hybrid 50 for distributing the LO signal in phase and outputting a distributed signal, and a frequency synthesis and amplification of one of the input signal of the frequency f1 and the other of the LO signal of the frequency f2, and amplifies the frequency. f1-f
A unit amplifier 12a for outputting the amplified signal of the frequency f2, the other distribution signal of the input signal of the frequency f1, and the frequency f2.
And a unit amplifier 12b for synthesizing and amplifying the other distributed signal of the LO signal to output an amplified signal of the frequency f1-f2, and setting the phase difference between these two amplified signals to 0 degree, and then synthesizing. 180-degree hybrid 52 for outputting and 180-degree hybrid 50
The transistor 1a which is a component of each of the unit amplifiers 12a and 12b via the hybrid 50
DC bias supply circuit 9 for supplying a DC bias to the bases of the transistors 1a and 1b, and a DC bias to the collectors of the transistors 1a and 1b via the 180-degree hybrid 52 via the 180-degree hybrid 52 DC bias supply circuit 1 for
0, a terminating resistor 17, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The 180-degree hybrid 50 has 90-degree phase delay lines 14k, 141, 14m, 14n, 14p, and 14q for delaying the input phase by 90 degrees and outputting the delayed signals.
including. The 180-degree hybrid 52 sets the phase of the input to 9
90-degree phase delay line 14 for delaying 0-degree output
r, 14s, 14u, 14v, 14w and 14x.

The unit amplifier 12a includes the transistor 1a
And matching circuits 2a and 3a. Unit amplifier 12
b includes a transistor 1b and matching circuits 2b and 3b.

Next, the operation of the single balance mixer 54 will be described. The input signal of the frequency f1 is distributed by the 180-degree hybrid 50, and is distributed to two distribution signals having phases different by 180 degrees. The LO signal of the frequency f2 is distributed by the 180-degree hybrid 50 and is distributed to two distribution signals having the same phase. The unit amplifier 12a performs frequency synthesis of one of the input signals of the frequency f1 and one of the LO signals of the frequency f2, amplifies the signals, and outputs an amplified signal of the frequencies f1 to f2. The unit amplifier 12b performs frequency synthesis of the other distributed signal of the input signal of the frequency f1 and the other distributed signal of the LO signal of the frequency f2, amplifies the signal, and outputs an amplified signal of the frequency f1−f2. These signals are 180 degrees out of phase.
The two amplified signals are phase-converted by the 180-degree hybrid 52 so that the signal components of the frequencies f1 and f2 have the same phase, and are combined to output a combined signal.

The amplified signals output from the unit amplifiers 12a and 12b each include an LO signal component. However, this signal component is a 180 degree hybrid 5
2, the two phases are oppositely synthesized, so that they are not mutually canceled and output.

The transistors 1a and 1b constituting the unit amplifiers 12a and 12b respectively have bias supply lines 9 and 10 connected to the 180-degree hybrid 50 and the 180-degree hybrid 52, respectively.
80 degree hybrid 50 and 180 degree hybrid 5
2, DC bias is supplied respectively. Further, the DC bias is cut off by the DC voltage cut-off capacitor 8 provided at the input / output port, and only the high frequency signal can be passed. In addition, termination resistor 1
Due to the DC voltage blocking capacitor 8 provided between the terminal 7 and the ground, the terminating resistor 17 functions as a resistance for a high-frequency signal and functions as an open for a DC current.

In the single balance mixer 54, the DC bias is supplied before and after distributing the high-frequency signal, so that the number of DC bias supply circuits conventionally required four becomes two. Therefore, the circuit configuration can be simplified, and the time required for the layout design can be reduced. Also,
Since the mutual influence between the high-frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal. Sixth Embodiment Referring to FIG. 6, a double balance mixer 64 according to a sixth embodiment includes a Wilkinson type divider / combiner 4 for dividing an input signal into two in-phase and outputting a divided signal. , And a 180-degree hybrid 60 for distributing the LO signal into two signals in opposite phases and outputting a distributed signal.
A single balance mixer 54a for receiving one distributed signal of the 0-degree hybrid 60 and one output of the Wilkinson type distributor / synthesizer 4 and outputting a composite signal after frequency conversion, and the other output of the 180-degree hybrid 60 And the other output of the Wilkinson divider / combiner 4, receives a single balance mixer 54b for performing frequency conversion and outputting a combined signal, and receives combined signals output from the single balance mixers 54a and 54b, respectively. A 180-degree hybrid 62 for returning the two combined signals to the same phase and combining and outputting the combined signals, and a component of the single balance mixer 54a which is connected to the Wilkinson divider / combiner 4 via the Wilkinson divider / combiner 4 Transistors 1a and 1b and a single balance The base of the transistor 1c and 1d is a component of the support 54b and the DC bias supply circuit 9 for supplying DC bias to each connected to a 180 degree hybrid 62, 180-degree hybrid 62
Through the transistors 1a, 1b, 1c and 1d
A DC bias supply circuit 10 for supplying a DC bias to the collectors of the DC / DC converters, a terminating resistor 17, and a DC voltage cutoff capacitor 8 for cutting off the DC voltage.

The structure of the 180-degree hybrid 60 is shown in FIG.
, And the description thereof will not be repeated. Main components of 180-degree hybrid 62 are the same as those of 180-degree hybrid 52 described with reference to FIG. 5, and therefore, description thereof will not be repeated. The main components of single balance mixers 54a and 54b are the same as those of single balance mixer 54 described with reference to FIG. 5, and therefore description thereof will not be repeated.

Next, the operation of the double balance mixer 64 will be described. The input signal of the frequency f1 is divided into two in-phase by the Wilkinson divider / combiner 4, and the divided signal is output. The LO signal of the frequency f2 is distributed by the 180-degree hybrid 60 into two distribution signals so that the phase difference becomes 180 degrees. The single balance mixer 54a outputs one of the divided signals of the frequency f1 input signal and the frequency f2.
Receiving one of the divided signals of the LO signal of frequency f1-f2
And outputs the synthesized signal. Single balance mixer 54b
Receives the other distributed signal of the input signal of the frequency f1 and the other distributed signal of the LO signal of the frequency f2, and receives the frequency f1-
The composite signal of f2 is output. These two combined signals are
Since the phase difference is 180 degrees, the 180-degree hybrid 62
After the phase difference is set to 0 degree and the images are synthesized, a synthesized signal is output.

Single balance mixers 54a and 54
The operation of b is similar to the operation of single balance mixer 54 described with reference to FIG. 5, and therefore, description thereof will not be repeated.

Transistors 12a, 12a constituting unit amplifiers 12a, 12b, 12c and 12d, respectively.
b, 12c, and 12d, the DC bias from the bias supply lines 9 and 10 connected to the Wilkinson divider / combiner 4 and the 180-degree hybrid 62 via the Wilkinson divider / combiner 4 and the 180-degree hybrid 62, respectively. Are supplied respectively. Also,
DC voltage blocking capacitor 8 provided at input / output port
As a result, the DC bias is cut off, and only the high-frequency signal can be passed. Furthermore, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 acts as a resistor for high-frequency signals and acts as an open for DC current.

The double balance mixer 64 supplies a DC bias before and after distributing a high-frequency signal, so that a DC bias supply circuit, which has conventionally required eight lines, is replaced by two.
Become a book. For this reason, the circuit configuration can be simplified,
The time required for layout design is reduced. Further, since there is no mutual influence between the high-frequency signal line and the DC bias supply circuit, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal.

The circuit configuration can be simplified by the high-frequency circuits described in the first to sixth embodiments. Also,
Since the layout is facilitated, the time for circuit design is reduced. Further, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without breaking the balance of the high-frequency signal.

[Brief description of the drawings]

FIG. 1 is a circuit diagram of a Wilkinson amplifier according to a first embodiment of the present invention.

FIG. 2 is a circuit diagram of a balanced amplifier according to a second embodiment of the present invention.

FIG. 3 is a circuit diagram of an image rejection mixer according to a third embodiment of the present invention.

FIG. 4 is a circuit diagram of an image rejection mixer according to a fourth embodiment of the present invention.

FIG. 5 is a circuit diagram of a single balance mixer according to a fifth embodiment of the present invention.

FIG. 6 is a circuit diagram of a double balance mixer according to a sixth embodiment of the present invention.

FIG. 7 is a circuit diagram of a conventional Wilkinson amplifier.

FIG. 8 is a circuit diagram of a conventional balanced amplifier.

FIG. 9 is a circuit diagram of a conventional image rejection mixer.

FIG. 10 is a circuit diagram of a conventional single balance mixer.

FIG. 11 is a circuit diagram of a conventional double balance mixer.

[Explanation of symbols]

 Reference Signs 1a, 1b Transistors 2a, 2b, 3a, 3b Matching Circuit 4, 5 Wilkinson-Type Distributor / Synthesizer 8 DC Voltage Blocking Capacitor 9, 10 DC Bias Supply Circuit 15 Wilkinson-Type Amplifier

Claims (9)

[Claims] A first high-frequency component passing means for passing only a high-frequency component of an input signal; and an output of the first high-frequency component passing means connected to an output of the first high-frequency component passing means. A distributing means for distributing and outputting a plurality of signals with a certain phase difference, a plurality of amplifying means connected to an output of the distributing means, respectively, for amplifying and outputting the output of the distributing means, A combining unit connected to an output of the amplifying unit and combining and outputting the outputs of the plurality of amplifying units with a certain phase difference; connected to an output of the combining unit, and outputting only a high-frequency component of the output of the combining unit. A second high-frequency component passing means for passing therethrough; and the plurality of amplifying means connected to the distribution means and / or the synthesis means, respectively, via the distribution means and / or the synthesis means. DC bias supply and means, high-frequency circuit for supplying a DC bias to each. 2. The in-phase distribution means is connected to an output of the first high-frequency component passing means, and distributes an output of the first high-frequency component passing means into a plurality with a phase difference of 0 degree and outputs the same. Including a distributor, the combining means is connected to the outputs of the plurality of amplifying means, includes an in-phase combiner for combining and outputting the outputs of the plurality of amplifying means with a phase difference of 0 degree,
The high-frequency circuit according to claim 1. 3. The distributing means is connected to an output of the first high-frequency component passing means, and distributes and outputs the output of the first high-frequency component passing means into two with a phase difference of 90 degrees. A plurality of amplifying means including two amplifying means, the combining means being connected to an output of the two amplifying means, and providing an output of the two amplifying means having a phase difference of 90 degrees. The high-frequency circuit according to claim 1, further comprising a 90-degree synthesizer for synthesizing and outputting the signals at a phase difference of 0 degree. 4. A plurality of high-frequency component passing means for respectively passing only high-frequency components of a plurality of input signals, and an output of said high-frequency component passing means connected to an output of each of said plurality of high-frequency component passing means. A plurality of distributing means for distributing and outputting a plurality of phase differences, and connected to a certain output of each of the plurality of distributing means;
A plurality of mixers for frequency-combining and outputting certain outputs of the plurality of distribution units; and a plurality of mixers connected to outputs of the plurality of mixers, and combining and outputting the outputs of the plurality of mixers with a certain phase difference. DC bias supply means connected to the plurality of distribution means or the synthesis means, respectively, for supplying a DC bias to the plurality of mixers via the plurality of distribution means or the synthesis means, respectively. And a high frequency circuit. 5. The plurality of input signals include an input signal having a frequency f1 and an input signal having a frequency f2, and the plurality of high-frequency component passing units pass only high-frequency components of the input signal having the frequency f1. And a second high-frequency component passing means for passing only a high-frequency component of the input signal of the frequency f2, wherein the plurality of distribution means include the first high-frequency component. 90 is connected to the output of the passing means for dividing and outputting the output of the first high frequency component passing means into two with a phase difference of 90 degrees.
A degree divider and an in-phase divider connected to the output of the second high-frequency component passing means for dividing the output of the second high-frequency component passing means into two with a phase difference of 0 degree and outputting the two. Wherein the plurality of mixers are connected to one output of the first distribution means and one output of the second distribution means, and one output of the first distribution means and the second distribution means A first unit mixer for frequency-synthesizing and outputting one of the outputs of the first distribution unit and the other unit output of the first distribution unit and the other output of the second distribution unit; A second unit mixer for frequency-synthesizing and outputting the other output of the unit and the other output of the second distribution unit, wherein the synthesizing unit includes an output of the first unit mixer and the second unit mixer. 2 is connected to the output of the unit mixer of 90-degree synthesis for synthesizing the signal components of | f1-f2 | with the phase difference of 0 degree and outputting the respective output components of the first unit mixer and the output of the second unit mixer. The high-frequency circuit according to claim 4, comprising a vessel. 6. The plurality of input signals include an input signal having a frequency f1 and an input signal having a frequency f2, and the plurality of high-frequency component passing units pass only high-frequency components of the input signal having the frequency f1. And a second high-frequency component passing means for passing only a high-frequency component of the input signal of the frequency f2, wherein the plurality of distribution means include the first high-frequency component. An anti-phase distributor connected to the output of the passing means for dividing the output of the first high-frequency component passing means into two with a phase difference of 180 degrees and outputting the same, and the output of the second high-frequency component passing means And an in-phase distributor for dividing the output of the second high-frequency component passing means into two with a phase difference of 0 degree and outputting the same, wherein the plurality of mixers are one of the first distributing means. The output of the A first unit mixer connected to one output of the first distributing means and frequency-synthesizing and outputting one output of the first distributing means and one output of the second distributing means; The other output of the first distribution means and the other output of the second distribution means are connected, and the other output of the first distribution means and the other output of the second distribution means are frequency-synthesized and output. A second unit mixer for connecting the first unit mixer to the output of the first unit mixer and the output of the second unit mixer. The high-frequency circuit according to claim 4, further comprising: an antiphase combiner for synthesizing a signal component of | f1-f2 | between the output and the output of the second unit mixer at a phase difference of 0 degree and outputting the resultant signal. . 7. A plurality of high-frequency component passing means for passing only high-frequency signals of a plurality of input signals, respectively connected to outputs of the plurality of high-frequency component passing means, and an output of the high-frequency component passing means is connected to a certain point. A plurality of distributing means for distributing into a plurality by the phase difference and respectively outputting, and connected to a certain output of each of the plurality of distributing means,
Receiving a certain output of each of the plurality of distribution means, performing frequency conversion, and outputting a plurality of frequency conversion means, respectively; and Combining means for combining and outputting the signals with a certain phase difference, connected to the plurality of distributing means or the combining means, respectively, to the plurality of frequency converting means via the plurality of distributing means or the combining means. A high-frequency circuit including a DC bias supply unit for supplying a DC bias. 8. The plurality of input signals include an input signal having a frequency f1 and an input signal having a frequency f2. The plurality of high-frequency component passing units pass only high-frequency components of the input signal having the frequency f1. A first high-frequency component passing means, and a second high-frequency component passing means for passing only the high-frequency component of the input signal having the frequency f2, wherein the plurality of distribution means include the first high-frequency component passing means. A first distributing means connected to the output of the first high frequency component passing means for dividing the output of the first high frequency component passing means into two with a certain phase difference, and outputting the divided two outputs; And a second distribution unit for dividing the output of the second high-frequency component passing unit into two with a certain phase difference and outputting the divided two, and wherein the plurality of frequency conversion units are the first distribution unit. One of the outputs and It is connected to one output of the serial second distribution means, one output and said second of said first distribution means
Receiving the output of one of the distribution means, and performing frequency conversion,
A first frequency converting means for outputting, the other output of the first distributing means and the other output of the second distributing means being connected to the other output of the first distributing means and the A second frequency converter for receiving the other output of the second distributor, performing frequency conversion, and outputting the second output. The synthesizing unit includes an output of the first frequency converter and the second frequency. 8. A phase difference synthesizing means connected to an output of the converting means for synthesizing an output of the first frequency converting means and an output of the second frequency converting means with a certain phase difference and outputting the result. 2. The high-frequency circuit according to 1. 9. The first distribution means is connected to an output of the first high-frequency component passing means, and distributes an output of the first high-frequency component passing means into two with a phase difference of 0 degree and outputs the two. The second high frequency component passing means is connected to the output of the second high frequency component passing means, and the output of the second high frequency component passing means is divided into two with a phase difference of 180 degrees. An anti-phase distributor for distributing and outputting, the phase difference synthesizing means being connected to an output of the first frequency converting means and an output of the second frequency converting means,
9. The anti-phase synthesizer according to claim 8, further comprising: an anti-phase synthesizer for synthesizing an output of the first frequency converter having a phase difference of 180 degrees and an output of the second frequency converter with a phase difference of 0 degrees and outputting the resultant. High frequency circuit.