JPH09252582A - Power supply means, driving circuit for capacitive load and controllable switching means, insulated switching circuit for unidirectional, bidirectional, 3-terminal, 3-terminal bidirectional, multiterminal, multiterminal bidirectional multiterminal changeover bidirectional types, ignition power distribution circuit, switching circuit, 3-terminal switching circuit, ignition device, insulated power supply means, and insulated switching circuit - Google Patents

Abstract

PROBLEM TO BE SOLVED: To supply a voltage whose polarity is opposite to the polarity of a DC power supply and which is higher than the power supply voltage to a load by a method wherein N capacitors are connected in parallel to each other through respective pairs of irreversible control switching means when a DC power supply is outputted and the parallel connection of the N capacitors is switched to the series connection through N+1 current limiting means when the DC power supply output is interrupted. SOLUTION: When a switch 26 is closed, a DC power supply 1 charges respective capacitors 8 through diodes (irreversible control switching means) 4 and 5 and, at the same time, supplies a DC voltage to a load 41. When the switch 26 is opened, the respective capacitors 8 in a series connection state supply a double voltage with a reverse polarity to the load 41 through 3 resistors (voltage limiting means) 10. With this constitution, the switching frequency of the switch 26 can be increased and, further, the circuit construction can be simplified.

Description

Detailed Description of the Invention

[0001]

[Technical Field] In the first invention, a DC voltage output means (eg, a series circuit of a DC power supply and a switching means capable of turning on and off) alternately outputs or does not output a DC voltage. Only, the DC voltage and the reverse polarity voltage having a magnitude larger than the DC voltage (eg: ~ 2 times ~ tens of times ~ hundreds of times ~) are alternately supplied to the load, or the DC voltage is supplied once. The present invention relates to a power supply means capable of supplying a load with a reverse polarity voltage having a magnitude equal to or higher than the magnitude of a DC voltage at once by simply outputting. Use this to load capacitive loads (eg:
Capacitance between gate and source, piezoelectric element, liquid crystal, electroluminescence, etc. ) Drive circuit and controllable switching means (eg: various transistors, various thyristors).
It is also possible to easily configure the drive circuit of the above. In the case of the drive circuit of the controllable switching means, the forward bias voltage or the forward bias current is supplied to the controllable switching means or the reverse bias voltage or A reverse bias current can be supplied or supplied.

Further, when the drive circuit of the controllable switching means is used, various insulated switching circuits and ignition distribution circuits which can be insulated conditionally or unconditionally, and various non-insulated switching circuits, etc. Can also be configured. Therefore, the first invention is a switching circuit,
It can be used in a wide range of fields such as power conversion circuits, charge pumps, piezoelectric elements, various drive circuits such as liquid crystals and electroluminescence, analog circuits, digital circuits, logic circuits, relays, electronic exchanges, and ignition devices. Incidentally, the ignition distribution circuit means, for example, a predetermined ignition discharge of the ignition discharge gap means connected to the secondary side of each of a plurality of ignition coils (ignition step-up transformers) in an internal combustion engine ignition device or the like. It is a circuit that supplies a high voltage only to the gap means. Further, when the primary coil of the ignition coil is used as the load of the power supply means of the first aspect of the invention and the magnitude of the reverse polarity voltage is set to, for example, several hundreds of volts, an ignition device combining a current interruption type and a CDI type is constructed. You can

A second aspect of the present invention is such that a DC voltage output means (eg, a series circuit of a DC power source and a switching means capable of turning on and off) alternately outputs a DC voltage and does not. A voltage higher than the DC voltage (eg: ~ 2 times ~ several tens of times ~ several hundred times ~) is supplied, or a voltage higher than the DC voltage (eg: ~ 2 times ~ several tens of times ~)
The present invention relates to a power supply means capable of supplying or supplying a reverse polarity voltage of several hundred times. In particular, the drive means can be simplified by reducing the number of controllable switching means as its constituent elements, or by eliminating the need to prevent a plurality of controllable switching means from being turned on at the same time, that is, eliminating the risk of a power supply short circuit. Power supply means that can be.

[0004]

BACKGROUND OF THE INVENTION DC voltage output means (eg, a series circuit of a DC power source and switching means capable of turning on and off, a solar cell or a photovoltaic diode array for outputting a DC voltage depending on the presence or absence of incident light). , A combination of a light source and a light transmitting / shielding device capable of transmitting or blocking the light and a photovoltaic device, etc.) outputs a DC voltage or does not output a DC voltage. A conventional power supply means for supplying a voltage is shown in FIG. Prior Art: JP-A-5-304454, Japanese Patent Application No. 5-66
165, Japanese Patent Application No. 6-313959. In the circuit of FIG. 2, when the switch 26 is on, the DC power supply 1
Supplies a voltage to the load 41 and at the same time charges the capacitor 8 (capacitance means for supplying a reverse voltage). Then, when the switch 26 is turned off, the capacitor 8 supplies the voltage having the opposite polarity to the load 41 to the load 41 through the resistors 10 and 11 (current limiting means).

Instead of the resistor 10 or 11, the switch 26 may be replaced with a switching means whose ON / OFF is controlled oppositely. The load 41 is a capacitive load (eg, gate-source capacitance, piezoelectric element, liquid crystal,
Electro luminescence, etc. ), The current limiting action of the switch 26 (eg, ON resistance, contact resistance, bipolar
Current limiting action due to saturation of collector current of transistor or IGBT. ) Is insufficient, a “series circuit of a switch, such as a resistor, a resistance means, a constant current means, a coil or a current limiting means, and the switch 26” may be used instead of the switch 26, or instead of the diode 4 or 5. A series circuit including a diode and a resistor, a resistance means, a constant current means, a coil or a current limiting means may be used. further,
Instead of the switch 26, any switching means that can be turned on and off can be used, such as a semiconductor switch, a mechanical switch, a contact, a relay, or an on / off function controllable switching means.

However, the reverse polarity voltage has the same magnitude as the power supply voltage, and a reverse voltage larger than the power supply voltage cannot be supplied. For example, power M
Using the gate-source capacitance of the OS • FET as a load, the DC power supply 1 gates it during the ON period of the switch 26 to reverse-bias it and control it OFF, and during the OFF period of the switch 26, the capacitor 8 gates it. In the case of forward biasing and on-control, if the power supply voltage is smaller than the gate forward bias voltage, sufficient gate forward bias cannot be performed. Even if the power supply voltage is about the same magnitude as the gate forward bias voltage, the voltage of the capacitor 8 is increased at the time of the forward bias due to the rise of the gate voltage (in the case of the N-channel type, the fall in the case of the P-channel type). Since the voltage difference between the gate voltage and the gate voltage disappears, the rise of the gate voltage becomes slower and the turn-on becomes slower. Therefore, it is necessary to supply a reverse voltage larger than the power supply voltage.

On the other hand, even if the gate voltage is controlled to be off by zero, a diode is connected between the gate and the source to clamp the reverse voltage, the power supply voltage is set to the reverse voltage, and the reverse voltage is applied via a resistor. When the gate-source capacitance is discharged, the fall (or rise) of the gate voltage becomes sharper and the turn-off becomes faster. In this case, the power supply voltage may be smaller than the gate reverse bias voltage, and it is meaningful to reverse the power supply voltage and apply it between the gate and the source. There is a need for power supply means capable of supplying a large positive voltage.

When a voltage is applied to the piezoelectric element such as a piezoelectric element due to a hysteresis characteristic and the like and then the voltage is set to zero and the voltage does not return to the original value, a slight reverse voltage is applied to the original voltage. May be returned to. Further, in the case of constructing a powerful ignition device combining a current interruption type ignition device using a direct current of 12 V as a power source and a CDI type ignition device using a charging voltage of several hundreds V, the power supply means of FIG. 2 is not useful. After all, there is a need for a power supply means capable of supplying a small reverse voltage and a larger positive voltage. Therefore,
There is a problem that "it is desired to be able to output a reverse polarity voltage having a magnitude larger than the output voltage of the DC voltage output means". ( problem )

[0009]

SUMMARY OF THE INVENTION Therefore, an object of the first invention is to provide a power supply means capable of outputting a reverse polarity voltage which is larger in magnitude than the output voltage of the DC voltage output means.

[0010]

2. Description of the Related Art As a conventional technique, a direct current voltage output means (eg, a series circuit of a direct current power source and a switching means that can be turned on and off, a solar cell or a photovoltaic device that outputs a direct current voltage depending on the presence or absence of incident light). A power diode array, a light source and a combination of a light transmitting / shielding means and a photovoltaic means capable of transmitting or blocking the light) outputting or not outputting a DC voltage, or There are various power supply means such as a charge pump that outputs a voltage of the same polarity or a reverse polarity which is equal to or higher than the magnitude of the DC voltage (for example, ~ 2 times) according to the switching on / off of each switching means. Prior art: JP-A-48-60227, JP-A-49-
No. 135128, Jitsukai Sho-410, No. 6-67182. Two power supply means for boosting the voltage three times are shown in FIGS. Both circuits have three capacitors and transistor 10
1 and the transistor 102 are controlled so as not to be turned on at the same time by using an insulation transformer, a pair of light emitting / receiving diodes, or an insulation driving means using a piezo coupler or the like. (Reference: FIG. 8 of JP-A-6-225518)
~ Insulation drive means shown in each of Figs. 10, 69, and 71. ) In either circuit, some or all of the diodes in the circuit may be replaced by controllable switching means such as various transistors or various thyristors. In this case, controllable switching in which this or these diodes are replaced is possible. The means is turned on at the same time as the transistor 101, and turned off so that the transistors 102 are not turned on at the same time. In addition, the transistor 101
There is also a method of electromagnetically driving the contacts at the same time by using a make contact instead of each other and using a break contact instead of each of the transistors 102, or using a make contact and a break contact instead of each other. However, it should be noted that there is a risk of power supply short circuit due to welding of contacts and delay of switching on and off.

However, in any conventional circuit, the ON control of the transistor 101 is kept waiting until all the transistors 102 are turned off in order to prevent the power supply short circuit, and the ON control of each transistor 102 is turned off by the transistor 101. I have to wait until
That is, there is a first problem that "the switching frequency cannot be increased" because a rest period in which all the transistors are off must be provided.
(Problem No. 1) Even when an electromagnetic contact relay is used, it is necessary to provide a period during which all the contacts are off to prevent a power supply short circuit, so driving of those contacts will be delayed.

Moreover, there is a second problem that "the driving means has a complicated structure" having the function of preventing the power supply short circuit. (Second problem) In particular, as the voltage boost rate increases, the transistor 10
Since the number of 2 also increases, the structure of the driving means becomes complicated. When using an electromagnetic contact relay, whether all contacts are driven by one electromagnetic coil or multiple electromagnetic coils are connected in series or in parallel using multiple relays, the make contact and break contact are turned on at the same time. Since it is necessary to control the driving so as not to do so, the driving means becomes complicated as expected.

[0013]

SUMMARY OF THE INVENTION An object of the second invention is to provide a power supply means which can cope with an increase in switching frequency and which can simplify the structure of the driving means.

[0014]

DISCLOSURE OF THE INVENTION In the first invention, when a plurality of predetermined numbers are set to N, a load and N capacitance means are connected in series to form a closed circuit. The closed circuit is formed by connecting means one by one, and the load, the N capacitance means and (N + 1) pieces are provided between both output terminals of the DC voltage output means capable of outputting or not outputting the DC voltage. When the current limiting means are connected in parallel to form a parallel circuit, each of the N sets of series circuits in which two uncontrollable switching means are connected in series so as to sandwich each capacitance means in the same direction, Between both output terminals, directly, or on the plus output terminal side, through the uncontrollable switching means of the capacitance means having a lower potential than itself during series discharge, or minus At the output terminal side, the power supply means forms the parallel circuit while connecting in the forward direction with respect to the DC voltage through the uncontrollable switching means of the capacitance means having a higher potential than itself during series discharge. is there. The number of the non-controllable switching means is two.
It is N.

By this, when the DC voltage output means is outputting a DC voltage to the load, it simultaneously connects the N capacitance means in parallel via each pair of the uncontrollable switching means. Charge all at once. On the other hand, when the DC voltage output means does not output a DC voltage, each capacitance means applies a reverse voltage to each uncontrollable switching means by its charging voltage to bring it into an OFF state. Capacitance means supplies a voltage opposite to the DC voltage to the load through the (N + 1) current limiting means. When the DC voltage is not output, a series circuit of N (≧ 2) capacitance means supplies the “sum of all charging voltages” larger than the DC voltage to the load in reverse polarity.
As a result, even if only one DC voltage output means is used, it supplies a positive voltage or a negative voltage to the load according to whether or not it outputs a DC voltage. Alternatively, a reverse voltage having a magnitude equal to or higher than that of the DC voltage (up to 2 times to tens of times to hundreds of times) can be supplied to the load. (effect)

When the uncontrollable switching means (eg, diode) is connected to the load so as to prevent the direct current voltage from being applied to the load, the polarity is opposite to the output voltage of the direct current voltage output means. Can only be supplied to the load. If each of the current limiting means limits the upper limit of the flowing current when the DC voltage is output, a resistance means, a constant current means, an inductance means having an internal resistance, a negative resistance means, or Any combination of these may be used. Further, as examples of the uncontrollable switching means, a diode, a PN junction, "a bipolar transistor having a collector and a base connected", "a reverse-blocking thyristor having an anode and a cathode gate or an anode gate and a cathode connected", and "drain" -Normally-off type MOS-FE in which the back gate potential is controlled so that no forward voltage is applied between the back gate and between the source and back gate, and the drain and gate are connected.
"T" etc. Then, in the power supply means according to the fifteenth aspect of the present invention, the direct current voltage output means is constituted by a series circuit of a direct current power supply and a switching means capable of turning on and off, and this switching means can be turned on and off. Any switching means such as a semiconductor switch, a mechanical switch, a contact point, a relay, an on / off function controllable switching means may be used. In this case, if the switching means is turned on and off only once, if the operation is ideal, it is possible to output a reverse polarity voltage that is more than twice the supply voltage (eg, 2 times to several tens times to several hundred times). become.

[0017]

DISCLOSURE OF THE INVENTION In the second invention, when a plurality of predetermined numbers are set to P, when P first capacitance means are connected in series to form a first series circuit, current flows between them. The first series circuit is formed by connecting the limiting means one by one, and P capacitance means and (P-) are provided between both output terminals of the DC voltage output means capable of outputting or not outputting a DC voltage. 1) When connecting the current limiting means in parallel to form a parallel circuit, two uncontrollable switching means are connected in series in the same direction so as to sandwich each capacitance means. Between each of the output terminals, directly, or on the positive output terminal side, through the uncontrollable switching means of the capacitance means having a lower potential than itself during series discharge, or before the minus. On the output terminal side, the power supply means forms the parallel circuit while being connected in the forward direction to the DC voltage through the uncontrollable switching means of the capacitance means having a higher potential than itself during series discharge. ..

Thus, when the DC voltage output means outputs a DC voltage, it simultaneously charges the P capacitance means in parallel through each pair of the uncontrollable switching means. On the other hand, when the DC voltage output means is not outputting a DC voltage, each capacitance means is turned off by applying a reverse voltage to each uncontrollable switching means by its charging voltage, and (P -1) Since the P current limiting means are in series with the P capacitance means, the sum of all charging voltages (ideally, P times the magnitude of the DC voltage) is (P-1). Is output via the current limiting means. Therefore, even if the DC voltage output means outputs or does not output the DC voltage only once, it is possible to output the same polarity voltage or the opposite polarity voltage having a magnitude higher than the DC voltage.

In the conventional circuit, a current limiting means (eg, a resistance, a negative resistance means, a controllable switching means, etc.) is used instead of the controllable switching means which has to control the drive while preventing a power source short circuit. Since there is no fear of a power source short circuit, it is possible to easily switch between outputting and not outputting a DC voltage. 』
(Effect of the first aspect) Even in the case of the power supply means according to claim 75, since there is only one switching means for on / off driving, there is no fear of power supply short circuit, and there is no on / off switching like the conventional circuit. Since it is not necessary to provide an idle period for turning off all switching means at times, the switching frequency can be increased. Further, in the case of the power supply means or the like according to claim 76, 77 or 78, although there are a plurality of switching means for ON / OFF driving, since they are controls for simultaneously ON-driving all of them, there is no possibility that these will cause a power supply short circuit or the like. Similarly, the switching frequency can be similarly increased.

Further, since the current limiting means is used, it is not necessary to drive and control the current limiting means in synchronism with the switching for outputting or not outputting the DC voltage, so that the whole "driving means is simple". become. 』
(Second effect)

Incidentally, these three are connected in series between both output terminals of the power supply means of the second invention so that the load is sandwiched by two additional current limiting means, and these three are connected to both outputs of the DC voltage output means. If the terminals are connected in parallel, the power supply means becomes the same as the power supply means of the first invention, and the effects of the first invention described above are obtained. If each of the current limiting means limits the upper limit of the flowing current when the DC voltage is output, a resistance means, a constant current means, an inductance means having an internal resistance, a negative resistance means, or Any combination of these may be used. Furthermore, as an example of the uncontrollable switching means, a diode, a PN junction, a "bipolar transistor in which a collector and a base are connected",
"A reverse-blocking thyristor that connects the anode and cathode / gate or the anode / gate and cathode", "Controls the back gate potential so that no forward voltage is applied between the drain and back gate, and between the source and back gate,
Normally-off type MOS with drain and gate connected
・ There are "FET" etc. Then, the second invention is claim 75.
In the case of the power supply means described above, the DC voltage output means is constituted by a series circuit of a DC power supply and a switching means that can be turned on and off.
Any switching means that can be turned off may be a semiconductor switch, a mechanical switch, a contact, a relay, an on / off function controllable switching means. In this case, even if the switching means is turned on and off only once, it is possible to output the same polarity voltage or a reverse polarity voltage equal to or higher than the supply voltage (eg, ~ 2 times to several tens times to several hundred times). .

[0022]

BEST MODE FOR CARRYING OUT THE INVENTION The present invention will be described in more detail with reference to the accompanying drawings. The embodiment of FIG. 1 is an embodiment of the first and second inventions,
It corresponds to the power supply means or the like described in claims 1, 2, 15, 61, 62 or 75. Then, each corresponds to each of the above-described components as follows. a) The series circuit of the DC power supply 1 and the switch 26 serves as the above-mentioned DC voltage output means. b) The DC power supply 1 is the first DC power supply according to claim 15 or 75. c) The switch 26 is the third switching means according to claim 15 or 75. d) With N = P = 2, the capacitor 8 becomes the aforementioned capacitance means. e) The load 41 is the load of the first invention described above. f) The resistor 10 serves as the aforementioned current limiting means. g) Diodes 4 and 5 are the above-mentioned uncontrollable switching means.

The operation is as follows. Switch 26
Is ON, the DC power supply 1 charges both capacitors 8 via the diodes 4 and 5, and simultaneously supplies a DC voltage to the load 41. After that, when the switch 26 is turned off, both capacitors 8 connected in series supply the load 41 with the doubled voltage of the opposite polarity to the load 41 through the three resistors 10.

The connection positions of the DC power supply 1 and the switch 26 may be opposite to each other. If the load 41 is a capacitive load and the current limiting action of the switch 26 (eg, current limiting action due to ON resistance, contact resistance, saturation of collector current of bipolar transistor or IGBT, etc.) is insufficient, the load of the switch 26 is reduced. Instead, a series circuit of a resistor, a constant current means, a resistance means, a coil, an inductance means or a current limiting means and a switch 26 may be used. Alternatively, a series circuit of "a resistor, a constant current means, a resistance means, a coil, an inductance means or a current limiting means" and a diode may be used instead of the diode 4 or 5. Further, as a current limiting means instead of the resistor 10, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, resistance means, constant current A combination of a diode, a bipolar transistor in which a resistor or a constant current diode is connected between its collector and base, a constant current means, a coil or an inductance means and "on / off period control means for controlling the on period and off period of the switch 26". A series circuit of the inductance means and the “resistance, constant current means or resistance means”, a negative resistance means, or a combination of at least any two of these may be used. Then switch 2
If it is a switching means that can be turned on and off instead of 6, it can be turned on by a semiconductor switch, a mechanical switch or a relay.
Any off-function controllable switching means can be used.

The embodiment of FIG. 5 is a case where the number of capacitors is three or more. In the embodiment of FIG. 6, the coil 103 is connected at the position shown in FIG. 6 in order to limit only the magnitude of the charging current of both capacitors 8. In the embodiment of FIG. 7, the magnitude of the supply current of the DC power supply 1 is limited by the coil 103. In the embodiment of FIG. 8, the coil 10 is used as each current limiting means.
The series circuit of 3 and the resistor 10 is used one by one, and the excitation energy of the three coils 103 is also added when the capacitor 8 is serially discharged, so that a reverse voltage of twice the power source voltage or more is supplied to the load 41. You can

In each of the embodiments shown in FIGS. 1 and 5 to 8, when the switch 26 is turned on, a current flows through each resistor 10 and energy is consumed, but if each resistance value is increased to reduce it, There is a problem that a voltage drop due to each resistor 10 becomes large when the capacitor 8 or the like supplies the DC voltage to the load 41 during the OFF period of the switch 26. Therefore, in each of the embodiments shown in FIGS.
The variable current limiting means whose current limiting action is changed by turning on or off 3, 44 or 51 or the switch 26 is used as the above-mentioned current limiting means, and when it is on, the current limiting action becomes large, When it is off, its current limiting effect is small. As a result, the energy consumed by each current limiting means when it is on and the voltage drop by each current limiting means when it is off can be reduced in these embodiments.

The embodiment shown in FIG. 11 has the following features:
In the embodiment of FIG. 1, a normally-on transistor 53, a Zener diode 54 and a resistor 18 (or a resistor 55) may be used as current limiting means instead of each resistor 10 in the embodiment of FIG. .)
Is a power supply means using one variable current limiting means formed by each. Each corresponds to the following as follows. a) The transistor 53 is the first switching means in claim 5. b) The Zener diode 54 is the first in claim 5.
To the voltage drop means of. c) The resistor 18 is the on-control means according to claim 5 and the resistor according to claim 11. d) The resistor 55 is the on control means and the first voltage drop means in claim 5, and the on control means (resistance) in claim 10.

The resistor 56 does not have to be connected. In this case, the capacitor 8 while the switch 26 is on.
Switch 26 is turned off before it is fully charged and its charging current cannot produce sufficient reverse bias voltage in zener diode 54. Alternatively, it is okay if the leakage drain current of transistor 53 causes a reverse bias voltage on zener diode 54 if not. At this time, the leak drain current causes a voltage drop (reverse bias voltage) generated in the Zener diode 54 and the leak drain current which the reverse bias voltage acts on the transistor 53 to pass therethrough, and influences each other, thereby maintaining a certain equilibrium state. Calm down. In addition, FIGS.
In each of the embodiments, a genuine thyristor or S1 thyristor may be used instead of the equivalent thyristor formed by PNP and NPN.

By the way, in each of the embodiments shown in FIGS. 1 and 5 to 14, if a capacitive load is used as the load 41, these power supply means become a driving circuit for the capacitive load. Examples of capacitive loads include piezoelectric elements, liquid crystals, electroluminescence,
Voltage-driven switching means (MOS / FET, IGB
T) etc. If controllable switching means is used for the load 41, these power supply means can supply forward bias voltage or forward bias current or reverse bias voltage or reverse bias current to the controllable switching means. It constitutes a drive circuit of the control switching means.
A drive circuit for controllable switching means such as these, or a one-way isolated switching circuit, a bidirectional isolated switching circuit, a three-terminal isolated switching circuit, a three-terminal bidirectional isolated switching circuit using these , Non-isolated switching circuit or non-isolated 3
Each embodiment of the terminal switching circuit is shown in FIGS.

The embodiment shown in FIG. 15 has the following features:
Power source means according to claim 6, 8, 11 or 15, or claim 2.
It corresponds to the drive circuit of the controllable switching means described in 3 and the like, and if it has the diodes 6 and 12, it corresponds to the one-way insulating switching circuit described in claim 24 or 25. Each corresponds to each as follows. a) The DC power supply 1 is the first DC power supply in claim 15. b) The transistor 51 is the third switching means in claim 15. c) The transistor 2 is the fifth switching means in claim 23. d) Both capacitors 8 and the capacitance between the gate and the source are in the aforementioned capacitance means and the aforementioned load. e) An equivalent circuit of three thyristors is provided in each of the current limiting means described above or the first switching means in claim 5. f) The diodes 4, 5, etc. are the uncontrollable switching means of each pair described above. g) The diodes 6 and 12 are the second (2N)
+1), to the (2N + 2) th uncontrollable switching means. h) The built-in diode of the transistor 2 is the (2N + 3) th uncontrollable switching means in claim 25. i) A transistor 2 having a built-in antiparallel diode.
5. One-way controllable two-way switching means described in 5. j) A unidirectional switching means according to claim 24, wherein a series circuit of the transistor 2 and the diode 12 is used.

The operation is as follows. When the transistor 51 is on, the DC power supply 1 charges both capacitors 8 in parallel via the diodes 4 and 5 and the transistor 51,
At the same time, the gate of transistor 2 is reverse biased via transistor 51 (with diode 6). Then, when the transistor 51 is turned off, both capacitors 8 gate-bias the transistor 2 through the three equivalent thyristors. Therefore, it can be considered that both capacitors 8 function as a power supply capacitor, and the DC power supply 1, the transistor 51, the diodes 4, 5 and both capacitors 8 constitute another DC power supply. Therefore, one DC power supply is used. The transistor 2 can be forward-biased or reverse-biased even if only used.

When a bipolar transistor is used instead of the transistor 51, if its current limiting action (saturation of collector current) is insufficient, its base current may be reduced, or instead of that transistor. "Resistance, resistance means or constant current means" and bipolar
A series circuit of transistors may be used. Further, as the fifth switching means in the twenty-third aspect, any controllable switching means can be used instead of the transistor 2 regardless of normally-on / off, regardless of presence / absence of the self-turn-off function. If the forward and reverse bias voltage polarities of the drive signal are the same as the transistor 2, it turns on when the transistor 51 is off. on the other hand,
If the forward and reverse bias voltage polarities are opposite to those of the transistor 2, such as PNP type transistor and P type MOS.FET,
The on and off operations are opposite. Replacing some of its components like these. A new embodiment (derivative embodiment) can be made from the embodiment of FIG. This also applies to the other embodiments.

When the diode 6 is provided in the embodiment of FIG. 15, the source potential of the diode 6 can be changed with respect to the DC power supply 1. The connection position of the diode 6 may be between the connection point between the anodes of the diodes 4 and the DC power supply 1 and the DC power supply 1 in addition to the connection position shown in FIG. When the diodes 6 and 12 are provided in the embodiment of FIG. 15, this embodiment corresponds to the one-way isolated switching circuit according to claim 24 or 25, and includes a transformer, a light emitting / receiving diode pair, and a piezo coupler. Without using isolation means such as transistor 2 and diode 12
There is an effect that a unidirectional controllable switch in which is connected in series can be used as an isolation switch while being conditional. (Additional effect)

Specifically, "switch terminals S1, S
2 As long as both potentials are higher than the positive power supply terminal potential of the DC power supply 1, that is, "as long as the diode 4 or 6 and the diode 12 or the built-in diode of the transistor 2 are not simultaneously turned on," the DC power supply 1
And the switch terminals S1 and S2 are always in an insulating state. However, the electrostatic capacitance between both main electrodes such as the electrostatic capacitance between each anode and cathode, and the leakage current when the switching means is turned on and off are ignored.

The operation is as follows. When the transistor 51 and the diodes 4 and 6 are on, the transistor 2, the built-in diode and the diode 12 are off, so that the switch terminals S1 and S2 and the DC power supply 1 are insulated. On the other hand, when the transistor 51 and the diodes 4 and 6 are off and the transistor 2 is on, the connection between the DC power source 1 and the transistor 2 side is cut off.
1, S2 and DC power supply 1 are insulated. Therefore, the DC power supply 1 and the switch terminals S1 and S2 are always insulated under the above-mentioned conditions. Can be used.

If there are diodes 6 and 12 in the embodiment of FIG. 15 and the potential of the DC power supply 1 is stable, another "transformer, light emission, light receiving diode pair, piezo coupler, etc." The effect that the isolation switch used does not have, that is, "both switch terminals S when it is off"
This embodiment also has the effect of "shield function between 1 and S2".
(Additional Effect) Because, when the transistor 51 is on, its source is directly connected to the DC power source 1 via the diode 6 and its source potential is fixed, and its gate is also the transistor 5.
This is because the gate potential is fixed by being directly connected to the DC power source 1 via 1 or the like, so that the switch terminals S1 and S2 are shielded. As a result, the leakage current or displacement current of the transistor 2 or the diode 12 does not directly flow between the switch terminals S1 and S2, and the DC power supply 1
Flows toward.

This effect is the same as that of the present invention including the embodiment of FIG. 15 except for the diode bridge connection type bidirectional isolation type switching circuit according to claim 30 to which the embodiment of FIG. 16 corresponds. There is an insulation type switching circuit, but if the one-way property and the bidirectional insulation type switching circuit to which it is applied are used for an electronic exchange for wired communication and wired communication, it is useful for preventing leakage of communication and communication. In particular, if the capacitance between both switch terminals of the insulating switch used as the frequency becomes higher cannot be ignored, the conventional technique cannot deal with it, and the above-mentioned effect is significant.

By the way, instead of the diode 4 or 5, a resistor, a bidirectional constant current means or a different kind of uncontrollable switching means may be used. Their role is to allow the capacitor 8 to forward bias the transistor 2 with its discharge energy when the transistor 3 is off. However, if the uncontrollable switching means is not used at the diode 4, even if the diodes 6 and 12 are connected, this circuit cannot be used as an isolation switch.

Therefore, in order to form a one-way insulating switching circuit or various insulating switching circuits described later from the drive circuit of the controllable switching means of the present invention, the third switching method according to claim 15 is used. It is necessary that the ON / OFF of the means and the ON / OFF of the fifth switching means in claim 23 are reversed. That is, when the third switching means is on, the first DC power supply in claim 15 must reverse bias the fifth switching means. Further, the diode 6 (4) and the diode 12 are connected in series in the same direction,
(4) and the built-in diode of the transistor 2 need to be connected in series in the same direction. Reference: JP-A-5-226998, JP-A-5-26598
268037, JP-A-5-304453-4,
JP-A-6-196991, JP-A-7-264030
No. 7-307654.

In the embodiment of FIG. 15, the diodes 6, 1
2 is connected and the second DC power supply is connected between the drain of the transistor 2 and the positive power supply terminal of the DC power supply 1 with both power supply voltage directions aligned, this embodiment corresponds to the switching circuit according to claim 52. Will come to do. If another controllable switching means is connected between the switch terminal S2 and its positive power supply terminal, it becomes a three terminal switching circuit. If two unidirectional insulating switching circuits shown in FIG. 15 are connected in antiparallel at both switch terminals, this embodiment corresponds to the bidirectional insulating switching circuit according to claim 31 or 32. Will come to do. Furthermore, when two unidirectional isolated switching circuits shown in FIG. 15 are connected in series at the switch terminals in the same direction, inward, or outward, the present embodiment provides claim 38.
Alternatively, it corresponds to the three-terminal insulated switching circuit described in 39 or the like.

The embodiment of FIG. 16 is a bridge connection type bidirectional insulating switching circuit using the embodiment of FIG. 15 and corresponds to the bidirectional insulating switching circuit according to claim 30. The embodiment of FIG. 17 corresponds to the bidirectional isolation type switching circuit according to claim 27, and even if the characteristics of both transistors are not uniform, the base current can be evenly distributed. The embodiment of FIG. 18 is a bidirectional isolated switching circuit using the embodiment of FIG.
It can be applied even if the forward bias voltage and forward bias current of NP and PMOS are different. The embodiment of FIG. 19 corresponds to the bidirectional insulating switching circuit according to claim 27 and can be applied even if the forward bias voltage and forward bias current of the PNP and PMOS to be combined are different. If the capacitance of the bottom capacitor in the figure is increased, it is convenient for the base forward bias current that consumes a large amount of current, and each charge energy can be used efficiently. The embodiment shown in FIG. 20 corresponds to the bidirectional isolation type switching circuit according to claim 29, 35 or 36. (Reference: JP-A-60-1703
22 and 22. )

When one of the above-mentioned one-way isolated switching circuit and any one of the two-way isolated switching circuits are connected in series at the switch terminal, they are insulated by the three-terminal insulation according to claim 40 or 41. Type switching circuit, etc., and if any two of the above-mentioned bidirectional insulating type switching circuits (the same two or different two may be connected) are connected in series at the switch terminals, these will be It corresponds to the three-terminal bidirectional insulating switching circuit according to claim 42 or 43.

The embodiment of FIG. 21 is the power supply means according to claim 1 or 56, the insulated power supply means according to claim 57, and the 59th embodiment.
The capacitive load driving circuit described above or the insulated switching circuit according to claim 60 corresponds to the present invention. The embodiment of FIG. 22 corresponds to the power supply means according to claim 1, the insulated power supply means according to claim 58, the drive circuit for the capacitive load according to claim 59, the insulation type switching circuit according to claim 60, and the like.

The embodiment of FIG. 136 is a switching circuit in which the gate of the MOS.FET is grounded, and the power supply means of the first invention drives this NMOS. The gate-source capacitance of the NMOS corresponding to the above-mentioned load (load of the power supply means) is connected between both terminals of the DC power supply and the series circuit of the switch via the load 45 (load of the switching circuit).

Each of the embodiments shown in FIGS. 23 to 39 is an embodiment of the second invention. The above-described embodiments of FIGS. 1 and 5 to 23 are also embodiments of the second invention. In the embodiment of FIG. 23, claim 6
It corresponds to the power supply means described in 1, 62 or 75, the above-mentioned P (the number of capacitance means) is 2, and each corresponds to the above-mentioned respective constituent elements as follows. a) The series circuit of the DC power supply 1 and the switch 26 serves as the above-mentioned DC voltage output means. b) The DC power supply 1 and the switch 26 are the first DC power supply and the third switching means in claim 75. c) The capacitors 8 and 48 are the two capacitance means described above. d) The resistor 10 serves as the aforementioned current limiting means. e) Diodes 4, 5, 46, 47 in the above-mentioned four uncontrollable switching means.

The operation is as follows. Switch 26
When is on, each capacitor 8, 48 is charged to the power supply voltage via each set of diode pairs. Then switch 2
When 6 is turned off, the respective charging voltages of the capacitors 8 and 48 reversely bias the diodes 4, 5, 46 and 47 to keep them in the off state, so that the open output voltage Vo from both output terminals is exceeded.
ut (double the power supply voltage if the operation is ideal) is output. It is the resistor 10 (current limiting means) that makes both the capacitors 8 and 48 connected in series. Since the resistor 10 does not limit the on / off control of the switch 26 at all, the "higher switching frequency of the switch 26" is set. The second effect, including the embodiment of FIG. 23, exists in the second invention. (First effect) When the switch 26 is manually operated, the switching operation can be speeded up.

Moreover, since the switch 26 can be simply turned on and off, the second effect that "the structure of the driving means can be simplified" is the second effect including the embodiment shown in FIG.
It is in the invention.
(Second Effect) When the switch 26 is manually operated, the operation is easy. If an inductive load is connected to this power supply means, the charging voltages of the capacitors 8 and 48 may be inverted, but when the inversion is not convenient, the diodes 49 and 50 may be connected. This also applies to the first invention.

Each of the embodiments shown in FIGS. 24 to 26 is a power supply means in the case where the above-mentioned P (the number of capacitance means) is an arbitrary plural number. The embodiment of FIG. 25 is claimed in claims 61, 63, 65, 7
1 or 75, and the embodiment of FIG. 26 corresponds to the power source means or the like described in claims 61, 63, 65, 66, 69 or 75. (Reference: Japanese Patent Laid-Open No. 2-15
Fig. 1 (c) and Fig. 46 of 3618)

In the embodiment of FIG. 27, if the operation is ideal, the transistor 51 is turned on and off to output a plus voltage four times the power source voltage between the minus power source line and the plus side output terminal. Therefore, the transistor 51 is connected to the negative power source line side, the negative side output terminal is connected to the positive power source line via a resistor (current limiting means), and the positive side output terminal is connected to the diode in the forward direction. It outputs a positive voltage. However, 52 is a power switch. It is also possible to output a voltage three times the power supply voltage between the positive side output terminal and the positive power supply line as in the embodiment of FIG. 28 described later. On the contrary, the transistor 51 is connected to the plus power source line side as in the embodiment of FIG. 30 described later, that is, the series circuit of the DC power source 1 and the transistor 51 reverses the connection position of both, and the plus side output terminal is It is also possible to connect a negative power supply line via a resistor, connect a diode to the negative side output terminal in the forward direction, and output a negative voltage from the diode. These things can be said almost similarly in each of the embodiments shown in FIGS.

In the embodiment of FIG. 28, the above-mentioned P (the number of capacitance means) is an arbitrary plural number, and the embodiment of claims 61 and 6 is provided.
Corresponding to the power supply means described in 3, 65, 71 or 75,
A variable current limiting means composed of a Darlington connection type transistor or the like connects the minus side output terminal and the plus power source line.

In the embodiment of FIG. 29, the above-mentioned P (the number of capacitance means) is an arbitrary plural number, and the embodiment of claims 61, 6
It corresponds to the power supply means described in 3, 65, 66, 68, 71 or 75. Also in this embodiment, the variable current limiting means constituted by the NPN transistor or the like connects the minus side output terminal and the plus power source line.

The embodiment shown in FIG. 30 corresponds to the case where the above-mentioned P is an arbitrary plural number, and it is defined by claim 61, 63, 65, 66, 69 or 75.
Corresponding to the described power supply means, Darlington connection type PN
A variable current limiting means formed by a P-transistor or the like connects the positive side output terminal and the negative power source line, and a negative voltage having a magnitude higher than the power source voltage is output from the negative side output terminal. (Reference: JP-A-2-153
(Fig. 46 of No. 618)

In the embodiment shown in FIG. 31, the astable multivibrator 71 is a power supply means for alternately turning on and off the transistors 51 in the two sets of power supply means of the second invention.

The respective embodiments shown in FIGS. 32 and 33 are defined by claim 15.
The controllable switching means (thyristor), which corresponds to the power supply means described in 16, 17, or 18, and is controlled to be turned on / off in cooperation with turning on / off of the switch 26 instead of each non-controllable switching means, one by one. It is the replaced power supply means. When the switch 26 turns on, each gate controls each thyristor to turn on, and when the switch 26 turns off, each capacitor applies a reverse voltage to each thyristor to control it off. In the embodiment of FIG. 32, one switch (corresponding to the turn-on prevention control means in claim 19) is connected between the gate and cathode of each thyristor on the upper side or the lower side of the figure, and these switches are connected. When some of them are turned on, the thyristor connected to it remains off and the capacitor connected to that thyristor is not charged. As a result, the output voltage at the time of series discharge changes, and the voltage boosting rate can be changed in this way. In that case, it is better to connect one diode to each capacitor in parallel as in the embodiment of FIG. 23 so that the uncharged capacitor does not hinder the discharge.
The fact that the voltage boosting rate is variable can be said also in the embodiment shown in FIG. 33. The resistance between the gates on the anode / cathode side or the resistance between the gates / cathode on the anode side is connected with a resistor (turn-on prevention control according to claim 19). Equivalent to means.)
It is sufficient to replace them one by one with the series circuit of.

The embodiment shown in FIG. 34 is defined by claims 15, 17, and 75.
Alternatively, the controllable switching means (remaining GTO thyristors) corresponding to the power supply means described in 77 or the like is replaced by one non-controllable switching means and one GTO thyristor is controlled to be turned on and off in cooperation with the on / off. Each of them is a power supply means that is directly connected to the DC power supply 1 without passing through one of the GTO thyristors. The switch connected between each gate and the cathode is a turn-on prevention control means. By turning these switches on and off in the same manner as described above, the voltage boosting rate can be variably controlled.

Each of the embodiments shown in FIGS. 36 and 37 corresponds to the power supply means according to the 75th or 77th aspect. 38 and 39
Each of the embodiments corresponds to the power supply means described in claims 75, 77 or 78. The switches connected between the respective gates and sources are ON blocking control means, and the voltage boosting rate can be controlled by turning on these switches as described above.

Each of the switching means shown in FIGS. 40 to 51 is an example of the first switching means which is a constituent element of each invention. In the case of switching means in which two insulated gate type switching means are connected as shown in FIG.
The switching means for DC cannot be constituted by only 5 and 36, and one switching means for DC is constituted by the transistors 35 and 36 and the diode 92 or 93. This means that the diodes 92, 93
If neither is connected, transistors 35, 36
This is because, even when is turned on, the gate and source are galvanically isolated. Therefore, the diode 92
Alternatively, connection of 93 is required, but instead, as circuit elements for passing direct current, other resistors, various resistance means, various constant voltage means, various constant current means, various voltage drop means, various current limiting means, various There is a flow means or a combination of these. On the other hand, in the case of the switching means shown in FIGS. 41 and 42, since there is a gate-source PN junction of the transistor 39 or a base-emitter PN junction of the transistor 29, the transistors 36 and 39 are provided.
Alternatively, only the transistors 36 and 29 can form a switching means for direct current. Of course, as shown in FIGS. 41 and 42, there is also each switching means in which one diode 93 is connected between the source and gate of the transistor 36 in each switching means.

Each of the current limiting means using the switching means shown in FIGS. 43 to 45 is an example of the current limiting means which is a constituent element of each invention, and is defined in claim 3 or claim 6.
It corresponds to the variable current limiting means described in 3. Incidentally, in these variable current limiting means, a plurality of resistors are connected as the ON control means, but if at least one of them is connected, they act as variable current limiting means. Further, in the variable current limiting means shown in FIGS. 44 and 45,
Each Zener diode 33 functions as a bidirectional constant voltage means, and its forward direction constant voltage means is the same as that of the diodes 92 and 93 of the switching means shown in FIG. The voltage means acts as a voltage drop means for reverse bias. Resistance 94, 9
Since 7 also functions as a bidirectional voltage drop means, if these are connected, each Zener diode 33 may be omitted, but it is better to have it as a measure against overvoltage.

Further, in each of the variable current limiting means shown in FIGS. 43 to 45, the transistors 29, 32, 35 and 36 have the same forward and reverse bias voltage polarities of their drive voltages, and the switching having the self-turn-off function. Any means can be used regardless of whether it is normally on or normally off. However, it is necessary to use a voltage drop means having a large voltage drop for the reverse bias in accordance with the required reverse bias voltage. And MOS / FE
As in the case of T or insulated gate type switching means, if the pair of control terminals for inputting the drive signal and the main terminal are insulated from direct current, it will be described in the explanation of each switching means of FIGS. As described above, the flow means in the forward bias direction is required. Each of FIGS. 46 to 51 shows an example of another variable current limiting means. SIT is normally on or normally off.

Then, in the variable current limiting means of FIG. 43, the transistors 29 and 32 form an equivalent circuit of a thyristor, and this equivalent thyristor is a GTO thyristor having a real plus gate and a minus gate or a normally-off SI. It may be replaced with a thyristor, and Fig. 4
Even in the variable current limiting means of 4, the transistors 35 and 36 form an equivalent circuit such as a normally-on SI thyristor, but this equivalent thyristor is replaced by a normally-on SI thyristor having a plus gate and a minus gate. Is also good. Each transistor pair shown in each of FIGS. 47 and 48 is normally on or normally off S.
An equivalent circuit of the I thyristor is constructed.

The embodiment shown in FIG. 52 is a unidirectional or bidirectional insulated switching circuit. In the figure, if a series circuit of Zener diode and diode is connected as shown by the dotted line, the constant voltage means is configured on the output side. Once the predetermined gate forward bias voltage is reached, there is an advantage that the discharge current of the capacitor is narrowed down and the consumption current is saved.

The embodiment shown in the drawing in which both FIGS. 53 and 54 are connected vertically is a three-terminal switching circuit, which corresponds to the switching circuit described in claim 52 or the three-terminal switching circuit described in claim 53.

The embodiment shown in FIG. 55 is an ignition device which incorporates the ignition distribution circuit of the present invention and utilizes a series inverter.
In the figure, 33 is a constant voltage means such as a three-terminal regulator, 34
Is a DC-DC converter circuit that outputs a negative voltage,
35 is a 3-terminal switching circuit, 36 is an ignition power distribution circuit,
Reference numeral 37 is a capacitance variable circuit that changes the capacitance of the commutation capacitor. A circuit diagram of the DC-DC converter circuit 34 is shown in FIG. 60, and a circuit diagram of the three-terminal switching circuit 35 is shown in FIG.
6, FIG. 57 is a combination of the above and lower figures, a circuit diagram of the ignition power distribution circuit 36 is shown in FIG. 56, and a circuit diagram of the capacitance variable circuit 37 is shown in FIG. 59. The embodiment of FIG. 61 is an ignition device with a power distribution function using the three-terminal switching circuit of the present invention. (Reference: JP-A-3-47470)

The embodiment shown in FIG. 62 corresponds to the ignition device according to the forty-fifth aspect of the invention and is an ignition device in which a current interrupting ignition device and a CDI ignition device are combined. A surge absorber that absorbs surge voltage is connected to both ends of the primary coil. For example, if the power supply voltage is 12 volts, the number of capacitors is 44, and the forward voltage of each diode and the on-voltage of each equivalent thyristor (total of 44) are 1 volt, each charging voltage is approximately 10 volts, and the total charging voltage is Is about 440
In volts, the voltage applied to the primary coil by all capacitors is approximately 396 volts. If all capacitors do not discharge at the same time due to variations in the capacitance of each capacitor or variations in each charging voltage, make sure that the capacitors that have completed discharge do not interfere with other discharges. A diode is attached to each capacitor as in the embodiment of FIG.
It is better to connect them in parallel one by one. Alternatively, one diode should be connected in parallel to each equivalent thyristor so that a current may flow backward from the ignition coil to each capacitor. Reverse conduction type GT instead of each equivalent thyristor
You may use one O thyristor at a time.

Each of FIGS. 63 to 88 shows another embodiment of the first or second invention. In the embodiment of FIG. 64, for example, all the switches may be make contacts, or all the switches may be break contacts, but they are simultaneously turned on and off. 89 to 96 each shows one embodiment of the second invention. 97-101 in each figure
Each of the embodiments of the first and second inventions shown here is a thyristor which is controlled to be turned on and off according to the presence or absence of the output of the above-mentioned DC voltage in place of each uncontrollable switching means in each of the embodiments described so far. They are replaced one by one. Each trigger (on control) is done by its output voltage,
Each off control is performed by the reverse voltage applied to each capacitor. 102 to 117, one embodiment of the first invention shown in each of the figures corresponds to the power supply means according to claim 21,
As in the conventional circuit shown in each of FIGS. 3 and 4, each transistor is controlled to be turned on / off in the opposite manner. For example, each transistor may be composed of a make contact and a break contact that are simultaneously driven as described in the description of the conventional circuit. An embodiment is also possible in which each transistor in which each capacitor is connected in series is replaced by one current limiting means (eg, resistance means, negative resistance means, variable current limiting means, etc.).

Each of the embodiments shown in FIGS. 118 and 119 is a unidirectional insulating type switching circuit which can unconditionally insulate each switch terminal from the DC power supply. Embodiments are also possible in which the connections for these capacitors, diodes and constant current diodes or resistors for switching between parallel charging and series discharge for each capacitor are replaced by similar connections used in other embodiments. is there. In each of the examples of FIGS. 118 and 119, the terminals a and c are separated from each other vertically,
A unidirectional or bidirectional isolated switching circuit in which the upper part thereof is replaced by the switching means shown in each of FIGS. 120 to 127 is also possible. However, in the case of the embodiment of FIG. 124, two separate lower drive circuits are required. (Reference: JP-A-7-307654.)

Each of FIGS. 128 to 145 shows one of various switching circuits utilizing the embodiment of the first or second invention. 142 to 145, each of the uncontrollable switching means, which is a component of the present invention, is replaced by a Zener diode one by one, and a positive voltage and a reverse voltage applied thereto are gate-biased. It is a drive circuit of controllable switching means in which a voltage and a gate reverse bias voltage are used. Each of FIGS. 146 to 149 shows a drive circuit of the controllable switching means utilizing the embodiment of the first or second invention. In these, the PN junction between the control terminal and the main terminal, which form a pair for inputting the drive signal, is used as the non-controllable switching means which is a component of the present invention. 150 to 1
51 Each of the figures shows one embodiment in which a plus voltage and a minus voltage larger than the magnitude (absolute value) of the power supply voltage can be output.
If the two switches 26 are turned on at the same time, the power supply is short-circuited.

Finally, the following will be supplemented. a) In each circuit of FIG. 10, FIG. 11, FIG. 13, etc., as the first switching means in claim 5 or 65,
N-channel type FET, MOS FET, IG instead of NPN transistor, NMOS or equivalent thyristor
BT, SIT, plus gate GTO thyristor, S
Any switching means, such as an I thyristor or an NPN type bipolar transistor, which has the same forward / reverse bias voltage polarity of the drive signal as those transistors and has a self-turn-off function can be used. However, it is necessary to increase the voltage drop of the voltage drop means according to the magnitude of the required reverse bias voltage. b) In each circuit of FIG. 9, FIG. 12, etc., claim 5 or 6
As the first switching means in 5, a P-channel type FET, MOS • FET, IGBT, SIT, negative gate GTO thyristor or SI thyristor, etc., instead of a PNP transistor or an equivalent thyristor, is used as a reverse bias of the drive signal. Voltage polarity is transistor 2
Same as 3, any switching means with self-turn-off function can be used. However, it is necessary to increase the voltage drop of the voltage drop means according to the magnitude of the required reverse bias voltage.

C) As the above-mentioned first or second voltage drop means, a resistor, a bipolar transistor having its collector and base connected directly or via a resistor or a diode, and its drain and gate directly or with a resistor or a diode are used. A MOS-FET connected through the control means, a control terminal for inputting the drive signal and a switching means in which the main terminal is connected directly or via a resistor or a diode, and a control terminal forming a pair for the drive signal input Normally-on type switching means connected to the main terminal,
Resistance means, diode, PN junction, non-controllable switch,
A diode or two uncontrollable switches connected in anti-parallel, Zener diode, Zener diode 2
Two connected in series in opposite directions, Zener diode and diode series circuit, constant voltage means, resistor and diode series circuit or parallel circuit, resistor and uncontrollable switch series circuit and uncontrollable switch in antiparallel There are connected ones or a combination of at least two of them. Therefore, an embodiment in which these voltage drop means are used instead in each embodiment is also possible.

D) As the above-mentioned ON control means, a MOS FET or an insulation type FET or SIT in which a resistor, its drain and gate are connected directly or via a resistor or a constant current means, a resistance means, a constant current diode and its collector .Bipolar transistor, constant current means or constant current means connected between bases, constant current means,
There is a current limiting means, or a combination of at least two of these, or the like. Therefore, an embodiment in which these ON control means are used instead in each embodiment is also possible. e) In each embodiment or a derivative embodiment derived from it, each semiconductor switch as a constituent element thereof is replaced with a semiconductor switch having a complementary relationship, and each directional circuit component means (eg, DC power supply, diode, electrolysis). Of course, a circuit having a symmetrical relationship with respect to the original circuit with respect to the voltage polarity with the direction of the capacitor etc.) reversed is also possible.

F) In each of the embodiments shown in FIGS. 21 and 22, the capacitor 8 acts so as to intercept the gate forward bias current of the transistor 2 when it is forward biased, so that the turn-on of the transistor 2 is delayed. On the other hand, transistor 2
Since the charging current of the capacitor 8 at the time of turn-off strongly reverse-biases the transistor 2, the turn-off is fast. Therefore, if two insulated switching circuits of FIG. 21 and FIG. 22 (the same two or different two may be connected) are connected in series to form a three-terminal switching circuit, a short circuit due to simultaneous turn-on hardly occurs. Occurs. g) Another non-controllable switching means is a Zener diode whose reverse voltage magnitude is less than or equal to its Zener voltage magnitude. h) Insulated power supply means using the various insulated switches of the present invention as the insulated power supply means is also possible. (Reference: JP-A-2-327
58, JP-A-2-146955, JP-A-6-225.
No. 518. )

I) The embodiments shown in each of FIGS. 140 and 141 are expressed in the claims as follows. “A first load and a second load are connected in series between the output terminals, and a P-th and a (P +
These are connected in series so that the second load is sandwiched by the current limiting means of 1), and when the DC voltage is not output, the first series circuit outputs a voltage in the opposite direction to the P-th, The power supply unit according to any one of claims 61 to 81, wherein a closed circuit that outputs to the second load via a (P + 1) th current limiting unit is formed. "In the above power supply means, the control terminal of the controllable fifth switching means, the main terminal is the control terminal ct5, and the main terminal mt.
5a, the main terminal mt5b, and when the control terminal ct5 and the main terminal mt5a form a pair for inputting the drive signal thereof, the control terminal ct5 and the main terminal mt5a are connected so that the DC voltage is in the reverse bias direction. A switching circuit, wherein the first load is connected between the main terminal mt5b and the main terminal mt5a as the second load.

[0073]

[Prior art] Jitsukaihei 3-69936,
Japanese Utility Model Publication No. 3-80691, Japanese Patent Application Laid-Open No. 4-170813,
JP-A-5-226998, JP-A-5-2680
37, JP-A-5-304453-4, JP-A-6-196991, and JP-A-6-219389.
issue.

[Brief description of drawings]

─────────────────────────────────────────────────── ───

[Procedure amendment]

[Submission date] March 15, 1996

[Procedure amendment 1]

[Document name to be amended] Statement

[Correction target item name] Brief description of drawings

[Correction method] Added

[Correction contents]

[Brief description of drawings]

FIG. 1 is a circuit diagram showing one embodiment of the present invention.

2 to 4 are circuit diagrams each showing an example of conventional power supply means.

5 to 39 are circuit diagrams each showing one embodiment of the present invention.

40 to 51 are circuit diagrams each showing one example of the constituent elements of the present invention.

FIG. 52 is a circuit diagram showing an embodiment of the present invention.

53 to 54 are both circuit diagrams showing an embodiment of the present invention in combination with each other.

FIG. 55 is a circuit diagram showing a circuit of an ignition device using a plurality of embodiments of the present invention.

56 to FIG. 57. Both figures are combined with each other in FIG.
5 is a circuit diagram showing an embodiment of the present invention used in the ignition device of FIG.

58 is a circuit diagram showing one embodiment of the present invention used in the ignition device of FIG. 55. FIG.

59 is a circuit diagram showing one embodiment of the present invention used in the ignition device of FIG. 55. FIG.

FIG. 60 is a circuit diagram showing an example of a DC-DC converter circuit used in the ignition device of FIG. 55.

FIG. 61 is a circuit diagram showing a circuit of an ignition device using a plurality of embodiments of the present invention.

62 to 119 are circuit diagrams each showing one embodiment of the present invention.

120 to 127 are views corresponding to FIGS. 118 and 119.
3 is a circuit diagram showing one example of each of the constituent elements that can be replaced with the constituent elements in the respective embodiments of FIG.

128 to 151 are drawings showing the first embodiment of the present invention.
It is a circuit diagram shown one by one.

[Explanation of Codes] 33 Constant Voltage Means 34 DC-DC Converter Circuits 35 3-Terminal Switching Circuits 36 Ignition Distribution Circuits 37 Capacitance Variable Circuits 41 Loads 71 Astable Multivibrator

─────────────────────────────────────────────────── ─── Continuation of the front page (51) Int.Cl. ⁶ Identification code Internal reference number FI Technical display location H02M 11/00 H03K 17/00 C H03K 17/00 17/04 E 17/04 17/68 17 / 567 17/725 17/68 H01L 29/78 17/687 H03K 17/56 C 17/725 17/687 G 17/73 AF 17/73 (31) Priority claim number Japanese Patent Application No. 8-32608 (32) Priority Day Hei 8 (1996) January 11 (33) Priority claiming country Japan (JP) (54) [Title of Invention] Power supply means, capacitive load drive circuit, controllable switching means drive circuit, one direction Insulation type switching circuit, bidirectional insulation type switching circuit, 3 terminal insulation type switching circuit, 3 terminal bidirectional insulation type switching circuit, multi-terminal insulation type switching circuit, multi-terminal bidirectional insulation type switch Circuit, multi-terminal switching type bidirectional isolation switching circuit, ignition distribution circuit, switching circuit, 3-terminal switching circuit, ignition device, power supply means, insulated power supply means, capacitive load drive circuit, insulation switching circuit, and , Power supply means

Claims (81)

[Claims] 1. When a plurality of predetermined numbers are set to N, when a load and N capacitance means are connected in series to form a closed circuit, one current limiting means is connected between each of them. The load, the N capacitance means, and (N +) are formed between both output terminals of the DC voltage output means capable of forming a closed circuit and outputting or not outputting the DC voltage.
1) When connecting the current limiting means in parallel to form a parallel circuit, two sets of N uncontrollable switching means are connected in series so as to sandwich each capacitance means in the same direction. Each of them is directly between the output terminals, or on the positive output terminal side, via the uncontrollable switching means of the capacitance means having a lower potential than itself during series discharge, or the negative output. On the output terminal side, the parallel circuit is formed while being connected in the forward direction to the DC voltage through the uncontrollable switching means of the capacitance means having a higher potential than itself during series discharge. Power supply means. 2. A resistor and its drain for any one of the (N + 1) current limiting means, or one for each of a plurality of them, or one for each of the (N + 1) current limiting means. Normally-off insulated gate FET or SIT that connects the gate and the gate, and normally-on FET or SI that connects the gate and the source
T, a resistance means, a constant current diode, a normally-off transistor in which a resistance means or a constant current means is connected between an unpaired control terminal for inputting a drive signal thereof and a main terminal, a constant current means, a resistance means A combination of a series circuit of an inductance means, a coil or an inductance means and "a period control means for controlling a period during which the DC voltage is output and a period during which the DC voltage is not output", or at least any two of them. A combination of
2. The power supply means according to claim 1, wherein: 3. The DC voltage is applied to any one of the (N + 1) current limiting means, or one to each of a plurality of them, or one to each of the (N + 1) current limiting means. 2. The power supply means according to claim 1, wherein the variable current limiting means has a smaller current limiting function when it is not outputting than when it is outputting. 4. The power supply means according to claim 3, wherein a negative resistance means is used as the variable current limiting means. 5. A control terminal of the first switching means having a self-turn-off function, a main terminal being a control terminal ct1a,
When the control terminal ct1a and the main terminal mt1a are paired for inputting the drive signal, they are called the main terminal mt1a and the main terminal mt1b, and the control terminal c serves as the variable current limiting means.
A first voltage drop means is connected for reverse bias between t1a and the main terminal mt1a, and a current path through which the current of the capacitance means or the load connected to the main terminal mt1a flows when the DC voltage is output. 4. The power supply unit according to claim 3, wherein the first voltage drop unit is included and an ON control unit for ON-controlling the first switching unit is provided. 6. A main terminal mt for inputting another drive signal.
There is a control terminal paired with 1b, and this is a control terminal ct
When called as 1b, control terminal ct1b / main terminal m
A second voltage drop means is connected for reverse bias between t1b, and the second current is passed through the current path of the capacitance means or the load connected to the main terminal mt1b when the DC voltage is output. 6. The power supply means according to claim 5, further comprising voltage drop means. 7. A normally-on type switching means that is on when the voltage between the control terminal ct1b and the main terminal mt1b is zero is used as the first switching means, and the control terminal ct1b and the main terminal mt1 are used as the on control means.
b) resistor, normally-off insulated gate FET or SIT with its drain and gate connected, normally-on FET or SIT with its gate and source connected, resistance means, constant current diode, and its drive signal input A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal not paired with each other, a constant current means, a current limiting means, a discharging means, or a combination of at least two of them. 7. The power source means according to claim 6, wherein the power source is connected to the power source. 8. A control terminal ct1 as the ON control means.
b, a resistor between the main terminal mt1a, a normally-off insulated gate FET or SIT with its drain and gate connected, and a normally-off gate with its source connected.
ON-FET or SIT, resistance means, constant current diode, normally-off transistor, constant current means, in which resistance means or constant current means is connected between a control terminal and a main terminal which are not paired for inputting a drive signal thereof 8. The power supply means according to claim 6 or 7, further comprising a current limiting means or a combination of at least two of them connected. 9. A control terminal ct1 as the ON control means.
a: A resistor between the control terminal ct1b, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, a resistance means, a constant current diode, and A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal which do not form a pair for inputting a drive signal, a constant current means, a current limiting means, or at least two of them. 9. A combination of, and are connected.
Power supply means described. 10. A normally-on type switching means which is on when the voltage between the control terminal ct1a and the main terminal mt1a is zero is used as the first switching means,
As the ON control means, a control terminal ct1a / main terminal mt
1a is a resistor, a normally-off insulated gate FET or SIT with its drain and gate connected, a normally-on FET or SIT with its gate and source connected, resistance means, constant current diode, and its drive signal input A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal which do not form a pair, a constant current means, a current limiting means, a discharging means,
Alternatively, the power supply means according to claim 5, 6, 7, 8 or 9, wherein a combination of at least two of them is connected. 11. A control terminal ct as the ON control means.
1a: a resistor between the main terminal mt1b, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, resistance means, constant current diode, and A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal which do not form a pair for inputting a drive signal, a constant current means, a current limiting means, or at least two of these The power supply means according to any one of claims 5 to 10, wherein a combination of them is connected. 12. Any one of the 2N uncontrollable switching means, or one each of a plurality of them, or one of each of the 2N thereof, the DC voltage being A controllable switching means that is ON-controlled when output and OFF-controlled when the DC voltage is not output.
The power supply means according to any one of 11 above. 13. Turn-on of any one or more of the controllable switching means, or one of each of a plurality thereof, or one of each of all of them. 13. The power supply means according to claim 12, further comprising a turn-on prevention control means for controlling whether or not to prevent the above. 14. The closed circuit includes a second switching means that can be turned on and off.
Power supply means given in any 1 paragraph of-13. 15. A series circuit of a first DC power supply and a third switching means capable of turning on and off is used as the DC voltage output means, according to any one of claims 1 to 11. Power supply means described. 16. Any one of the 2N uncontrollable switching means, or one each of a plurality of them, or one of each of the 2N thereof, the third. 16. The power supply device according to claim 15, wherein the power supply device is replaced by a controllable switching device that is on / off controlled in cooperation with on / off of the switching device. 17. One of N non-controllable switching means connected to the third switching means side.
Or one of each of them,
Alternatively, each one of the N switching means is replaced by a controllable switching means that is on / off controlled in cooperation with turning on / off of the third switching means, and the controllable switching means is switched to the third switching means. The power supply means according to claim 15, wherein the power supply means is connected to the first DC power supply without any means. 18. Any one of the N uncontrollable switching means connected to the side of the first DC power supply, or one of each of the plurality of uncontrollable switching means, or one of the N number of the uncontrollable switching means. 18. The power supply means according to claim 15 or 17, wherein each of them is replaced by a controllable switching means that is on / off controlled in cooperation with on / off of the third switching means. 19. A turn-on of any one or more of the controllable switching means, or one of each of a plurality thereof, or one of each of all of them. 19. The power supply means according to claim 16, 17, or 18, further comprising turn-on prevention control means for controlling whether or not to prevent the electric power supply. 20. The closed circuit includes a fourth switching means capable of being turned on and off.
The power supply means according to any one of 5 to 19. 21. One or more or all of the current limiting means are controlled by a controllable switching means that is turned off when the DC voltage is output and turned on when the DC voltage is not output. 21. The power supply means according to claim 1, wherein the power supply means is replaced. 22. A driving circuit for a capacitive load according to claim 1, wherein a capacitive load is used as the load. 23. The drive circuit for controllable switching means according to claim 1, wherein a fifth controllable controllable switching means is used as the load. 24. The control circuit of the controllable switching means according to claim 23, wherein a pair of control terminals for inputting a drive signal of the fifth switching means and a main terminal are called a control terminal ct5 and a main terminal mt5a. Then, the connection position of the third switching means is set between the first DC power source and the control terminal ct5, and the main terminal mt5a and the first terminal mt5a are connected.
The DC power source of the
1) The uncontrollable switching means is connected, and when the third switching means is turned on, the first DC power supply connects the fifth switching means via the (2N + 1) th uncontrollable switching means. Reverse bias, main terminal m
The (2N + 2) th non-controllable switching means is connected to t5a to controllable 1 with the fifth switching means.
1. A directional switching means is constructed.
Directional isolated switching circuit. 25. The fifth switching means is provided with a second (2
N + 3) non-controllable switching means are provided in parallel,
25. The unidirectional isolated switching circuit according to claim 24, wherein the unidirectional controllable bidirectional switching means is constituted by both of them. 26. The one-way isolated switching circuit according to claim 25, wherein there is a controllable sixth switching means, and a control terminal and a main terminal forming a pair for inputting a drive signal thereof are control terminals ct6, When the bias voltage polarity between the control terminal ct5 and the main terminal mt5a is the same as that between the control terminal ct6 and the main terminal mt6a, the sixth switching means is referred to as the main terminal mt6a.
2) is provided in parallel with the non-controllable switching means to constitute a bidirectional controllable switching means together with the fifth switching means and the (2N + 3) non-controllable switching means, and the seventh switching means is turned on. When the first DC power supply has a closed circuit for reverse biasing the sixth switching means via the (2N + 1) th uncontrollable switching means, N pieces are provided when the seventh switching means is OFF. 2. A bidirectional insulating switching circuit, wherein any one or a plurality or all of the capacitance means of (1) are provided with a closed circuit for forward biasing the sixth switching means. 27. The control terminal ct5 and the third switching means are temporarily disconnected from each other, and the second (2N + 4)
The non-controllable switching means of is connected to the control terminal ct6.
And the seventh switching means are once separated from each other, and a (2N + 5) th uncontrollable switching means is connected between them, and the third and seventh switching means are commonly used and integrated into one. When the switching means is on, the first DC power source is the second (2N + 4), the second (2N + 4)
27. The bidirectional isolated switching circuit according to claim 26, wherein each of the fifth and sixth switching means is reverse biased via each of the +5) uncontrollable switching means. 28. A control terminal ct5 and a control terminal ct6 are connected, the third and seventh switching means are commonly used and integrated, and when the common switching means is off, N capacitance means are provided. 27. The bidirectional isolated switching circuit according to claim 26, wherein the fifth and sixth switching means are forward-biased through (N + 1) current limiting means. 29. In place of the bidirectional controllable switching means constituted by the fifth and sixth switching means and the (2N + 2) th and (2N + 3) th uncontrollable switching means, a back gate thereof is provided. A 4-terminal MO in which the directions of both PN junctions formed in the opposite direction between the drain and the source, respectively, and the directions of the (2N + 2) th and (2N + 3) th uncontrollable switching means are the same.
29. The bidirectional insulated switching circuit according to claim 28, wherein an S-FET or an insulated gate FET is used. 30. The one-way isolated switching circuit according to claim 24, wherein the fifth switching means comes to both rectified output terminals of the second (2N + 2) uncontrollable switching means and the second (2N + 2) uncontrollable switching means. 2N + 6) to the second (2N
A bidirectional isolated switching circuit, characterized in that a bridge connection type rectifying circuit is constituted by four uncontrollable switching means of +8). 31. A bidirectional isolated switching circuit, wherein the unidirectional isolated switching circuit according to claim 24 or 25 and the unidirectional isolated switching circuit according to claim 24 or 25 are connected in antiparallel. circuit. 32. Both control terminals ct5 and main terminal mt5
32. The bidirectional isolated switching circuit according to claim 31, wherein the bias voltage polarities between a are the same. 33. Both of the first DC power supplies are made common
33. The bidirectional isolated switching circuit according to claim 32, characterized in that 34. The control terminal ct5 on one side and the third switching means on one side are once cut off, and a (2N + 9) th uncontrollable switching means is connected therebetween, and the other control terminal ct5 and the other control terminal ct5 are connected. Between the third switching means, and the (2N + 10) th uncontrollable switching means is connected between them, and both the third switching means are made common and integrated into one, and the common switching means 34. The first DC power supply reverse biases each of the fifth switching means via the (2N + 9) th and (2N + 10) th uncontrollable switching means, respectively. The bidirectional isolated switching circuit described. 35. The drive circuit for controllable switching means according to claim 23, wherein the fifth switching means is bidirectionally turned on according to a drive terminal pair forming a pair for inputting a drive signal thereof and the input drive signal thereof. , A four-terminal type switching means having four terminals of a switch terminal pair to be turned off, and one PN junction is formed in the opposite direction between one of the drive terminals and each of the switch terminals. The connecting position of the switching means between the first DC power supply and the other drive terminal, and one drive terminal and the first DC power supply are once cut off, and during this time, the (2N + 11) th uncontrollable Connect switching means,
Bidirectional isolation wherein the first DC power supply reverse biases the fifth switching means via the (2N + 11) th uncontrollable switching means when the third switching means is on. Type switching circuit. 36. As the fifth switching means, 4
Using the MOS FET or insulated gate type FET of the terminal,
36. The bidirectional isolated switching circuit according to claim 35, wherein the gate terminal and the back gate terminal are the drive terminal pair and the drain terminal and the source terminal are the switch terminal pair. 37. As the fifth switching means,
The bidirectional controllable switching means in which the control terminals of the two one-way controllable bidirectional switching means and the main terminals are connected to each other is used, and the common control terminal and the main terminal are the drive terminal pair. The bidirectional isolated switching circuit according to claim 35. 38. The unidirectional isolated switching circuit according to claim 24 or 25 and the unidirectional isolated switching circuit according to claim 24 or 25 in the same direction, inward, or outward. Characterized by being connected in series 3
Terminal isolated switching circuit. 39. Both control terminals ct5 and main terminal mt5
39. The three-terminal isolated switching circuit according to claim 38, wherein the bias voltage polarities between a are the same. 40. The one-way isolated switching circuit according to claim 24 or 25 and any one of claims 26 to 37.
A three-terminal insulation type switching circuit in which the bidirectional insulation type switching circuit described in the item 1 is connected in series. 41. Both control terminals ct5 and main terminal mt5
The three-terminal isolated switching circuit according to claim 40, wherein the bias voltage polarities between a and a are the same. 42. A bidirectional insulating switching circuit according to any one of claims 26 to 37 and claim 26 to 3.
7. A three-terminal bidirectional isolated switching circuit, wherein the bidirectional isolated switching circuit according to any one of 7 is connected in series. 43. Both control terminals ct5 and main terminal mt5
The three-terminal bidirectional isolated switching circuit according to claim 42, wherein the bias voltage polarities between a and a are the same. 44. The unidirectional isolated switching circuit according to claim 24 or 25 is connected to the unidirectional isolated switching circuit according to claim 24 or 25, and the connecting point is further connected to the unidirectional isolated switching circuit. The multi-terminal insulated switching circuit, wherein the one-way isolated switching circuit of No. 1 is connected, and a predetermined number of them are similarly connected to the connection point. 45. All control terminals ct5 and main terminals mt
45. The multi-terminal isolated switching circuit according to claim 44, wherein the bias voltage polarities between 5a are the same. 46. A bidirectional insulating switching circuit according to any one of claims 26 to 37 and claim 26 to 3.
The bidirectional insulating switching circuit according to any one of claims 7 to 7 is connected, and further, the connection point is connected to the bidirectional isolated switching circuit.
7. A multi-terminal bidirectional insulating switching circuit, wherein the bidirectional insulating switching circuit according to any one of 7 is connected, and a predetermined number of the bidirectional insulating switching circuits are similarly connected. 47. All control terminals ct5 and main terminals mt
47. The multi-terminal bidirectional isolated switching circuit according to claim 46, wherein the bias voltage polarities between 5a are the same. 48. A predetermined number of series circuits in which the circuit constituent means, circuit or load to be switched and the bidirectional isolated switching circuit according to any one of claims 26 to 37 are connected in series. Multi-terminal switching type bidirectional isolated switching circuit characterized by being connected. 49. All control terminals ct5 and main terminals mt
49. The multi-terminal switching type bidirectional isolation switching circuit according to claim 48, wherein the bias voltage polarities between the terminals 5a are the same. 50. A primary coil of an ignition coil, wherein an ignition discharge gap means is connected to the secondary coil.
37. An ignition distribution circuit, characterized in that a predetermined number of series circuits in which the bidirectional isolated switching circuits according to any one of 37 are connected in series are connected in parallel. 51. All control terminals ct5 and main terminals mt
51. The ignition distribution circuit according to claim 50, wherein the bias voltage polarities between 5a are the same. 52. The one-way isolated switching circuit according to claim 24, wherein between the main terminal not paired with the control terminal ct5 of the fifth switching means and the first DC power supply. A switching circuit in which a second DC power supply is connected to the unidirectional direction. 53. Both control terminals ct5 and main terminal mt5
A drive circuit of the controllable switching means according to claim 23 and a switching circuit according to claim 52, wherein the bias voltage polarity between a is the same, and the former fifth switching means and the latter unidirectional switch are combined into the latter. A three-terminal switching circuit, characterized in that it is connected in series between both power supply terminals of a second DC power supply, and both of the first DC power supplies are common and integrated. 54. The control circuit of the controllable switching means according to claim 23, wherein there is an eighth switching means which has a reverse bias polarity opposite to that of the fifth switching means in the order of the driving voltage and the reverse bias polarity. A three-terminal switching circuit in which both control terminals are connected to each other and main terminals are connected to each other so that the OFF state is reversed. 55. A power supply means according to claim 1, wherein a primary coil of an ignition coil is connected as the load, and an ignition discharge gap means is connected to the secondary coil. Ignition device. 56. As the DC voltage output means, a ninth switching means capable of being turned on and off and a primary winding of a transformer are connected in series between both power supply terminals of a third DC power supply, and the transformer is used. The power supply means according to any one of claims 1 to 14, wherein a DC output is taken out from the secondary winding of the container. 57. The power supply means according to claim 56,
Insulated power supply means characterized in that the primary and secondary windings are insulated from each other. 58. The power supply means according to claim 1, wherein the direct current voltage output means is a tenth power source that can be turned on and off between both power source terminals of a fourth direct current power source.
Switching means, a light emitting diode or a light emitting means for converting electricity into light, and a resistance means, a constant current means or a current limiting means connected in series in the forward direction, and the light emitting diode or the light emitting means has a light receiving diode or a photovoltaic means An isolated power supply means for extracting a direct current output from the light receiving diode or the photovoltaic means by using a light-coupled one. 59. The capacitive load driving circuit according to claim 56 or the insulated power source means according to claim 57 or 58, wherein a capacitive load is used as the load. 60. The insulated switching circuit according to claim 57, wherein the controllable eleventh switching means is used as the load. 61. When a plurality of predetermined numbers are set to P, one current limiting means is connected between each of the P capacitance means when connected in series to form a first series circuit. The first series circuit is formed, and P capacitance means (P-1) are provided between both output terminals of the DC voltage output means capable of outputting or not outputting a DC voltage.
When the current limiting means are connected in parallel to form a parallel circuit, two uncontrollable switching means are connected in series so as to sandwich each capacitance means in the same direction.
Directly connecting each of the series circuits between the two output terminals,
Alternatively, the positive output terminal side is connected through the uncontrollable switching means of the capacitance means having a lower potential than itself during series discharge, or the negative output terminal side is connected during series discharge. Power supply means characterized in that the parallel circuit is formed while being connected in the forward direction to the DC voltage via the uncontrollable switching means of the capacitance means having a higher potential. 62. One of the (P-1) current limiting means, or one for each of a plurality of them, or one for each of the (P-1). , A normally-off insulated gate FET or SIT with its drain and gate connected, and a normally-on FET or SI with its gate and source connected
T, a resistance means, a constant current diode, a non-paired control terminal for inputting a drive signal thereof, and a resistance means or a constant current means connected between the main terminals. A combination of an off transistor, a constant current means, a series circuit of a resistance means and an inductance means, a coil or an inductance means and "a period control means for controlling a period during which the DC voltage is output and a period during which the DC voltage is not output", or The power supply means according to claim 61, wherein a combination of at least any two of these is used. 63. Any one of the (P-1) current limiting means, or one for each of a plurality thereof, or one for each of the (P-1). 62. The power supply means according to claim 61, wherein a variable current limiting means is used whose current limiting function is smaller when the DC voltage is not being output than when the DC voltage is being output. 64. The power supply means according to claim 63, wherein a negative resistance means is used as the variable current limiting means. 65. The control terminal and the main terminal of the first switching means having a self-turn-off function are replaced by the control terminal ct1.
a, a main terminal mt1a, and a main terminal mt1b, and when the control terminal ct1a and the main terminal mt1a are paired for inputting a drive signal thereof, the variable current limiting means is provided between the control terminal ct1a and main terminal mt1a The first voltage drop means is connected for reverse bias, and the first voltage drop means is included in the current path through which the current of the capacitance means connected to the main terminal mt1a flows when the DC voltage is output. 64. The power supply means according to claim 63, further comprising: an ON control means for ON-controlling the first switching means. 66. A main terminal m for inputting another drive signal.
There is a control terminal paired with t1b, and this is a control terminal c
When referred to as t1b, the second voltage drop means is connected between the control terminal ct1b and the main terminal mt1b for reverse bias, and the current of the capacitance means connected to the main terminal mt1b outputs the DC voltage. 66. The power supply means according to claim 65, wherein the second voltage drop means is included in a current path that flows when the power is on. 67. A normally-on type switching means which is on when the voltage between the control terminal ct1b and the main terminal mt1b is zero is used as the first switching means,
As the ON control means, a control terminal ct1b / main terminal mt
Resistor between 1b, normally-off insulated gate FET or SIT with its drain and gate connected, normally-on FET or SIT with its gate and source connected, resistance means, constant current diode, and its drive signal input A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal that do not form a pair, a constant current means, a current limiting means, a discharging means,
67. The power supply means according to claim 66, wherein a combination of at least two of them is connected. 68. The control terminal ct as the ON control means
1b A resistor between the main terminal mt1a, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, a resistance means, a constant current diode, and A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal which do not form a pair for inputting a drive signal, a constant current means, a current limiting means, or at least two of these 67. A combination of the above is connected, and the combination is connected.
Power supply means described. 69. A control terminal ct as the ON control means
1a: a resistor between the control terminal ct1b, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, a resistance means, a constant current diode, and A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal which do not form a pair for inputting a drive signal, a constant current means, a current limiting means, or at least two of these 67. A combination of the above and the connected ones.
The power supply means according to 7 or 68. 70. As the first switching means, a normally-on type switching means that is on when the voltage between the control terminal ct1a and the main terminal mt1a is zero is used.
As the ON control means, a control terminal ct1a / main terminal mt
Resistor between 1a, normally-off insulated gate FET or SIT with its drain and gate connected, normally-on FET or SIT with its gate and source connected, resistance means, constant current diode, and its drive signal input A normally-off transistor in which a resistance means or a constant current means is connected between a control terminal and a main terminal that do not form a pair, a constant current means, a current limiting means, a discharging means,
70. The power supply means according to claim 65, wherein a combination of at least two of them is connected. 71. The control terminal ct as the ON control means
1a: a resistance between the main terminal mt1b, a normally-off insulated gate FET or SIT having its drain and gate connected, a normally-on FET or SIT having its gate and source connected, a resistance means, a constant current diode, and A normally-off transistor in which a resistance means or a constant current means is connected to a control terminal and a main terminal which do not form a pair for inputting a drive signal, a constant current means, a current limiting means, or at least two of them are provided. 71. Power supply means according to any one of claims 65 to 70, characterized in that a combination of them is connected. 72. Any one of the 2P uncontrollable switching means, or one each of a plurality of them, or one of each of the 2P thereof, wherein the DC voltage is 62. A controllable switching means that is on-controlled when output and is off-controlled when the DC voltage is not output.
72. A power supply means according to any one of items 71 to 71. 73. Turn-on to any one of the one or more controllable switching means, or to each of a plurality thereof, or to each of all of them. 73. The power supply means according to claim 72, further comprising turn-on prevention control means for controlling whether or not to prevent the electric power from being turned off. 74. The power supply means according to claim 61, wherein the series circuit of the P capacitance means includes a second switching means capable of being turned on and off. . 75. A series circuit of a first DC power supply and a third switching means capable of turning on and off is used as the DC voltage output means, according to any one of claims 61 to 71. Power supply means described. 76. Any one of the 2P uncontrollable switching means, or one each of a plurality of them, or one of each of the 2P thereof, and the third 76. The power supply means according to claim 75, wherein the power supply means is replaced by a controllable switching means that is on / off controlled in cooperation with turning on / off of the switching means. 77. Any one of the P uncontrollable switching means connected to the side of the third switching means.
Or one of each of them,
Alternatively, each one of the P switching units is replaced with a controllable switching unit that is on / off controlled in cooperation with turning on / off of the third switching unit, and the controllable switching unit is switched to the third switching unit. 76. The power supply means according to claim 75, wherein the power supply means is connected to the first DC power supply without any means. 78. Any one of the P uncontrollable switches connected to the side of the first DC power supply, or one of each of the plurality of uncontrollable switches, or each of the P thereof. 78. The power supply means according to claim 75 or 77, wherein each of the above is replaced by a controllable switching means that is on / off controlled in cooperation with turning on / off of the third switching means. 79. The turn-on of any one or more of the controllable switching means, or one of each of a plurality thereof, or one of each of all of them. 79. The power supply means according to claim 76, 77 or 78, further comprising a turn-on prevention control means for controlling whether or not to prevent the above. 80. The power supply means according to claim 75, wherein the series circuit of the P capacitance means includes a fourth switching means capable of being turned on and off. . 81. One or more or all of the current limiting means are each controlled by a controllable switching means that is turned off when the DC voltage is output and turned on when the DC voltage is not output. The power supply unit according to any one of claims 75 to 80, which is replaced.