JPH0832353A - Frequency mixing circuit - Google Patents

Abstract

PURPOSE:To provide an economical frequency mixing circuit without using an operational amplifier by multiplying high frequency signals and local oscillation signals by a mixing circuit and adjusting the phase shift of mutually inverted intermediate frequency signals by a phase shift circuit. CONSTITUTION:Reception radio waves inputted from an antenna are passed through a capacitor C3 and inputted from terminals T3 and T4 to a Gibert multiplication circuit 1 as RF signals. When the local oscillation signals LO provided with a bias voltage VB1 are impressed as an input voltage V1 and the RF signals provided with the bias voltage VB2 are impressed as the input voltage V2, the Gilbert multiplication circuit 1 functions as a mixer. Thus, the frequency of a current made to flow to load resistors RA and RB is provided with the frequency component of the difference of the frequencies of the local oscillation signals LO and the RF signals. A buffer circuit 3 changes the change of base voltages whose polarities are mutually inverted inputted to transistors Q7 and Q8 to the current and it is supplied from the terminals T5 and T6 to the phase shift circuit. Intermediate frequency signals are obtained by the capacitor for the phase shift and a resistance circuit.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a so-called frequency mixing circuit used in a front end (high frequency circuit) of a receiver, and in particular, mixing two frequency signals and setting a frequency component of a difference between the two frequency signals to an intermediate frequency. The present invention relates to a frequency mixing circuit that is extracted as a signal.

In recent years, GPS (Global Pos
itioning system) Ultra-high frequency wave receivers for use in systems have been developed. Since the reception frequency of these receiving devices has a very short wavelength, it is usually converted into a signal of a certain intermediate frequency (intermediate frequency signal) before being demodulated to a low frequency signal. What is needed for this is a frequency mixing circuit.

In the frequency mixing circuit, in order to generate the intermediate frequency, the reception frequency and a predetermined local oscillation frequency are mixed to obtain a difference signal between them. At that time, frequency interference may occur due to interference of other frequency components. Therefore, a frequency mixing circuit (image reject mixer circuit) capable of removing the frequency interference has been developed.

[0004]

2. Description of the Related Art The principle of frequency mixing operation will be described with reference to FIG. FIG. 3A shows the frequency distribution of the reception frequency and the local oscillation frequency, and FIG. 3B is a conceptual diagram of the frequency mixing circuit.

Now, the receiver has a frequency f of 1.5 [GHz].
A radio wave having ₁ is received, and this is input as an RF signal in the mixing circuit 20 shown in FIG. On the other hand, the local oscillation signal LO having a frequency of 1.4 [GHz] generated inside the receiver is another input of the mixing circuit 20. When both signals are multiplied in the mixing circuit 20, a sum signal (= f ₁ + f _LO = 2.9 [GHz
]) And a difference signal (= f ₁ −f _LO = 0.1 [GHz]) are generated. The low pass filter 21 filters the output of the mixing circuit 20 at a predetermined cutoff frequency. As a result, only the difference signal component having a low frequency is output, and this becomes the intermediate frequency signal.

The above is the concept of generating an intermediate frequency signal, but in practice this circuit has a problem. For example, as shown in FIG. 3 (A), the RF signal is 1.5 [GHz]
Consider a case where an RF signal having a frequency component f ₂ of 1.3 [GHz] exists in addition to the frequency f ₁ of ₁ . This frequency f
Frequency of the difference signal between the _second RF signal and the local oscillation signal LO has the same 0.1 the frequency of the difference signal between the frequency f ₁ of the RF signal and the local oscillation signal LO is a received radio wave of normal [GHz]
Is. Therefore, the converted signals of both received radio waves are both output as an intermediate frequency signal, causing interference.

Therefore, a frequency mixing circuit (image reject mixer circuit) capable of removing interference as shown in FIG. 4 has been conventionally used. The mixing circuits 6 and 7 are supplied with a local oscillation signal having a phase relationship of 0 ° and a local oscillation signal having a phase relationship of 90 °. Each mixing circuit 6 and 7 is mixed with the RF signal by a different local oscillation signal, and the phase shift circuits 9 and 10 are mixed.
The phase relationship is adjusted at and is added by the adder 11. With this frequency mixing circuit, the difference signal between the higher frequency RF signal and the local oscillation signal or the lower frequency R signal
It is possible to output the intermediate frequency (IF) signal of only one of the difference signals between the F signal and the local oscillation signal.

In these frequency mixing circuits, the phase relationship is finely adjusted.
Since it is necessary to adjust the phase, only the phase is changed without changing the amplitude.
A changeable phase shift circuit is essential. This phase shift circuit is shown in FIG.
The conceptual diagram of a structure of is shown. The phase shift circuit responds to the positive phase signal
Inverters 12 and 13 that generate signals of opposite phases,
Resistor R between both outputs_{twenty one}, R_{twenty two}And capacitor C_{twenty one}, C _{twenty two}
Are connected in series. Actually the phase shift circuit shown in FIG.
Can operate at high frequency as an inverter
It is possible to use a different operational amplifier.

FIG. 6 shows a conventional phase shift circuit using a high frequency operational amplifier. As shown in FIG. 6, a phase shift circuit can be configured by operational amplifiers 14 and 15 that can operate at high speed and can be used for high frequencies, and resistors and capacitors. Delay circuit consisting of resistor and capacitor (R ₂₄ and C ₂₃ , R ₂₈
And C ₂₄ ) as the positive phase input of the operational amplifier, and the signal without delay is input as the negative phase, the result is the same operation as in FIG.

[0010]

However, in the above-described conventional phase shift circuit, the frequency band of the operational amplifier required for realizing the circuit is very wide, and there is a problem in actually forming the operational amplifier into an IC. Was there.

Normally, in constructing an operational amplifier as an integrated circuit, NPN type transistors and PNP type transistors are mixed and manufactured. However, N
When an integrated circuit is manufactured by mixing PN-type transistors and PNP-type transistors, the number of steps in the manufacturing process increases and the circuit area increases. Further, since transistors having different characteristics are mixed, parasitic capacitance or the like may affect the operation speed.

In order to maintain sufficient circuit characteristics for such an operational amplifier, it is necessary that the actual operable frequency band has a band of about 10 times the frequency to be handled. For example, if the input IF signal is several MHz
In this case, the operational amplifier needs to have a frequency characteristic of about several tens of MHz. Therefore, in a circuit handling a high frequency signal, it is practically difficult to configure a phase shift circuit or the like with an operational amplifier. Further, an operational amplifier capable of operating at a high frequency needs to overcome the above-mentioned conditions, and is very expensive in terms of price.

Therefore, an object of the present invention is to economically provide a frequency mixing circuit that can operate even in a high frequency region without using an operational amplifier with a simple structure.

[0014]

In order to achieve the above object, the invention according to claim 1 inputs a high frequency signal as a first original signal and a local oscillation signal as a second original signal. A mixing circuit for mixing the original signal and the second original signal to output a mixed signal of the first original signal and the second original signal and an inverted mixed signal obtained by inverting the mixed signal; And a phase shift circuit for connecting the capacitance means and the resistance means in series between the output of the signal and the output of the intermediate frequency signal from the connection portion of the capacitance means and the resistance means.

According to a second aspect of the present invention, in the frequency mixing circuit according to the first aspect, the mixing circuit is composed of a single balanced type multiplication circuit including a single differential pair transistor.

According to a third aspect of the present invention, in the frequency mixing circuit according to the first aspect, the mixing circuit is composed of a double balance type multiplication circuit (Gilbert multiplication circuit).
According to a fourth aspect of the present invention, a high frequency signal is used as a first original signal and a local oscillation signal having no phase shift with respect to the high frequency signal is used as a second original signal, and a first intermediate frequency signal having no phase shift is output. 4. The frequency mixing circuit according to claim 1, wherein the local oscillation signal having a high frequency signal as a first original signal and having a phase shift with respect to the high frequency signal has a phase shift with respect to the second original signal. The frequency mixing circuit according to any one of claims 1 to 3, which outputs a second intermediate frequency signal.

[0017]

According to the first aspect of the invention, the mixing circuit inputs the received high frequency signal as the first original signal and the local oscillation signal as the second mixed signal, and outputs the first original signal as the first original signal. Multiplication with the second original signal is performed, and a mixed signal of the first original signal and the second original signal and an inverted mixed signal obtained by inverting the mixed signal are output. The frequency of both mixed signals is an intermediate frequency signal. If a capacitance means and a resistance means are connected in series between the outputs of the mixed signal and the inverted mixed signal which are in opposite phase to each other, this constitutes a phase shift circuit, so that the connection portion of the capacitance means and the resistance means is connected. An intermediate frequency signal whose phase has been adjusted can be output.

According to the second aspect of the present invention, a single balance type multiplication circuit having a single differential pair transistor is provided as the mixing circuit. Therefore, the intermediate frequency signals that can be taken out from the differential pair are in opposite phase to each other. Therefore, an intermediate frequency signal whose phase has been adjusted by a phase shift circuit which receives both the mixed signals can be taken out.

According to the third aspect of the present invention, since the double balance type multiplication circuit (Gilbert multiplication circuit) is provided as the mixing circuit, intermediate frequency signals having mutually opposite phases can be taken out from the output of the mixing circuit.

According to the fourth aspect of the present invention, two mixing circuits are used, one of which is supplied with a local oscillation signal having no phase shift to obtain a first intermediate frequency signal having no phase shift.
On the other hand, a local oscillation signal having a phase shift is input to obtain a second intermediate frequency signal having a phase shift. By adjusting the phase of each by a phase circuit, an intermediate frequency signal having two phase relationships that can be input to the adder can be obtained.

[0021]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT A preferred embodiment of the frequency mixing circuit of the present invention will be described with reference to the drawings. (I) First Embodiment A first embodiment of the present invention applies a Gilbert multiplication circuit as a mixing circuit that performs frequency mixing.

FIG. 1 shows the configuration of the first embodiment of the present invention.
As shown in FIG. 1, the frequency mixing circuit 100 of the first embodiment.
Is divided into a system that generates an intermediate frequency signal IF (0 °) with a phase of 0 ° and a system that generates an intermediate frequency signal IF (90 °) with a phase of 90 °. Both the generated intermediate frequency signal IF (0 °) and the intermediate frequency signal (90 °) are supplied to an adder (not shown) or the like, and only the intermediate frequency signal regarding the desired reception frequency is finally extracted. Become.

The system of the intermediate frequency signal IF (0 °) includes a Gilbert multiplication circuit 1 provided as a mixing circuit for mixing frequencies, a buffer circuit 3 for phase adjustment, and resistors R _{1 to} R ₅ . And capacitors C _{1 to} C ₄ . The system of the intermediate frequency signal IF (90 °) includes a Gilbert multiplication circuit 2 that mixes frequencies, a buffer circuit 4 that performs phase adjustment, resistors R _{11 to} R ₁₅ , and capacitors C _{11 to} C ₁₄ . , Is provided.

The system of the intermediate frequency signal IF (90 °) and the system of the intermediate frequency signal IF (0 °) have a phase shift condition (that is,
Since the circuits are the same except for the resistor R ₄ and the capacitor C ₄ , the resistor R ₁₄ and the capacitor C ₁₄ ), only the system of the intermediate frequency signal IF (0 °) will be described below unless otherwise specified. The description of the system of the intermediate frequency signal IF (90 °) is omitted.

The Gilbert multiplication circuit 1 is widely known as a mixing circuit and a multiplication circuit, and includes transistors Q _{1 to} Q ₈ , load resistors R _A and R _B, and a constant current source I.
_{1 to} I ₃ . The buffer circuit 3 includes a constant current source I
And ₂ transistor Q ₇ connected, constituted by a transistor Q ₈ which is a constant current source I ₃ is connected.

Next, the operation will be described. The received radio wave input from an antenna (not shown) is converted into an RF signal by a capacitor C
Through _3, it is inputted from the terminal T ₃ and T ₄ in Gilbert circuit 1. V _B2 is a bias voltage that defines the operating point of transistors Q ₅ and Q ₆ through resistors R ₃ and R ₄ . In addition, the local oscillation signal LO is T ₁ and T
It becomes the input of two differential pairs via ₂ . V _B1 defines the bias voltage of the differential pair.

Consider the operation of the Gilbert multiplier circuit below. Now, the thermal voltage of each NPN transistor is set to V _T (=
kT / q≈26 [mV] (T = 300 ° K); g is electronic charge, k is Boltzmann constant), voltage applied between terminals T _{1 and} T _{2 is} between V ₁ and terminals T _{3 and} T _4. When the voltage applied to the transistor is V ₂ and the collector currents of the transistors Q _{1 to} Q ₆ are I _{C1 to} I _C6 , respectively, the collector current of each transistor is I _C1 = I _C5 / (1 + exp (-V ₁ / V _T )) (1-1) I _C2 = I _C5 / (1 + exp (V ₁ / V _T )) (1-2) I _C3 = I _C6 / (1 + exp (V ₁ / V _T )) (1-) 3) I _C4 = I _C6 / (1 + exp (-V ₁ / V _T )) (1-4) I _C5 = I _EE / (1 + exp (-V ₂ / V _T )) (1-5) I _{C6 = I EE / (1 + exp} (V 2 / V T)) ... a (1-6). The differential output current is ΔI = I _C1-3 −I _C2-4 = I _C1 + I _C3 − (I _C2 + I _C4 ) = (I _C1 −I _C4 ) − (I _C2 −I _C3 ) = I _EE [tanh (V ₁ / 2V _T )] · [tanh (V ₂ / 2V _T )] ... (2) The Gilbert multiplier circuit has input voltages V ₁ and V ₂
Is kept smaller than V _T , the hyperbolic tangent function of equation (2) is approximated by a linear proportional equation, so the circuit operates as a multiplier and outputs V ₁ and V The product of ₂ is obtained (Equation (3)).

ΔI 〓I _EE (V ₁ / 2V _T ) (V ₂ / 2V _T ) (3) Therefore, as in this embodiment, the bias voltage V _{1 is set} as V _{1.
When the} local oscillation signal LO having _B1 is applied and the RF signal having the bias voltage V _B2 is applied as V ₂ , the present Gilbert multiplication circuit 1 causes the multiplier of the local oscillation signal LO and the RF signal, that is, a mixer (mixer). Circuit). for that reason,
The frequencies of the currents I _{C1 -3} and I _C2-4 flowing through the load resistors R _A and R _B have frequency components corresponding to the difference between the frequency of the local oscillation signal LO and the frequency of the RF signal. The signal of current I _C1-3 is
It has an opposite phase to the signal of the current I _C2-4 and is converted into an output voltage by the load resistors R _A and R _B , respectively.

The buffer circuit 3 is connected in series and serves as a phase shift circuit from the terminals T ₅ and T ₆ for converting the changes in the base voltages, which are input to the transistors Q ₇ and Q ₈ and whose polarities are inverted, into the changes in the current. It is supplied to the capacitor C ₄ and the resistor R ₅ . The capacitor C ₄ and the resistor R ₅ forming the phase shift circuit change the amplitude, and the intermediate frequency signal IF (0 °) with the adjusted phase shift is obtained from the intermediate point of both elements.

On the other hand, the Gilbert multiplication circuit 2 and the buffer circuit 4 operate in the same manner as described above, and the phase shift circuit composed of the capacitor C ₁₄ and the resistor R ₁₅ connected in series to the terminals T ₁₅ and T ₁₆ causes only a predetermined angle. A phase shifted intermediate frequency signal is obtained. Phase shift circuit (C ₄ and R ₅ ) and phase shift circuit (C
₁₄ and R ₁₅ ), if the constants of the respective elements are set so that the phase shift relationship with R ₁₄ and R ₁₅ ) becomes 90 °, the intermediate frequency signal IF (0
And the intermediate frequency signal IF (90 °) are deviated by 90 ° with respect to the intermediate frequency. If these two signals are input to a mixing means such as the adder 11 shown in FIG. 4, the intermediate frequency signal IF relating to the desired reception frequency is obtained.
Only can be taken out.

As shown above, according to the first embodiment,
An image reject mixer circuit at high frequency can be easily constructed by using the Gilbert multiplication circuit. The Gilbert multiplication circuit is excellent in frequency characteristics because it can be configured with NPN transistors, and is optimal as a mixing circuit at high frequencies. Moreover, since the intermediate frequency signals of the positive and negative phases of the Gilbert multiplication circuit are used as they are as the inverter of the phase shift circuit which has been a problem in the conventional frequency mixing circuit, it is possible to obtain a good frequency without providing an operational amplifier or the like. Phase shift operation can be performed while maintaining the characteristics.

Further, since the Gilbert multiplication circuit, the buffer circuit, etc. can all be composed of NPN transistors,
Compared to a mixed P-type and NPN-type circuit, there are less difficulties associated with the design and manufacture of monolithic ICs. As a manufacturing method, the Gilbert circuit and the buffer circuit part are integrated into an IC, and the other resistors and capacitors are added parts, so-called external parts, so that the user can arbitrarily set the constants of each element. It is preferable because the degree of freedom of the circuit is increased. At this time, not only the Gilbert multiplication circuit and the buffer circuit are integrated into an IC, but also the two Gilbert multiplication circuits 1 and 2 and the buffer circuits 3 and 4 which perform operations having different phase conditions, and an adder (not shown) are integrated into an IC. Can also be considered. According to this structure, it is possible to provide a frequency mixing circuit that can be completed with only external components.

Further, since the Gilbert multiplication circuit can realize a stable linear characteristic over a wide voltage range, there is a margin in the input voltage range and the output voltage range, and stable operation can be expected. (Ii) Second Embodiment In the second embodiment of the present invention, as the mixing circuit described in the frequency mixing circuit of the first embodiment, a single balance type multiplication circuit is applied instead of the Gilbert multiplication circuit.

FIG. 2 shows a mixing circuit of the second embodiment. The mixing circuit 5 of this embodiment is the frequency mixing circuit 100 shown in FIG.
Of these, it is directly applied to the portion of the mixing circuit, that is, the portion of the Gilbert multiplication circuits 1 and 2. As shown in FIG. 2, the mixing circuit of the present embodiment has a transistor Q ₂₁
And a differential pair of Q ₂₂ , a control transistor Q ₂₃ ,
It includes load resistors R _E and R _F and a constant current source I ₂₀ . In FIG. 2, the intermediate frequency signal IF is shown as the mixing circuit 5.
Only the system of (0 °) is shown, but the intermediate frequency signal I
The F (90 °) system also uses an equivalent mixing circuit and is applied instead of the Gilbert multiplication circuit 2 in FIG. In the following description, only the system of the intermediate frequency signal IF (0 °) will be described.

The terminals T ₂₁ and T ₂₂ correspond to T ₁ and T ₂ of the Gilbert multiplication circuit 1 of FIG. Further, in the Gilbert multiplication circuit 1 of FIG. 1, the RF signal is transmitted to the terminal T ₃ −.
Had been applied between T _4, since the mixing circuit 5, the control input of this embodiment is only one of the base terminal input of the transistor Q _23, without dividing by resistors, capacitors C to decouple It is supplied to the base terminal of the transistor Q ₂₃ from the terminal T ₂₃ via ₃ . The output voltage is supplied from the load resistors R _E and R _F to the buffer circuit 3 of FIG.

Next, the operation will be described. The mixing circuit 5 of the present embodiment constitutes a single balance type multiplication circuit.
This circuit uses only one differential pair of the Gilbert multiplication circuit which is the double balance type multiplication circuit described in the first embodiment. Therefore, the current analysis can be performed as in the first embodiment.

Transistor Q_{twenty one}Collector current of
I_C21, Transistor Q_{twenty two}The collector current of_C22, To
Langista Q_{twenty three}The collector current of_C23And then the terminal
Le T_{twenty one}-T _{twenty two}Voltage between V₁And terminal T_{twenty three}Potential of
To V₂Then, I_C21= I_C23/ (1 + exp (-V₁/ V_T)) ... (3-1) I_C22= I_C23/ (1 + exp (V₁/ V_T)) (3-2), and I_C23Changes in proportion to the change in base current
Therefore, the collector current I_{C2 1}And I_C22Are in opposite phase to each other
The current value is the input voltage V₁And V₂Proportional to the product of
Changes.

[0038] applying a local oscillation signal LO having a bias voltage V _B1 as the input voltage V _1, by applying an RF signal having a bias voltage V _B2 as the input voltage V _2, the current I
The frequency of the signal included in _C21 and I _C22 is a difference signal between the frequency of the RF signal and the frequency of the local oscillation signal. This current is taken out as a change in voltage generated in the load resistors R _E and R _F , and the transistors Q ₇ and Q _{8 of the} buffer circuit 3 are taken out.
, The buffer circuit 3 operates in the same way as in the first embodiment, and the final intermediate frequency signal IF (0
°) is obtained.

As described above, according to the second embodiment, the frequency mixing circuit can be constructed by using the single balance type multiplication circuit. Even in this mixed circuit, since only NPN type transistors are used as transistors, high-speed operation can be expected and IC
It is also possible. Other Modifications Various modifications are possible without being limited to the above embodiment of the present invention.

For example, in the above embodiment, all the transistors are NPN type transistors, but it is also possible to use all PNP type transistors. In this case, the constant current source, the control transistor and the differential pair are connected in this order from the high potential side.

Further, as the mixing circuit applied to the present invention, another multiplication circuit can be applied. For example, a two-quadrant multiplication circuit and a four-quadrant multiplication circuit that perform two-input multiplication even if the internal configurations are different can be directly applied to the mixing circuit portion. If the mixing circuit has a differential pair, output voltages that are mutually inverted are obtained as a differential output. Therefore, by applying this output voltage to the phase shift circuit, the phase shift operation can be performed even at high frequencies. it can.

[0042]

As described above, according to the first aspect of the present invention, the mixing circuit multiplies the high frequency signal and the local oscillation signal and outputs an intermediate frequency signal which is inverted from each other, and the phase shift circuit outputs these two outputs. Since the phase shift operation is performed by utilizing it, it is possible to easily and economically provide the frequency mixing circuit without using an operational amplifier.

According to the second aspect of the present invention, since the single balance type multiplication circuit using a single differential pair transistor is used as the mixing circuit, output signals whose polarities are inverted to each other are obtained even at a high frequency, and the phase shift is performed. It can be directly applied to the circuit.

According to the third aspect of the invention, since the double balance type multiplication circuit is used as the mixing circuit, two intermediate frequency signals having polarities which are inverted to each other while having a mixing characteristic having high linearity are used. It is possible to obtain a phase shift circuit that can be used even at a high frequency by using both of these signals, and to simply and economically provide the phase shift circuit.

According to the invention described in claim 4, since the phase shift adjustment is performed by using the mixing circuit excellent in the high frequency characteristic as the mixing circuit, it is possible to easily obtain two intermediate frequency signals having different phase states. Then, since the two intermediate frequency signals having different phase states are added, it is possible to provide an image reject mixer circuit which finally takes out only the intermediate frequency signal corresponding to the desired reception frequency.

[Brief description of drawings]

FIG. 1 is a circuit diagram of a first embodiment of the present invention.

FIG. 2 is a circuit diagram of a second embodiment of the present invention.

3A and 3B are explanatory diagrams of a frequency mixing operation, FIG. 3A is a frequency distribution diagram, and FIG. 3B is a concept of frequency mixing.

FIG. 4 is a block diagram of a conventional frequency mixing circuit.

FIG. 5 is a conceptual diagram of a phase shift circuit.

FIG. 6 is a circuit diagram of a conventional phase shift circuit.

[Explanation of symbols]

1, 2 ... Gilbert multiplier cel
l: = double balance type multiplication circuit) 3, 4 ... buffer circuit 5 ... single balance type multiplication circuit 6, 7 ... mixing circuit 8 ... local oscillation supply circuit 9, 10 ... phase shift circuit 11 ... adder 12, 13 ... inverter 15 ... operational amplifier 20 ... mixing circuit 21 ... low-pass filter 100 ... frequency mixing circuit _{Q 1 ~Q 8, Q 11 ~Q} 18, Q 21 ~Q 23 ... transistor _{R 1 ~R 5, R 11 ~R} 15, R _{21 ~R 28, R A, R} B, R
_{C, R D, R E,} R F ... resistor _{C 1 ~C 4, C 11 ~C} 14, C 21 ~C 24 ... Capacitor _{I 1 ~I 3, I 11 ~I} 13, I 20 ... constant current source

Claims (4)

[Claims] 1. A high frequency signal is input as a first original signal, a local oscillation signal is input as a second original signal, and the first original signal and the second original signal are multiplied to obtain the first original signal. A mixing circuit for outputting a mixed signal of a signal and the second original signal and an inverted mixed signal obtained by inverting the mixed signal; and a capacitance means and a resistance means connected in series between the outputs of the mixed signal and the inverted mixed signal. A frequency mixing circuit comprising: a phase shift circuit that outputs an intermediate frequency signal from a connecting portion between the capacitance means and the resistance means. 2. The frequency mixing circuit according to claim 1, wherein the mixing circuit is configured by a single balance type multiplication circuit. 3. The frequency mixing circuit according to claim 1, wherein the mixing circuit is configured by a double balance type multiplication circuit (Gilbert multiplier cell). 4. A high frequency signal is used as a first original signal and a local oscillation signal having no phase shift with respect to the high frequency signal is used as a second original signal to output a first intermediate frequency signal having no phase shift. The frequency mixing circuit according to any one of claims 1 to 3, wherein the local oscillation signal having the high frequency signal as a first original signal and having a phase shift with respect to the high frequency signal has a phase shift with a second original signal. 4. A frequency mixing circuit according to claim 1, which outputs a second intermediate frequency signal, and a frequency mixing circuit.