JPH082180B2 - AC-DC converter - Google Patents

AC-DC converter

Info

Publication number
JPH082180B2
JPH082180B2 JP59059878A JP5987884A JPH082180B2 JP H082180 B2 JPH082180 B2 JP H082180B2 JP 59059878 A JP59059878 A JP 59059878A JP 5987884 A JP5987884 A JP 5987884A JP H082180 B2 JPH082180 B2 JP H082180B2
Authority
JP
Japan
Prior art keywords
circuit
thyristor
output voltage
voltage
current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
JP59059878A
Other languages
Japanese (ja)
Other versions
JPS60204266A (en
Inventor
英明 高原
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Toshiba Corp
Original Assignee
Toshiba Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Toshiba Corp filed Critical Toshiba Corp
Priority to JP59059878A priority Critical patent/JPH082180B2/en
Publication of JPS60204266A publication Critical patent/JPS60204266A/en
Publication of JPH082180B2 publication Critical patent/JPH082180B2/en
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

Links

Classifications

    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/505Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/515Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Inverter Devices (AREA)

Description

【発明の詳細な説明】 〔発明の技術分野〕 本発明は交流入力を直流に変換する交直変換器に関す
る。
Description: TECHNICAL FIELD OF THE INVENTION The present invention relates to an AC / DC converter for converting an AC input into a DC.

〔技術的背景〕[Technical background]

近年ゲートターンオフサイリスタ等の高速にて電流を
オンオフできる半導体素子の発達により直流交流交換器
(インバータ)許りでなく交流直流変換器にも高周波変
調方式が用いられるようになっている。
In recent years, due to the development of semiconductor elements such as gate turn-off thyristors that can turn on / off current at high speed, a high frequency modulation system has come to be used not only in DC / AC converters (inverters) but also in AC / DC converters.

第1図はこの高周波変調により入力交流電流波形の制
御を行い得る単相交流−直流変換器の主回路構成を示し
ており、D1〜D4はダイオード、GT1〜GT4はゲートターン
オフサイリスタ(以下GTOと呼ぶ)でありブリッジ回路
を構成している。このブリッジ回路の入力側には交流電
源SがリアクトルLを介して接続されており、また出力
側にはコンデンサCが並列接続された負荷Mが接続され
ている。
Fig. 1 shows the main circuit configuration of a single-phase AC-DC converter that can control the input AC current waveform by this high-frequency modulation. D1 to D4 are diodes, GT1 to GT4 are gate turn-off thyristors (hereinafter referred to as GTO). It is called) and constitutes the bridge circuit. An AC power supply S is connected to the input side of this bridge circuit via a reactor L, and a load M to which a capacitor C is connected in parallel is connected to the output side.

この回路は、GTOを電源周波数よりかなり高い周波数
でオンオフし、入力電流波形の基本波位相を電圧と同相
になるようにして入力力率を向上させると共に、同時に
入力電流波形を正弦波に近くなるようにして高調波成分
を除去するようにしている。
This circuit turns on and off the GTO at a frequency considerably higher than the power supply frequency to improve the input power factor by making the fundamental wave phase of the input current waveform in phase with the voltage, and at the same time makes the input current waveform close to a sine wave. In this way, harmonic components are removed.

第2図は第1図の回路の動作時各部波形を示したもの
である。この波形図において、期間T1ではGT2、GT4に点
弧信号が与えられているため電源SからリアクトルL、
GT2、D4を介して流れる電流が増加する。次に期間T2に
おいてはGT1、GT4に点弧信号が与えられているが、実際
にはリアクトルLに蓄積されたエネルギによって電流は
減衰しながらも期間T1と同方向に流れようとするため、
ダイオードD4、電源S、リアクトルL、ダイオードD1、
コンデンサCを通して電流が流れる。期間T3では再び期
間T1と同様のGTOに点弧信号が与えられるため再び電流
は増加し同様に期間T4では電流が減少する。この繰返し
により電流を高周波で増加減少させることによって瞬時
波形を制御し位相および波形を制御することができる。
第2図の例では説明のために、変調周波数を電源周波数
に対しあまり高く選んでいないため電流波形では比較的
凹凸の多い波形となっているが、変調周波数を高くとれ
ばより滑らかな波形とすることができる。
FIG. 2 shows waveforms at various parts during operation of the circuit of FIG. In this waveform diagram, since the ignition signal is applied to GT2 and GT4 in the period T 1 , the power source S causes the reactor L,
The current flowing through GT2 and D4 increases. Next, in the period T2, the ignition signal is given to GT1 and GT4, but in reality, the current is going to flow in the same direction as the period T1 while the current is attenuated by the energy accumulated in the reactor L.
Diode D4, power supply S, reactor L, diode D1,
Current flows through the capacitor C. In the period T3, the ignition signal is applied to the GTO similar to the period T1 again, so that the current increases again, and similarly, the current decreases in the period T4. By repeating this process, the current can be increased and decreased at high frequencies to control the instantaneous waveform and thus the phase and waveform.
In the example of FIG. 2, for the sake of explanation, the modulation frequency is not selected so high as to the power supply frequency, so that the current waveform has a relatively irregular waveform, but if the modulation frequency is increased, a smoother waveform is obtained. can do.

〔背景技術の問題点〕[Problems of background technology]

この回路は次のような問題点がある。すなわち入力電
圧と出力電圧の関係は第3図に示すように、直流側のコ
ンデンサ電圧ecが入力交流電圧e1の絶対値e1より常に高
いことを要する。したがって直流負荷としては零電圧か
ら連続に制御を必要とするもの、例えば直流電動機を徐
々に電圧を上げて回転数を制御するような場合には適用
することができない。このような場合には、直流出力側
に電圧を変えることができる回路を更に付加しなければ
ならない。
This circuit has the following problems. That is, the relationship between the input voltage and the output voltage requires that the capacitor voltage ec on the DC side is always higher than the absolute value e1 of the input AC voltage e1, as shown in FIG. Therefore, it cannot be applied to a DC load that requires continuous control from zero voltage, for example, when the DC motor is gradually increased in voltage to control the rotation speed. In such a case, a circuit capable of changing the voltage must be added to the DC output side.

〔発明の目的〕[Object of the Invention]

本発明は上述の点を考慮してなされたもので、直流電
圧を連続的に制御し、しかも大きい負荷をとる状態では
交流電流の位相と波形を高周波制御し外部への影響が少
い交直変換回路を提供することを目的とする。
The present invention has been made in consideration of the above points, and in a state where a direct current voltage is continuously controlled and a large load is applied, the phase and waveform of the alternating current are controlled at a high frequency to reduce the influence on the outside. The purpose is to provide a circuit.

〔発明の概要〕[Outline of Invention]

上述した目的を達成するために、本発明は、自己消弧
性半導体素子とサイリスタとを逆並列接続した回路を2
組直列接続してその中点を交流電源の一方の端子に接続
し、また自己消弧性半導体素子とダイオードもしくはサ
イリスタとを逆並列接続した回路を2組直列接続してそ
の中点を交流電源の他方の端子に接続し、逆並列接続し
た回路の各他端をアノード同士およびカソード同士で接
続してブリッジ回路を構成し、これらアノード同士接続
点およびカソード同士接続点から直流出力電圧を取り出
し、サイリスタの点弧位相制御角を制御して直流出力電
圧を上昇させ、直流出力電圧が最大になった際に、自己
消弧性半導体素子の動作を行って交流電源を流れる交流
電流の位相と波形を制御する交直変換器を提供するもの
である。
In order to achieve the above-mentioned object, the present invention provides a circuit in which a self-extinguishing semiconductor element and a thyristor are connected in antiparallel.
Connect in series and connect the middle point to one terminal of the AC power supply. Also, connect two sets of circuits in which the self-extinguishing semiconductor element and the diode or thyristor are connected in anti-parallel, and connect the middle point to the AC power supply. Connected to the other terminal of the, and the other ends of the circuits connected in anti-parallel are connected to each other between the anodes and the cathodes to form a bridge circuit, and the DC output voltage is extracted from the connection point between the anodes and the connection point between the cathodes, The phase and the waveform of the alternating current flowing through the alternating current power supply by operating the self-extinguishing semiconductor element when the direct current output voltage is increased by controlling the firing phase control angle of the thyristor and the direct current output voltage becomes maximum. It is intended to provide an AC / DC converter for controlling.

〔実施例〕〔Example〕

以下第4図乃至第6図を参照して本発明を実施例につ
き説明する。
Hereinafter, the present invention will be described with reference to FIGS. 4 to 6.

第4図は本発明の一実施例を示したもので、この回路
は第1図の回路におけるダイオードD1,D2をサイリスタT
H1,TH2に置き換えたものであり、第1図と同符号は同一
要素を示す。
FIG. 4 shows an embodiment of the present invention. This circuit has the diodes D1 and D2 in the circuit of FIG.
It is replaced with H1 and TH2, and the same symbols as in FIG. 1 indicate the same elements.

この第4図の回路において、GTOサイリスタGT1〜GT4
のゲートに信号が与えられなければサイリスタTH1,TH2
およびダイオードD3,D4は単なる混合ブリッジ回路とし
て動作を行うもので、サイリスタTH1,TH2に位相制御パ
ルスを与えることにより連続的な直流出力電圧制御がで
きる。
In the circuit of FIG. 4, GTO thyristors GT1 to GT4
If no signal is applied to the gates of thyristors TH1 and TH2
The diodes D3 and D4 operate merely as a mixed bridge circuit, and continuous DC output voltage control can be performed by applying a phase control pulse to the thyristors TH1 and TH2.

第5図はこの様子を示したもので、サイリスタTH1,TH
2に与えるゲート信号すなわち位相制御角αを180゜から
順次0゜へ近付けることにより直流出力電圧の連続制御
を行う。
Fig. 5 shows this state. Thyristors TH1, TH
The DC output voltage is continuously controlled by gradually approaching the gate signal given to 2 (ie, the phase control angle α) from 180 ° to 0 °.

第6図は高周波変調運転を行う際のサイリスタTH1,TH
2に与えるゲート信号を示したものである。このゲート
信号は直流電圧最大となったところでGTOサイリスタGT1
〜GT4と協調をとって与えられ、これにより第4図の回
路は第1図の回路と同一機能となるため、この時点から
高周波変調運転を行うことができる。
Fig. 6 shows thyristors TH1 and TH when performing high frequency modulation operation.
2 shows the gate signal given to 2. This gate signal is the maximum DC voltage GTO thyristor GT1
~ GT4 in cooperation with each other, the circuit of Fig. 4 has the same function as the circuit of Fig. 1, so that high frequency modulation operation can be performed from this point.

このような運転を行った場合、GTOサイリスタGT1〜GT
4を動作させない期間では当然に入力電流は従来の通常
の整流器と同一となるため入力力率も比較的良くはない
し波形歪による高調波の発生も従来の整流器に比べて何
ら改善はない。しかしこの領域では入力電力自体が少い
ため発生無効電力も少く、また電流の絶対値も少いため
高調波自体も少い。そして直流出力電圧が大となり消費
電力が大となると高周波変調による本来の機能を発揮す
る。
When such an operation is performed, GTO thyristor GT1 ~ GT
In the period when 4 is not operated, the input current is naturally the same as that of the conventional normal rectifier, so the input power factor is relatively good, and the generation of harmonics due to waveform distortion is not improved at all compared to the conventional rectifier. However, in this region, the input power itself is low, so the reactive power generated is low, and the absolute value of the current is low, so the harmonics are low. When the DC output voltage becomes large and the power consumption becomes large, the original function by high frequency modulation is exerted.

第7図は本発明の他の実施例を示す回路図であり、第
4図におけるダイオードD3,D4をそれぞれサイリスタTH
3,TH4に置き換えた点を除き第4図の実施例と同一であ
る。
FIG. 7 is a circuit diagram showing another embodiment of the present invention, in which the diodes D3 and D4 in FIG.
It is the same as the embodiment of FIG. 4 except that it is replaced with TH4.

この回路におけるサイリスタTH1〜TH4の制御は、第4
図の回路と同様に直流負荷電圧が小のときは通常の位相
制御整流器として動作させ直流負荷電圧大の領域では高
周波変調交流直流変換器として動作させるものである。
The control of the thyristors TH1 to TH4 in this circuit is the fourth
Similar to the circuit shown in the figure, when the DC load voltage is small, it operates as a normal phase control rectifier, and in the region where the DC load voltage is large, it operates as a high frequency modulation AC / DC converter.

第8図は第7図の実施例における入力電力が少いとき
の各サイリスタに与えるゲート信号の例を示したもの
で、第5図の場合と同様に位相制御角αを順次制御する
ことにより直流電圧の平均値を小さい値から大きい値へ
制御することができる。
FIG. 8 shows an example of the gate signal given to each thyristor when the input power is small in the embodiment of FIG. 7, and by sequentially controlling the phase control angle α as in the case of FIG. The average value of the DC voltage can be controlled from a small value to a large value.

第9図は、直流電圧が最大となった後にサイリスタTH
1〜TH4およびGTOサイリスタGT1〜GT4に与えるべきゲー
トパルスを示したもので、第6図に示したものと同様に
第7図の回路に高周波変調運転を行わせる。
Fig. 9 shows thyristor TH after the DC voltage becomes maximum.
The gate pulses to be given to 1-TH4 and GTO thyristors GT1-GT4 are shown, and the circuit of FIG. 7 is made to perform high frequency modulation operation like the one shown in FIG.

〔変形例〕(Modification)

上記実施例では単相交流直流変換器を説明したが、本
発明を多相変換器に適用することもできる。
Although a single-phase AC / DC converter has been described in the above embodiment, the present invention can also be applied to a polyphase converter.

〔発明の効果〕〔The invention's effect〕

本発明は上述のように、GTO等の自己消弧性半導体素
子とサイリスタとの逆並列回路2組ならびにGTO等の自
己消弧性素子とダイオードもしくはサイリスタとの逆並
列回路2組によってブリッジ回路を構成し、このブリッ
ジ回路を入力電力が少いときは位相制御整流器として、
また入力電力が大となったら高周波変調整流器として動
作させるようにしたため、特別の電圧調整装置を必要と
せずに出力電圧を零から連続的に増すような制御ができ
る。しかも入力電流が大きく負荷電力の大きい状態では
入力電流の位相を入力電圧の位相と等しくなるように制
御して入力力率をよくし、電圧降下や不要な発熱の低
減、さらには同一電力系統の他の機器への影響を少くす
る等の効果を発揮するばかりでなく、入力電流波形を正
弦波に近くなるように制御し高調波電流の発生を低減す
ることができる。
As described above, the present invention forms a bridge circuit by two sets of anti-parallel circuits including a self-extinguishing semiconductor device such as GTO and a thyristor and two sets of anti-parallel circuits including a self-extinguishing device such as GTO and a diode or thyristor. Configure this bridge circuit as a phase control rectifier when the input power is low,
Further, since the high-frequency modulation rectifier is operated when the input power becomes large, it is possible to continuously increase the output voltage from zero without requiring a special voltage regulator. Moreover, when the input current is large and the load power is large, the input current phase is controlled to be equal to the input voltage phase to improve the input power factor, reduce voltage drop and unnecessary heat generation, and reduce the Not only can the effects on other devices be reduced, but the input current waveform can be controlled to be close to a sine wave to reduce the generation of harmonic currents.

【図面の簡単な説明】[Brief description of drawings]

第1図は従来の高周波変調交直変換器の主回路を示す
図、第2図は第1図の回路の動作説明図、第3図は第1
図の回路の入出力電圧関係説明図、第4図は本発明の一
実施例の回路図、第5図は第4図の回路を位相制御動作
させたときの各部波形を示す図、第6図は第4図の回路
を高周波変調動作させたときの各部波形を示す図、第7
図は本発明の他の実施例の回路図、第8図は第7図の回
路を位相制御動作させたときの各部波形を示す図、第9
図は第7図の回路を高周波変調動作させたときの各部波
形を示す図である。 GT……GTO、D……ダイオード、TH……サイリスタ。
FIG. 1 is a diagram showing a main circuit of a conventional high-frequency modulation AC / DC converter, FIG. 2 is an operation explanatory diagram of the circuit of FIG. 1, and FIG.
FIG. 4 is an explanatory diagram of input / output voltage relations of the circuit of FIG. 4, FIG. 4 is a circuit diagram of an embodiment of the present invention, FIG. 5 is a diagram showing waveforms of respective parts when the circuit of FIG. FIG. 7 is a diagram showing waveforms at various parts when the circuit of FIG. 4 is subjected to high frequency modulation operation, FIG.
FIG. 8 is a circuit diagram of another embodiment of the present invention, FIG. 8 is a diagram showing waveforms at various parts when the circuit of FIG. 7 is operated in phase control, and FIG.
The figure is a diagram showing waveforms at various parts when the circuit of FIG. 7 is subjected to high frequency modulation operation. GT ... GTO, D ... Diode, TH ... Thyristor.

Claims (1)

【特許請求の範囲】[Claims] 【請求項1】自己消弧性半導体素子とサイリスタとを逆
並列接続した回路を2組直列接続してその中点を交流電
源の一方の端子に接続し、 また自己消弧性半導体素子とダイオードもしくはサイリ
スタとを逆並列接続した回路を2組直列接続してその中
点を交流電源の他方の端子に接続し、 前記逆並列接続した回路の各他端をアノード同士および
カソード同士で接続してブリッジ回路を構成し、 これらアノード同士接続点およびカソード同士接続点か
ら直流出力電圧を取り出し、前記サイリスタの点弧位相
制御角を制御して前記直流出力電圧を上昇させ、前記直
流出力電圧が最大になった際に、前記自己消弧性半導体
素子の動作を行って前記交流電源を流れる交流電流の位
相と波形を制御する交直変換器。
1. A self-extinguishing semiconductor device and a thyristor are connected in antiparallel and two sets of circuits are connected in series, the middle point of which is connected to one terminal of an AC power source. Alternatively, two sets of circuits connected in anti-parallel with a thyristor are connected in series, the middle point is connected to the other terminal of the AC power supply, and the other ends of the circuits connected in anti-parallel are connected to each other between anodes and cathodes. A bridge circuit is configured, and a DC output voltage is taken out from the connection point between the anodes and the connection point between the cathodes, and the firing phase control angle of the thyristor is controlled to increase the DC output voltage, thereby maximizing the DC output voltage. An AC / DC converter that controls the phase and waveform of the AC current flowing through the AC power supply by operating the self-extinguishing semiconductor element when it becomes low.
JP59059878A 1984-03-28 1984-03-28 AC-DC converter Expired - Lifetime JPH082180B2 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP59059878A JPH082180B2 (en) 1984-03-28 1984-03-28 AC-DC converter

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP59059878A JPH082180B2 (en) 1984-03-28 1984-03-28 AC-DC converter

Publications (2)

Publication Number Publication Date
JPS60204266A JPS60204266A (en) 1985-10-15
JPH082180B2 true JPH082180B2 (en) 1996-01-10

Family

ID=13125845

Family Applications (1)

Application Number Title Priority Date Filing Date
JP59059878A Expired - Lifetime JPH082180B2 (en) 1984-03-28 1984-03-28 AC-DC converter

Country Status (1)

Country Link
JP (1) JPH082180B2 (en)

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS62207177A (en) * 1986-03-06 1987-09-11 Fuji Electric Co Ltd Control method of pulse width modulation converter
JP2595593B2 (en) * 1987-12-21 1997-04-02 三菱電機株式会社 Rectifier

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5336563A (en) * 1977-10-01 1978-04-04 Masami Ikemura Conveying apparatus

Also Published As

Publication number Publication date
JPS60204266A (en) 1985-10-15

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