JPH05184148A - Resonant switching power supply - Google Patents

Abstract

PURPOSE:To achieve resonance regardless of the fluctuation of capacitor charging voltage by switching a charging circuit from parallel operation to series operation when the charging voltage reaches a predetermined level and then charging a main capacitor. CONSTITUTION:A switching circuit 58 is turned OFF and a switching element(SW) 55 is turned OFF so long as the charging voltage V0 is lower than about half of the maximum voltage. Consequently, a charging circuit for the secondary winding(SC) 51, a diode bridge(DB) 52 and a diode(DD) 54 operates in parallel with a charging circuit for an SC51', DB52' and a DD53 to charge a main capacitor(MC') 14. When the charging voltage V0 reaches about half of the maximum voltage, the switching circuit 58 turns ON to conduct the SW55. Consequently, a transmission voltage is applied on the DD53, DD54 to short- circuit the negative terminal of the DB52 and the positive terminal of the DB 52' through the SW55. In other words, two sets of rectifying circuits operate in series to charge the MC14.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a resonance type switching power supply. In particular, when the high frequency voltage generated on the secondary side of the output transformer is changed to a DC voltage to charge the capacitor and then the capacitor is charged to a constant voltage, the load is discharged. Then, the present invention relates to one in which this charging and discharging is repeated.

[0002]

2. Description of the Related Art Conventionally, as a circuit for repeatedly charging and discharging a capacitor by a switching power supply, a circuit based on pulse width modulation (hereinafter referred to as PWM) is generally used. For example, an example thereof is shown in FIG. This circuit uses a flash lamp as the load. In FIG. 1, 1 is an AC power supply, 2 is a diode bridge, 3,
4 is an electrolytic capacitor connected in series for smoothing and dividing the direct current obtained by rectifying the AC voltage, 5 is an inductance, 6 is a voltage conversion transformer (hereinafter referred to as transformer), and 61 is its primary winding. , 62 are secondary windings, respectively. 7 is a current detection circuit, 8 and 9 are diodes,
Switching elements 10, 11 are MOS in this case.
I am using FET. 13 is a diode bridge for high frequency rectification, 14 is a main capacitor, 15 is an inductance for optimizing the waveform of the discharge current of the capacitor 14, 16
Is a flash lamp as a load, 17 is an output of the current detection circuit 7, and turns on the switching elements 10 and 11.
The drive signal generation circuits for off control are shown respectively.
Vi represents the output voltage of the diode 2, and the voltage across each of the electrolytic capacitors 3 and 4 is half that, (1/2) × V.
i. Further, the charging voltage of the main capacitor 14 is set to V0.

FIG. 2 is a time chart diagram in the circuit of FIG. The current flowing through the inductance 5 is Ip, and the drive signals for the switching elements 10 and 11 are Vg1 and Vg2, respectively. In FIG. 2, the drive signals Vg1 and Vg2 have an appropriate dead time DT so that they do not overlap in time, and the drive signal generation circuit 17
Is generated from. The timing at which each drive signal turns off is the time when the current value Ip detected by the current detection circuit 7 reaches the preset limit values Ic and -Ic. Further, the timing of turning on is the time when the set dead time has passed after the other signal turned off at the above timing.

(1) Description of Current Ip in Period in FIG. 2 Now, the drive signal Vg1 is applied to the switching element 10, at which time the electric field capacitor 3 → switching element 10 → primary winding 61 → inductance 5 → A current Ip flows in a closed circuit formed by the electric field capacitor 3. When the winding ratio of the transformer 6 is n (n is the primary winding 61 of the transformer 6 / the secondary winding 62 of the transformer 6), nV0 counter electromotive force is generated at both ends of the primary winding 61. (However, the voltage drop due to the diode bridge 13 is ignored.) At this time, the inductance 5 is (1/2) × Vi-nV0
Is applied. Then, assuming that the self-inductance of the inductance 5 is L, the current Ip linearly increases with a slope (dIp / dt) determined by L × (dIp / dt) = (1/2) Vi−nV0. (However, the voltage change due to the discharge of the electric field capacitor 3 and the voltage drop when the switching element 10 is turned on are ignored.)

(2) Description of Current Ip in Period in FIG. 2 When the current Ip reaches the limit value Ic, the switching element 10 is turned off as described above. Then, the energy accumulated in the inductance 5 is released, and the current Ip commutates to the diode 9. After that, the current Ip flows in the closed circuit formed by the diode 9 → the primary winding 61 → the inductance 5 → the electrolytic capacitor 4 → the diode 9 to charge the electrolytic capacitor 4. The voltage across the electrolytic capacitor 4 and the primary winding 61 at this time has a polarity opposite to that of the current Ip, and the current Ip has a gradient determined by L × (dIp / dt) = − ((1/2) Vi + nV0). Decrease. As can be seen in the figure, the rate of change during the period is smaller than that during the period.
The current flows through the diode 9 until the current Ip becomes zero, so that the current does not flow even if the drive signal Vg2 is applied to the switching element 11 in the middle.

(3) Description of Current Ip in Period in FIG. 2 After all the stored energy in the inductance 5 is released, the current Ip as shown in the period starts to flow in the switching element 11. The operation at this time is the same as that of the period although the polarity is different, and thus the description is omitted. In this way, the main capacitor 14 is charged and energy is accumulated by repeating the period ,. Then, when the charged energy reaches a certain constant value, a trigger (not shown) is applied to discharge the charged energy at once. This causes the lamp to emit light. This light emission is performed at, for example, 2 to 5 Hz.
Although the operation of the circuit shown in FIG. 1 has been described above, the charging voltage V0 of the output capacitor 14 changes 10 times or more before and after the flash lamp 16 emits light. Therefore, the counter electromotive force nV0 generated in the primary winding 61 is
Also changes greatly.

In the case of the conventional PWM control switching circuit, the following problems occur. (1) Since the switching elements 10 and 11 turn off at the maximum point of the triangular waveform depending on the current value Ip, a very large switching loss and switching noise are generated. Therefore, a large and expensive switching element, noise filter, etc. are required. (2) In the waveform of the current Ip shown in FIG. 2, the period is
This is the time during which the energy stored in the inductance 5 is released. A part of this energy is charged in the main capacitor 14 via the transformer 6. However, most of them return to the electrolytic capacitor 4 without being used as charging energy. The ratio between the energy used as the charging voltage and the energy that is fed back to the electrolytic capacitor is as follows:
It corresponds to the ratio of the voltage across the electrolytic capacitor 4. The rate at which the stored energy is used as charging energy in the main capacitor 14 is immediately before the lamp 16 emits light (when V0 is high), and about half the amount immediately after the emission (V0).
(When 0 is low), it is rarely used. As described above, it is very inefficient to store and release the energy that is not effectively used in the inductance 5. That is, returning the energy supplied from the AC power supply again without using it for the load increases the loss of the elements constituting the circuit.

Therefore, recently, as a method for solving such a problem, the use of a resonance type switching power supply has been studied. An example thereof is shown in FIG. In the figure, 30 indicates a smoothing electrolytic capacitor. Reference numerals 31 and 32 denote resonance capacitors. Reference numerals 33 and 34 denote diodes for clamping the voltage across the resonance capacitor to be equal to or lower than the voltage across the smoothing capacitor 30. Reference numeral 35 represents a resonance inductance. Reference numeral 36 denotes a resonance tank composed of the resonance capacitors 33 and 34 and the resonance inductance 35. V in the figure
s represents the voltage across the diode 9, and Vc represents the voltage across the resonant capacitor 32. The current Ip represents the current flowing through the resonance inductance 35 and the primary winding 61. Other,
Since the same numbers are the same as those in FIG. 1, description thereof will be omitted. This circuit is commonly referred to as an improved series resonant converter. Since the flash lamp 16 is used as a load as in the circuit shown in FIG. 1, the charging voltage V0 of the main capacitor 14 varies greatly each time the lamp emits light. FIG. 4 shows a time chart corresponding to FIG. FIG. 4 (a) shows each value immediately after the lamp emits light and when the charging voltage V0 is small. FIG. 4B shows the respective values when the charging voltage V0 is high immediately before the lamp emits light. A normal resonant converter operates with a waveform as shown in FIG. 4 (b), but in the case where the charging voltage V0 changes significantly, the operation as shown in FIG. 4 (a) also occurs. Vg1 and Vg2 are drive signals from the drive signal generation circuit 17, but in the case of the resonance type circuit, the pulse width during the ON period is fixed to about 1.2 times the resonance half cycle.
That is, the output control generally changes the frequency (hereinafter, referred to as an operating frequency) instead of changing the pulse width like PWM. The series resonance tank 36 composed of the resonance capacitors 6 and 7 and the resonance inductance 8 resonates at the resonance frequency fr.

(1) Description of the period in FIG. 4 (a) and the period in FIG. 4 (b) In FIG. 4 (a),
During the period, the switching element 10 is on. At this time, capacitor 30 → switching element 10 → primary winding 61 → resonance inductance 35 → resonance capacitor 32
→ Resonant current flows in the closed circuit of the capacitor 30. Then, the resonance capacitor 32 is charged to Vi. On the other hand, the resonance capacitor 31 → the switching element 10 → the primary winding 6
A resonance current also flows in a closed circuit formed of 1 → resonance inductance 35 → resonance capacitor 31 and discharges the resonance capacitor 31 from Vi to zero. A current Ip obtained by combining both resonance currents flows through the switching element 10, the primary winding 61, and the resonance inductance 35. In the section, when the time at which the current Ip starts to flow is t0, the self-inductance of the resonance inductance 35 is L, and the capacitances of the resonance capacitors 31 and 32 are C, the current Ip is

[0011]

[Equation 1]

It is represented by From this equation, it can be seen that the smaller the charging voltage V0, the larger the current Ip. That is, the charging voltage Vc of the resonance capacitor 32 is small in the resonance half cycle immediately after the lamp emits light when the charging voltage V0 is small.
Will reach the voltage Vi across the capacitor 30 at an early point. On the other hand, in FIG. 4B, the charging voltage V0 is
Since it is higher than that in the case of FIG. 4A, the current Ip has a small value. Therefore, the charging voltage Vc of the resonance capacitor 32 becomes
As for the timing when the voltage Vi across the capacitor 30 is reached,
It is later than in FIG.

(2) Description of the period in FIG. 4A and the period in FIG. 4B 'When the charging voltage Vc of the resonance capacitor 32 reaches the voltage Vi across the capacitor 30, the current Ip changes from the period to the period. It becomes the state of. This time is designated as t1. Then, the resonance is stopped, and the current flowing through the resonance capacitors 31 and 32 is changed to the diode 33.
Commute to. During the period, both the voltage Vc and the voltage Vs are Vi, and the value obtained by adding the counter electromotive force generated in the primary winding 61 and the voltage of the resonance inductance 35 becomes zero. Therefore, the counter electromotive force generated in the primary winding 61 is nV0
Therefore, nV0 + L × (dIp / dt) = 0, and (dIp / dt) =-(n / L) V0 Since V0 immediately after the lamp 16 emits light is a very small value, (dIp / dt) ) Has a small absolute value,
Ip is gradually reduced, and the energy stored in the inductance 35 is slowly released to charge the capacitor 14 via the transformer 6 during this period. On the other hand, the basic operation in the period 'in FIG. 4 (b) is the same as that in the period, but the current Ip decreases at a large rate because the charging voltage V0 is large. That is, the current Ip becomes zero before the switching element 10 is turned off, and all the energy stored in the resonance inductance 35 is used for charging the main capacitor 14 via the transformer 6.

(3) Description of the period in FIG. 4A and the period'in FIG. 4B 'Switching element 10
When is turned off (t2), the operation mode shifts from period to period. When the switching element 10 is turned off, the current Ip flowing in the period is commutated to the diode 9. Then, the current flows in the closed circuit of the diode 9, the primary winding 61, the resonance inductance 35, the diode 33, the capacitor 30, and the diode 9. If the voltage drop in the diode 33 and the diode 9 is ignored, the sum of the voltages in the closed circuit becomes zero, and Vi + L × (dIp / d
t) + nV0, and therefore (dIp / dt) =-
(1/2) (Vi + nV0), which shows that the current Ip decreases more rapidly in the period than in the period. Then, at time t3, the current Ip becomes zero. The period is a time when the energy stored in the resonance inductance 35 is released, and a part of the energy is charged in the main capacitor 14 through the transformer 6, but most of the energy is charged in the electrolytic capacitor 30. I will return in a form. More specifically, the ratio of the charging energy to the main capacitor 14 and the charging energy returned to the electrolytic capacitor 30 is nV0 to Vi. That is, when the charging voltage V0 is small immediately after the light emission, most of the energy is not effectively used. When the current Ip becomes zero (t3 in FIG. 4), the resonance inductance 35
Of the stored energy is released and the half cycle of the resonant operation is completed. Hereinafter, the period, the period, and the operation of the period are essentially the same as the period, the period, and the operation of the period, and the description thereof will be omitted.

That is, as described with reference to FIGS. 3 and 4,
In the case of the resonance type switching power supply, the current Ip becomes zero as shown in FIG. 4 (b) when the charging voltage V0 of the capacitor 14 which is the load is larger than that in the PWM system (that is, immediately before the light emission of the lamp 16). The switching element is turned off at the timing when it becomes low, so that the switching loss and the switching noise can be suppressed low.
Furthermore, since all the stored energy of the resonance inductance 35 is used for charging the main capacitor 14 via the transformer 6, the stored energy can be effectively used. On the other hand, as can be seen in FIG. 4A, when the charging voltage V0 of the capacitor 14 is low (immediately after the light emission of the lamp 16), when the switching element 10 is turned off (t2), the current Ip is at the highest point. No, but it's quite expensive. Therefore, the problems of switching loss and switching noise still remain. Furthermore, since the stored energy of the inductance is turned off while being turned off, most of the stored energy is fed back to the electrolytic capacitor. That is, as in the PWM method, the energy supplied from the AC power supply is returned to the load without being used, and thus the loss of the elements forming the circuit increases. Generally, in such a resonance circuit, when the voltage fluctuation of the load is large, the winding of the transformer is set for a high voltage state. (That is, in this case, when the charging voltage of the main capacitor 14 is high) This is because if the winding is set for the time when the voltage is low, the resonance operation does not occur when the voltage is high. Therefore, when the resonance circuit is used, there is no problem when the voltage value is high, but when the voltage value is low, the same problem as the PWM method still remains.

[0016]

The problem to be solved by the present invention is to solve the following points in a resonance type switching power supply used for repeatedly charging and discharging a capacitor even when the charging voltage is low. It is in. (1) To reduce switching noise and switching loss due to the switching element and to use a small and inexpensive switching element and noise filter. (2) To prevent or reduce the stored energy of the resonant inductance from being fed back to the electrolytic capacitor on the primary side without being used by the load, the switching element is turned off with the stored energy being as small as possible. Especially.

[0017]

In order to solve such a problem, the resonance type switching power supply of the present invention is a power supply which stores energy in a main capacitor and discharges this energy to a load. Then, this charging / discharging is repeated. In such a resonance type switching power supply, a voltage conversion transformer, a resonance tank composed of a resonance inductance and a resonance capacitor connected to the primary winding of the transformer, and a secondary side of the transformer, which is divided into a plurality of parts. The secondary winding includes a charging circuit connected to each of the secondary windings to charge the main capacitor, a charging voltage detection circuit for the main capacitor, and a switching circuit driven by a signal from the detection circuit. The switching circuit has means for switching the respective charging circuits from parallel operation to series operation to charge the main capacitor when the charging voltage reaches a predetermined value.

[0018]

With the circuit having such a configuration, even if the charging voltage of the capacitor fluctuates greatly, the secondary winding and the operation of the charging circuit are switched from parallel to series, so that the fluctuation is hardly affected. Can be resonated.

[0019]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS The present invention will be specifically described below with reference to the drawings. FIG. 5 is an example of the resonance type switching power supply according to the present invention, and shows only the secondary side of the transformer 6 of the circuit shown in FIG. That is, the primary side is the same as in FIG. Further, the same numbers as those in FIG. 3 indicate the same parts. The secondary winding of the transformer 6 is divided into two windings 51 and 51 '. The number of turns of each is the secondary winding 62 shown in FIG.
The number of turns is 1/2. High frequency rectifier diode bridges 52 and 52 'are connected to the windings 51 and 51', respectively. Reference numerals 53 and 54 denote diodes. The positive side terminal of the diode bridge 52 'is connected to the anode of the diode 53, and the cathode of the diode 53 is connected to the positive side terminal of the diode bridge 52 and the positive side terminal of the capacitor 14. .. The negative side terminal of the diode bridge 52 is connected to the cathode of the diode 54, and the anode of the diode 54 is connected to the negative side terminal of the diode bridge 52 ′ and the negative side terminal of the main capacitor 14. Secondary winding 51,
The diode bridge 52 and the diode 54 configure one charging circuit, and the secondary winding 51 ′, the diode bridge 52 ′ and the diode 53 configure another charging circuit. Switching element 55 (in this embodiment,
I am using an IGBT. ), Its collector is connected to the anode of diode 53, and its emitter is diode 5
4 cathode. The charging voltage detection circuit 57 detects the value of the charging voltage V0 of the capacitor 14 and outputs a signal Vg3 for opening and closing the switching element 55 via the switching circuit 58. The switching element 55 is an IGB
Not limited to T, MOSFET, bipolar transistor and the like can be applied.

In this circuit, the switching circuit 5 is operated until the charging voltage V0 becomes about 1/2 of the set maximum voltage value.
The signal Vg3 from 8 is off, so the switching element 55 is off. The maximum voltage value in this case refers to the value set as the charging voltage of the capacitor 14 when the lamp 16 emits light. This maximum voltage value is prevented from being charged more than this value by an output voltage limiting circuit (not shown). When the switching element 55 is off, one charging circuit composed of the secondary winding 51, the diode bridge 52, and the diode 54, and the secondary winding 51 ′,
The other charging circuit composed of the diode bridge 52 ′ and the diode 53 operates in parallel and charges the main capacitor 14. Therefore, the charging voltage V0 is applied to each of the secondary windings 51 and 51 '. (However, the voltage drop due to the diode in the circuit on the secondary winding side is ignored.)

Next, when the charging of the main capacitor 14 progresses and the charging voltage V0 thereof reaches about 1/2 of the maximum voltage value, the output signal Vg3 of the switching circuit 58 is turned on and the switching element 55 becomes conductive. At this time, the reverse voltage is applied to the diode 53 and the diode 54, and the negative side terminal of the diode bridge 52 and the diode bridge 5 are connected.
The positive terminal of 2 ′ is short-circuited via the switching element 55. That is, the two sets of rectifier circuits operate in series,
The main capacitor 14 will be charged. At this time, the charging voltage of the main capacitor 14 is applied to the secondary winding 51 and the secondary winding 51 'in half, that is, a voltage of 1 / 2.times.V0 is applied. In the latter half of the charging cycle in which each rectifying circuit is connected in series, the secondary winding is divided into two, but the total number of turns is the same as when there is one, and basically the circuit of FIG. Same as the case. On the other hand, when they are connected in parallel, the charging voltage V0 is applied to each of the two secondary windings whose number of turns is halved. Therefore, as compared with the circuit example of FIG. 3 in which the number of secondary windings is one, the voltage per turn is 2
Doubled. That is, the voltage across the primary winding 61 (counter electromotive force) of the transformer 6, which is determined by the value of the charging voltage V0, is 2 as compared with the conventional circuit until the charging voltage V0 becomes about 1/2 of the maximum voltage value. It becomes double, that is, 2nV0, and after it exceeds about 1/2, it becomes nV0 as in the case of FIG. That is, the problem that occurs when V0 is small at the initial stage of charging is solved by switching the series or parallel connection of a plurality of charging circuits.
It is devised so that the voltage between both ends of 1 becomes large. For example, the charging voltage V0 changes about 10 times before and after the flash lamp 16 emits light. At this time, in the case of the conventional circuit, the counter electromotive force generated in the primary winding 61 also changes ten times, but in the case of the present invention, the change can be suppressed to about five times. Therefore, the amplitude of the current Ip at the beginning of charging can be brought close to the waveform at the end of charging. That is, the current due to the release of stored energy when the switching element is turned off can be considerably reduced. Therefore, the switching loss and the switching noise in the switching element can be suppressed to a low level, and further, the amount of energy to be returned without being used for the load can be suppressed to a low level.

Another embodiment of the present invention is shown in FIG. In this circuit, the secondary winding 61 of the transformer 6 is
It is divided into four secondary windings of -2, 71-3, and 71-4, and the number of turns of each is 1/4 of that of the primary winding. The charging voltage detection circuit 57 outputs Vg3-1 and Vg3-2 when the charging voltage V0 becomes about 1/4 of the maximum voltage value,
The switching elements 75-1 and 75-2 are turned on. When the maximum voltage value becomes about 1/2, Vg3-3 is output and the switching element 75-3 is turned on.
At this time, switching elements 75-1, 75-2, 75-
All three are on. This state is shown in FIG. According to this circuit, the fluctuation range of the counter electromotive force generated in the secondary winding 61 during the resonance operation can be suppressed to about 1/4. Therefore, when the charging voltage V0 is small, the operation of the current Ip can be made closer to that shown in FIG. 4B, so that the switching loss and the switching noise in the switching element can be further suppressed. Furthermore, the switching element can be turned off with a small amount of accumulated energy. Therefore, the energy that returns without being used as a load can be further reduced.

Although the embodiment has been specifically described above, the following may be used, for example. The flash lamp 16 is a lamp that emits light with a light emission length of 400 mm, a light emission energy of 400 J, and 4 Hz. In addition, the main capacitor 14
Has a maximum voltage value of 1800V and a resonance inductance of 2
A capacitor with 0 μH and a resonance capacitor of 0.15 μF can be used.

[0024]

According to the present invention, the counter electromotive force generated in the primary winding of the transformer can be suppressed to a considerably small fluctuation range even if the charging voltage of the capacitor fluctuates greatly due to the light emission of the flash lamp, for example. You can Therefore, switching loss and switching noise due to the switching element can be suppressed to a considerably low level. Further, since the switching element is turned off in a state where the energy stored in the inductance forming the resonance tank is as small as possible, the amount of energy fed back can be reduced without using it as a load. Therefore, it is possible to reduce the loss of the elements that form the circuit.

[Brief description of drawings]

FIG. 1 is a circuit diagram of a PWM type switching power supply.

FIG. 2 is a time chart diagram of a circuit diagram of a PWM switching power supply.

FIG. 3 is a circuit diagram of a resonant switching power supply.

FIG. 4 is a time chart diagram by a circuit diagram of a resonance type switching power supply.

FIG. 5 is a circuit diagram of a resonance type switching power supply of the present invention.

FIG. 6 is a circuit diagram of another embodiment of the resonance type switching power supply of the present invention.

FIG. 7 is a time chart diagram of a circuit diagram of another embodiment of the resonance type switching power supply of the present invention.

[Explanation of symbols]

 6 transformer 10 switching element 11 switching element 14 main capacitor 30 electrolytic capacitor 31 resonant inductance 35 resonant capacitor 36 resonant tank 51 secondary winding 52 diode bridge 53 diode 51 'secondary winding 52' diode bridge 54 diode 55 switching element 57 charging Voltage detection circuit 58 Switching circuit 61 Primary winding of transformer 62 Secondary winding of transformer

Claims (1)

[Claims] 1. A resonance type switching power supply in which an operation of storing energy in a main capacitor and discharging this energy to a load is repeated periodically, in a voltage conversion transformer and a resonance connected to a primary winding of the transformer. A resonance tank composed of an inductance and a resonance capacitor, a secondary winding on the secondary side of the transformer, divided into a plurality of secondary windings, and a charging for charging the main capacitor by connecting to each of the secondary windings. A main circuit, a charging voltage detection circuit for the main capacitor, and a switching circuit driven by a signal from the detection circuit, wherein the switching circuit is configured to charge the plurality of charging circuits when the charging voltage reaches a predetermined value. A resonance type switching power supply having means for switching a circuit from parallel operation to series operation to charge a main capacitor.