JPH0449851A - Driving circuit for dc/dc converter - Google Patents
Driving circuit for dc/dc converterInfo
- Publication number
- JPH0449851A JPH0449851A JP16013790A JP16013790A JPH0449851A JP H0449851 A JPH0449851 A JP H0449851A JP 16013790 A JP16013790 A JP 16013790A JP 16013790 A JP16013790 A JP 16013790A JP H0449851 A JPH0449851 A JP H0449851A
- Authority
- JP
- Japan
- Prior art keywords
- mosfet
- gate
- mosfets
- terminal
- source
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 238000004804 winding Methods 0.000 claims description 23
- 230000000630 rising effect Effects 0.000 abstract 2
- 230000000694 effects Effects 0.000 description 2
- 238000010586 diagram Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000004904 shortening Methods 0.000 description 1
Landscapes
- Dc-Dc Converters (AREA)
- Electronic Switches (AREA)
Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は、DC−DCコンバータのドライブ回路、特に
、スイッチングMOSFETのON時の遅延時間のみ長
くして、MOSFETにかかるストレスおよび発生する
ノイズを低減するDC−DCコンバータのドライブ回路
に関する。Detailed Description of the Invention [Industrial Field of Application] The present invention increases the delay time of the drive circuit of a DC-DC converter, especially when the switching MOSFET is turned on, thereby reducing stress on the MOSFET and noise generated. The present invention relates to a drive circuit for a DC-DC converter that reduces power consumption.
従来、この種のDC−DCコンバータの)’−IFイブ
回路は、第2図に示すように、ドライブトランス9の2
次巻線19の巻き始めのMOSFETI5のゲート端子
を接続し、ドライブトランス9の2次巻線19の巻き終
りとMO8FEr16のソース端子を接続し、MOSF
ET15のゲート端子、ソース端子間に並列に抵抗21
を接続している。Conventionally, the )'-IF circuit of this type of DC-DC converter has two parts of the drive transformer 9, as shown in FIG.
Connect the gate terminal of MOSFET I5 at the beginning of winding of the next winding 19, connect the end of winding of the secondary winding 19 of the drive transformer 9 and the source terminal of MO8FEr16,
Resistor 21 is connected in parallel between the gate terminal and source terminal of ET15.
are connected.
トランスの2次巻線19の巻き初めと巻き終り間にパル
ス電圧を発生させることによって抵抗21にパルス電圧
を発生させ、MOSFET15のゲート端子、ソース端
子間にスイッチング信号となるパルス電圧を与えてMO
SFET15をスイッチングさせている。By generating a pulse voltage between the beginning and end of the winding of the secondary winding 19 of the transformer, a pulse voltage is generated in the resistor 21, and a pulse voltage serving as a switching signal is applied between the gate terminal and the source terminal of the MOSFET 15.
SFET15 is switched.
上述した従来のDC−DCコンバータのドライブ回路は
、MOSFETのゲート・ドレイン間に印加するスイッ
チング信号の立ち上り時立ち下り時の遅延時間を短縮さ
せることによってドレイン・ソース間の電圧の立ち上り
時立ち下り時の遅延時間を短縮させようとすると、MO
SFET45.18の08時にはMOSFET18.1
7の出力容量を充電する電流のピーク値が増大するため
にMSOFET15.18のドレイン・ソース間を流れ
るスパイク状の電流のピーク値が増大し、MOSFET
15.18にかかるストレスが大きくなり、ノイズも増
大する。The conventional DC-DC converter drive circuit described above reduces the rise and fall times of the voltage between the drain and source by shortening the delay time at the rise and fall of the switching signal applied between the gate and drain of the MOSFET. When trying to shorten the delay time of MO
SFET45.18 at 08:00 MOSFET18.1
Because the peak value of the current that charges the output capacitance of MSOFET 15.18 increases, the peak value of the spike-like current flowing between the drain and source of MSOFET15.18 increases, and the
The stress placed on 15.18 increases, and the noise also increases.
また同様にMOSFET16.17の08時にはOFF
状態のMOSFET15.18の出力容量を充電する電
流のピーク値が増大するために、MOSFET16.1
7のドレイン・ソース電流の立ち上り時のスパイク状の
電流のピーク値が増大しMOSFET16.17に加わ
るストレスが大きくなり、ノイズも増大するという欠点
がある。Similarly, MOSFET16.17 turns off at 08:00.
Because the peak value of the current charging the output capacitance of MOSFET 15.18 in the state increases, MOSFET 16.1
The disadvantage is that the peak value of the spike-like current at the rise of the drain-source current of No. 7 increases, the stress applied to the MOSFETs 16 and 17 increases, and the noise also increases.
本発明のDC−DCコンバータのドライブ回路は、ドラ
イブトランスの2次巻線の巻き始めとスイッチング用M
OSFETのゲート暑ソース端子間に並列に接続された
抵抗のスイッチング用MOSFETのゲート端子に接続
された端子との間に直列に接続されたインダクタンスと
、ドライブトランスの巻き始めとカソード端子が接続さ
れスイッチング用MOSFETのゲート・ソース端子間
に接続された抵抗のスイッチング用MOSFETのゲー
ト端子に接続された端子にアノード端子が接続されたダ
イオードを宵している。The drive circuit of the DC-DC converter of the present invention includes the winding start of the secondary winding of the drive transformer and the switching M
For switching, the resistor is connected in parallel between the gate and source terminals of the OSFET, and the inductance is connected in series with the terminal connected to the gate terminal of the MOSFET, and the winding start and cathode terminal of the drive transformer are connected for switching. A diode whose anode terminal is connected to a terminal connected to the gate terminal of the switching MOSFET and a resistor connected between the gate and source terminals of the switching MOSFET is used.
次に本発明について図面を参照して説明する。 Next, the present invention will be explained with reference to the drawings.
第1図は本発明の一実施例を示す回路図である。FIG. 1 is a circuit diagram showing an embodiment of the present invention.
インダクタンス7はドライブトランスθの2次巻線19
の巻き始めと抵抗10のMOSFETIのゲート端子に
接続された一端との間に直列に接続される。Inductance 7 is the secondary winding 19 of drive transformer θ
is connected in series between the winding start of the resistor 10 and one end of the resistor 10 connected to the gate terminal of the MOSFET I.
ダイオード5はインダクタンス7に並列になるようにカ
ソード端子がドライブトランス9の2次巻線19の巻き
初めにアノード端子が抵抗10のMOSFETIのゲー
ト端子に接続された一端に接続される。The diode 5 has a cathode terminal connected to one end of the secondary winding 19 of the drive transformer 9 at the beginning of winding and an anode terminal connected to the gate terminal of the MOSFET I of the resistor 10 so as to be parallel to the inductance 7 .
インダクタンス8はドライブトランス9の2次巻線20
の巻き始めと抵抗10のMOSFET4のゲート端子に
接続された一端との間に直列に接続される。ダイオード
6はインダクタンス8に並列になるように、カソード端
子がドライブトランス9の2次巻線20の巻き初めに、
アノード端子が抵抗11のMOSFET4のゲート端子
に接続された一端に接続される。The inductance 8 is the secondary winding 20 of the drive transformer 9
is connected in series between the winding start of the resistor 10 and one end of the resistor 10 connected to the gate terminal of the MOSFET 4. The cathode terminal of the diode 6 is connected to the beginning of the winding of the secondary winding 20 of the drive transformer 9 so that it is parallel to the inductance 8.
The anode terminal is connected to one end of the resistor 11, which is connected to the gate terminal of the MOSFET 4.
また、ドライブトランス9の2次巻線19の巻き終りは
抵抗工0のMOSFETIのソース端子に接続された一
端に2次巻線20の巻き終りは抵抗11のMOSFET
4のソース端子に接続された一端にそれぞれ接続される
。The end of the secondary winding 19 of the drive transformer 9 is connected to the source terminal of the MOSFET with resistance 0, and the end of the secondary winding 20 is connected to the source terminal of the MOSFET with resistance 11.
Each of the terminals is connected to one end connected to the source terminal of No. 4.
MOSFETI、4が同時にONするときに、MOSF
ETI、2のゲート・ソース電圧の立ち上り遅延時間は
インダクタンス7.8によって長くなるために、MOS
FET2.3の出力容量が充電されるためにMOSFE
T1.4のドレインΦソース電流の立ち上り時のスパイ
ク状電流のピーク値を低減することができる。When MOSFETI and 4 are turned on at the same time, MOSFET
Since the rise delay time of the gate-source voltage of ETI,2 becomes longer due to the inductance 7.8, the MOS
Since the output capacitance of FET2.3 is charged, the MOSFE
The peak value of the spike-like current at the rise of the drain Φ source current of T1.4 can be reduced.
MOSFET1.4が同時にOFFするときに、インダ
クタンス7.8はダイオード5.6のv2によってクラ
ンプされるのでMOSFET1.4のゲートOソース電
圧の立ち下り時の遅延時間は長くならないので、スイッ
チングロスは増加しない。When MOSFET 1.4 is turned off at the same time, inductance 7.8 is clamped by v2 of diode 5.6, so the delay time when the gate O source voltage of MOSFET 1.4 falls does not become long, so switching loss increases. do not.
MOSFET3.2に接続されるドライブ回路において
も上述のようにダイオードとインダクタンスを有するこ
とによって、MOSFET3.2の08時にMOSFE
T3,2のドレインΦソース電流の立ち上り時のスパイ
ク状電流のピーク値を低減する。The drive circuit connected to MOSFET 3.2 also has a diode and an inductance as described above, so that the MOSFET 3.2 is
The peak value of the spike-like current at the rise of the drain Φ source current of T3,2 is reduced.
MOSFET2.3のOFF時にはMOS F ET2
,3のゲー)−ソース電圧の立ち下り遅延時間は長くな
らないために、MOSFET2.3のドレイン・ソース
電圧の立ち上り遅延時間が長くならないので、スイッチ
ングロスは増加しない。When MOSFET2.3 is OFF, MOSFET2
, 3) - Since the fall delay time of the source voltage does not become long, the rise delay time of the drain-source voltage of MOSFET 2.3 does not become long, so the switching loss does not increase.
以上説明したように本発明は、スイッチング用のMOS
FETのゲート・ソース電圧の立ち上り時の遅延時間の
み長くすることによって、スイッチング用のMOSFE
Tのストレスの低減と、ノイズの低減を実施でき、さら
にスイッチング用MOSFETのOFF時のスイッチン
グロスの増加を防ぐことができる効果がある。As explained above, the present invention provides switching MOS
By increasing only the delay time when the FET gate-source voltage rises, switching MOSFE
This has the effect of reducing stress on T and reducing noise, and further preventing an increase in switching loss when the switching MOSFET is turned off.
イツチング用のMOSFET15.6・・・ダイオード
、7,8・・・インダクタンス、9.14・・・ドライ
ブトランス、10.11・・・抵抗。MOSFET for switching15.6...Diode, 7,8...Inductance, 9.14...Drive transformer, 10.11...Resistance.
Claims (1)
用MOSFETのゲート・ソース端子間に並列に接続さ
れた抵抗の該スイッチング用MOSFETのゲート端子
に接続された一端との間に直列に接続されたインダクタ
ンスを有し、ドライブトランスの2次巻線の巻き始めに
カソード端子で接続され該スイッチング用MOSFET
のゲート・ソース端子間に並列に接続された抵抗の該ス
イッチング用MOSFETのゲート端子に接続された一
端にアノード端子が接続されたダイオードを有し、前記
抵抗の他端は該スイッチング用MOSFETのソース端
子と前記ドライブトランスの2次巻線の巻き終りと接続
されたことを特徴とするDC−DCコンバータのドライ
ブ回路。An inductance connected in series between the winding start of the secondary winding of the drive transformer and one end connected to the gate terminal of the switching MOSFET of a resistor connected in parallel between the gate and source terminals of the switching MOSFET. The switching MOSFET is connected at the cathode terminal to the beginning of the secondary winding of the drive transformer.
has a diode whose anode terminal is connected to one end connected to the gate terminal of the switching MOSFET of a resistor connected in parallel between the gate and source terminals of the resistor, and the other end of the resistor is connected to the source terminal of the switching MOSFET. A drive circuit for a DC-DC converter, characterized in that a terminal is connected to an end of a secondary winding of the drive transformer.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP16013790A JPH0449851A (en) | 1990-06-19 | 1990-06-19 | Driving circuit for dc/dc converter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP16013790A JPH0449851A (en) | 1990-06-19 | 1990-06-19 | Driving circuit for dc/dc converter |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH0449851A true JPH0449851A (en) | 1992-02-19 |
Family
ID=15708676
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP16013790A Pending JPH0449851A (en) | 1990-06-19 | 1990-06-19 | Driving circuit for dc/dc converter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH0449851A (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2010158112A (en) * | 2008-12-26 | 2010-07-15 | Tdk-Lambda Corp | Gate driving circuit |
-
1990
- 1990-06-19 JP JP16013790A patent/JPH0449851A/en active Pending
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2010158112A (en) * | 2008-12-26 | 2010-07-15 | Tdk-Lambda Corp | Gate driving circuit |
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