JPH0433527A - Harmonic compensation device - Google Patents
Harmonic compensation deviceInfo
- Publication number
- JPH0433527A JPH0433527A JP2140746A JP14074690A JPH0433527A JP H0433527 A JPH0433527 A JP H0433527A JP 2140746 A JP2140746 A JP 2140746A JP 14074690 A JP14074690 A JP 14074690A JP H0433527 A JPH0433527 A JP H0433527A
- Authority
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- Prior art keywords
- power
- order
- command signal
- current command
- current
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Links
- 230000004069 differentiation Effects 0.000 claims description 8
- 239000003990 capacitor Substances 0.000 claims description 7
- 239000000470 constituent Substances 0.000 abstract 5
- 238000004364 calculation method Methods 0.000 description 10
- 238000010586 diagram Methods 0.000 description 4
- 238000006243 chemical reaction Methods 0.000 description 3
- 238000000034 method Methods 0.000 description 3
- 239000011159 matrix material Substances 0.000 description 2
- 230000009466 transformation Effects 0.000 description 2
- 101100509103 Schizosaccharomyces pombe (strain 972 / ATCC 24843) ish1 gene Proteins 0.000 description 1
- 208000032140 Sleepiness Diseases 0.000 description 1
- 206010041349 Somnolence Diseases 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000006872 improvement Effects 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 230000004044 response Effects 0.000 description 1
- 230000037321 sleepiness Effects 0.000 description 1
- 230000000087 stabilizing effect Effects 0.000 description 1
- 230000007704 transition Effects 0.000 description 1
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
- Y02E40/40—Arrangements for reducing harmonics
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Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は電源系統および負荷設備間の系統ラインに設け
られた高調波補償装荷の改良に関するものである。DETAILED DESCRIPTION OF THE INVENTION [Field of Industrial Application] The present invention relates to an improvement in harmonic compensation loading provided in a system line between a power supply system and load equipment.
３相ＰＷＭコンバータと、前記３相ｐ Ｗ Ｍコンバー
タの交流側に電源に直列に接続される交流リアクトルと
、前記３相ＰＷＭコンバータの直流側に端子間に接続さ
れる直流コンデンサとで構成されるアクティブフィルタ
は、アクティブフィルタ自身が発生するリップル電流を
除去するために高次フィルタが併設され、全体として高
調波補償装Ｐ３
置が構成されるのが一般的である。Consisting of a 3-phase PWM converter, an AC reactor connected in series to a power supply on the AC side of the 3-phase PWM converter, and a DC capacitor connected between terminals on the DC side of the 3-phase PWM converter. The active filter is generally provided with a high-order filter in order to remove the ripple current generated by the active filter itself, and the harmonic compensator P3 is configured as a whole.
このような高調波補償装置においては電源系統のインピ
ーダンスと高次フィルタの間で共振が発生し補償特性が
悪化することがある。このような共振をアクティブフィ
ルタによって抑制する制御方式として４源側高調波電流
をフィードバックする方法が、昭和６２年電気学会全国
大会講演論文集の５６６として「アクティブフィルタの
制御方式に関する検討−」に報告されている。In such a harmonic compensator, resonance may occur between the impedance of the power supply system and the high-order filter, and the compensation characteristics may deteriorate. A method of feeding back harmonic currents on the four-source side as a control method to suppress such resonance using an active filter was reported in ``Study on Control Methods of Active Filters'' as 566 of the Proceedings of the National Conference of the Institute of Electrical Engineers of Japan in 1988. has been done.
以下、このような従来の高調波補償装置について図面を
参照しながら説明する。第３図は従来の高調波補償装置
を具えた３相交流電源系統の主回路構成図であり、第４
図は高調波補償時の系統のブロック図である。Hereinafter, such a conventional harmonic compensation device will be explained with reference to the drawings. Figure 3 is a main circuit configuration diagram of a three-phase AC power supply system equipped with a conventional harmonic compensation device.
The figure is a block diagram of the system during harmonic compensation.
第３図において、３は系統インピーダンスを示し、３相
交流系統電源１は系統インピーダンス３を経てサイリス
クレオナード装置等の負荷２に負荷側交流リアクトル８
を介して電力を供給している。この系統ラインに３相Ｐ
Ｗ Ｍコンノマータ５゜交流リアクトル４．直流コン
デンサ６から成るアクティブフィルタ及び高次フィルタ
７で構成される高調波補償装置が接続されている。In Fig. 3, 3 indicates the system impedance, and the three-phase AC system power supply 1 passes through the system impedance 3 and is connected to the load 2, such as a Thyris-Screenard device, to the load-side AC reactor 8.
Power is supplied through the 3-phase P in this system line
WM Connomata 5゜AC reactor 4. A harmonic compensation device consisting of an active filter consisting of a DC capacitor 6 and a high-order filter 7 is connected.
第４図において、３３は電源電流の高調渡分ＩＳＨのフ
ィードバック制御関数０１３１はアクティブフィルタの
伝達関数ＧＡＦ、３２は電源側高調波流入インピーダン
スＺであり、電源側高調波流入インピーダンス２は系統
の高調波インピーダンスＺｓおよび高次フィルタ７のイ
ンピーダンスｚｆより次の式％式％
このような伝達関数で構成される系統において、負荷電
流高調渡分ＩＬｔ（と、電源電流高調渡分ＩＳＨにフィ
ードバック制御関数Ｇを掛けたＩＯを加え合わせて、そ
れらをアクティブフィルタの伝達関数ＧＡＦの入力とす
る。In Fig. 4, 33 is the feedback control function 01 of the harmonic component ISH of the power supply current, 31 is the transfer function GAF of the active filter, 32 is the harmonic inflow impedance Z on the power supply side, and harmonic inflow impedance 2 on the power supply side is the harmonic inflow impedance 2 of the system. From the wave impedance Zs and the impedance zf of the high-order filter 7, the following formula % Formula % In a system configured with such a transfer function, the load current harmonic portion ILt (and the power supply current harmonic portion ISH are given by the feedback control function G The multiplied IOs are added together and used as input to the active filter's transfer function GAF.
その出力ＩＦと負荷電流高調渡分ＩＬＨの差を電源側高
調波流入インピーダンスＺの入力とすると、その出力が
電源電流高調渡分ＩＳＨとなる１、ここで、フィードバ
ック制御関数Ｇとして比例微分回路を採用すれば、電源
系統のインビーダンスと高次フィルタ７の間で発生する
共振を抑制し、補償性能を向上させることができる。比
例微分回路を採用した時、フィードバック関数Ｇは比例
微分回路の伝達関数となり次式で表される。If the difference between the output IF and the load current harmonic distribution ILH is input to the harmonic inflow impedance Z on the power supply side, the output becomes the power supply current harmonic distribution ISH1.Here, a proportional differential circuit is used as the feedback control function G. If adopted, resonance generated between the impedance of the power supply system and the high-order filter 7 can be suppressed, and compensation performance can be improved. When a proportional differentiation circuit is employed, the feedback function G becomes a transfer function of the proportional differentiation circuit and is expressed by the following equation.
Ｑ＝ ＫＴＳ ・・・・・・・・・・・・・・・・
・・・・・・・・・・・・・・（２）１＋ＴＳ
ここに
に：比例微分回路のゲイン
Ｔ；比例微分回路の時定数
を示す。Q=KTS・・・・・・・・・・・・・・・
・・・・・・・・・・・・・・・(2) 1+TS Here: Gain T of the proportional differentiation circuit; shows the time constant of the proportional differentiation circuit.
第２図に示した負荷２の負荷側交流リアクトル８の値が
小さい時、負荷電流ＩＬＵ ＋ ■ｔ、ｖ ｌ ＩＬＷ
の重なり角が小さくなり、有限な値を有する交流リアク
トル４のためにアクティブフィルタは負荷電流ＩＬＵ
ｒ ＩＬＶ ｒ ＩＬＶの転流時に補償指令に追従でき
なくなる。その結果、高次高調波の抑制は高次フィルタ
７で行なうとしても、低次高調波が多量に残るという不
具合があった。When the value of the load side AC reactor 8 of the load 2 shown in Fig. 2 is small, the load current ILU + ■t, v l ILW
Since the overlap angle of the AC reactor 4 is small and has a finite value, the active filter is configured to reduce the load current ILU
r ILV r It becomes impossible to follow the compensation command when ILV commutates. As a result, even if high-order harmonics are suppressed by the high-order filter 7, a large amount of low-order harmonics remain.
この抑制されない低次高調波は第４図においてＩＬＨ−
Ｉ ｉｉ’で示される電流の中で低次の電流であす、フ
ィードバック関数Ｇのゲインを上げても抑制できない電
流である。This unsuppressed lower harmonic is shown in FIG.
This is a low-order current among the currents indicated by Iii', and is a current that cannot be suppressed even if the gain of the feedback function G is increased.
本発明は前記の不具合を解消して、低次から高次に至る
高調波を抑制する高調波補償装置を提供するものである
・
〔課題を解決するための手段］
本発明にかかる高調波補償装置は電源系統および負荷設
備間の系統ラインに設けられる高調波補償装置であって
、３相ＰＷＭコンバータと、該３相ＰＷＭコンバータの
交流側各相に系統ラインに直列に接続された交流リアク
トルと、前記３相ＰＷＭコンバータの直流側端子間に接
続された直流コンデンサと、前記交流リアクトルの電源
側に併設された高次フィルタと、前記３相ＰＷＭコンバ
ータを制御する制御装置を備えたものにおいて、該制御
装置は負荷設備の瞬時実電力および虚電力を演算する手
段と、該瞬時実電力および虚電力からその低次交流分を
検出する手段と、該瞬時実電力および虚電力の低次交流
分より第１の電流指令信号を生成する手段と、電源電流
からその瞬時実Ｐ７
電力および虚電力を演算して第２の電流指令信号を生成
する手段と、該第２の電流指令信号を入力して比例微分
を施し第３の電流指令信号を生成する手段と、該第３の
電流指令信号と前記第１の電流指令信号を加算して電流
指令信号を生成する手段と、該電流指令信号と前記交流
リアクトルに流れる補償電流検出値とを比較して３相Ｐ
ＷＭコンバータの各相スイ１．チング信号を生成する手
段とを具えたことを特徴とするものである。The present invention solves the above-mentioned problems and provides a harmonic compensation device that suppresses harmonics from low order to high order. [Means for Solving the Problems] Harmonic compensation according to the present invention The device is a harmonic compensation device installed in a system line between a power supply system and load equipment, and includes a three-phase PWM converter, an AC reactor connected in series to the system line on each phase of the AC side of the three-phase PWM converter, and , comprising a DC capacitor connected between DC side terminals of the three-phase PWM converter, a high-order filter attached to the power supply side of the AC reactor, and a control device for controlling the three-phase PWM converter, The control device includes means for calculating instantaneous real power and imaginary power of the load equipment, means for detecting a low-order AC component from the instantaneous real power and imaginary power, and low-order AC component of the instantaneous real power and imaginary power. means for generating a first current command signal from a power supply current; means for generating a second current command signal by calculating instantaneous actual P7 power and imaginary power from a power supply current; means for generating a third current command signal by applying proportional differentiation to the current command signal; means for generating a current command signal by adding the third current command signal and the first current command signal; The three-phase P is compared with the detected value of the compensation current flowing through the AC reactor.
Each phase switch of WM converter 1. The present invention is characterized in that it includes means for generating a switching signal.
本発明にかかる高調波補償装置においては、負荷電流の
瞬時実′屯力および虚電力よりバンドパスを利用して、
低次の高調渡分を検出して第１の電流指令信号を得る事
により、第１の電流指令信号の波形が従来は鋸歯状であ
ったものがバンドパスにより正弦波状に緩やかなものと
なるので、有限の値を有する交流リアクトル４により有
限のスイ、チング周波数で十分な低次補償性能を得る事
ができる。In the harmonic compensator according to the present invention, a bandpass is used from the instantaneous real force and imaginary power of the load current to
By detecting the low-order harmonic component and obtaining the first current command signal, the waveform of the first current command signal, which was previously sawtooth, becomes gentle like a sine wave due to bandpass. Therefore, sufficient low-order compensation performance can be obtained with a finite switching and switching frequency by using the AC reactor 4 having a finite value.
高次の高調渡分は高次フィルタにより抑制することがで
きる。又、低次の高調渡分が残った場合には、電源電流
の瞬時実電力および虚電力より生成した第２の電流指令
信号およびその値を比例微分した第３の電流指令信号に
より電源インピーダンスと高次フィルタとの間で発生す
る共振を抑制することができる。High-order harmonic components can be suppressed by high-order filters. In addition, if a low-order harmonic component remains, the power supply impedance is determined by a second current command signal generated from the instantaneous real power and imaginary power of the power supply current, and a third current command signal obtained by proportionally differentiating the value. Resonance occurring with the high-order filter can be suppressed.
以下、一実施例につき図面を参照しつつ説明する。本発
明にかかる高調波補償装置を具えた３相交流電源系統の
主回路構成図は、従来の場合と同様に第３図に示した通
りであり、第１図は本考案にかかる高調波補償装置の一
実施例の制御装置のブロック図を示す。Hereinafter, one embodiment will be described with reference to the drawings. The main circuit configuration diagram of a three-phase AC power supply system equipped with the harmonic compensation device according to the present invention is shown in FIG. 3 as in the conventional case, and FIG. 1 shows the harmonic compensation system according to the present invention. FIG. 2 shows a block diagram of a control device of an embodiment of the device.
３相交流系統電源１は系統インピーダンス３および負荷
側交流リアクトル８を経てサイリスタレオナード装置等
の負荷２に電力を供給し、負荷２の各相には負荷電流Ｉ
ＬＵ ＊ ＩＬＶ ＋ ＩＬＶが流れ込んでいる。この
系統ラインに負荷２と並列に高次フィルタ７とアクティ
ブフィルタが接続されている。A three-phase AC system power supply 1 supplies power to a load 2 such as a thyristor Leonard device through a system impedance 3 and a load-side AC reactor 8, and each phase of the load 2 receives a load current I.
LU * ILV + ILV is flowing. A high-order filter 7 and an active filter are connected to this system line in parallel with the load 2.
アクティブフィルタは３相ＰＷＭコンバータ５と、その
交流側各相端子を系統ラインへ接続する交流リアクトル
４と、３相ＰＷＭコンバータの直流側端子間に接続され
た直流コンデンサ６とから成っている。The active filter consists of a three-phase PWM converter 5, an AC reactor 4 that connects each phase terminal on the AC side to the system line, and a DC capacitor 6 connected between the DC side terminals of the three-phase PWM converter.
３相ＰＷＭコンバータ５はオン、オフ可能なスイッチン
グ素子８１〜Ｓ６およびダイオードＤ１〜Ｄ６から構成
され、各スイッチング素子８１〜Ｓ６はそれぞれダイオ
ード■）１〜Ｄ６を並列接続された上、３相ブリッジ回
路として接続され、制御装置から供給されるスイッチン
グ信号Ｖ、によりスイッチング素子８１〜Ｓ６がオン、
オフされて高調波補償を行うものである。The three-phase PWM converter 5 is composed of switching elements 81 to S6 and diodes D1 to D6, which can be turned on and off, and each switching element 81 to S6 is connected in parallel with diodes 1 to D6, and a three-phase bridge circuit is formed. The switching elements 81 to S6 are turned on by the switching signal V supplied from the control device.
It is turned off to perform harmonic compensation.
なお、３相ＰＷＭコンバータ５の交流側に直列に挿入さ
れた交流リアクトル４は、３相ＰＷＭコンバータ５の電
流の立ち上がりを制限するためのものであり、直流側に
接続された直流コンデンサ６は、３相ＰＷＭコンバータ
５の直流側の電圧を安定化させるためのものであって、
通常は３相交流系統電源１の電圧と等しい３相ＰＷＭコ
ンバタ５の交流側電圧の２倍程度の電圧に充電されてい
る。Note that the AC reactor 4 inserted in series on the AC side of the three-phase PWM converter 5 is for limiting the rise of the current of the three-phase PWM converter 5, and the DC capacitor 6 connected to the DC side is It is for stabilizing the voltage on the DC side of the three-phase PWM converter 5,
Normally, it is charged to a voltage that is approximately twice the AC side voltage of the three-phase PWM converter 5, which is equal to the voltage of the three-phase AC system power supply 1.
今、第３図に示す主回路構成において、負荷２に流入す
る負荷電流を工ＬＵ ＋ ＩＬＶ ｒ ＩＬＷ、アクテ
ィブフィルタすなわち３相Ｐ ＩＮ Ｍコンバータ５に
流入する補償電流をＩＵ ＋ ＩＶ ｒ ＩＷ％高次フ
ィルタ７に流入するフィルタ電流をＩＦＵ ｒ ＩＦＶ
＋ ＩＦＷとすると、系統電源１に流れる電源電流■
ＳＵ ＋ Ｉ８Ｖ １■ＳＷは負荷電流と補償電流とフ
ィルタ電流とをベクトル的に加算したものとなる。従っ
て、補償電流とフィルタ電流のベクトル和ＩＵ＋ＩＦＵ
、 Ｉｖ＋Ｉｐｖ ＋ＩＷ＋ＩＦＷがそれぞれ負荷電
流ＩＬＵ ＋ 工ＬＶ ＋ ＩＬＶの高調渡分を打ち消
すものであれ（（よい。Now, in the main circuit configuration shown in Fig. 3, the load current flowing into the load 2 is expressed as LU + ILV r ILW, and the compensation current flowing into the active filter, that is, the three-phase PIN converter 5, as IU + IV r IW%. The filter current flowing into the next filter 7 is IFU r IFV
+ IFW, the power supply current flowing to grid power supply 1■
SU+I8V 1■SW is the vectorial sum of the load current, compensation current, and filter current. Therefore, the vector sum of compensation current and filter current IU + IFU
, Iv+Ipv +IW+IFW cancel the harmonic transition of the load current ILU + engineering LV + ILV, respectively ((good).
前記のような高調波補償を行うため、ここでは以下に説
明するような３相〜２相変換を行い、実電力および虚電
力なる概念を導入している。この概念については昭和５
８年７月発行の眠気学会論文誌１０３巻Ｂ分冊７号掲載
の論文５８．−８６０の「瞬時無効電力の一般化理論と
その応用」などとして発表されているが、以下、その演
算法について説明する。In order to perform harmonic compensation as described above, three-phase to two-phase conversion as described below is performed here, and the concepts of real power and imaginary power are introduced. This concept was introduced in Showa 5.
Paper 58 published in Journal of the Sleepiness Society, Vol. 103, Part B, No. 7, published in July 2013. -860, ``Generalized Theory of Instantaneous Reactive Power and Its Applications'', etc., and its calculation method will be explained below.
ｐＨ
この概念は、まず次の（３）〜（５）式を用いて３相の
負荷電流■ＬＴＪ ＋ ’ＬＶ ｒ ＩＬＷおよび系統
電圧ｅＵ、Ｐｙ。pH This concept is first calculated by using the following equations (3) to (5) to calculate the three-phase load current ■LTJ + 'LV r ILW and the system voltage eU, Py.
憎を２相の電流■い、■１．βおよび電圧ｆ！ｄ、ｅβ
に変換するものである。、
ここで［０〕は３相〜２相の変換行列である。A two-phase current ■1. β and voltage f! d, eβ
It is converted into . , where [0] is a three-phase to two-phase transformation matrix.
上記（３）〜（５）式より求めた２相の電圧および電流
を用いると、次の（６）式により実電力ｐおよび虚電力
ｑが求められる。Using the two-phase voltages and currents obtained from the above equations (3) to (5), the real power p and the imaginary power q can be obtained from the following equation (6).
これらの実電力ｐおよび虚電力ｑは、次の（７）。These real power p and imaginary power q are as follows (7).
（８）式によりそれぞれ直流分子）＋Ｃ１と低次交流外
ｐ１２．ｑ１．および高次交流分ｐＨｌ ｑ［（に分解
される。According to equation (8), the DC molecule)+C1 and the low-order AC external p12. q1. and the higher-order alternating current component pHl q [(decomposed into
ｐ ＝ ｐ ＋ Ｉ）Ｌ−１−Ｉ）Ｈ・・・・・・・・
・・・・・・・・・・・・・・・・（７）ｑ”’ ｑ＋
’ Ｑｔ、”ｔ−Ｑ＋□ ・・・・・・・・・・・
・・・・・・・・・・・・・（８）ここで、２相負荷電
流ＩＬα、ＩＬβの低次高調渡分は実電力の低次交流外
ｐｒ、および虚電力の低次交流外ｑＬに変換されるので
、バンドパスフィルタを通して分離することができる。p = p + I) L-1-I) H・・・・・・・・・
・・・・・・・・・・・・・・・・・・(7) q”' q+
' Qt, "t-Q+□ ・・・・・・・・・・・・
(8) Here, the low-order harmonic parts of the two-phase load currents ILα and ILβ are the low-order AC outside pr of the real power and the low-order AC outside of the imaginary power. Since it is converted into qL, it can be separated through a bandpass filter.
次に、以上に述べた原理に基づいて構成された第１図の
制御装置を説明する。Next, the control device shown in FIG. 1 constructed based on the principle described above will be explained.
電力演算回路１１は負荷電流ＩＬＵ ＋ ＩＬＶ ＊
ＩＬＷに比例する負荷電流信号ｉｔ、ｕ ｒ ’ｔ、ｖ
＋ ｉｔ、ｗと、系統電圧ｅｕ ＋ ｅｖ ＊ ｅｗ
とを受けて、（３）〜（６）式に従って瞬時実電力ｐｔ
および瞬時虚電力ｑ１を演算し、こレラをバンドパスフ
ィルタ１２へ送ル・。The power calculation circuit 11 calculates the load current ILU + ILV *
Load current signal it,ur't,v proportional to ILW
+ it, w, and grid voltage eu + ev * ew
According to equations (3) to (6), the instantaneous actual power pt
and instantaneous imaginary power q1, and sends this to the bandpass filter 12.
バンドパスフィルタ１２はこれらから直流分および高次
交流分を除去して、瞬時実電力の低次交流外ｐ１Ｌおよ
び瞬時虚電力の低次交流外ｑＩＬを符号反転回路１３へ
送出する。符号反転回路１３はこれら＊
の符号を反転し、実電力指令信号ｐ１ および虚電力
指令信号ｑごとして電流指令値演算回路】４へ出力する
。The bandpass filter 12 removes the DC component and the high-order AC component from these, and sends the instantaneous real power low-order AC external p1L and the instantaneous imaginary power low-order AC external qIL to the sign inversion circuit 13. The sign inverting circuit 13 inverts the signs of these signals * and outputs them as the real power command signal p1 and the imaginary power command signal q to the current command value calculation circuit 4.
＊−一 〜
ｐ、 −−ｐｌ ・・・・・・・・・・・・・
・・・・・・・・−へ・・・・・・（９）＊−〜
ｑｌ −−−−−Ｑ １ ・・・・・・・・−
・・・・・・・・・・・・・・・・・・・・・（１０）
これらは電流指令値演算回路１４において生成する電流
指令イ言号の原形となるものである。すなオ）ち、（９
）式により得られる実電力指令信号ｐ１ を基に低次高
調波有効電力が制御され、（１０）式により得られる虚
電力指令信号ｑ、＊を基に低次高調波無効電力が制御さ
れる３、
電流指令値演算回路１４は、実電力指令信号ｐ１＋虚電
力指令信号ｑ、および系統電圧ｅＩｊ、 ｅｙ 、 ｅ
ｗを受けて、前記（３）式および次の（１１）〜（１３
）式に従って、２相電流指令値号１ｃｔ１．＋β１を得
、２相〜３相変換を行って電流指令信号ＩＵ□ＩＩＶＩ
Ｉｉｗ＋を生成して加算回路１５へ出力する。*-1 ~ p, --pl ・・・・・・・・・・・・・・・
・・・・・・・・・−・・・・・・(9)*−～ ql −−−−−Q 1 ・・・・・・・・・−
・・・・・・・・・・・・・・・・・・・・・(10)
These are the original forms of the current command words generated in the current command value calculation circuit 14. Sunao) Chi, (9
) The low-order harmonic active power is controlled based on the actual power command signal p1 obtained by the equation (10), and the low-order harmonic reactive power is controlled based on the imaginary power command signal q, * obtained from the equation (10). 3. The current command value calculation circuit 14 calculates the real power command signal p1 + imaginary power command signal q, and the system voltages eIj, ey, e
In response to w, the above equation (3) and the following (11) to (13
), the two-phase current command value number 1ct1. +β1 is obtained, the 2-phase to 3-phase conversion is performed, and the current command signal IU□IIIVI is obtained.
Iiw+ is generated and output to the adder circuit 15.
Ｐ］、４ なお、〔Ｃ〕 は〔Ｃ〕の逆変換行列である。P], 4 Note that [C] is an inverse transformation matrix of [C].
次に、電力演算回路２１は電源電流■ＳＵ ＋ ＩＳＶ
＊Ｉｓｗに比例する電源電流イ１ｉ号１ｓＵ−ｉｓｖ
＋ ｉｓｗと、系統電圧ｅＵ、 ｅｙ 、 ｅｗとを
受けて、（３）〜（６）式に従って瞬時実電力ｐ２およ
び瞬時虚電力ｑ２を演算し、これらをバイパスフィルタ
２２へ送る。Next, the power calculation circuit 21 calculates the power supply current ■SU + ISV
*Power supply current I1i 1sU-isv proportional to Isw
+isw and the system voltages eU, ey, and ew, calculate instantaneous real power p2 and instantaneous imaginary power q2 according to equations (3) to (6), and send these to the bypass filter 22.
バイパスフィルタ２２はこれらから直流分を除去して、
瞬時実電力の交流外ｐ２および瞬時虚電力の交流外ｑ２
を符号反転回路２３へ送出する。イ、ｆ号反転回路２３
はこれらの符号を反転し、実電力指令信号＊
＊ｐ２ およ
び虚電力指令信号ｑ２ として電流指令値演算回路２
４へ出力する。The bypass filter 22 removes the DC component from these,
Instantaneous real power outside AC p2 and instantaneous imaginary power outside AC q2
is sent to the sign inversion circuit 23. A, f inversion circuit 23
inverts these signs and outputs the actual power command signal*
*p2 and the current command value calculation circuit 2 as the imaginary power command signal q2
Output to 4.
Ｐ １５
＊−〜 ・・・・・・・・・・・・・・・・・・・・
・・・・・・・・・・・・（１４）ｐ２ −−−ｐ２
１−〜 ・・・・・・・・・・・・・・・・・・・・・
・・・・・・・・・・・・（１５）ｑ２ − Ｑ
２
電流指令値演算回路２４は、実電力指令信号ｐ２ ｒ＊
虚電力指令信号ｑ２ および系統電圧ｅＵ、 ｅｙ
、 ｅｗを受けて、前記（３） 、 （１３）式および
次の（１６）〜（１７）式に従って２相電流指令信号１
．１２＊、ｌβ２＊を得、２相〜３相変換を行って電流
指令信号ｉ、Ｊ２．ｉｖ□。P 15 *-～ ・・・・・・・・・・・・・・・・・・・・・
・・・・・・・・・・・・(14) p2 −−−p2 1−〜 ・・・・・・・・・・・・・・・・・・
・・・・・・・・・・・・(15)q2 − Q
2 The current command value calculation circuit 24 calculates the real power command signal p2 r*, the imaginary power command signal q2, and the system voltage eU, ey
, ew, the two-phase current command signal 1 is generated according to the above equations (3) and (13) and the following equations (16) and (17).
．． 12*, lβ2* are obtained, and 2-phase to 3-phase conversion is performed to obtain current command signals i, J2. iv□.
ｉｗｚを生成して比例微分回路２５へ出力する。iwz is generated and output to the proportional differentiation circuit 25.
比例微分回路２５は電流指令信号ｉＵ２ ＋ ｌｙ□。The proportional differentiation circuit 25 receives the current command signal iU2 + ly□.
ｉｗｚを得て、（２）式の伝達関数に基づいて第３の電
流指令信号ｉｕｚ’ １ｉｖｚ ＊ ｉｗ２’を演算し
加算回路１５へ出力する。iwz is obtained, a third current command signal iuz' 1ivz * iw2' is calculated based on the transfer function of equation (2), and is output to the addition circuit 15.
加算回路１５は電流指令信号’Ｕｌ ｌ ｉｖ＋ 、ｉ
ｗ□と電流指令信号ｉｕｚ ＋ ｉｖ２’ ＋ ｉｗｚ
’とを各相それぞれ、＊、ン七、＊
加算して電流指令信号’ＩＪ Ｉ ｔｖ ＋ ｔｗ
を生成し、電流制御回路１６へ送出する。The adder circuit 15 receives the current command signal 'Ul iv+ , i
w□ and current command signal iuz + iv2' + iwz
' and for each phase, *, n7, * are added to obtain the current command signal 'IJ I tv + tw
is generated and sent to the current control circuit 16.
電流制御回路１６は電流指令信号ｉＵ＊＋ ！ｙ＊ｉｗ
＊と補償電流ＩＵ ＋ ＩＶ ＋ ＩＷに比例する補償
検出電流信号ｉＵ ＋ ＩＶ ＋ ｊｗとを比較し、例
えば、 ＊ 〜 、
＊ＩＩＪ＜０ で且つ １１Ｊ≦＋ＩＵなるとき、
３相ＰＷＭコンバータ５のスイッチング素子Ｓ４をオン
し、
ネ 、
ＩＵ さ０ で且つ １Ｕ）ｉ・Ｕ＊
なるときスイッチング素子Ｓ４をオフし、またＩＵ 〈
０ で且つ ＩＵ≦ｉＵ＊
、 ＊
なるとき、スイッチング素子Ｓｌをオフするようなスイ
ッチング信号ＶＧを生成するものであり、このスイッチ
ング信号ｖＧによってスイッチング素子Ｓ１〜Ｓ６がオ
ン、オフ制御され、高調波補償装置の各相の電流瞬時値
が制御される。The current control circuit 16 receives a current command signal iU*+! y＊iw
* and a compensation detection current signal iU + IV + jw proportional to the compensation current IU + IV + IW, for example, * ~ ,
*When IIJ<0 and 11J≦+IU,
The switching element S4 of the three-phase PWM converter 5 is turned on, and when IU is 0 and 1U)i・U*, the switching element S4 is turned off, and when IU
0 and IU≦iU*, *, a switching signal VG is generated that turns off the switching element Sl, and this switching signal vG turns on and off the switching elements S1 to S6, and performs harmonic compensation. The instantaneous current values of each phase of the device are controlled.
このようにして、電流指令信号”Ｕｌ ｌ ｉＶｌ ｌ
ｉｗ＋により低次の高調波成分が補償され、高次フィル
タにより高次の高副波成分が補償される。又、ｉ７
電源インピーダンスと高次フィルタによる共振は電流指
令信号ｉｔ＋ｚ’ 、ｉｖ□＋ ｉｗｚ’により抑制さ
れる。In this way, the current command signal "Ul l iVl l
iw+ compensates for low-order harmonic components, and the high-order filter compensates for high-order high subwave components. Further, resonance due to the i7 power supply impedance and the high-order filter is suppressed by the current command signals it+z' and iv□+iwz'.
以上、一実施例により詳細に説明したように、本発明に
かかる高調波補償装置は、負荷に接続される負荷側交流
リアクトルが小さい場合でも、低次の高調波をバンドパ
スを使用して検出する事により良好に補償する事ができ
、高次の高調波は高次フィルタにより補償する事ができ
る。As described above in detail with one embodiment, the harmonic compensation device according to the present invention detects low-order harmonics using a bandpass even when the load-side AC reactor connected to the load is small. Good compensation can be achieved by using a high-order filter, and high-order harmonics can be compensated by a high-order filter.
又、補償しきれなかった低次の高調波の、電源インピー
ダンスと高次フィルタによる共４辰による増大も電源電
流を検出する事によって抑制できる。Furthermore, an increase in low-order harmonics that could not be compensated for due to both the power supply impedance and the high-order filter can be suppressed by detecting the power supply current.
第１図は本考案にかかる高調波補償装置の一実系統イン
ピーダンス、４・・・・・・交流リアクトル、５・・・
・・・３相ＰＷＭコンバータ、６・・・・・・直流コン
デンサ、７・・・・・・高次フィルタ、８・・・・・・
負荷側交流リアクトル、１１ 、２１・・・・・・電力
演算回路、１２・・・・・・バンドパスフィルタ、２２
・・・・・・バイパスフィルタ、１３゜２３・・・・・
・符号反転回路、１４ 、２４・・・・・・′電力指令
演算回路、１５・・・・・・加算回路、１６・・・・・
・電流制御回路。Figure 1 shows the actual system impedance of the harmonic compensator according to the present invention, 4... AC reactor, 5...
...Three-phase PWM converter, 6...DC capacitor, 7...High-order filter, 8...
Load side AC reactor, 11, 21...Power calculation circuit, 12...Band pass filter, 22
...Bypass filter, 13゜23...
・Sign inversion circuit, 14, 24...'Power command calculation circuit, 15...Addition circuit, 16...
・Current control circuit.
Claims (1)
る高調波補償装置であって、３相ＰＷＭコンバータと、
該３相ＰＷＭコンバータの交流側各相に系統ラインに直
列に接続された交流リアクトルと、前記３相ＰＷＭコン
バータの直流側端子間に接続された直流コンデンサと、
前記交流リアクトルの電源側に併設された高次フィルタ
と、前記３相ＰＷＭコンバータを制御する制御装置を備
えたものにおいて、該制御装置は負荷設備の瞬時実電力
および虚電力を演算する手段と、該瞬時実電力および虚
電力からその低次交流分を検出する手段と、該瞬時実電
力および虚電力の低次交流分より第１の電流指令信号を
生成する手段と、電源電流からその瞬時実電力および虚
電力を演算して第２の電流指令信号を生成する手段と、
該第２の電流指令信号を入力して比例微分を施し第３の
電流指令信号を生成する手段と、該第３の電流指令信号
と前記第１の電流指令信号を加算して電流指令信号を生
成する手段と、該電流指令信号と前記交流リアクトルに
流れる補償電流検出値とを比較して３相ＰＷＭコンバー
タの各相スイッチング信号を生成する手段を具えたこと
を特徴とする高調波補償装置。1 A harmonic compensation device installed in a system line between a power supply system and load equipment, comprising a three-phase PWM converter,
an AC reactor connected in series to a system line for each AC side phase of the three-phase PWM converter; and a DC capacitor connected between DC side terminals of the three-phase PWM converter;
A high-order filter attached to the power supply side of the AC reactor and a control device for controlling the three-phase PWM converter, the control device comprising means for calculating instantaneous real power and imaginary power of the load equipment; means for detecting a low-order AC component from the instantaneous real power and imaginary power; means for generating a first current command signal from the low-order AC component of the instantaneous real power and imaginary power; means for calculating electric power and imaginary power to generate a second current command signal;
means for inputting the second current command signal and performing proportional differentiation to generate a third current command signal; and means for adding the third current command signal and the first current command signal to generate a current command signal. 1. A harmonic compensation device comprising: means for generating, and means for comparing the current command signal with a detected compensation current flowing through the AC reactor to generate switching signals for each phase of a three-phase PWM converter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2140746A JP2859930B2 (en) | 1990-05-30 | 1990-05-30 | Harmonic compensator |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2140746A JP2859930B2 (en) | 1990-05-30 | 1990-05-30 | Harmonic compensator |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH0433527A true JPH0433527A (en) | 1992-02-04 |
| JP2859930B2 JP2859930B2 (en) | 1999-02-24 |
Family
ID=15275767
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2140746A Expired - Fee Related JP2859930B2 (en) | 1990-05-30 | 1990-05-30 | Harmonic compensator |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2859930B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005029690A1 (en) * | 2003-09-19 | 2005-03-31 | Kabushiki Kaisha Yaskawa Denki | Pwm cyclo converter |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0196741U (en) * | 1987-12-16 | 1989-06-27 | ||
| JPH0253234U (en) * | 1988-09-30 | 1990-04-17 | ||
| JPH02131330A (en) * | 1988-11-09 | 1990-05-21 | Toshiba Corp | Control system for higher harmonic compensator |
-
1990
- 1990-05-30 JP JP2140746A patent/JP2859930B2/en not_active Expired - Fee Related
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0196741U (en) * | 1987-12-16 | 1989-06-27 | ||
| JPH0253234U (en) * | 1988-09-30 | 1990-04-17 | ||
| JPH02131330A (en) * | 1988-11-09 | 1990-05-21 | Toshiba Corp | Control system for higher harmonic compensator |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005029690A1 (en) * | 2003-09-19 | 2005-03-31 | Kabushiki Kaisha Yaskawa Denki | Pwm cyclo converter |
| GB2421125A (en) * | 2003-09-19 | 2006-06-14 | Yaskawa Denki Seisakusho Kk | Pwm cyclo converter |
| GB2421125B (en) * | 2003-09-19 | 2006-12-20 | Yaskawa Denki Seisakusho Kk | Pwm cycloconverter |
| US7495937B2 (en) | 2003-09-19 | 2009-02-24 | Kabushiki Kaisha Yaskawa Denki | PWM cycloconverter |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2859930B2 (en) | 1999-02-24 |
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