JPH04304004A - Band pass filter - Google Patents
Band pass filterInfo
- Publication number
- JPH04304004A JPH04304004A JP9277891A JP9277891A JPH04304004A JP H04304004 A JPH04304004 A JP H04304004A JP 9277891 A JP9277891 A JP 9277891A JP 9277891 A JP9277891 A JP 9277891A JP H04304004 A JPH04304004 A JP H04304004A
- Authority
- JP
- Japan
- Prior art keywords
- coupling
- coaxial
- resonant
- sub
- resonator
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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Links
- 238000010168 coupling process Methods 0.000 claims description 116
- 238000005859 coupling reaction Methods 0.000 claims description 116
- 230000008878 coupling Effects 0.000 claims description 82
- 238000005192 partition Methods 0.000 claims description 9
- 239000002184 metal Substances 0.000 claims description 3
- 238000003780 insertion Methods 0.000 abstract description 7
- 230000037431 insertion Effects 0.000 abstract description 7
- 230000005684 electric field Effects 0.000 description 16
- 238000010586 diagram Methods 0.000 description 10
- 230000005540 biological transmission Effects 0.000 description 7
- 238000009826 distribution Methods 0.000 description 3
- 230000003321 amplification Effects 0.000 description 1
- 230000015572 biosynthetic process Effects 0.000 description 1
- 239000004020 conductor Substances 0.000 description 1
- 230000001808 coupling effect Effects 0.000 description 1
- 230000003247 decreasing effect Effects 0.000 description 1
- 239000003989 dielectric material Substances 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000010295 mobile communication Methods 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
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- Control Of Motors That Do Not Use Commutators (AREA)
Abstract
Description
【0001】0001
【産業上の利用分野】本発明は、自動車電話等の移動通
信方式における基地局の送信アンテナと受信アンテナの
設置個所が比較的近接しているか、送受共用アンテナを
用いる場合に、基地局装置の受信増幅系を構成する帯域
通過ろ波器に要求される特性、すなわち、受信周波数の
通過帯域幅が比較的広く、送信周波数帯域の減衰量が極
めて大きいと共に、通過帯域における挿入損失の少ない
帯域通過ろ波器に関するものである。[Industrial Application Field] The present invention is applicable to mobile communication systems such as car telephones, in which the transmitting antenna and receiving antenna of a base station are relatively close to each other, or when a shared transmitting and receiving antenna is used. The characteristics required of the bandpass filter that constitutes the reception amplification system are that the passband width of the reception frequency is relatively wide, the amount of attenuation in the transmission frequency band is extremely large, and the bandpass has low insertion loss in the passband. It concerns a filter.
【0002】0002
【従来の技術】上記のような特性上の要求に応える帯域
通過ろ波器として、従来は、複数個のTE01テ゛ルタ
モ−ド誘電体共振器を縱続接続して構成した帯域通過
ろ波器が用いられている。[Prior Art] Conventionally, as a band-pass filter that meets the above-mentioned characteristics requirements, a band-pass filter constructed by connecting a plurality of TE01 alternator mode dielectric resonators in series has been used. is used.
【0003】0003
【発明が解決しようとする課題】複数個のTE01テ゛
ルタ モ−ド誘電体共振器を縱続接続して帯域通過ろ波
器を構成する場合には、入力結合回路と初段の共振器と
の結合度及び終段の共振器と出力結合回路との結合度を
それぞれ密にすることが不可能で、通過帯域幅の広い帯
域通過ろ波器を実現することが困難である。[Problem to be Solved by the Invention] When configuring a bandpass filter by connecting a plurality of TE01 alternator mode dielectric resonators in series, it is necessary to It is impossible to increase the degree of coupling between the resonator at the final stage and the output coupling circuit, and it is difficult to realize a bandpass filter with a wide passband width.
【0004】0004
【課題を解決するための手段】本発明は、共通のシ−ル
ドケ−スに内装された入力結合素子に結合する同軸共振
素子より成る初段の同軸共振器と、前記共通のシ−ルド
ケ−スに内装された出力結合素子に結合する同軸共振素
子より成る終段の同軸共振器と、前記初段及び終段の同
軸共振器間における前記共通のシ−ルドケ−スに内装さ
れた適宜数のTE01テ゛ルタ モ−ド誘電体共振素子
より成る適宜数のTE01テ゛ルタ モ−ド誘電体共振
器とを備えた帯域通過ろ波器を実現することによって従
来の欠点を除こうとするものである。[Means for Solving the Problems] The present invention provides a first-stage coaxial resonator comprising a coaxial resonant element coupled to an input coupling element housed in a common shield case, and a final stage coaxial resonator comprising a coaxial resonant element coupled to an output coupling element installed in the TE01, and an appropriate number of TE01s installed in the common shield case between the first and final stage coaxial resonators. The present invention attempts to eliminate the drawbacks of the prior art by realizing a bandpass filter with an appropriate number of TE01 alternating dielectric resonators comprising alternating alternating dielectric resonators.
【0005】[0005]
【作用】入力結合素子と初段の同軸共振素子とは電磁界
結合され、この結合係数は入力結合素子と初段の同軸共
振素子との間隔を変化させることにより、密結合から疎
結合までの広い範囲に亙って変化する。終段の同軸共振
素子と出力結合素子との結合も入力側と全く同様である
。初段の同軸共振素子と次段のTE01テ゛ルタ モ−
ド誘電体共振素子とは、電界結合と磁界結合によって結
合されるため、同軸共振素子とTE01テ゛ルタ モ−
ド誘電体共振素子との間隔を変化させることにより、密
結合から疎結合までの広い範囲に亙って変化する。終段
の同軸共振素子とその前段のTE01テ゛ルタ モ−ド
誘電体共振素子との結合も入力側と同様である。TE0
1テ゛ルタ モ−ド誘電体共振素子のうち、隣接する共
振素子相互間の結合は、主に磁界結合であるため、結合
は共振素子相互の間隔に応じて中間程度の結合から疎結
合に到る範囲で変化する。[Operation] The input coupling element and the first stage coaxial resonant element are electromagnetically coupled, and this coupling coefficient can be varied over a wide range from close coupling to loose coupling by changing the distance between the input coupling element and the first stage coaxial resonant element. changes over time. The coupling between the final stage coaxial resonant element and the output coupling element is also exactly the same as that on the input side. First-stage coaxial resonant element and second-stage TE01 alternator
A coaxial resonant element and a TE01 rotor motor are coupled to each other by electric field coupling and magnetic field coupling.
By changing the distance from the dielectric resonant element, the coupling can be varied over a wide range from close coupling to loose coupling. The coupling between the coaxial resonant element at the final stage and the TE01 alternator mode dielectric resonant element at the preceding stage is also the same as on the input side. TE0
In a 1-telter mode dielectric resonant element, the coupling between adjacent resonant elements is mainly magnetic field coupling, so the coupling ranges from medium to loose coupling depending on the spacing between the resonant elements. Varies in range.
【0006】[0006]
【実施例】図1(a)は、本発明の一実施例の要部を示
す断面図{図1(b)のB−B断面図}、図1(b)は
、図1(a)のA−A断面図で、両図において、Sは共
通のシ−ルドケ−ス、R1C 及びR8C は同軸共振
器を形成する棒状又は筒状の共振素子、R2D ないし
R7D はTE01テ゛ルタ モ−ド誘電体共振素子で
、各中心軸が互いに平行(向きは、すべてが同一でも逆
向きのものを含んでも差支えない)となるように配設す
ると共に、同軸共振素子R1C 及びR8C の各中心
軸方向とTE01テ゛ルタ モ−ド誘電体共振素子R2
D 及びR7D の各中心軸方向とが互いに直交するよ
うに配設してある。[Embodiment] FIG. 1(a) is a cross-sectional view showing a main part of an embodiment of the present invention {BB cross-sectional view of FIG. 1(b)}, and FIG. In both figures, S is a common shield case, R1C and R8C are rod-shaped or cylindrical resonant elements forming a coaxial resonator, and R2D to R7D are TE01 alternator mode dielectrics. The body resonant elements are arranged so that their central axes are parallel to each other (the directions may be the same or opposite), and the directions of the central axes of the coaxial resonant elements R1C and R8C are parallel to each other. TE01 alternator mode dielectric resonant element R2
The central axis directions of D and R7D are arranged so as to be perpendicular to each other.
【0007】CIは入力結合素子で、図には適宜幅の金
属板の一端を入力端子TIに、他端を共通のシ−ルドケ
−スSにそれぞれ接続すると共に、その長手方向が初段
の同軸共振素子R1C の中心軸方向と平行となるよう
に設けた結合線路より成る場合を例示してあるが、ル−
プ又は容量素子等で形成してもよい。COは出力結合素
子で、入力結合素子CIと同様の構成である。TOは出
力端子である。
以下、入力結合素子CI及び出力結合素子COを結合線
路で形成した場合について説明する。なお、図1には、
各共振素子毎に設ける共振周波数微調整素子を図示する
のを省略してある。CI is an input coupling element, and in the figure, one end of a metal plate of an appropriate width is connected to an input terminal TI, the other end is connected to a common shield case S, and its longitudinal direction is connected to the first stage coaxial Although a case is illustrated in which the coupling line is provided parallel to the central axis direction of the resonant element R1C, the rule
It may also be formed using a loop or a capacitive element. CO is an output coupling element and has the same configuration as the input coupling element CI. TO is an output terminal. Hereinafter, a case where the input coupling element CI and the output coupling element CO are formed by coupling lines will be described. In addition, in Figure 1,
The illustration of the resonant frequency fine adjustment element provided for each resonant element is omitted.
【0008】図2は、図1に示した本発明帯域通過ろ波
器における入力結合線路と初段の同軸共振素子間の結合
及び共振素子相互間の結合を説明するための一部拡大断
面図で、図2(a)は、図2(b)のB−B断面図、図
2(b)は、図2(a)のA−A断面図である。図2(
a)における矢印を付した実線は電界を示し、図2(b
)おける破線は磁界を示す。図2における符号は、図1
と同様で、図2には、入力側の電界及び磁界の分布を示
したが、出力側における電界及び磁界の分布も入力側と
同様である。FIG. 2 is a partially enlarged sectional view for explaining the coupling between the input coupling line and the first-stage coaxial resonant element and the coupling between the resonant elements in the band-pass filter of the present invention shown in FIG. , FIG. 2(a) is a sectional view taken along line BB in FIG. 2(b), and FIG. 2(b) is a sectional view taken along line AA in FIG. 2(a). Figure 2 (
The solid line with an arrow in a) indicates the electric field, and the solid line with an arrow in Fig. 2(b)
) The dashed line in ) indicates the magnetic field. The symbols in Figure 2 are the same as those in Figure 1.
Although FIG. 2 shows the distribution of the electric field and magnetic field on the input side, the distribution of the electric field and magnetic field on the output side is also the same as that on the input side.
【0009】図3は、図1に示した本発明帯域通過ろ波
器の等価回路図で、EI1 、E12 、E78 及び
E8O は電界結合係数、MI1 、M12 、M23
、M34 、M45 、M56 、M67 、M78
及びM8O は磁界結合係数である。FIG. 3 is an equivalent circuit diagram of the band-pass filter of the present invention shown in FIG. 1, where EI1, E12, E78 and E8O are electric field coupling coefficients, MI1, M12, M23
, M34 , M45 , M56 , M67 , M78
and M8O is the magnetic field coupling coefficient.
【0010】本発明帯域通過ろ波器においては、図2に
示すように、入力結合線路CIと初段の同軸共振素子R
1C との結合は電磁界結合で、その結合度は、入力結
合線路CIと初段の同軸共振素子R1Cの間隔に応じて
密結合から疎結合までの広い範囲に亙って変えることが
できる。終段の同軸共振素子R8C と出力結合線路C
Oとの結合も入力側と同様である。初段の同軸共振素子
R1C と次段のTE01テ゛ルタ モ−ド誘電体共振
素子R2D とは、電界結合と磁界結合によって結合さ
れるため、同軸共振素子R1C とTE01テ゛ルタ
モ−ド誘電体共振素子R2D の間隔に応じて密結合か
ら疎結合までの広い範囲に亙って変化させることが可能
である。TE01テ゛ルタ モ−ド誘電体共振素子R7
D と同軸共振素子R8Cとの結合も入力側と同様であ
る。TE01テ゛ルタ モ−ド誘電体共振素子R2D
ないしR7D のうち、隣接する共振素子相互間は、磁
界結合が主な結合であるため、共振素子相互の間隔に応
じて中間程度の結合から疎結合に到る範囲で変化する。In the bandpass filter of the present invention, as shown in FIG. 2, the input coupling line CI and the first stage coaxial resonant element R
The coupling with 1C is electromagnetic coupling, and the degree of coupling can be varied over a wide range from close coupling to loose coupling depending on the distance between the input coupling line CI and the first stage coaxial resonant element R1C. Final stage coaxial resonant element R8C and output coupling line C
The connection with O is also the same as on the input side. The first-stage coaxial resonant element R1C and the next-stage TE01-mode dielectric resonant element R2D are coupled by electric field coupling and magnetic field coupling.
It is possible to vary it over a wide range from close coupling to loose coupling depending on the spacing between the mode dielectric resonant elements R2D. TE01 alter mode dielectric resonant element R7
The coupling between D and the coaxial resonant element R8C is also the same as that on the input side. TE01 alter mode dielectric resonant element R2D
to R7D, since magnetic field coupling is the main coupling between adjacent resonant elements, the coupling varies from medium to loose coupling depending on the spacing between the resonant elements.
【0011】本発明帯域通過ろ波器は、入力結合線路C
Iと初段の同軸共振素子R1C 間の結合及び終段の同
軸共振器R8C と出力結合線路CO間の結合をそれぞ
れ密にすることができ、初段の同軸共振素子R1C と
終段の同軸共振素子R8C との間に配設される共振素
子をTE01テ゛ルタ モ−ド誘電体共振素子で形成し
てあるから、通過帯域幅を広く、通過帯域における挿入
損失を少なくすることができる。The bandpass filter of the present invention has an input coupling line C
The coupling between I and the first stage coaxial resonant element R1C and the coupling between the final stage coaxial resonator R8C and the output coupling line CO can be made tighter. Since the resonant element disposed between the TE01 and TEL mode dielectric resonant elements is formed by a TE01 alternator mode dielectric resonant element, the pass band width can be widened and the insertion loss in the pass band can be reduced.
【0012】複数個の共振素子を縱続接続して帯域通過
ろ波器を構成する場合、その次数に応じて各共振器の負
荷時のQの配分を適当にすることによって、伝送信号に
含まれるリップル分を小さくすることができるが、本発
明帯域通過ろ波器においても次数が例えば図1に示すよ
うに8の場合には、基準となる共振器の負荷時のQをQ
Lとした場合、初段及び終段の共振素子R1C 及びR
8C より成る共振器の負荷時のQをほぼ0.3QL
に、共振素子R2D 及びR7D より成る共振器の負
荷時のQをほぼ0.63QLに、共振素子R3D 及び
R6Dより成る共振器の負荷時のQをほぼ0.79QL
に、共振素子R4D 及びR5D より成る共振器の負
荷時のQをほぼ0.82QLに、それぞれ選定すること
によってリップル分を小さくすることができる。[0012] When configuring a bandpass filter by connecting a plurality of resonant elements in series, by appropriately distributing the Q of each resonator when loaded according to its order, it is possible to However, even in the band-pass filter of the present invention, if the order is 8 as shown in FIG.
In the case of L, the first and final stage resonant elements R1C and R
The Q of the resonator made of 8C when loaded is approximately 0.3QL.
In addition, the Q of the resonator composed of resonant elements R2D and R7D when loaded is approximately 0.63QL, and the Q of the resonator composed of resonant elements R3D and R6D when loaded is approximately 0.79QL.
Furthermore, the ripple can be reduced by selecting the load Q of the resonator consisting of the resonant elements R4D and R5D to approximately 0.82QL.
【0013】本発明帯域通過ろ波器を構成するTE01
テ゛ルタ モ−ド誘電体共振素子R2D ないしR7D
より成る共振器の無負荷時におけるQ(QU)は、例
えば共振周波数900MHzにおいて最高25000
、初段及び終段の同軸共振素子R1C及びR8C より
成る共振器の無負荷時におけるQ(QU)は最高値がほ
ぼ8300で、TE01テ゛ルタ モ−ド誘電体共振素
子より成る共振器のほぼ1/3 であるが、帯域通過ろ
波器の挿入損失に影響を与えるおそれはない。TE01 constituting the bandpass filter of the present invention
Delta mode dielectric resonant element R2D to R7D
The unloaded Q (QU) of a resonator consisting of
The Q (QU) at no load of the resonator consisting of coaxial resonant elements R1C and R8C in the first and final stages has a maximum value of approximately 8300, which is approximately 1/1 of that of the resonator consisting of TE01 alternator mode dielectric resonant elements. 3, but there is no risk of affecting the insertion loss of the bandpass filter.
【0014】各共振素子と共通のシ−ルドケ−スによっ
て形成される共振器毎の挿入損失は、次式で求めること
ができる。The insertion loss for each resonator formed by each resonant element and a common shield case can be determined by the following equation.
【数1】 上式において、 LQk :共振器の挿入損失 QUk :無負荷時のQ QLk :負荷時のQ k :1から8まで[Math 1] In the above formula, LQk: Resonator insertion loss QUk: Q at no load QLk: Q at load k: from 1 to 8
【0015】本発明帯域通過ろ波器においては、図1に
破線で示すように、適当な伝送線路より成る副結合線路
SL27の一端を、容量素子又はル−プ等より成る電界
(又は磁界)副結合素子C2(L2)を介して共振素子
R2D に副結合すると共に、他端を電界(又は磁界)
副結合素子C7(L7)を介して共振素子R7D に副
結合し、副結合線路SL27と同様構成の副結合線路S
L36の一端を電界(又は磁界)副結合素子C3(L3
)を介して共振素子R3D に副結合すると共に、他端
を電界(又は磁界)副結合素子C6(L6)を介して共
振素子R6D に副結合することによって、有極形帯域
通過ろ波器を構成することができる。In the band-pass filter of the present invention, as shown by the broken line in FIG. 1, one end of the sub-coupling line SL27 made of a suitable transmission line is connected to an electric field (or magnetic field) made of a capacitive element or a loop, etc. It is sub-coupled to the resonant element R2D via the sub-coupling element C2 (L2), and the other end is connected to an electric field (or magnetic field).
A sub-coupling line S is sub-coupled to the resonant element R7D via the sub-coupling element C7 (L7) and has the same configuration as the sub-coupling line SL27.
One end of L36 is connected to electric field (or magnetic field) sub-coupling element C3 (L3
) and sub-coupling the other end to the resonant element R6D via the electric field (or magnetic field) sub-coupling element C6 (L6), thereby forming a polarized bandpass filter. Can be configured.
【0016】副結合線路SL27及びSL36の各電気
長を適当に定めると、縦続接続された共振素子R1C
ないしR8C より成る主回路を伝送して共振素子R7
D に到る信号の位相と、副結合線路SL27を介して
共振素子R7D に達する信号の位相を互いに逆相とし
、同様に、主回路を伝送して共振素子R6D に到る信
号の位相と、副結合線路SL36を介して共振素子R6
D に達する信号の位相を互いに逆相とすることができ
る。When the electrical lengths of the sub-coupled lines SL27 and SL36 are determined appropriately, the cascade-connected resonant element R1C
The main circuit consisting of R8C is transmitted to the resonant element R7.
The phase of the signal reaching D and the phase of the signal reaching the resonant element R7D via the sub-coupling line SL27 are opposite to each other, and similarly, the phase of the signal transmitted through the main circuit and reaching the resonant element R6D, Resonant element R6 via sub-coupling line SL36
The phases of the signals reaching D can be made to be opposite to each other.
【0017】したがって、副結合素子C2(L2)、C
3(L3)、C6(L6)及びC7(L7)と共振素子
間の各結合度を適当にして、主回路及び副結合線路SL
27を各伝送して共振素子R7D に達する両信号の振
幅を互いに等しくすることにより、減衰域におけるこの
信号の周波数位置に減衰極を生じさせ、同様に主回路及
び副結合線路SL36を各伝送して共振素子R6D に
達する両信号の振幅を互いに等しくすることにより、減
衰域におけるこの信号の周波数位置に減衰極を生じさせ
ることができる。Therefore, the sub-coupling elements C2 (L2), C
3 (L3), C6 (L6), and C7 (L7) and the resonant element, and connect the main circuit and sub-coupling line SL.
By making the amplitudes of the two signals that reach the resonant element R7D after each transmission of 27 equal to each other, an attenuation pole is generated at the frequency position of this signal in the attenuation region, and similarly, the main circuit and the sub-coupling line SL36 are transmitted. By making the amplitudes of both signals reaching the resonant element R6D equal to each other, an attenuation pole can be generated at the frequency position of this signal in the attenuation range.
【0018】以上は、2個の副結合線路を用いた場合を
例示したが、適宜増減して本発明を実施することができ
、必要に応じて帯域通過ろ波器の次数を増して副結合線
路の数を増加させるようにしてもよい。いずれの場合に
も、2個又はその整数倍の個数の共振素子を介して対向
する共振素子相互を副結合することによって減衰域に減
衰極を生じさせることができる。Although the above example uses two sub-coupled lines, the present invention can be implemented by increasing or decreasing the number of sub-coupling lines as necessary.If necessary, the order of the band-pass filter can be increased to The number of lines may be increased. In either case, an attenuation pole can be generated in the attenuation region by sub-coupling opposing resonant elements through two resonant elements or an integral multiple thereof.
【0019】図4は、本発明の他の実施例の要部を示す
図で、図4(a)は、図4(b)のB−B断面図、図4
(b)は、図4(a)のA−A断面図である。両図にお
いて、SUは共通のシ−ルドケ−ス、SSは金属板より
成る隔壁で、シ−ルドケ−スSU内をコの字形に仕切っ
てある。TIは入力端子、CIは入力結合線路、R1C
は同軸共振素子、R2D ないしR7D はTE01
テ゛ルタ モ−ド誘電体共振素子、R8C は同軸共振
素子、COは出力結合線路、TOは出力端子で、これら
を隔壁SSで仕切られたコの字形空間にコの字形に配設
した他は、共振素子R1C 及びR2D の両中心軸方
向が直交し、共振素子R8C 及びR7D の両中心軸
方向がを直交すると共に、共振素子R2D ないしR7
D の各中心軸が平行となるように配設してあること図
1に示した実施例と同様である。SC18は副結合容量
素子で、共振素子R1C 及びR8C との各間に容量
を形成する電極を、隔壁SSに穿った孔隙に挿通された
導体の両端部に取付けて形成してある。SH27は隔壁
SSに穿った副結合孔、SC36は副結合容量素子で、
素子SC18と同様の構成である。FIG. 4 is a diagram showing essential parts of another embodiment of the present invention, and FIG. 4(a) is a sectional view taken along line BB in FIG. 4(b).
(b) is a sectional view taken along line AA in FIG. 4(a). In both figures, SU is a common shield case, and SS is a partition wall made of a metal plate, which partitions the inside of the shield case SU into a U-shape. TI is the input terminal, CI is the input coupling line, R1C
is a coaxial resonant element, R2D to R7D is TE01
The alternator mode dielectric resonant element, R8C is a coaxial resonant element, CO is an output coupling line, TO is an output terminal, and these are arranged in a U-shape in a U-shaped space partitioned by a partition wall SS. The central axes of the resonant elements R1C and R2D are perpendicular to each other, and the central axes of the resonant elements R8C and R7D are perpendicular to each other.
This is similar to the embodiment shown in FIG. 1 in that the central axes of D are arranged in parallel. SC18 is a sub-coupling capacitance element, which is formed by attaching electrodes that form a capacitance between each of the resonant elements R1C and R8C to both ends of a conductor inserted through a hole bored in the partition wall SS. SH27 is a sub-coupling hole drilled in the partition wall SS, SC36 is a sub-coupling capacitance element,
It has the same configuration as element SC18.
【0020】図5は、図4に示した本発明帯域通過ろ波
器の等価回路図で、E18 及びE36 は副電界結合
係数、M27 は副磁界結合係数で、他の符号は図3と
同様である。FIG. 5 is an equivalent circuit diagram of the band-pass filter of the present invention shown in FIG. 4, where E18 and E36 are sub-electric field coupling coefficients, M27 is a sub-magnetic field coupling coefficient, and other symbols are the same as in FIG. 3. It is.
【0021】本実施例における共振素子間の結合作用及
び減衰域における減衰極の形成作用等は、図1に示した
実施例と同様であるが、本実施例においては、各共振素
子より成る主回路をコの字形に配設してあるため、全体
を小形化することができ、隔壁SSを介して設けた副結
合容量素子SC18、SC36及び隔壁に穿った副結合
孔SH27によって副結合を行うことができるから、図
1に示した実施例のように、副結合線路と電界(又は磁
界)副結合素子を用いて副結合回路を形成する場合に比
し、副結合回路の構成を簡潔にすることができる。図4
に示した実施例においても、副結合素子を省いて無極形
帯域通過ろ波器を構成することができること勿論である
。The coupling effect between the resonant elements and the formation of attenuation poles in the attenuation region in this embodiment are similar to those in the embodiment shown in FIG. Since the circuit is arranged in a U-shape, the entire circuit can be miniaturized, and sub-coupling is performed by the sub-coupling capacitance elements SC18 and SC36 provided through the partition wall SS and the sub-coupling hole SH27 bored in the partition wall. Therefore, the configuration of the sub-coupling circuit can be simplified compared to the case where the sub-coupling circuit is formed using a sub-coupling line and an electric field (or magnetic field) sub-coupling element as in the embodiment shown in FIG. can do. Figure 4
It goes without saying that even in the embodiment shown in FIG.
【0022】図6は、本発明帯域通過ろ波器の伝送特性
の一例を示す曲線図、図7は、図6における通過帯域部
分の拡大図で、両図において、横軸は伝送周波数f(M
Hz)、縦軸は減衰量ATT(dB) である。FIG. 6 is a curve diagram showing an example of the transmission characteristics of the bandpass filter of the present invention, and FIG. 7 is an enlarged diagram of the passband portion in FIG. 6. In both figures, the horizontal axis represents the transmission frequency f ( M
Hz), and the vertical axis is the attenuation amount ATT (dB).
【0023】[0023]
【発明の効果】本発明帯域通過ろ波器は、初段及び終段
の共振素子を同軸共振素子で形成し、中間の共振素子を
TE01テ゛ルタ モ−ド誘電体共振素子で形成するこ
とによって、入力結合線路と初段の共振素子との結合度
及び終段の共振素子と出力結合線路との結合度をそれぞ
れ密にして、通過帯域幅を広くすることが可能であると
共に、通過帯域における挿入損失を少なくすることがで
きる。Effects of the Invention In the bandpass filter of the present invention, the first and final stage resonant elements are formed by coaxial resonant elements, and the intermediate resonant element is formed by a TE01 alternator mode dielectric resonant element. By increasing the degree of coupling between the coupling line and the first-stage resonant element and the degree of coupling between the last-stage resonant element and the output coupling line, it is possible to widen the passband width and reduce insertion loss in the passband. It can be reduced.
【図1】本発明の一実施例の要部を示す断面図である。FIG. 1 is a sectional view showing essential parts of an embodiment of the present invention.
【図2】本発明帯域通過ろ波器における電界及び磁界分
布を示す図である。FIG. 2 is a diagram showing electric field and magnetic field distributions in the bandpass filter of the present invention.
【図3】本発明帯域通過ろ波器の等価回路図である。FIG. 3 is an equivalent circuit diagram of the bandpass filter of the present invention.
【図4】本発明の他の実施例の要部を示す断面図である
。FIG. 4 is a sectional view showing essential parts of another embodiment of the present invention.
【図5】本発明帯域通過ろ波器の等価回路図である。FIG. 5 is an equivalent circuit diagram of the bandpass filter of the present invention.
【図6】本発明帯域通過ろ波器の伝送特性の一例を示す
曲線図である。FIG. 6 is a curve diagram showing an example of the transmission characteristics of the bandpass filter of the present invention.
【図7】本発明帯域通過ろ波器の伝送特性の一例を示す
曲線図である。FIG. 7 is a curve diagram showing an example of the transmission characteristics of the bandpass filter of the present invention.
S 共通のシ−ルドケ−ス
R1C 共振素子
R2D 共振素子
R3D 共振素子
R4D 共振素子
R5D 共振素子
R6D 共振素子
R7D 共振素子
R8C 共振素子
CI 入力結合素子
CO 出力結合素子
TI 入力端子
TO 出力端子
SL27 副結合線路
SL36 副結合線路
C2(L2) 副結合素子
C3(L3) 副結合素子
C6(L6) 副結合素子
C7(L7) 副結合素子
SU 共通のシ−ルドケ−スSS
隔壁
SC18 副結合素子
SC36 副結合素子
SH27 副結合素子
EI1 電界結合係数
E12 電界結合係数
E78 電界結合係数
E8O 電界結合係数
MI1 磁界結合係数
M12 磁界結合係数
M23 磁界結合係数
M34 磁界結合係数
M45 磁界結合係数
M56 磁界結合係数
M67 磁界結合係数
M78 磁界結合係数
M8O 磁界結合係数
E18 副電界結合係数
E36 副電界結合係数
M27 副磁界結合係数S Common shield case R1C Resonant element R2D Resonant element R3D Resonant element R4D Resonant element R5D Resonant element R6D Resonant element R7D Resonant element R8C Resonant element CI Input coupling element CO Output coupling element TI Input terminal TO Output terminal SL27 Sub-coupling line SL36 Sub-coupling line C2 (L2) Sub-coupling element C3 (L3) Sub-coupling element C6 (L6) Sub-coupling element C7 (L7) Sub-coupling element SU Common shield case SS
Partition wall SC18 Sub-coupling element SC36 Sub-coupling element SH27 Sub-coupling element EI1 Electric field coupling coefficient E12 Electric field coupling coefficient E78 Electric field coupling coefficient E8O Electric field coupling coefficient MI1 Magnetic field coupling coefficient M12 Magnetic field coupling coefficient M23 Magnetic field coupling coefficient M34 Magnetic field coupling coefficient M45 Magnetic field coupling coefficient M56 Magnetic field coupling coefficient M67 Magnetic field coupling coefficient M78 Magnetic field coupling coefficient M8O Magnetic field coupling coefficient E18 Sub-electric field coupling coefficient E36 Sub-electric field coupling coefficient M27 Sub-magnetic field coupling coefficient
Claims (6)
合素子に結合する同軸共振素子より成る初段の同軸共振
器と、前記共通のシ−ルドケ−スに内装された出力結合
素子に結合する同軸共振素子より成る終段の同軸共振器
と、前記初段及び終段の同軸共振器間における前記共通
のシ−ルドケ−スに内装された適宜数のTE01テ゛ル
タ モ−ド誘電体共振素子より成る適宜数のTE01テ
゛ルタ モ−ド誘電体共振器とを備えたことを特徴とす
る帯域通過ろ波器。Claim 1: A first stage coaxial resonator comprising a coaxial resonant element coupled to an input coupling element housed in a common shield case, and an output coupling element housed in the common shield case. a final stage coaxial resonator comprising coaxial resonant elements to be coupled, and an appropriate number of TE01 alternator mode dielectric resonant elements housed in the common shield case between the first stage and final stage coaxial resonators. A bandpass filter comprising an appropriate number of TE01 alternator mode dielectric resonators.
軸方向と、この同軸共振素子に隣接するTE01テ゛ル
タ モ−ド誘電体共振器におけるTE01テ゛ルタ モ
−ド誘電体共振素子の軸方向とが直交し、終段の同軸共
振器における同軸共振素子の軸方向と、この同軸共振素
子に隣接するTE01テ゛ルタ モ−ド誘電体共振器に
おけるTE01テ゛ルタ モ−ド誘電体共振素子の軸方
向とが直交すると共に、各TE01テ゛ルタ モ−ド誘
電体共振器におけるTE01テ゛ルタ モ−ド誘電体共
振素子が平行となるように配設された請求項1に記載の
帯域通過ろ波器。[Claim 2] The axial direction of the coaxial resonant element in the first-stage coaxial resonator and the axial direction of the TE01 alternator mode dielectric resonator in the TE01 alternator mode dielectric resonator adjacent to this coaxial resonator are different. The axial direction of the coaxial resonant element in the final stage coaxial resonator is orthogonal to the axial direction of the TE01 alternator mode dielectric resonator in the TE01 alternator mode dielectric resonator adjacent to this coaxial resonator. 2. The bandpass filter according to claim 1, wherein the TE01 alternator mode dielectric resonant elements in each TE01 alternator mode dielectric resonator are arranged in parallel.
項1に記載の帯域通過ろ波器。3. A bandpass filter according to claim 1, wherein the common shield case is linear.
して対向する共振素子相互を副結合させた請求項1に記
載の帯域通過ろ波器。4. The bandpass filter according to claim 1, wherein the opposing resonant elements are sub-coupled via two resonant elements or an integral multiple thereof.
隔壁で仕切ってコの字形空間を形成し、この空間内に複
数個の共振素子をコの字形に配設した請求項1に記載の
帯域通過ろ波器。5. Claim 1, wherein a common shield case is partitioned by partition walls made of metal plates to form a U-shaped space, and a plurality of resonant elements are arranged in a U-shape within this space. A bandpass filter as described in .
して対向する共振素子相互を副結合させた請求項5に記
載の帯域通過ろ波器。6. The bandpass filter according to claim 5, wherein the opposing resonant elements are sub-coupled via two resonant elements or an integral multiple thereof.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP9277891A JPH04304004A (en) | 1991-03-31 | 1991-03-31 | Band pass filter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP9277891A JPH04304004A (en) | 1991-03-31 | 1991-03-31 | Band pass filter |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH04304004A true JPH04304004A (en) | 1992-10-27 |
Family
ID=14063882
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP9277891A Pending JPH04304004A (en) | 1991-03-31 | 1991-03-31 | Band pass filter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH04304004A (en) |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH05235607A (en) * | 1992-02-24 | 1993-09-10 | Nippon Dengiyou Kosaku Kk | Band pass filter |
JPH10173408A (en) * | 1996-12-06 | 1998-06-26 | Nec Corp | Adjacent wave branching filter |
US5969584A (en) * | 1997-07-02 | 1999-10-19 | Adc Solitra Inc. | Resonating structure providing notch and bandpass filtering |
Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS51134548A (en) * | 1975-05-19 | 1976-11-22 | Nec Corp | Microwave band-pass filter |
JPS5227244A (en) * | 1975-08-26 | 1977-03-01 | Nec Corp | Microwave polarized bandpass filter |
JPS63176002A (en) * | 1987-01-17 | 1988-07-20 | Murata Mfg Co Ltd | Dielectric resonator device |
-
1991
- 1991-03-31 JP JP9277891A patent/JPH04304004A/en active Pending
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS51134548A (en) * | 1975-05-19 | 1976-11-22 | Nec Corp | Microwave band-pass filter |
JPS5227244A (en) * | 1975-08-26 | 1977-03-01 | Nec Corp | Microwave polarized bandpass filter |
JPS63176002A (en) * | 1987-01-17 | 1988-07-20 | Murata Mfg Co Ltd | Dielectric resonator device |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH05235607A (en) * | 1992-02-24 | 1993-09-10 | Nippon Dengiyou Kosaku Kk | Band pass filter |
JPH10173408A (en) * | 1996-12-06 | 1998-06-26 | Nec Corp | Adjacent wave branching filter |
US5969584A (en) * | 1997-07-02 | 1999-10-19 | Adc Solitra Inc. | Resonating structure providing notch and bandpass filtering |
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