JPH04290321A - Nonlinear distortion compensating method - Google Patents
Nonlinear distortion compensating methodInfo
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- JPH04290321A JPH04290321A JP5511791A JP5511791A JPH04290321A JP H04290321 A JPH04290321 A JP H04290321A JP 5511791 A JP5511791 A JP 5511791A JP 5511791 A JP5511791 A JP 5511791A JP H04290321 A JPH04290321 A JP H04290321A
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- signal
- power amplifier
- frequency power
- nonlinear distortion
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Abstract
Description
【0001】0001
【産業上の利用分野】本発明はデイジタルマイクロ無線
装置で使用する非線形歪補償方法に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a nonlinear distortion compensation method used in digital micro radio equipment.
【0002】近年、変調方式の多値化に伴い、高周波電
力増幅器のバックオフ量が増大している。例えば、16
QAM 変調方式の場合は約8dBであったが、64Q
AM 変調方式の場合は約10dBとなり、更に256
QAM変調方式の場合は12〜13dBのバックオフを
取ならければならなくなっている。[0002] In recent years, the amount of backoff of high frequency power amplifiers has increased as modulation methods have become more multi-valued. For example, 16
In the case of QAM modulation method, it was about 8 dB, but 64Q
In the case of AM modulation method, it is approximately 10 dB, and further 256 dB.
In the case of QAM modulation, a backoff of 12 to 13 dB must be taken care of.
【0003】この様なバックオフ量の増加に対応して、
装置全体の電源効率が低下すると共に、電源容量を大き
くしなければならないので、コストアップ、収容スペー
スの増大、より効果的な熱設計が必要となる。[0003] In response to this increase in backoff amount,
The power efficiency of the entire device decreases, and the power supply capacity must be increased, which increases costs, increases housing space, and requires more effective thermal design.
【0004】そこで、高周波電力増幅器のバックオフ量
を低減させることにより、電源効率を改善すると共に、
この増幅器の大幅な小形化を図ることが必要である。[0004] Therefore, by reducing the amount of back-off of the high frequency power amplifier, power efficiency can be improved, and
It is necessary to significantly downsize this amplifier.
【0005】[0005]
【従来の技術】図5は従来例のブロック図、図6は図5
中の送信側詳細ブロック図、図7は高周波電力増幅器動
作説明図である。[Prior Art] FIG. 5 is a block diagram of a conventional example, and FIG. 6 is a block diagram of a conventional example.
FIG. 7 is a detailed block diagram of the transmitting side in FIG.
【0006】以下、図6,図7を参照して図5の動作を
説明する。先ず、図6において、変調部1に入力した、
例えばI ch及びQ chのデイジタル信号をデイジ
タル/アナログ変換器11でアナログ信号に変換した後
、低域通過フイルタ12で帯域幅を制限して直交変調器
13に加える。The operation of FIG. 5 will be explained below with reference to FIGS. 6 and 7. First, in FIG. 6, input to the modulation section 1,
For example, after the digital signals of I ch and Q ch are converted into analog signals by the digital/analog converter 11, the bandwidth is limited by the low pass filter 12 and the signal is applied to the quadrature modulator 13.
【0007】直交変調器では、I ch及びQ chの
アナログ信号を用いて、例えば中間周波帯のキャリア1
4を多値QAM 変調して多値QAM 変調波を生成し
、送信部2の中の周波数変換器21に送出する。周波数
変換器には、送信局部発振器22からの送信局発信号も
加えられているので、高周波帯の多値QAM 変調波に
周波数変換した後、プリディストータ31に加える。In the quadrature modulator, for example, carrier 1 in the intermediate frequency band is
4 is subjected to multi-value QAM modulation to generate a multi-value QAM modulated wave, which is sent to the frequency converter 21 in the transmitter 2. Since the frequency converter also receives the transmitting local oscillator signal from the transmitting local oscillator 22, the signal is frequency-converted into a multi-level QAM modulated wave in a high frequency band and then applied to the predistorter 31.
【0008】ここで、高周波電力増幅器32はA 級動
作をしているので、図7の■に示す様に、入力レベルが
あるレベル付近までは入出力特性は直線的に変化する。
しかし、あるレベル以上になるとAM−AM 変換が生
じて, 直線部分から外れて除々に飽和状態に近ずく。Here, since the high frequency power amplifier 32 operates in class A operation, the input/output characteristics change linearly until the input level approaches a certain level, as shown in (■) in FIG. However, when a certain level is exceeded, AM-AM conversion occurs and the signal deviates from the straight line and gradually approaches saturation.
【0009】また、入出力特性が直線部分から外れる付
近になると、AM−PM 変換が生じて、例えば図7の
■に示す様な位相特性を示す。そこで、プリデイストー
タ31は、図7の■及び■に示す様な歪を、周波数変換
器21の出力に与えて高周波電力増幅器32に送出する
。この為、高周波電力増幅器で発生する非線形歪をある
程度、補償して図7の■及び■に示す様に入出力特性の
直線部分が多少伸び、位相特性もある範囲内( 図中の
一点鎖線の間) に入る様になる。なお、図7の■に示
す様な特性はダイオードの非線形部分を重ね合わせるこ
とにより形成する。Furthermore, when the input/output characteristics deviate from the linear portion, AM-PM conversion occurs, resulting in a phase characteristic as shown, for example, in FIG. 7. Therefore, the predistorter 31 applies distortions as shown in (1) and (2) in FIG. 7 to the output of the frequency converter 21 and sends it to the high frequency power amplifier 32. For this reason, the nonlinear distortion generated in the high-frequency power amplifier is compensated to some extent, and the linear portion of the input/output characteristics is slightly extended as shown in ■ and ■ in Figure 7, and the phase characteristic is within a certain range (as indicated by the dashed line in the figure). (pause). Note that the characteristics shown in (■) in FIG. 7 are formed by overlapping the nonlinear portions of the diodes.
【0010】さて、図5に示す様に、高周波電力増幅器
32から送出された多値QAM 変調波は相手局の受信
部71で中間周波帯の多値QAM変調波に周波数変換さ
れた後、所定レベルまで増幅されて復調部72に加えら
れる。Now, as shown in FIG. 5, the multi-level QAM modulated wave sent out from the high-frequency power amplifier 32 is frequency-converted into a multi-level QAM modulated wave in the intermediate frequency band by the receiving section 71 of the partner station, and then is converted into a multi-level QAM modulated wave in the intermediate frequency band. The signal is amplified to the level and applied to the demodulator 72.
【0011】復調部では多値QAM 変調波からベース
バンド信号が取り出された後、識別されてデイジタル信
号に変換され、トランスバーサル等化器73で等化され
て符号間干渉が最小のデイジタル信号が得られる。In the demodulation section, a baseband signal is extracted from the multilevel QAM modulated wave, and then identified and converted into a digital signal.The transversal equalizer 73 equalizes the baseband signal to produce a digital signal with minimum intersymbol interference. can get.
【0012】0012
【発明が解決しようとする課題】さて、高周波電力増幅
器の大幅な小形化を図るには、バックオフ量を低減する
必要があるが、上記の様な単純な回路構成のプリデイス
トータが一般に使用されている。[Problem to be Solved by the Invention] Now, in order to significantly reduce the size of high-frequency power amplifiers, it is necessary to reduce the amount of backoff, but a predistorter with a simple circuit configuration as described above is generally used. There is.
【0013】しかし、この方式は高周波電力増幅器の単
調な非線形歪の部分は補償することができるが、それ以
外の非線形歪(単調関数で表現できない領域)について
は補償が不可能である。However, although this method can compensate for the monotonous nonlinear distortion of the high-frequency power amplifier, it cannot compensate for other nonlinear distortions (regions that cannot be expressed by a monotone function).
【0014】また、プリディストータの為に、高周波電
力増幅器の変動に対して完全に補償することはできず、
更に、帰還ループが構成されていないので、温度及び電
源変動,経年変化に対する補償が不可能である。Furthermore, due to the predistorter, it is not possible to completely compensate for fluctuations in the high frequency power amplifier.
Furthermore, since no feedback loop is configured, compensation for temperature and power supply fluctuations and aging is not possible.
【0015】しかも、高周波電力増幅器との組合せに対
しても、個別に設定する必要が有り、1台毎に調整しな
ければならない。即ち、非線形歪が単調関数で表現でき
ない領域や環境条件の変動、経年変化などによる歪の補
償は不可能であるので、バックオフ量を大幅に低減する
ことが不可能であると云う問題がある。[0015] Moreover, it is necessary to make individual settings for combinations with high-frequency power amplifiers, and adjustments must be made for each unit. In other words, it is impossible to compensate for distortion caused by areas where nonlinear distortion cannot be expressed as a monotonic function, fluctuations in environmental conditions, changes over time, etc., so there is a problem that it is impossible to significantly reduce the amount of backoff. .
【0016】本発明はバックオフ量を大幅に低減して、
高周波電力増幅器の大幅な小形化を図ることを目的とす
る。[0016] The present invention greatly reduces the amount of backoff,
The aim is to significantly reduce the size of high-frequency power amplifiers.
【0017】[0017]
【課題を解決するための手段】図1は第1〜第3の本発
明の原理ブロック図である。1は入力するデイジタル信
号をデイジタル/アナログ変換器でアナログ信号に変換
した後、該アナログ信号を用いて変調波を生成する変調
部で、2は内部の送信局部発振器の出力を用いて、入力
した該変調波の周波数を送信周波数に変換する送信部で
ある。[Means for Solving the Problems] FIG. 1 is a block diagram of the principle of the first to third aspects of the present invention. 1 is a modulation section that converts an input digital signal into an analog signal using a digital/analog converter, and then generates a modulated wave using the analog signal; 2 is a modulation section that uses the output of an internal transmitting local oscillator to convert an input digital signal into an analog signal; This is a transmitter that converts the frequency of the modulated wave into a transmission frequency.
【0018】また、3は入力した該送信周波数の変調波
を電力増幅して送出する高周波電力増幅器で、4は高周
波電力増幅器で発生する非線形歪を補償するための補償
係数が格納されたROMが付加されたデイジタルフイル
タである。Further, 3 is a high frequency power amplifier that amplifies the power of the input modulated wave of the transmission frequency and sends it out, and 4 is a ROM that stores compensation coefficients for compensating for nonlinear distortion generated in the high frequency power amplifier. This is an added digital filter.
【0019】更に、5は該高周波電力増幅器から送出さ
れる変調波を、内部で発生した受信局発信号を用いて周
波数変換した後、復調信号を取り出す受信・復調部で、
6は復調信号を利用して制御信号を生成する制御部であ
る。Further, 5 is a receiving/demodulating section which converts the frequency of the modulated wave sent out from the high frequency power amplifier using an internally generated receiving station oscillation signal and extracts a demodulated signal.
6 is a control unit that generates a control signal using the demodulated signal.
【0020】そして、第1の本発明は、デイジタルフイ
ルタをデイジタル/アナログ変換器の入力側に設け、該
デイジタルフイルタが該デイジタル/アナログ変換器に
入力するデイジタル信号に、高周波電力増幅器で発生す
る非線形歪を補償する歪を予め与える様にした。In the first aspect of the present invention, a digital filter is provided on the input side of the digital/analog converter, and the digital filter filters the nonlinear signal generated in the high frequency power amplifier into the digital signal input to the digital/analog converter. Distortion to compensate for the distortion was given in advance.
【0021】第2の本発明は、受信・復調部と、該復調
信号を利用して制御信号を生成する制御部とを設け、該
制御部が該高周波電力増幅器の動作条件の変動によって
生ずる符号間干渉が最小となる様に、該制御信号を利用
して該デイジタルフイルタの動作を制御する様にした。[0021] The second aspect of the present invention is provided with a receiving/demodulating section and a control section that generates a control signal using the demodulated signal, and the control section is configured to detect codes generated due to fluctuations in operating conditions of the high frequency power amplifier. The control signal is used to control the operation of the digital filter so that interference between the filters is minimized.
【0022】第3の本発明は、該受信局発信号を該送信
局部発振器の出力と同期させる。The third aspect of the invention synchronizes the receiving station oscillator signal with the output of the transmitting local oscillator.
【0023】[0023]
【作用】本発明は、高周波電力増幅器によって生ずるA
M−AM 変換,AM−PM 変換は、この増幅器の振
幅特性と遅延特性に変換される。一方、線形のデイジタ
ルフイルタは振幅特性と遅延特性を補償できるので、高
周波電力増幅器のダイナミック範囲内のある領域内で発
生する非線形歪(AM−AM変換, AM−PM 変換
) は上記のデイジタルフイルタで補償できると云う考
えに基づいている。[Operation] The present invention is directed to the A
M-AM conversion and AM-PM conversion are converted into amplitude characteristics and delay characteristics of this amplifier. On the other hand, since a linear digital filter can compensate for the amplitude characteristics and delay characteristics, the nonlinear distortion (AM-AM conversion, AM-PM conversion) that occurs within a certain region within the dynamic range of the high-frequency power amplifier can be compensated for by the above-mentioned digital filter. It is based on the idea that it can be compensated.
【0024】これを実現する為、第1の本発明はデイジ
タルフイルタを用いて該デイジタル/アナログ変換器に
入力するデイジタル信号に、高周波電力増幅器で発生す
る非線形歪を補償する様な歪を予め与える様にした。In order to achieve this, the first aspect of the present invention uses a digital filter to apply distortion to the digital signal input to the digital/analog converter in advance so as to compensate for the nonlinear distortion generated in the high frequency power amplifier. I did it like that.
【0025】第2の本発明は、送信側に単純化した受信
・復調部と制御部を設けると共に、デイジタル/アナロ
グ変換器の入力側にデイジタルフイルタを設けて帰還ル
ープを形成する。また、第3の本発明は受信局発信号を
該送信局部発振器の出力と同期させる。In the second aspect of the invention, a simplified reception/demodulation section and a control section are provided on the transmitting side, and a digital filter is provided on the input side of the digital/analog converter to form a feedback loop. Further, the third aspect of the present invention synchronizes the receiving station oscillation signal with the output of the transmitting local oscillator.
【0026】なお、上記の帰還ループを形成することに
より、制御部からの制御信号を用いて、高周波電力増幅
器の非線形歪が最小になる様にデイジタルフイルタの動
作を制御する。By forming the feedback loop described above, the operation of the digital filter is controlled using the control signal from the control section so that the nonlinear distortion of the high frequency power amplifier is minimized.
【0027】これにより、高周波電力増幅器のバックオ
フ量が大幅に低減すると共に、電源・温度・経年変化に
よる高周波電力増幅器自身のパラメータ変動によるビッ
ト誤り率の劣化が最小になる。[0027] As a result, the amount of backoff of the high frequency power amplifier is significantly reduced, and the deterioration of the bit error rate due to parameter fluctuations of the high frequency power amplifier itself due to changes in power supply, temperature, and aging is minimized.
【0028】即ち、高周波電力増幅器の大幅な小形化が
図れる。In other words, the high frequency power amplifier can be significantly downsized.
【0029】[0029]
【実施例】図2は第1〜第3の本発明の実施例の要部ブ
ロック図で、図3は図2の制御部・デイジタルフイルタ
構成図の一例、図4は図3の同相,直交タップ部の構成
図の一例で、(A) は基本的構成図、(B) は本発
明の構成図である。[Embodiment] FIG. 2 is a block diagram of main parts of the first to third embodiments of the present invention, FIG. 3 is an example of the control unit/digital filter configuration diagram of FIG. 2, and FIG. 4 is an in-phase and quadrature An example of a configuration diagram of a tap section, (A) is a basic configuration diagram, and (B) is a configuration diagram of the present invention.
【0030】ここで、受信部51, 復調部52は受信
・復調部5の構成部分、相関器61, 積分器62は制
御部6の構成部分である。なお、全図を通じて同一符号
は同一対象物を示す。Here, the receiving section 51 and the demodulating section 52 are the constituent parts of the receiving/demodulating section 5, and the correlator 61 and the integrator 62 are the constituent parts of the control section 6. Note that the same reference numerals indicate the same objects throughout the figures.
【0031】以下、図3,図4を参照して図2の動作を
説明する。先ず、入力した、例えば、I ch, Q
chのデイジタル信号はデイジタルフイルタ4で、後述
する様に予め定められた歪が付与された後、デイジタル
/アナログ変換器11でアナログ信号に変換される。そ
して、図示しない直交変調器で、このアナログ信号を用
いて、例えば多値QAM 変調波を発生する。The operation of FIG. 2 will be explained below with reference to FIGS. 3 and 4. First, input, for example, I ch, Q
The digital signal of channel is subjected to a predetermined distortion as described later by a digital filter 4, and then converted into an analog signal by a digital/analog converter 11. Then, a quadrature modulator (not shown) uses this analog signal to generate, for example, a multilevel QAM modulated wave.
【0032】この多値QAM 変調波は、送信部2で送
信局部発振器21からの送信局発信号を用いて周波数変
換し、高周波電力増幅器3で電力増幅して外部に送出さ
れるが、一部は受信部51で、内蔵の受信局部発振器5
11 からの受信局発信号を用いて中間周波帯の多値Q
AM 変調波に周波数変換する。This multi-level QAM modulated wave is frequency-converted in the transmitting section 2 using a transmitting station oscillator signal from the transmitting local oscillator 21, power amplified in the high-frequency power amplifier 3, and sent to the outside. is the receiving section 51, and the built-in receiving local oscillator 5
11 using the receiving station oscillation signal from the intermediate frequency band.
Frequency conversion to AM modulated wave.
【0033】なお、第3の本発明は、例えば内部に設け
たPLL 回路(図示せず) を用いることにより、受
信局発信号を送信局発信号に同期させる。さて、復調部
52は入力した中間周波帯の多値QAM 変調波を復調
して復調信号を取り出すが、このうち極性信号と誤差信
号を制御部6に加える。[0033] In the third aspect of the present invention, the receiving station oscillation signal is synchronized with the transmitting station oscillation signal by using, for example, an internally provided PLL circuit (not shown). Now, the demodulator 52 demodulates the input multi-level QAM modulated wave in the intermediate frequency band and extracts a demodulated signal, of which a polar signal and an error signal are added to the controller 6.
【0034】そこで、図3に示す制御部は、相関器61
で極性信号と誤差信号との相関をとり、積分器62は相
関結果を所定時間の間、アップダウンカウンタ( 図示
せず) にて積分して制御信号としてデイジタルフイル
タ4に送出する。Therefore, the control section shown in FIG.
The integrator 62 calculates the correlation between the polarity signal and the error signal, and the integrator 62 integrates the correlation result for a predetermined time using an up/down counter (not shown) and sends it to the digital filter 4 as a control signal.
【0035】デイジタルフイルタ4はI ch, Q
chの同相成分を補償する為の同相タップ部分41,
44と、 I ch →Q ch, Q ch→ I
ch の直交成分を補償する為の直交タップ部分42,
43から構成され、各タップ部分は図4の(A) に
示す様にFF1 〜FF4 で構成されたシフトレジス
タと乗算器M1〜M3と加算器とから構成されている。
なお、シフトレジスタは4段としてある。Digital filter 4 has I ch, Q
In-phase tap portion 41 for compensating the in-phase component of ch.
44, I ch →Q ch, Q ch→ I
orthogonal tap portion 42 for compensating the orthogonal component of ch.
43, and each tap portion is comprised of a shift register composed of FF1 to FF4, multipliers M1 to M3, and an adder, as shown in FIG. 4(A). Note that the shift register has four stages.
【0036】そこで、I chのデータはFF( フリ
ップフロップ) を1つ通過する毎に乗算器で制御信号
と乗算され加算器で加算されるが、センタタップa0
からの各時間毎に符号間干渉が最小となる様に制御信号
が制御される。Therefore, each time the I channel data passes through one FF (flip-flop), it is multiplied by a control signal in a multiplier and added in an adder.
The control signal is controlled so that intersymbol interference is minimized at each time from .
【0037】ここで、図4の(B) に示す様に、FF
1 〜FF3 の出力側に高周波電力増幅器の非線形成
分を補償する様な制御信号の値を書き込んだROM1〜
ROM3を設けておく。そして、電源投入時にはこの書
き込んだ値のデイジタル信号が、乗算器を通して初期値
として加算器に加えられる。これ以降は高周波電力増幅
器の変化分に対して、帰還ループが補償する様になるが
、これによりこのループのダイナミックレンジが広がる
。Here, as shown in FIG. 4(B), the FF
ROM1~ in which the value of the control signal that compensates for the nonlinear component of the high frequency power amplifier is written on the output side of FF1~FF3
ROM3 is provided. Then, when the power is turned on, the digital signal of this written value is added to the adder as an initial value through the multiplier. From this point on, the feedback loop begins to compensate for changes in the high-frequency power amplifier, which widens the dynamic range of this loop.
【0038】なお、ROM1〜ROM3と乗算器M1〜
M3の機能をそれぞれ対応するROM に書き込むこと
により、ROM と乗算器が1つのROM に置き換え
ることが可能である。つまり、本来、図2のデイジタル
/アナログ変換器11から送信部2までは歪は発生しな
い筈であるが、これが歪むと云うことはバックオフ量を
小さくした高周波電力増幅器で発生した非線形歪による
歪が入ってきたものとして、制御部6でデイジタルフイ
ルタの乗算器に印加する制御信号の値を符号間干渉が最
小になる様に制御させる。Note that ROM1 to ROM3 and multipliers M1 to
By writing the functions of M3 into the respective ROMs, it is possible to replace the ROM and the multiplier with one ROM. In other words, originally, no distortion should occur from the digital/analog converter 11 to the transmitter 2 in FIG. is input, the control unit 6 controls the value of the control signal applied to the multiplier of the digital filter so that the intersymbol interference is minimized.
【0039】この時の制御は緩慢でよい。何故ならば、
非線形歪の発生は緩慢であり、また電源変動、温度変動
も緩慢である為である。そこで、復調部, 制御部,
デイジタルフイルタの動作速度も緩慢にすれば( これ
らの部分に供給するクロックを間引く) 、これらの部
分の消費電力が低下する。Control at this time may be slow. because,
This is because nonlinear distortion occurs slowly, and power supply fluctuations and temperature fluctuations also occur slowly. Therefore, the demodulation section, the control section,
If the operating speed of the digital filter is also made slower (by thinning out the clocks supplied to these parts), the power consumption of these parts will be reduced.
【0040】但し、高周波電力増幅器の非線形歪の様な
アナログ的な変動に対しては、主信号のn倍の速度でサ
ンプリング(オーバーサンプリング方式)を行なって該
デイジタルフイルタをフラクショナルな形で動作させ、
主信号はその1/nで間引いて信号を通過させる様に構
成すれば非線形保証をより細かく保証することができる
。However, in response to analog fluctuations such as nonlinear distortion in a high-frequency power amplifier, sampling is performed at n times the speed of the main signal (oversampling method) to operate the digital filter in a fractional manner. ,
If the main signal is thinned out by 1/n and configured to pass the signal, it is possible to more precisely guarantee the nonlinearity.
【0041】[0041]
【発明の効果】以上詳細に説明した様に、本発明によれ
ば、高周波電力増幅器のバックオフ量を小さくできるの
で、高周波電力増幅器の大幅な小形化を図ることができ
ると云う効果がある。As described above in detail, according to the present invention, the amount of backoff of the high frequency power amplifier can be reduced, so that the high frequency power amplifier can be significantly downsized.
【図1】第1〜第3の本発明の原理ブロック図である。FIG. 1 is a principle block diagram of first to third aspects of the present invention.
【図2】第1〜第3の本発明の実施例の要部ブロック図
である。FIG. 2 is a block diagram of main parts of first to third embodiments of the present invention.
【図3】図2の制御部・デイジタルフイルタ構成図の一
例である。FIG. 3 is an example of a configuration diagram of a control unit and digital filter in FIG. 2;
【図4】図3の同相,直交タップ部の構成図の一例で、
(A) は基本的構成図、(B) は本発明の構成図で
ある。[Figure 4] An example of a configuration diagram of the in-phase and quadrature tap sections in Figure 3.
(A) is a basic configuration diagram, and (B) is a configuration diagram of the present invention.
【図5】従来例のブロック図である。FIG. 5 is a block diagram of a conventional example.
【図6】図5中の送信側詳細ブロック図である。FIG. 6 is a detailed block diagram of the transmitting side in FIG. 5;
【図7】高周波電力増幅器動作説明図である。FIG. 7 is an explanatory diagram of high frequency power amplifier operation.
1 変調部
2 送信部3 高周波電力増幅
器 4 デイジタルフイ
ルタ1 Modulation section
2 Transmitter 3 High frequency power amplifier 4 Digital filter
Claims (3)
/アナログ変換器(11)でアナログ信号に変換した後
、該アナログ信号を用いて変調波を生成する変調部(1
) と、内部の送信局部発振器の出力を用いて、入力し
た該変調波の周波数を送信周波数に変換する送信部(2
) と、入力した該送信周波数の変調波を電力増幅して
送出する高周波電力増幅器(3) とを有するデイジタ
ル無線送信装置において、該高周波電力増幅器で発生す
る非線形歪を補償するための補償係数が格納されたRO
Mが付加されたデイジタルフイルタ(4) を該デイジ
タル/アナログ変換器の入力側に設け、該デイジタルフ
イルタが、該デイジタル/アアログ変換器に入力するデ
イジタル信号に、高周波電力増幅器で発生する非線形歪
を補償する歪を予め与えることを特徴とする非線形歪補
償方法。1. A modulator (1) that converts an input digital signal into an analog signal by a digital/analog converter (11) and then generates a modulated wave using the analog signal.
) and a transmitter (2) that converts the frequency of the input modulated wave into a transmit frequency using the output of an internal transmit local oscillator.
) and a high-frequency power amplifier (3) that amplifies the power of an input modulated wave of the transmission frequency and transmits the same, a compensation coefficient for compensating for nonlinear distortion generated in the high-frequency power amplifier is provided. Stored RO
A digital filter (4) to which M is added is provided on the input side of the digital/analog converter, and the digital filter applies nonlinear distortion generated in the high-frequency power amplifier to the digital signal input to the digital/analog converter. A nonlinear distortion compensation method characterized by providing distortion to be compensated in advance.
調波を、内部で発生した受信局発信号を用いて周波数変
換した後、復調信号を取り出す受信・復調部(5) と
該復調信号を利用して制御信号を生成する制御部(6)
とを設け、該制御部は、該高周波電力増幅器の動作条
件の変動によって生ずる符号間干渉が最小となる様に、
該制御信号を用いて該デイジタルフイルタの動作を制御
することを特徴とする請求項1の非線形歪補償方法。2. A receiving/demodulating section (5) that frequency-converts the modulated wave sent out from the high-frequency power amplifier using an internally generated receiving station oscillation signal and then extracts the demodulated signal, and utilizes the demodulated signal. A control unit (6) that generates a control signal by
and the controller is configured to minimize intersymbol interference caused by fluctuations in the operating conditions of the high frequency power amplifier.
2. The nonlinear distortion compensation method according to claim 1, wherein the control signal is used to control the operation of the digital filter.
出力と同期させることを特徴とする請求項2の非線形歪
補償方法。3. The nonlinear distortion compensation method according to claim 2, wherein the receiving station oscillator signal is synchronized with the output of the transmitting local oscillator.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP5511791A JPH04290321A (en) | 1991-03-19 | 1991-03-19 | Nonlinear distortion compensating method |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP5511791A JPH04290321A (en) | 1991-03-19 | 1991-03-19 | Nonlinear distortion compensating method |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH04290321A true JPH04290321A (en) | 1992-10-14 |
Family
ID=12989810
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP5511791A Withdrawn JPH04290321A (en) | 1991-03-19 | 1991-03-19 | Nonlinear distortion compensating method |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH04290321A (en) |
Cited By (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0865352A (en) * | 1994-08-24 | 1996-03-08 | Yuseisho Tsushin Sogo Kenkyusho | Digital modulator |
WO1998023068A1 (en) * | 1996-11-19 | 1998-05-28 | Matsushita Electric Industrial Co., Ltd. | Transmitter |
US5903823A (en) * | 1995-09-19 | 1999-05-11 | Fujitsu Limited | Radio apparatus with distortion compensating function |
US6400774B1 (en) | 1997-12-10 | 2002-06-04 | Matsushita Electric Industrial Co., Ltd. | Nonlinearity-caused distortion compensating system |
US6915118B2 (en) | 2000-06-21 | 2005-07-05 | Matsushita Electric Industrial Co., Ltd. | Linear compensated amplifying equipment |
JP2007116240A (en) * | 2005-10-18 | 2007-05-10 | Anritsu Corp | Digital modulation signal generating apparatus |
JP2008532381A (en) * | 2005-02-24 | 2008-08-14 | テレフオンアクチーボラゲット エル エム エリクソン(パブル) | IQ modulator predistortion |
-
1991
- 1991-03-19 JP JP5511791A patent/JPH04290321A/en not_active Withdrawn
Cited By (11)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0865352A (en) * | 1994-08-24 | 1996-03-08 | Yuseisho Tsushin Sogo Kenkyusho | Digital modulator |
US5903823A (en) * | 1995-09-19 | 1999-05-11 | Fujitsu Limited | Radio apparatus with distortion compensating function |
US6081698A (en) * | 1995-09-19 | 2000-06-27 | Fujitsu Limited | Radio apparatus and offset compensating method |
US6091941A (en) * | 1995-09-19 | 2000-07-18 | Fujitsu Limited | Radio apparatus |
WO1998023068A1 (en) * | 1996-11-19 | 1998-05-28 | Matsushita Electric Industrial Co., Ltd. | Transmitter |
US6418173B1 (en) | 1996-11-19 | 2002-07-09 | Matsushita Electric Industrial Co., Ltd. | Transmission Apparatus |
US6400774B1 (en) | 1997-12-10 | 2002-06-04 | Matsushita Electric Industrial Co., Ltd. | Nonlinearity-caused distortion compensating system |
US6915118B2 (en) | 2000-06-21 | 2005-07-05 | Matsushita Electric Industrial Co., Ltd. | Linear compensated amplifying equipment |
JP2008532381A (en) * | 2005-02-24 | 2008-08-14 | テレフオンアクチーボラゲット エル エム エリクソン(パブル) | IQ modulator predistortion |
JP4653183B2 (en) * | 2005-02-24 | 2011-03-16 | テレフオンアクチーボラゲット エル エム エリクソン(パブル) | IQ modulator predistortion |
JP2007116240A (en) * | 2005-10-18 | 2007-05-10 | Anritsu Corp | Digital modulation signal generating apparatus |
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