JPH04172972A - Pwm power converting device - Google Patents
Pwm power converting deviceInfo
- Publication number
- JPH04172972A JPH04172972A JP2275984A JP27598490A JPH04172972A JP H04172972 A JPH04172972 A JP H04172972A JP 2275984 A JP2275984 A JP 2275984A JP 27598490 A JP27598490 A JP 27598490A JP H04172972 A JPH04172972 A JP H04172972A
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- Prior art keywords
- frequency
- wave
- sampling
- arithmetic
- time
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000005070 sampling Methods 0.000 claims abstract description 27
- 238000006243 chemical reaction Methods 0.000 claims description 5
- 238000010586 diagram Methods 0.000 description 8
- 230000006698 induction Effects 0.000 description 3
- 230000000694 effects Effects 0.000 description 2
- 230000007274 generation of a signal involved in cell-cell signaling Effects 0.000 description 1
- 238000000034 method Methods 0.000 description 1
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- Inverter Devices (AREA)
Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野１
この発明は、ＰＷＭ電力変換装置に関するもので、特に
電圧歪みの発生防止技術に関するものである。DETAILED DESCRIPTION OF THE INVENTION [Industrial Application Field 1] The present invention relates to a PWM power conversion device, and particularly to a technique for preventing the occurrence of voltage distortion.
［従来の技術１
第５図は例えば特開平１−２７４６６９号公報に示され
た従来のＰＷＭ電力変換装置を示す図である。また、同
図に示す変調口！４ （５）の詳細を第６図に、第６図
における各部の信号波形図を第７図に示す。図において
、（１）は直流電源、（２ａ）〜（２ｆ）は直流電源（
１）に接続され３相の各アームを構成するスー１′ツチ
ング素子、（３ａ）〜（３ｆ）は各スイ・ソチング素子
に逆並列接続されたダイオード、（４）は誘導電導機な
どの負荷、（５）は変調回路、（６）は搬送波（三角波
）発生器、（７）は変調制御信号発生器、（７ａ）〜（
７ｆ）はそれぞれ位相が互いに１２０°ずれた正弦波変
調制御信号（交流電圧指令信号）、（８）は比較器であ
る。[Prior Art 1] FIG. 5 is a diagram showing a conventional PWM power conversion device disclosed in, for example, Japanese Patent Laid-Open No. 1-274669. Also, the modulation port shown in the same figure! 4. Details of (5) are shown in FIG. 6, and signal waveform diagrams of various parts in FIG. 6 are shown in FIG. In the figure, (1) is a DC power supply, (2a) to (2f) are DC power supplies (
1) is connected to the switching element that constitutes each arm of the three phases, (3a) to (3f) are diodes connected in anti-parallel to each switching element, and (4) is a load such as an induction machine. , (5) is a modulation circuit, (6) is a carrier wave (triangular wave) generator, (7) is a modulation control signal generator, (7a) to (
7f) are sinusoidal modulation control signals (AC voltage command signals) whose phases are shifted by 120° from each other, and (8) is a comparator.
上記構成においては、変調回路（５）で作成された変調
信号（５ａ）〜（５Ｃ）とそれらの各反転信号（５ｄ）
〜（５ｆ）とにより、各アームを構成するスイッチング
素子（３ａ）〜（３ｆ）をオン、オフ制御して負荷（４
）に供給される負荷電圧（インバータ出力電圧）を制御
する。In the above configuration, the modulation signals (5a) to (5C) created by the modulation circuit (5) and their respective inverted signals (5d)
to (5f), the switching elements (3a) to (3f) constituting each arm are controlled on and off, and the load (4
) to control the load voltage (inverter output voltage) supplied to the inverter.
また、搬送波（三角波） （６ａ）と各正弦波変調制御
信号（７ａ）〜（７ｃ）と比較器（８）の出力（８ａ）
〜（８Ｃ）の波形は第７図に示す通りであり、ここで、
正弦波変調制御信号（７ａ）〜（７ｃ）はサンプリング
ディジタル制御演算を行うため、第８図に示された演算
周期の階段波形となる。In addition, the carrier wave (triangular wave) (6a), each sine wave modulation control signal (7a) to (7c), and the output of the comparator (8) (8a)
The waveforms of ~(8C) are as shown in Figure 7, where:
Since the sine wave modulation control signals (7a) to (7c) undergo sampling digital control calculations, they have a step waveform with the calculation period shown in FIG.
［発明が解決しようとする課題］
従来のＰＷＭ電力変換装置は以上のように構成されてお
り、誘導電動機などの負荷（４）の無騒音化を図るため
には、ＩＧＢＴなどの高速スイッチング素子を用い、ま
た、スイッチング周波数を１５〜２０ｋＨｚに高周波化
するのに当然搬送波（三角波）（６ａ）の周波数を１５
〜２０ｋＨｚに高周波化し、さらに、サンプリングディ
ジタル制御演算の演算周期を同様に搬送波（６ａ）の周
期まで高速化する必要があった。ただ、これまではディ
ジクル制御演算を行うマイクロプロセッサの能力にも制
限され、搬送波（三角波） （６ａ）の周波数より低い
周波数でしかディジタル制御演算を行うことができない
ため、正弦波変調信号（７ａ）〜（７ｃ）は搬送波（三
角波） （６ａ）の周期より低い階段波形となり、ＰＷ
Ｍ変調後、変調信号は低周波の電圧歪みを含み完全無騒
音化を図れないという問題点があった。[Problem to be solved by the invention] The conventional PWM power converter is configured as described above, and in order to make the load (4) such as an induction motor noiseless, it is necessary to use a high-speed switching element such as an IGBT. In addition, in order to increase the switching frequency to 15 to 20kHz, it is natural to increase the frequency of the carrier wave (triangular wave) (6a) to 15kHz.
It was necessary to increase the frequency to ~20 kHz and also to increase the calculation period of the sampling digital control calculation to the period of the carrier wave (6a). However, until now, the ability of the microprocessor to perform digital control calculations was limited, and digital control calculations could only be performed at frequencies lower than the frequency of the carrier wave (triangular wave) (6a). ~(7c) is a step waveform with a period lower than that of the carrier wave (triangular wave) (6a), and PW
After M modulation, the modulation signal contains low-frequency voltage distortion, so there is a problem that complete noiselessness cannot be achieved.
この発明は上記のような問題点を解消するためになされ
たもので、低周波の電圧歪みを低減する高周波ＰＷＭ電
力変換装置を得ることを目的とする。The present invention has been made to solve the above-mentioned problems, and an object of the present invention is to obtain a high frequency PWM power conversion device that reduces low frequency voltage distortion.
［課題を解決するための手段］
この発明に係るＰＷＭ電力変換装置は、サンプリング制
御演算で出力される交流電圧指令の変調波信号と上記サ
ンプリング制御演算のサンプリング周波数より高い周波
数の搬送波信号とを比較して得られるパルス幅変調信号
により制御されるＰ Ｗ Ｍ電力変換装置において、上
記交流電圧指令信号の前回演算値と今回演算値の線形補
間を行いその値を変調波信号として補正する線形補間手
段を備えたものである。[Means for Solving the Problems] A PWM power converter according to the present invention compares a modulated wave signal of an AC voltage command outputted by sampling control calculation with a carrier wave signal having a frequency higher than the sampling frequency of the sampling control calculation. In the PWM power converter controlled by the pulse width modulation signal obtained by the above, linear interpolation means performs linear interpolation between the previously calculated value and the currently calculated value of the AC voltage command signal, and corrects the resulting value as a modulated wave signal. It is equipped with the following.
［作用］
この発明における線形補間手段は、サンプリング制御演
算の演算周期の階段波形を線形補間することにより、サ
ンプリング制御演算のサンプリング周波数に起因する搬
送波（三角波）の周波数より低い周波数の電圧歪みを＠
滅する。[Operation] The linear interpolation means in the present invention linearly interpolates the step waveform of the calculation period of the sampling control calculation, thereby eliminating voltage distortion at a frequency lower than the frequency of the carrier wave (triangular wave) caused by the sampling frequency of the sampling control calculation.
perish.
［実施例］
以下、この発明の一実施例を図について説明する。第５
図及び第６図と同一部分は同一番号を付して示す第１図
及び第２図において、新たな構成としての（１０）はサ
ンプリング制御演算で出力される交流電圧指令信号の前
回演算値と今回演算値の線形補間を行う線形補間回路で
、サンプリング制御演算の演算周期の階段波形を線形補
間することにより、サンプリング制御演算のサンプリン
グ周波数に起因する搬送波（三角波）の周波数より低い
周波数の電圧歪みを低減するようになされている。[Example] Hereinafter, an example of the present invention will be described with reference to the drawings. Fifth
In FIGS. 1 and 2, parts that are the same as those in FIGS. 1 and 6 are given the same numbers. In FIGS. This time, the linear interpolation circuit that performs linear interpolation of the calculated value linearly interpolates the staircase waveform of the calculation cycle of the sampling control calculation, resulting in voltage distortion at a frequency lower than the frequency of the carrier wave (triangular wave) caused by the sampling frequency of the sampling control calculation. It is designed to reduce the
次に動作について上記線形補間回路（１０）の動作フロ
ーチャートを示す第３図に従い説明する。まず、今回演
算の正弦波変調制御信号と前回演算の正弦波変調制御信
号の差分を算出する（Ｓｌ）。次のステップＳ２でその
差分に対し、搬送波（三角波）周波数とディジタル制御
演算のサンプリング周波数の比で除算する。次のステッ
プＳ３では今回演算の正弦波変調制御信号と前回演算の
正弦波変調制御信号の平均値から差分の展を減算し初期
値を算出する。以上より搬送波（三角波）周波数毎にそ
の値を初期値に加算し変調回路（５）の比較器（８）に
出力する（５４〜Ｓ６）。これにより正弦波変調制御信
号（７ａ）と線形補間回路の出力ｆｌＯａ） と搬送波
（三角波） （６ａｌの波形は例えば第４図に示すもの
となる。Next, the operation will be explained with reference to FIG. 3, which shows an operation flowchart of the linear interpolation circuit (10). First, the difference between the sine wave modulation control signal of the current calculation and the sine wave modulation control signal of the previous calculation is calculated (Sl). In the next step S2, the difference is divided by the ratio of the carrier wave (triangular wave) frequency and the sampling frequency of the digital control calculation. In the next step S3, an initial value is calculated by subtracting the expansion of the difference from the average value of the sine wave modulation control signal of the current calculation and the sine wave modulation control signal of the previous calculation. As described above, the value is added to the initial value for each carrier wave (triangular wave) frequency and output to the comparator (8) of the modulation circuit (5) (54 to S6). As a result, the waveforms of the sine wave modulation control signal (7a), the output flOa of the linear interpolation circuit, and the carrier wave (triangular wave) (6al) become as shown in FIG. 4, for example.
なお、正弦波変調制御信号ｆ７ｂ］、 （７ｂｌにつ
いても同様であり、その後は従来例と同様な動作が実行
される。The same applies to the sine wave modulation control signals f7b] and (7bl, and thereafter the same operation as in the conventional example is performed.
従って、上記実施例によれば、サンプリング制御演算の
演算周期の階段波形を線形補間することにより、サンプ
リング制御演算のサンプリング周波数に起因する搬送波
（三角波）の周波数より低い周波数の電圧歪みを低減す
ることができる。Therefore, according to the above embodiment, by linearly interpolating the step waveform of the calculation period of the sampling control calculation, voltage distortion at a frequency lower than the frequency of the carrier wave (triangular wave) caused by the sampling frequency of the sampling control calculation can be reduced. I can do it.
［発明の効果〕
以上のように、この発明によれば、線形補間手段は、サ
ンプリング制御演算で出力される交流電圧指令信号の前
回演算値と今回演算値の線形補間を行い、その値を変調
波信号として別途人力されるサンプリング制御演算のサ
ンプリング周波数より高い周波数の搬送波信号とを比較
し、これにより得られるパルス幅変調信号を用いてＰＷ
Ｍ制御するようにしたため、サンプリング制御演算のサ
ンプリング周波数に起因する搬送波（三角波）の周波数
より低い周波数の電圧歪みは低減され、誘導電動機など
の負荷が無騒音化され、騒音フィルタ等が不要になると
いう効果がある。[Effects of the Invention] As described above, according to the present invention, the linear interpolation means performs linear interpolation between the previously calculated value and the currently calculated value of the AC voltage command signal output in the sampling control calculation, and modulates the value. The PW signal is compared with a carrier wave signal of a higher frequency than the sampling frequency of the sampling control calculation, which is manually performed separately, as a wave signal, and the resulting pulse width modulation signal is used to perform PW.
M control reduces voltage distortion at frequencies lower than the frequency of the carrier wave (triangular wave) caused by the sampling frequency of the sampling control calculation, making loads such as induction motors noiseless and eliminating the need for noise filters, etc. There is an effect.
第１図と第２図はこの発明の一実施例を示すＰＷＭ電力
変換装置のブロック図、第３図はこの発明の一実施例の
動作を示すフローチャート、第４図は第２図における各
部の信号波形図、第５図と第６図は従来のＰＷＭ電力変
換装置と第５図における変調回路の詳細を示すブロック
図、第７図は第６図における各部の信号波形図、第８図
は第７図の信号波形の拡大図である。
（５）；変調回路
（６）：搬送波（三角波）発生器
（７）：変調制御信号発生器
（８）：比較器
（１０） ：線形補間回路
尚、各図中、同一符号は同−又は相当部分を示６搬送１
ｐ！発生話
７ 変調制御ＩＩ信信号発生
日：比較器
第２図
第 ３ 図
第５図
第６図
Ｃ
第７図
第８図1 and 2 are block diagrams of a PWM power conversion device showing one embodiment of the present invention, FIG. 3 is a flowchart showing the operation of one embodiment of the present invention, and FIG. 4 is a block diagram of each part in FIG. 2. Signal waveform diagrams, Figures 5 and 6 are block diagrams showing details of the conventional PWM power converter and the modulation circuit in Figure 5, Figure 7 is a signal waveform diagram of each part in Figure 6, and Figure 8 is a block diagram showing details of the modulation circuit in Figure 5. 8 is an enlarged view of the signal waveform of FIG. 7. FIG. (5); Modulation circuit (6): Carrier wave (triangular wave) generator (7): Modulation control signal generator (8): Comparator (10): Linear interpolation circuit Note that the same symbols in each figure indicate the same - or Showing the corresponding part 6 Transport 1
p! Occurrence story 7 Modulation control II signal generation date: Comparator Fig. 2 Fig. 3 Fig. 5 Fig. 6 C Fig. 7 Fig. 8
Claims (1)
波信号と上記サンプリング制御演算のサンプリング周波
数より高い周波数の搬送波信号とを比較して得られるパ
ルス幅変調信号により制御されるＰＷＭ電力変換装置に
おいて、上記交流電圧指令信号の前回演算値と今回演算
値の線形補間を行いその値を変調波信号として補正する
線形補間手段を備えたことを特徴とするＰＷＭ電力変換
装置。In the PWM power converter controlled by a pulse width modulation signal obtained by comparing a modulated wave signal of an AC voltage command outputted by the sampling control calculation and a carrier wave signal of a frequency higher than the sampling frequency of the sampling control calculation, A PWM power conversion device comprising linear interpolation means for performing linear interpolation between a previously calculated value and a currently calculated value of an AC voltage command signal and correcting the resulting value as a modulated wave signal.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2275984A JP2645176B2 (en) | 1990-10-15 | 1990-10-15 | PWM power converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2275984A JP2645176B2 (en) | 1990-10-15 | 1990-10-15 | PWM power converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH04172972A true JPH04172972A (en) | 1992-06-19 |
| JP2645176B2 JP2645176B2 (en) | 1997-08-25 |
Family
ID=17563158
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2275984A Expired - Fee Related JP2645176B2 (en) | 1990-10-15 | 1990-10-15 | PWM power converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2645176B2 (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005034327A1 (en) * | 2003-09-30 | 2005-04-14 | Mitsubishi Denki Kabushiki Kaisha | Inverter apparatus |
| JP2007124858A (en) * | 2005-10-31 | 2007-05-17 | Yaskawa Electric Corp | Motor control device and its control method |
| JP2012110087A (en) * | 2010-11-16 | 2012-06-07 | Daikin Ind Ltd | Control method of power converter and power converter |
| CN112072943A (en) * | 2019-11-27 | 2020-12-11 | 中国船舶重工集团公司第七一九研究所 | H-bridge inverter power supply PWM modulation method for eliminating odd-order switch harmonic waves |
-
1990
- 1990-10-15 JP JP2275984A patent/JP2645176B2/en not_active Expired - Fee Related
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2005034327A1 (en) * | 2003-09-30 | 2005-04-14 | Mitsubishi Denki Kabushiki Kaisha | Inverter apparatus |
| GB2423198A (en) * | 2003-09-30 | 2006-08-16 | Misubishi Denki Kabushiki Kais | Inverter Apparatus |
| GB2423198B (en) * | 2003-09-30 | 2006-12-13 | Misubishi Denki Kabushiki Kais | Inverter Device |
| US7436144B2 (en) | 2003-09-30 | 2008-10-14 | Mitsubishi Denki Kabushiki Kaisha | Inverter apparatus |
| JP2007124858A (en) * | 2005-10-31 | 2007-05-17 | Yaskawa Electric Corp | Motor control device and its control method |
| JP2012110087A (en) * | 2010-11-16 | 2012-06-07 | Daikin Ind Ltd | Control method of power converter and power converter |
| CN112072943A (en) * | 2019-11-27 | 2020-12-11 | 中国船舶重工集团公司第七一九研究所 | H-bridge inverter power supply PWM modulation method for eliminating odd-order switch harmonic waves |
| CN112072943B (en) * | 2019-11-27 | 2022-04-12 | 中国船舶重工集团公司第七一九研究所 | H-bridge inverter power supply PWM modulation method for eliminating odd-order switch harmonic waves |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2645176B2 (en) | 1997-08-25 |
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| Date | Code | Title | Description |
|---|---|---|---|
| LAPS | Cancellation because of no payment of annual fees |