JPH0347762B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to a tuner that can be used in radio, television transmitters and receivers, and other communication equipment in general.

Conventional configuration and its problems In recent years, the number of radio and television broadcast waves and communication waves of communication devices has increased, and the performance of the tuner that selects the frequency of the radio waves that you want to receive has a high level of stability. and reliability is required. On the other hand, reducing the manufacturing cost of receivers and transmitters that install tuners and communication equipment is also a major issue, and it is especially necessary to develop radical new technology for tuning circuit components in the high frequency section, which is difficult to rationalize. has been done.

A conventional tuner will be described below with reference to the drawings. Figure 1 shows a basic tuning circuit, with 1
is an inductor, and 2 is a capacitor. and,
A tuner composed of a parallel resonant circuit 3 composed of an inductor and a capacitor 2 has conventionally been realized with a configuration of components as shown in FIG. 2 or 3. That is, as shown in FIG. 2, separate components, an inductor component 4 and a capacitor component 5, are connected by circuit conductors 6 and 7 to form a tuner. As another method as shown in FIG. 3, a planar inductor 9 is installed on the surface of a plate-shaped dielectric 8, and a capacitor 1 consisting of opposing electrodes 10 and 11 is formed.
2 were installed, each with a separate inductor 9 and capacitor 12 connected by circuit conductors 13 and 14 to form a tuner.

However, in the above configuration, as shown in Figure 2, the inductor component 4 is large in size compared to other components, and in particular, the height dimension is very large, so it is difficult to make the device smaller and thinner. was hindering the realization of Furthermore, the setting position of the ferrite core inserted into the coil of the inductor component fluctuates due to mechanical vibration, and as a result, the tuning frequency fluctuates considerably. Furthermore, the inductance is unstable due to the large temperature dependence of the magnetic permittivity μ in the ferrite core, which also causes the tuning frequency to fluctuate greatly. At the same time, the tuning Q was also influenced and fluctuated greatly. Furthermore, in order to stably maintain the tuning frequency at the set target value, each component must be installed at a predetermined setting position with high precision, and it is difficult to ensure installation accuracy, especially when mass-producing a high frequency tuner. As a result, the tuning frequency deviates greatly from the set target value, and it is impossible to keep it within a constant value, which poses a problem in mass production.

The device shown in FIG. 3 occupies a large area due to the inductor and capacitor, which hinders the miniaturization of the device. Furthermore, each component requires at least three functional electrodes: an inductor electrode and a counter electrode that forms a capacitor, which requires the use of a large amount of electrode material that has high conductivity and is therefore expensive. This increases the manufacturing cost of the tuner and makes it impossible to save materials.

A common problem with those shown in Figures 2 and 3 is that the inductor and capacitor are each formed as separate components, and each has a long path of circuit conductor to the installed component. configured to be connected. As a result, many unnecessary lead inductors and stray capacitors are generated, which makes the operation of the tuner unstable and makes it difficult to realize the initial design goals.
Therefore, a lot of time was wasted on design work including modifications. In addition, since each tuner is a collective circuit of separate components with an independent minimum functional unit,
Existing technical concepts have not been able to reduce the number of parts and rationalize manufacturing.

This has resulted in problems such as a limit to the cost reduction of the tuner.

Purpose of the Invention The purpose of the present invention is to realize a thin tuner that integrates a variable inductor component including a secondary coil and a variable capacitor component with a simple configuration, and to make the form of the tuner ultra-thin and compact. Tuning is stable even against mechanical vibrations, and the temperature dependence of the tuning frequency is small.
It is an object of the present invention to provide a tuner which is stable at high frequencies by eliminating the adverse effects of connection leads of a tuning circuit, and which enables streamlining of manufacturing processes by reducing the number of parts.

Structure of the Invention The tuner of the present invention has electrodes arranged opposite to each other with a dielectric interposed therebetween, and the ground terminal of each sub-electrode relative to the main electrode is placed in the opposite direction to the ground terminal of the main electrode, and in the same direction. By doing so, and by not setting either terminal as the ground terminal, the variable capacitor and the secondary coil can be arbitrarily selected and formed. In the operation of the tuner, the main electrode acts as an inductor, and the sub-electrode, whose ground terminal is set in the opposite direction to the main electrode, faces the main electrode to form a distributed constant circuit with an open tip. By setting the equivalent length to less than λ/4 length of the operating frequency wavelength, a capacitor is realized by the negative reactance generated at the end of the distributed constant circuit, and it is made to act in parallel with the inductor by the main electrode. On the other hand, either the ground terminal is set in the same direction as the main electrode, or the sub-electrode, in which neither terminal is set as the ground terminal, acts as a secondary coil.

DESCRIPTION OF EMBODIMENTS The implementation of the tuner of the present invention will be described below with reference to the drawings.

FIG. 4 shows a configuration diagram of a tuner in an embodiment of the present invention. In FIG. 4, a shows a front view, b shows a side view, and c shows a back view. (Hereafter, 5th
13) In each of the figures, 15 is a dielectric substrate, 16 is an electrode that forms an inductor, and 17 is an electrode that together with the electrode 16 forms a distributed constant circuit and forms a capacitor. 18 and 19 are electrodes forming a secondary coil, respectively. Terminal 20 of electrode 16 is a ground terminal, and terminal 21 is an open terminal. Further, the terminal 22 of the electrode 17 and the terminal 23 of the electrode 18 are ground terminals, and the terminal 22 of the electrode 19 is a ground terminal.
4, 25, 26, and 27 are open terminals. The sides shown in FIG. 3a correspond to the sides shown in FIG. 3c. In addition, electrodes 17, 18,
The installation positional relationship and area distribution of each of the 19 units are arbitrary. (The same applies to FIGS. 5 to 12 hereinafter.) FIG. 4 shows a configuration diagram of a tuner in another embodiment of the present invention. The arrangement of the electrode 29 and the electrodes 30, 31, 32 on the dielectric substrate 28 is reversed on the front and back surfaces compared to the embodiment explained in FIG. The settings are upside down. Terminal 36 of electrode 30 and terminal 35 of electrode 32 are ground terminals, and terminals 37 and 38 of electrode 31 are open terminals. Here, the electrodes forming the capacitor are 32, and the electrodes 30 and 31 forming the secondary coil. (Here, Figures 4 and 5
As shown in the illustrated embodiment, each electrode 16, 2
The opposing electrodes 18, 22, 30, and 32 can be arbitrarily set as capacitor electrodes or secondary coils by setting the ground terminal and open terminal of 9. In other words, electrodes 17 and 32 whose ground terminals are set in the opposite direction to the ground terminals of electrodes 16 and 29 become capacitor electrodes, while electrodes 18 and 30 whose ground terminals are set in the same direction become secondary coil electrodes. .
(The same applies to FIGS. 6 to 12 below.) FIG. 6 shows the configuration of a tuner in another embodiment of the present invention. The installation configuration and terminal mode of the electrode 49 and the electrodes 50, 51, 52 on the dielectric substrate 48 are the same as the embodiment described in FIG. 4, but the electrode 49 and the electrodes 50, 51, 52 partially face each other. 53 and 54 are open terminals of the secondary coil electrode 51.

FIGS. 7 to 9 show configuration diagrams of tuners in other embodiments of the present invention. Electrode 56 and electrode 5 for dielectric substrate 55 in FIG.
Installation configuration and terminal mode of 7, 58, 59, open terminals 60, 61, electrode 63 and electrode 64, 65, 6 for dielectric substrate 62 in FIG.
6, and the open terminals 67 and 68, the installation configuration and terminal mode of the electrode 70 and the electrodes 74, 75, and 76 relative to the dielectric substrate 69 in FIG. Although the embodiment is similar to the embodiment described in the drawings, each electrode has at least one bent portion indicating an arbitrary bending angle and bending direction.

FIG. 10 shows a configuration diagram of a tuner in another embodiment of the present invention. The installation configuration and terminal mode of the electrode 77 and electrodes 78, 79, 80 with respect to the dielectric substrate 76, and the open terminals 81, 82 are the same as in the embodiment described in FIG. 4, but each electrode has a spiral shape. use something

FIG. 11 shows a configuration diagram of a tuner in another embodiment of the present invention. The installation configuration and terminal mode of the electrode 84 and the electrodes 85, 86, 87 on the dielectric substrate 83, and the open terminals 88, 89 are the same as in the embodiment described in FIG.
5, 86, and 87 are arranged so as to partially face each other within a range included in the area of the electrode 84.

FIG. 12 shows a configuration diagram of a tuner in another embodiment of the present invention. The installation configuration and terminal mode of the electrode 91 and the electrodes 92, 93, 94 on the dielectric substrate 90, and the open terminals 95, 96 are the same as in the embodiment described in FIG.
1 is provided inside the dielectric substrate 90 .

Needless to say, Figures 6, 11, and 1
It goes without saying that each electrode in the embodiment explained in FIG. 2 may have the electrode shape of the embodiment explained in FIGS. 7 to 10.

Next, the principle of operation of the tuner of the present invention will be explained.

13a to 13e are equivalent circuits for explaining the operation of the tuner of the present invention. In FIG. 13a, the transmission line electrodes 97, 9 each have an electrical length l and have their ground terminals set in opposite directions.
Assume that a signal source 99 that generates a voltage e is connected to a transmission line electrode 97 to supply a signal to the transmission line formed by 8. As a result, a traveling wave voltage e _A is excited at the open terminal at the tip of the transmission line electrode 97 . On the other hand, since the transmission line electrode 98 is disposed close to the above-mentioned transmission line electrode 97 and facing each other or in parallel, a voltage is induced by mutual induction. The transmission line electrode 9
Let e _B be the traveling wave voltage induced in the open terminal at the tip of 8.

Since the respective ground terminals of the transmission line electrodes 97 and 98 are set in opposite directions, the induced traveling wave voltage e _B has an opposite phase to the excited traveling wave voltage e _A. Since the ends of the transmission paths of the respective traveling wave voltages e _A and e _B are in an open state, voltage standing waves are formed in the transmission path formed by the transmission path electrodes 97 and 71 . Here, if the voltage distribution coefficient indicating the distribution mode of the voltage standing wave at the transmission line electrode 97 is represented by K, then the voltage distribution coefficient at the transmission line electrode 98 can be expressed as (1-K).

Therefore, next, we will discuss the potential difference V generated at any opposing portions of the transmission line electrodes 97 and 98.
can be expressed as V=Ke _A −(1−K)e _B (1). Here, assuming that the respective transmission line electrodes 70 and 71 have the same electrical length l, e _B = -e _A ...(2), so that the potential difference V in the first equation is V = Ke _A + (1 -K) e _A = e _A ...(3). That is, a potential difference V can be generated in all parts where the transmission line electrodes 97 and 98 face each other.

Here, it is assumed that the transmission line electrodes 97 and 98 have an electrode width W (the thickness of the electrode is thin), and that the transmission line electrodes 97 and 98 have a width W per unit length of the transmission line at a distance d through a dielectric material having a dielectric constant ε _S. forming capacitor
C _O is C _O =Q/V=Q/e _A ……(4) Q=ε _O ε _S W・V/d=ε _O ε _S W・e _A /d ……(5) Therefore, C _O = ε _O ε _S W/d ...(6).

Therefore, the transmission line shown in FIG. 13a becomes a transmission line including a distributed capacitor 100 of C _O determined by the formula 6 per unit length as shown in FIG. 13b. As shown in FIG. 13c, this transmission line consists of transmission line electrodes 102 and 10 excited in a balanced mode by a balanced signal pole 101 having a balanced voltage e'.
This is equivalent to a balanced mode transmission line formed by 3. Needless to say, its electrical length is the same as the electrical length l shown in FIG. 13a. Furthermore, as shown in FIG. 13d, this balanced mode transmission line is composed of comprehensive distributed inductors 104 and 105 and a distributed capacitor 100, which are composed of a distributed inductor component of the transmission line and a lumped inductor component generated by the bent shape of the transmission line, respectively. It can be equivalently expressed as a distributed constant circuit.

Next, the relationship between the formation of the distributed capacitor 100 and the electrical length L of the transmission path will be explained.
The characteristic impedance Z _O per unit length in a balanced mode transmission line as shown in Figure 14a is
It can be expressed by the equivalent circuit shown in Figure b. Its characteristic impedance Z _O is generally becomes. If the transmission path is lossless, then becomes. This assumption can be applied to many of the embodiments of the tuner of the present invention, and to simplify the explanation, the characteristic impedance Z _O
Use. The capacitance C _O in the eighth equation is the same as the capacitance C _O per unit in the transmission line found in the sixth equation. In other words, the characteristic impedance per unit length in the transmission line
Z _O is a function of the capacitance C _O , which is also a function of the permittivity ε _S of the dielectric material responsible for the capacitance C _O , the width W of the transmission line electrodes and the installation spacing d of the respective transmission line electrodes.

As described above, the characteristic impedance per unit length in the transmission line is Z _O , the electrical length is l, and the equivalent reactance X generated at the terminal of the transmission line with the end open is X = -Z _O cotθ can be expressed as (9). Here, θ=2πl/λ...(10), and especially in the case of θ=0~π/2 θ=π~3/4π...(11), the equivalent reactance X is X≦0...(12) becomes. In other words, the equivalent reactance at the terminal of the transmission line can be the capacitive reactance. Therefore, depending on the electrical length l of the transmission path, θ becomes the
When formula 11 is satisfied, for example, a capacitor can be formed by setting the electrical length l to λ/4 or less. And the capacitance C of the capacitor that can be formed is As expressed by , any capacitance C can be realized by changing θ, that is, by setting the electrical length l of the transmission path.

FIG. 15 is a diagram illustrating the operation mode of the transmission line explained in Equations 9 to 13 above. FIG. 15 shows how the equivalent reactance X generated at the terminal changes in accordance with the change in the electrical length l of the transmission line with its tip in an open state. As is clear from Fig. 15, the electrical length l of the transmission line is λ/4 or less or λ/2 ~
In cases such as at 4λ/3, it is possible to form a negative terminal reactance, ie equivalently to form a capacitor.
Further, by arbitrarily setting the electrical length l of the transmission path under conditions that generate negative terminal reactance, it is possible to realize the capacitance C to an arbitrary value.

The capacitance C formed in this way
can be equivalently replaced as the lumped constant capacitor 106 shown in FIG. 13d. The inductor formed by combining the distributed inductor component existing in the transmission line and the lumped inductor component generated by bending the transmission line can be equivalently replaced as the lumped constant inductor 107. If the ground terminal is shown in common in FIG. 13d, it will eventually become equivalent to a parallel resonant circuit consisting of a lumped constant capacitor 106 and a lumped constant inductor 107, as shown in FIG. 13e, and the tuned can be realized.

Although the configuration and operation described above realize the tuner of the present invention, the configuration of the tuner of the present invention and its operating principle are completely different from those of conventional tuners.
Therefore, in order to prove that the tuner according to the present invention is completely different from conventional tuners or those having other configurations even if they use the same transmission line as the tuner of the present invention. To,
The construction and operation of conventional tuners or tuners with other transmission line configurations will now be described and contrasted. This clarifies the difference from the tuner according to the present invention and also clarifies the novelty of the tuner according to the present invention.

FIG. 16 shows the operation when the transmission line electrode is made of the same material as used in the tuner of the present invention, but the difference is that the ground terminals are set in the same direction. be. In FIG. 16a, transmission line electrodes 108 and 109
It is assumed that an open-ended transmission line consisting of the following is driven by a signal source 110 that generates a voltage e. As a result, a standing wave voltage e _A is excited at the open terminal at the tip of the transmission line electrode 108, and a standing wave voltage e _B is excited at the open terminal at the tip of the transmission line electrode 109, which is installed opposite or in parallel. shall be induced. Here, since the ground terminals of the transmission line electrodes 108 and 109 are set in the same direction, the standing wave voltages e _A and e _B are in phase with each other. Therefore, the respective voltage distribution coefficients at transmission line electrodes 108 and 109 will have the same K. As a result, the potential difference V at any part where the transmission line electrodes face each other becomes V=Ke _A -Ke _B (14). Here, assuming that the electrical lengths of the transmission line electrodes 108 and 109 are the same, e _A = e _B ... (15), so the potential difference V in Equation 14 is V = Ke _A - Ke _A = O...(16). In other words, no potential difference occurs in any part of the transmission path. FIG. 16b shows a configuration in which the signal source 110 in FIG. 16a is replaced at the end of the transmission line, and is equivalent to installing an unbalanced signal source 111 that generates voltage e'. In this equivalent circuit, there are only parallel transmission lines that have potential differences between them. In other words, it is clear that this is equivalent to the case where only one transmission line electrode 112 exists, as shown in FIG. 16c. Then, by equivalently replacing the signal source 110 and the ground terminal with the original circuit shown in FIG. 16a, the circuit shown in FIG. 16d is obtained. In other words, only an equivalent lumped constant inductor 113 is formed, which is composed of a distributed inductor component of the transmission line and a lumped inductor component generated by the curved shape of the transmission line. As is clear from the above, since a capacitor cannot be formed in parallel with an inductor, the intended parallel resonant circuit tuner cannot be realized.

Figure 17 shows a general microstrip line formed with the same transmission line electrode as in the tuner of the present invention as one side of the transmission line electrode, but the electrode facing the transmission line electrode has a sufficiently wide ground. This shows the operation when the curved points are different. In FIG. 17a, a transmission line electrode 114 faces a sufficiently wide ground electrode 115, is driven by a signal source 116 that generates a voltage e, and a standing wave voltage e _A is excited at the open terminal at the tip of the transmission line. Let K be the voltage distribution coefficient. On the other hand, assuming that a standing wave voltage e _B having a voltage distribution coefficient K is virtually generated at the ground electrode 115, the transmission line electrode 114 and the ground electrode 11
The potential difference V at any part where 5 faces each other is expressed as: V=Ke _A −Ke _B (17). However, the standing wave voltage e _B at the ground electrode 115 is uniformly at the ground potential (zero potential), and e _B =O (18). Therefore, there is no voltage distribution coefficient in the ground electrode 115 either. As a result, the potential difference V becomes V=Ke _A (19). This makes it possible to form a distributed capacitor between the transmission line electrode 114 and the ground electrode 115. However, the transmission line electrode 11
4 is close to and opposite to the ground electrode 115, so the two ends of the transmission line electrode 114 are almost in a shot state due to mutual induction. Therefore, the Q performance of the inductor component in the transmission line electrode 114 is significantly degraded. That is, this microstrip line has an equivalent loss resistance of 1 as shown in Figure 17b.
A parallel resonant circuit is formed of a lumped constant inductor 118 and a lumped constant capacitor 119, respectively. Here, since the equivalent loss resistance 117 actually has a considerably large resistance value, the loss in the resonant circuit becomes very large.
Therefore, it is obvious that only a tuner with very low Q performance can be realized, and is not suitable for practical use.

FIG. 18 shows the circuit configuration of a λ/4 resonator, which is most commonly used in the past. This shows that the tuner is completely different from the tuner of 1st
In FIG. 8, the balanced mode transmission line electrodes 120 and 121 have an electrical length l set equal to λ/4 at the resonance frequency, and have shortened ends. and a balanced signal source 1 that generates a voltage e
22, each transmission line electrode is driven in a balanced mode. The ground terminal is set at the neutral point of the balanced signal source 122, and does not specifically ground any terminal in the transmission line electrode. In this case, the equivalent terminal reactance X generated at the terminal of the transmission line is as follows, where Z _O is the characteristic impedance of the transmission line: X=Z _O tanθ (20). Here, the characteristic impedance Z _O is the same as that shown in the 8th equation, and θ is also the same as that shown in the 10th equation. In this resonator, the electrical length l of the transmission path is l=λ/4...(21), so θ=π/2...(22). Therefore, _the terminal reactance X in Equation 20 is as follows: However, when comparing the configuration of this λ/4 resonator with the configuration of the tuner of the present invention, first of all, regarding the terminal conditions of the transmission line, the tuner of the present invention is in an open state, whereas the conventional λ/4 resonator has an open state. It is clear that the /4 resonator is in a short state and therefore has a completely different configuration in terms of terminal conditions. Furthermore, regarding the setting of the electrical length l of the transmission line, in the tuner of the present invention, it is set to λ/4 or less of the tuning frequency, and in practice it is set to a very short value of about λ/16. However, the conventional λ/4
In the resonator, the resonant frequency is strictly set to λ/4, and it is therefore clear that the configuration is fundamentally different in setting the electrical length l of the transmission path. Also, the electrical length l of the transmission path in the configuration
Due to the difference in λ/
In the case of four resonators, it is necessary to provide a very long transmission path, which has the disadvantage of increasing the size. Conventional λ/
4.In order to downsize the resonator, there are some cases in which the length of the transmission path is shortened by interposing a dielectric material with a very high permittivity, but the dielectric material with a high permittivity used for this purpose generally has a dielectric loss tanδ. It is very large, and therefore has the disadvantage that the Q performance as a resonator is significantly reduced. Furthermore, the temperature dependence of the dielectric constant of a dielectric material having a high dielectric constant is generally large, and therefore there is also the disadvantage that it is difficult to ensure the stability of the resonant frequency.

Next, in order to clarify the superiority of the performance of the tuner of the present invention, experimental results will be shown and explained in comparison with the performance of a conventional tuner. FIG. 19 is a graph showing the experimental results of measuring the temperature dependence of the tuning frequency. FIG. 20 is a graph showing the experimental results of measuring the temperature dependence characteristics of resonance Q. In FIGS. 19 and 20, characteristic A is the temperature dependence of the tuner according to the present invention, and is an experimental result when an alumina ceramic material or a resin printed circuit board is used as the dielectric material. On the other hand, characteristic B is as shown in FIG.
This is the temperature-dependent characteristic of the tuner most commonly used in the past. From these experimental results, it is clear that in the tuner of the present invention, even if it is constructed using a general dielectric material, its tuning frequency is extremely stable, and furthermore, the resonance Q is high and it is stable. On the other hand, in conventional tuners, the tuning frequency and Resonance Q
It was difficult to ensure stability. Thereby, other temperature compensation components or other self-stabilizing compensation circuits were added to compensate for the instability.

The operation of the tuning frequency adjustment of the tuner of this embodiment constructed as described above will be described below using the embodiment shown in FIG. 10 as a representative. First, the inductor is formed by a spiral shaped electrode 77 as shown in FIG. 10a. The capacitor is then connected to spiral shaped electrodes 77 and 78 as shown in FIGS. 10a and 10c.
is formed by the distributed capacitance generated by the dielectric 76 present between the two. Then the 21st
The operation equivalent circuit of this tuner is shown and explained in the figure. 123 in FIG. 21a is a transmission path equivalent to a spiral electrode forming an inductor;
4 is a transmission path equivalent to a spiral electrode that acts together with the inductor forming electrode 123 to form a distributed capacitor 125. Here, since the earth point of the spiral electrode 124 is set in the opposite direction to the earth point of the spiral electrode 123 forming the inductor, the inductive component of the spiral electrode 124 is canceled as shown in FIG. 21b. The spiral shaped electrode 127 of the inductor becomes equivalent to the ground plane 126.
A distributed capacitor 128 is formed opposite to. This is shown in FIG. 21c using a distributed constant circuit, in which a distributed inductor 129 and a distributed capacitor 13
A distributed constant circuit with 0 is formed. Here, the respective values of the distributed capacitance 130 and the distributed inductance 129 can be determined by cutting at an arbitrary electrode part 132 of the distributed capacitor electrode 131 which becomes the ground, and by cutting at an arbitrary electrode part 133 of the distributed inductor 129. It is possible to change it arbitrarily.

Figure 21d shows this as a lumped constant equivalent circuit, which includes a variable inductor 134 and a variable capacitor 1.
35 parallel resonant circuits are formed.

The inductance of the inductor of this tuner can be arbitrarily designed depending on the number of turns of the spiral electrode or the length of the electrode. on the other hand,
The capacitance of the distributed capacitor can be arbitrarily set by the opposing areas of the opposing spiral-shaped electrodes and the dielectric constant ε and thickness of the dielectric.
The formation of this distributed capacitance will be explained with reference to FIG. 22. Let the equivalent length of the transmission path of the opposing spiral-shaped electrodes be l, and the equivalent length of the transmission path l
is designed to be shorter than the λ/4 length at the operating frequency in consideration of the wavelength shortening rate 1/√ determined by the dielectric constant ε of the dielectric used. This λ/4
By arbitrarily designing the ratio of the transmission line equivalent length l to the length, the capacitance reactance can be reduced.
It is possible to arbitrarily design the value of _XC . This capacitance reactance X _C and operating frequency
_O gives a capacitance C=1/2π _O X _C. Now, let this transmission line equivalent length l be the transmission line equivalent length
When shortened to l′, the capacitance reactance X _C changes to the capacitance reactance X _C ′. This capacitance reactance X _C ′ and operating frequency
Capacitance C'=1/2π _O X _C ' is obtained by _O , and since C'<C, the capacitance can be varied. A capacitor having this capacitance C is equivalent to the variable capacitor 132 shown in FIG. 21d. Here, the length of the spiral-shaped electrode [spiral-shaped electrode 78 in FIG. 10 c] forming the capacitor electrode serving as the ground is the same as the length of the spiral-shaped electrode [spiral-shaped electrode 78 in FIG. 10 a] forming the inductor electrode in the above explanation. The length is the same as that of the electrode 77], but as explained in the embodiment shown in FIG. Even if it is formed, the desired purpose can be achieved.

Next, the electrodes 79, 8 in the embodiment of FIG.
The operation of 0 will be explained. Both ends of the electrode 79 are open terminals 81 and 82, and in order to form a free transmission path facing the electrode 77, which becomes an inductor, an inductor proportional to the square of the winding ratio with the electrode 77 is formed by mutual induction. Exhibiting table reactance2
Next, form a coil. Further, since the electrode 80 has a ground terminal installed in the same direction as the ground terminal of the electrode 77, a mutual induction effect similarly acts, and an inductance reactance proportional to the square of the winding ratio with the electrode 77 is exhibited. Next, form a coil.

Here, the capacitor action by the electrode 78 and the secondary coil action by the electrodes 79 and 80 each act independently, and therefore, each action can be individually controlled.

FIGS. 23, 24, 25, and 26 show how the variable capacitor and variable inductor are adjusted, representing the embodiment shown in FIG. 10. 14th
The figure is an explanatory diagram of a mode in which the variable capacitor is adjusted by cutting the capacitor electrode. As shown in Figure 23, the electrode length from the open terminal to the cut position is defined as the electrode cut amount d, and the The relationship among distributed capacitance C, distributed inductance, and self-resonant frequency _O is as shown in FIG. That is, as the electrode cut amount d increases, the distributed capacitance C decreases, but the distributed inductance L remains unchanged. Accordingly, the self-resonant frequency _O becomes higher. On the other hand, the 25th
Figure 26 is an explanatory diagram of a mode in which variable inductance and variable capacitor are adjusted simultaneously by cutting the inductor electrode, and as shown in Figure 25, the electrode length from the open terminal to the cut position is Similarly, assuming that the electrode cut amount is d, the relationship between the distributed inductor L, the distributed capacitor C, and the self-resonant frequency _O is as shown in FIG. 26. That is, as the electrode cut amount d increases, both the distributed inductance L and the distributed capacitance C decrease, and the self-resonance frequency _O increases accordingly.

Here, as a method for cutting the electrode, it is preferable to use a non-contact cutting means that does not affect the tuning frequency during adjustment, such as a laser cutter or sand plaster.

Next, the operation of another method for adjusting the tuning frequency of the tuner of this embodiment constructed as described above will be explained below, using the embodiment shown in FIG. 10 as a representative. 136 in FIG. 27a is a transmission line equivalent to a spiral electrode forming an inductor;
7 is a transmission path equivalent to a spiral-shaped electrode that acts together with the inductor-forming electrode 136 to form a distributed capacitor 138. Here, the earth point of the transmission line electrode 137 is at any electrode site 13.
9, as shown in FIG. 27b, the inductive component of the opposing part from the earth point 140 to the earth side of the electrode 137 is canceled and becomes equivalent to the earth surface 141, and the transmission line electrode 142 forming an inductor. Opposed distributed capacitor 143
form. This is shown as a distributed constant circuit in FIG. 27c, in which a distributed inductor 144 and a distributed capacitor 145 form a distributed constant circuit.
By arbitrarily adjusting the electrode end 147 of the distributed capacitor electrode 146 that serves as the ground, it is possible to arbitrarily vary the value of the distributed capacitor 145. FIG. 27d shows this as a lumped constant equivalent circuit, which forms a parallel resonant circuit of an inductor 148 and a variable capacitor 149.
Further, FIG. 28 shows another operational equivalent circuit of this tuner and will be described. Reference numeral 150 in FIG. 28a is a transmission line electrode forming an inductor, an arbitrary electrode portion 151 is used as a ground terminal, and 152 is a transmission line electrode acting together with the electrode 150 to form a distributed capacitor 153. As shown in FIG. 28b, only the transmission line 155 whose ground terminal is 154 contributes as an inductor, and the transmission line 1
Only a distributed capacitor 157 is formed between the ground electrode 156 and the opposing portion. FIG. 28c shows this in the form of a distributed constant circuit, in which a distributed inductor 158 and a distributed capacitor 159 form a distributed constant circuit. By arbitrarily adjusting the electrode end 161 of the distributed inductor electrode 158 that serves as the ground, it is possible to arbitrarily and simultaneously vary the values of the distributed inductor 158 and the distributed capacitor 159. FIG. 28d shows this as a lumped constant equivalent circuit, which forms a parallel resonant circuit of the variable inductor 129 and variable capacitor 163.

FIGS. 29, 30, 31, and 32 show how the variable capacitor and variable inductor are adjusted, representing the embodiment shown in FIG. 10. 29th
30 are explanatory diagrams of a mode in which the variable capacitor is adjusted by adjusting the ground terminal position of the capacitor electrode, and as shown in FIG. 29, the electrode length from the open electrode 163 to the ground terminal position is shown in FIG. The effective length d of the electrode is defined as the relationship between the distributed capacitance C, the distributed inductance L, and the self-resonant frequency _O as shown in FIG. That is, as the effective electrode length d increases, the distributed capacitance C increases, but the distributed inductance L remains unchanged. Accordingly, the self-resonant frequency _O becomes lower. On the other hand, FIGS. 31 and 32 are explanatory diagrams of a mode in which the variable inductor and variable capacitor are adjusted simultaneously by adjusting the ground terminal position of the inductor electrode, and as shown in FIG. 31, the open terminal 164 is the starting point. The length of the electrode up to the ground terminal position is also the effective electrode length d, and the distributed inductor L, distributed capacitor C, and
The relationship between the self-resonant frequency O and the self-resonant frequency _O is as shown in FIG. That is, as the electrode effective length d increases, both the distributed inductance L and the distributed capacitance C increase, and the self-resonant frequency _O decreases accordingly.

In the above embodiment, each electrode is commonly connected to the ground, but it is also possible to connect the electrodes to the ground through a common terminal.

Although the configuration and operation described above achieve the desired objective, the effectiveness of this configuration will be briefly compared with cases where other electrode configurations are used. The spiral shaped electrode that forms the variable inductor is similar to the one explained above, but first of all, if the spiral shaped electrode that forms the variable capacitor is not spiral shaped but is made into a full ground electrode, the Q performance of the variable inductor will be significantly reduced. It becomes less practical. Next, if the spiral-shaped electrode that forms the variable capacitor is spiral-shaped and the ground point is set in the same direction as the spiral-shaped electrode that forms the variable inductor, the two act as a single variable inductor and form a distributed capacitance. It becomes impossible to do so, and the desired objective cannot be achieved.

As described above, the feature of this embodiment is that the inductor electrode is shared with the capacitor electrode, and the inductance component of the capacitor electrode serving as the ground is canceled, thereby realizing the integration of the variable inductor and the variable capacitor.

Effects of the Invention As is clear from the above description, in the tuner of the present invention, the electrodes are arranged opposite to each other with a dielectric interposed therebetween, and the ground terminal of each sub-electrode with respect to the main electrode is on the side opposite to the ground terminal of the main electrode. The variable capacitor and secondary coil can be arbitrarily selected and formed by setting the terminals to the same direction as the terminals, and by not setting either terminal to the ground terminal, resulting in a simple configuration. With this, a variable inductor including a secondary coil and a variable capacitor can be integrally formed.

An ultra-thin and compact tuner can be realized.

Since the tuner with the secondary coil can be modularized, the tuned frequency after adjustment is extremely stable, and in particular, the tuning frequency shift due to mechanical vibration can be minimized.

Since the variable inductor including the secondary coil and the variable capacitor are connected in a leadless manner, the influence of lead inductance and stray capacitor is eliminated, and therefore the circuit operation becomes extremely stable.

It is possible to reduce the number of parts, streamlining manufacturing and reducing costs.

When using the electrode cut method to adjust the tuning frequency of the tuner, a non-contact adjustment means can be used, so that adjustment processing can be performed without affecting the tuning frequency.

Furthermore, when using the ground terminal position adjustment method, a non-destructive adjustment means for the electrode can be used, so that the tuning frequency of the tuner can be repeatedly adjusted up and down.

The tuning frequency trimming speed of the tuner becomes faster.

Excellent effects can be obtained.

Furthermore, the design of the initial values of inductance and capacitance for setting the tuning frequency of the tuner depends on the simple artwork of the electrode pattern, which improves the degree of freedom in designing the tuner and makes it easy to modify the constants. .

Furthermore, since a part of the electrode conductor may be installed inside the dielectric substrate, it is also possible to form it in an intermediate layer of a multilayer circuit board configuration, and the degree of freedom in the mounting design of the tuner can be expanded.

[Brief explanation of drawings]

FIG. 1 is a basic circuit diagram of a tuner, FIGS. 2 and 3 are perspective views showing the configuration of a conventional tuner, and FIGS. 4 a to 12 a to c are implementations of the present invention. Front view, side view and back view of the tuner in the example, Figures 13a-g, Figures 14a, b and 1
Figure 5 is an explanatory diagram showing the operating principle of the tuner, No. 16
Figures a to d, Figures 17a and b, and Figure 18 are explanatory diagrams showing the operating principle of a conventional tuner; Figure 19;
Figure 20 is a characteristic diagram of the tuning frequency and resonance Q with respect to temperature changes for the tuner of the present invention and the conventional tuner.
1A to 1D are equivalent circuit diagrams for explaining the tuning frequency adjustment method of the tuner of the present invention, FIG. 22 is a characteristic diagram showing the relationship between transmission path length and reactance of the tuner, and FIGS. Figure 26 is an explanatory diagram showing how the variable capacitor and variable inductor of the tuner are adjusted; Figures 27 a to d and Figures 28 a to d are diagrams for explaining other tuning frequency adjustment methods of the tuner The equivalent circuit diagrams of FIGS. 29 to 32 are explanatory diagrams showing how the variable capacitor and variable inductor of the tuner can be adjusted. 15, 28, 48, 55, 62, 69, 76,
83, 90...dielectric substrate, 16, 29, 49,
56, 63, 70, 77, 84, 91...Main electrode, 17, 18, 19, 30, 31, 32, 5
0, 51, 52, 57, 58, 59, 64, 6
5, 66, 71, 72, 73, 88, 89, 9
0, 95, 96, 97, 92, 93, 94... Sub-electrode.

Claims (1)

[Claims] 1. A plurality of sub-electrodes are provided via a dielectric material, facing a main electrode having a predetermined electrical equivalent length and one terminal set to ground, and the above-mentioned The first sub-electrode is the one in which the ground is set to a terminal in a position opposite to the ground terminal in the main electrode, and the ground is set to the terminal in the sub-electrode which is in a position opposite to the ground terminal in the main electrode. A tuner characterized in that a second sub-electrode is defined as a sub-electrode, and a third sub-electrode is defined as a main electrode whose terminal is not set to ground. 2. The tuner according to claim 1, wherein a first sub-electrode and a second sub-electrode or a third sub-electrode are respectively provided at predetermined positions as sub-electrodes. 3. The tuner according to claim 1, wherein a predetermined tuning frequency is set by cutting out a predetermined portion of the main electrode or the first sub-electrode. 4. Tuning according to any one of claims 1 and 2, which adjusts to a predetermined tuning frequency by setting a predetermined portion of the main electrode or the first sub-electrode as a terminal connected to ground. vessel. 5. A tuner according to any one of claims 1 to 4, using an electrode having at least one bent portion exhibiting a predetermined bending angle or bending rate and a predetermined bending direction. 6. A tuner according to any one of claims 1 to 4, using an electrode having a spiral shape. 7. The tuner according to any one of claims 1 to 6, wherein the length of one electrode is set shorter than the length of the other electrode, and the tuner is arranged to face each other at a predetermined portion. 8. The tuner according to any one of claims 1 to 7, wherein each electrode or one side of the electrode is partially or entirely installed inside the dielectric. 9. The tuner according to any one of claims 1 to 8, wherein the respective electrodes are installed on the inner circumference or the outer circumference of a cylindrical or prismatic dielectric body. 10. The tuner according to any one of claims 1 to 9, wherein the main electrode or the second sub-electrode is partially cut out. 11 A plurality of sub-electrodes are provided via a dielectric material, facing a main electrode having a predetermined electrical equivalent length and one terminal set to ground, and these sub-electrodes are connected to the ground terminal of the main electrode. The first one is the one in which a common terminal is set for terminals that are in different opposing positions.
A second sub-electrode is defined as a sub-electrode, and a second sub-electrode in which the common terminal is set at a terminal opposite to the ground terminal of the main electrode in these sub-electrodes; A tuner characterized in that a terminal not set as the common terminal is used as a third sub-electrode.