JPH01501356A - Single-phase and multi-phase electromagnetic induction machines with adjusted magnetic pole symmetry - Google Patents

Abstract

(57) [Summary] This bulletin contains application data before electronic filing, so abstract data is not recorded.

Description

[Detailed description of the invention]

TECHNICAL FIELD The present invention relates to single-phase and multiphase electromagnetic induction machines with adjusted magnetic pole symmetry. Prior Art With the advent of high usage charges, power factor penalties and demand-based pricing regimes, known induction motors have developed a number of drawbacks. Most induction motors in use today are too large and inefficient. Therefore, due to this low motor efficiency, high demand, and poor power factor (KW/KVA), the bill for electricity is higher than necessary. As is well known. Power factor is based on the phase relationship between alternating voltage and alternating current. Electric power companies generally state that when the power factor drops below 0.85 (voltage and current are completely phase-wise (When the power factor is 1 when the waveform is the same), premium charges are imposed on users. When energy costs were low, these drawbacks were not as important as they are now. Demand power (the total power that must be obtained from the line but not necessarily used) and power factor penalties are often significantly higher than the basic energy bill. The most efficient known single-phase induction motors are permanently split-phase capacitor designs, but these have poor torque characteristics and the magnetic field of the main phase winding is It is only effective when the currents of each of them are offset from each other by 906 when balanced with the field. stomach. In most split-phase capacitor motors, the large stator winding is the power end. A small auxiliary winding connected directly to the input and in series to the capacitor is connected to the input. Therefore, the 90° deviation in current between the two connected stator windings is equal to the design load. No cracking occurs. At other load points, the magnetic flux is distributed non-uniformly, which causes the rotor and Theta is set with a negative sequence of current. Spatial harmonics occur in the air gap (e.g. to the extent that the magnetic flux distribution in the air gap is no longer sinusoidal) and leakage reactance from the end turns of the stator becomes high. Unbalance increases motor losses by as much as 15% to 20%. This condition is not limited to single-phase motors, but can also occur in polyphase motors when unbalance occurs in the polyphase power supply. These losses in both single-phase and multi-phase motors lead to overheating of each motor, reducing insulation performance. Shorten bearing life. Furthermore, in addition to rotor heating, as is evident from Table 1, the imbalance causes large magnetostrictive noise and degrades operational performance. Another serious drawback arises when manufacturing new motors; Design tolerances are of concern in attempts to increase motor efficiency, but motors are susceptible to failure due to environmental changes and bearing wear. Also, the series common Attempts have been made to form an equilibrium state by combining swing windings with phase windings. However, this is a condition that is tuned only over a narrow spectrum, and at a load point consisting of 1! The circulating harmonic currents increase and the efficiency is lower than that of the standard design. Induction motors and generators are effective only when properly sized for the load and when line voltages are balanced. When operating at a lower than design load or when the system is unbalanced, uneven magnetic pole conditions can occur, causing damage to the rotor and A negative sequence of current is set in the stator and stator, creating spatial harmonics in the air gap. Similarly, large currents in the phase windings increase leakage reactance. In this case as well, the 7 imbalance will be about 3%. Motor or generator losses amount to 15% to 20%. Due to this 7, insulation This results in unbalanced conditions that lead to high magnetostrictive noise and reduced operating performance, as well as reduced performance and bearing life. Also, by combining the series resonant winding with the phase winding, balanced control can be achieved. Attempts have been made to create a condition in the motor that is tuned to a narrow spectrum, such that at the load point the circulating harmonic current increases and the efficiency decreases to Ill! lower than that of the semi-designed one. SUMMARY OF THE INVENTION Single-phase generator motors (including motors or generators) typically include a rotatable rotor within an interior space defined by a hollow, cylindrical, stationary stator. The rotor and stator have slots facing each other, in which the windings are placed. It will be done. The rotor windings are connected at each end to form a squirrel cage, or are pulled out through slip rings. In a stator, two windings are electrically connected in series. The magnetic poles are arranged circumferentially along the inner surface of the hollow stator core to form magnetic poles. A capacitor is connected in parallel to one winding, and this combination is connected in series with the second winding. The capacitor is sized such that it forms a quasi-series resonant circuit with the second winding and a quasi-parallel resonant circuit with the first winding. Stator windings connected in series can be connected across single-phase or polyphase power input terminals. Continued. When power is supplied to the motor, a balanced rotating magnetic field is generated and the motor rotates 5 times. The Q-factor of the path is continuously adjusted by the admittance of the rotor winding. Pseudo direct The interaction between the column resonant circuit and the quasi-parallel resonant circuit causes the unused energy sent to the rotor in the form of magnetic flux to be returned through one of the stator windings, causing the magnetic field to collapse. During this process, the resulting voltage is stored in the capacitor. This is due, for example, to a reduction in the load torque exerted on the rotor. In another sense, when the torque demands on the rotor are high, the capacitor supplies stored energy to the appropriate windings, compensating for the additional power demand and balancing the distribution of magnetic flux rotating around the rotor. Maintain balance. The method of generating torque from an AC power source is to form a quasi-double resonant circuit that includes a capacitive element.The capacitive element is connected in parallel to one of the inductive elements, and this combination is connected in series to the other inductive element. ), a rotatable inductive element is provided which is used to supply torque, and power is applied across two series connected fixed inductive elements. All inductive elements are magnetically coupled and quasi-series and quasi-parallel resonant circuits are The method includes the step of generating a balanced rotating magnetic flux wave through the above-described mechanism. In one embodiment, a polyphase induction motor includes three pairs of series-connected stator windings, one winding of the multiple pairs has a capacitor connected in parallel, and one winding of the multiple pairs has a capacitor connected in parallel. are connected in series to the other winding of the pair to form a quasi-double resonant circuit. The polyphase motor, in yet another embodiment, includes three primary stator windings, which are connected to the motor via one of the power input terminals to separate the three phases of power supplied to the motor. Receive phase. The three secondary stator windings are The secondary stator windings are circumferentially interleaved between the primary stator windings and are magnetically coupled to these secondary windings, but not directly connected to the motor power input terminals. A capacitor is provided for each pair, and each capacitor has a small number of capacitors. in parallel with at least one secondary stator winding. Each capacitor is connected in parallel. The secondary stator winding forms a quasi-parallel floating resonant circuit. It is said to be iz. Therefore, a primary object of the present invention is to eliminate or control spatial harmonics in the air gap, negative sequence currents in the rotor and stator windings, and to The aim is to increase the efficiency of a motor or generator. Another object of the present invention is to provide a motor without increasing hysteresis loss due to magnetic saturation. The aim is to increase the torque rating of the motor. Yet another object of the invention is to improve the power factor of induction motors. An additional object of the invention is to store unused energy returned to the stator windings. This stored energy is then supplied to the magnetic circuit according to demand. Yet another object of the invention is to provide a balanced rotating system under substantially all loads. The idea is to form magnetic flux waves around the rotor. SUMMARY OF THE INVENTION 1 Other objects and advantages of the present invention will be readily understood from the following detailed description with reference to the accompanying drawings. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a schematic diagram of a single-phase motor with adjusted magnetic pole symmetry; Fig. 2 is an electrical diagram of the single-phase motor of Fig. 1 without an indication of stator core material or rotor material; The circuit diagram, Figure 3A, shows how the oscilloscope is configured to trigger on positive going slopes of the supply line voltage. Related to each stator winding NI & (and capacitor) when setting the Roscope. Figure 3B shows an oscilloscope trace of the voltage waveform generated by the oscilloscope to trigger on the positive slope of the supply line voltage. Figure 4A shows an oscilloscope trace of the current waveforms associated with each stator winding and capacitor when the scope is set. Oscilloscope trace of line supply voltage VL and line current at load. Figure 4B shows the line supply voltage and line current oscillations at half load. Diagram showing a loss scope trace. Figure 4C shows the oscilloscope trace of line supply voltage and line current at no load. Figure 5 shows an oscilloscope diagram of the line supply voltage and line current over the entire motor load range. A time course diagram showing a copy trace. 6 is a graph showing the rotor current versus slip speed for the induction motor of FIG. 1. FIG. 7A is a graph showing the effect of resistance on the shape of the series resonance curve. FIG. 7B is a graph showing the effect of resistance on the shape of the series resonance curve. Figure 7C is a diagram showing the effect of L/C ratio, Figure 7C is a diagram showing a parallel resonance curve, and Figure 8 is a diagram showing a polyphase induction motor with adjusted magnetic pole symmetry including a pseudo double resonance equalizer circuit. FIG. 1 and FIG. 9 are electrical circuit diagrams showing the multi-phase pseudo double-resonant induction motor of FIG. 8 in which the resonant winding of the stator is connected to the source in a Δ configuration. Fig. 1O is an electrical circuit diagram showing the multi-phase pseudo double resonance induction motor of Fig. 8 in which the resonant winding of the stator is connected to the source in a Y-form; One current and magnetic state of a pole three-phase induction motor Figure 12A shows the line supply voltage VL and line current IL at full load on one phase in a 40 horsepower three-phase quasi-double-resonant induction motor. Oscilloscope trace, Figure 12B, shows the line supply power at 75% load for one phase of the motor in Figure 12A. Figure 13 shows the switching network that changes the rotation of the dual-resonant polyphase motor of Figure 8. Figure 14A shows the magnetic pole symmetry with parallel floating quasi-resonant circuits. Schematic diagram of a polyphase induction motor with the -order stator winding connected in a Y configuration to the source. The parallel floating windings are connected in a Y configuration and the floating circuit is FIG. 3 is a diagram showing the capacitors of the circuit connected in a Δ configuration. Figure 14B is an electrical circuit diagram of a polyphase induction motor with adjusted magnetic pole symmetry having a parallel floating quasi-resonant circuit, in which the -order stator winding is connected to the source in a Y configuration. The parallel floating windings are connected in a Y configuration and the floating windings are FIG. 3 is a diagram showing capacitors in a programming circuit connected in a Δ configuration. FIG. 15 is an electrical circuit diagram of a multi-phase parallel floating quasi-resonant induction motor in which the -order stator windings are connected in a Y configuration to the input and the parallel floating stage Figure 16 is a diagram showing the motor winding and capacitor connected in a delta configuration. An electric current showing a multiphase induction motor with adjusted magnetic pole symmetry in a rotating aa parallel resonance design. In the circuit diagram, the stator winding of the − next phase is connected in delta form with the source, and its parallel Figure 3 shows the floating resonant stator windings connected in a Y configuration and the floating circuit capacitors connected in a Δ configuration. Figure 17 is an electrical circuit diagram of a multi-phase parallel floating induction motor, in which the negative stator windings are connected in a Δ configuration, and the secondary stator windings, that is, parallel floating windings, are connected in a Δ configuration. and the floating circuit capacitors are connected in a Y configuration. Diagram showing ro. Figure 18A is an oscilloscope trace showing the line supply voltage and line current at full load for one phase of a 40 horsepower three-phase pseudo-parallel floating resonant induction motor. Oscilloscope trace showing the line supply voltage and line current at 75% load on the phases. Part 19 shows the phases of an ideal double resonant motor with quasi series resonance at full load. Figure. Figure 20 shows a 1/3 horse motor with pseudo series resonance and pseudo double resonance at full load. Figure 21 shows the phases of an ideal double resonance motor with parallel resonance at no load, and Figure 22 shows the phases of a 1/3 horse motor with no load. At the load, the quasi-series resonance quasi-double resonance A diagram showing the phases after conversion to a vibration motor. FIG. 23 is an electrical circuit diagram of a double resonance motor according to the technique of the present invention used to explain FIGS. 19 to 22, and FIG. Figure 2 is a diagram illustrating the magnetomotive force produced in the gap, with each waveform representing the force (magnetic flux) produced in the air gap around the rotor at a given time of one cycle of input power; Figure 11 is a schematic diagram showing a single-phase AC induction motor with a squirrel cage rotor configuration. Ste Data STI is a generally hollow cylindrical slot made of laminated sheet steel. It is a structure with tags. The rotor ROI is rotatably arranged in the internal space of the stator. placed. Due to the 0M singulation, the stator STI is formed of similar materials. It is shown as having four pole areas or teeth TAX, TBI, TCI and TDI projecting from its return path or back iron BII. The actual number of poles or teeth depends on physical size, horsepower and rotational speed. The physical dimensions of the motor and its integral parts are shown only schematically and do not necessarily represent the optimal physical construction. The stator or primary is shown as having two windings WA and WB, commonly referred to as wound on J-tooth TAI, TBI, TCI and TDI. The windings are arranged in an axially extending thrower 1 provided inside the stator. Similarly, the rotor windings WC are distributed in axially extending slots provided around the rotor RO. Stator windings WA and WB are connected in series at midpoint 4P, and the series circuit is connected across power input terminals L1 and L2. The midpoint connection MP is passively connected to the input terminal L1 by two capacitors CA and CB. Ru. Capacitor CB is permanently connected while capacitor CA is is disconnected from the circuit by centrifugal force switch C8 when the motor reaches a predetermined speed during startup. Be far apart. When using the motor in low torque applications, capacitor CA and centrifugal force switch C8 are removed from the circuit. The rotor winding WC is divided into stator windings WA and WB by the four m-pole regions, namely teeth TAI, TBI, TCl, TDI, the air gap AG, the magnetic material of the rotor ROI, and the return magnetic path or rear iron part BII. closely magnetically coupled to the The present invention provides an adjustment circuit that equalizes the magnetic pole area around the rotor regardless of the magnitude of the electromotive force or its waveform. By arranging the magnetic flux axially symmetrically in this way, This arrangement reduces the spatial harmonics generated in the air gap between the stator and rotor, increasing the net magnetic flux available for connecting the rotor windings. The symmetry reduces the possibility of negative sequential currents being established in the rotor and allows higher torque ratings to be obtained for 1,000 to 1,000 times without increasing hysteresis losses due to magnetic saturation. 7. High efficiency can be obtained by intermediate transfer and storage of energy, and public In contrast to the induction/resistance ratio of conventional induction motors, the current rise time of the resonant circuit is reduced. The amount of force or mechanical torque acting on the rotor is based on the following equation: F = BΩ (1) where F is the mechanical force, B is the magnetic flux density connecting the rotor windings, Q is the physical length of the windings, and I is the force applied to the windings. It is a flowing current. squirrel cage induction motor The largest energy loss in a motor is due to the resistance of the winding when current flows through it. This is the heat generated by The amount of this loss is based on a first-order equation. I ” R (2) However, R is the current (ampere) and R is the resistance (ohm), so the low By increasing the available net magnetic flux connecting the rotor (e.g. by increasing B and keeping F and Ω constant in Equation 5), the current components in the rotor are reduced. This results in less heat generation, longer bearing life and higher efficiency. Additionally, the effects of eddy currents on all induction motors and generators are reduced due to the reduction of spatial harmonics. The sound is reduced. Resonant circuits do not send unused energy back to the source, but instead store it primarily in capacitors, so that by transferring the energy of the phase back and forth and between the two windings, This results in an energy-efficient topology. t in the quasi-resonant circuit? , VWB is at a high level and It is at a low level. Therefore, the magnetic flux density in the core is reduced and hence the hysteresis loss, vortex 11E flow loss losses and I”R losses are reduced compared to standard motor designs. This allows the controller to operate in the linear part of the BH curve. IWB is at a high level Because. The magnetic flux in the air gap will be at a high level, therefore it? The torque produced by - is considerably greater than in the standard seven-wheel case. Under high loads, Ie provides ~VAR5 at the stator and +VAR8 at the rotor, thus maximizing the energy to the rotor. The maximum energy transfer to the rotor reaches +Y (jw) rotor = -Y (jv) stator Occurs when This condition is used in the present invention and especially in the quasi-double resonance equalizer. This is normally obtained in the iser circuit. Furthermore, the admittance of the rotor The energy transfer varies proportionally with each speed of the motor, so the energy transfer is constant over the entire motor load range. It remains in a proportional state. FIG. 6 shows the rotor current versus slip frequency curve. The conductance G of the resonant circuit is governed by the first-order equation. Y = v' and 71T ding ``PARCTAN B e, -G (3) However, Y is the admittance (reciprocal of impedance), that is, the total ability to pass alternating current, and G is the Siemons circuit conductance (reciprocal of resistance). In other words, passing current B is the Siemons susceptance (the reciprocal of reactance), or the ability of inductance or capacitance to pass alternating current. Beq=Be-BL is the net equivalent susceptance in the above three equations. As is well known, the admittance of a circuit is equal to the conductance (real component) + susceptance (imaginary component). Y (jv) = G (v) + j B (w) (4) In the resonant state, the reactive power of the inductance is equal to and of opposite sign to the reactive power of the capacitance, and the source of the electromotive force is caused by the resistance of the circuit. Provides only the power needed One important characteristic of a quasi-double resonant circuit is the check/balance network. Figures 19 to 22 show the pseudo double resonance modes shown in Tables 1.2 and 3. Contains vector illustrations of data. FIG. 23 is an equivalent circuit of the motor, and the vectors shown in FIGS. 19 to 22 are This is used to examine the diagram. As is clear to those skilled in the art, under no load, there exists a state in which the currents of WB and CB are equal to 180"M, a state called parallel resonance. As the slip of the rotor increases, the resistance of the rotor changes, and the magnetic coupling between the resonant and rotor windings causes the circuit to move from a parallel resonance condition to a condition very similar to that occurring during series resonance. change into a state. Does the circuit conduct current even when there is no load? It is not a theoretical parallel resonance, but is therefore called a pseudo-parallel resonance. at full load If the maximum current does not flow, in other words, the current is limited only by the resistance of the circuit. Therefore, there is no theoretical series resonance. Therefore, the circuit is It is called a quasi-series resonant circuit. In both parallel resonance and series resonance, circuit polarization The tans cancel out and there is a power factor of 1. This condition exists in this unique circuit. Therefore, it is called a pseudo double resonant circuit. This circuit controls the current and voltage in each winding. control and adjust to maintain optimal magnetic flux conditions for each magnetic pole region. This creates a perfectly rounded rotating magnetic flux waveform of constant amplitude in the air gap, as shown in FIG. This condition is necessary to reduce magnetic losses and increase efficiency. As shown in FIG. 24, the upper set of curves shows that FA is volume 1! ! It shows a state like the magnetic flux of the air gap caused by WA, and is true The middle set of curves shows the situation where FA' is the magnetic flux component produced in the air gap by winding WB. The lower curve shows FA+FA'. As is clear from Figures 19 to 24, in the quasi-resonant state, the vector sum of the voltage drops across the capacitor CB and the inductor of the series branch (winding WA) is equal to the line voltage; As is clear from Table 3, the vector sum of the currents in the crossroads (CB and WB) is equal to the line current in this system. Maintain uniform power distribution between the two branches. Inductance or capacitance at resonance The ratio of the reactive power of the resonance to the active power of the fully resonant circuit is called the Q factor of the circuit. Ru. Let the symbol of the resonant frequency be rf rJ. At resonance, the capacitance The reactance is equal to the reactance of the inductor from the following equation (XL=XC). 2fL=1-(2πf c) (5) The following equation can be obtained. f r=1-C2tc (T:te) (6) where fr is a cycle of 7 seconds, L is Henry, and C is Farad. The above 6 equations are the inductance or shows that by changing the capacitance, the RLC circuit can be brought into resonance at a given frequency. What is the resistance of the series resonant circuit at the resonant frequency fr? Note that there is no equality relationship. Resistance affects only Q, and the minimum impedance of the circuit at resonance, and thus the height of the resonance curve, varies as shown by the curve in Figure 7A. Also, in Figure 7A Therefore, as long as the product of L and C is constant, the resonant frequency of the series circuit is constant. However, and others. When the L/C ratio is increased by a factor of 4=1 (Figure 7B). The “skirt” of the resonance curve becomes steeper. Decreasing the resistance of a series resonant circuit and increasing the L/C ratio changes the height of the curve and narrows the resonant frequency band. This has the effect of making the "skirt" of the curve steeper. In an AC circuit that includes both inductance and capacitance, the voltage increases. As the energy increases, instantaneous energy (1/2Cv 2 ) is stored in the capacitor, and once On the other hand, as the current increases, energy (1/2LI”) is stored in the inductance. This is done alternately twice in each cycle. Therefore, the inductance and the Reactive energy is exchanged with the capacitance. The source of the emf (energy delivered to the motor) only needs to supply the difference between the reactive energy of the inductance and the reactive energy of the capacitance, which is the net reactor of the series circuit. This takes into account that reactance is the difference between inductive reactance and capacitive reactance. Ru. That is, Xnet = XL - XC (7) Furthermore, consider that the reactive voltage of the series circuit is the difference between the inductance voltage and the capacitance voltage. The reactance is. It is the imaginary component of impedance, and resistance is its real component. This must be compared with Equation 4. The Q-factor of a resonant circuit is the ratio of reactive power to the power consumed by the resistor. Shown here In this example, the resistance represents the mechanical load on the motor. The response curve of a parallel branch or quasi-parallel resonant circuit (CB and WB) is shown in FIG. 7C, which is generally the inverse of the series resonant curve. Since the Q of the parallel winding has an opposite effect on the circuit compared to the Q of the series winding, the quasi-parallel resonant circuit is balanced with the quasi-series resonant circuit, and the instantaneous energy imbalance that occurs in one of these circuits is other times compensated very quickly by the road. As a result, as shown in Fig. 24, A coherent rotating magnetic flux waveform is formed around the rotor. The sensitivity of a resonant circuit can be increased by increasing the Q of the circuit or Alternatively, it can be reduced by lowering Q. Deliberately lowering the Q of the tuned circuit The result when Q=1/2 is called "critical damping". Coming An example of field damping is damping the movement of a meter pointer so that it does not oscillate. Therefore, this resonance characteristic can be utilized in a quasi-double resonance induction motor. By appropriately selecting the Q factor, energy transfer to the rotor can be improved. energy provided by the source can be controlled. Q is Admitter The inrush current can be reduced because it is a multiplier of A uniform distribution of power can be maintained. The operation of the single-phase quasi-double resonance induction mode shown in Figures 1 and 2 is explained below. When AC voltage is applied to input terminals T, ] and L2, the capacitor Capacitors CA and CB start charging, and capacitor CA closes when centrifugal force switch C8 closes. The circuit is connected by This charging current flows through the winding WA and sets up a magnetic flux path which includes the teeth TAI and TBi, their respective air gaps AG, and the The data ROI and the return magnetic path, ie, the rear iron part BII, are traced horizontally. When current begins to flow through winding WA, capacitor CB starts charging - next winding, I! Potential begins to be established at WB. This potential is approximately 90° out of phase with the potential of winding WA. See Figure 3A. In comparison, V WA leads V uB by 90''. Therefore, when the current in WA reaches its maximum value, the potential in WB also reaches its peak. The current flows through the winding WB. Figures 3A and 3B show the phase relationship of a single-phase motor with adjusted magnetic pole symmetry. are doing. In the example shown, the motor is a dual-resonant 1/4 horse motor adapted to receive an AC input of 2 o volts. It shows. This figure shows the open phase relationship between V WA, V WB, and V CB; The phase relationship creates a balanced rotating magnetic field. The traces in Figures 3A and 3B begin with a positive going slope of the voltage sent to the motor. These show that V IjA lags the supply voltage VL by about 45''. See Figure 3B. The current in the first winding WA (IVA) decreases and the current IWB in the winding WB is established. When it is turned on, the energy stored in the magnetic field of the six windings WA is stored in the capacitor CB. The accumulated energy is transferred to the winding WB, forming a rotating magnetic flux waveform. This waveform extends from the horizontal polar axis pre-established in the motor's magnetic material to the stator teeth TCI and TDl, their respective air gaps, the rotor's magnetic material and the It rotates through the magnetic path, ie, the rear iron section B 1, to a centered vertical position. child The rotating magnetic flux waves in the rotor ROI cut the rotor winding WC, which causes a current to flow, establishing a magnetic field in the rotor, which is in turn connected to the rotating magnetic flux waves established in the magnetic material of the stator STI. Attempt to self-align. Figure 3B shows capacitor CB and stator winding 1! Current waves flowing through WA and WB respectively Forms I CB, I vA and I WB are shown. IMA and IvB are shown to be completely 901 out of phase with each other. and I CB is 1809 out of phase with respect to I WB. Figures 3A and 3B have the same time base and therefore direct relationship between voltage and current. A direct comparison can be made. When the current in winding WB (iWB) reaches its peak, it starts decreasing by 5 and its magnetic The energy stored in the field is released into the rotor winding or capacitor CB. Additional energy passing from the source through winding WA is also stored in capacitor CB. This pattern causes the magnetic flux wave to continue through each cycle of alternating current one revolution, causing each cycle to undergo one revolution. Although four poles are shown in the drawing, the magnetic field advances by ]74 revolutions every 1/4 cycle, so the motor is at rest or stopped, which is considered to be a two-pole motor. In this case, when a voltage is applied to input 1 and L2, the magnetic flux wave that rotates once cuts all the rotor windings WC at the maximum rate, so that the net equivalent susceptance Beq becomes a high level. This causes a considerable amount of current to flow through both the stator and rotor windings. As the speed of the rotor increases, the rate at which the winding WC is cut decreases and the net equivalent susceptibility increases. Figure 6 shows the curves of 50 - motor current vs. slip frequency. In the 90 - tarok condition, the current flowing in the stator and rotor windings is The current has the same frequency as the line current. At no load, when the motor reaches synchronous speed, the frequency of the rotor current becomes 0. Rotor windings 11 The dual resonant equalizer circuit is stored in the active elements (WA, WB and/or CB). This feedback also controls the Q-factor of the resonant circuit and adjusts the amount of energy required from the power source (Figure 6). B In the rotor lock (ORPM) condition, the rotor current frequency is the same as the line frequency. It decreases with the speed of mouth and evening, and eventually becomes 0 at the synchronous speed. Resonant circuits are important in several ways. First, we will strictly examine the quasi-series resonant branch consisting of the winding WA and the capacitor CB. In Figure 20, under full load conditions, it appears as if there is a condition that violates Kirchhoff's voltage law. By measuring the voltage drop across WA and CB (which is the same as VWB), it is determined that they are the same. This means that the unit is twice as large as the source. Series resonant circuits do not violate Kirchhoff's laws. This is because the vector sum of WA and CB is equal to the input voltage, as shown in Figures 19 to 22. The ability of a quasi-series resonant circuit to generate a voltage higher than the applied voltage is one of the most important circuit properties. This is the ability to store unused energy in WA and CB. In the series part of a circuit enabled by the power, Q is the voltage of WA and CB. This is the magnification factor (admittance factor) that determines how much higher the voltage can be increased than the applied voltage. Consider separately the parallel branch of the pseudo double resonant equalizer circuit consisting of WB and CB. Ru. In Figure 22, when there is no load, the current in CB leads the voltage applied to it by 90'', and the current in WB lags the voltage applied to it by 84.2@.CB and WB are in parallel. Since the same voltage appears on both of them (Figure 3A), their currents are therefore 174.2° out of phase. This is shown in Figure 22. This shows that when a current flows in one direction in WB, an equal current flows in the opposite direction in CB. When Kirchhoff's current law is applied to the midpoint MP, as is clear from Fig. 21, in parallel resonance, no current flows to or from the source; the current flows simply. It simply oscillates back and forth between the capacitor and the winding. ideal parallel resonance circuit In the circuit, only a source voltage is required to initiate this oscillation. child Once this has started, the source can be removed and the circuit will continue to oscillate indefinitely. Parallel resonant circuits exhibit opposite characteristics to series resonant circuits, so they are called antiresonant circuits. It is also sometimes called ``Furi''. However, this condition only occurs when there is no loss in one circuit. Loss occurs in a quasi-double-resonant induction motor. That is, the maximum loss is the one supplied to the load. Another loss that should be minimized is the current flowing through the resistance of one winding. It is caused by the current. Therefore, energy must be constantly added from the source. This ability of the parallel resonant circuit to sustain oscillations after removing the source voltage Duplex is an important feature in motor circuits because with each vibration a magnetic field is established around the WB. When this magnetic field collapses, the energy of the magnetic field An electromotive force (V) is induced in CB by the force. This energy transfer method is the most efficient because it is intermediate in nature and does not return unused energy to the source. It is a topology. Since the two stator windings are in series and the two resonant circuits are essentially opposite (FIGS. 7A and 7B), they electrophysically control or coordinate each other. The end result is an induction motor with tuned magnetic pole symmetry over the entire point range. Figures 4A, 4B, and 4C show the applied emf (radius) in a single-phase motor with well-aligned pole symmetry of the same type as that described for Figures 3A and 3B. The relationship between line voltage VL) and current (line current IL) is shown. Figure 4A shows the full load condition, Figure 4B shows the half load condition, and Figure 4C shows the no load condition. Indicates the condition of the load. Note that line current IL is kept strictly in phase with line voltage VL. The power factor of a circuit is therefore 1 over the entire load range. FIG. 5 is a diagram showing the time characteristics for the entire load range of the single-phase motor of FIGS. 3A and 3B. FIG. 5 shows the line voltage and current phase relationships over the entire load range. Another unique and desirable characteristic of the motor is a flattened current waveform IL. child Since the signal IL is a non-sinusoidal wave, its RMS value, that is, its effective value is the same peak value as the positive A magnetic field that is considerably larger than a string wave and can maintain a high level for a long time without saturating the iron. give rise to a world. This maintains high torque and reduces hysteresis in the magnetic core material. Reduces cis loss. The motor operates in the linear part of the BH curve. The present invention substantially eliminates the significant current problems associated with conventional induction motors and generators. Although the present invention describes a motor, torque is applied to the rotor. If the device is driven at a synchronous speed or higher, the device can be operated as a generator. It should be noted that in the case of a zero-shot TLT machine, since the power factor of the device is 1, there is no need to supply reactive power.The scope of the claims shall also include such usage of the device. Conventional polyphase motors, by design, have uncoordinated rotating magnetic flux waves that become asymmetrically distorted under certain operating conditions. This distortion, or magnetic irregularity, reduces the operating efficiency of conventional motors. The present invention provides an adjustment circuit that equalizes the magnetic pole area regardless of the magnitude of the electromotive force or its waveform. By aligning the magnetic flux axially symmetrically in this way, undesired spatial harmonics in the air gap between the stator and rotor are reduced, as shown in Figure 24. In this way, the available net magnetic flux connecting the rotor windings can be increased. Magnetic symmetry reduces the risk of negative sequential currents being established in the rotor, leading to magnetic saturation. To obtain a high torque value without increasing hysteresis loss. Also, the intermediate transfer and storage of energy provides high efficiency and short current rise times in the resonant circuit, in contrast to standard motors. The polyphase motor will be explained below. Some important properties of a quasi-double resonant circuit are its checking and balancing network and its ability to generate a rotating magnetic vector. power and the ability of the circuit to act as a phase doubler. Therefore, the coil placement is once An example of a suitable coil arrangement, which should be made to increase the rotating magnetic sinusoidal waveform, is shown in FIG. It should be understood that changes can be made to form a module with gender 2. Therefore, the present invention is not limited to the embodiment shown in FIG. As in the case of the single-phase motor of the present invention, at quasi-resonance, the vector sum of the voltage drops across the capacitors and inductors of the quasi-series branch is equal to the line voltage (Figure 19) and the quasi-series branch The vector sum of the currents in the quasi-parallel branches becomes equal to the line current (Figure 19). Two electrical circuit diagrams of a quasi-double resonant polyphase motor are shown in Figures 9 and 10. Ru. The configuration shown in FIG. 9 is schematically illustrated in FIG. In Figure 8, the windings of each quasi-resonant circuit are electrically separated by 90". It is understood that this angle can be adjusted to produce different torque and operating characteristics for the motor. I want to be. FIG. 8 schematically shows a quasi-double resonant multiphase AC induction motor of squirrel cage design. This motor has a sheet steel laminated stator ST2 and a similar material rotor. It has data RO2. For simplicity, the stator is assumed to have 12 poles or teeth TA, TB, TC...TL protruding from the return magnetic path or rear iron part B12. The actual number of these teeth will depend on physical size, horsepower and rotational speed. The physical size of the motor and its integral parts is It is for illustration purposes only and does not represent its optimum physical structure. The stator has three sets of pseudo double resonant circuits, one set for each phase of the input. It is shown as. The first pseudo-double resonant circuit consists of series connected windings WBa and WAa wrapped around teeth TA, TB, TC and TD, these windings straddling inputs A and B and ending at midpoint M. are connected in series at P a. With the windings connected in this way, this midpoint is passively connected to input terminal A by capacitor CBa, that is, connected in parallel to winding WBa and in series with WAa. It is continued. The rotor winding WC has four pole regions namely teeth TA, TB, TC, TD. They are magnetically connected to the stator windings WBa and WAa by their respective air gaps AG, the magnetic material RO2 of the rotor, and the return path or back iron BI2. A second set of quasi-resonant windings WBb and WAb are connected to input terminals A and C. These are wrapped around the teeth TE, TF, TG and H and are also connected in series at the midpoint MPb. Its connection is passively connected to input terminal B by capacitor CBb. The rotor winding WC is divided into stator windings by four magnetic pole regions, namely teeth TE, TF, TG, TH, their respective ρ air gaps AG, the rotor's magnetic material RO2, and a return path, or rear iron part BI2. Closely connected to mWBb and WAb. A third set of quasi-resonant windings WBc and WAc are connected to input terminals A and C. These are wrapped around the teeth TI, TJ, TK and TL and at the midpoint M P c. connected in series. The midpoint connection M Pc is passively connected to the input terminal C by a capacitor CBc. The secondary winding WC is connected to the primary winding WBc and Closely connected to WAc. The operating principle of the pseudo double-resonant polyphase motor shown in FIG. 8 is as follows. When a polyphase AC voltage is applied to input terminals A, B, and C (A is O and the capacitor CBa starts charging. This charging current flows through winding WAa. stator teeth TC and TD, their respective air gaps, rotor magnetic material and A return magnetic path, that is, a magnetic flux path passing through the rear iron portion BI2 is set. At the same time, Ste. Since three phases act on the motor simultaneously, a situation similar to that shown in Figure 11a occurs. Figures 11A-11L show a standard induction motor during one revolution in 30' increments. The current and magnetic flux paths of the motor are shown. These diagrams illustrate motors, especially pseudo-duplex motors. This helps explain the very complex conditions that occur in vibrational induction motors. public Both the known induction motor and the induction motor of the present invention generate rotating magnetic flux waves, but the magnetic flux waves of the conventional motor are one wave of the quasi-double resonant motor of the present invention, and the induction motor of the present invention generates rotating magnetic flux waves. It is not necessarily symmetrical or balanced under the conditions of transformation. In Figures 11A-11L, the solid and dashed lines represent the current flowing through the stator windings, and the dash-dotted lines represent the magnetic flux path through the stator and rotor. One of the structural differences between conventional polyphase induction motors and induction motors constructed according to the principles of the present invention is. For example, if a quasi-double resonant induction motor is connected to power input terminals A and B, It has circumferentially interleaved windings between the windings. The winding connected in series with the capacitor is identified by the reference letter rAJ of rWAaJ. The lower case letter refers to the phase of the winding. Therefore, considering the stator windings WAa and WBa, both stator windings are connected by the lower case raJ such that winding WAa is connected in series with capacitor CBa and stator winding WBa is connected in series with capacitor CBa. Since they are connected in parallel to the passacitor CBa, they are connected in series with each other. Referring to Figures 1LA through 1LL, one of the physical differences between conventional motors and the motor of the present invention is that the motor of the present invention is located between two stator windings. It is equipped with an additional winding. 1st. Diagram IA shows the circumferential arrangement of teeth TA, TK and TE. Referring to this figure and FIG. 8 together, the power input sum A is applied to the winding WBa wound around the tooth TA at the same time that current flows through the winding WBb wound around the tooth TE. However, the winding W A e is wound around the teeth TK and TL, and the winding is 1 turn A! Interleaved in the circumferential direction between WBa and WBb. The circumferential positions of other stator teeth are not shown in FIG. 11A for clarity of illustration. Figure 11B shows the rotor rotated 30' clockwise by the rotating magnetic flux wave. It shows ro. In this case, the magnetic flux wave cuts the stator winding IIAWAc wound around the teeth TK and TL. As soon as the potential between power terminals A and B reaches its peak, the energy stored in capacitor CBa begins to discharge into winding 11WBa. This energy, together with the energy stored in the magnetic field of WAa, is transferred to the winding WBa and the teeth TA and TB are Set the magnetic flux pattern through each of these air gaps, the return magnetic material of the rotor, and the return path or rear iron section Bl. This flux path is similar in a general sense to that shown in FIG. 11L, where the motor is designated at 330@. Also, a potential is established in the positive direction with respect to terminal C, causing current to flow through stator winding WAe, and capacitor Trying to charge Pacita CBc. When this current starts to flow in WAe, the magnetic field of WBc starts to collapse, and the energy multiplied by WBc&:W then flows into the first winding WAc. It is stored in the capacitor CBe and the new magnetic field in the winding WAc, along with the energy that has been released. This moves the position of the magnetic flux wave 30" clockwise relative to the 0 shown in Figure 11A. This process continues as long as the polyphase source is applied to motor terminals A, B, and C. .Therefore, for each new cycle of alternating current, one winding of the motor denoted by the letter WA, i.e. WAx (where X is a, b or C) (winding connected in series with a capacitor) Let's charge the capacitor of each of them. A magnetic field is established in these windings and an electric field or potential is generated across the associated capacitor. As each magnetic field in the motor collapses, the energy stored in that field is converted into a current that is stored in its associated winding pair or in its associated capacitor. It will be done. On the other hand, when each capacitor discharges, the stored energy is converted into current. and flows to any of its associated windings. Therefore, a highly efficient system of coordinated energy transfer and exchange has been established. At the same time, a rotating magnetic field similar to that shown in FIGS. 11A-11L is generated. The magnetic center of the rotating magnetic flux wave moves one tooth clockwise for every 30 degrees the polyphase source advances. There is also a check and balance network. It is clear that there are Since all the windings have a high coupling coefficient to each other, excess energy from one circuit phase is transferred directly or indirectly to another part of the network. sent. This balanced rotating magnetic flux wave or pattern is The magnetic flux wave, which continues one revolution throughout the entire cycle, advances one complete revolution. When the motor is at rest or stopped, the polyphase source connects motor terminals A, B, and and C, the rotating magnetic flux waves cut through all the rotor windings of the WC, resulting in a high level of net equivalent susceptance. This causes a significant amount of current to flow in both the stator and rotor windings, most of which is converted into mechanical torque that tends to synchronize the rotor with the rotating magnetic field. As the rotor speed increases, the rate of winding break and the net equivalent susceptance decrease, reaching the theoretical ○ at synchronous speed. do. Since the rotor winding BWC is closely magnetically coupled to the main stator winding, the unused energy of the rotor winding mwc is returned via magnetic coupling to the reactive elements (WAx- WBx or CBs, x is a, b or C) or step Accumulated in the data circuitry. This feedback also adjusts the Q-factor of the resonant circuit. and adjust the amount of energy required from the power source. In the rotor locked state, ORPM, the frequency of the rotor current is the same as the line frequency, but decreases with the speed of the rotor and eventually reaches 0 at the synchronous speed, as shown in FIG. Figures 12A and 12B show the line current (IL) applied to one phase of a three-phase power line connected to a quasi-double-resonant polyphase motor, which is a double-resonant 40-horse motor. The relationship with electromotive force (line voltage VL) is shown. Power input was 460 volts, 3 phase. Figure 12A shows the line voltage and line voltage at full load. Figure 12B shows the relationship between line voltage and line current at a 5% shift load. Note that the line voltage VL is in phase with the line current IL and the power factor of the circuit is 1 over the entire load range as shown in FIG. Another unique and desirable characteristic is a flattened waveform of the current component. Because the current IL is non-sinusoidal, its RMS or effective value is very large, so that the transfer of magnetic energy is much stronger than that produced by a standard sinusoidal current. It becomes a powerful thing. This allows the current to perform the same function as a conventional motor without driving the core into saturation, reducing hysteresis losses in the magnetic core material and reducing the coercive force required to return the magnetic material to zero. That is, the energy is reduced to 0. Reducing harmonics also reduces eddy current losses in the magnetic core material. When operating a quasi-double-resonant polyphase motor, it was found that the quasi-double-resonance equalizer circuit is thought to limit how the polyphase motor can be used. This is because it is not possible to change the rotation of the motor simply by reversing the phase order of the inputs (A-B-C changes to A-C-B), as is usual in today's standard designs. It is from. Also, for different operating voltages, the capacitive reload required to maintain a suitable Q-factor is It is necessary to vary the amount of actance. These drawbacks can be overcome by the switching network shown in Figure 13. Wear. Switching of motor rotation. This is done by two reversing contactors (C1, C2) and (C3, C4). For one direction of rotation, C2 and C4 remain open while C1 and C3 close. Reverse switching exists for rotation in the opposite direction. This network essentially consists of the top two reversing the phase sequence and the bottom two responding to this phase change. It consists of two reversing motor contactors connected to reverse the windings. By sacrificing the admittance multiplier of the series resonant branch, it is possible to connect the -order stator winding directly to the input polyphase source, for example by connecting winding WAa with terminal A' to form a Y configuration as in Figure 14B. and connect the secondary stator winding to the Δ configuration (Fig. 15) or are wired in a Y configuration (Figure 14B) and kept floating relative to the primary stator winding, e.g. WBa', or by being closely magnetically coupled to it. A similar result is obtained, namely a balanced rotating magnetic flux wave. The angular displacement of each winding can be varied to give the motor different rolling characteristics. Therefore, the invention is not limited to any set angular displacement of the five windings. The concept of parallel floating is shown in Figures 14A, 14B, 15, 16 and and the electrical circuit diagram in FIG. Since the floating stator winding (secondary) is only inductively coupled to the power supply, the secondary winding can be chosen to use the most economical amount of capacitive reactance. . A capacitor CBx (where X is a, b or C) is connected in parallel with WBx to form a parallel resonant circuit. Its Q factor is determined in the same way as for the pseudo double resonant circuit. A combination of a floating pseudo-parallel resonant circuit and a phase winding is a pseudo-double resonant circuit. Acting similarly to a swing circuit, energy is transferred magnetically between the two-turn pair and the rotor winding. The source is determined by the mechanical torque of the rotor and the resistance of the circuit by viewing the primary winding as having a reactance O, or power factor of unity. A zero circuit that is good at supplying only the power that is The rotation of the rotor can be changed simply by reversing the rotation direction. In addition, the capacitive resonant circuit It is also possible to use dual voltage primary circuits without changing the actance. Quasi-double-resonant polyphase motors can be used where fairly low inrush current control is required but their operation does not need to be reversible. For motors that require high starting torque and easy reversal, floaters are recommended. parallel resonant motors are more suitable. The secondary stator windings 1WBx can be connected as if they were individual single-phase circuits. Each of these connections can provide the motor with different operating characteristics, such as those obtained with Y-Δ starting. Figure 14A shows the parallel resonance or parallel floating polyphase alternating current of squirrel cage rotor design. 2 schematically shows a flow induction motor. This motor is made of sheet steel laminated steel. It comprises a rotor ST2 and a rotor RO made of the same material. Due to N singleization, stay Although the motor is shown as having 12 magnetic poles or teeth TA, TB, TC...TL projecting from the return path or rear iron part BI2, the actual number of these teeth is Depends on physical size, horsepower and rotational speed. The physical dimensions of the motor and its integral parts are shown here for illustrative purposes only. The stator may not be sown in Δ or Y configuration, which does not represent the optimal physical structure of the motor. It is equipped with three primary phase windings that can be connected to a ground, and three sets of floating parallel resonant circuits, one set for each input sum. The three primary phase windings WA a', WAb' and WAc' are connected to input terminals A, B and C in a Y configuration. Ru. The three secondary stator windings WBa', WBb' and WBe' are In FIG. 14, it is connected in a Y-shape and is connected in parallel with three capacitors CBa', CBb' and CBc', which are connected in a Δ-shape. In this circuit, capacitor CB b' is in parallel with secondary stator windings WBb' and WBc'. As shown in FIG. 15, the parallel floating capacitor need only be in parallel with one secondary stator winding to form a floating parallel resonant circuit. The floating parallel circuit is composed of secondary windings WBa' + WBb' and WBe' and capacitors CBa', CBb' and CBc'. The secondary stator windings are wound respectively in the lower stages C, TD, TG, TH, TK and TL. - The next stator phases aWA a ′, WA b ′ and WA c ′ are wound around teeth TA-TB, TE, TF, TI and TJ, respectively. The secondary windings are circumferentially interleaved between the secondary windings, eg, WBa' is interleaved between WAa' and WAb'. The floating circuit is magnetically coupled to the negative phase winding and the rotor RO. Actual phase shift between two primary winding sets The positions differ from those shown and can form everything from close bonds to zo1 bonds. These changes give the desired changes in the motor's operating characteristics. However, the present invention is not limited to the embodiment shown in FIG. 14A.6 The principle of operation of the motor shown in FIG. 14A will be briefly described below. When a polyphase alternating current potential is applied to input terminals A, B, and C, the negative phase windings WAa', WAb', and WAc' are as shown in Figures 11A-11L for standard motor designs. Generates a rotating magnetic flux wave similar to the one shown. This is because these windings are connected to the source just like the windings in a standard motor design. When this magnetic flux wave rotates in the magnetic material of the stator, the magnetic flux becomes a floating The parallel circuits WBa', WBb' and WBe' and the winding WC of the rotor RO are disconnected. This creates a potential in the windings of the floating circuit and In this case, current flows through the two windings, causing their associated teeth to flow through their respective air gaps. A magnetic field is set in the magnetic material RO of the rotor and the material of the return magnetic path, that is, the rear iron part BI2. determined. Energy stored in capacitors CBa', CBb' and CB e' The energy is released into each winding in the form of a current. This ability of the quasi-parallel resonant circuit to sustain oscillations represents flywheel action and is an important feature of motors. The parallel bloating circuit not only generates the necessary magnetizing current, but also attempts to equalize the magnetic energy of the poles. That is because is floating in nature and therefore regulates the flow of energy into the rotor windings. This is because it will be adjusted. This is an intermediate exchange of energy between two windings or is the most efficient topology. motor glue acti Since unused energy is stored in the active elements, the source must supply the energy necessary to provide the required mechanical torque and of course to replenish the energy expended.

[I is fine. Therefore, the motor has a power factor of 1 or below over its entire load range. It operates near. Referring to FIGS. 18A and 18B, the current waveform IL is flat. Note at the top, Figures 18A and 18B are similar to Figures 12A and 1, respectively. For motors of the type described in connection with Figure 2B, the activity at full load and at 75% load is It shows the relationship between line voltage and wine current. This current waveform is highly desirable. This is because the RMS energy level is a sine wave. 1 novel, because more energy transfer occurs within the same time frame. It is. Therefore, only low current components are required and copper losses in the associated motor windings are reduced. It will be less. Another important feature is the symmetry of the magnetic flux waves cutting through the winding WC of the rotor RO. Ru. This symmetry, caused by the intermediate exchange of energy between two windings, The physical magnetic adjustment makes the rotor's net magnetic coupling stronger, which in turn reduces losses. decreases. This particular topology requires motor windings and complex switching machines. The 7-parallel branch winding allows you to directly reverse the motor without having to reconfigure the structure. Since it is floating, it is similar to the secondary winding of a transformer. This makes it possible to Reduces the cost and physical size of the capacitor needed to obtain a reasonable Q-factor You can choose the windings and connections as you like. I mentioned the three-phase motor, but The scope of the present invention is intended to include polyphase motors constructed in accordance with the principles of the present invention. do. Features of the invention include a 173 horsepower Marathon single phase induction motor. Table 1 shows the 1M type ]/3 HP Marathon single-phase induction motor. performance with the same motor rewound to incorporate quasi-double resonance technology. It is for comparison. 1/3 horsepower marathon single phase induction motor Model: 5PB56C17F5302A marathon pair pseudo double resonance before after Kudan breath fish cargo 衾ゆ亙 fish and lotus 衾fish藉 horsepower 0.00 0.3301 0.0 0 0.3303 Line voltage 230.352 230.256 230.01 230.976 line current 2.5227 2.9492 0.5454 1 ．． 4455 line frequency 60.0 60.0 60.0 60. ORPM 1 792.8 1759.5 1795.2 1760.4 Torque (oz, in, ) 0.0 11.82 0.0 11.82 Watt 154.7493 42 1゜4933　122.0228　331.5053VA　581.1090　 679.0709 N25.4475 333.8758VAR3560,12 53532, 424329, 112139, 7151 Power factor 26.63% 62 ．． 07% 97.27 and 99.29% efficiency -58,4235% -74,2 8% ambient temperature 22.2507 22.8080 22.4563 22.91 09 case temperature 50.7649 51.1410 39,4897 39.7 817 Bearing temperature 45.0604 46.5713 36.3931 3 7.9134 Breaking torque 35.58 (oz, in,) 35. Fi5 (oz, in,) rotor lock 1-luke 37.62 (oz, in,) 54.42 (o z, in,) Rotator current 15.37 8.301 Sound pressure level 85 d B SPL 81 dB 5PL (linear) (linear) Table 2 compares the winding specifications of the original marathon motor and the pseudo double resonance motor. It is. lord of feces 1/3 horsepower marathon single phase induction motor Model: 5PB56C17F5302A marathon/pair/pseudo double resonance winding specifications 1-8 0.9807853 37 36.289061-6 0.83146 93 33 27.438501, -4 0.5555703 29 16.1 1154 total effective number of turns/pole 79°83910 Wire size: 1#20AWG Lateral displacement 90° electrical angle ! -80,98078536865,693401-60,831469352 43,236421-40,55557033217,77825 Total effective number of turns / pole 127.70810 wire size: 11Fi9Awa Lateral displacement 90° electrical angle Specification of pseudo double resonant winding Motorcycle A, 51 members, y people Span Danjigo Koki (Kaiku 1 Happi count 1-8 0.9807853 50 49.039271-6 0.8314693 54 44.899361-4 0.5555703 32 17.77825 Total effective number of turns/pole 111.7 1690 wire size: 1$23AWG Lateral displacement 90' electrical angle Koda f purchase WB Span Uni-dama” Shugetsu Cap 1-8 0.9807853 50 49.039271-6 0.8314693 54 44.899361-4 0.5555703 32 17.77825 Total effective number of turns/pole ill, 7 1690 wire size: 1 #22 and] #23 pole displacement 90° electrical angle Table 8 shows the test data of the marathon motor after changing the motor to a pseudo double resonant circuit. This shows the data. Individual L 1/3 horsepower marathon single phase induction motor Model: Data after changing to 5PB56C17F5302A pseudo double resonance circuit Ta1tff l! −Xia Yi Watt Grave A mushroom Winding W A 153.40 0.5458 72.87% 61.0109 Winding W winding 188°202°5760 12.50% 60.6004 capacitor C.B. (43mfd) 188.20 3.0100 0.0009% 0.5098 Power supply 230.00 0.5458 97.27% 122.1069 JW Winding wire W A 158.10 N, 4410 69.00% 157.1973 volumes Wire W winding 167.10 N, 9660 53.00% 174.0107 kya Pacita CB (43mfd) 167.00 2.6570 0°0001 increments 0.3993 z source 230°001°4410 IG, 9%331.09861 Nishiri-2- the law of nature Winding WA ill. 00 L310 77.17% 711.8238 winding W winding Line 153.10 10.960 70.19% 1] 77° 77] 4 Capacity Ta CB (43mfd) 153.10 2.422 0.0003% 0.1H2 kya Pacita CA (145mfd) 153.10g, 550 0.000g 1.0472 Source 230,00 8.310 98.93% 111190.8491 All Testing was conducted according to IEEE standard 112-B. These tests I used Lebov's torque sensor and Ohio Semi-Trax. Ink (Ohio Se+++1tronics. Inc.) electric quadrupole transducers, voltage transducers and current transducers All authors are from the United States National Bureau of Standards (U, S, National Bureau). The test system is within the current calibration conditions that comply with 5 standards). Calibrated. Magtrol (Mag) is used to load the motor being tested. trol) hysteresis brake was used. The right size for all cases Rebow's inline rotating shaft torque sensor is connected between the motor and the load. It was. The signal was processed with a Daytronjc strain gauge regulator. Powered by Compudas computers. Also, computer The controller includes an electronic high-precision voltage transducer, an RMS voltage transducer, RM S current transducer, frequency transducer and thermocouple? Information was also provided. Computers continuously integrate, collect, and process data from all these sources. The system was compiled into a coherent form for display and communication. Also, test system Some parts of the system are unbalanced even at balanced voltages to the desired degree. It was a large variable transformer that could be tested at voltages as low as . All readings were taken after running the motor under load for 30 minutes. sound pressure level The Quest Elec was installed in a Ray Proof double-walled acoustic chamber. Quest Electronics Model 215 Sound Level Mechanism 1 foot Mt was also obtained by the data. As shown in Table 2, when the motor is in its initial manufacturing condition, the two The effective number of turns of the windings is not equal (the starting winding has 79.8 turns and the operating Sa is 127:7 turns), and after re-creating the quasi-double resonance condition, the two windings are This change results in a perfectly round rotating magnetic field with the same number of turns (111.7 each). The quasi-double resonant technique can be implemented using small diameter wires. In addition to increasing the loading factor, it is also possible to use a smaller motor and/or a motor with less magnetic loss. can be manufactured. As is clear from the above numbers, the wires used are is less than half the size of the wire. Table 3 shows that the power factor is kept at ':1 over the entire load range (97.2 at no load). 7 to 99.9 at full load). Due to the accuracy of the test equipment, Easily the sum of the power measurements for each component equals the amount of power drawn from the power supply It is clear that energy in two windings even if the voltage, current and power factor are not equal. (Electric energy) is equal to Z at no load and at full load. Furthermore, Table 1 shows that the motor did not slip much after changing to the pseudo double resonant circuit. , high efficiency, high power factor, low temperature, low sound pressure level, and low inrush current. This indicates that the starting torque is high. The following claims are intended to cover the invention, with and without modifications disclosed herein. and shall cover all changes falling within the scope of. Fig, 5 C N7 + a: (i 勺LO I KOヱ) Kona N Jyo 1! F (Contents (work) without L) 5. No varnish) n condolence (in '8 (2 no change) /7σ-24 Procedural amendment (formality) %formula% 3. Person who makes corrections Relationship to the case: Applicant 4. Agent 7. Contents of amendment as attached international search report l″lem*+″′l AINHN′M N11. PaT/US 87101 929　2 International Search Report

Claims (1)

[Claims] 1. a rotatable and excitable rotor; and a fixed operatively associated with said rotor. a stator and at least two windings electrically connected in series; each forming a pair of magnetic poles disposed within said stator near said rotor. two windings, and capacitor means combined in parallel with one of said windings. The combination is connected in series with the other winding, and the size of the capacitor is , a quasi-parallel resonant circuit is formed with the one winding, and a quasi-parallel resonant circuit is formed with the other winding. An induction generator characterized in that the size is such that a quasi-series resonant circuit is formed. . 2. further comprising at least one pair of power input terminals, the terminals being connected to an alternating current power source; and wherein the series-connected windings are connected across the input terminals. 1. The generator motor according to 1. 3. The rotor has a plurality of longitudinally insulated conductors, and the stator surrounds said rotor and extends radially toward said rotor. The above winding is equipped with teeth and the above magnetic pole through the above teeth when this is energized. is established, energy is transferred from the energized winding to the above rotor, and the above rotor energy is returned to the winding and this returned energy is transferred to the capacitor. According to claim 2, a balanced rotating magnetic field is produced by accumulating the magnetic field in the magnetic field. The generator motor described. 4. The power generator according to claim 1, wherein the rotor surrounds the fixed stator. Electric motor. 5. The capacitor means comprises at least one AC bipolar electrolyte type capacitor. The generator motor according to claim 1, comprising: 6. further comprising second capacitor means arranged in series with the switch means; The structure is in parallel with said capacitor means and said switch means is normally closed. 2. The rotor according to claim 1, wherein the rotor is opened when the rotor reaches a certain speed. Generator motor. 7. The second capacitor means is essentially an AC bipolar electrolyte type capacitor or and an AC bipolar electrolyte type capacitor. The generator motor included. 8. The capacitor means of the two quasi-resonant circuits are connected to two Acts as a phase doubler capacitor by forming a balanced phase The generator motor according to claim 2. 9. The phase voltage generated for each of the above two windings is equal to the applied phase voltage. 2. The generator motor of claim 1, wherein the generator motor is approximately equal to 2 divided by the square root of 2. 10. The windings connected in series above have an effective number of turns starting from the same number of turns in each winding. The generator motor of claim 1, wherein the generator motor is wound with a ratio up to 1.05:1. 11. The above series connected windings essentially mean that the wire size is The generator motor according to claim 1, wherein the generator motor is wound in a range from the same size to a ratio of 1:2. Machine. 12. The above series connected windings are wound with unequal wire sizes. has a quasi-series winding as the winding of the smallest circular mill area, and 12. A pseudo-parallel winding as a winding in the largest circular mill area. The generator motor included. 13. An air gap is provided between the teeth and the rotor, and this air gap is completely 2. The generator motor of claim 1, comprising a completely round rotating magnetic field. 14. Due to the decrease in the winding current, the generator motor will move below the saturation state of the BH curve. The generator motor according to claim 1, which operates in a linear section. 15. The quasi-resonant windings are offset from each other by an electrical angle of 60° to 130°. The generator motor according to claim 1. 16. 16. The quasi-resonant windings are offset from each other by an electrical angle of approximately 90°. The generator motor included. 17. The above stator is a hollow cylindrical stator with slots in the longitudinal direction. and said at least two windings are arranged in said slot around the interior of said stator. The above generator-motor is A longitudinal slot located in the internal space defined by the stator above. A rotatable rotor with a and a rotor winding electrically connected to the stator winding and the rotor winding. The wires are magnetically coupled together and under virtually all load conditions, the capacitor Energy is stored and supplied by the stator, stator windings and rotor windings. 2. The generator motor according to claim 1, wherein a balanced rotating magnetic flux wave is generated. 18. The capacitance value of the above capacitor is selected to form the above pseudo double resonant circuit. The Q factor of the above pseudo double resonant circuit is determined by the admittance of the rotor winding. 18. The generator motor of claim 17, wherein the generator motor is continuously regulated. 19. Polyphase power is supplied at the same number of power phase input terminals and can rotate above rotor supports multiple interconnected rotor windings, The stator surrounds the rotor and is arranged on the stator. A pair of series-connected stator windings is provided for each phase of the polyphase power supply. , each pair receiving a separate phase of said polyphase power supply via one of said power input terminals. and magnetically coupled to the rotor windings, and each of the stator windings. Each pair includes a respective capacitor means, each capacitor means being connected to the pair. is connected in pseudo series to the first winding of the winding, and in parallel to the second winding of , the size of each capacitor means is such that each quasi-series resonant circuit with the first winding is and each quasi-parallel resonant circuit is formed with the second winding. The induction generator motor according to claim 1, which has a size. 20. All pairs of the stator windings are connected in a delta configuration to the input terminals. The generator motor according to claim 19. 21. All pairs of stator windings are connected in a wye configuration to the input terminals. The generator motor according to claim 19. 22. Polyphase power is supplied at a plurality of input terminals, and the rotatable rotor is configured to It has multiple interconnected rotor windings, the at least two windings arranged on the stator for each phase of the multiphase power; A separate primary stator winding is selected from the receives different phases of said multiphase power and magnetically couples said rotor windings. and a separate secondary stator winding selected from the other of said at least two windings. is provided for each primary stator winding, and in the stator the primary stator winding is The secondary stator windings are arranged circumferentially interleaved between the theta windings and A wire is magnetically coupled to the primary winding and magnetically coupled to the rotor winding. And furthermore, A capacitor is provided for each secondary stator winding, and the capacitor is , in parallel with the at least one secondary stator winding and said at least one Size such that it forms a quasi-parallel floating resonant circuit with the secondary stator winding. The induction generator motor according to claim 1, which is an induction generator motor. 23. The voltage in the floating winding circuit is the voltage in the phase winding multiplied by the number of turns in the phase winding. and dividing it by the number of turns of the floating winding The generator motor according to claim 22. 24. The phase windings connected to the power supply consist of approximately 2/3 of the total circular mill area of the stator. The generator motor according to claim 22. 25. Floating windings, which are not physically connected to the power supply, are 23. The generator motor of claim 22, comprising about one-third of the area of the motor. 26. 23. The floating windings are arranged at an angle to each other. The generator motor included. 27. The floating windings are arranged at an electrical angle of approximately 90° to each other. 23. The generator motor according to claim 22. 28. The generator according to claim 22, wherein the secondary stator winding is not directly connected to the input terminal. Electric motor. 29. Polyphase power is supplied at the same number of power phase input terminals and can rotate above rotor supports multiple interconnected rotor windings, The rotor surrounds the fixed stator and is arranged on the stator. A pair of stator windings connected in series are provided for each phase of the multiphase power. each pair is connected to a different one of said polyphase power via one of said power input terminals. and magnetically coupled to the rotor windings, and the stator of each pair. A respective capacitor means is provided for each winding, and each capacitor means is is connected in pseudo series with the first winding of the pair and in parallel with its second winding. The size of each capacitor means is such that each quasi-series resonant circuit is formed with the first winding. and the second winding to form respective quasi-parallel resonant circuits. The induction generator motor according to claim 1, wherein the induction generator motor is 30. 23. The power generator according to claim 22, wherein the stator surrounds the rotor. Motive. 31. 23. The rotor according to claim 22, wherein the rotor surrounds the fixed stator. The generator motor included.