JPH01501190A - Upstream link and downstream link combined satellite antenna feed network - Google Patents

Abstract

(57) [Summary] This bulletin contains application data before electronic filing, so abstract data is not recorded.

Description

[Detailed description of the invention] Upstream and downstream links Coupled satellite antenna feed network Background of the invention The present invention relates to a microwave transmission network, and particularly to an artificial satellite power supply network. It is related to The satellite antenna feed network is the radiator of the antenna feed array. control the amplitude and phase distribution used to excite the radiation elements, and thus the antenna radiation. control the radiation pattern.

Communication satellites are used to provide communication links between ground stations. many In applications, satellites function as communication repeaters, transmitting data from one station to the other. Receives the flow link 2 signal and sends it “downward” to the other ground station that makes up the link. The signal is retransmitted as a current link signal.

A satellite is typically coupled to an antenna system for receiving upstream link signals. a transmitter coupled to an antenna system for transmitting downstream link signals. including transmitter. To minimize interference between upstream link signals and downstream link signals , separate upstream link and downstream link frequency bands are used. Satellites are also A frequency in the downstream link frequency band from a frequency in the upstream link frequency band to a frequency in the downstream link frequency band. and frequency conversion means for converting the upstream link signal into a link signal.

In traditional communications satellite designs, upstream and downstream link coverage A separate feed network for the antenna system is used to couple the receiver to the antenna system. A separate downstream link network is used to couple the transmitter to the antenna system. It is used to Separate feed networks are attached to a common antenna feed array. When connected, each frame transmits upstream link and downstream link signals to each feeder network. It is necessary to place a frequency detection diplexer at the input of the feed element.

The use of separate upstream link and downstream link power networks is expensive and takes up space. and increase the weight of the ship. As well as the size of the spacecraft, the weight also depends on the launch conditions. Limited.

Therefore, for relatively lightweight, space-efficient, and low-cost communication satellites, It is advantageous to provide a power supply network.

Summary of the invention Improvements for coupling satellite antenna systems to satellite receivers and transmitters The microwave power supply network has been revealed. According to the invention, the signal broadband A regional upstream link and downstream link power supply network is used. The power supply network is feeder network to separate the received and received signals and couple them to the receiver and transmitter. Contains a single, frequency-sensitive diplexer in power. The feed network further includes an antenna system. signal broadband cooperative feeding network for coupling to each antenna radiating element that makes up the system including. The diplexers and elements of the cooperative feed network are similar to the antenna radiating elements. is adapted for wideband operation across both upstream and downstream link frequency bands. It will be done. The present invention has consistent satellite reception and transmission beam coverage and is low cost. These and Other features and advantages are shown in the accompanying drawings below. This will become clearer from the detailed explanation.

FIG. 1 shows a simplification of a combined upstream link and downstream link power supply network according to the present invention. FIG.

FIG. 2 shows the end of a broadband coupler which preferably includes the feed network of FIG. It is a diagram.

3 is a plan view of the coupler of FIG. 2 taken along line 3--3 of FIG. 2; FIG.

FIG. 4 is a longitudinal cross-sectional view of the coupler taken along line 4--4 of FIG.

FIG. 5 is a longitudinal cross-sectional view of the coupler taken along line 5--5 of FIG.

FIG. 6 shows the phase diagram for each of the two phase shifting parts of the coupler of FIG. FIG.

FIG. 7 is a top schematic view of a typical horn antenna.

Figure 8 shows the different horn lengths as a function of horn length at selected high and low frequencies. FIG. 3 is a diagram of the horn phase delay for a two horn antenna with an aperture size of .

Figure 9 shows the phase as a function of horn length for two horns with different aperture sizes. FIG. 3 is a diagram of delay.

Figure 10A shows a simplified reference horn antenna with a total length of 12 inches and a 2 inch aperture. This is a schematic diagram.

Figures 10B and 10c show a host having a length of 12 inches and an opening of 4 inches. is a simplified diagram of a main antenna, each operating at two different frequencies within the frequency band of interest. Efficiently utilized (combined upstream and downstream links using the present invention) A simplified schematic of the supply network is shown in FIG. satellite antenna system The system includes multiple wide-bandwidth, non-frequency dispersive horns used for receiving and transmitting. Includes 0-87. Antenna 6°-67 is dioptered by a cooperating feed network 20. Coupled to the lexer 5, the feed network 20 includes a plurality of wide bandwidth non-frequency dispersive cups. 21.25.30.32.34.36 and 38.

The diplexer device 5 receives substantially all signal power in the upstream link frequency band. 10 to substantially couple the signal power in the downstream link frequency band to the receiver. A device that is sensitive to frequencies that are configured not to. Therefore, diplex The function of the server device 5 is to separate the upstream link signal from the downstream link signal. da The Iplexer provides very good separation between the received and transmitted signals and also 5 is configured to transmit a relatively high signal power provided by.

It is noted that the network revealed in Figure 1 uses a single diplexer device 5. It will be done. This means that separate feed networks for upstream link and downstream link signals are used. This contrasts with conventional technology designs that can be In conventional technology, the horn antenna is located upstream. Although shared by link and downstream link signals, separate diplexers are typical The upstream and downstream link signals that power each upstream and downstream link network are Used on each horn antenna to separate link signals.

Since the diplexers are distributed in the horn according to the antenna pattern, these The diplexer in prior art designs is The signal does not need to be designed to transfer power, but only a portion of the power. There is only that. For example, the diplexer 5 in the disclosed embodiment has a kilowatt However, in the prior art, each horn is Each diplexer placed in the It is only required to do so. Diplex for transmitting higher power levels The design of the sensor is conventionally known in the art.

Diplexer 5 is coupled to a cooperating feed network 20, which 6 and each antenna horn 60-87 to the network 20). 60a-67a. well known by those skilled in the art The associated Each phase delay and attenuation affects the beam pattern of the antenna system. times The network 20 includes a diplexer 5 and a transmitter 15 between each antenna boat 60a-67a. divide the downstream link energy input into network 20 on line 6 from Combines and downloads the upstream link energy received at ports 60a-87a from the antennas. Energy coupled to boat 6 for coupling via iplexer 5 to receiver lO It operates to supply.

Therefore, the coupler device including network 20 will be discussed in the following description as a power divider. Although disclosed, it is understood that this device also operates as a power combiner in reverse. be done.

In the circuit network shown in FIG. Wideband phase compensation coupler 21.2 to divide the signal power between 60a-67a 5.30.32.34.38.38. Network 20 further performs additional phase compensation. Phase adjustment trombone 41.43.45.47.49.51.53.5 Contains 5.

The resultant force is 21.25.30.32.34.38.38 of the separated boats. each terminated in a matched load. As mentioned above, a coupler is a coupling The input power given to the input port between the pass port and the coupling port according to the factor To divide.

The input port 21a of the coupler 21 is connected to the input port 21a by the transmission line 6 of the power supply network 20. It is coupled to the plexer 5. The passage port 21b of the coupler 21 is connected to the transmission line 23. Therefore, it is coupled to the input port 30a of the coupler 30. Coupling port of coupler 21 port 21c is coupled to input port 25a of coupler 25 by transmission line 22. Ru.

The passage port 34b of the coupler 34 is connected to the transmission line via the phase compensation trombone 47. 46 to the antenna boat 63a.

The coupling port 34c of the coupler 34 is connected to the transmission line 44 via the trombone 45. and is coupled to the antenna boat 62a.

The passage port 32b of the coupler 32 is connected to the transmission line 40 via the trombone 41. and is coupled to the antenna boat 60a. The coupling port 32c of the coupler 32 is It is coupled to the antenna port 61a by the transmission line 42 via the long port 43. Ru.

The passage port 38b of the coupler 3B is connected to the transmission line 48 via the trombone 49. and is coupled to the antenna boat 64a. Combined PoH8c is Trompone 51 via transmission line 50 to antenna boat 65a.

The passage port 38b of the coupler 38 is connected to the transmission line 54 via the trombone 55. and is coupled to the antenna boat 67a. Its coupling port 38C is a trombone. 53 to antenna boat 86a by transmission line 52. A specific coupling factor and phase compensation of the coupler and a trompo that constitutes the circuit network 20. The phase compensation of the beam will depend on the specific application as well as its general shape and will be well understood by those skilled in the art. will be evaluated correctly by

Using the same network for both upstream and downstream link frequencies network components than if separate upstream and downstream link networks were used. It also requires a wider band. Upstream link and frequency band settings 1 Examples are 13.75 Ghz to 14.25 Ghz for upstream link bandwidth.

For the downstream link band it is 11.75 Ghz to 12.25 Ghz.

Therefore, for example, each component in the power supply network is between 11.75 Ghz and 14.2 Ghz. 5 GHz, or an operational bandwidth of approximately 2.5 GHz. required to create.

Referring to FIGS. 2-5, the circuitry 20 shown in FIG. A good hybrid coupler 110 is shown. This coupler 110 is 198 Patent Issue No. 782゜677 (“Phase Compensat ed　Hybrid　Coupler”.

M, N, Wong and W, J, Linholdt %docket PD - 84060), which is the subject of the same applicant as the present application. coupler 110 is formed from a first waveguide 112 and a second waveguide 114, each of which has a short It has a rectangular cross-sectional shape such that the ratio of long walls to long walls is 2=1. 12 For operation at microwave frequencies of GHz, waveguide type WR-75 is used. Ru. Each waveguide has two long walls: a top wall 11B and a bottom wall 118; They have short walls, namely the outer sidewall 120 and each of the two waveguides 112 and 114. They are joined by a common wall 122 which acts as an internal side wall. coupler 1 10 is 11.70H'z to 14.5GHz in the preferred embodiment of the present invention It is a very wide band device with an operating range of .

Coupler 110 hybridizes electromagnetic energy between two waveguides 112 and 114. Provides dual functions of decoupling and phase compensation. A cup of electromagnetic energy This is achieved by a gate 124 placed in the common wall 122. 3dB ( decibel) coupling, the gate 124 is always open and the waveguide 112 or 1 free space wave of electromagnetic energy measured along the longitudinal axis of either 114 has a fixed length approximately equal to the length. For a smaller amount of coupling For example, the length of gate 124 is 0.8 waveguide for 6 dB coupling. Reduced to tube.

Coupler 110 is shown as a pass-through port 126 and a coupling port 128, each with a There are two output terminals located at the ends of each waveguide 112 and 114. coupler 110 is further located at the end of the first waveguide 112 opposite the passage port 126 at the end of the second waveguide opposite the input port 130 and the coupling port 128. includes an isolation port 132. Separation port 132 connects the impedance of second waveguide 114 to - resistor 13 representing a non-reflective load with an impedance matched to the 4 is shown schematically connected to. Such loads (not shown) ) typically absorbs electromagnetic energy at the operating frequency of coupler 110. The isolation port is configured in the form of a wedge with a flange (not shown). 132, attached in a conventional manner to a portion of the waveguide (not shown) connected to It is. In use, coupler 110 includes the circuitry shown in FIG. Connected to microwave circuit components such as. Such parts are normally , ports 126, 1 of coupler 110 by flanges (not shown) Includes waveguide fittings connected to 28 and 130.

of the coupling gate 124 in the common sidewall 122 of the two waveguides 112 and 115. The arrangement provides a right angle sidewall short slot hybrid coupler. Through gate 124 The microwave signal coupled between the two waveguides undergoes a phase shift of 90″ delay. , this phase shift is similar to the well-known right-angle sidewall short-slot hybrid coupler. It is action specific. The combined upstream and downstream links shown in Figure 1 In many microwave circuits, including the disclosed embodiments of link feed networks, , such a phase shift is not desired and some kind of phase compensation is required for the two waveguides 112. and 114 to equalize the phase between the microwave signals.

The necessary phase compensation is provided by a pair of waveguides placed in the first waveguide 112 beyond the gate 124. placed in the second waveguide 115 beyond the four capacitive apertures 13B and the gate 124. is provided by the use of a set of four inductive apertures 138. Waveguide 112 The shape of the capacitive aperture 136 in the middle is such that the phase leads to a 45° delay phase in the passing boat 12B. Shifter 140 is configured. The configuration of the inductive aperture 138 in the waveguide 114 is similar to that of the coupling port. The phase shifter 142 which introduces an advance phase shift of 45 @ is constructed by the step 128. Gate -90″ shift induced by 124 and +45″ induced by shifter 142 The coupling with the shift is the one 45 induced by the shifter 140 at the passage port 12B. @Gives -45'' at coupling port 128 to balance the shift.

A microwave network 10 transmits and receives communications by means of an antenna carried by an artificial satellite. Due to the use of coupler 11O in certain situations, such as when dealing with 0 is separated in the frequency domain by a blank band that provides interference between the two channels. configured with sufficient bandwidth to provide transmit and receive channels located at It will be done. The increased bandwidth of coupler 110 is on the outer side on the centerline of gate 124. This is achieved through the use of a stepped platform 144 placed on the wall 120. The base 144 is The width of waveguides 112 and 114 at gate 124 is reduced.

Each platform 144 has three steps 146a-e and risers 148a-e. Consists of steps. The dimensions of pedestal 144 are adjusted to achieve the desired bandwidth. can be Typical dimensions in terms of free space wavelength are: So The total length of step 146C is 1-1/4 wavelength, and step 146C is 1/2 wavelength; Steps 146b and 146d are each a quarter wavelength, and steps 146a and 146 Each e is 1/8 wavelength. Rising portions 148a and 148e are each 0.050 inch, the rising portions 148b and 148d are each 0.045 inch, and the square The rising portions 148c on each side of the step 48c are o and oeo inches, respectively. standing Each of the rising parts has a wavelength of 1/10 or more of the wavelength to minimize reflection from the base part 144. It is noteworthy that the lower

Regarding the configuration of phase shifter 140, the two central apertures 136 are equal to 1/8 wavelength. It has a high height, which is 0.110 inches at the operating frequency of coupler 110.

The remaining two apertures 13B at the ends of the aperture set are approximately 1/1 6 wavelengths, and this length is o, og at the operating frequency of coupler 110. o inches, which is shorter than the height of the center aperture 13B. Each of the apertures 138 has a thickness of 1/8 wavelength as measured along the axis of waveguide 112. Aperture 13B The centerline spacing between successive ones is equal to 1/4 of a wavelength. Each of the apertures 13B The width of the waveguide is approximately 0.2 inches, measured transverse to the waveguide axis.

The length of the wall segment adjacent to the capacitive orifice 13B is 1,000 mm. Capacity throttle The wall 136 is centered between the two side walls 120 and 122. Capacity aperture 13 6 is shown extending upwardly from the bottom wall 118, but instead... They may be configured to extend downwardly from the top wall 11B. 42 configuration, the two central inductive apertures 138 are located at a distance from the outer sidewalls 120. The remaining two outer apertures 138 are separated from the sidewalls 120 by 0.115 inches. It extends a short distance, or 0.110 inch. between the centers of the inductive aperture 138 The spacing is equal to 1/4 of the wavelength. The thickness of the inductive aperture 138 is approximately 178 free space wavelengths, measured along.

Other dimensions of coupler 110 are as follows. Adjacent to 130 The cross section of the common wall 122 is 0. It was the size of Twift. Waveguides 112 and 1 The space between sidewalls 120 and 122 of each of 14 is 0.75 inch, which is approximately It is approximately 3/4 wavelength. The overall length of coupler 110 is 3.6 inches.

Both the pedestal 144 and the inductive aperture 138 are located between the top wall 11B and the bottom wall 118. It extends over the entire distance. The desired phase shift and bandwidth are as described above. The two side walls 122 and 120 of the first waveguide 112 extend in only one direction, as The preferred embodiment achieves this by configuring the volume aperture 136 to have a certain width. can be obtained.

In operation, coupler 110 has phase compensation introduced to output terminals 126 and 128. It functions as a Ku band sidewall short slot hybrid coupler. Phase compensation is frequency The phase-shifting structure is non-dispersive in number and can be used in wideband power distribution networks. Allows the construction of the coupling device in a compact and lightweight assembly of the dam. Capacity level Phase shifter 140 introduces a -45" phase shift at pass port 126. Inductive Phase shifter 142 introduces a +456 phase shift in second waveguide 114. , it is about 190＠ that the phase shift is introduced by the hybrid coupling. Algebraically combined with phase shift. -45″ phase in the second waveguide 114 and The algebraic combination of 90° phase shifts yields a composite phase shift of -45″ with a 12g bonding boat. occurs, and this resultant phase shift is equal to 145@phase shift at pass port 126. . Therefore, in applying the radiant energy to the input port 130, it is necessary to connect the pass-through port 12B. The combined electromagnetic waves present at the coupling port 128 are in phase with each other.

FIG. 6 shows the frequency dispersion characteristics of phase shifters 140 and 142.

As is well known, the phase shift introduced by a phase shifter at one frequency is somewhat similar to the phase shift introduced at the other frequency. Coupler 110 is wide used over a range of frequencies and therefore the frequency dependence of the phase shift also results in shall be modified to prevent distortions in the antenna coverage pattern caused by Must be. The nominal value of the phase shift of the inductive aperture 138 and the capacitive aperture 136 is +45@ and -45@, but the actual value of the phase shift is the public value as a function of frequency. Changes from the nominal value. As shown in FIG. 6, inductive phase shifter 142 Introducing a phase shift of more than +45″ at low values of As the value increases, the value decreases toward the nominal value.

The phase shift introduced by capacitive phase shifter 140 is nominally smaller than the value and increases to the nominal value at higher frequencies.

However, the phase shift introduced by a series of inductive and capacitive apertures The difference between the signals remains constant at 90° over the desired band frequency range. Therefore, Ka The coupler 110 has an inherent 90″ phase shift associated with the eight-brid coupler. Compensate the frequency that induces the change in phase shift as given for broadband compensation. Make amends. As shown in Figure 6, the upper trace for the series of inductive apertures is Follow exactly the bottom trace representing the capacitance restriction of the series. Thereby, the coupler The phase compensation of 110 avoids frequency dispersion. This advantage is due to reduced package support. The associated mechanical advantages of reduced size and weight are obtained.

Horns 60-67 are also used for the desired upstream and downstream link frequency bands. is adapted for non-frequency dispersive operation on effective antenna system equipment. horn 80 −87 is the phase to the received or transmitted signal whose value is a linear function of the signal frequency. Introduce a delay. To achieve non-frequency dispersive operation, horns 60-87 each include: It has a phase delay versus frequency function that is not only linear but also has the same slope. This characteristic One of the known methods to achieve this is to use antenna system elements of equal size as using a horn.

Horn antennas are well-known antenna array components. typical horna The antenna is shown in the top view of FIG. 7 and has a flare length Lf and a waveguide length Lv. It has a total length Lh equal to the total sum of . Horn opening A is measured using the plane dimension of horn H. . The throat of the horn has a dimension Lt. The axial length La of the horn is the distance between the aperture and the protrusion of the horn. Measured between the intersection points of the flared walls.

United States patent application specification filed by a common assignee with the present invention (docket) nuo+ber P D -85175, “Horn Antenna Arra y Matched 0ver Large Bandwidth") Each horn has a different aperture size that allows it to phase track over a wide frequency band. An array of horn antennas is described. This array is a horn antenna and The antennas 60-67 shown in FIG. It is effectively used as

Because of the rectangular aperture horn, the phase delay through the horn (its electrical length) is primarily The H plane dimensions are determined by the length of the horn and the size of the throat opening of the horn.

The phase slope characteristic is defined by the phase delay of the horn per unit length of the horn. phase The slope shown in Figure 8 for a given opening and throat dimension, regardless of the horn length, is the required frequency. Two differences at two frequency boundaries (11, 7 and 14.5Ghz) of several bands shows the phase tilt of the horn antenna, where one horn has a larger aperture have the same overall length, bandwidth, and center frequency. For explanation of the invention , the horn with the smaller aperture is considered the reference horn. Line 220 is a low lap The phase slope of the reference horn at a wave number of 11.7 GHz is shown. Line 225 is a high frequency The phase slope of the same horn at several 14.7 Ghz is shown.

Lines 230 and 235 are low and high frequency, respectively, i.e. 11.7G Figure 2 represents the phase slope of the second horn at hz and 14.5Ghz. second horn Since the aperture of the first horn is larger than the aperture of the reference horn, it The phase delay caused by the second horn is larger than the phase delay caused by the reference horn. Hey.

In this example, the first horn depicted in FIG. 8 has a waveguide cutting length Lν equal to zero. shall have the following.

A standard waveguide whose cross-sectional shape matches that of the reference and second horn antenna throats. The phase slope of the cross section is also determined by line 240 for each of the required low and high frequencies. and 245 in Figure 8. For purposes of explaining the invention, a reference horn is used. Each phase retardation of the waveguide cross-section is equal in length to the desired high and low frequencies. is shown equal to or with reference to the phase delay of the reference horn at .

Line 2 represents the waveguide phase referenced to the phase shift of the reference horn at low frequencies. 40 is the low frequency line 230 or second horn at point A shown in FIG. intersects with the number phase gradient characteristic. Referenced phase shift of reference horn at high frequency Line 245 representing the waveguide phase slope is connected to line 235 or the second hoop at point B. intersects with the high frequency phase slope characteristic of the tone. Two points A and B are practically water It is significant that along the flat axis it occurs at the same value of length "Xo", as will be explained below. , the value of X represents the optimal flare length Lf of the second horn, and the value of Corresponding waveguide length needed to optimize the second horn for racking is Lh-Lf.

Therefore, Figure 8 shows the required total phase slope of the optimized horn and the optimal Given the parameters of the phase slope of the horn flare part and the waveguide part that are not represents an analytical solution for the determination of the lengths Lf' and Lv. This solution uses two lines. lines 235 and 245 and the intersection of two lines 230 and 240.

by a second horn with flare length and waveguide length selected as described above. , the phase slope of the waveguide section is cycled to maintain the value of X approximately equal to the same constant. Changes when the wave number changes. When the frequency increases, for a given flare portion The ideal flare length decreases and at the same time the ideal length of the waveguide section increases, and Thus, it compensates for changes in the electrical length of the two parts. Properly selected waveguide Depending on the length of the tube and flare sections, this mutual compensation can be achieved over a wide frequency band. The result is a horn with a substantially constant electrical length. Therefore, it is possible to The maximum length of the horn is determined by the difference in total horn length in the waveguide section. , reduce the flare length of each horn in relation to the flare length of the horn with the smallest aperture. By doing this, phase matching can be achieved over the frequency band.

The optimization is further explained by reference to the specific example shown in FIG. child In the example, the reference horn antenna is between 11.7Ghz and 14.5GhZ. 700’ phase delay at band center frequency and 2” opening over 12” overall length It has mouth dimensions. The second unoptimized horn antenna has a flare length and the same frequency. 800° phase delay in numbers and all the same physical lengths as the reference horn, and 4 It has an inch opening. When maintaining the physical aperture and length of the second horn, wide a second horn whose electrical length is equal to that of the reference horn over a wide frequency range; The goal is to optimize the

The phase slope of the reference horn is between the points with coordinates CX1a Yl) and (X3°Y3) is drawn by line 250. The phase slope of the larger horn is determined by the coordinates (Xl, Yt) and (Xl.

Y2) is drawn by a line 255 between the points.

This slope m1 is equal to Y2/X2 for the case where Xl and Yl are zero. standard waveguide The phase slope m2 of the tube section is between the points with coordinates (X4°Y4) and (X31Y3) It is shown as an elongated dashed line 260. The slope m2 is (Y, a - Y3) / (X 4×3). This phase slope m2 is also 360”/λ g, where λg represents the waveguide wavelength.

Two lines defining lines 255 and 260 with respective slopes m1 and m2 shown in FIG. The solution to the equation for the value x-Lf is the optimized one with a 4-inch aperture. Determine the flare length of the horn. y to X for line 255 with slope m1 The equation related to the value of is given by Equation 1.

y-(ml) x (1) The equation relating the values of y to X for line 260 with slope m2 is Eq. 2.

)'-Ya +X (m2) (2) Y4 mY3-(m2)X3, so equations 1 and 2 are their internal cuts It is solved for the point xmLf.

Lf'-(Y3-m2・X3)/(ml-m2) (3) To complete phase compensation The length of the waveguide section that needs to be cut off is simply the horn length Lf' minus the flare length Lf. ’, and the total horn length is equal to the total length of the reference horn. .

The above calculations are facilitated by a digital computer to automate the design process. Implemented. Exemplary programs for basic programming languages are This is given in Table 1.

The example of Figure 9 is further depicted in Figures 10A, 10B and 10C, which each A simplified top view of the reference horn (without wavelength section), with the desired low frequency ( 11,7GhZ) and a larger aperture horn optimized by this method. and the required high frequency (14,5Ghz) The aperture horn is shown.

The reference horn with a 2 inch aperture is 3894 at each of the high and low frequencies. ．． Total electrical length equivalent to a phase shift of 67’ and 5002.09’ It has a certain quality. Phase shift of a horn with a 4 inch aperture (not optimized) 4090.95' at 11.7GhZ, 5155.83 at 14.5Ghz Calculated as @. Therefore, the position between the two (non-optimized) horns is The phase dispersion is 198.25' at low frequency and 158.28'' at high frequency.

Using the computer program shown in Table 1, the horn design was 11.7Gh. z and 14.5Ghz. Low frequency (11.7Ghz) A length and waveguide length are calculated as 9.444 inches and 2.556 inches respectively. be done. This is shown in Figure 10B, where the unoptimized horn is shown as a solid line. The optimized horn is depicted as a dashed line. Optimal at 11.7Ghz The flared portion of the horn has a calculated phase delay of 3219.58°; The waveguide section has a total phase delay of 875.11'. Therefore, at 11.7Ghz The total phase delay of the optimized horn is 3894.69’, which is calculated exactly is equivalent to the phase delay of the reference horn. 14.5Ghz, optimized horn The flare part has a calculated phase delay of 4057.64° and the waveguide part has a calculated phase delay of 9 It has a phase delay of 49.50°. Total phase of horn used at 14.5Ghz The delay is 5007.14°, which is calculated at the same frequency by 5.05″ different from the reference horn phase delay.

Also using the computer program in Table 1, the horn design was Optimized. This is a slightly different calculated dimension for Lf' and Lf', That is, 9.35 inches and 2.643 inches, respectively. This design is shown in Figure 10C. is shown, where the unoptimized horn is drawn as a solid line and the optimized horn is depicted as a solid line. The horn is shown with a dashed line. Optimized horn frequency at 14.5Ghz The part A has a calculated phase delay of 4020.26°, and the waveguide part has a calculated phase delay of 981. It has a phase delay of 82°. Therefore, due to the horn used at 14.5Ghz The total phase delay is 5002.09'' and the reference hoop calculated exactly at this frequency. The phase delay is superior. At 11.7Ghz, the optimized horn flare section has a calculated phase delay of 3189.92' and the waveguide section has a calculated phase delay of 698.02' ’ phase delay. Therefore, at 11.7Ghz the horn used in Figure 4C The total phase delay through is 3887.94'.

This differs from the calculated reference horn for this frequency delay by 6.75'.

The mutual phase compensation obtained by the horn optimization is Further explanation from each phase delay of the flare and waveguide section at high and low frequencies. It will be done. 2.643 inch waveguide section is calculated as 981.82@ at 14.5Ghz 2.558" waveguide section has a phase delay of 949.50" with a difference of calculated phase delays, i.e. 32.32'. Corresponding 9, 35 ft. The flare part of the inch has a phase delay of 4020.28” at 14.5Ghz, and ．． The 444 inch flare section has a phase delay of 4057.64° at the same frequency, i.e. - There is a difference of 87,38@. The sum of the two differences (32,32'-37.38'') The total difference between the two horn optimizations at 14.5Ghz is -5,06' only. Causes phase dispersion. Therefore, two horns used at different frequencies are 14.5 have virtually equal electrical length in Ghz.

Similar compensation at the lower band edge (11,7 GHz) produces a phase dispersion of -6,75@ Jiru.

The calculated results for optimization at the upper and lower bounds of this bandwidth are Slightly better phase tracking across the band, but the horn has slightly better phase tracking characteristics at the lower frequency boundaries. Show what is achieved when used. In fact, the frequency at which the horn is optimized is typically Typically located between the low frequency limit of the band and the midband frequency.

As known to those skilled in the art, to avoid antenna pattern deterioration, the horn flap is The rare angle should be chosen to minimize phase errors across the aperture. Open The phase error across the horn with mouth A and axial length La is given by Equation 4: It will be done.

Δφ−(2π/λ)(((A/2)2+La2)”−La) (4) Ray Ray Using the (Reylejgh) standard, the maximum phase error should not exceed 90°. No. This limits the amount of phase compensation achieved by the horn optimization technique. do.

The described embodiment of the invention is such that the transmit and receive beams have the same coverage at the same time. Useful for applications where It means that only one feeder network connects upstream and downstream links. the same level of characteristics from separate circuit networks. cannot be obtained. This loss in characteristics is due to the frequency bands of the upstream and downstream links. Optimize each upstream link and downstream link network separately due to the characteristics in each arises from the ability to become However, for many applications, a single method according to the invention The advantages of the feed network outweigh the losses in characteristics. These advantages include Approximately 50 percent reduction in energy consumption, fewer components, and separate damascene in each horn. Including eliminating the need for Iplexer equipment and resulting cost savings.

The combined upstream link/downstream link feeding system connects the satellite antenna system to Designed for coupling to satellite receivers and transmitters. Examples described above It is understood that the following are merely illustrations of specific embodiments that may represent the principles of the invention. It will be. Other arrangements can be made by those skilled in the art without departing from the scope of the invention. It is devised according to the principle of

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Claims (12)

[Claims] (1) A frequency coupled to a transmitter and receiver for separating transmitted and received signals. wave number sensitive diplexer means, and the diplexer means is connected to each satellite antenna element. a cooperating feed network for coupling to said diplexer means and said diplexer means; The cooperating power supply network covers the satellite frequency band and the satellite transmission frequency band. A satellite antenna element system characterized in that it is adapted for wideband operation. Microwave feed network for coupling system elements to satellite receivers and transmitters . (2) Claim 1 in which the receiving and transmitting beam patterns of the artificial satellite match. The power supply network described in Section 1. (3) a plurality of antennas for coupling the cooperating feed network to each antenna element; a feed port and a diplexer feed port for coupling to the diplexer means. and wherein the cooperating power supply network transmits the data in accordance with the characteristics of the satellite beam coverage. A predetermined phase shift and 2. A power supply network according to claim 1, configured to provide attenuation. (4) the antenna system is a non-frequency antenna that spans the receive and transmit frequency bands; A feeding system according to claim 1, comprising a plurality of antenna elements adapted for multi-dispersion operation. circuit network. (5) The antenna element has an electrical length that substantially corresponds to the satellite reception and transmission. Claim 4 includes a plurality of antenna horns that are equal across the radio frequency band. power supply network. (6) said cooperating power supply network spanning said respective receive and transmit frequency bands; Multiple phase compensated waveguide hybrid cube adapted for non-frequency dispersive operation 2. The power supply network according to claim 1, comprising: a. (7) Across a satellite antenna system including multiple non-frequency distributed antenna elements. The upstream link signal is received within the upstream link frequency bandwidth, and the upstream link signal is received within the upstream link frequency bandwidth. In a communications satellite configured to transmit downstream link signals at A combined upstream link for coupling transmitters and transmitters to satellite antenna systems. link/downstream link feed network, the elements of said network being connected to said upstream link and Adapted to wide-bandwidth non-frequency dispersive operation across the downstream link frequency band A communication satellite characterized by being configured as follows. (8) the feed network is such that the upstream link signal is not coupled to the transmitter and the downstream link signal is not coupled to the transmitter; Separate upstream and downstream link frequencies so that signals are not coupled into the receiver Claims comprising diplexer means coupled to said receiver and said transmitter for Communication satellite described in item 7. (9) The feed circuit network has multiple antenna feeds for coupling to each antenna element. port and a diplex support for coupling to said diplexer. the same feed network, said cooperative feed network providing a desired satellite beam each upstream between the antenna port and the diplex support to achieve range 9. A communication satellite according to claim 8, which distributes link and downstream link signals. (10) the cooperating feeder network is connected to the diplex support and each of the antenna feeds; means for creating a predetermined phase shift and attenuation between the power ports; Each of said phase shifts and attenuations spans said upstream link and downstream link frequency bands. 10. A communications satellite according to claim 9, wherein the communications satellite has a substantially constant value. (11) The cooperating power supply network is connected to the upstream link and downstream link frequency bands. Multiple phase-compensated waveguide hybrid couples adapted for non-frequency dispersive operation across 10. The communication satellite according to claim 9, which includes a satellite. (12) In a non-frequency distributed system, the receiving and transmitting equipment of communication satellites is In a combined feed network for coupling to a satellite antenna, Satellite reception signals in the upstream link frequency band and satellite reception signals in the downstream link frequency band Frequency sensitive diode coupled to the receiver and transmitter to separate the star transmitted signal a plurality of antenna ports for coupling to the satellite antenna; Broadband cooperative feed circuit with diplex support for coupling to diplexer network, wherein the cooperative feeding network connects each of the antenna ports and the diplexer. between ports to predetermined signals in the upstream and downstream link frequency bands. A power supply characterized in that the power supply is configured to introduce a respective phase shift and attenuation. circuit network.