JP6943666B2 - NMR measuring device - Google Patents

Description

The present invention relates to an NMR measuring device, particularly to processing received data.

NMR (nuclear magnetic resonance) is a phenomenon in which an atomic nucleus placed in a static magnetic field interacts with an electromagnetic wave having a frequency peculiar to the atomic nucleus. An NMR measuring device is a device for observing the phenomenon and analyzing a sample at the atomic level. The NMR measuring device is utilized in the analysis of organic compounds (for example, chemicals, pesticides), polymer materials (for example, vinyl, polyethylene), biological substances (for example, nucleic acids, proteins) and the like. By using an NMR measuring device, for example, it is possible to elucidate the molecular structure.

Patent Document 1 discloses an NMR measuring device. In the device, the RF received signal is converted into an IF (intermediate frequency) received signal, and the IF received signal is sampled. The received data generated by the sampling is converted into complex received data by orthogonal detection. Filtering and FFT operations are applied step by step to the received data in complex format.

Japanese Unexamined Patent Publication No. 2016-024117

Time division measurement (Time Share measurement) alternately executes transmission and reception. It is also called time-division transmission and reception. For example, an NMR measurement probe having only one port (transmission / reception channel) is used to detect a FID signal from 1H while performing decoupling irradiation for 1H (irradiation that eliminates a specific interaction between 1H and 1H). Time division measurement is used when doing so. Even when an NMR measurement probe having a plurality of ports is used, time division measurement is used as necessary.

In the time-division measurement, the received signal cannot be obtained in each transmission period, and the received signal is generated intermittently on the time axis. Usually, in each transmission period, the sampling operation of the received signal is stopped, or the acquisition of the sampled received data is stopped. As a result, the effective sampling rate is lowered in the data processing circuit provided after the sampling circuit. Along with this, unnecessary signals such as turnaround noise, which is a problem in spectrum observation, increase.

An object of the present invention is to prevent an increase in unnecessary signals or reduce unnecessary signals when the NMR measuring device intermittently receives signals. Alternatively, an object of the present invention is to properly operate a data processing circuit provided after the sampling circuit when the NMR measuring device intermittently receives data.

The NMR measuring apparatus according to the embodiment includes a sampling circuit that converts a plurality of divided reception signals intermittently obtained by executing a pulse sequence that transmits and receives in a time division into a plurality of divided reception data, and the plurality of divisions. It includes a compensation circuit that constitutes the supplemented reception data by supplementing the received data with a plurality of dummy data, and a processing circuit that processes the supplemented reception data.

According to the above configuration, by adding a plurality of dummy data to a plurality of divided reception data obtained by performing transmission and reception in a time division manner, that is, a dummy is provided in a plurality of blank periods corresponding to a plurality of transmission periods. By inserting the data, the supplemented received data is constructed. The supplemented received data is processed by the processing circuit. Since the supplemented received data has the same configuration as or close to the received data obtained when continuous reception is performed, it is possible to avoid or mitigate a decrease in the effective sampling rate. It becomes. In other words, it is possible to optimize the operation of the processing circuit that processes the supplemented received data. It is desirable that the dummy data is filled without gaps over the entire blank period, but a modified example in which the dummy data is filled for a part of each blank period is also conceivable. In the specification of the present application, the individual analog reception signals generated intermittently are referred to as divided reception signals, and the digital data generated by sampling the divided reception signals is referred to as divided reception data.

In the embodiment, the individual elements constituting each of the dummy data are the data corresponding to the zero level in each of the divided reception signals. With such data, it is possible to prevent secondary problems from occurring due to compensation. Moreover, the compensation circuit can be easily configured. However, data other than the above can be used as dummy data as long as it does not affect the final signal observation. In the embodiment, the processing circuit includes a digital filter, and the dummy data is data having a period corresponding to the operating frequency of the digital filter.

In the embodiment, a complex conversion circuit for converting the plurality of division reception data into a plurality of complex format division reception data is provided between the sampling circuit and the compensation circuit, and the plurality of divisions processed by the compensation circuit are provided. The received data is the plurality of complex format divided reception data. Alternatively, in the embodiment, a complex conversion circuit for converting the supplemented received data into the complex-format supplemented received data is provided between the supplemented circuit and the processing circuit, and the supplemented received data input to the processing circuit is provided. The received data is the complex-format supplemented received data.

In the embodiment, the processing circuit is a digital filter circuit having a band limiting function. By supplementing the dummy data, the band limiting function of the digital filter circuit can be maintained. In other words, it is possible to avoid the problem that the band limiting function changes due to intermittent reception and the number of wraps increases. In the embodiment, the dummy data compensation period is changed according to the change of the divided transmission period in the pulse sequence.

According to the present invention, when the NMR measuring device intermittently receives signals, it is possible to prevent an increase in unnecessary signals or reduce unnecessary signals. Alternatively, according to the present invention, when the NMR measuring device intermittently receives data, it is possible to properly operate the data processing circuit provided after the sampling circuit.

It is a figure which shows the NMR measuring apparatus which concerns on embodiment. It is a figure which shows the 1st configuration example of the receiving part shown in FIG. It is a figure which shows the action of the BPF shown in FIG. It is a figure which shows the structural example of the digital filter shown in FIG. It is a figure which shows the pulse sequence using 2 channels. It is a figure which shows the pulse sequence including the time division transmission and reception. It is a figure which shows the received data which concerns on a comparative example, and the supplemented received data which concerns on embodiment. It is a figure which shows the proper operation state of the digital filter circuit shown in FIG. It is a figure which shows the change of the intake band and the turnaround accompanying it. It is a figure which shows the 2nd configuration example of a receiving part.

Hereinafter, embodiments of the present invention will be described with reference to the drawings.

FIG. 1 shows the overall configuration of the NMR measuring apparatus according to the embodiment as a block diagram. This NMR measuring device is a device used when analyzing a sample or the like.

The arithmetic control unit 10 controls the transmission unit 14 and the reception unit 26 according to a set or selected pulse sequence. The arithmetic control unit 10 has a processor that operates a program, and functions as a transmission sequencer and a reception sequencer in the present embodiment. The pulse sequence is generated by a main control unit (computer) (not shown), or is generated by an arithmetic control unit 10. The arithmetic control unit 10 according to the present embodiment has a function of controlling the transmission unit 14 and the reception unit 26 according to a pulse sequence for time-division transmission / reception. For example, time-division transmission / reception is used when detecting a FID signal from 1H while performing decoupling irradiation for 1H (irradiation that eliminates a specific interaction between 1H-1H). Also, when observing a FID signal from the other of 1H and 19F while performing decoupling irradiation (irradiation that eliminates a specific interaction between 1H and 19F) on one of 19F and 1H, it is time. Divided transmission / reception is used. The pulse sequence will be described later with reference to FIGS. 5 and 6.

The transmission unit 14 is a circuit that generates a transmission pulse train, that is, a transmission signal. In FIG. 1, a power amplifier 16 is provided after the transmission unit 14. Of course, the power amplifier 16 may be provided inside the transmission unit 14. The transmission signal is amplified by the power amplifier 16, and the amplified transmission signal is transmitted to the NMR measurement probe 20 via the transmission / reception changeover switch 18.

The NMR measurement probe 20 is composed of an insertion portion 20A and a base portion 20B. The insertion portion 20A is inserted into the bore 22A of the static magnetic field generator 22. The base 20B is a portion arranged outside the bore 22A. The illustrated NMR measurement probe 20 has one transmit / receive channel (one port) (see reference numeral 30). Of course, an NMR measurement probe having a plurality of ports may be used (see reference numerals 30 and 32). As the transmission unit 14, a transmission unit having a function of generating a plurality of transmission signals in parallel may be used.

In the NMR measurement probe 20, the sample is irradiated with electromagnetic waves. As a result, nuclear magnetic resonance (NMR) occurs in the target nucleus in the sample, and a FID signal reflecting the resonance is detected. The signal is sent to the receiving unit 26 as an RF receiving signal via the transmission / reception changeover switch 18 and the receiving amplifier 24. A preamplifier that amplifies the RF reception signal is provided in the transmission / reception changeover switch 18. The receiving amplifier 24 may be provided in the receiving unit 26.

The receiving unit 26 is an electronic circuit having a sampling function, a filter function, and the like. The receiving unit 26 includes an analog circuit portion and a digital circuit portion. A specific configuration example of the receiving unit 26 will be described later with reference to FIG.

The arithmetic control unit 10 has a frequency analysis function. It is shown as the frequency analysis unit 12 in FIG. The frequency analysis unit 12 generates a spectrum representing the FID signal component by executing frequency analysis (complex FFT calculation) on the received data. After storing the received data output from the receiving unit 26 in the memory, the received data read from the memory may be sent to the frequency analysis unit 12. A plurality of received data may be added and averaged, and then the processed received data may be sent to the frequency analysis unit 12. The frequency analysis unit 12 is realized as a function of software or as a function of hardware.

FIG. 2 shows a first configuration example of the receiving unit 26. The frequency conversion circuit 33 is an analog circuit that converts an RF reception signal into an IF (intermediate frequency) reception signal. The frequency conversion circuit 33 is composed of a mixer 34 as a multiplier and a BPF (bandpass filter) 36. In the mixer 34, the RF received signal is multiplied by the signal 35 having a predetermined frequency. The multiplication yields a signal with a sum frequency and a signal with a difference frequency. Among them, the BPF 36 extracts signals having different frequencies, that is, IF received signals. The BPF 36 acts as an anti-aliasing filter (anti-aliasing filter) as described below and later as shown in FIG.

The ADC 38 is a sampling circuit as a sampling means, and the IF reception signal is sampled in the ADC 38. That is, it is converted into a digital signal. In this embodiment, the undersampling method disclosed in Patent Document 1 and the like is adopted. For example, the IF received signal is a signal that belongs to the third Nyquist zone after sampling. In that case, the BPF 36 exerts an action of suppressing a signal component existing outside the third Nyquist zone. More specifically, it exerts an action of suppressing signal components existing in a band other than a predetermined band in the third Nyquist zone. The bandwidth of the predetermined band is, for example, 5 MHz. The bandwidth and center frequency of a predetermined band can be varied according to various conditions such as the nuclide to be observed. After the complex conversion described later (after conversion to the baseband or audio frequency band), the target signal (baseband signal or audio frequency signal) appearing in the first Nyquist zone is observed. The target signal is an image signal (mirror signal) generated by turning back twice.

The Nyquist zone is a frequency band determined by the sampling theorem, and specifically, is a frequency band corresponding to 1/2 of the sampling frequency. For example, when the intermediate frequency is 125 MHz and the sampling frequency is 100 MHz, the third Nyquist zone has a frequency band of 100-150 MHz, and the first Nyquist zone has a frequency band of 0-50 MHz (see Patent Document 1). When the frequency of the RF reception signal is low, the RF reception signal bypassing the frequency conversion circuit 33 may be sent to the ADC 38 described below.

In the ADC (analog-digital converter) 38, the RF received signal is sampled as described above. Reference numeral 40 indicates a sampling clock, the frequency of which is, for example, 100 MHz. By this sampling, the received signal as an analog signal is converted into the received data as a digital signal. The received data is composed of a sequence of elements arranged on the time axis during normal transmission / reception (during continuous reception), and each element is amplitude data indicating an instantaneous amplitude value.

An orthogonal detector 42 is provided after the ADC 38. The orthogonal detector 42 functions as a complex conversion circuit and a frequency conversion circuit. In the orthogonal detector 42, the received data as non-complex data is converted into the received data as complex data. At that time, frequency conversion is also performed, that is, the intermediate frequency is converted to the baseband frequency (audio frequency). The received data in complex format consists of real part data and imaginary part data.

More specifically, the orthogonal detector 42 has a plurality of mixers 42A, 42B. In the mixer 42A, the reference signal 46A for the real part is multiplied by the real part data. In the mixer 42B, the reference signal 46B for the imaginary part is multiplied by the imaginary part data. The reference signal generation circuit 44 is a circuit that generates a pair of reference signals 46A and 46B that are orthogonal to each other. The frequencies of the reference signals 46A and 46B are, for example, 125 MHz.

A compensation circuit 48 that functions as a compensation means is provided in the subsequent stage of the orthogonal detector 42. The supplementary circuit 48 is an electronic circuit that functions in time-division transmission / reception or intermittent reception. When performing normal transmission / reception, that is, continuous reception, the compensation circuit 48 does not function. More specifically, when the received data is composed of a plurality of divided reception data separated from each other on the time axis, in other words, the received data includes a plurality of blank periods corresponding to the plurality of divided transmission periods. If so, dummy data is inserted into each blank period, which constitutes received data that apparently has no blank period. This will be described in detail later with reference to FIG. The dummy data supplemented during the blank period is, in the embodiment, a zero data string corresponding to the zero level (baseline) in the RF received signal. However, other data can be used as dummy data as long as it does not affect the observation of the target signal.

In the embodiment, two compensators 48A and 48B are provided corresponding to the real part and the imaginary part in the received data. The individual compensators 48A and 48B are circuits that insert a zero data string into the received data (real part data, imaginary part data) in each transmission period (divided transmission period). As a result, as described below, it is possible to provide the digital filter circuit 52 with input data having the same data structure as in the case of performing normal continuous reception.

The digital filter circuit 52 functions as a data processing means, and in the present embodiment, the digital filter circuit 52 is composed of two digital filters 52A and 52B corresponding to a real number part and an imaginary number part. The individual digital filters 52A and 52B have the same configuration as each other, and are each configured by a CIC (Cascaded Integrator Comb) filter. The digital filter circuit 52 has a band limiting function and the like. The specific configuration and operation thereof will be described later with reference to FIG. 4 and the like. The received data output from the digital filter circuit 52 is sent to the frequency analysis unit.

FIG. 3 shows the action of BPF shown in FIG. The horizontal axis represents the frequency f, and the vertical axis represents the signal strength. Here, the IF received signal is shown as spectrum 200. For example, peak 208 is the observation target. In the illustrated example, the observation target belongs to the third Nyquist zone 202. The left side (low frequency side) of the third Nyquist zone 202 is the second Nyquist zone 204, and the right side (high frequency side) of the third Nyquist zone 202 is the fourth Nyquist zone 206. Reference numeral 210 indicates the frequency characteristic of BPF. The frequency characteristic 210 is merely an example. A BPF having a frequency characteristic suitable for the purpose and conditions is used. The BPF has an anti-aliasing action, that is, exerts an action of suppressing signal component noise belonging to other than the third Nyquist zone 202. More specifically, it exerts an action of suppressing signal components existing in a band other than a predetermined band in the third Nyquist zone. The BPF can effectively suppress the aliasing noise entering the third Nyquist zone 202 from the Nyquist zone other than the third Nyquist zone (see reference numerals 212 and 214).

FIG. 4 shows a specific configuration example of the digital filter 52A shown in FIG. The digital filter 52B shown in FIG. 2 has a similar configuration. The digital filter 52A includes an integration section 54, a thinning circuit 56, and a differentiation section 58. The integrator section 54 is composed of a plurality of integrators 60 connected in series. Each integrator 60 has a memory 62 and an adder 64. In the adder 64, the input signal and the output signal from the memory 62 (the previous input signal) are added. The thinning circuit 56 is a circuit that thins out data at a designated thinning rate. The differentiating section 58 is composed of a plurality of directly connected differentiators 66. Each differentiator 66 is composed of a memory 68 and a differentiator 70. In each differencer 70, the output signal (the previous input signal) from the memory 68 is subtracted from the input signal. The digital filter 52A is configured as hardware, which operates at the same frequency as the sampling frequency. By changing the thinning rate in the thinning circuit 56, the capture band and the filter band, which will be described later, are variably set.

In the case of adopting the circuit configuration shown in FIG. 4, if the number of elements constituting the input received data is reduced due to intermittent reception, the operation or frequency characteristics of the digital filter become inappropriate, and specifically, it is appropriate. The capture band is not set. Therefore, in the present embodiment, a supplementary circuit is provided between the ADC and the digital filter circuit to supplement the missing received data element. This will be described in detail below, but prior to that, the pulse sequence will be described.

FIG. 5 shows a non-time division type pulse sequence. For example, when using an NMR measurement probe with two ports for 1H and 19F, this pulse sequence is performed. (A) indicates the first port, that is, the first channel. (B) indicates the second port, that is, the second channel. For example, transmission and reception for 1H are executed using the first channel. Specifically, reference numeral 72 indicates transmission for 1H, and reference numeral 76 indicates reception for 1H. In the reception period 74, transmission 78 for 19F is executed for decoupling irradiation.

FIG. 6 shows a time-division pulse sequence. This pulse sequence is used when using an NMR measurement probe having only one port for 1H and 19. After the transmission 72 for 1H, in the transmission / reception period 79, the transmission (division transmission) 80 for 19F and the reception (division reception) 82 for 1H are alternately performed in a time division manner. In other words, intermittent reception 82 is performed. In the illustrated example, the individual split transmission period is T1 and the individual split reception period is T2. The individual periods T1 and T2 are appropriately determined according to the purpose and situation of the measurement.

In FIG. 7A, received data 88 according to a comparative example is shown. It corresponds to the input data (real part data or imaginary part data) of each digital filter. Reference numeral 84 indicates a divided transmission period, and reference numeral 86 indicates a divided reception period. The received data 88 includes a plurality of divided received data 90A, 90B, 90C. The individual divided reception data 90A, 90B, 90C are composed of a plurality of amplitude data as shown in the figure, or are composed of one amplitude data. On the time axis, a blank period corresponding to the divided transmission period 84 is generated between the adjacent divided reception data 90A, 90B, 90C. The blank period is a sampling stop period or a sampling data acquisition stop period, and the existence of the blank period makes it impossible to obtain the originally required number of data elements in each digital filter. Alternatively, it takes a long period of time including a stop period to obtain the originally required number of data elements, and as a result, the sampling rate is effectively lowered. The individual data elements are amplitude data.

In FIG. 7B, the received data 100 according to the embodiment is shown. The received data 100 is data after compensation by the compensation circuit (compensated reception data), and corresponds to input data (real part data or imaginary part data) of each digital filter. Specifically, dummy data 92A, 92B, 92C are inserted in each divided transmission period, that is, in each blank period. In other words, dummy data 92A, 92B, 92C are inserted between adjacent divided reception data 90A, 90B, 90C on the time axis, and the reception data 100 without missing elements is configured. The individual dummy data 92A, 92B, 92C are composed of a plurality of elements, and each element is zero data in the illustrated example. Zero data is data corresponding to the midpoint or baseline on the ADC input side. However, as dummy data, other data that does not affect the final signal observation or can be finally removed (for example, data having a period matching the operating frequency of the digital filter or DC data) is supplemented. You may do so. In this way, by performing data supplementation in the previous stage of each digital filter, it is possible to prevent a decrease in the effective sampling rate due to intermittent reception, or to send data to each digital filter at a rate suitable for it. It becomes possible. That is, each digital filter can be operated in the same manner as in the case of undivided transmission / reception. It is desirable to insert zero data strings without gaps for each blank period, but consider a modified example of inserting multiple zero data for a part of each blank period (for example, every other blank period). obtain. The effect of dummy data supplementation will be further described below.

FIG. 8 shows the operation of the digital filter circuit (CIC filter). The received data converted to the baseband is shown there as spectrum 101.

The observation band 102 is a frequency range that finally displays the spectrum. Even if aliasing noise occurs outside the observation band 102, it does not matter in practice. The capture band 104 is a frequency range in which signals are captured, and can be said to be a pass band of the digital filter circuit. The signal component in the capture band 104 is the target of frequency analysis. The filter limiting band 106 is a frequency range corresponding to both ends of the filter characteristic 108 exhibited by the digital filter circuit. The signal is suppressed to zero at both ends of the filter characteristic 108.

When the capture band 104 and the filter limiting band 106 are matched, the signal to be observed is excessively suppressed in the vicinity of both ends of the capture band 104. On the other hand, if the filter limiting band 106 is set so as to include the capture band 104 and, for example, have twice the size thereof, a relatively uniform filter action can be generated over the entire capture band 104. Is possible. As shown by reference numeral 110, signal wrapping occurs at the end of the capture band 104 as a boundary, but the filter characteristic 108 considerably suppresses aliasing noise and unnecessary signals entering the observation band 102, which is a problem. It will never be. That is, in a normal operating state, aliasing noise and unnecessary signals can be sufficiently reduced within the observation band 102.

On the other hand, in the case of intermittent reception (time division reception), the effective sampling rate is lowered, so that the capture band is narrowed as shown in FIG. For example, the capture band shown is 104A. In the illustrated example, the capture band 104A coincides with the observation band 102A. However, the relationship between the two can change depending on various conditions.

Here, focusing on the signal 114 which is not so suppressed by the filter characteristic 108A, as shown by reference numeral 110A, the aliasing noise 114A due to the signal 114 is unnecessary in the observation band 102A due to the folding at the end of the capture band 104A. The signal comes in. That is, as the capture band 104A is narrowed, a large number of unnecessary signals are generated in the observation band 102A. Reference numeral 112 indicates a signal to be observed.

On the other hand, in the present embodiment, dummy data that eliminates the blank period can be supplemented to the received data obtained by intermittent reception, so that the narrowing of the capture band can be prevented. That is, even if intermittent reception is performed, it is possible to prevent an increase in unnecessary signals such as aliasing noise within the observation band. In other words, it is possible to properly operate the digital filter circuit as usual even if intermittent reception is performed, and to maintain the capture band and the like (even when intermittent reception is performed, FIG. 8 shows. Band relations can be formed).

In the present embodiment, the operation of the CIC filter has been described in detail, but the problem described above can occur in other digital filter circuits, and also occurs in digital data processing circuits other than the digital filter circuit. What you get.

FIG. 10 shows a second configuration example of the receiving unit. In FIG. 10, the same reference numerals are given to the configurations similar to those shown in FIG. 2, and the description thereof will be omitted. In the receiving unit 26A shown in FIG. 10, a compensator 115 as a compensating circuit is provided immediately after the ADC 38. Reference numeral 116 indicates a control signal (synchronous signal) given to the compensator 115. An orthogonal detector 42 is provided immediately after the compensator 115. There, a plurality of dummy data are inserted into the plurality of divided reception data, thereby forming the supplemented reception data. After that, the compensated received data is converted into the compensated data in the complex format.

Even with such a configuration, as a result, the same effect as that of the first configuration example can be obtained. Also in the second configuration example, when normal continuous reception is performed, the compensator 115 does not function, and the received data passes there as it is. If compensation is performed before complex conversion, the circuit scale can be reduced. In the receiving unit, the digital circuit portion is composed of, for example, an FPGA.

According to the above embodiment, when the NMR measuring device intermittently receives the signal, it is possible to prevent the unnecessary signal from increasing or reduce the unnecessary signal. Alternatively, the data processing circuit provided after the sampling circuit can be properly operated.

10 Computational control unit, 14 Transmitter unit, 18 Transmission / reception selector switch, 20 NMR measurement probe, 22 Static magnetic field generator, 26 Receiver unit, 33 Frequency conversion circuit, 36 BPF, 38 ADC, 42 Orthogonal detector, 48 Compensation circuit, 52 Digital filter circuit.

Claims (7)

A sampling circuit that converts a plurality of divided reception signals intermittently obtained by executing a pulse sequence that transmits and receives in a time division into a plurality of divided reception data.
A compensation circuit that constitutes the supplemented reception data by supplementing a plurality of dummy data to the plurality of divided reception data, and a compensation circuit.
A processing circuit that processes the supplemented received data, and
Only including,
The plurality of divided reception data and the plurality of blank periods corresponding to the plurality of transmission periods are alternately arranged on the time axis, and the plurality of dummy data are supplemented to the plurality of blank periods.
An NMR measuring device characterized by the above. In the apparatus according to claim 1,
The individual elements constituting each of the dummy data are data corresponding to the zero level in each of the divided reception signals.
An NMR measuring device characterized by the above. In the apparatus according to claim 1,
The processing circuit includes a digital filter.
The dummy data is data having a period corresponding to the operating frequency of the digital filter.
An NMR measuring device characterized by the above. In the apparatus according to claim 1,
A complex conversion circuit for converting the plurality of divided reception data into a plurality of complex format divided reception data is provided between the sampling circuit and the supplement circuit.
The plurality of divided reception data processed by the compensation circuit is the plurality of complex format divided reception data.
An NMR measuring device characterized by the above. In the apparatus according to claim 1,
A complex conversion circuit for converting the supplemented received data into a complex-format supplemented received data is provided between the supplemented circuit and the processing circuit.
The supplemented received data input to the processing circuit is the complex-format supplemented received data.
An NMR measuring device characterized by the above. In the apparatus according to claim 1,
The processing circuit is a digital filter circuit having a band limiting function.
An NMR measuring device characterized by the above. A sampling circuit that converts a plurality of divided reception signals intermittently obtained by executing a pulse sequence that transmits and receives in a time division into a plurality of divided reception data.
A compensation circuit that constitutes the supplemented reception data by supplementing a plurality of dummy data to the plurality of divided reception data, and a compensation circuit.
A processing circuit that processes the supplemented received data, and
Including
The dummy data compensation period is changed according to the change of the divided transmission period in the pulse sequence.
An NMR measuring device characterized by the above.

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