JP6483548B2 - Wireless communication system, elevator system using the same, and substation monitoring system - Google Patents

Description

  The present invention relates to a wireless communication system, an elevator system using the same, and a substation monitoring system.

High-efficiency operation of social infrastructure systems that produce and distribute energy, water, gas, oil, etc. is important for the realization of a sustainable society. High-efficiency operation of social infrastructure systems is realized by high-efficiency operation of devices that constitute the social infrastructure system, and a device monitoring and control network that enables this operation is required.
In order to perform highly efficient operation | movement of the said apparatus, the technique which arrange | positions many sensors in the apparatus and presumes and predicts the operating condition of an apparatus from many acquired data is promising. In this way, the network for collecting and analyzing data from many sensors, estimating operating conditions, and transmitting control information to the device has a large number of transmission paths. A network configuration based on technology is desired.
The sensors arranged in the devices constituting the social infrastructure system and the actuators that control the devices are themselves electromagnetic wave scatterers. Therefore, in a wireless network using electromagnetic waves as a communication medium, the wireless devices constituting the network It is not expected to communicate in a state where the aircraft can be seen, and it is operated in a special situation where non-line-of-sight waves using multiple reflected waves reflected by the device are used.
The electromagnetic wave is a vector wave, and the physical state called polarization perpendicular to the traveling direction is inherently changed by reflection. For this reason, radio waves that are polarized waves automatically radiated from a transmitter in multiple directions are reflected by multiple devices, and receive a change in specific polarization through multiple propagation paths. Will come as. Therefore, the receiver can realize a good communication state between transmission and reception by appropriately selecting an unpredictable polarization direction generated by vector combination of the plurality of incoming radio waves.
Changes in multiple propagation paths and inherent polarization due to multiple reflections by equipment formed during transmission and reception are unpredictable. Therefore, a transmitter transmits using a polarization having a plurality of different polarization directions, and a receiver uses a communication system having a plurality of different polarization directions to monitor and control a radio network for equipment constituting a social infrastructure system Suitable for

Moreover, there exists patent document 1 as background art of this technical field.
Patent Document 1 states that “a radio transmitter (10) modulates an information signal having a frequency f1 with a carrier wave having a frequency f2 and outputs a first modulated signal, and the first modulated signal. Is transmitted by the linearly polarized transmission antenna (20), and the angle of the linearly polarized wave to be transmitted is rotated at the frequency f3 by the motor (14) that rotates the transmission antenna (20) at the frequency f3. A radio receiver (30) superimposes a first modulated signal on two vertically polarized wave components and a horizontally polarized wave component, and a diversity receiving antenna (31) that receives a plurality of input signals and receives a plurality of input signals respectively. The path difference phase shifter (32) for correcting the phase due to the path difference of each input signal and the synthesizer (33) for synthesizing the corrected received signal are provided (see [Summary] [Solution means]). And polarized Techniques degrees divided diversity radio transmitter is disclosed.

JP2015-039218A

However, the patent document 1 has the following problems.
In the technique disclosed in Patent Document 1, the transmitter mechanically rotates the antenna, and the receiver uses a plurality of antennas arranged in spatially different directions to achieve good communication between transmission and reception. Although the transmission polarization and the reception polarization are obtained, since the mechanical rotation is involved, there is a problem in the reliability of the operating part of the antenna system with respect to the transmitter and the increase in the size of the antenna system device with respect to the receiver. is there.

  The present invention was devised in view of the above-described problems, and is a highly reliable and wireless communication system including a small-sized wireless device that does not interfere with the original operation of a social infrastructure system, and an elevator system using the wireless communication system, An object is to provide a substation monitoring system.

In order to solve the above-described problems and achieve the object of the present invention, the present invention is configured as follows.
That is, the wireless communication system of the present invention is a wireless communication system that includes a transmitter and a receiver having a plurality of spatially orthogonal antennas, and performs wireless communication by rotating the polarization of a carrier wave that carries an information signal. The transmitter rotates the polarization of the carrier wave at a plurality of rotation frequencies that are integer multiples of any one of the frequencies, and transmits the plurality of carriers having the plurality of rotation frequency polarizations together. An information signal detecting means for removing the carrier wave from the received signal including the information signal, and selecting and combining each signal obtained from the plurality of rotation frequencies in a predetermined combination. It is characterized by providing.
Other means will be described in the embodiment for carrying out the invention.

  ADVANTAGE OF THE INVENTION According to this invention, a wireless communication system provided with the small-sized radio | wireless machine which is reliable and does not prevent original operation | movement of a social infrastructure system, an elevator system using the same, and a substation monitoring system can be provided.

It is a figure which shows the structural example of the radio | wireless communications system which concerns on 1st Embodiment of this invention. It is a figure which shows the structural example of the radio | wireless communications system which concerns on 2nd Embodiment of this invention. It is a figure which shows the structural example of the radio | wireless communications system which concerns on 3rd Embodiment of this invention. It is a figure which shows the structural example of the receiver of the radio | wireless communications system which concerns on 4th Embodiment of this invention. It is a figure which shows the structural example of the transmitter of the radio | wireless communications system which concerns on 5th Embodiment of this invention. It is a figure which shows the structural example of the receiver of the radio | wireless communications system which concerns on 6th Embodiment of this invention. It is a figure which shows the structural example of the transmitter of the radio | wireless communications system which concerns on 7th Embodiment of this invention. It is a figure which shows the structural example of the radio | wireless communications system which concerns on 8th Embodiment of this invention. It is a figure which shows the structural example of the transmitter of the radio | wireless communications system which concerns on 9th Embodiment of this invention. It is a figure which shows the structural example of the transmitter of the radio | wireless communications system which concerns on 10th Embodiment of this invention. It is a figure which shows the structural example of the elevator system which concerns on 11th Embodiment of this invention. It is a figure which shows the structural example of the substation equipment monitoring system which concerns on 12th Embodiment of this invention.

  Hereinafter, modes for carrying out the present invention (hereinafter referred to as “embodiments”) will be described with reference to the drawings. Note that components having the same function are denoted by the same reference symbols throughout the drawings for describing the embodiment, and the repetitive description will be omitted as appropriate.

<< First Embodiment >>
As a first embodiment of the present invention, a configuration example of a wireless communication system in which a transmitter performs transmission with polarized waves with different angles in time series and a receiver performs reception with polarized waves with different angles will be described.
FIG. 1 is a diagram illustrating a configuration example of a wireless communication system according to the first embodiment of the present invention.
In FIG. 1, a transmitter 10 and a receiver 20 constitute a wireless communication system.

<Configuration of transmitter>
The transmitter 10 includes a digital transmission module 101, a carrier frequency generation circuit 71, transmission multipliers 17 and 27 (third and sixth transmission multipliers), power amplifiers 18 and 28 (first and second power amplifiers). ) And transmission antennas 19 and 29 (first and second transmission antennas).
Note that a configuration in which the digital transmission module 101, the carrier frequency generation circuit 71, and the transmission multipliers 17 and 27 are combined is appropriately referred to as transmission wave generation means.

The digital transmission module 101 includes an information signal generator 100, a fundamental cosine wave generation circuit 11 having a fundamental rotational polarization frequency, and a plurality of cosine harmonic generation circuits 122 to 12N (N is a fundamental frequency of different fundamental rotational polarization frequencies). A sine fundamental wave generating circuit 21 having a fundamental rotational polarization frequency, a sine fundamental wave generating circuit 21 having a fundamental rotational polarization frequency, and generating a plurality of sine harmonics having different integer multiples of the fundamental rotational polarization frequency. Circuits 222 to 22N are provided.
The cosine fundamental wave generation circuit 11 of the fundamental rotational polarization frequency generates cos ωt.
A plurality of cosine harmonic generation circuits 122 to 12N having different integer multiples of the fundamental rotational polarization frequency generate cos2ωt,..., CosNωt, respectively.
The sine fundamental wave generation circuit 21 having the fundamental rotational polarization frequency generates sin ωt.
A plurality of sinusoidal harmonic generation circuits 222 to 22N having an integral multiple of different fundamental rotational polarization frequencies generate sin2ωt,..., SinNωt, respectively.
As described above, N is an integer of 3 or more.
Further, the fundamental rotational polarization frequency ω and the integer multiples 2ω,..., Nω are frequencies different from the carrier frequency ω _c generated by the carrier frequency generation circuit 71.

  The digital transmission module 101 includes transmission multipliers 14, 15, 24, and 25 (first, second, fourth, and fifth transmission multipliers) and switching units 13 and 23 (first and second switching). And adder circuits 16 and 26 (first and second adder circuits).

The output (ω _i (t)) of the information signal generator 100 that generates information to be transmitted is sent to the transmission multipliers 14, 15, 24, and 25.
In the transmission multiplier (first transmission multiplier) 14, the output (ω _i (t)) of the information signal generator 100 is multiplied by the modulation wave cos ωt of the cosine fundamental wave generation circuit 11 having the fundamental rotational polarization frequency ω ( The information signal ω _i (t) is modulated by the modulated wave cos ωt.
In the transmission multiplier (second transmission multiplier) 15, the output (ω _i (t)) of the information signal generator 100 and cos 2ωt,..., CosNωt via the switch 13 (first switch). One of the signals is multiplied (multiplied), and the information signal ω _i (t) is modulated by one of the modulated waves cos2ωt,..., CosNωt.
Both the output of the transmission multiplier 14 and the output of the transmission multiplier 15 are input to the adder circuit 16 (first adder circuit).
The output signal of the adder circuit 16 is sent to the transmission multiplier (third transmission multiplier) 17.

In the transmission multiplier (fourth transmission multiplier) 24, the output (ω _i (t)) of the information signal generator 100 and the modulated wave sin ωt of the sine fundamental wave generation circuit 21 having the fundamental rotational polarization frequency ω are generated. Multiplication (multiplication) is performed, and the information signal ω _i (t) is modulated by the modulated wave sin ωt.
In the transmission multiplier (fifth transmission multiplier) 25, the outputs of the information signal generator 100 (ω _i (t)) and sin2ωt,..., SinNωt via the switch 23 (second switch). One of the signals is multiplied (multiplied), and the information signal ω _i (t) is modulated by one of the modulated waves sin2ωt,..., SinNωt.
Both the output of the transmission multiplier 24 and the output of the transmission multiplier 25 are input to the adder circuit 26 (second adder circuit).
The output signal of the adder circuit 26 is sent to the transmission multiplier (sixth transmission multiplier) 27.

The output signal of the adder circuit 16 and the carrier wave ω _c of the carrier frequency generation circuit 71 are input to the transmission multiplier 17 and multiplied (multiplied), whereby the carrier wave modulated by the information signal ω _i (t). The first transmission signal is obtained.
The first transmission signal is amplified by the power amplifier 18 (first power amplifier), and is radiated as electromagnetic waves from the transmission antenna 19 (first transmission antenna).

The output signal of the adder circuit 26 and the carrier wave ω _c of the carrier frequency generating circuit 71 are input to the transmission multiplier 27 and multiplied (multiplied), whereby the carrier wave modulated by the information signal ω _i (t). The second transmission signal is obtained.
The second transmission signal is amplified by the power amplifier 28 (second power amplifier), and is radiated into the space as an electromagnetic wave from the transmission antenna 29 (second transmission antenna).
The transmission antenna 19 and the transmission antenna 29 are installed in directions that are spatially orthogonal to each other.

<Transmitter operation / function>
The operation and function of the transmitter described above will be described.

<< Modulation by cosωt and sinωt >>
The information signal ω _i (t) of the information signal generator 100 is modulated at the transmission multiplier 14 by cos ωt, which is the fundamental rotational polarization frequency, and is radiated from the transmission antenna 19 to the space as an electromagnetic wave.
The information signal ω _i (t) of the information signal generator 100 is modulated by the transmission multiplier 24 with sin ωt, which is the fundamental rotational polarization frequency, and is radiated from the transmission antenna 29 to the space as an electromagnetic wave.
As described above, the transmission antenna 19 and the transmission antenna 29 are installed in directions that are spatially orthogonal to each other.
With these configurations, the polarization of cos ωt radiated as an electromagnetic wave from the transmission antenna 19 and the polarization of sin ωt radiated as an electromagnetic wave from the transmission antenna 29 installed in a spatially orthogonal direction are combined in a vector manner. , A rotationally polarized wave rotating in a circular shape in the space is formed.

This principle will be briefly described.
For example, the following equation is well known as Euler's formula in the complex plane.
exp (iθ) = cos θ + i · sin θ (1)
Here, i is an imaginary unit, and θ is a rotation angle.
In Equation 1, when θ takes each value, Equation 1 draws a circle and moves (rotates) around the circumference. Further, cos θ is a real number, and i · sin θ is an imaginary number. That is, in the complex plane of the real number axis and the imaginary number (i) axis, cos θ and i · sin θ move and rotate around the circumference as vectors.
The fact that the real number axis and the imaginary number (i) axis are orthogonal corresponds to the fact that the transmitting antenna 19 and the transmitting antenna 29 according to the first embodiment of the present invention are installed in a spatially orthogonal direction. To do.
Further, this corresponds to the fact that the transmission antenna 19 emits the cosωt polarization as an electromagnetic wave, and the transmission antenna 29 emits the sinωt polarization as an electromagnetic wave.

<< Modulation of cos2ωt to cosNωt, sin2ωt to sinNωt >>
In FIG. 1, the information signal ω _i (t) of the information signal generator 100 is modulated by any one of cos 2ωt to cosNωt via the switch 13 (first switch) and the transmission multiplier 15. It is radiated into the space as electromagnetic waves from the transmitting antenna 19.
Further, the information signal ω _i (t) of the information signal generator 100 is modulated by any one of sin 2ωt to sinNωt via the switch 23 (second switch) and the transmission multiplier 25, and is transmitted to the transmission antenna. 29 is radiated to space as electromagnetic waves.

As described above, cos ωt and sin ωt form a rotationally polarized wave that rotates in a circular shape in the space. As will be described later, the electromagnetic wave is reflected and scattered by an obstacle while propagating, and the direction of the rotationally polarized wave is also changed. Since it changes, it is impossible to determine which of the rotational polarizations including the basic rotational polarization frequency ω is optimal from the viewpoint of the receiver 20.
Therefore, it is possible to use a rotationally polarized wave that is more suitable for the angle of the transmission antenna 29 on the reception side by using a modulated wave of higher harmonics of cos2ωt to cosNωt and sin2ωt to sinNωt.
How to specifically determine will be described in detail in the section of the receiver.

<Propagation of space>
With the configuration of the transmitter 10 described above, the same signal (ω _i (t)) from the two spatially orthogonal transmitting antennas (19, 29) has the same propagation frequency (ω _c ) and the first rotational polarization. A radio wave whose polarization is rotated at a frequency (ω) and a radio wave (frequency 2ω to Nω) obtained by multiplying only the rotation polarization frequency by an integer (2 to N) are simultaneously transmitted to the space.

In addition, the radio wave transmitted from the transmitter 10 travels through the space and is reflected a plurality of times by an electromagnetic wave scatterer such as a device existing between the transmitter 10 and the receiver 20. To reach.
In addition, it is rare in the field that the transmitter 10 and the receiver 20 are in a line-of-sight arrangement. In fact, as described above, there are many electromagnetic scatterers such as devices. Therefore, the reflected wave by the electromagnetic wave scatterer mainly contributes to transmission.
When the rotational polarization transmitted from the transmitter 10 hits an electromagnetic wave scatterer, the rotation direction of the polarization changes. Therefore, the direction of the rotational polarization of the radio wave when it reaches the receiver 20 cannot be generally grasped. Under such circumstances, the receiver 20 needs to efficiently receive radio waves.

<Receiver configuration>
Next, the receiver will be described.
The receiver 20 includes receiving antennas 39 and 49 (first and second receiving antennas), low noise amplifiers 31 and 41 (first and second low noise amplifiers), and the same frequency (ω _c ) as the carrier wave. Local oscillation circuit 38, reception multipliers 32 and 42 (first and second reception multipliers), low-pass filters 33 and 43 (first and second low-pass filters), and buffers Amplifiers 34 and 44 (first and second buffer amplifiers) and a digital reception module 201 are provided.

The receiving antenna 39 (first receiving antenna) and the receiving antenna 49 (second receiving antenna) are spatially orthogonal to each other.
The receiver 20 amplifies the reception power obtained from the reception antenna 39 by the low noise amplifier 31 (first low noise amplifier). Also, the received power obtained from the receiving antenna 49 is amplified by the low noise amplifier 41 (second low noise amplifier).
The output of the low noise amplifier 31 and the output of the local oscillation circuit 38 having the same frequency (ω _c ) as that of the carrier wave are multiplied (multiplied) by the reception multiplier 32 (first reception multiplier) to downconvert. (Frequency conversion to a lower frequency).
Further, the output of the low-noise amplifier 41 and the output of the local oscillation circuit 38 are multiplied (multiplied) by the reception multiplier 42 (second reception multiplier), and down-converted.

The carrier frequency component (ω _c ) of the received power is removed from the signal down-converted by the reception multiplier 32 by the low-pass filter 33 (first low-pass filter), and the buffer amplifier 34 (first Is amplified by a buffer amplifier) and input to the first input terminal of the digital reception module 201.
Also, the carrier frequency component (ω _c ) of the received power is removed from the signal down-converted by the reception multiplier 42 by the low-pass filter 43 (second low-pass filter), and the buffer amplifier 44 (the first amplifier) Are amplified by the second buffer amplifier) and input to the second input terminal of the digital reception module 201.
The configuration including the local oscillation circuit 38, the reception multipliers 32 and 42, and the low-pass filters 33 and 43 is appropriately referred to as carrier wave removal means.
Further, a configuration in which the local oscillation circuit 38, the reception multipliers 32 and 42, the low-pass filters 33 and 43, and the digital reception module 201 described below are combined is appropriately referred to as information signal detection means. .

The digital reception module 201 includes a first series of delay units (351, 352,..., 35N) having a delay amount of a predetermined time interval (details will be described later), and a first delay unit having a delay amount of a predetermined time interval. Two series of delay units (451, 452,... 45N) and a plurality of first series decimators (361, 362,..., 36N) respectively connected to outputs of the plurality of first series delay units. And a plurality of second series decimators (461, 462,..., 46N) respectively connected to outputs of the second series of delay devices, and a baseband processing circuit (BB) 48. Configured.
It should be noted that the delay amount of the first series of delay units at a predetermined time interval is the maximum of the cosine harmonic generation circuit (122 to 12N) and the sine harmonic generation circuit (222 to 22N) included in the transmitter 10. This is a delay amount of a time interval obtained by dividing the period of the fundamental rotational polarization generated by the cosine fundamental wave generation circuit 11 and the sine fundamental wave generation circuit 21 by the harmonic number (N).
In addition, the functions of the decimators of the plurality of first series decimators (361, 362,..., 36N) and the plurality of second series decimators (461, 462,..., 46N) The signals detected by the delay units (351, 352,..., 35N) and the second series of delay units (451, 452,... 45N) are down-converted by the maximum harmonic number N.

The first input signal of the digital reception module 201 is the same number as the maximum harmonic number N of the first series of delay units (351, 352,..., 35N) having the delay amount of the time interval described above. Due to the cascade connection, a delay is caused in sequence. The first series of delay devices (351, 352,..., 35N) having this delay amount sequentially detect the signals while delaying the signals.
Then, each output of the plurality of delay devices (351, 352,..., 35N) of the first series is output by a plurality of decimators (361, 362,..., 36N) of the first series. , Down-converted by the harmonic number N to obtain a plurality of positive phase signal inputs (i1, i2,..., IN) of the baseband processing circuit (BB) 48.

Further, the second input signal of the digital reception module 201 is the maximum harmonic number N of the second series of delay devices (451, 452,..., 45N) having the delay amount of the time interval described above. Sequential delays are caused by the same number of cascade connections. The second series of delay devices (451, 452,... 45N) having this delay amount sequentially detect the signals while delaying the signals.
Then, each output of the plurality of delay devices (451, 452,..., 45N) of the second sequence is output by a plurality of decimators (461, 462,..., 46N) of the second sequence. , Down-converted by the harmonic number N to obtain a plurality of orthogonal signal inputs (q1, q2,..., QN) of the baseband processing circuit (BB) 48.

Note that the first series of delay units (351, 352,..., 35N), the second series of delay units (451, 452,..., 45N), the first series of decimators (361, 362,... ., 36N), and the second series of decimators (461, 462,..., 46N) are configured by, for example, a DSP (Digital Signal Processor).
Further, the first series of delay units (351, 352,..., 35N), the second series of delay units (451, 452,..., 45N), the first series of decimators (361, 362,... .., 36N), and the configuration including the second series of decimators (461, 462,..., 46N) is appropriately referred to as data acquisition means.

The baseband processing circuit (BB) 48 is constituted by, for example, a CPU (Central Processing Unit), and the plurality of normal phase signal inputs (i1, i2,..., IN) and the plurality of quadrature signal inputs (q1, q2). ,..., QN) to perform arithmetic processing based on the accumulated data.
The contents to be executed in this arithmetic processing are equivalent to the cosine harmonic generation circuit (122 to 12N) and the sine harmonic generation circuit (222 to 22N) using the plurality of positive phase signals and quadrature signals. Corresponding to receiving the received electromagnetic wave by distinguishing it for each polarization angle with the maximum number of divisions of harmonics (for example, N).
In addition, each signal obtained from these processes is combined with selection and combination with the best reception sensitivity from the viewpoint of reconstructing the information signal ω _i (t) transmitted by the transmitter 10.
In addition, the baseband processing circuit (BB) 48 is appropriately referred to as information signal synthesis means.
The principle of receiving the received electromagnetic wave separately for each polarization angle will now be described in detail.

<Principle of receiving electromagnetic waves separately for each polarization angle>
As described above, the same signal (ω _i (t)) is transmitted from the two transmitting antennas (19, 29) that are spatially orthogonal to each other at the first propagation polarization frequency (ω _c ). A radio wave whose polarization of ω) rotates and a radio wave obtained by multiplying only the rotation polarization frequency (ω) by an integer are simultaneously transmitted.
The radio wave (electromagnetic wave) output from the transmitter 10 travels through space, and is reflected a plurality of times by an electromagnetic wave scatterer such as a device existing between transmission and reception, and then reaches the receiver 20.
In the receiver 20, radio waves received by two spatially orthogonal receiving antennas (39, 49) are multiplied by a signal source having the same frequency (ω _c ) as that of the carrier wave, down-converted, and further low-pass The carrier wave component (ω _c ) is removed by the filters (33, 43), and the amplitude changes sinusoidally at the polarization rotation frequency (ω), and the integer (2,. ..., N) A signal in which information whose amplitude changes sinusoidally at a frequency is synthesized is obtained.

The obtained signal has a timing at which two integer rotation waves having different rotational polarization frequencies are in reverse phase in one cycle of polarization rotation.
This timing is the same as the timing in the specific polarization direction of the radio wave whose polarization rotates at the polarization rotation frequency. The fact that the two radio waves cancel each other at that timing corresponds to the direction of the antenna being coincident with a direction that is spatially orthogonal to a specific polarization direction.
Since the receiver 20 has two receiving antennas (39, 49) that are spatially orthogonal to each other, information obtained by changing the amplitude in a sinusoidal manner at the polarization rotation frequency obtained from them and an integral multiple of the polarization rotation frequency. Information whose amplitude changes sinusoidally with frequency is also orthogonal.
Therefore, digital signal processing (base) is performed using information in which the amplitude changes sinusoidally at the polarization rotation frequencies orthogonal to each other and information in which the amplitude changes sinusoidally at a frequency that is an integral multiple of the polarization rotation frequency. By applying the band processing circuit 48), it is possible to virtually form a receiving antenna directed in an arbitrary single direction with respect to the received radio wave.

The number of divisions in the imaginary direction is determined by how many times an integer multiple of the fundamental polarization rotation frequency is taken. As the number of divisions in the virtual direction increases, the possibility that the polarization direction of the radio wave can be more accurately aligned with the direction of the reception antenna that is virtually realized increases.
Increasing the integer multiple increases the number of divisions, but the maximum polarization rotation frequency increases and the frequency spectrum occupied by the radio waves expands, which is not preferable from the viewpoint of effective use of frequency.
In addition, if multiple integers are relatively prime, the difference is that the two polarization rotation frequency waves are in opposite phase within one period of the rotation polarization. By changing the integer value, it is possible to increase the number of receiving antenna directions that are virtually but not simultaneously realized.

Also, which of the circularly polarized waves (rotational polarized waves) of the frequencies ω, 2ω,..., Nω is most suitable for transmission / reception depends on the environment in which an electromagnetic wave scatterer such as a device exists. The polarization rotation frequencies (ω, 2ω,..., Nω) of the transmitter 10 shown in FIG. 1 are sequentially switched and used by the switches 13 and 23 at the beginning of transmission / reception. However, in the above environment, when there is a polarization rotation frequency having the highest transmission / reception sensitivity among these polarization rotation frequencies (ω, 2ω,..., Nω), the highest transmission / reception sensitivity is present. The polarization rotation frequency by the switches 13 and 23 may be fixed and used so that the polarization rotation frequency is used.
In addition, after the polarization rotation frequency is fixed, when the sensitivity of transmission / reception is lowered (changed) or may be lowered due to a change in the environment, switching of the polarization rotation frequency by the switches 13 and 23 is performed. There is also a way to resume.

As described above, it is possible to realize wireless data transmission with higher quality by using the optimum polarization in transmission / reception of the wireless device.
In other words, according to the present (first) embodiment, the transmitter 10 has a basic rotational polarization frequency (first rotational polarization frequency ω) of 90 degrees from two spatially orthogonal antennas (19, 29). Each electromagnetic wave having a phase difference of Therefore, since the emitted electromagnetic wave rotates at the basic rotational polarization frequency, information can be wirelessly transmitted using all the different polarized waves (an integer multiple of the rotational polarization frequency) at different times.
Thereby, the receiver 20 virtually divides the cosine harmonic generation circuit (122 to 12N) used by the transmitter 10 at the same time and the maximum harmonic (N) of the sine harmonic generation circuit (222 to 22N). Incoming waves can be received separately for each polarization angle.
Therefore, it is possible to realize wireless data transmission with higher quality using optimum polarization in transmission and reception.

<< Second Embodiment >>
As a second embodiment of the present invention, another configuration example of a wireless communication system in which a transmitter performs transmission with polarized waves with different angles in time series and a receiver performs reception with polarized waves with different angles will be described.
FIG. 2 is a diagram illustrating a configuration example of a radio communication system according to the second embodiment of the present invention.
In FIG. 2, a transmitter 10B and a receiver 20 constitute a wireless communication system.
The second embodiment shown in FIG. 2 differs from the first embodiment shown in FIG. 1 in the configuration of the digital transmission module 102. The configuration of the transmitter 10B excluding the digital transmission module 102 and the configuration of the receiver 20 are the same as those of the first embodiment shown in FIG.

<Configuration of Digital Transmission Module 102>
The difference between the digital transmission module 102 shown in FIG. 2 and the digital transmission module 101 shown in FIG. 1 is the number and connection method of transmission multipliers (152 to 15N) and transmission multipliers (252 to 25N). This is the number of signal lines input from the transmission multiplier (152 to 15N) and the transmission multiplier (252 to 25N) respectively input to the circuits 16B and 26B. Further, FIG. 2 is also different in that the switches 13 and 23 in FIG. 1 are not provided.
That is, in FIG. 1, the signals of the plurality of cosine harmonic generation circuits (122 to 12N) are switched by the switch 13 and the plurality of sine harmonic generation circuits (222 to 22N) are switched by the switch 23.

On the other hand, in FIG. 2, the signals of the plurality of cosine harmonic generation circuits (122 to 12N) are directly input to the transmission multipliers (152 to 15N), respectively, and the respective outputs of the transmission multipliers (152 to 15N). Are all input to the adder circuit 16B.
Further, the signals of the plurality of sine harmonic generation circuits (222 to 22N) are directly input to the transmission multipliers (225 to 225N), respectively, and all the outputs of the transmission multipliers (252 to 25N) are input to the addition circuit 26B. You are typing.
For this reason, the output of the adder circuit 16B includes all the signals of the plurality of cosine harmonic generation circuits (122 to 12N), and the transmission antenna 19 includes a plurality of cosines having different integer multiples of the fundamental rotational polarization frequency. Harmonics cos2ωt, ..., cosNωt are included.
Further, the output of the adder circuit 26B includes all the signals of the plurality of sine harmonic generation circuits (222 to 22N), and the transmitting antenna 29 has a plurality of sine frequencies having different integral multiples of the fundamental rotational polarization frequency. Harmonics sin2ωt,..., SinNωt are included.

According to this (second) embodiment, information whose amplitude changes sinusoidally at the polarization rotation frequency of the fundamental rotation polarization frequency (ω) and sinusoidal at a plurality of integer multiples of the same polarization rotation frequency. A signal in which information whose amplitude changes is synthesized is obtained.
Then, the timing at which the obtained signal is in the opposite phase of two different rotational polarization frequency waves in one cycle of the polarization rotation is compared to the first embodiment shown in FIG. Therefore, the types of polarization at the receiving antennas (39, 49) that receive incoming waves that can be selected by the receiver for good wireless data transmission are increased, which is effective in improving the quality of wireless data transmission between transmission and reception. There is.

«Third embodiment»
As a third embodiment of the present invention, another configuration example of a wireless communication system in which a transmitter performs transmission with polarized waves with different angles in time series and a receiver performs reception with polarized waves with different angles will be described.
FIG. 3 is a diagram illustrating a configuration example of a wireless communication system according to the third embodiment of the present invention.
In FIG. 3, a transmitter 10C and a receiver 20C constitute a wireless communication system.
The third embodiment shown in FIG. 3 differs from the first embodiment shown in FIG. 1 in the configuration of the digital transmission module 103 and the configuration of the digital reception module 202. The configuration of the transmitter 10C excluding the digital transmission module 103 and the digital reception module 202 and the configuration of the receiver 20C are the same as those of the first embodiment shown in FIG.

<Configuration of Digital Transmission Module 103>
The third embodiment of the present invention shown in FIG. 3 is different from the first embodiment shown in FIG. 1 in that the cosine harmonic generation circuits 12M and 12N included in the transmitter, the sine harmonic generation circuit 22M, There are two types, 22N having two harmonics (M, N) of relatively prime integers.
That is, in the first embodiment shown in FIG. 1, the cosine harmonic generation circuit (122 to 12N) generates cos2ωt,..., CosNωt, and the sine harmonic generation circuit (222 to 22N) is sin2ωt. , ..., sinNωt was generated.
On the other hand, in the third embodiment shown in FIG. 3, the cosine harmonic generation circuits 12M and 12N generate cosMωt and cosNωt, respectively, and the sine harmonic generation circuits 22M and 22N generate sinMωt and sinNωt.
Then, cosine harmonic generation circuits 12M and 12N and sine harmonic generation circuits 22M and 22N having different harmonics are used while being switched in terms of time.
The effect of this configuration will be described later together with the description of the digital reception module 202 of the next receiver 20C.

<Configuration of Digital Reception Module 202>
In FIG. 3, the digital reception module 202 includes a first series of delay devices (351, 352,..., 35N) having a delay amount (N) of a predetermined time interval, and a delay amount (N of a predetermined time interval). ), And a plurality of first series decimators (361, 362) connected to outputs of the plurality of first series delay elements, respectively. , 36N) and a plurality of second series decimators (461, 462, ..., 46N) respectively connected to the outputs of the plurality of delay devices of the second series.
Further, the digital reception module 202 includes a third-series delay device (751, 752,..., 75M) having a delay amount (M) of a predetermined time interval and a delay amount (M) of the predetermined time interval. A fourth series of delay units (851, 852... 85M) and a plurality of third series decimators (761, 762,..., Respectively connected to outputs of the plurality of third series delay units. 76M) and a plurality of fourth series decimators (861, 862,..., 86M) respectively connected to the outputs of the plurality of fourth series delay devices.

  Further, the digital reception module 202 includes outputs (ia1, ia2,..., IAN) of a plurality of first series decimators (361, 362,..., 36N) and a plurality of second series decimators (461, 461). , 46N) outputs (qb1, qb2,..., QbN), outputs of a plurality of third series decimators (761, 762,..., 76M) (ib1, ib2,. , IbM) and a baseband processing circuit 88 for inputting outputs (qa1, qa2,..., QaM) of a plurality of fourth series decimators (861, 862,..., 86M).

Note that the delay amount at a predetermined time interval of the first-series and second-series delay units is the maximum of the cosine harmonic generation circuit (12N) and sine harmonic generation circuit (22N) included in the transmitter 10C. This is the delay amount of the time interval obtained by dividing the period of the cosine fundamental wave generation circuit 11 and the sine fundamental wave generation circuit 21 by the harmonic number (N).
The delay amount of the third series and the fourth series of delay units at a predetermined time interval is the maximum of the cosine harmonic generation circuit (12M) and sine harmonic generation circuit (22M) included in the transmitter 10C. This is the delay amount of the time interval obtained by dividing the period of the cosine fundamental wave generation circuit 11 and the sine fundamental wave generation circuit 21 by the harmonic number (M).
The functions of the decimators of the plurality of first series, the plurality of second series, the plurality of third series, and the plurality of fourth series are to remove the fundamental rotational polarization component (frequency ω).

In the digital reception module 202 shown in FIG. 3, the delay amounts of the first series of delay units (351,..., 35N) and the second series of delay units (451,..., 45N) are T / N, and the delay amounts of the third series of delay units (751,..., 75N) and the fourth series of delay units (851,..., 85N) are T / M.
In this way, a series of delay units having different delay amounts (T / N) and (T / M) is divided into the frequency Nω of the cosine (sine) harmonic generation circuit 12N (22N) and the cosine (sine) harmonic generation circuit. They are provided separately according to a frequency Mω of 12M (22M).
This is because it is more preferable from the viewpoint of detection sensitivity that the delay amount of the delay device accurately corresponds to the frequency of the cosine (sine) harmonic generation circuit.
As in the first embodiment shown in FIG. 1, the first series of delays is applied to any frequency (ω, 2ω,..., Nω) of the cosine harmonic generation circuit (122,..., 12N). The signals can be detected even if the delay amounts of the delay units (351,..., 35N) and the second delay units (451,..., 45N) are both T / N. As in the third embodiment, the frequency (Nω, Mω) of the cosine (sine) harmonic generation circuit and the delay amount (T / N, T / M) of the delay device correspond to each other in reception. Desirable from the viewpoint of detection sensitivity.

<Wireless communication system>
In the wireless communication system of the present (third) embodiment, the cosine harmonic generation circuit (12M, 12N) and the sine harmonic generation circuit (22M, 22N) having different harmonics (M, N) are switched over time. Use.
The harmonics (M, N) of the cosine harmonic generation circuit (12M, 12N) and the sine harmonic generation circuit (22M, 22N) of the two types of frequencies (Mω, Nω) included in the transmitter 10C are relatively prime. Therefore, information whose amplitude changes sinusoidally at the polarization rotation frequency (ω) of the basic rotation polarization frequency (ω) obtained by the receiver, and frequencies (Mω) of integer multiples (M, N) different from the polarization rotation frequency , Nω), a signal in which information whose amplitude changes sinusoidally is synthesized is obtained.

Since the obtained signals have different timings at which two different rotational polarization frequency waves are in reverse phase in one cycle of polarization rotation, the transmitter is connected to a cosine harmonic generation circuit (12M, 12N). ), And the sinusoidal harmonic generation circuit (22M, 22N) are temporally switched to increase the type of polarization of the receiving antenna virtually formed by the receiver.
In general, when the harmonics increase, the frequency occupation spectrum of the radio wave radiated from the transmitter spreads, which is a problem in terms of effective use of frequency resources.
According to the present (third) embodiment, it is possible to increase the type of polarization of the receiving antenna although it is not simultaneous with few harmonics, so there is an effect of reducing the frequency resources used by the wireless system of the present invention, As a result, the power consumption of the wireless system of the present invention can be reduced.

<< Fourth Embodiment >>
As a fourth embodiment of the present invention, another configuration example of a receiver of a wireless communication system in which a transmitter transmits with polarized waves with different angles in time series and a receiver receives with polarized waves with different angles. explain.
FIG. 4 is a diagram illustrating a configuration example of the receiver 20D of the wireless communication system according to the fourth embodiment of the present invention.
FIG. 4 shows the configuration of the receiver 20D in the wireless communication system. As the transmitter, for example, the transmitter 10 of FIG. 1 (or the transmitter 10B of FIG. 2) can be used, and illustration and description thereof are omitted.

The receiver 20D shown in FIG. 4 is different from the receiver 20 shown in FIG. Except for the digital reception module 203, the receiver 20 is the same as the receiver 20 shown in FIG.
In FIG. 4, the digital reception module 203 includes a total of mN delay units (<7411 to 741m>,..., 74) having a delay amount (T1 / mN) of a predetermined time interval (details will be described later). , <74N1 to 74Nm>) and a total of mN delay units (<8411 to 841m>,..., <84N1 to 84Nm>) having a delay amount of the predetermined time interval, It has.
The digital reception module 203 includes a total mN decimator (<3611 to 361 m>,..., <36N1 to 36Nm>) and a second series mN decimator (<4611 to 461m>,..., <46N1 to 46Nm>), N reception synthesis circuits (first reception synthesis circuit) 731,..., 73N, and N reception synthesis circuits (second , 83N and a baseband processing circuit 48.

The first series of delay units (<7411 to 741m>,..., <74N1 to 74Nm>) and the second series of delay units (<8411 to 841m>,..., <84N1 to 84Nm>) The delay amount (T1 / mN) of the predetermined time interval is the maximum harmonic number of the cosine harmonic generation circuit (122 to 12N) and the sine harmonic generation circuit (222 to 22N) included in the transmitter 10. N) is an integer (m), that is, mN, which is a delay amount of a time interval obtained by dividing the period of the cosine fundamental wave generation circuit 11 and the sine fundamental wave generation circuit 21.
That is, in the fourth embodiment shown in FIG. 4, the delay amount (T1 / mN) of the time interval is further reduced to 1 / m and the number of delay devices is m as compared with the first embodiment shown in FIG. It has doubled.
Also, a plurality (mN) of first series decimators (<3611-1361m>,..., <36N1 to 36Nm>) and a plurality (mN) of second series decimators (<4611 to 461m>, .., <46N1 to 46Nm>) is to down-convert the maximum harmonic number N.

Next, the digital reception module 203 in FIG. 4 will be described in more detail.
In FIG. 4, the digital reception module 203 adds a first series of delay devices (<7411 to 741 m>,..., <74N1 to 74Nm>) having a delay amount (T1 / mN) at a predetermined time interval. mN pieces are connected in cascade.
That is, the first series of delay units is composed of m delay units (7411 to 741m) as the first group, and the second group of m delay units (7421 to 742m) (FIG. 4). , And the last Nth set consists of m delay units (74N1 to 74Nm).
Then, the signal input from the first input terminal is input to the delay device 7411 and sequentially into the delay devices 7412,..., The delay devices 741m,. Propagating while generating a delay amount (T1 / mN).

Further, the total mN first series decimators are composed of m decimators (3611 to 361 m) as the first set, and m decimators (3621 to 362 m) as the second set (see FIG. 4 and not shown), and the Nth set consists of m decimators (36N1 to 36Nm).
Each signal output from the total mN first-sequence delay units (<7411 to 741m>,..., <74N1 to 74Nm>) is the plurality of (total mN) first sequences. Decimators (<3611-361m>,..., <36N1-36Nm>).

As the first set, the outputs of the decimators (3611 to 361m) are input to the reception synthesis circuit 731. That is, the outputs of the decimators (3611 to 361m) are collected in order along the signal flow.
Further, as the second set, each output of the decimator (3621 to 362m: not shown) is input to the reception synthesis circuit 732 (not shown).
And each output of a decimator (36N1-36Nm) is input into the reception synthetic | combination circuit 73N as a Nth group.
That is, the outputs of the decimators (3611 to 361m),..., Decimators (46N1 to 46Nm) are sequentially collected by the reception synthesis circuits (731 to 73N) along the signal flow.
The outputs of the plurality of reception synthesis circuits (731 to 73N) are input to input terminals (i1 to iN) which are a plurality of positive phase signal inputs of the baseband processing circuit 48, respectively.

The second series of delay units includes m delay units (8411 to 841m) as the first set, and m delay units (8421 to 842m) as the second set (FIG. 4). , And the last Nth set consists of m delay units (84N1 to 84Nm).
Then, the signal input from the second input terminal is input to the delay device 8411 and sequentially to the delay devices 8412,..., The delay devices 841m,. Propagating while generating a delay amount (T1 / mN).

The total mN second-series decimators are composed of m decimators (4611 to 461m) as the first set, and m decimators (4621 to 462m) as the second set (see FIG. 4 is not shown), and the Nth set consists of m decimators (46N1 to 46Nm).
Each of the signals output from the total mN second-sequence delay units (<8411 to 841m>,..., <84N1 to 84Nm>) is the plurality of (total mN) second sequences. Decimators (<4611 to 461m>,..., <46N1 to 46Nm>).

As the first set, the outputs of the decimators (4611 to 461m) are input to the reception synthesis circuit 831. That is, the outputs of the decimators (4611 to 461m) are collected sequentially along the signal flow.
Further, as the second set, each output of the decimator (4621 to 462m: not shown) is input to the reception synthesis circuit 832 (not shown). The outputs of the decimators (46N1 to 46Nm) are input to the reception synthesis circuit 83N as the Nth set.
In other words, the outputs of the decimators (4611 to 461m),..., Decimators (86N1 to 86Nm) are sequentially collected by the reception synthesis circuits (831 to 83N) along the signal flow.
The outputs of the plurality of reception synthesis circuits (831 to 83N) are input to input terminals (q1 to qN), which are a plurality of orthogonal signal inputs, of the baseband processing circuit 48, respectively.

The baseband processing circuit 48 is configured by, for example, a DSP (Digital Signal Processor), and equivalently uses a plurality of positive phase signals and quadrature signals, and a cosine harmonic generation circuit (122 to 12N), and a sine harmonic. The incoming electromagnetic waves are distinguished and received for each polarization angle with a division number (for example, mN) which is m times the maximum harmonic of the wave generation circuit (222 to 22N).
The baseband processing circuit 48 in FIG. 4 has the same operation and function as the baseband processing circuit 48 in FIG.

However, in FIG. 4, a first series of delay devices (<7411 to 741m>,..., <74N1 to 74Nm>) having a delay amount (T1 / mN) of a predetermined time interval, and a second series of delay units. The outputs of the delay devices (<8411 to 841m>,..., <84N1 to 84Nm>) are respectively the plurality of (total mN) first series decimators (<3611 to 361m>,. 36N1 to 36Nm>) and a plurality of (total mN) second series decimators (<4611 to 461m>,..., <46N1 to 46Nm>) and then received the first series. The signals are averaged by the synthesis circuit (731 to 73N) and the second series of reception synthesis circuits (831 to 83N).
Therefore, when the radio wave propagating between the transmitter 10 and the receiver 20D fluctuates over time due to some external factor, the fluctuation is averaged, and reception of a specific polarization virtually formed by the receiver 20D that receives this fluctuation. Absorbs disturbances in determining the polarization angle of the antennas 39 and 49.
Therefore, in the wireless system in which the transmitter 10 of the present (fourth) embodiment transmits with an arbitrary polarization and the receiver 20D receives with an arbitrary polarization, the operation of the receiver 20D becomes more stable. There is.

«Fifth embodiment»
As a fifth embodiment of the present invention, another configuration example of a transmitter of a wireless communication system in which a transmitter performs transmission with polarized waves having different angles in time series and a receiver performs reception with polarized waves having different angles. explain.
FIG. 5 is a diagram illustrating a configuration example of the transmitter 10E of the wireless communication system according to the fifth embodiment of the present invention.
FIG. 5 illustrates the configuration of the transmitter 10E in the wireless communication system. As the receiver, for example, the receiver 20 of FIG. 1 can be used, and illustration and description thereof are omitted.

The transmitter 10E shown in FIG. 5 differs from the transmitter 10 shown in FIG. 1 in that digital delta-sigma modulation circuits 58 and 68 (FIG. 5) are added in the digital transmission module 104 (FIG. 5). The carrier frequency generation circuit 71 (FIG. 1) and the transmission multipliers 17 and 27 (FIG. 1) in FIG. 1 are deleted. Since other than that is the same, repeated description will be omitted as appropriate.
In FIG. 5, the outputs of the adder circuit 16 and the adder circuit 26 pass through a digital delta sigma modulation circuit (first digital delta sigma modulation circuit) 58 and a digital delta sigma modulation circuit (second digital delta sigma modulation circuit) 68. Are respectively input to the power amplifier 18 and the power amplifier 28.

According to the fifth embodiment, the outputs of the adder circuits 16 and 26 can be up-converted (frequency conversion to a higher frequency) using the alias signals generated by the digital delta-sigma modulation circuits 58 and 68.
Therefore, in the wireless system in which the transmitter 10E of the present (fifth) embodiment transmits with an arbitrary polarization and the receiver receives with an arbitrary polarization, a carrier frequency generation circuit 71 (FIG. 1) is transmitted from the transmitter. The analog circuits of the transmission multipliers 17 and 27 (FIG. 1) can be eliminated.
Therefore, the aging resistance of the transmitter of the wireless system in which the transmitter 10E of the present (fifth) embodiment transmits with an arbitrary polarization and the receiver 20 (FIG. 1) receives with an arbitrary polarization, and Temperature change resistance can be improved. It is also effective in improving the reliability of the wireless system.

<< Sixth Embodiment >>
As a sixth embodiment of the present invention, another configuration example of a receiver of a wireless communication system in which a transmitter transmits with polarized waves with different angles in time series and a receiver receives with polarized waves with different angles. explain.
FIG. 6 is a diagram illustrating a configuration example of the receiver 20F of the wireless communication system according to the sixth embodiment of the present invention.
FIG. 6 illustrates the configuration of the receiver 20F in the wireless communication system. For example, the transmitter 10 of FIG. 1 can be used as the transmitter, and thus illustration and description thereof are omitted.

The receiver 20F shown in FIG. 6 is different from the receiver 20 shown in FIG. 1 in that a local oscillation circuit 38, reception multipliers 32 and 42, low-pass filters 33 and 43, and a buffer amplifier 34 are provided. , 44 are deleted, and a clock generation circuit (CLK) 81 and reception delta-sigma circuits 72 and 82 are added instead.
Then, the outputs of the low noise amplifier 31 and the low noise amplifier 41 are respectively supplied to a reception delta sigma circuit (first reception delta sigma circuit) 72 and a reception delta sigma supplied with a clock from a clock generation circuit (CLK) 81. A first input and a second input of the digital reception module 201 are provided via a circuit (second reception delta sigma circuit) 82.

According to the present (sixth) embodiment, the outputs of the low noise amplifier 31 and the low noise amplifier 41 can be down-converted using alias signals generated by the reception delta sigma circuits (delta sigma circuits) 72 and 82. Therefore, in the wireless communication system of the present embodiment, when the transmitter (for example, the transmitter 10: FIG. 1) transmits with an arbitrary polarization and the receiver 20F receives with an arbitrary polarization, the receiver 20F. From the local oscillation circuit 38 (FIG. 1), the reception multipliers 32 and 42 (FIG. 1), the low-pass filters 33 and 43 (FIG. 1), and the analog circuits such as the buffer amplifiers 34 and 44 (FIG. 1). it can.
Therefore, the aging of the receiver of the wireless system in which the transmitter (for example, transmitter 10: FIG. 1) of the present (sixth) embodiment transmits with an arbitrary polarization and the receiver receives with an arbitrary polarization. The resistance to change and the resistance to temperature change can be improved, which is effective in improving the reliability of the wireless system.

<< Seventh Embodiment >>
As a seventh embodiment of the present invention, another configuration example of a transmitter of a wireless communication system in which a transmitter performs transmission with polarized waves having different angles in time series and a receiver performs reception with polarized waves having different angles. explain.
FIG. 7 is a diagram illustrating a configuration example of the transmitter 10G of the wireless communication system according to the seventh embodiment of the present invention.
In FIG. 7, the configuration of the transmitter 10G in the wireless communication system is illustrated. As the receiver, for example, the receiver 20 of FIG. 1 can be used, and illustration and description thereof are omitted.

Digital transmission module 105, a cosine fundamental carrier wave generating circuit 52 of the carrier frequency (omega _m), carrier frequency (omega _m) fundamental rotational polarization frequency (omega), or the fundamental rotating polarized wave frequencies different integer multiples of the frequency ( a plurality of cosine subcarrier generating circuit (531 and 532 K?) were added frequency _{(ω m + Kω), ···} , and 53K), a sine fundamental carrier wave generating circuit 62 of the carrier frequency (omega _m), carrier frequency A plurality of sinusoidal subcarrier generation circuits (631, 632) having a frequency (ω _m + Kω) obtained by adding (K _m ), which is a basic rotational polarization frequency (ω), or an integral multiple of (Kω) different from the fundamental rotational polarization frequency to (ω _m ). ,..., 63K).
The digital transmission module 105 includes an adder circuit (third adder circuit) 57 that adds (sums) the signals of the plurality of cosine subcarrier generation circuits (531, 532,..., 53K); An adder circuit (fourth adder circuit) 67 that adds (sums) the signals of the plurality of sine subcarrier generation circuits (631, 632,..., 63K).

The digital transmission module 105 includes an in-phase synthesis circuit 51 that synthesizes the output of the cosine basic carrier generation circuit 52 and the output of the addition circuit 57 in phase, and the output of the sine basic carrier generation circuit 62. And an anti-phase synthesis circuit 61 for synthesizing the output of the adder circuit 67 in anti-phase.
The digital transmission module 105 also multiplies (multiplies) the output (ω _i (t)) of the information signal generator 100 and the output of the in-phase synthesis circuit 51 (the ninth transmission multiplier). 59 and a transmission multiplier (tenth transmission multiplier) 69 that multiplies (multiplies) the output (ω _i (t)) of the information signal generator 100 and the output of the anti-phase synthesis circuit 61. I have.
The digital transmission module 105 includes a digital delta sigma modulation circuit 58 that delta-sigma modulates the output of the transmission multiplier 59 and a digital delta sigma modulation circuit 68 that delta-sigma modulates the output of the transmission multiplier 69. I have.
Outputs of the digital delta sigma modulation circuits 58 and 59 are output as two output signals of the digital transmission module 105.

The output of the digital delta sigma modulation circuit 58 is amplified by the power amplifier 18 and radiated from the transmitting antenna 19 to the space.
The output of the digital delta sigma modulation circuit 68 is amplified by the power amplifier 28 and radiated from the transmitting antenna 29 to the space.

  Since the digital transmission module 105 according to the seventh embodiment of the present invention can reduce the number of multipliers compared to the digital transmission module 101 according to the first embodiment shown in FIG. The digital signal processing load can be reduced. Therefore, the transmitter 10G according to the present (seventh) embodiment is effective in reducing the power consumption of the transmitter of the wireless system in which the transmitter 10G transmits with an arbitrary polarization and the receiver receives with an arbitrary polarization.

In the digital transmission module 105 shown in FIG. 7, the carrier frequency is expressed as ω _m, and in FIG. 1, the carrier frequency is expressed as ω _c in the carrier frequency generation circuit 71. Both ω _m and ω _c represent the carrier frequency, but there is a relationship of ω _m <ω _c . That is, the carrier frequency ω _m in FIG. 7 of the seventh embodiment is a relatively low frequency of 1 GHz or less. That is, the digital transmission module 105 in FIG. 7 can be configured with a DSP if the carrier frequency ω _m is 400 MHz or less, for example, and there is an effect that the transmitter 10G can be made compact and cost-effective.

<< Eighth Embodiment >>
As an eighth embodiment of the present invention, another configuration example of a wireless communication system in which a transmitter performs transmission with polarized waves with different angles in time series and a receiver performs reception with polarized waves with different angles will be described.
FIG. 8 is a diagram illustrating a configuration example of a wireless communication system according to the eighth embodiment of the present invention.
In FIG. 8, the configuration of the transmitter 10H and the receiver 20H in the wireless communication system is illustrated.

<Digital transmission module 106>
The digital transmission module 106 shown in FIG. 8 further includes a BPSK (Binary Phase Shift Keying) modulator (BPSKMOD) 50 in addition to the configuration of the digital transmission module 104 of the transmitter 10E according to the fifth embodiment shown in FIG. It is.
The output of the information signal generator 100 is converted into a positive / negative binary signal using a BPSK modulator (binary signal converter) 50. For this positive / negative binary signal, the cosine polarization of the fundamental rotational polarization frequency, the cosine polarization of an integer multiple of the fundamental rotational polarization frequency, the sine polarization of the fundamental rotational polarization frequency, the fundamental It performs sinusoidal polarization with a frequency that is an integral multiple of the rotational polarization frequency.
Except for the addition of the BPSK modulator 50, the transmitter 10E is the same as the transmitter 10E according to the fifth embodiment illustrated in FIG.

<Receiver 20H>
The receiver 20H shown in FIG. 8 is different from the receiver 20 shown in FIG. 1 in that a local oscillation circuit 38, reception multipliers 32 and 42, low-pass filters 33 and 43, and a buffer amplifier 34 are provided. , 44 are deleted, and a threshold generation circuit (TH) 70 and comparators 77 and 87 are added instead.
Then, the outputs of the low noise amplifier 31 and the low noise amplifier 41 are determined via a comparator (first comparator) 77 and a comparator (second comparator) 87 that determine the threshold value supplied from the threshold value generation circuit 70. It is converted to a square wave. These converted signals are inputted as the first input and the second input of the digital reception module 201, respectively.

<Wireless Communication System (Eighth Embodiment)>
According to the present (eighth) embodiment, by making the transmission signal of the transmitter 10H a binary signal, each circuit that performs frequency conversion from the analog circuit of the receiver 20H includes a comparator (77, 87) and threshold generation. It can be replaced with a circuit (TH) 70. Therefore, it is possible to greatly simplify the configuration of a receiver in a wireless system in which a transmitter transmits at an arbitrary polarization and a receiver receives at an arbitrary polarization, and the number of parts, size reduction, and consumption of the receiver can be greatly reduced. Electric power reduction is achieved. Further, it is effective in reducing the introduction cost of a radio system in which the transmitter transmits with an arbitrary polarization and the receiver receives with an arbitrary polarization.

<< Ninth embodiment >>
As a ninth embodiment of the present invention, another configuration example of a transmitter of a wireless communication system in which a transmitter performs transmission with polarized waves having different angles in time series and a receiver performs reception with polarized waves having different angles. explain.
FIG. 9 is a diagram illustrating a configuration example of the transmitter 10I of the wireless communication system according to the ninth embodiment of the present invention.
In FIG. 9, the configuration of the transmitter 10I in the wireless communication system is illustrated. As the receiver, for example, the receiver 20 of FIG. 1 can be used, and illustration and description thereof are omitted.

The transmitter 10I shown in FIG. 9 is different from the transmitter 10 shown in FIG. 1 in that the information signal generator 100 of FIG. 1 is replaced with an information signal generation module 60 in FIG. Since other than that is the same, repeated description will be omitted as appropriate.
In FIG. 9, the information signal generation module 60 includes an information signal generation circuit 54, a synchronization signal generation circuit 55, a selection switch 64, and a data buffer 65.
An information signal to be transmitted is output from the information signal generation circuit 54. The synchronization signal generation circuit 55 outputs a synchronization signal for synchronization.
The outputs of the information signal generation circuit 54 and the synchronization signal generation circuit 55 are selected by being switched by the selection switch 64, and either output of the information signal generation circuit 54 or the synchronization signal generation circuit 55 is input to the data buffer 65. It is sent out and becomes the output of the information signal generation module 60.

For example, when the receiver 20 of FIG. 1 receives the output of the information signal generation module 60 of FIG. 9, the receiver 20 receives the synchronization signal from the received signal by the digital reception module 201 (FIG. 1). Can be detected. This detected synchronization signal can be used for synchronization at the time of reception.
Since the transmitter 10I and the receiver (for example, the receiver 20: FIG. 1) can be synchronized by the configuration in which the synchronization signal generation circuit 55 (FIG. 9) is added in this way, a specific transmission that the transmitter 10I transmits The receiver can know the polarization. For this reason, it is possible to easily determine the optimum polarizations of the transmitter and the receiver so that the transmitter 10I and the receiver can perform good data transmission between transmission and reception.
That is, there is an effect in improving the throughput of a wireless communication system in which the transmitter of the present (9th) embodiment performs transmission with an arbitrary polarization and the receiver receives with an arbitrary polarization.

«Tenth embodiment»
As a tenth embodiment of the present invention, another configuration example of a transmitter of a wireless communication system in which a transmitter performs transmission with polarized waves having different angles in time series and a receiver performs reception with polarized waves having different angles. explain.
FIG. 10 is a diagram illustrating a configuration example of the transmitter 10J of the wireless communication system according to the tenth embodiment of the present invention. As the receiver, for example, the receiver 20 of FIG. 1 can be used, and illustration and description thereof are omitted.

The transmitter 10J shown in FIG. 10 differs from the transmitter 10E shown in FIG. 5 in that the information signal generator 100 of FIG. 5 is replaced with an information signal generation module 60 in FIG. Since other than that is the same, repeated description will be omitted as appropriate.
10, the information signal generation module 60 includes an information signal generation circuit 54, a synchronization signal generation circuit 55, a selection switch 64, and a data buffer 65.
The outputs of the information signal generation circuit 54 and the synchronization signal generation circuit 55 are selected by being switched by the selection switch 64, and the output of either the information signal generation circuit 54 or the synchronization signal generation circuit 55 is sent to the data buffer 65. Then, it becomes an output of the information signal generation module 60.
Similarly to the ninth embodiment shown in FIG. 9, the transmitter 10J and the receiver (for example, the receiver 20: FIG. 1) can be synchronized with the configuration to which the synchronization signal generation circuit 55 is added. The receiver can know the specific polarization transmitted by 10J. For this reason, it is possible to easily determine the optimum polarization of the transmitter and the receiver so that the transmitter 10J and the receiver can perform good data transmission between transmission and reception.
That is, the present invention is effective in improving the throughput of a radio communication system in which the transmitter of the present invention transmits with an arbitrary polarization and the receiver receives with an arbitrary polarization.

<< 11th Embodiment >>
As an eleventh embodiment of the present invention, a configuration example of an elevator system 1100 to which a wireless communication system in which a transmitter performs transmission with polarized waves with different angles in time series and a receiver performs reception with polarized waves with different angles is applied. Will be explained.
FIG. 11 is a diagram illustrating a configuration example of an elevator system 1100 according to an eleventh embodiment of the present invention.
In FIG. 11, in the elevator system 1100 of the present (eleventh) embodiment, the elevator cage 1111 moves up and down in the building 1101 where the elevator is installed.

In addition, a base station radio 1103a including a transmitter and a receiver including an antenna capable of transmitting and receiving the rotational polarization described in the first to tenth embodiments and a base station rotation are provided on the floor inside the building 1101. A polarization antenna 1102a is connected and installed. Then, the signal generated by the base station radio 1103a is transmitted from the base station rotational polarization antenna 1102a.
Note that the base station rotational polarization antenna 1102a includes two orthogonal antennas (for example, transmission antennas 19 and 29: FIG. 1).
In addition, a base station radio 1103b and a base station rotational polarization antenna 1102b each having a transmitter and a receiver including an antenna capable of transmitting and receiving the rotational polarization are coupled to a ceiling portion of the building 1101. Installed. The base station rotational polarization antenna 1102b is also composed of two orthogonal antennas.

On the outer floor surface of the lifting / lowering cage 1111, a terminal station rotation bias including a transmitter and a receiver using a rotation polarization electromagnetic wave including the antenna capable of transmitting and receiving the rotation polarization described in the first to tenth embodiments. A wave antenna 1112a is installed.
In addition, a terminal station rotational polarization antenna 1112b equipped with a transmitter and receiver using a rotationally polarized electromagnetic wave having an antenna capable of transmitting and receiving the rotational polarization is installed on the external ceiling of the lifting cage 1111. Yes.
Both the terminal station rotational polarization antenna 1112 a and the terminal station rotational polarization antenna 1112 b are coupled to the terminal station radio 1113 using a high-frequency cable 1114.

Since the base station radios 1103a and 1103b and the terminal station radio 1113 use the inside of the building 1101 as a radio transmission medium, the electromagnetic waves are subjected to multiple reflections by the inner wall of the building 1101 and the outer wall of the lifting cage 1111. An interference environment is formed.
In the elevator system 1100 of the present (11th) embodiment, since the wireless communication system of any of the first to 10th embodiments is used, communication between transmission and reception is performed using a plurality of reflected waves in a multiwave interference environment. High-quality wireless transmission that compensates for quality degradation is possible.
That is, by using the wireless connection means using the wireless communication system, the elevator cage 1111 of the elevator system 1100 can be controlled and monitored remotely in the building 1101 without using the wired connection means. The wired connection means can be deleted.
Therefore, the same transportation capacity can be realized with a smaller building volume, or the transportation capacity can be improved by increasing the elevator size with the same building volume.

<< Twelfth Embodiment >>
As a twelfth embodiment of the present invention, a substation equipment monitoring system 1200 to which a wireless communication system in which a transmitter transmits with polarized waves with different angles in time series and a receiver receives with polarized waves with different angles is applied. A configuration example will be described.
FIG. 12 is a diagram illustrating a configuration example of a substation equipment monitoring system 1200 according to the twelfth embodiment of the present invention.
In FIG. 12, a substation equipment monitoring system 1200 according to the present (twelfth) embodiment uses a plurality of substations 1201 and the radio communication system according to any one of the first to tenth embodiments. The machine 1203 and the terminal station polarization antenna 1202 are combined and installed.
Also, a smaller number of base station apparatuses 1211 than the number of the substations 1201 are installed in the vicinity of the plurality of substations 1201. A base station radio 1213 using the radio communication system according to any one of the first to tenth embodiments and a base station rotational polarization antenna 1212 are connected and installed. Then, the signal generated by the base station radio 1213 is transmitted from the base station rotational polarization antenna 1212.

In addition, the terminal station radio 1203 includes a transmitter and a receiver of a radio communication system that uses an electromagnetic wave having a rotationally polarized wave that includes an antenna capable of transmitting and receiving the rotationally polarized wave.
The base station apparatus 1211 includes a transmitter and a receiver of a wireless communication system that uses an electromagnetic wave having a rotationally polarized wave and includes an antenna capable of transmitting and receiving the rotationally polarized wave.
In FIG. 12, there are a plurality of transformers 1201, a base station apparatus 1211, a base station rotational polarization antenna 1212, and a base station radio 1213, but only representative ones are denoted by the same reference numerals. The sign is not given to the thing.

Since the dimensions of the outer shape of the transformer 1201 are on the order of several meters and are overwhelmingly larger than wavelengths corresponding to several hundred MHz to several GHz which are frequencies of electromagnetic waves used by the radio, the plurality of transformers By 1201, the electromagnetic wave receives multiple reflections, and a multi-wave interference environment is formed.
In the substation equipment monitoring system 1200 of the present (12th) embodiment, the radio communication system according to any one of the first to 10th embodiments is applied. It is possible to realize high-quality wireless transmission that compensates for a decrease in communication quality between transmission and reception using.
Therefore, using the wireless connection means to which the above-described wireless devices (transmitters, receivers) are applied, the control / monitoring of the transformer 1201 is performed by the base station apparatus 1211 of a plurality of wireless base stations without using the wired connection means. Can be implemented remotely. Further, a failure of the transformer 1201 can be detected.
Therefore, it is possible to solve the problem of high-voltage induced power that becomes a problem when using a wired connection means such as a cable, and it is possible to eliminate the installation cost of the cable. Therefore, it is effective in improving the safety and reducing the cost of the control / monitoring system (transformer equipment monitoring system) of the substation 1201.

<< Other Embodiments >>
Although the present invention has been specifically described based on the above-described embodiments, the present invention is not limited to the above-described embodiments, and various modifications can be made without departing from the scope of the invention.
Other embodiments and modifications will be further described below.

<< Combination of integer multiples of different fundamental rotational polarization frequencies: Part 1 >>
In the first embodiment shown in FIG. 1, the fundamental rotational polarization frequency is ω, the integral multiples of the fundamental rotational polarization frequency are different, and 2ω,. However, it may not necessarily be a combination of consecutive integers. It may be a combination of integers with intermediate integers skipped.

<< Combination of frequencies with different integral rotational polarization frequencies: Part 2 >>
In addition, as an integer multiple frequency different from the fundamental rotational polarization frequency, an integer from 2 to N may be a power of 2 or a combination of even numbers in 2ω,..., Nω.
In this case, since there is a common divisor 2 in integers from 2 to N, the delay amount T / N of the delay units (351,..., 35N) in the digital reception module 201 of the receiver 20 of FIG. However, since the frequency cycle and the sampling cycle are in an integer multiple relationship at any integer multiple of the fundamental rotational polarization frequency, data that can be easily processed by the baseband processing circuit 48 (FIG. 1) can be obtained. There is an effect that it can be acquired.

<< Combination of integer multiples of different fundamental rotational polarization frequencies: Part 3 >>
In the third embodiment shown in FIG. 3, the basic rotational polarization frequency is assumed to be ω, the integral multiples of the basic rotational polarization frequency are different, and Mω and Nω are used as a combination in which M and N are relatively prime. However, the combination of M and N is not necessarily required. For example, three combinations of L, M, and N that are relatively prime may be used. In this case, there is an effect that the frequency that can be effectively used is further increased.

《Delay amount of delay device》
In the first embodiment shown in FIG. 1, the delay amount of the delay units (351,..., 35N) in the digital reception module 201 of the receiver 20 is T / N, where N is the transmitter 10. In the digital transmission module 101, it is described that the switching unit 13 is constant regardless of the selection of the switching unit 13. However, when the switching unit 13 selects one of cos ωt,. ,..., 35N) may be configured to interlock and change the value of N in the T / N of the delay amount.
In this case, there is an effect that the reception sensitivity is further improved.

《Application to solar power generation system》
In the twelfth embodiment shown in FIG. 12, an example of a substation equipment monitoring system in which a plurality of substations 1201 are arranged has been described, but a similar application example is not limited to the above.
For example, the above-described wireless communication system can also be applied to a power generation facility monitoring system in a solar cell power generation system in which a plurality of solar cells are arranged.
In a power generation facility in which a plurality of solar cells are arranged, it is not always a good idea to use electric wiring for control or monitoring. Therefore, control or monitoring by wireless communication is performed.
At this time, since the environment in which the plurality of solar cells are arranged is a multiwave interference environment, it is effective to apply the above-described wireless communication system.

10, 10B, 10C, 10E, 10G, 10H, 10I, 10J Transmitter 11 Cosine fundamental wave generation circuit 13, 23 Switcher 14, 15, 17, 24, 25, 27, 59, 69, 152-15N, 252 25N transmission multiplier 16, 26, 16B, 26B, 57, 67 Adder circuit 18, 28 Power amplifier 19, 29 Transmit antenna 20, 20C, 20D, 20F, 20H Receiver 21 Sine fundamental wave generation circuit 31, 41 Low noise amplifier 32, 42 Reception multiplier 33, 43 Low-pass filter 34, 44 Buffer amplifier 38 Local oscillation circuit 39, 49 Reception antenna 48, 88 Baseband processing circuit 50 BPSK modulator (binary signal converter)
Reference Signs List 51 In-phase synthesis circuit 52 Cosine basic carrier generation circuit 54 Information signal generation circuit 55 Synchronization signal generation circuit 58, 68 Digital delta-sigma modulation circuit 60 Information signal generation module 61 Reverse phase synthesis circuit 62 Sine basic carrier generation circuit 64 Select switch 65 Data buffer 70 Threshold Generation Circuit 71 Carrier Frequency Generation Circuit 72, 82 Reception Delta Sigma Circuit 77, 87 Comparator 81 Clock Generation Circuit 100 Information Signal Generator 101, 102, 103, 104, 105, 106, 107, 108 Digital Transmission Module 122-12N , 12M cosine harmonic generation circuit 201, 202, 203 Digital reception module 222-22N, 22M sine harmonic generation circuit 351-35N, 451-45N, 7411-741m, ..., 74N1-74Nm , 751-75M, 8411-841m,..., 84N1-84Nm, 851-85M Delay devices 361-36N, 461-46N, 761-76M, 861-86M, 3611-361m, 36N1-36Nm, 4611-461m, 46N1-46Nm Decimator 531-53K Cosine subcarrier generation circuit 631-63K Sine subcarrier generation circuit 731-73N, 831-83N Reception synthesis circuit 1100 Elevator system 1101 Building 1102a, 1102b Base station Rotating polarization antenna 1103a, 1103b Base station radio Machine 1111 Lifting cage 1112a, 1112b Terminal station rotation polarization antenna 1113 Terminal station radio 1114 High frequency cable 1200 Substation equipment monitoring system 1201 Electric transformer 1202 Terminal station rotation polarization antenna 1203 Station radio 1211 base station apparatus 1212 base station rotary polarized antenna 1213 base station radios

Claims (12)

A wireless communication system comprising a transmitter and a receiver having a plurality of spatially orthogonal antennas and performing wireless communication by rotating the polarization of a carrier wave carrying an information signal,
The transmitter rotates a polarization of the carrier wave at a plurality of rotation frequencies that are integer multiples of any one of the frequencies, and transmits a plurality of carrier waves having the polarizations at the plurality of rotation frequencies. With means,
The receiver includes an information signal detection unit that removes a carrier wave from a reception signal including the information signal, and selects and combines each signal obtained from the plurality of rotation frequencies in a predetermined combination. Wireless communication system. A wireless communication system comprising a transmitter and a receiver having a plurality of spatially orthogonal antennas and performing wireless communication by rotating the polarization of a carrier wave carrying an information signal,
The transmitter rotates a polarization of the carrier wave at a plurality of rotation frequencies that are integer multiples of any one of the frequencies, and transmits a plurality of carrier waves having the polarizations at the plurality of rotation frequencies. With means,
The receiver
Carrier wave removing means for removing a carrier wave from the received signal including the information signal;
Sampling at a time interval obtained by dividing a cycle corresponding to any one frequency by a maximum integer of the integer multiple, and data acquisition means for storing data acquired by sampling at each cycle at different timings;
Information signal synthesizing means for selecting and synthesizing a plurality of signals obtained by digital frequency conversion of the data into any one of the frequencies in a predetermined combination;
A wireless communication system comprising: In claim 1 or claim 2,
The transmitter rotates the polarization of the carrier wave at two rotation frequencies and transmits the two carrier waves together;
The two rotation frequencies are one frequency and an integer multiple of the frequency,
A radio communication system, wherein a carrier wave having a rotation frequency that is an integral multiple of the frequency is switched to a carrier wave having a rotation frequency that is an integer multiple different from the integer multiple. In claim 3,
The one frequency, an integer that is an integer multiple of the frequency, and an integer that is an integer multiple different from the integer are relatively prime,
Switch the frequency of integer multiples of the two integers that are relatively prime,
The receiver removes a carrier wave from the received signal, branches to two rotation frequencies used by the transmitter, and corresponds to any one of the rotation frequencies by an integer multiple of each of the branched signals. Sampling a cycle at a time interval divided by any one of the integers, storing data sampled for each cycle at different timings, and digitally converting them to any one of the frequencies Communications system. In any one of Claims 1 thru | or 4,
The receiver removes a carrier wave from the received signal, samples at a time interval obtained by dividing a period corresponding to any one frequency by an integer obtained by multiplying the integer that is the integer multiple by another integer,
The sampled results are added together for the other integers and added,
Data sampled every period corresponding to the maximum integer of the integer multiple at different timings are accumulated, and a plurality of signals obtained by digital frequency conversion of the data to any one of the above frequencies are selected in a predetermined combination. A wireless communication system characterized by combining. In any one of Claims 1 thru | or 5,
The transmitter synthesizes cosine waves with different rotational frequencies, superimposes an information signal, multiplies the carrier wave and transmits it from the first antenna,
A wireless communication system characterized by combining sine waves of different rotational frequencies, superimposing an information signal, multiplying the carrier wave, and transmitting from a second antenna spatially orthogonal to the first antenna. In any one of Claims 1 thru | or 5,
The transmitter uses a plurality of cosine wave signals and sine wave signals having a frequency that is an integral multiple of zero including a carrier frequency and a rotation frequency of zero,
A plurality of cosine wave signals obtained by adding a positive integer multiple of rotation frequency to the carrier wave frequency to the cosine wave signal of the carrier wave frequency are added in phase, and the information signal is superimposed and transmitted from the first antenna.
A second antenna that is spatially orthogonal to the first antenna by adding a plurality of sinusoidal signals obtained by adding a positive integer multiple of the carrier frequency to the sine wave signal of the carrier frequency in reverse phase and superimposing the information signal A wireless communication system, wherein In claim 6 or claim 7,
The transmitter comprises a delta-sigma circuit;
Wireless communication system, characterized in that the up-converted signal to the carrier wave frequency, is formed by using the alias signal delta-sigma circuit generates. In any one of Claims 6 to 8,
The transmitter includes a binary signal converter, wherein the binary signal converter modulates the information signal with a binary signal;
The wireless communication system, wherein the receiver includes a comparator having a threshold value set, and the received signal having the information signal is demodulated by the comparator. In any one of Claims 6 to 8,
The transmitter selectively transmits an information signal and a synchronization signal;
The wireless communication system, wherein the receiver detects the synchronization signal and synchronizes with the transmitter using the synchronization signal. An elevator system comprising the wireless communication system according to any one of claims 1 to 10. A substation monitoring system comprising the wireless communication system according to any one of claims 1 to 10.

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