JP6370104B2 - Wire impedance matching device and system - Google Patents

Description

  The present invention relates to a wire impedance matching device and system for matching the impedance of each wire of a multi-laying wire.

  Generally, a bus duct or the like is used in a low-voltage and large-capacity electric circuit. Moreover, it may replace with a bus duct and may lay many low voltage | pressure cables (electric wire) from the surface of workability | operativity or cost-saving (for example, refer patent document 1). In this case, the allowable current is calculated on the assumption that the current is distributed evenly over the multiple wires, but in reality, the load current is not evenly distributed over the wires of each line due to the difference in the layout of the electric circuit and the contact resistance. In some cases, the load current concentrates on the wires and flows into an overheated state. This is presumably because impedance variation occurs due to the influence of the contact resistance of each wire laid in multiple lines and the mutual inductance from other lines.

  If an imbalance occurs in the load current flowing through the wires of each line, the current of the specific wire may increase and the wire may burn out. Therefore, even if an imbalance occurs in the load currents of the electric wires of the respective strips, electric wires having a large current capacity are employed so that the electric wires do not burn out.

JP 2002-122627 A

  However, if an electric wire with a large current capacity is adopted, the cost becomes high, and the electric wire becomes thick, so that the installation work becomes difficult. In addition, when the load current increases due to the addition of a load, etc., a wire (strip) with insufficient current capacity will be added to the multi-strip laying wire. In addition to the wires having the same current capacity, wires having different current capacities may be added. Even in such cases, it is necessary to prevent unbalance in the load current flowing through the wires of each line.

  Therefore, the present applicant has developed an application that can suppress the unbalance of the current flowing through each electric wire by matching the impedance of each electric wire so that the current flowing through each electric wire is balanced, and filed as Japanese Patent Application No. 2013-105833. .

This means that at least n-1 combinations including n wires are always selected from the combination of two wires _n C ₂ of n (n = 2, 3, 4,...) Wires. The two selected electric wires are set as a set, and are passed through the through holes of separate iron cores for each set in a direction in which the magnetic fluxes generated by the currents of the two wires are canceled out.

  In Japanese Patent Application No. 2013-105833, there is a limit to reducing the size and weight of the device because two wires are passed through the through-hole of the iron core, and magnetic fluxes generated by the currents of the two wires cancel each other. There is room for improvement in workability because two wires must be penetrated in the direction.

  An object of the present invention is to provide an electric wire impedance matching device and system that can suppress an imbalance of currents flowing through each of multiple wires laid, and that can be reduced in size and weight and improved in workability.

The wire impedance matching device of the present invention comprises a closed iron core having a through hole in a central portion thereof and forming a magnetic circuit by a current of an electric wire penetrating the through hole, and a winding formed on the iron core, A transformer is formed with the electric wire penetrating the through hole as the primary side and the winding as the secondary side, and at least 2n of the transformers corresponding to n (n = 3, 4, 5,...) Wires Prepare at least 2 wires by passing through the through holes of the iron core of at least 2 transformers for each of the n wires, and selecting at least 2 wires in the order of the ring from the n wires N transformers, and the secondary side of each of the at least two transformers so as to cancel the magnetic flux generated in the iron core on the primary side of each of the at least two transformers of each of the n sets. The total current generated in the windings of each of the at least two Vessels of the secondary winding of the to flow to the secondary side winding at least two of each of the transformer connected in series, characterized in that the formation of the secondary circuit.

According to the present invention, at least 2n transformers are prepared corresponding to n (n = 3, 4, 5,...) Wires, and at least two transformer cores are provided for each n wires. And selecting at least two wires in the order of the ring from the n wires to form n sets of at least two transformers, and at least two of each of the n sets. The total current generated in the secondary windings of the at least two transformers is at least two of the transformers in each transformer so as to cancel the magnetic flux generated in the primary core of each transformer. Since the secondary windings of at least two transformers are connected in series so as to flow through the secondary windings, this secondary circuit causes the current imbalance of the primary side of the at least two transformers. Can be suppressed.

Explanatory drawing of the electric wire impedance matching apparatus which concerns on 1st Embodiment of this invention. FIG. 2 is a detailed circuit diagram of FIG. FIG. 3 is a circuit diagram of individual iron cores when secondary windings of two iron cores shown in FIG. 2 are not connected in series. The magnetic circuit diagram of FIG.2 and FIG.3. The vector diagram of the electric current and magnetic flux of the electric wire impedance matching apparatus which concerns on 1st Embodiment of this invention. The circuit diagram of the other example of the electric wire impedance matching apparatus which concerns on 1st Embodiment of this invention. Explanatory drawing of the imbalance suppression of an electric current at the time of applying the electric wire impedance matching apparatus which concerns on 1st Embodiment of this invention to the electric circuit whose 1 phase electric wire is 4 articles | strands. The circuit diagram of the electric wire impedance matching apparatus which concerns on 2nd Embodiment of this invention. The lineblock diagram of the electric wire impedance matching device concerning a 3rd embodiment of the present invention. The circuit diagram of other examples of the electric wire impedance matching device concerning a 3rd embodiment of the present invention. The lineblock diagram of the electric wire impedance matching system concerning a 4th embodiment of the present invention. The lineblock diagram of the electric wire impedance matching system concerning a 5th embodiment of the present invention. The lineblock diagram of the electric wire impedance matching system concerning a 6th embodiment of the present invention.

  Embodiments of the present invention will be described below. 1A and 1B are explanatory diagrams of a wire impedance matching device according to a first embodiment of the present invention. FIG. 1A is a configuration diagram, and FIG. 1B is a circuit diagram. In FIG. 1, the case where the wire impedance matching apparatus which concerns on 1st Embodiment is applied with respect to the electric wires 11a and 11b whose 1 phase is 2 articles | strands is shown.

  As shown to Fig.1 (a), the closed iron cores 12a and 12b have a through-hole in the center part, and let the electric wires 11a and 11b penetrate the through-hole. On the other hand, windings (not shown) are formed on the iron cores 12a and 12b, and terminals K and L are provided at both ends of the windings. The terminal K of the iron core 12a and the terminal L of the iron core 12b are connected, and the terminal L of the iron core 12a and the terminal K of the iron core 12b are connected. As a result, two transformers are formed with the electric wires 11a, 11b penetrating through the through holes of the iron cores 12a, 12b as the primary side and the windings formed in the iron cores 12a, 12b as the secondary side, The secondary side windings of 12b are connected in series to form a closed loop secondary side circuit.

  When the currents Ia1 and Ib1 flow through the electric wires 11a and 11b passing through the through holes of the iron cores 12a and 12b, a magnetic circuit is formed in the iron cores 12a and 12b by the currents Ia1 and Ib1, and magnetic fluxes φa and φb are generated in the iron cores 12a and 12b. Will occur. In the secondary circuit of the iron cores 12a and 12b, currents Ia2 and Ib2 flow in a direction to cancel the magnetic fluxes φa and φb generated in the iron cores 12a and 12b. This is because a transformer is formed in which the wires 11a and 11b penetrating the iron cores 12a and 12b are primary windings, and the windings formed on the iron cores 12a and 12b are secondary windings. is there. Since the electric wires 11a and 11b only penetrate the iron core, it is assumed that the number of turns around the iron cores 12a and 12b is one. Further, since the windings formed on the iron cores 12a and 12b have the same number of turns, the current transformation ratios of the iron cores 12a and 12b are the same.

  In FIG. 1B, the secondary windings of the iron cores 12a and 12b are formed between the terminals K and L, and the secondary circuit of the iron cores 12a and 12b forms a closed loop. The current I2 flowing through the secondary circuit of the iron cores 12a and 12b is the sum of the currents Ia2 and Ib2 in the direction to cancel the magnetic fluxes φa and φb generated in the iron cores 12a and 12b.

  Next, operation characteristics of the wire impedance matching device according to the first embodiment of the present invention will be described. FIG. 2 is a detailed circuit diagram of FIG. The secondary windings 13a and 13b of the iron cores 12a and 12b are formed between the terminals K and L, and the secondary circuit of the iron cores 12a and 12b forms a closed loop. When currents Ia1 and Ib1 flow through the electric wires 11a and 11b penetrated through the through holes of the iron cores 12a and 12b, magnetic fluxes φa and φb are generated by the currents Ia1 and Ib1. The current generated in the winding 13a in the direction to cancel the magnetic flux φa of the iron core 12a is Ia2, and the current generated in the winding 13b in the direction to cancel the magnetic flux φb in the iron core 12a is Ib2. Since the secondary side windings 13a and 13b of the iron cores 12a and 12b are connected in series to form a closed loop secondary side circuit, the current I2 flowing through the secondary side circuit of the iron cores 12a and 12b is the iron core 12a, This is the sum of currents Ia2 and Ib2 in a direction to cancel the magnetic fluxes φa and φb generated in 12b.

  FIG. 3 is a circuit diagram of the individual iron cores 12a and 12b when the secondary windings 13a and 13b of the two iron cores 12a and 12b shown in FIG. 2 are not connected in series, and FIG. FIG. 3B is a circuit diagram of the iron core 12a, and FIG. 3B is a circuit diagram of the iron core 12b.

  When the secondary windings 13a and 13b of the iron cores 12a and 12b are not connected in series, as shown in FIG. 3A, the secondary side circuit of the iron core 12a has a direction to cancel the magnetic flux φa of the iron core 12a. Current flows through Ia2. Similarly, as shown in FIG. 3B, the current Ib2 flows in the secondary side circuit of the iron core 12b in the direction to cancel the magnetic flux φb of the iron core 12b.

  4 is a magnetic circuit diagram of FIGS. 2 and 3, FIG. 4 (a) is a magnetic circuit diagram of FIG. 3 (a), FIG. 4 (b) is a magnetic circuit diagram of FIG. 3 (b), and FIG. (C) is a magnetic circuit diagram of FIG. As shown in FIG. 4A, when the magnetic circuit of the iron core 12a is a magnetomotive force Fa, a magnetic resistance Rma, and a magnetic flux φa, the magnetic flux φa is expressed by φa = Fa / Rma. Similarly, as shown in FIG. 4B, when the magnetic circuit of the iron core 12b is a magnetomotive force Fb, a magnetic resistance Rmb, and a magnetic flux φb, the magnetic flux φb is expressed by φb = Fb / Rmb.

  Here, the circuit of the first embodiment shown in FIG. 2 has a secondary circuit in which the secondary windings 13a and 13b of the iron cores 12a and 12b are connected in series. As shown, the magnetic circuit of FIG. 4A and the magnetic circuit of FIG. 4B are considered to be a series magnetic circuit. That is, the magnetic circuit is composed of magnetomotive force Fa + Fb, magnetic resistance Rma + Rmb, and magnetic flux φa + φb, and the magnetic flux φ is expressed by φ = φa + φb = (Fa + Fb) / (Rma + Rmb). The magnetic fluxes φa and φb of the iron cores 12a and 12b are ½ of the total magnetic flux φ (= φa and φb) by a secondary circuit in which the secondary windings 13a and 13b of the iron cores 12a and 12b are connected in series. The magnetic flux is balanced so as to be φ / 2.

  FIG. 5 is a vector diagram of current and magnetic flux of the wire impedance matching device according to the first embodiment of the present invention, FIG. 5A is a vector diagram of current flowing in the secondary circuit, and FIG. FIG. 5C is a vector diagram of the current flowing through the primary-side electric wires 11a and 11b.

  Currents Ia2 and Ib2 flow in the secondary circuit of the iron cores 12a and 12b in a direction to cancel the magnetic fluxes φa and φb generated in the iron cores 12a and 12b. As shown in FIG. 5A, the currents Ia2 and Ib2 are out of magnitude and phase, but the secondary circuits of the iron cores 12a and 12b are connected in series, so that the currents Ia2 and Ib2 are balanced. So that it flows in balance. That is, the current Ia2 is shifted in the direction of the arrow Xa, the current Ib2 is shifted in the direction of the arrow Xb, and the magnitude is also shifted to be equal. The total current after the shift becomes the current I2 of the secondary side circuit of the iron cores 12a and 12b. As a result, the currents Ia2 and Ib2 are balanced so that the current I2 / 2 is ½ of the total current I2.

Regarding the magnetic fluxes φa and φb generated in the iron cores 12a and 12b, the currents Ia2 and Ib2 of the secondary side circuits of the iron cores 12a and 12b flow in a balanced manner, so that the magnetic fluxes φa and φb are also balanced. As shown in FIG. 5B, the magnetic fluxes φa and φb are out of magnitude and phase, but the currents Ia2 and Ib2 of the secondary circuits of the iron cores 12a and 12b flow in a balanced manner so that they are balanced. The magnetic flux φa is shifted in the direction of the arrow Ya, the magnetic flux φb is shifted in the direction of the arrow Yb, and the sizes are also shifted to be equal.
The total magnetic flux after the shift becomes the magnetic flux φ. Thus, the magnetic fluxes φa and φb are balanced so that the magnetic flux φ / 2 is ½ of the total magnetic flux φ by the secondary side circuit in which the secondary side windings 13a and 13b of the iron cores 12a and 12b are connected in series. Is done.

  Similarly, for the currents Ia1 and Iba flowing through the primary-side wires 11a and 11b, the currents Ia2 and Ib2 of the secondary-side circuits of the iron cores 12a and 12b flow in a balanced manner, so that the magnetic fluxes φa and φb are also balanced. As shown in FIG. 5 (c), the currents Ia1 and Ib1 of the electric wires 11a and 11b are shifted in size and phase, but are balanced so that the currents Ia2 and Ib2 of the secondary circuit of the iron cores 12a and 12b are balanced. Therefore, the current Ia1 of the electric wire 11a is shifted in the direction of the arrow Za, the current Ib1 of the electric wire 11b is shifted in the direction of the arrow Zb, and the size is also shifted. Thereby, the currents Ia1 and Iba flowing through the primary-side electric wires 11a and 11b are balanced so as to be equal.

  In the above description, the case where one phase is applied to two wires 11a and 11b has been described, but it is also possible to apply to n (n = 2, 3, 4,...) Wires 11a to 11n. . In that case, n transformers are prepared corresponding to the n (n = 2, 3, 4,...) Strips of the electric wires 11a to 11n, and the n strips of the electric wires 11a to 11n are arranged one by one. It penetrates through the through holes of the iron cores 12a to 12n. Then, the secondary windings of the n transformers are connected in series so that the currents Ia2 to In2 generated in the secondary windings of the n transformers are added to form a secondary circuit. To do.

  FIG. 6 is a circuit diagram of another example of the wire impedance matching device according to the first embodiment of the present invention. One phase of the first embodiment shown in FIG. 1 is replaced with two wires 11a and 11b. The electric wire impedance matching device according to the first embodiment is applied to the electric wires 11a to 11d whose one phase is four.

  In FIG. 6, four transformers (four iron cores 12a to 12d) are prepared corresponding to the four wires 11a to 11d when applied to the four wires 11a to 11d. ˜11d is passed through the through holes of the four transformer cores 12a to 12d one by one. Then, the secondary windings of the four transformers (four iron cores 12a to 12d) are added so that the currents Ia2 to Id2 generated in the secondary windings of the four transformers are added. Terminals K and L are sequentially connected in series to form a secondary circuit. In this case, the same effect as that of the first embodiment can be obtained.

  FIG. 7 is an explanatory diagram of current imbalance suppression when the wire impedance matching device according to the first embodiment of the present invention is applied to an electric circuit having four lines of one-phase wires, and FIG. FIG. 7 is a current waveform diagram when the wire impedance matching device according to the first embodiment of the present invention is used, and FIG. 7B is a current waveform diagram when the wire impedance matching device is not used.

  As shown in FIG. 7B, when the wire impedance matching device is not used, the current flowing through each of the four wires is out of magnitude and phase, but according to the first embodiment of the present invention. When the wire impedance matching device is used, it can be seen that the currents flowing through the four wires are almost the same in magnitude and phase, and the unbalance of the currents Ia to Id flowing through the wires 11a to 11d can be suppressed.

  As described above, according to the first embodiment of the present invention, n transformers are prepared corresponding to n (n = 2, 3, 4,...) Wires, and one n wire is provided. The windings on the secondary side of the n transformers are added so that the currents generated in the windings on the secondary side of the n transformers are added to the through holes of the iron cores of the n transformers one by one. Are connected in series to form a secondary side circuit, and this secondary side circuit can suppress the current imbalance of the primary side of the n transformers. Further, only one electric wire passes through the through-hole of the iron core of each transformer, and the secondary side circuit is added with the current generated in the secondary side windings of the n number of transformers. Since the secondary side windings of the n transformers are simply formed in series, the apparatus can be reduced in size and weight and the directivity can be improved.

  Next, a second embodiment of the present invention will be described. FIG. 8 is a circuit diagram of the wire impedance matching device according to the second embodiment of the present invention, FIG. 8A is a circuit diagram of an example of the wire impedance matching device according to the second embodiment, and FIG. It is a circuit diagram of other examples of the electric wire impedance matching device concerning a 2nd embodiment.

  This second embodiment is different from the first embodiment in that a secondary side circuit is formed by connecting secondary windings of n transformers (n iron cores) in series. At least two wires are selected in the order of the ring from among the wires, and at least two transformers are formed, and the secondary windings of the at least two transformers are connected in series. A secondary circuit is formed.

  In FIG. 8A, an example of the second embodiment is obtained by arranging secondary windings of four transformers (four iron cores 12a to 12d) in the first embodiment shown in FIG. Instead of forming a secondary circuit by connecting in series, select two wires in the order of the ring from the four wires 11a to 11d, and form four sets of transformers of two each. A secondary circuit is formed by connecting secondary windings of two transformers in series.

  In FIG. 8, first, two wires are selected in the order of the ring from the four wires 11a to 11d. Two wires 11a and 11b, two wires 11b and 11c, two wires 11c and 11d, and two wires 11d and 11a are selected. Next, four pairs of two transformers are formed. That is, a set of two transformers of a transformer of the iron core 12a1 and a transformer of the iron core 12b1 is formed for the two wires 11a and 11b. Hereinafter, similarly, two sets of transformers of a transformer of the iron core 12b2 and a transformer of the iron core 12c1 are formed for the two wires 11b and 11c, and the two wires 11c and 11d are formed. A pair of transformers of a transformer of the iron core 12c2 and a transformer of the iron core 12d1 is formed, and two transformers of the iron core 12d2 and the transformer of the iron core 12a2 are formed with respect to the two wires 11d and 11a. A set of transformers is formed.

  Then, the secondary windings of the two transformers are connected in series so that the current generated in the secondary windings of the two transformers of each of the four sets is added. A side circuit is formed. That is, two transformers (iron core 12a1) are added so that the current generated in the secondary winding is added to the set of two transformers of the transformer of iron core 12a1 and the transformer of iron core 12b1. 12b1) are connected in series to form a secondary circuit. Similarly, the two transformers are set so that the current generated in the secondary winding is added to the set of two transformers of the transformer of the iron core 12b2 and the transformer of the iron core 12c1. (Secondary side windings of the iron cores 12b2 and 12c1) are connected in series to form a secondary circuit, and two sets of transformers of the transformer of the iron core 12c2 and the transformer of the iron core 12d1 are The secondary windings of the two transformers (iron cores 12c2, 12d1) are connected in series so that the current generated in the secondary winding is added to form a secondary circuit. Two transformers (iron cores 12d2, 12a2) are added so that the current generated in the secondary winding is added to the pair of transformers of the transformer and the transformer of the iron core 12a2. The secondary winding is formed by connecting the secondary windings in series.

  8B, another example of the second embodiment is 2 in the order of the ring from the four wires 11a to 11d with respect to the example of the second embodiment shown in FIG. Instead of selecting the wire of the strip and forming four sets of transformers of two each, the secondary side windings of the two transformers are connected in series to form a secondary side circuit. The three wires are selected from the wires 11a to 11d in the order of the ring, and four sets of three transformers are formed, and the secondary windings of the three transformers are connected in series. A secondary circuit is formed.

  In FIG. 8B, first, three wires are selected from the four wires 11a to 11d in the order of the ring. The three wires 11a, 11b, 11c, the three wires 11b, 11c, 11d, the three wires 11c, 11d, 11a, and the three wires 11d, 11a, 11b are selected. Next, four sets of three transformers are formed. That is, for the three wires 11a, 11b, and 11c, a set of three transformers of a transformer of the iron core 12a1, a transformer of the iron core 12b1, and a transformer of the iron core 12c1 is formed. Similarly, for the three wires 11b, 11c, and 11d, a set of three transformers including a transformer of the iron core 12b2, a transformer of the iron core 12c1, and a transformer of the iron core 12d2 is formed. For the electric wires 11c, 11d, and 11a, a set of two transformers, that is, a transformer of the iron core 12c2, a transformer of the iron core 12d1, and a transformer of the iron core 12a2, is formed, and three wires 11d, 11a, and 11b are formed. On the other hand, a set of three transformers of a transformer of the iron core 12d3, a transformer of the iron core 12a3, and a transformer of the iron core 12b3 is formed.

  Then, the secondary windings of the three transformers are connected in series so that the current generated in the secondary windings of the three transformers of each of the four sets is added. A side circuit is formed. That is, in order to add the current generated in the secondary winding to the set of the transformer of the iron core 12c1 and the transformer of the iron core 12b1, the transformer of the iron core 12b1, and the three transformers, Secondary windings of the transformers (iron cores 12a1, 12b1, 12c1) are connected in series to form a secondary circuit.

  Hereinafter, similarly, the current generated in the secondary winding is added to the set of three transformers of the transformer of the iron core 12b2, the transformer of the iron core 12c1, and the transformer of the iron core 12d1. Secondary windings of three transformers (iron cores 12b2, 12c2, 12d1) are connected in series to form a secondary circuit, and the transformer of the iron core 12c3, the transformer of the iron core 12d2, and the iron core 12a2 are transformed. Windings on the secondary side of the three transformers (cores 12c3, 12d2, 12a2) so that the current generated in the secondary winding is added to the set of three transformers with the transformer Are connected in series to form a secondary circuit, which is generated in the secondary winding for a set of three transformers of the transformer of the iron core 12d3, the transformer of the iron core 12a3, and the transformer of the iron core 12b3. Three transformers (iron cores 12d3, 12a3, 12b3 The secondary windings are connected in series to form a secondary circuit.

  In the above description, the case where one phase is applied to four wires 11a to 11d has been described, but it is also possible to apply to n (n = 3, 4,...) Wires 11a to 11n. In that case, i × n (i = 2, 3, 4,...) Transformers corresponding to n (n = 3, 4, 5,...) Wires are prepared, and each of the n wires is provided. Each of the i transformers penetrates through the through-holes of the iron cores, selects the i-shaped wires from the n-shaped wires in the order of the ring, and forms n sets of i transformers. A secondary circuit is formed by connecting the secondary windings of i transformers in series so that the current generated in the secondary windings of the i transformers is added.

  Also, at least two wires are selected in the order of the ring from the n wires, and at least two transformers are formed in n sets, and the secondary windings of at least two transformers are connected in series. It is also possible to connect to form a secondary circuit.

  According to the second embodiment, since the secondary side circuit is formed by connecting the secondary side windings in series for each of the two wire units, the number of transformers increases, but each of the wires 11a to 11d It can be expected to balance the current more stably.

  FIG. 9 is a configuration diagram of a wire impedance matching device according to the third embodiment of the present invention. The third embodiment is provided with current adjusting means 14 for adjusting the current flowing in the secondary circuit of the transformer (iron cores 12a, 12b), compared to the first embodiment shown in FIG. 1 (b). Is. The same elements as those in FIG. 1B are denoted by the same reference numerals, and redundant description is omitted.

  As described above, in the first embodiment shown in FIG. 1B, the electric wires 11a and 11b penetrating through the through holes of the iron cores 12a and 12b are used as the primary side, and the winding formed on the iron cores 12a and 12b is used as the secondary. Two transformers are formed, and the secondary windings of the iron cores 12a and 12b are connected in series to form a closed-loop secondary circuit.

  Here, the transformer has a constant current range and a constant voltage range as operation characteristics. The constant current range is a range that outputs a constant current as a secondary current and operates as a constant current source, while the constant voltage range is a range that outputs a constant voltage as a secondary voltage and operates as a constant voltage source. is there. Using a constant current range results in a current transformer, and using a constant voltage range results in a transformer.

  In the third embodiment of the present invention, the iron cores 12a and 12b are used in an intermediate region between the constant current range and the constant voltage range. When the transformer is in the constant current range (current transformer), it operates as a constant current source, so the current I2 (Ia2, Ib2) of the secondary circuit is determined by the primary currents Ia1, Ib1, and the secondary voltage Changes depending on the circuit state of the secondary circuit. On the other hand, when the transformer is in the constant voltage range (transformer), it operates as a constant voltage source, so the voltage of the secondary circuit is determined by the primary voltage, and the secondary current is the circuit state of the secondary circuit Will change.

  In the third embodiment of the present invention, the iron cores 12a and 12b are used in an intermediate region between the constant current range and the constant voltage range, and therefore have both the characteristics of a current transformer and a transformer. That is, due to the characteristics of the current transformer, a current I2 (Ia2, Ib2) flows in the secondary side circuit in a direction to cancel the magnetic flux due to the currents Ia1, Ib1 flowing through the wires 11a, 11b passing through the iron cores 12a, 12b. In this case, as described above, the currents Ia2 and Ib2 are balanced. On the other hand, the current I2 (Ia2, Ib2) flowing in the secondary circuit can be changed by changing the circuit state of the secondary circuit from the characteristics of the transformer.

  Therefore, in the third embodiment of the present invention, the current adjusting means 14 for adjusting the current I2 (Ia2, Ib2) flowing in the secondary side circuit of the iron cores 12a, 12b is provided, and the current I2 ( Ia2, Ib2) can be adjusted. For example, a variable resistor is used as the current adjusting unit 14. By changing the resistance value of the variable resistor which is the current adjusting means 14, the current I2 (Ia2, Ib2) flowing through the secondary circuit is adjusted, and the current Ia1, flowing through the two wires 11a, 11b on the primary side, Adjust Ib1.

As a result, the currents Ia and Ib flowing through the two wires 11a and 11b on the primary side can be simulated as unbalanced, light load to rating to overload.
(A) To set the unbalanced state, the resistance value of the current adjusting means (variable resistor) 14 is set to the ∞ state (opened).
(B) To set the light load state, the resistance value of the current adjusting means (variable resistor) 14 is increased.
(C) To achieve the rated state, the resistance value of the current adjusting means (variable resistor) 14 is kept at a predetermined value and is not changed.
(D) In order to enter an overload state, the resistance value of the current adjusting means (variable resistor) 14 is reduced.

  According to the third embodiment, the current I2 (Ia2, Ib2) flowing through the secondary circuit is adjusted by changing the resistance value of the variable resistor that is the current adjusting unit 14, and the two wires on the primary side are adjusted. Since the currents Ia1 and Ib1 flowing through 11a and 11b are adjusted, the currents Ia1 and Ib1 flowing through the two wires 12a and 12b on the primary side can be simulated as unbalanced, light load to rating to overload.

  In the above description, the case where one phase is applied to two wires 11a and 11b has been described, but it is also possible to apply to n (n = 2, 3, 4,...) Wires 11a to 11n. . In that case, n transformers are prepared corresponding to the n (n = 2, 3, 4,...) Strips of the electric wires 11a to 11n, and the n strips of the electric wires 11a to 11n are arranged one by one. It penetrates through the through holes of the iron cores 12a to 12n. Then, the secondary windings of the n transformers are connected in series so that the currents Ia2 to In2 generated in the secondary windings of the n transformers are added to form a secondary circuit. To do.

  FIG. 10 is a circuit diagram of another example of the wire impedance matching device according to the third embodiment of the present invention, in which one phase of the first embodiment shown in FIG. 9 is replaced with two wires 11a and 11b. The electric wire impedance matching device according to the third embodiment is applied to the electric wires 11a to 11d whose one phase is four.

  In FIG. 10, when applying to the four wires 11a to 11d, four transformers (four iron cores 12a to 12d) are prepared corresponding to the four wires 11a to 11d, and the four wires 11a. ˜11d is passed through the through holes of the four transformer cores 12a to 12d one by one. Then, the secondary windings of the four transformers (four iron cores 12a to 12d) are added so that the currents Ia2 to Id2 generated in the secondary windings of the four transformers are added. Terminals K and L are sequentially connected in series to form a secondary circuit. And the current adjustment means 14 is provided in a secondary side circuit. In this case, the same effect as that of the third embodiment can be obtained.

  In the above description, the current I2 (Ia2, Ib2) flowing through the secondary circuit is adjusted by the current adjusting means (variable resistor) 14, and the current Ia1, flowing through the two wires 11a, 11b on the primary side, Ib1 is adjusted, but by changing the number of turns of the secondary winding 13 of the transformer core 12 to change the current transformation ratio of the transformer, the two wires 11a on the primary side are changed. , 11b, currents Ia1 and Ib1 can be adjusted.

  When the current capacities of the n-shaped wires 11a to 11n are the same and the current transformation ratios of the iron cores 12a to 12n of the transformer are the same, the current I2 that flows through the secondary circuit flows to the wires 11a to 11n. Unbalance of the currents Ia to In can be suppressed. On the other hand, when the current capacities of the n-shaped electric wires 11a to 11n are different and the current transformation ratios of the iron cores 12a to 12n of the transformer are the same, the electric current I2 flowing in the secondary side circuit flows to the electric wires 11a to 11n. Since the unbalance of the currents Ia to In is suppressed, it acts so that the current flows evenly to the n-shaped electric wires 11a to 11n having different current capacities. In this case, a current exceeding the current capacity may flow through the electric wire having a small current capacity.

  Therefore, depending on the current capacity of the wires 11a to 11n, the number of turns of the windings 13 of the transformer cores 12a to 12n is varied to vary the current transformation ratio of the transformer, so that the current capacity of the wire 11 having a small current capacity is reduced. Make sure that the current does not exceed. Thereby, the electric wires 11a-11n from which current capacity differs can be used, and it can prevent the electric current exceeding current capacity from flowing into the electric wire with small current capacity.

  Next, FIG. 11 is a configuration diagram of a wire impedance matching system according to the fourth embodiment of the present invention, and FIG. 11A is a configuration illustrating an example of a wire impedance matching system according to the fourth embodiment of the present invention. FIG. 11 and FIG. 11B are configuration diagrams showing another example of the wire impedance matching system according to the fourth embodiment of the present invention. In the fourth embodiment, the wire impedance matching device of the first embodiment is provided in multiple stages.

  FIG. 11A shows a multi-stage arrangement of the wire impedance matching device of the first embodiment shown in FIG. 1B, and FIG. 11B shows the first embodiment shown in FIG. A wire impedance matching device is provided in multiple stages. By providing the wire impedance matching device of the first embodiment in multiple stages, in addition to the effects of the first embodiment, it is possible to suppress the unbalance of the current flowing through the primary-side wire 11 more stably.

  In the fourth embodiment, the case where the wire impedance matching device is applied to the wire 11 having two or four one-phase wires 11 has been described, but n (n = 2, 3, 4,... It can also be applied to the wire 11 of the strip.

  FIG. 12 is a configuration diagram of a wire impedance matching system according to the fifth embodiment of the present invention. In the fifth embodiment, the wire impedance matching device of the second embodiment shown in FIG. 8 is provided in multiple stages. By providing in multiple stages, in addition to the effects of the second embodiment, the unbalance of the currents Ia to In flowing through the electric wires 11a to 11d can be further suppressed.

  In the fifth embodiment, the case where the wire impedance matching device is applied to the wires 11a to 11d in which the one-phase wires 11 are four lines has been described, but n (n, 3, 4, 5,...) The present invention can also be applied to the strip electric wire 11.

  FIG. 13: is a block diagram of the wire impedance matching system which concerns on 6th Embodiment of this invention, FIG.13 (a) is a block diagram which shows an example of the wire impedance matching system which concerns on 6th Embodiment of this invention, figure FIG. 13B is a configuration diagram illustrating another example of the wire impedance matching system according to the sixth embodiment of the present invention. In the sixth embodiment, the wire impedance matching device of the third embodiment is provided in multiple stages.

  FIG. 13A shows a multistage arrangement of the wire impedance matching device of the third embodiment shown in FIG. 9, and FIG. 13B shows the wire impedance matching of the third embodiment shown in FIG. The apparatus is provided in multiple stages. By providing the wire impedance matching device of the third embodiment in multiple stages, in addition to the effects of the third embodiment, it is possible to suppress the unbalance of the current flowing through the primary-side wire 11 more stably.

  In the sixth embodiment, the case where the wire impedance matching device is applied to the wire 11 in which the one-phase wire 11 is 2 or 4 has been described, but n (n = 3, 4, 5,... It can also be applied to the wire 11 of the strip.

  As mentioned above, although some embodiment of this invention was described, these embodiment is shown as an example and is not intending limiting the range of invention. These novel embodiments can be implemented in various other forms, and various omissions, replacements, and changes can be made without departing from the scope of the invention. These embodiments and modifications thereof are included in the scope and gist of the invention, and are included in the invention described in the claims and the equivalents thereof.

DESCRIPTION OF SYMBOLS 11 ... Electric wire, 12 ... Iron core, 13 ... Winding, 14 ... Current adjustment means

Claims (5)

A closed iron core that has a through hole in the center and forms a magnetic circuit by the electric current of the electric wire passing through the through hole, and a winding formed on the iron core, and the electric wire that penetrates the through hole is connected to the primary side And forming a transformer with the winding as the secondary side,
Prepare at least 2n transformers corresponding to n (n = 3, 4, 5,...) wires,
through each of the n-wires through at least two transformer iron core through-holes;
Select at least two wires in the order of the ring from the n wires, and form at least two transformers n sets,
Sum of currents generated in the secondary windings of the at least two transformers so as to cancel the magnetic flux generated in the primary core of at least two transformers in each of the n sets. A secondary circuit is formed by connecting the secondary windings of each of the at least two transformers in series so that the current flows through the secondary winding of the at least two transformers. Wire impedance matching device characterized by the above.   The wire impedance matching device according to claim 1, wherein a current adjusting means for adjusting a current flowing through the secondary side circuit is connected to the secondary side circuit. The transformer is a transformer operating characteristics of the intermediate region between the constant current range and a constant voltage range, said current adjusting means, and through the core is to adjust the current flowing in the secondary circuit the primary side The electric wire impedance matching device according to claim 2, wherein a current flowing through the electric wire is adjusted.   4. The wire impedance matching device according to claim 1, wherein the number of turns of the secondary winding of the iron core of the transformer is varied to vary the current ratio of the transformer.   An electric wire impedance matching system according to any one of claims 1 to 4, wherein the electric wire impedance matching device is provided in multiple stages with respect to the n-shaped electric wires.

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