JP6183624B2 - Electronic components - Google Patents

Description

  The present invention relates to an electronic component including a dielectric line that propagates an electromagnetic wave having a frequency within a range of 1 GHz to 10 GHz.

  In recent years, a microwave band, particularly a frequency band of 1 GHz to 10 GHz, is often used for short-range wireless communication and mobile communication. Communication devices used for these communications are strongly required to be small and thin, and electronic components used in the communication devices are also strongly required to be small and thin.

  In general, a transmission line having a structure in which a conductor and a dielectric are combined is used for transmission of a high-frequency signal in a frequency band of 1 GHz to 10 GHz, such as a coaxial line, a strip line, a microstrip line, and a coplanar line.

  Some electronic components used in communication devices include a resonator such as a band-pass filter. These resonators include those using distributed constant lines, those using inductors and capacitors, and all include transmission lines. The resonator is required to have a large unloaded Q value. The unloaded Q value of the resonator can be increased by reducing the loss in the resonator.

  Transmission line losses include dielectric loss, conductor loss and radiation loss. As the frequency of the signal increases, the skin effect becomes more prominent and the conductor loss increases significantly. The loss in the resonator is mostly due to the conductor loss. Therefore, in order to increase the unloaded Q value of the resonator, it is effective to reduce the conductor loss. As techniques for reducing the conductor loss and increasing the unloaded Q value of the resonator, techniques described in Patent Documents 1 and 2 are known.

  In Patent Document 1, in a symmetric stripline resonator, a plurality of strip conductors that are separated from each other by a dielectric material are disposed between a pair of ground conductors in parallel to the ground conductor, thereby providing a conductor of the strip conductor. A technique for reducing the loss and increasing the unloaded Q value of the resonator is described.

  In Patent Document 2, in a resonator having a stripline electrode, the stripline electrode is a multilayer electrode having a multilayer portion and a conductor in which dielectric layers and conductor layers are alternately laminated, and each layer constituting the multilayer portion is provided. A technique is described in which the conductor loss of the stripline electrode is reduced and the unloaded Q value of the resonator is increased by arranging the surface so as to be perpendicular to the surface of the ground electrode.

  On the other hand, a dielectric line is known as a transmission line for propagating a millimeter wave band electromagnetic wave of about 50 GHz. For example, in Patent Document 3, a high dielectric constant tape is arranged between two parallel conductor plates arranged in parallel, and a filled dielectric made of a low dielectric constant material between the two parallel conductor plates and the high dielectric constant tape. A transmission line configured by arranging is described. In this transmission line, the electric field of electromagnetic waves is distributed in the filling dielectric. Patent Document 3 describes that an actually manufactured transmission line has low dispersion characteristics in a frequency band of 30 GHz to 60 GHz.

  Patent Document 4 describes a magnetic dielectric material having excellent magnetic characteristics even in the GHz frequency band.

JP-A-4-43703 JP-A-10-13112 JP 2007-235630 A JP 2013-45859 A

  As described above, a conventional transmission line for a frequency band of 1 GHz to 10 GHz has a structure in which a conductor and a dielectric are combined. In this transmission line, it is difficult to significantly reduce the conductor loss even if measures such as increasing the surface area of the conductor are taken as in the techniques described in Patent Documents 1 and 2. Therefore, in the resonator using this transmission line, there is a limit to increasing the no-load Q value.

  On the other hand, as described above, a dielectric line that propagates an electromagnetic wave in the millimeter wave band of about 50 GHz is known, but a dielectric line that propagates an electromagnetic wave in a frequency band of 1 GHz to 10 GHz is not known.

  The wavelength of the electromagnetic wave is inversely proportional to the frequency. The wavelength of the electromagnetic wave in the frequency band of 1 GHz to 10 GHz is about 5 to 50 times the wavelength of the electromagnetic wave in the millimeter wave band of about 50 GHz. In general, the size of a conventional dielectric line increases as the wavelength of an electromagnetic wave propagated increases. Therefore, even if an attempt is made to configure an electronic component such as a resonator for a frequency band of 1 GHz to 10 GHz using a conventional dielectric line, the electronic component is enlarged and a practical electronic component can be realized. Can not.

  Note that the wavelength of the electromagnetic wave propagating through the dielectric line becomes shorter than the wavelength of the electromagnetic wave propagating through the vacuum due to the wavelength shortening effect of the dielectric. However, the conventional dielectric line cannot provide a significant wavelength shortening effect. For example, Patent Document 3 describes that the relative dielectric constant of the filling dielectric is, for example, 4 or less. When the relative dielectric constant is 4, the wavelength shortening rate is 0.5. Therefore, even if a conventional dielectric line is used, the electronic component cannot be significantly downsized due to the wavelength shortening effect of the dielectric.

  The present invention has been made in view of such problems, and an object thereof is an electron including a resonator configured using a dielectric line that propagates an electromagnetic wave having one or more frequencies within a range of 1 GHz to 10 GHz. To provide parts.

  The electronic component of the present invention includes a resonator having an inductor and a capacitor connected in parallel and having a resonance frequency within a range of 1 GHz to 10 GHz. The electronic component of the present invention includes a dielectric line. The dielectric line includes a line part made of a first dielectric having a first relative dielectric constant and a surrounding dielectric part made of a second dielectric having a second relative dielectric constant. The line portion propagates electromagnetic waves having one or more frequencies within a range of 1 GHz to 10 GHz. The surrounding dielectric part exists around the line part in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line part. The first relative dielectric constant is 1000 or more. The second relative dielectric constant is smaller than the first relative dielectric constant. The inductor is constituted by a line portion of a dielectric line. In the present application, the relative permittivity refers to the real part of the complex relative permittivity. In addition, the line portion in the present invention is not limited to one that propagates electromagnetic waves in one direction, but may be one that propagates two electromagnetic waves that travel in opposite directions, such as traveling waves and reflected waves.

  In the electronic component of the present invention, the first relative dielectric constant may be 500,000 or less. Further, the second relative dielectric constant may be 1/10 or less of the first relative dielectric constant.

  In the electronic component of the present invention, at least a part of the surrounding dielectric part may have a relative magnetic permeability of 1.02 or more. In this case, the relative permeability of at least a part of the surrounding dielectric portion may be 30 or less. In the present application, the relative permeability refers to the real part of the complex relative permeability.

  The electronic component of the present invention may further include a first conductor layer and a second conductor layer facing the first conductor layer at a predetermined interval. In this case, a part of the surrounding dielectric portion is interposed between the first conductor layer and the second conductor layer, and one end of the line portion in the propagation direction of the electromagnetic wave in the line portion is connected to the second conductor layer. It may be connected. The capacitor may be constituted by the first and second conductor layers and a part of the surrounding dielectric portion therebetween.

  In the electronic component of the present invention, the first dielectric constant of the first dielectric constituting the line portion is 1000 or more, and the second dielectric constant of the second dielectric constituting the surrounding dielectric portion is It is smaller than the first relative dielectric constant. As a result, the line section can propagate electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz. Therefore, according to the present invention, it is possible to realize an electronic component including a resonator configured using a dielectric line that propagates electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz. There is an effect.

It is a perspective view which shows the dielectric material line and electronic component which concern on the 1st Embodiment of this invention. It is a side view which shows the electronic component seen from the A direction in FIG. It is sectional drawing which shows the cross section of the dielectric material line shown in FIG. It is a circuit diagram which shows the circuit structure of the electronic component shown in FIG. It is a perspective view which shows the dielectric material line and electronic component which concern on the 2nd Embodiment of this invention. It is a side view which shows the electronic component seen from the A direction in FIG. FIG. 6 is a cross-sectional view showing a cross section of the dielectric line shown in FIG. 5. It is a perspective view which shows the dielectric material line and electronic component which concern on the 3rd Embodiment of this invention. It is a top view of the electronic component shown in FIG. It is sectional drawing which shows the cross section of the dielectric material line shown in FIG. It is a perspective view which shows the dielectric material line and electronic component which concern on the 4th Embodiment of this invention. It is a top view of the electronic component shown in FIG. It is sectional drawing which shows the cross section of the dielectric material line shown in FIG. It is a perspective view of the 1st electronic component designed by the 1st simulation. It is a top view of the 1st electronic component shown in FIG. It is a perspective view of the 2nd electronic component designed by the 1st simulation. It is a top view of the 2nd electronic component shown in FIG. FIG. 15 is a characteristic diagram illustrating reflection attenuation characteristics of the first electronic component illustrated in FIG. 14. FIG. 17 is a characteristic diagram illustrating a reflection attenuation characteristic of the second electronic component illustrated in FIG. 16. It is a characteristic view which shows the result of a 2nd simulation. It is a characteristic view which shows the result of a 3rd simulation. It is explanatory drawing which shows the result of a 4th simulation. It is a top view of the electronic component which concerns on the 5th Embodiment of this invention. It is a perspective view of the electronic component shown in FIG. FIG. 24 is a circuit diagram showing a circuit configuration of the electronic component shown in FIG. 23. It is a characteristic view which shows the frequency characteristic of the electronic component shown in FIG. It is a perspective view of the electronic component which concerns on the 6th Embodiment of this invention. It is a perspective view which shows the inside of the electronic component shown in FIG. It is a perspective view which shows the capacitor part of the electronic component shown in FIG. It is a perspective view which shows the inside of one resonator part of the electronic component shown in FIG. It is a perspective view which shows the resonator part shown in FIG. 30, and two division shield layers. It is a front view of the resonator part shown in FIG. It is a side view of the resonator part shown in FIG. It is a circuit diagram which shows the circuit structure of the electronic component shown in FIG. It is a characteristic view which shows an example of the passage attenuation characteristic of the electronic component shown in FIG. It is a characteristic view which shows the characteristic of the resonator part shown in FIG.

[First Embodiment]
Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings. First, with reference to FIG. 1 to FIG. 3, the structure of the dielectric line and the electronic component according to the first embodiment of the present invention will be described. FIG. 1 is a perspective view showing a dielectric line and an electronic component according to the present embodiment. FIG. 2 is a side view showing the electronic component viewed from the direction A in FIG. FIG. 3 is a sectional view showing a section of the dielectric line shown in FIG.

  As shown in FIGS. 1 to 3, the electronic component 1 according to the present embodiment includes a dielectric line 2 according to the present embodiment. The dielectric line 2 includes a line part 10 made of a first dielectric having a first relative dielectric constant E1 and a surrounding dielectric part 20 made of a second dielectric having a second relative dielectric constant E2. I have. The line unit 10 propagates an electromagnetic wave having one or more frequencies within a range of 1 GHz to 10 GHz. The surrounding dielectric part 20 exists around the line part 10 in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line part 10. In the present embodiment, particularly, in the cross section, the surrounding dielectric portion 20 is in contact with the entire outer periphery of the line portion 10. The first relative dielectric constant E1 is 1000 or more. The second relative dielectric constant E2 is smaller than the first relative dielectric constant E1.

  In the present embodiment, the line portion 10 has a cylindrical shape. The propagation direction of the electromagnetic wave in the line part 10 is the central axis direction of the cylinder. The surrounding dielectric part 20 has a rectangular parallelepiped shape. In the cross section orthogonal to the propagation direction of the electromagnetic wave in the line portion 10, the shape of the line portion 10 is circular, and the shape of the surrounding dielectric portion 20 is rectangular. Here, as shown in FIG. 1, the direction parallel to the long side of the rectangle which is the shape of the surrounding dielectric portion 20 in the cross section is defined as the X direction, and the direction parallel to the short side of the rectangle is the Y direction. It is defined as Further, the propagation direction of the electromagnetic wave in the line portion 10, that is, the central axis direction of the cylinder which is the shape of the line portion 10 is defined as the Z direction. The X direction, the Y direction, and the Z direction are orthogonal to each other. FIG. 3 shows a cross section orthogonal to the propagation direction of the electromagnetic wave in the line portion 10, that is, the Z direction.

  The surrounding dielectric portion 20 includes an upper surface 20a and a lower surface 20b positioned at both ends in the Z direction, two side surfaces 20c and 20d positioned at both ends in the X direction, and two side surfaces 20e and 20f positioned at both ends in the Y direction. have.

  At least a part of the surrounding dielectric portion 20 may be made of a magnetic dielectric material, that is, a magnetic dielectric material. In other words, at least a part of the surrounding dielectric part 20 may have a relative magnetic permeability greater than 1. In this case, it is preferable that the relative magnetic permeability of at least a part (magnetic dielectric) of the surrounding dielectric part 20 is 1.02 or more. The magnetic dielectric constituting at least part of the surrounding dielectric part 20 is at least part of the second dielectric. Therefore, the magnetic dielectric has the second relative dielectric constant E2.

  In the present embodiment, in particular, the entire surrounding dielectric portion 20 is constituted by one type of second dielectric. Accordingly, the entire surrounding dielectric portion 20 has the same relative permittivity and the same relative permeability. The one type of second dielectric may be a dielectric having no magnetism, that is, a dielectric having a relative permeability of 1, or a magnetic dielectric.

  The electronic component 1 further includes conductor layers 3, 4, 5, and 6 disposed on the upper surface 20a, the lower surface 20b, and the side surfaces 20e and 20f of the surrounding dielectric part 20, respectively. The length of the conductor layer 3 in the X direction is smaller than the length of the upper surface 20a in the X direction. The length of the conductor layer 3 in the Y direction is equal to the length of the upper surface 20a in the Y direction. The conductor layer 3 covers only a part of the upper surface 20a. The length of the conductor layer 4 in the X direction is smaller than the length of the lower surface 20b in the X direction. The length of the conductor layer 4 in the Y direction is equal to the length of the lower surface 20b in the Y direction. The conductor layer 4 covers only a part of the lower surface 20b. The conductor layer 5 covers the entire side surface 20 e and is electrically connected to the conductor layers 3 and 4. The conductor layer 6 covers the entire side surface 20f and is electrically connected to the conductor layers 3 and 4. The conductor layers 3, 4, 5, 6 are connected to the ground.

  The electronic component 1 further includes a conductor layer 7 disposed inside the peripheral dielectric portion 20 so as to face the conductor layer 4 with a predetermined interval. A part of the surrounding dielectric portion 20 is interposed between the conductor layer 4 and the conductor layer 7.

  One end of the line portion 10 in the Z direction is connected to the conductor layer 7. The conductor layer 7 has an end portion 7 a exposed at the side surface 20 c of the surrounding dielectric portion 20. The other end of the line portion 10 in the Z direction is connected to the conductor layer 3.

  The conductor layers 3, 4, 5, 6, and 7 are made of a metal such as Ag or Cu. The electronic component 1 may include a dielectric layer made of a dielectric having the first relative dielectric constant E1 instead of the conductor layer 3.

  Next, the circuit configuration of the electronic component 1 according to the present embodiment will be described with reference to the circuit diagram of FIG. The electronic component 1 according to the present embodiment includes a resonator 30 having an inductor 31 and a capacitor 32 connected in parallel, and an input / output terminal 33. One end of the inductor 31 and one end of the capacitor 32 are electrically connected to the input / output terminal 33. The other end of the inductor 31 and the other end of the capacitor 32 are electrically connected to the ground. The inductor 31 and the capacitor 32 constitute a parallel resonance circuit. The resonator 30 has a resonance frequency within a range of 1 GHz to 10 GHz.

  The resonator 30 is configured using the dielectric line 2. More specifically, the inductor 31 constituting the resonator 30 is constituted by the line portion 10 of the dielectric line 2. The capacitor 32 is configured by the conductor layers 4 and 7 shown in FIG. 1 and a part of the surrounding dielectric portion 20 therebetween. The input / output terminal 33 is constituted by the end 7a of the conductor layer 7 shown in FIG. Note that a conductor layer connected to the end portion 7 a of the conductor layer 7 may be provided on the side surface 20 c of the surrounding dielectric portion 20, and this conductor layer may be used as the input / output terminal 33.

  Next, the operation of the dielectric line 2 and the electronic component 1 according to the present embodiment will be described. The input / output terminal 33 constituted by the end 7a of the conductor layer 7 is supplied with electric power having an arbitrary frequency including a frequency within a range of 1 GHz to 10 GHz. Due to this electric power, electromagnetic waves are excited in the line portion 10 connected to the conductor layer 7. The line unit 10 propagates an electromagnetic wave having one or more frequencies within a range of 1 GHz to 10 GHz. One or more frequencies of the electromagnetic wave propagated by the line unit 10 include the resonance frequency of the resonator 30. The resonator 30 resonates at a resonance frequency within a range of 1 GHz to 10 GHz. The potential of the input / output terminal 33 becomes maximum when the frequency of the power supplied to the input / output terminal 33 matches the resonance frequency, and decreases as the frequency of the power supplied to the input / output terminal 33 increases from the resonance frequency. To do.

  In the present embodiment, the first dielectric constant E1 of the first dielectric that constitutes the line portion 10 is 1000 or more, and the second dielectric constant of the second dielectric that constitutes the surrounding dielectric portion 20. The rate E2 is smaller than the first relative permittivity E1. The value of the first relative permittivity E1 of 1000 or more is very large compared to the relative permittivity of a dielectric used in a conventional dielectric line that propagates millimeter wave electromagnetic waves of about 50 GHz. By setting the value of the first relative dielectric constant E1 to such a large value, the line portion 10 can propagate electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz.

  As the first relative permittivity E1 increases, the electromagnetic wave easily propagates through the line portion 10, and the wavelength shortening effect of the line portion 10 increases and the resonance frequency of the resonator 30 tends to decrease. Therefore, theoretically, there is no upper limit to the first relative dielectric constant E1. However, when the first relative dielectric constant E1 is 500,000 or more, the above effect becomes almost constant. From this viewpoint, the first relative dielectric constant E1 is preferably 500,000 or less.

  The surrounding dielectric portion 20 made of the second dielectric having the second relative dielectric constant E2 smaller than the first relative dielectric constant E1 has a function of concentrating the electromagnetic wave on the line portion 10. The second relative dielectric constant E2 is preferably 1/10 or less of the first relative dielectric constant E1 so that this function is effectively exhibited.

  When the second dielectric is a magnetic dielectric, it is possible to increase the inductance of the dielectric line 2 as compared with the case where the second dielectric does not have magnetism. The resonant frequency of the vessel 30 can be lowered. In addition, as the relative permeability of the magnetic dielectric increases, the inductance of the dielectric line 2 can be increased, and thereby the resonance frequency of the resonator 30 can be further decreased. However, as the relative permeability of the magnetic dielectric increases, the loss of the magnetic material in the surrounding dielectric portion 20 increases. Therefore, it is preferable that the relative magnetic permeability of the magnetic dielectric constituting the surrounding dielectric part 20 is 30 or less.

  Examples of the dielectric material constituting the first dielectric include barium titanate or a metal oxide material containing barium titanate, such as barium strontium titanate or barium calcium titanate. According to these dielectric materials, it is possible to realize a first dielectric having a first relative dielectric constant E1 of 1000 or more.

  Examples of the dielectric material constituting the second dielectric when the second dielectric does not have magnetism include resins such as polytetrafluoroethylene, ceramics such as alumina, glass, and composites thereof Materials can be mentioned. According to these dielectric materials, a second dielectric having a second relative dielectric constant E2 that is 1/10 or less of the first relative dielectric constant E1 can be realized.

  In the case where the second dielectric is a magnetic dielectric, the dielectric material constituting the second dielectric is obtained by dispersing magnetic particles in a dielectric material having no magnetism as described above. Can be used. In this case, in order to reduce the magnetic loss of the magnetic particles in the frequency band of 1 GHz to 10 GHz, the particle diameter of the magnetic particles is set to the skin depth or less in the frequency band of 1 GHz to 10 GHz, specifically to 100 nm or less. It is preferable to make it small. Further, the magnetic permeability of the magnetic dielectric can be increased by making the magnetic particles into a flat shape and orientation-dispersing in the dielectric material. Further, as described in Patent Document 4, the relative permeability of the magnetic dielectric is increased by orienting and dispersing aggregates having anisotropic shapes in which magnetic particles are aggregated in the dielectric material. It is possible.

  As described above, according to the present embodiment, it is possible to realize the dielectric line 2 that propagates electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz. Further, according to the present embodiment, the electronic component 1 including the dielectric line 2 can be realized. The electronic component 1 has a portion that propagates an electromagnetic wave having one or more frequencies within a range of 1 GHz to 10 GHz. The electronic component 1 according to the present embodiment particularly includes a resonator 30 configured using the dielectric line 2. The resonator 30 has a resonance frequency in the range of 1 GHz to 10 GHz.

[Second Embodiment]
Next, a dielectric line and an electronic component according to the second embodiment of the present invention will be described with reference to FIGS. FIG. 5 is a perspective view showing a dielectric line and an electronic component according to the present embodiment. FIG. 6 is a side view showing the electronic component viewed from the direction A in FIG. FIG. 7 is a sectional view showing a section of the dielectric line shown in FIG.

  In the dielectric line 2 and the electronic component 1 according to the present embodiment, the configuration of the surrounding dielectric portion 20 is different from that of the first embodiment. In other words, in the present embodiment, the surrounding dielectric part 20 includes a magnetic dielectric part 21 made of a magnetic dielectric and a nonmagnetic dielectric part 22 made of a dielectric having no magnetism. Yes. The magnetic dielectric portion 21 exists around the line portion 10 in a cross section orthogonal to the propagation direction of electromagnetic waves in the line portion 10, that is, the Z direction. In the present embodiment, in particular, in the cross section, the magnetic dielectric portion 21 is in contact with the entire outer periphery of the line portion 10. The shape of the magnetic dielectric part 21 is, for example, a cylindrical shape. The nonmagnetic dielectric portion 22 exists around the magnetic dielectric portion 21 in the cross section.

  The magnetic dielectric portion 21 and the nonmagnetic dielectric portion 22 have the second relative permittivity E2 described in the first embodiment. The magnetic dielectric portion 21 has a relative magnetic permeability greater than 1. The relative magnetic permeability of the magnetic dielectric part 21 is preferably 1.02 or more. Since the surrounding dielectric part 20 includes the magnetic dielectric part 21, it is possible to increase the inductance of the dielectric line 2 as compared with the case where the entire surrounding dielectric part 20 does not have magnetism. Thus, the resonance frequency of the resonator 30 can be lowered. In addition, as the relative permeability of the magnetic dielectric portion 21 increases, the inductance of the dielectric line 2 can be further increased, and thereby the resonance frequency of the resonator 30 can be further decreased. However, as the relative permeability of the magnetic dielectric portion 21 increases, the loss of the magnetic material in the magnetic dielectric portion 21 increases. Therefore, the relative magnetic permeability of the magnetic dielectric part 21 is preferably 30 or less.

  Examples of the magnetic dielectric material constituting the magnetic dielectric portion 21 are as described in the first embodiment. An example of a dielectric material constituting the nonmagnetic dielectric portion 22 is the dielectric constituting the second dielectric when the second dielectric does not have magnetism, as described in the first embodiment. Same as material example.

  Other configurations of the dielectric line 2 and the electronic component 1 according to the present embodiment are the same as those of the first embodiment. The operation and effect of the dielectric line 2 and the electronic component 1 according to the present embodiment are the same as those in the first embodiment when the second dielectric constituting the surrounding dielectric portion 20 is a magnetic dielectric. It is the same.

[Third Embodiment]
Next, a dielectric line and an electronic component according to the third embodiment of the invention will be described with reference to FIGS. FIG. 8 is a perspective view showing a dielectric line and an electronic component according to the present embodiment. FIG. 9 is a plan view of the electronic component shown in FIG. 10 is a cross-sectional view showing a cross section of the dielectric line shown in FIG.

  As shown in FIGS. 8 to 10, the electronic component 51 according to the present embodiment includes a dielectric line 52 according to the present embodiment. The dielectric line 52 includes a line part 60 made of a first dielectric having a first relative dielectric constant E1, a surrounding dielectric part 70 made of a second dielectric having a second relative dielectric constant E2, and And a ground conductor 80. The line unit 60 propagates electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz. The surrounding dielectric part 70 exists around the line part 60 in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line part 60. In the present embodiment, in particular, in the cross section, the surrounding dielectric portion 70 is in contact with the entire outer periphery of the line portion 60. Similar to the first embodiment, the first relative permittivity E1 is 1000 or more. The second relative dielectric constant E2 is smaller than the first relative dielectric constant E1.

  The surrounding dielectric part 70 has a rectangular parallelepiped shape. Here, as shown in FIG. 8, the X direction, the Y direction, and the Z direction are defined. The X direction, the Y direction, and the Z direction are orthogonal to each other. The peripheral dielectric part 70 includes an upper surface 70a and a lower surface 70b positioned at both ends in the Z direction, two side surfaces 70c and 70d positioned at both ends in the X direction, and two side surfaces 70e and 70f positioned at both ends in the Y direction. have.

  In the present embodiment, the line portion 60 has a plate shape that is long in the X direction, and is embedded in the surrounding dielectric portion 70. The line portion 60 has an upper surface facing the upper surface 70 a of the surrounding dielectric portion 70 and a lower surface facing the lower surface 70 b of the surrounding dielectric portion 70. The propagation direction of the electromagnetic wave in the line portion 60 is the X direction. FIG. 10 shows a cross section orthogonal to the propagation direction of the electromagnetic wave in the line portion 60, that is, the X direction. In this cross section, the shape of the line portion 60 is a quadrangle, particularly a rectangle, and the shape of the surrounding dielectric portion 70 is also a rectangle.

  The ground conductor 80 is disposed on the lower surface 70 b of the surrounding dielectric part 70. The ground conductor 80 extends from a position away from the ridge line between the side surface 70c and the lower surface 70b to the position of the ridge line between the side surface 70d and the lower surface 70b.

  At least a part of the surrounding dielectric part 70 may be configured by the magnetic dielectric described in the first embodiment. In other words, at least a part of the surrounding dielectric part 70 may have a relative magnetic permeability greater than 1. In this case, it is preferable that the relative permeability of at least a part (magnetic dielectric) of the surrounding dielectric part 70 is 1.02 or more. Note that the magnetic dielectric constituting at least part of the surrounding dielectric part 70 is at least part of the second dielectric. Therefore, the magnetic dielectric has the second relative dielectric constant E2.

  In the present embodiment, in particular, the entire surrounding dielectric portion 70 is configured by one type of second dielectric. Accordingly, the entire surrounding dielectric portion 70 has the same relative permittivity and the same relative magnetic permeability. The one type of second dielectric may be a dielectric having no magnetism, that is, a dielectric having a relative permeability of 1, or a magnetic dielectric.

  The electronic component 51 further includes a conductor layer 53 disposed on the side surface 70 d of the surrounding dielectric part 70. The conductor layer 53 covers the entire side surface 70 d and is electrically connected to the ground conductor 80. The ground conductor 80 and the conductor layer 53 are connected to the ground. The ground conductor 80 and the conductor layer 53 are made of a metal such as Ag or Cu.

  The line portion 60 has an end portion 60 a that is located at one end in the X direction and is exposed on the side surface 70 c of the surrounding dielectric portion 70. The end portion of the line portion 60 opposite to the end portion 60 a is connected to the conductor layer 53.

  The structure of the dielectric line 52 according to the present embodiment is similar to the structure of the microstrip line. The dielectric line 52 according to the present embodiment is different from the microstrip line in that a line portion 60 made of a first dielectric is provided instead of the conductor line in the microstrip line.

  The electronic component 51 according to the present embodiment includes a resonator having a resonance frequency within a range of 1 GHz to 10 GHz. This resonator is configured using a dielectric line 52. More specifically, the dielectric line 52 according to the present embodiment functions as a distributed constant line like the microstrip line. The dielectric line 52 constitutes a tip short-circuited quarter-wave resonator. This tip short-circuited quarter wavelength resonator is equivalent to a parallel resonant circuit. Therefore, an equivalent circuit of the tip short-circuited quarter-wave resonator which is the resonator in the present embodiment is as shown in FIG. Hereinafter, the resonator according to the present embodiment is denoted by reference numeral 30 as in the first embodiment. In the present embodiment, the end portion 60a of the line portion 60 constitutes the open end of the short-circuited quarter-wave resonator and the input / output terminal 33 in FIG. A conductor layer connected to the end portion 60 a of the line portion 60 may be provided on the side surface 70 c of the surrounding dielectric portion 70, and this conductor layer may be used as the input / output terminal 33. Alternatively, a through hole in which the lower end is connected to a portion of the line portion 60 near the end portion 60a and the upper end is exposed on the upper surface 70a of the peripheral dielectric portion 70 is provided inside the surrounding dielectric portion 70. The upper end may be used as the input / output terminal 33. The end portion of the line portion 60 opposite to the end portion 60a is connected to the conductor layer 53 to constitute a short-circuited end of the tip short-circuited quarter-wave resonator.

  Preferred ranges of the first relative dielectric constant E1, the second relative dielectric constant E2, and the relative magnetic permeability of the magnetic dielectric, and the first dielectric, the second dielectric, and the magnetic dielectric in the present embodiment Examples of the respective materials are the same as those in the first embodiment.

  Next, the operation of the dielectric line 52 and the electronic component 51 according to the present embodiment will be described. The input / output terminal 33 constituted by the end portion 60a of the line portion 60 is supplied with electric power having an arbitrary frequency including a frequency within a range of 1 GHz to 10 GHz. Due to this electric power, electromagnetic waves are excited in the line portion 60. The line unit 60 propagates electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz. One or more frequencies of the electromagnetic wave propagated by the line unit 60 include the resonance frequency of the resonator 30. The resonator 30 resonates at a resonance frequency within a range of 1 GHz to 10 GHz. The potential of the input / output terminal 33 becomes maximum when the frequency of the power supplied to the input / output terminal 33 matches the resonance frequency, and decreases as the frequency of the power supplied to the input / output terminal 33 increases from the resonance frequency. To do.

  When the second dielectric is a magnetic dielectric, it is possible to increase the inductance of the dielectric line 52 as compared with the case where the second dielectric does not have magnetism. The resonant frequency of the vessel 30 can be lowered. Other operations and effects of the dielectric line 52 and the electronic component 51 according to the present embodiment are the same as those of the first embodiment.

[Fourth Embodiment]
Next, a dielectric line and an electronic component according to the fourth embodiment of the invention will be described with reference to FIGS. FIG. 11 is a perspective view showing a dielectric line and an electronic component according to the present embodiment. FIG. 12 is a plan view of the electronic component shown in FIG. FIG. 13 is a cross-sectional view showing a cross section of the dielectric line shown in FIG.

  In the dielectric line 52 and the electronic component 51 according to the present embodiment, the configuration of the surrounding dielectric portion 70 is different from that of the third embodiment. That is, in the present embodiment, the surrounding dielectric part 70 includes a magnetic dielectric part 71 made of a magnetic dielectric and a nonmagnetic dielectric part 72 made of a dielectric having no magnetism. Yes. The magnetic dielectric portion 71 exists around the line portion 60 in a cross section orthogonal to the propagation direction of electromagnetic waves in the line portion 60, that is, the X direction. In the present embodiment, in particular, in the cross section, the magnetic dielectric portion 71 is in contact with the entire outer periphery of the line portion 60. In the cross section, the shape of the outer edge of the magnetic dielectric portion 71 is, for example, a rectangle. The nonmagnetic dielectric part 72 exists around the magnetic dielectric part 71 in the cross section.

  The magnetic dielectric part 71 and the nonmagnetic dielectric part 72 have the second relative dielectric constant E2 described in the first embodiment. The magnetic dielectric portion 71 has a relative magnetic permeability greater than 1. The relative magnetic permeability of the magnetic dielectric part 71 is preferably 1.02 or more. The relative magnetic permeability of the magnetic dielectric part 71 is preferably 30 or less. Examples of the magnetic dielectric material constituting the magnetic dielectric portion 71 are as described in the first embodiment. An example of a dielectric material constituting the nonmagnetic dielectric portion 72 is the dielectric constituting the second dielectric when the second dielectric does not have magnetism, as described in the first embodiment. Same as material example.

  Other configurations of the dielectric line 52 and the electronic component 51 according to the present embodiment are the same as those of the third embodiment. The operation and effect of the dielectric line 52 and the electronic component 51 according to the present embodiment are the same as those of the third embodiment when the second dielectric constituting the surrounding dielectric portion 70 is a magnetic dielectric. It is the same.

  Hereinafter, the results of the first to fourth simulations performed on the dielectric line of the present invention will be described.

[First simulation]
First, the first simulation will be described. In the first simulation, the first and second electronic components each configured using the dielectric line of the present invention were designed. The first electronic component includes a first resonator having a resonance frequency of 1 GHz. The second electronic component includes a second resonator having a resonance frequency of 10 GHz.

  First, the first electronic component 101 will be described with reference to FIGS. 14 and 15. FIG. 14 is a perspective view of the first electronic component 101. FIG. 15 is a plan view of the first electronic component 101. The configuration of the first electronic component 101 is basically the same as that of the electronic component 1 according to the first embodiment shown in FIG. In FIG. 15, the conductor layer 3 is omitted.

  The dimensions of each part in the first electronic component 101 are as follows. As shown in FIG. 14, the length of the line portion 10 in the Z direction is 3 mm. The length in the X direction and the length in the Y direction of the surrounding dielectric part 20 are 4.5 mm and 3.2 mm, respectively. As shown in FIG. 15, the diameter of the line part 10 in the cross section orthogonal to the Z direction is 1 mm. The region where the conductor layer 4 and the conductor layer 7 overlap is rectangular when viewed from the Z direction. The length in the X direction and the length in the Y direction of this region are 0.85 mm and 2.2 mm, respectively. The distance between the conductor layer 4 and the conductor layer 7 is 0.03 mm. Since the thickness of the conductor layer 7 and the distance between the conductor layer 4 and the conductor layer 7 are sufficiently smaller than the length of the line portion 10 in the Z direction, the length of the surrounding dielectric portion 20 in the Z direction is about 3 mm. It is.

  In the first electronic component 101, the first dielectric constant E1 of the first dielectric constituting the line portion 10 is 1000. The dielectric loss tangent of the first dielectric is 0.001. The second dielectric constant E2 of the second dielectric constituting the surrounding dielectric part 20 is 10. The relative permeability of the second dielectric is 20. The capacitance of the capacitor 32 (see FIG. 4) formed by the conductor layers 4 and 7 and a part of the surrounding dielectric portion 20 therebetween is 5.792 pF. The first resonator includes an inductor 31 and a capacitor 32. The inductor 31 is configured by the line portion 10.

  Next, the second electronic component 102 will be described with reference to FIGS. 16 and 17. FIG. 16 is a perspective view of the second electronic component 102. FIG. 17 is a plan view of the second electronic component 102. The configuration of the second electronic component 102 is basically the same as that of the electronic component 1 according to the first embodiment shown in FIG. In FIG. 17, the conductor layer 3 is omitted.

  The dimensions of each part in the second electronic component 102 are as follows. As shown in FIG. 16, the length of the line portion 10 in the Z direction is 1.5 mm. The length in the X direction and the length in the Y direction of the surrounding dielectric part 20 are 4.5 mm and 3.2 mm, respectively. As shown in FIG. 17, the diameter of the line part 10 in the cross section orthogonal to the Z direction is 0.6 mm. The region where the conductor layer 4 and the conductor layer 7 overlap is rectangular when viewed from the Z direction. The length in the X direction and the length in the Y direction of this region are 0.25 mm and 1 mm, respectively. The distance between the conductor layer 4 and the conductor layer 7 is 0.03 mm. Since the thickness of the conductor layer 7 and the distance between the conductor layer 4 and the conductor layer 7 are sufficiently smaller than the length of the line portion 10 in the Z direction, the length of the surrounding dielectric portion 20 in the Z direction is about 1 .5 mm.

  In the second electronic component 102, the first dielectric constant E1 of the first dielectric constituting the line portion 10 is 1000. The dielectric loss tangent of the first dielectric is 0.001. The second dielectric constant E2 of the second dielectric constituting the surrounding dielectric part 20 is 10. The relative permeability of the second dielectric is 1. The capacitance of the capacitor 32 (see FIG. 4) formed by the conductor layers 4 and 7 and a part of the surrounding dielectric portion 20 therebetween is 0.851 pF. The second resonator includes an inductor 31 and a capacitor 32. The inductor 31 is configured by the line portion 10.

  FIG. 18 shows the reflection attenuation characteristics of the first electronic component 101. In FIG. 18, the horizontal axis represents frequency and the vertical axis represents return loss. As shown in FIG. 18, in the reflection attenuation characteristic of the first electronic component 101, the reflection attenuation amount has a maximum value at 1 GHz. From this, it can be seen that the first resonator of the first electronic component 101 has a resonance frequency of 1 GHz. This also indicates that the line portion 10 of the first electronic component 101 can propagate an electromagnetic wave having a frequency of at least 1 GHz.

  FIG. 19 shows the reflection attenuation characteristics of the second electronic component 102. In FIG. 19, the horizontal axis represents frequency, and the vertical axis represents return loss. As shown in FIG. 19, in the reflection attenuation characteristic of the second electronic component 102, the reflection attenuation amount has a maximum value at 10 GHz. From this, it can be seen that the second resonator of the second electronic component 102 has a resonance frequency of 10 GHz. This also indicates that the line portion 10 of the second electronic component 102 can propagate an electromagnetic wave having a frequency of at least 10 GHz.

  Further, from the result of the first simulation, by adjusting the size of each part in the electronic component, the first relative permittivity E1, the second relative permittivity E2, and the relative permeability of the second dielectric. It is possible to realize an electronic component including a line unit 10 that propagates an electromagnetic wave having one or more frequencies between 1 GHz and 10 GHz, and a resonator including the line unit 10 and having a resonance frequency between 1 GHz and 10 GHz. it is obvious.

  In the first electronic component 101 and the second electronic component 102, the first dielectric constant E1 of the first dielectric constituting the line portion 10 is 1000. As the first relative permittivity E1 increases, the electromagnetic wave easily propagates inside the line portion 10. Therefore, if the first relative permittivity E1 is 1000 or more, the line portion 10 that propagates electromagnetic waves having one or more frequencies within the range of 1 GHz to 10 GHz and the line portion 10 are included, and the range of 1 GHz to 10 GHz. It is clear that an electronic component having a resonator having a resonance frequency within can be realized.

[Second simulation]
Next, the second simulation will be described. In the second simulation, the relationship among the shape of the line portion 10 in the electronic component 1 according to the first embodiment, the first relative permittivity E1, the second relative permittivity E2, and the resonance frequency of the resonator 30 is expressed. Examined. In the second simulation, the models A to E of the five electronic components 1 having different second dielectric constant E2 and the shape of the line portion 10 were used. Table 1 below shows the second dielectric constant E2 in the models A to E, the diameter D of the line portion 10 and the length L in the Z direction of the line portion 10 in a cross section orthogonal to the Z direction. The relative permeability of the first dielectric and the second dielectric is both 1.

  In the second simulation, the relationship between the first dielectric constant E1 and the resonance frequency of the resonator 30 was examined for the models A to E. The capacitance of the capacitor 32 was 3 pF. The result of the second simulation is shown in FIG. In FIG. 20, the horizontal axis is the first relative dielectric constant E1 and the vertical axis is the resonance frequency of the resonator 30.

  From the result shown in FIG. 20, it can be seen that the resonance frequency decreases as the line portion 10 increases and the first dielectric constant E1 increases. However, when the first relative permittivity E1 is 500,000 or more, the resonance frequency becomes substantially constant regardless of the size of the line portion 10. Therefore, the first relative dielectric constant E1 is preferably 500,000 or less.

[Third simulation]
Next, the third simulation will be described. In the third simulation, regarding the electronic component 1 according to the second embodiment, the first relative permittivity E1, the relative permeability of the magnetic dielectric portion 21, the resonance frequency of the resonator 30, and the absence of the resonator 30 are shown. The relationship between the load Q value was examined. In the model of the electronic component 1 used in the third simulation, the diameter of the line portion 10 in the cross section orthogonal to the Z direction is 150 μm, the thickness of the magnetic dielectric portion 21 in the cross section orthogonal to the Z direction is 25 μm, and the Z direction The diameter of the outer periphery of the magnetic dielectric portion 21 in the cross section perpendicular to the line portion is 200 μm, the length of the line portion 10 in the Z direction is 460 μm, and the capacitance of the capacitor 32 is 3 pF. The second relative dielectric constant E2 was 75, and the dielectric loss tangent of the first dielectric and the magnetic dielectric portion 21 were both 0.001. The results of the third simulation are shown in Table 2 below. Here, the relative magnetic permeability of the magnetic dielectric portion 21 is represented by the symbol μ. Further, the case where the entire surrounding dielectric portion 20 does not have magnetism is represented as a case where the relative permeability μ of the magnetic dielectric portion 21 is 1.0 for convenience.

  In the third simulation, instead of the line portion 10 in the model of the electronic component 1 used in the third simulation, a conductor line portion made of Ag having the same shape as the line portion 10 is provided, and the relative permeability of the magnetic dielectric portion 21 is provided. The resonance frequency of the resonator and the unloaded Q value of the resonator were also obtained for the comparative model with a magnetic susceptibility of 1.0. In the model of the comparative example, the resonance frequency of the resonator was 4.52 GHz, and the unloaded Q value of the resonator was 130.9.

  In the model of the electronic component 1 used in the third simulation under the conditions of the first relative permittivity E1 and the relative permeability μ of the magnetic dielectric portion 21 shown in Table 2, the range of 1 GHz to 10 GHz is used. A resonance frequency and an unloaded Q value larger than the unloaded Q value in the model of the comparative example are obtained.

  FIG. 21 shows a part of the result of the third simulation, specifically, the relative permeability μ of the magnetic dielectric portion 21 and the resonator 30 when the first relative permittivity E1 is 5,000. The relationship with the resonance frequency is shown. In FIG. 21, the horizontal axis represents the relative permeability μ of the magnetic dielectric part 21, and the vertical axis represents the resonance frequency of the resonator 30. In FIG. 21, the relationship between the relative permeability μ of the magnetic dielectric portion 21 and the resonance frequency when the first relative permittivity E1 is 5,000 is represented by a plurality of triangular points and a curve connecting them. ing. In FIG. 21, the resonance frequency of the resonator in the model of the comparative example is indicated by a one-dot chain line.

  From Table 2 and FIG. 21, in the model of the electronic component 1 used in the third simulation, when the first relative permittivity E1 is 5,000, the relative permeability μ of the magnetic dielectric portion 21 is 1.02. If it is above, it turns out that the resonant frequency of 10 GHz or less is obtained. Further, it can be seen from Table 2 and FIG. 21 that the resonance frequency decreases as the relative permeability μ of the magnetic dielectric portion 21 increases. Therefore, as the relative permeability μ of the magnetic dielectric portion 21 increases, it becomes easier to realize the electronic component 1 including the resonator 30 having a resonance frequency within the range of 1 GHz to 10 GHz. However, the loss of the magnetic substance in the magnetic dielectric part 21 increases as the relative permeability μ of the magnetic dielectric part 21 increases. It is sufficient that the relative permeability μ of the magnetic dielectric portion 21 is about 30 at the maximum.

[Fourth simulation]
Next, the fourth simulation will be described. In the fourth simulation, the magnetic field strength in the vicinity of the line portion 10 in the dielectric line 2 according to the first and second embodiments was examined. 22A to 22E show models of five dielectric lines 2 under different conditions. The four models shown in (a) to (d) are models of the dielectric line 2 according to the first embodiment. In the four models shown in (a) to (d), the diameter of the line portion 10 in the cross section orthogonal to the Z direction is 150 μm, the second relative permittivity E2 is 7, and the permeability of the surrounding dielectric portion 20 is Was set to 1. In the four models shown in (a) to (d), the first relative permittivity E1 was set to 1,000, 2,000, 5,000, and 10,000, respectively. In all the four models shown in (a) to (d), the dielectric loss tangent of the first dielectric was set to 0.001.

  The model shown in (e) of FIG. 22 is a model of the dielectric line 2 according to the second embodiment. In the model shown in FIG. 22E, the diameter of the line portion 10 in the cross section orthogonal to the Z direction is 150 μm, the thickness of the magnetic dielectric portion 21 in the cross section orthogonal to the Z direction is 25 μm, and is orthogonal to the Z direction. The diameter of the outer periphery of the magnetic dielectric portion 21 in the cross section is 200 μm. In the model shown in FIG. 22E, the first relative dielectric constant E1 is 10,000, the dielectric loss tangent of the first dielectric is 0.001, and the second relative dielectric constant E2 is 7 The relative permeability μ of the magnetic dielectric part 21 was set to 5.

  In FIGS. 22A to 22E, the magnetic field strengths at 12 positions in the vicinity of the line portion 10 are indicated by arrows. The size of the arrow increases as the magnetic field strength increases. As shown in FIGS. 22A to 22D, the magnetic field strength in the vicinity of the line portion 10 increases as the first relative permittivity E1 increases. From this, it can be seen that as the first relative permittivity E1 increases, the inductance of the dielectric line 2 can be increased, and thereby the resonance frequency of the resonator 30 can be lowered. .

  Further, from FIGS. 22D and 22E, the surrounding dielectric portion 20 includes the magnetic dielectric portion 21, so that the line portion is compared with the case where the entire surrounding dielectric portion 20 does not have magnetism. It can be seen that the magnetic field strength near 10 increases. From this, it is possible to increase the inductance of the dielectric line 2 by at least a part of the surrounding dielectric part 20 being magnetic, and thereby the resonance frequency of the resonator 30 can be lowered. I understand that

[Fifth Embodiment]
Next, a dielectric line and an electronic component according to the fifth embodiment of the invention will be described. FIG. 23 is a plan view of the electronic component according to the present embodiment. 24 is a perspective view of the electronic component shown in FIG.

  Electronic component 200 according to the present embodiment realizes a band-pass filter including two resonators. The electronic component 200 includes a dielectric substrate 201 having an upper surface, and four conductor layers 211, 212, 213, and 214 disposed on the upper surface of the dielectric substrate 201. The relative dielectric constant of the dielectric substrate 201 is 2.6.

  The conductor layers 211 and 212 are both long in one direction and arranged so as to be aligned in this one direction. A gap 210 having a predetermined size is formed between the conductor layers 211 and 212. Here, the direction in which the conductor layers 211 and 212 are arranged is defined as the X direction, and the direction parallel to the upper surface of the dielectric substrate 201 and orthogonal to the X direction is defined as the Y direction. The conductor layers 213 and 214 are disposed on both sides of the conductor layers 211 and 212 in the Y direction so as to sandwich the conductor layers 211 and 212.

  The conductor layer 213 is disposed with a certain distance from the conductor layers 211 and 212. The conductor layer 214 has side portions 214 a facing the conductor layers 211 and 212. The side portion 214a has a first portion 214a1 facing the side portion of the conductor layer 211 facing the side portion 214a with a first interval, and a side portion of the conductor layer 212 facing the side portion 214a. The second portion 214a2 is opposed to the second portion 214a2 with a second interval, and the third portion 214a3 is located between the first portion 214a1 and the second portion 214a2. The third portion 214a3 faces the side portions of the conductor layers 211 and 212 facing the side portion 214a with a third gap. The first and second intervals are equal in size. The size of the third interval is larger than the size of the first and second intervals.

  Dielectric substrate 201 and conductor layers 211, 212, 213, and 214 constitute a coplanar line. The conductor layers 213 and 214 are connected to the ground. The conductor layers 211 and 212 transmit high frequency signals.

  The electronic component 200 further includes two dielectric blocks 221 and 231 and two chip-shaped capacitors 222 and 232. Each of the dielectric blocks 221 and 231 has a rectangular parallelepiped shape that is long in the Y direction. The portion of the dielectric block 221 near one end in the Y direction is in contact with the portion of the upper surface of the conductor layer 214 near the third portion 214a3 of the side portion 214a and the other end of the dielectric block 221 in the Y direction. The nearby portion is in contact with the upper surface of the conductor layer 211. The portion of the dielectric block 231 near one end in the Y direction is in contact with the portion of the upper surface of the conductor layer 214 near the third portion 214a3 of the side portion 214a and the other end of the dielectric block 231 in the Y direction. The nearby portion is in contact with the upper surface of the conductor layer 212. The capacitor 222 connects the conductor layer 211 and the conductor layer 213. The capacitor 232 connects the conductor layer 212 and the conductor layer 213. The capacitances of the capacitors 222 and 232 are both 0.6 pF.

  The lengths of the dielectric blocks 221 and 231 in the Y direction are both 1.6 mm. The cross-sectional shapes of the dielectric blocks 221 and 231 orthogonal to the Y direction are both squares with a side length of 0.5 mm. The dielectric blocks 221 and 231 are both made of barium strontium titanate. Dielectric blocks 221 and 231 constitute a line portion in the dielectric line according to the present embodiment. The relative permittivity of the dielectric blocks 221 and 231, that is, the first relative permittivity E 1 is 1000. The propagation direction of electromagnetic waves in the dielectric blocks 221 and 231 is the Y direction. In the cross section orthogonal to the propagation direction of electromagnetic waves in the dielectric blocks 221 and 231, that is, the Y direction, the shapes of the dielectric blocks 221 and 231 are quadrangular.

  The electronic component 200 further includes a surrounding dielectric portion (not shown) made of a second dielectric having a second relative dielectric constant E2. The surrounding dielectric portions exist around the dielectric blocks 221 and 231 in a cross section orthogonal to the propagation direction of the electromagnetic waves in the dielectric blocks 221 and 231. The second dielectric constituting the surrounding dielectric part may be a dielectric material or air. The electronic component 200 includes a dielectric line constituted by the dielectric block 221 and the surrounding dielectric part, and a dielectric line constituted by the dielectric block 231 and the surrounding dielectric part.

  FIG. 25 is a circuit diagram showing a circuit configuration of electronic component 200 shown in FIG. The electronic component 200 includes an input end 241, an output end 242, resonators 220 and 230, and a capacitor 240. The resonator 220 includes a dielectric block 221 and a capacitor 222 connected in parallel. The resonator 230 includes a dielectric block 231 and a capacitor 232 connected in parallel. The dielectric blocks 221 and 231 each function as an inductor.

  The input end 241 is configured by a conductor layer 211. One end of the dielectric block 221 and one end of the capacitor 222 are connected to the input end 241 (conductor layer 211). The other end of the dielectric block 221 is connected to the ground (conductor layer 214). The other end of the capacitor 222 is connected to the ground (conductor layer 213).

  The output end 242 is constituted by the conductor layer 212. One end of the dielectric block 231 and one end of the capacitor 232 are connected to the output end 242 (conductor layer 212). The other end of the dielectric block 231 is connected to the ground (conductor layer 214). The other end of the capacitor 232 is connected to the ground (conductor layer 213).

  The capacitor 240 is composed of conductor layers 211 and 212 and a gap 210 between them. One end of the capacitor 240 is connected to the input end 241 (conductor layer 211), and the other end of the capacitor 240 is connected to the output end 242 (conductor layer 212).

  The resonator 220 and the resonator 230 are electromagnetically coupled. This electromagnetic field coupling includes inductive coupling between the dielectric blocks 221 and 231 and capacitive coupling by the capacitor 240.

  When the resonators 220 and 230 were actually manufactured, the resonance frequency of the resonators 220 and 230 was 7.04 GHz, and the unloaded Q value was 98.6. In order to compare with the resonators 220 and 230, an inductor constituted by a conductor layer made of Ag was provided instead of the dielectric block 221, and a resonator of a comparative example constituted by the inductor and the capacitor 222 was also produced. The resonance frequency of the resonator of this comparative example was 5.86 GHz, and the unloaded Q value was 60.4. As described above, according to this embodiment, it was confirmed that a resonator having a large unloaded Q value as compared with the resonator of the comparative example can be realized.

  FIG. 26 is a characteristic diagram showing frequency characteristics of the electronic component 200 shown in FIG. In FIG. 26, the horizontal axis represents frequency and the vertical axis represents attenuation. In FIG. 26, the curve with the symbol S1 indicates the passing attenuation characteristic of the electronic component 200, and the curve with the symbol S2 indicates the reflection attenuation characteristic of the electronic component 200. From FIG. 26, it can be seen that the electronic component 200 implements a bandpass filter. The center frequency of the passband of this bandpass filter is 7.8 GHz, and the passband width is 0.6 GHz. The pass band of the band pass filter is a frequency range in which the attenuation in the pass attenuation characteristic S1 is 3 dB or less.

[Sixth Embodiment]
Next, a dielectric line and an electronic component according to the sixth embodiment of the invention will be described. FIG. 27 is a perspective view of the electronic component according to the present embodiment. FIG. 28 is a perspective view showing the inside of the electronic component shown in FIG. As shown in FIG. 27, electronic component 300 according to the present embodiment has a rectangular parallelepiped shape. Here, as shown in FIG. 27, the X direction, the Y direction, and the Z direction are defined. The X direction, the Y direction, and the Z direction are orthogonal to each other. The electronic component 300 has an upper surface 300a and a lower surface 300b positioned at both ends in the Z direction, two side surfaces 300c and 300d positioned at both ends in the X direction, and two side surfaces 300e and 300f positioned at both ends in the Y direction. doing. As shown in FIG. 27, the dimensions of the electronic component 300 in the X direction, the Y direction, and the Z direction are, for example, 1.0 mm, 0.5 mm, and 0.35 mm, respectively.

  As shown in FIG. 28, the electronic component 300 includes an inductor unit 310 and a capacitor unit 350. FIG. 29 is a perspective view showing the capacitor unit 350. The inductor unit 310 is disposed on the capacitor unit 350. As shown in FIG. 27, the electronic component 300 further includes a coating layer 309 made of an insulating material that covers the inductor section 310 and the capacitor section 350.

  The electronic component 300 includes an input terminal 301 exposed on the side surface 300c (see FIGS. 28 and 29), an output terminal 302 exposed on the side surface 300d, and ground terminals 303 and 304 exposed on the side surfaces 300e and 300f (see FIG. 29). And an external shield layer 305 exposed on the upper surface 300a and a ground layer 306 exposed on the lower surface 300b. The input terminal 301, the output terminal 302, the ground terminals 303 and 304, the external shield layer 305, and the ground layer 306 are composed of conductors. The ground terminals 303 and 304 are electrically connected to the ground layer 306. The inductor section 310 includes six dielectric lines arranged side by side in the X direction. The six dielectric lines will be described in detail later.

  As shown in FIG. 29, the capacitor unit 350 has six capacitor conductor layers 351 disposed above the ground layer 306. The six capacitor conductor layers 351 are arranged side by side in the X direction. The capacitor conductor layer 351 closest to the input terminal 301 is electrically connected to the input terminal 301. The capacitor conductor layer 351 closest to the output terminal 302 is electrically connected to the output terminal 302.

  The capacitor unit 350 further includes five capacitor conductor layers 352 arranged between the ground layer 306 and the six capacitor conductor layers 351. When viewed from the Z direction, one capacitor conductor layer 352 is disposed so as to overlap two adjacent capacitor conductor layers 351.

  The capacitor unit 350 further includes a dielectric substrate 353 that holds the ground layer 306, the six capacitor conductor layers 351, and the five capacitor conductor layers 352. The relative dielectric constant of the dielectric substrate 353 is, for example, 100. The relative permeability of the dielectric substrate 353 is 1.

  A portion obtained by combining one dielectric line in the inductor section 310 and a part of the capacitor section 350 located thereunder is referred to as a resonator section 360. The electronic component 300 includes six resonator portions 360 arranged side by side in the X direction.

  FIG. 30 is a perspective view showing the inside of one resonator portion 360. FIG. 30 specifically shows the resonator portion 360 closest to the output terminal 302. As shown in FIG. 30, the dielectric line 311 includes a line portion 312 and a surrounding dielectric portion 313 existing around the line portion 312. The line portion 312 is embedded in the surrounding dielectric portion 313. The surrounding dielectric part 313 has a rectangular parallelepiped shape. The overall shape of the line portion 312 as viewed from the X direction is a meander shape. The propagation direction of the electromagnetic wave in the line portion 312 is a direction in which the line portion 312 extends. The surrounding dielectric portion 313 exists around the line portion 312 in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line portion 312. In the present embodiment, in particular, in the cross section, the surrounding dielectric portion 313 is in contact with the entire outer periphery of the line portion 312. In the cross section, the shape of the line portion 312 is a quadrangle, particularly a rectangle.

  The line portion 312 is configured by a first dielectric having a first relative dielectric constant E1. In the present embodiment, the first relative dielectric constant E1 is, for example, 500,000, and the dielectric loss tangent of the first dielectric is, for example, 0.001. The surrounding dielectric portion 313 is configured by a second dielectric having a second relative dielectric constant E2. In the present embodiment, the second relative dielectric constant E2 is 20, for example, and the dielectric loss tangent of the second dielectric is, for example, 0.001. Moreover, the relative magnetic permeability of the second dielectric is in the range of 1 to 23, for example.

  One resonator portion 360 includes one capacitor conductor layer 351. One end of the line portion 312 is connected to the capacitor conductor layer 351. In addition, one resonator portion 360 includes a conductor portion 354 that connects the other end of the line portion 312 and the ground layer 306. The conductor portion 354 is embedded in the dielectric substrate 353.

  As shown in FIG. 30, the dimensions of the resonator portion 360 in the X direction, the Y direction, and the Z direction are, for example, 0.15 mm, 0.5 mm, and 0.35 mm, respectively.

  The electronic component 300 includes a plurality of partition shield layers 361 disposed between two adjacent resonator portions 360 and on the outer surfaces of the two resonator portions 360 located at both ends in the X direction. . FIG. 31 shows one resonator portion 360 and two partition shield layers 361 located on both sides thereof.

  FIG. 32 is a front view of the resonator portion 360 viewed from the X direction. FIG. 33 is a side view of the resonator portion 360 viewed from the Y direction. As shown in FIG. 32, the width of the line portion 312 viewed from the X direction is, for example, 30 μm. As shown in FIG. 33, the thickness of the line portion 312 as viewed from the Y direction is, for example, 5 μm.

  FIG. 34 is a circuit diagram showing a circuit configuration of the electronic component 300. The electronic component 300 includes an input terminal 301, an output terminal 302, six resonators 371 to 376, six capacitors 381 to 386, and two inductors 388 and 389. Any two adjacent resonators of the six resonators 371 to 376 are electromagnetically coupled.

  The resonator 371 includes inductors 371L1 and 371L2 and a capacitor 371C. One end of each of the inductors 371L1 and 371L2 is connected to the input terminal 301. One end of the capacitor 371C is connected to the other end of the inductor 371L2. The inductor 371L1 is configured by a line portion 312 that is closest to the input terminal 301. The inductor 371L2 is configured by a capacitor conductor layer 351 that is closest to the input terminal 301. The capacitor 371C includes a capacitor conductor layer 351 closest to the input terminal 301, a ground layer 306, and a part of the dielectric substrate 353 therebetween.

  The resonator 372 includes an inductor 372L and a capacitor 372C. The resonator 373 includes an inductor 373L and a capacitor 373C. The resonator 374 includes an inductor 374L and a capacitor 374C. The resonator 375 includes an inductor 375L and a capacitor 375C.

  The inductors 372L, 373L, 374L, and 375L are configured by four line portions 312 excluding the line portion 312 that is closest to the input terminal 301 and the line portion 312 that is closest to the output terminal 302. Capacitors 372C, 373C, 374C, and 375C include four capacitor conductor layers 351 excluding the capacitor conductor layer 351 connected to the input terminal 301 and the capacitor conductor layer 351 connected to the output terminal 302, the ground layer 306, , And a part of the dielectric substrate 353 between them.

  The resonator 376 includes inductors 376L1 and 376L2 and a capacitor 376C. One end of each of the inductors 376L1 and 376L2 is connected to the output terminal 302. One end of the capacitor 376C is connected to the other end of the inductor 376L2. The inductor 376L1 is configured by a line portion 312 that is closest to the output terminal 302. The inductor 376L2 is configured by the capacitor conductor layer 351 closest to the output terminal 302. The capacitor 376C includes a capacitor conductor layer 351 closest to the output terminal 302, a ground layer 306, and a part of the dielectric substrate 353 therebetween.

  One end of the capacitor 381 is connected to one end of each of the inductors 371L1 and 371L2. The other end of the capacitor 381 is connected to one end of each of the inductor 372L and the capacitor 372C. One end of the capacitor 382 is connected to one end of each of the inductor 372L and the capacitor 372C. The other end of the capacitor 382 is connected to one end of each of the inductor 373L and the capacitor 373C. One end of the capacitor 383 is connected to one end of each of the inductor 373L and the capacitor 373C. The other end of the capacitor 383 is connected to one end of each of the inductor 374L and the capacitor 374C. One end of the capacitor 384 is connected to one end of each of the inductor 374L and the capacitor 374C. The other end of the capacitor 384 is connected to one end of each of the inductor 375L and the capacitor 375C. One end of the capacitor 385 is connected to one end of each of the inductor 375L and the capacitor 375C. The other end of the capacitor 385 is connected to one end of each of the inductors 376L1 and 376L2.

  The capacitors 381 to 385 are constituted by five capacitor conductor layers 352, six capacitor conductor layers 351, and a part of the dielectric substrate 353 therebetween. Each of the capacitors 381 to 385 is configured by one capacitor conductor layer 352, two capacitor conductor layers 351 located on both sides thereof, and a part of the dielectric substrate 353 therebetween.

  One end of the inductor 388 is connected to the other end of each of the inductors 371L1, 372L, 373L, 374L, 375L, and 376L1. The other end of the inductor 388 is connected to the ground. One end of the inductor 389 is connected to the other ends of the capacitors 371C, 372C, 373C, 374C, 375C, and 376C. The other end of the inductor 389 is connected to the ground. The inductors 388 and 389 are constituted by the ground layer 306.

  One end of the capacitor 386 is connected to the input terminal 301, and the other end of the capacitor 386 is connected to the output terminal 302. The capacitor 386 is configured by a distributed capacitance generated between the line portion 312 closest to the input terminal 301 and the line portion 312 closest to the output terminal 302.

  The electronic component 300 realizes a six-stage pseudo elliptic function type bandpass filter. FIG. 35 is a characteristic diagram illustrating an example of a passing attenuation characteristic of the electronic component 300 obtained by simulation. In FIG. 35, the horizontal axis represents frequency, and the vertical axis represents passage attenuation. In this example, the relative permeability of the second dielectric constituting the surrounding dielectric portion 313 is 23, and the capacitances of the capacitors 371C to 376C are 1.4 pF, respectively. In the example shown in FIG. 35, the electronic component 300 realizes a bandpass filter having a passband center frequency of 2.43 GHz.

  Next, a fifth simulation performed for resonator portion 360 in the present embodiment will be described. In the fifth simulation, the relationship between the relative magnetic permeability and dielectric loss tangent of the second dielectric that constitutes the surrounding dielectric portion 313, and the resonance frequency and unloaded Q value of the resonator that is constituted by the resonator portion 360. I investigated. In the models M1 to M4 of the resonator portion 360 used in the fifth simulation, conditions other than the relative permeability and dielectric loss tangent of the second dielectric are as described above.

  The results of the fifth simulation are shown in Table 3 below and FIG. In FIG. 36, the horizontal axis represents the resonance frequency of the resonator, and the vertical axis represents the unloaded Q value. In the fifth simulation, instead of the line portion 312 in the model of the resonator portion 360 used in the fifth simulation, a conductor line portion made of Ag having the same shape as the line portion 312 is provided, and the ratio of the surrounding dielectric portion 313 is determined. For the comparative model with a permeability of 1.0, the resonance frequency of the resonator and the unloaded Q value of the resonator were also determined. In the model of the comparative example, the resonance frequency of the resonator was 3.59 GHz, and the unloaded Q value of the resonator was 22. In FIG. 36, the resonance frequency and the no-load Q value in the model of the comparative example are represented by white square points, and the resonance frequency and the no-load Q value in the models M1 to M4 are represented by solid square points. The unloaded Q values in the models M1 to M4 are all greater than the unloaded Q value in the model of the comparative example. The arrows in FIG. 36 indicate that the no-load Q value increases in the order of models M1, M2, M3, and M4.

  From Table 3 and FIG. 36, in the model of the resonator part 360 used in the fifth simulation, as the relative permeability of the surrounding dielectric part 313 increases, the resonance frequency decreases and the unloaded Q value increases. I understand. Therefore, the larger the relative permeability of the surrounding dielectric portion 313, the easier it is to realize a resonator having a resonance frequency in the range of 1 GHz to 10 GHz and a large unloaded Q value. Further, it can be seen from Table 3 and FIG. 36 that the unloaded Q value of the resonator can be increased by reducing the dielectric loss tangent of the second dielectric.

  In addition, this invention is not limited to said each embodiment, A various change is possible. For example, when the surrounding dielectric part includes a magnetic dielectric part and a nonmagnetic dielectric part, the magnetic dielectric part is one of the entire outer circumferences of the line part in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line part. It may be provided so as to contact only the part. In addition, the electronic component of the present invention is not limited to the one provided with the resonator configured using the dielectric line of the present invention, and may be any as long as it includes the dielectric line of the present invention. For example, the electronic component of the present invention may include a circuit other than the resonator, such as an antenna, a directional coupler, a matching circuit, and a transformer, each configured using the dielectric line of the present invention. Good.

  DESCRIPTION OF SYMBOLS 1 ... Electronic component, 2 ... Dielectric line, 10 ... Line part, 20 ... Surrounding dielectric part, 21 ... Magnetic dielectric part, 22 ... Nonmagnetic dielectric part

Claims (6)

An electronic component comprising a resonator having a resonance frequency within a range of 1 GHz to 10 GHz, having an inductor and a capacitor connected in parallel,
Including dielectric lines,
The dielectric line includes a line part made of a first dielectric having a first relative dielectric constant, and a surrounding dielectric part made of a second dielectric having a second relative dielectric constant,
The line section propagates electromagnetic waves having one or more frequencies within a range of 1 GHz to 10 GHz,
The surrounding dielectric part is present around the line part in a cross section orthogonal to the propagation direction of the electromagnetic wave in the line part,
The first relative dielectric constant is 1000 or more,
The second dielectric constant is smaller than the first dielectric constant,
The inductor is constituted by the line portion of the dielectric line.   The electronic component according to claim 1, wherein the first relative dielectric constant is 500,000 or less.   3. The electronic component according to claim 1, wherein the second relative dielectric constant is 1/10 or less of the first relative dielectric constant.   4. The electronic component according to claim 1, wherein at least a part of the surrounding dielectric part has a relative magnetic permeability of 1.02 or more.   The electronic component according to claim 4, wherein the relative magnetic permeability of at least a part of the surrounding dielectric portion is 30 or less. The electronic component further includes a first conductor layer and a second conductor layer facing the first conductor layer at a predetermined interval,
A part of the surrounding dielectric portion is interposed between the first conductor layer and the second conductor layer,
One end of the line part in the propagation direction of the electromagnetic wave in the line part is connected to the second conductor layer,
6. The electronic component according to claim 1, wherein the capacitor is constituted by the first and second conductor layers and a part of the surrounding dielectric portion therebetween.

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