JP5793021B2 - Current detector - Google Patents

Description

  The present invention relates to a current detection device that uses the non-linear characteristics of a high magnetic permeability material used for leakage detection and the like.

As this type of current detection device, devices having various configurations have been proposed and implemented, but a flux gate type current sensor is known as a device that is structurally simple and capable of detecting a minute current. (For example, refer to Patent Document 1).
The conventional example described in Patent Document 1 has a configuration shown in FIG. That is, the same shape and isometrically formed cores 101 and 102 made of a soft magnetic material, the exciting coil 103 wound around the cores 101 and 102, and the cores 101 and 102 in a lump. And a wound detection coil 104.
An AC power supply (not shown) is connected to the excitation coil 103, and a detection circuit (not shown) is connected to the detection coil 104. And the to-be-measured conducting wire 107 which is an object which measures an electric current is inserted in the center of both the cores 101 and 102.
The exciting coil 103 is wound around the cores 101 and 102 so that the magnetic fields generated in the cores 101 and 102 are opposite in phase when they are energized and cancel each other.

Then, when the exciting current iex is supplied to the exciting coil 103, the change with time of the magnetic flux density B generated in each of the cores 101 and 102 is as shown in FIG. The magnetic characteristics of the soft magnetic cores 101 and 102 have a linear relationship between the magnetic field magnitude H and the magnetic flux density B when the magnetic field magnitude H is within a predetermined range. However, when the magnitude H of the magnetic field exceeds a predetermined value, the magnetic flux density B does not change and the magnetic saturation state is established. Therefore, when the exciting current iex is supplied to the exciting coil 103, it is generated in each of the cores 101 and 102. The magnetic flux density B to be changed changes to a vertically symmetric trapezoidal wave shape as shown by the solid line, and the phases are 180 ° out of phase with each other.
Assuming that a direct current value I is energized downward as shown by an arrow in the lead 107 to be measured, a magnetic flux density corresponding to this direct current component is superimposed. As a result, the magnetic flux density B is as shown in FIG. As indicated by the broken line, the upper trapezoidal wave has an enlarged width while the lower trapezoidal wave has a reduced width.

Here, when the change in the magnetic flux density B generated in both the cores 101 and 102 is expressed by a sine wave (corresponding to the electromotive force), it is as shown in FIG. In FIG. 10C, a sine wave (electromotive force) having a frequency f shifted by 180 ° as shown in the solid line corresponding to the trapezoidal wave shown in the solid line in FIG. Are offset by 180 °, so they cancel each other. On the other hand, corresponding to the trapezoidal wave shown by the broken line in FIG. 10B, the second harmonic of the double frequency 2f as shown by the broken line appears in FIG. 10C. Since the second harmonics are 180 ° out of phase, if they are superimposed on each other, a sine wave signal as shown in the lowermost stage of FIG. 10C is obtained, and this is detected by the detection coil 104.
The detection signal captured by the detection coil 104 corresponds to the direct current value I flowing through the conductor 107 to be measured, and the current value I can be detected by processing this.

JP 2000-162244 A

  However, in the conventional example described in Patent Document 1, since the two cores 101 and 102 are used, it is actually difficult to completely match the magnetic characteristics of the cores 101 and 102. Due to the difference in characteristics, the voltage due to the excitation current Iex is generated without being completely canceled out. This deteriorates the S / N ratio of the detection voltage corresponding to the second harmonic component, and there is an unsolved problem that it is difficult to detect a minute current.

Moreover, since at least two cores are used, there is an unsolved problem that it is difficult to realize miniaturization and cost reduction.
Furthermore, since it is necessary to excite the cores 101 and 102 to the saturation region, there is an unsolved problem that a large excitation current is required and the consumption current of the sensor is large.
Therefore, the present invention has been made paying attention to the above-mentioned unsolved problems of the conventional example, and is hardly affected by ambient environmental conditions, and can detect a minute current with a small size, low cost, and low current consumption. An object of the present invention is to provide a current detection device that can be used.

In order to achieve the above object, a first aspect of a current detection device according to the present invention includes a primary winding through which a measurement current flows, and the primary winding by a magnetic core electrically insulated from the primary winding. A current detecting device including a magnetically coupled secondary winding, wherein the magnetic core is supplied to the secondary winding in a saturated state or in the vicinity thereof in accordance with a set threshold voltage. An oscillating means for generating a rectangular wave voltage for reversing the direction of the exciting current, a current detecting means for detecting the measurement current based on a duty change of the rectangular wave voltage output from the oscillating means, and the oscillating means Frequency detection means for detecting the frequency of the output rectangular wave voltage, threshold setting means for setting a threshold voltage of the oscillation means based on the frequency detected by the frequency detection means, and a secondary for supplying the excitation current Winding And a winding number selection means for varying the current detecting characteristic as selectable number in a plurality of steps, said oscillating means, said secondary winding connected between the output side and the inverting input, the output side connected to an output terminal An operational amplifier, a resistance inserted between a connection point of the inverting input side of the operational amplifier and the secondary winding and the ground, and the operational amplifier for supplying the threshold voltage to the non-inverting input side of the operational amplifier A voltage dividing resistor connected between the output side of the output terminal and the ground, and the operational amplifier compares the threshold voltage with the voltage at the connection point to generate the rectangular wave voltage to generate the output terminal. you output to.

According to this configuration, by applying a rectangular wave voltage to the exciting coil according to the threshold set by the oscillation means, an exciting current that becomes a sawtooth wave determined by the inductance of the exciting coil flows, and the direction of the exciting current is switched. By making the current to be switched match the saturation current of the magnetic core when the current is zero, the current width at which the direction of the magnetizing current changes according to the measured current flowing through the conductor, and the rectangular wave is changed accordingly. Varying the voltage fall. Further, the frequency of the rectangular wave voltage is detected by the frequency detection means, and the threshold value is changed according to the detected frequency, thereby reducing the excitation current and reducing the current consumption.
Furthermore, since the number of turns of the secondary winding wound around the magnetic core can be switched by the number-of-turns selection means, a desired current detection characteristic can be selected.
Further, according to a second aspect of the current detection device of the present invention, the winding number selection means includes a plurality of lead wires individually connected to a plurality of different winding number positions of the secondary winding, and the plurality of lead wires include And a selection switch having a plurality of individually connected fixed terminals and a movable terminal for selecting one of the plurality of fixed terminals.

According to this configuration, the number of turns of the secondary winding wound around the magnetic core can be adjusted by selecting one of the plurality of connection terminals with the selection switch.
Furthermore, a third aspect of the current sensing device according to the present invention, the threshold value setting means, when the frequency of the rectangular wave voltage detected by said frequency detecting means is smaller than the predetermined set value, the threshold voltage the When the peak value of the excitation current is set to be small, and the detected frequency of the rectangular wave voltage is higher than the predetermined set value, the threshold voltage is increased and the peak value of the excitation current is increased. The voltage frequency is set to be lower than the predetermined set value.
According to this configuration, the threshold current can be set low during standby or when the measurement current is small, and the excitation current can be reduced.

  According to the present invention, by utilizing the fact that the characteristic that the inductance of the magnetic core suddenly disappears in the vicinity of the saturation current is shifted by the current of the conducting wire penetrating the inside, the excitation means and the rectangular winding voltage are applied to the secondary winding. Is applied to supply an exciting current to bring the magnetic core into saturation or in the vicinity thereof, causing a current change in the secondary winding in accordance with the disappearance of the magnetic core inductance, and a threshold set by this current change. The falling of the rectangular wave voltage is changed according to For this reason, the measurement current flowing through the conducting wire is detected by detecting the duty of the rectangular wave voltage. For this reason, the current detection device can be configured using one magnetic core, and the S / N ratio does not decrease due to the difference in the material characteristics of the magnetic core, and a minute current can be detected with high accuracy. .

In addition, since the current detection device can be configured with one magnetic core and one winding, it is possible to reduce the size and cost.
Furthermore, since a magnetic sensor or the like is not used, it is possible to provide a current detection device that is robust and less affected by ambient environmental conditions.
In addition, since the threshold value of the oscillating means is changed according to the frequency of the rectangular wave voltage, the excitation current can be suppressed and the current consumption can be reduced.
In addition, since the number of turns of the secondary winding wound around the magnetic core can be selected by the number-of-turns selection means, it is possible to detect a small current with high sensitivity even if the detection range is narrow, or a wide range of current even if the sensitivity is low. The current detection characteristic can be set according to the use conditions such as when it is detected.

1 is a configuration diagram illustrating a first embodiment of a current detection device according to the present invention. FIG. It is a figure which shows the specific structure of the winding number selection part of FIG. FIG. 2 is a circuit diagram illustrating an example of the oscillation circuit of FIG. 1. It is a schematic diagram which shows the output voltage waveform of an oscillation circuit, and the current waveform of an exciting coil. It is a characteristic diagram which shows the relationship between the magnetic field strength of a magnetic core, and a magnetic flux density, and a characteristic diagram which shows the inductance characteristic of a magnetic core. It is a block diagram which shows an example of the frequency detection circuit which can be applied to this invention. It is a characteristic diagram which shows the relationship between an exciting current and a threshold current. It is a characteristic diagram which shows an exciting current waveform when a threshold current is switched. It is a characteristic diagram which shows the relationship between the number of turns of an exciting coil, a current detection sensitivity, and a current detection range. It is explanatory drawing which shows a prior art example, Comprising: (a) The block diagram of a sensor part, (b) is a figure which shows the magnetic flux density of each magnetic core when an exciting current is supplied to an exciting coil, (c) is each magnetic core It is the figure which expressed the magnetic flux density of sine wave.

Hereinafter, embodiments of the present invention will be described with reference to the drawings.
FIG. 1 is a configuration diagram showing an embodiment of a current detection device according to the present invention. In the figure, reference numeral 1 denotes a current detection device, which detects a minute difference current between conductors 2a and 2b through which a reciprocating current I of 10A to 800A, for example, provided on an object such as leakage detection is flowing. Here, the sum of the currents flowing through the conductors 2a and 2b is zero in a healthy state, but the sum of the currents flowing through the conductors 2a and 2b is not zero when there is an electric leakage or a ground fault, and the detection target is, for example, 15 mA to 500 mA. A very small difference current flows. Around these conducting wires 2a and 2b, a ring-shaped magnetic core 3 is disposed so that the conducting wires 2a and 2b serve as primary windings. That is, the conducting wires 2 a and 2 b are inserted into the magnetic core 3 as primary windings.

An exciting coil 4 as a secondary winding is wound around the magnetic core 3 with a predetermined number of turns. The exciting coil 4 is connected to an oscillation circuit 6 via a winding number selection unit 5 as a winding number selection means.
The winding number selection unit 5 includes, for example, four connection lines L1 to L4 connected to a plurality of different winding positions of the exciting coil 4, and a selection switch SW to which the other ends of the connection lines L1 to L4 are connected. Yes. The connection line L1 is connected to the winding start side of the excitation coil 4, for example, and the connection line L4 is connected to the winding end of the excitation coil 4.
As shown in FIG. 2, the selection switch SW includes fixed terminals Ts1 to Ts4 to which connection lines L1 to L4 are connected, and a movable terminal Tm that selects one of the fixed terminals Ts1 to Ts4.

The movable terminal Tm of the selection switch SW is connected to one output terminal to1 of the oscillation circuit 6, and the winding start of the exciting coil 4 is connected to the other output terminal to2 of the oscillation circuit 6.
As shown in FIG. 3, the oscillation circuit 6 includes an operational amplifier 11 that operates as a comparator. Output terminals to1 and to2 are connected to the output side and the inverting input side of the operational amplifier 11. The inverting input side of the operational amplifier 11 is connected to the ground via the resistor 12, and the non-inverting input side of the operational amplifier 11 is the voltage dividing resistors 13, 14 and 15 connected in series between the output side of the operational amplifier 11 and the ground. Are connected between the voltage dividing resistors 13 and 14.

In addition, an analog switch circuit 16 is connected in parallel with the resistor 14, and the analog switch circuit 16 is in an off state when the frequency detection signal Sf output from the frequency detection circuit 8 described later is, for example, at a low level. When the frequency detection signal Sf is at a high level, the analog switch circuit 16 is controlled to be on. Here, the resistor 14 and the analog switch circuit 16 constitute a threshold setting circuit 17 as threshold setting means.
The external output terminal to is connected to the connection point between the output side of the operational amplifier 11 and the output terminal to1.

For this reason, in the oscillation circuit 6, the connection point E between the voltage dividing resistors 13 and 14 in a state where the movable switch Tm selects any one of the fixed terminals Ts 1 to Ts 4 with the selection switch SW of the winding number selection unit 5. The threshold voltage Vth is supplied to the non-inverting input side of the operational amplifier 11. At this time, when the analog switch circuit 16 is in an OFF state, the threshold voltage Vth1 is expressed by the following equation (1) when the resistance value of the resistor 13 is R1, the resistance value of the resistor 14 is R2, and the resistance value of the resistor 15 is R3. It is represented by
Vth1 = {R1 / (R1 + R2 + R3)} Va (1)
When the analog switch circuit 16 is in the on state, the threshold voltage Vth2 is expressed by the following equation (2).
Vth2 = {R1 / (R1 + R3)} Va (2)

Therefore, the threshold value Vth2 when the analog switch circuit 16 is in the on state is larger than the threshold value Vth1 when the analog switch circuit 16 is in the off state.
Therefore, assuming that the analog switch circuit 16 is in the OFF state, the threshold voltage Vth1 at this time is compared with the voltage Vd at the connection point D between the exciting coil 4 and the resistor 12, and the comparison output is shown in FIG. It is output from the output side as a rectangular wave output voltage Va shown in FIG.
Now, as shown in FIG. 4A, when the output voltage Va on the output side of the operational amplifier 11 becomes high level at time t1, this is applied to the exciting coil 4. For this reason, the exciting coil 4 is excited with the exciting current Ib corresponding to the output voltage Va and the resistance value R12 of the resistor 12. At this time, as shown in FIG. 4B, the excitation current Iex takes a parabolic shape that rises relatively steeply from the rising point of the output voltage Va and then gradually increases.

At this time, the comparison is made by dividing the output voltage Va on the non-inverting input side of the operational amplifier 11 by the resistance values R1, R2 and R3 of the voltage dividing resistors 13, 14 and 15 obtained at the connection point E of the voltage dividing resistors 13 and 14. A small threshold voltage Vth1 is input.
On the other hand, the voltage Vd at the connection point D between the exciting coil 4 on the inverting input side of the operational amplifier 11 and the resistor 12 increases as the exciting current Iex of the exciting coil 4 increases, and then the exciting current Iex increases sharply again. When the voltage Vd exceeds the threshold voltage Vth1 on the non-inverting input side at the point F in FIG. 4B at time t2, the output voltage Va of the operational amplifier 11 is inverted to a low level as shown in FIG. 4A. .

In response to this, the direction of the excitation current Ib flowing through the excitation coil 4 is reversed, and the excitation current Iex first decreases relatively steeply and then decreases to a parabolic shape that gradually decreases.
At this time, the threshold voltage Vth is also a low voltage −Vth1 because the output voltage Va is at a low level. Then, the voltage Vd at the connection point D between the exciting coil 4 on the inverting input side of the operational amplifier 11 and the resistor 12 decreases in accordance with the decrease in the exciting current Ib of the exciting coil 4, and this voltage Vd is reduced to the non-inverting input side at time t3. When the output voltage Va falls below the threshold voltage −Vth1, the output voltage Va of the operational amplifier 11 is inverted to the high level as shown in FIG. 4A.

Therefore, as shown in FIG. 4A, the output voltage Va becomes a rectangular wave voltage that repeats a high level and a low level, and the oscillation circuit 6 operates as an astable multivibrator. The excitation current Iex of the excitation coil 4 has a waveform that repeatedly increases and decreases as shown in FIG.
Incidentally, as shown in FIG. 5A, the magnetic core 3 has a BH characteristic representing a relationship between a magnetic flux density B having a large squareness ratio and a magnetic field strength H, and is a non-linear type of a high permeability material. It has special characteristics. The inductance of the magnetic core 3 having the BH characteristic disappears rapidly near the saturation current G as shown in FIG. 5B when the difference current between the conductors 2a and 2b is zero. When a minute difference current C to be detected is generated in the conducting wires 2a and 2b penetrating the magnetic core 3, the BH characteristic in FIG. 5B shows a magnetic field according to the difference current C as shown by the broken line. The timing at which the inductance disappears is changed by shifting in the positive direction of the intensity H.

For this reason, the current at which the inductance is saturated when the current is zero (G in FIG. 5) and the current at which the direction of the excitation current Iex switches (F in FIG. 4) are matched. Then, since the current at which the inductance is saturated (J in FIG. 5) changes according to the current value C of the difference current between the conductors 2a and 2b, the current that switches the direction of the excitation current Iex (H in FIG. 4B). Will change as well.
By changing the current value at which the direction of the excitation current Iex changes, the timing at which the voltage Vd at the connection point D between the excitation coil 4 and the resistor 12 exceeds the threshold voltage Vth1 is delayed. For this reason, the falling point of the output voltage Va output from the operational amplifier 11 is delayed as shown by the broken line in FIG. 4A according to the current value C of the difference current between the conductors 2a and 2b. As a result, the duty ratio of the rectangular wave voltage of the output voltage Va changes according to the current value C of the difference current between the conducting wires 2a and 2b.

  Therefore, the duty detection circuit 7 as current detection means for detecting the duty ratio is connected to the external output terminal to of the oscillation circuit 6. The duty detection circuit 7 can detect the duty ratio by measuring the time during which the output voltage Va is maintained at the high level and the time during which the output voltage Va is maintained at the low level. The current value C of the minute difference current of the conducting wires 2a and 2b can be detected based on the above.

Further, the rectangular wave voltage Va output from the external output terminal to of the oscillation circuit 6 is also supplied to the frequency detection circuit 8 as frequency detection means. As shown in FIG. 6, the frequency detection circuit 8 includes a frequency-voltage conversion circuit 81 to which the output voltage Va from the oscillation circuit 6 is input, and an output voltage Vf of the frequency-voltage conversion circuit 81 that is a non-inverting input terminal. In addition, the comparator circuit 83 is configured such that the reference voltage Vref from the reference voltage source 82 is input to the inverting input terminal. Here, the reference voltage Vref output from the reference voltage source 82 is set to a value that causes the excitation current Iex to change in duty according to the current value C to be detected in correspondence with the output voltage Vf from the frequency-voltage conversion circuit 81. Is set.
Therefore, when the output voltage Vf of the frequency-voltage conversion circuit 81 is equal to or lower than the reference voltage Vref, the frequency detection signal Sf output from the comparison circuit 83 is maintained at a low level, but compared when the output voltage Vf exceeds the reference voltage Vref. The frequency detection signal Sf output from the circuit 83 becomes high level.

On the other hand, if the threshold voltage Vth at the connection point E of the oscillation circuit 6 is fixed at the threshold voltage Vth1 determined by the resistance values R1, R2 and R3 of the voltage dividing resistors 13, 14 and 15, the threshold current FIG. 7 schematically shows the relationship between the excitation current waveform and the threshold current when a current value C2 exceeding ± Ith1 is applied to the excitation coil 4. As shown in FIG.
As is apparent from FIG. 7, when the current value C2 is energized to the exciting coil 4, the gradient of the exciting current Iex becomes steep toward the threshold current ± Ith1 due to saturation of the magnetic core 3 as shown by the broken line. Since the threshold current ± Ith1 is reached at the point H2 in FIG. 7 before starting to change, the oscillation frequency becomes higher and the change in the duty ratio is substantially zero as compared with the current value C = 0 shown in the solid line. It becomes.

  However, when the frequency of the output voltage Va output from the oscillation circuit 6 is detected by the frequency detection circuit 8 and the output voltage Vf output from the frequency-voltage conversion circuit 81 exceeds the reference voltage Vref, the comparison circuit 83 When the output frequency detection signal Sf becomes high level, the analog switch circuit 16 is turned on accordingly. For this reason, since the resistor 14 is bypassed by the analog switch circuit 16, the threshold voltage Vh at the connection point E becomes the threshold voltage Vth2 expressed by the above-described equation (2), which is larger than the threshold voltage Vth1, Accordingly, the threshold current becomes a threshold current ± Ith2 larger than the threshold current ± Ith1, as shown in FIG. Therefore, when the above-described current value C2 is applied to the exciting coil 4, the exciting current gradually increases beyond the point H2 in FIG. 7 as shown by the broken line in FIG. The threshold current + Ith2 is reached.

For this reason, the output voltage Va output from the oscillation circuit 6 changes from the high level to the low level, and accordingly, the excitation current Iex starts to decrease sharply, and the lower limit is reached at substantially the same time as the current value C = 0. Side threshold current −Ith2 is reached. For this reason, the output voltage Va of the oscillation circuit 6 is inverted to a high level, and the excitation current Iex supplied to the excitation coil 4 increases sharply.
Therefore, the duty change according to the current value C2 can be obtained without changing the oscillation frequency of the oscillation circuit 6. Therefore, the duty ratio detected by the duty detection circuit 7 corresponds to the current value C2, and accurate current detection can be performed.
As described above, by detecting the oscillation frequency of the oscillation circuit 6, the threshold current can be switched according to the current value to be measured, and the threshold current can be set low during standby or when the measurement current is small. The current can be reduced.
The relationship between the measured current and the threshold current is summarized as shown in Table 1 below.

By the way, the relationship between the number N of turns of the exciting coil 4, the current detection sensitivity, and the current detection range is as shown in FIG. That is, the current detection sensitivity is high in a region where the number of turns N of the exciting coil 4 is small as represented by a hyperbolic characteristic line L11 shown by a solid line in FIG. 9, and as the number N of turns of the exciting coil 4 increases. It gradually decreases into a hyperbola. On the contrary, the current detection range is narrow in the region where the number of turns N of the exciting coil 4 is small as shown by the hyperbolic characteristic line L12 shown by the dotted line in FIG. As the value increases, the current detection range gradually increases.
Therefore, the current detection range may be narrow, but when it is desired to increase the current detection sensitivity, the fixed terminal Ts1 is selected by the movable terminal Tm in the selection switch SW of the winding number selection unit 5 so that the winding number N is reduced. As a result, the number of turns N of the exciting coil 4 is reduced, and the current detection sensitivity can be increased.

Conversely, the current detection sensitivity may be low, but when the current detection range is widened, the fixed terminal Ts4 is selected by the movable terminal Tm in the selection switch SW of the winding number selection unit 5 so that the winding number N becomes large. As a result, the number of turns N of the exciting coil 4 is increased, and the current detection range can be widened.
That is, by selecting the fixed terminals Ts1, Ts2, Ts3, and Ts4 in order of the movable terminal Tm of the selection switch SW of the winding number selection unit 5, the current detection sensitivity is gradually switched from the high sensitivity state to the low sensitivity state. The current detection range is gradually switched from a narrow range to a wide range.
Therefore, it is possible to select both the current detection characteristic emphasizing the current detection sensitivity and the current detection characteristic emphasizing the current detection range with a single current detection device. The desired characteristics can be set according to the use conditions.

In the above embodiment, the case where the number of turns N of the exciting coil 4 is selected in four stages by the number of turns selection unit 5 has been described. However, the present invention is not limited to this, and the number of connection lines to the exciting coil 4 is 2 By selecting the above arbitrary number and setting the number of fixed terminals of the selection switch SW to the number corresponding to the connection line, selection of the number of turns of the exciting coil 4 can be set in two or more arbitrary stages.
In the above embodiment, the case where the number of turns N of one excitation coil 4 is selected by the selection switch SW has been described. However, the present invention is not limited to this, and a plurality of excitation coils having different numbers of turns are attached to the magnetic core 3. A plurality of exciting coils may be selected with a selection switch.

In the above embodiment, the case where the threshold voltage Vth of the oscillation circuit 6 is switched in two stages has been described. However, the present invention is not limited to this, and a window comparator is applied as the comparison circuit 83 of the frequency detection circuit 8. By omitting the resistor 14 and connecting three series circuits of analog switch circuits and resistors having different resistance values in parallel, the threshold value is switched to three levels according to the frequency of the output voltage Va, or three levels. It is also possible to switch to the above.
Moreover, in the said embodiment, although the case where the difference electric current of the two conducting wires 2a and 2b was detected was demonstrated, it is not limited to this, The minute electric current which flows into one conducting wire can also be detected. .

  DESCRIPTION OF SYMBOLS 1 ... Current detection apparatus, 2a, 2b ... Conductor wire, 3 ... Magnetic core, 4 ... Excitation coil, 5 ... Number of turns selection part, L1-L4 ... Connection line, SW ... Selection switch, 6 ... Oscillation circuit, 7 ... Duty detection circuit , 8 ... frequency detection circuit, 11 ... operational amplifier, 12 to 15 ... resistor, 16 ... analog switch circuit, 17 ... threshold setting circuit, 71 ... frequency-voltage conversion circuit, 72 ... reference voltage source, 73 ... comparison circuit

Claims (3)

A current sensing device comprising a primary winding through which a measurement current flows, and a secondary winding magnetically coupled to the primary winding by a magnetic core electrically insulated from the primary winding;
Oscillating means for generating a rectangular wave voltage that reverses the direction of the excitation current supplied to the secondary winding in a state where the magnetic core is saturated or in the vicinity thereof in accordance with a set threshold voltage ;
Current detection means for detecting the measurement current based on a duty change of the rectangular wave voltage output from the oscillation means;
A frequency detection means for detecting the frequency of the rectangular wave voltage outputted from said oscillating means,
Threshold setting means for setting a threshold voltage of the oscillation means based on the frequency detected by the frequency detection means;
The number of turns of the secondary winding for supplying the exciting current can be selected in a plurality of stages, and the number of turns selection means for changing the current detection characteristics ,
The oscillating means connects the secondary winding between the output side and the inverting input side, the operational amplifier having the output side connected to the output terminal, and a connection point between the inverting input side of the operational amplifier and the secondary winding. A resistor interposed between the ground and the operational amplifier, and a voltage dividing resistor connected between the ground and the output side of the operational amplifier that supplies the threshold voltage to the non-inverting input side of the operational amplifier. the op amp compares the voltage of the connection point with the threshold voltage, the current sensing device according to claim also be output from the output terminal to generate the square wave voltage.   The winding number selection means includes a plurality of lead wires individually connected to a plurality of different winding number positions of the secondary winding, a plurality of fixed terminals to which the plurality of lead wires are individually connected, and the plurality of fixed terminals. The current detection device according to claim 1, further comprising: a selection switch having a movable terminal for selecting one of the two. The threshold setting means sets the threshold voltage so that the peak value of the excitation current is small when the frequency of the rectangular wave voltage detected by the frequency detection means is smaller than a predetermined set value, and the detected When the frequency of the rectangular wave voltage is higher than the predetermined set value, the threshold voltage is set so that the peak value of the exciting current is increased and the frequency of the rectangular wave voltage is lower than the predetermined set value. The current detection device according to claim 1, wherein:

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