JP4829287B2 - Internal ripple generation type fixed on-time voltage regulator with improved output voltage accuracy - Google Patents

Description

  No. 11/530548 filed Sep. 11, 2006 (Japanese Patent Application No. 2007-216153 filed Aug. 22, 2007) “Utilization of Output Capacitor with Arbitrary Equivalent Series Resistance” Ripple generation in a voltage regulator that uses a fixed on-time control to enable the "and is a continuation-in-part application having at least one common inventor, and the contents of the description of that application with reference to that application Is incorporated herein.

  In addition, this application is filed on the same date as this application and assigned to the same assignee, U.S. Patent Application No. 11 / 955,157 (Japanese Patent Application No. 2008- filed Dec. 12, 2008-“Maximum Duty Cycle And the content of the specification of that application is incorporated herein by reference.

  The present invention relates to a switching type voltage regulator, that is, a DC-DC converter. More specifically, the present invention relates to a fixed on-time controlled utilization type back having an output capacitor with an arbitrary equivalent series resistance (ESR) for improving output voltage accuracy. The present invention relates to a control scheme incorporated in a voltage regulator.

A DC voltage regulator, i.e., a switching voltage regulator, converts one DC voltage level to another DC voltage level. These types of switching voltage regulators are also called DC-DC converters. Switching voltage regulators, sometimes referred to as switching mode power supplies, are low-loss circuit components such as capacitors, inductors, and transformers, and power that performs on / off operations for discrete packet transfer of energy from the input side to the output side. A power supply function is provided by the switch. A feedback circuit or feedback circuit is used to adjust the energy transfer so as to maintain a constant output voltage within a desired load limit range of the circuit.

  The switching voltage regulator can be configured to provide input voltage step-up and / or step-down functions. More specifically, a buck switching voltage regulator, also called a “buck converter”, steps down the input voltage, and a boost switching voltage regulator, also called a “boost converter”, steps up the input voltage. A buck-boost switching voltage regulator, or buck-boost converter, provides both step-up and step-down functions.

  The operation of the switching voltage regulator is well known and can be generalized as follows. That is, energy is applied to the inductor of the output filter circuit when the power switch is turned on so that the current flowing through the inductor can be built up. When the power switch is turned off, the voltage applied to both terminals of the inductor is reversed in polarity, and the charge is transferred to the output capacitor and the load of the output filter circuit. The output capacitor maintains the output voltage at a relatively constant voltage. A second power switch for the synchronous control operation may be used.

  The switching voltage regulator can be constructed using an integrated (internal) power switch or an external power switch. When a switching voltage regulator is composed of an integrated circuit (IC) and a power switch is externally attached to the IC, the switching voltage regulator IC is sometimes called a “switching voltage regulator controller” or a converter controller. Yes, thereby representing that the controller generates a control signal for driving an external power switch connected to the output filter circuit to generate a relatively constant output voltage. A switching voltage regulator controller may also be referred to as a buck controller, a boost controller, or a buck-boost controller, depending on the voltage conversion function of the controller.

  The buck switching voltage regulator with fixed on-time control, that is, the “buck voltage regulator” has high efficiency of light load operation in the pulse width modulation (PWM) mode and is easy to synchronize with an external signal. It has been recognized in the industry for its important advantages such as easy control of relatively long off times and very short fixed on times to adjust high input voltages to low output voltages. .

  A fixed on-time (ie constant on-time) voltage regulator is one type of voltage regulator with ripple mode control, and a hysteretic voltage regulator is another type of switching voltage regulator with ripple mode control. . Generally speaking, the ripple mode voltage regulator adjusts the output voltage based on the ripple component in the output signal. Due to the switching operation of the power switch, the switching voltage regulator generates a ripple current through the output inductor to be switched. This ripple current appears as output voltage ripple mainly due to the equivalent series resistance (ESR) of the output capacitor inserted in parallel with the load.

  The hysteresis voltage regulator uses a comparator to compare the output voltage to be regulated including ripples with a hysteresis control voltage band. Above the hysteresis upper limit, the hysteretic controller switches the output inductor to a low value, and below the lower limit, the hysteretic controller switches the output inductor to a high value. On the other hand, the fixed on-time voltage regulator operates in the same manner as the above-described hysteretic controller, but switches the output inductor to a high value for a fixed time length when the output ripple falls below a single reference point. If the output ripple is still lower than the single reference point at the end of the fixed on-time length, the output inductor is lowered to a low value for a minimum off-time before switching to a high value again for a fixed on-time. Switch.

  In the voltage regulator based on the ripple mode control, the output ripple is useful for adjusting the output voltage, but is disadvantageous in terms of a noise component of the output voltage and a load voltage limit value. Thus, the requirement to keep output ripple to a minimum has prompted the design and manufacture of low ESR capacitors. Decreasing the ESR of the output capacitor can greatly reduce the output ripple signal. By reducing ripple, noise can be minimized and load voltage fluctuation can be reduced, but voltage adjustment in the ripple mode becomes difficult. Further, if the size of the ripple is suppressed, the comparison voltage difference becomes small, and accurate and quick comparison becomes very difficult.

  To that end, manufacturers of fixed on-time voltage regulators minimize the output capacitor's equivalent series resistance (ESR) to ensure that the output voltage has a minimum ripple voltage and can perform effective ripple mode control. The value is fixed. In other words, an output capacitor having a large ESR value must be used for all the fixed on-time voltage regulators. If the ESR value of the output capacitor itself is not large enough, the manufacturer may suggest adding a series resistance to the output capacitor to produce the required ripple voltage minimum.

  One approach that satisfies the above requirements for output capacitors with high ESR values is to add current feedback to the control loop. Another approach is to internally generate a virtual ripple proportional to the inductor current using a virtual ripple generator. Although these methods enable the ripple mode voltage regulator to use an output capacitor having a small ESR value, the voltage regulator becomes more complicated and expensive.

  Since the output signal is required to include a ripple voltage component equal to or greater than the minimum value as described above, the application of the fixed on-time voltage regulator is limited to an application that allows the presence of the ripple voltage component in the output voltage. Also, a capacitor with an ESR value of zero, such as a ceramic capacitor, which is usually cheaper than a tantalum capacitor having a large ESR value, cannot be used because it does not satisfy the ESR minimum value condition necessary for proper operation of the control loop.

USP 5 773 966 Japanese Patent Application No. 2007-216153

  SUMMARY OF THE INVENTION Accordingly, an object of the present invention is to provide a switching type voltage regulator that generates a required ripple voltage with a simple circuit configuration and improves output voltage accuracy.

  According to one embodiment of the present invention, a buck switching voltage regulator configured in an integrated circuit receives an input voltage and uses a constant on-time / variable off-time feedback control loop to provide a first switch and a second switch. The switch is controlled so that an output is supplied to the switch output node for taking out the switching output voltage. The switch output node is connected to an LC filter externally attached to the integrated circuit so that an adjusted output voltage having a substantially constant value is output to the output node. The adjusted output voltage is fed back to the buck switching type voltage regulator through a voltage dividing circuit that generates a feedback voltage at the feedback voltage node. The back-switching voltage regulator includes a first input terminal connected to receive the feedback voltage, a second input terminal connected to receive the first reference voltage, and the feedback voltage. A high output impedance amplifier having an output terminal for producing a first output voltage representative of a difference between the first reference voltage, a first input terminal for receiving a second reference voltage, and a first output of the amplifier; On the integrated circuit of the second input terminal that receives the voltage and an output comparator for generating the output voltage signal for controlling the constant on time / variable off time feedback control loop of the buck switching type voltage regulator, and the buck switching type voltage regulator A first capacitor and a first resistor, which are inserted in series between the switch output node and the output terminal of the amplifier, and And a second capacitor connected between said output node and said output terminal of said amplifier. In operation, the first capacitor and the second resistor generate a ripple voltage signal associated with the switching output power, and the ripple voltage signal is supplied to the output terminal of the amplifier, and the ripple voltage signal is supplied to the constant on-time. • Used for variable off-time recovery control loop. The magnitude of the ripple voltage signal is a function of the capacitance value of the second capacitor.

  According to another aspect of the invention, the first switch and the second switch are configured using a constant on-time / variable off-time feedback control loop to receive the input voltage and produce a switching output voltage at the switch output node. A buck switching type voltage regulator for controlling, wherein the switch output node is connected to an LC filter circuit to generate a regulated voltage having a substantially constant magnitude, that is, a feedback voltage to the feedback voltage node. A method in a buck switching voltage regulator that generates a regulated voltage that is fed back to a voltage dividing circuit inside the buck switching voltage regulator, wherein the feedback voltage is applied to the first output of the high output impedance amplifier. Supplying to the input terminal; supplying a first reference voltage to the second input terminal of the amplifier; and an output terminal of the amplifier. Generating a first output voltage representing the difference between the feedback voltage and the first reference voltage; generating a ripple voltage signal from the switching output voltage; and a ripple voltage signal at the output terminal of the amplifier. And supplying the first output voltage of the amplifier and the injected ripple voltage signal to the first input terminal of the comparator. And a method of supplying a second reference voltage to a second input terminal of the comparator and adjusting a magnitude of the ripple voltage signal at the output terminal of the amplifier by a capacitive voltage divider. can get.

  A voltage regulator with a simple circuit configuration and high output voltage accuracy can be provided.

  According to the principle of the present invention, a buck switching type voltage regulator using a fixed (constant) on-time / minimum off-time control loop internally generates a required ripple voltage signal using a switch output voltage, and the ripple voltage. It includes a ripple injection circuit that injects the signal into the feedback control loop of the voltage regulator. The magnitude of the ripple voltage to be generated is adjusted by a feed-forward capacitor that can be integrated with the voltage regulator or externally attached. In this way, the buck voltage regulator can be configured to accommodate output capacitors having any value of ESR. More specifically, when the output capacitor connected to the buck voltage regulator has a large ESR value, a feedforward capacitor is used to program the ripple injection circuit so that little or no ripple is generated from the switch output voltage. On the other hand, if the ESR value of the output capacitor is zero or close to it, a feedforward capacitor is used to program a ripple injection circuit that generates a required ripple voltage from the switch output voltage.

  The buck-switching voltage regulator of the present invention incorporating a ripple injection circuit has a number of advantages over this type of prior art circuit. First, this switching type voltage regulator can cope with any value of ESR of the output capacitor. That is, it is possible to use an output capacitor such as a ceramic capacitor having a small ESR value so as to generate an output voltage containing almost no ripple. On the other hand, the ripple injection circuit can generate the required ripple voltage internally using the switch output voltage in such a way that the ripple voltage is adjusted and the output voltage is not adversely affected.

  According to one aspect of the present invention, a ripple injection circuit includes a first capacitor and a first resistor inserted in series between a switch output voltage and a feedback voltage, and an output voltage and a feedback voltage. And a feed forward capacitor connected between the two. In one embodiment, the first capacitor and the first resistor are mounted on the integrated circuit of the buck switching voltage regulator together with the resistor voltage dividing circuit, and the feed forward capacitor is connected to the switching voltage. Externally connected to the regulator integrated circuit. In another embodiment, the feedforward capacitor is also incorporated into the switching voltage regulator integrated circuit. The feed forward capacitor, if installed, can be formed in the form of a capacitor with a capacitance value that can be programmed to select the desired capacitance for adjustment of the required amount of ripple to be generated.

  According to another aspect of the present invention, a backing switching voltage regulator using a constant on-time / variable off-time feedback control loop is a ripple injection circuit with improved accuracy, ie, a feedback control loop of a voltage regulator. A ripple injection circuit for injecting a ripple voltage signal at a point different from the feedback voltage node. With this configuration, an error in the output voltage is suppressed, and the accuracy of the output voltage is significantly increased. In one embodiment, the ripple injection circuit includes a gain stage that receives a feedback voltage, and the ripple voltage is injected into the output node of the gain stage. By using a gain stage to amplify the feedback voltage and injecting a ripple voltage signal at a point that bypasses the gain stage, voltage errors mixed in the adjusted output voltage can be greatly suppressed.

  In one embodiment, the ripple injection circuit includes a gain stage embodied in the form of an operational transconductance amplifier (OTA) that receives a feedback voltage and a first reference voltage. The ripple injection circuit further includes a first capacitor and a first resistor inserted in series connection between the switching output voltage and the output terminal of the OTA. The ripple injection circuit includes a feed forward capacitor inserted between the output voltage and the output terminal of the OTA. This ripple injection circuit with improved accuracy will be described in more detail.

FIG. 1 is a schematic diagram of a fixed on-time / minimum off-time buck switching voltage regulator incorporating a ripple injection circuit according to one embodiment of the present invention. Referring to FIG. 1, a buck switching voltage regulator system 10 includes a buck switching voltage regulator (hereinafter also referred to as “buck voltage regulator”) 100 connected to an output LC filter circuit. The buck voltage regulator 100 receives the input voltage _VIN and supplies the switch output voltage V _SW (terminal 104) to the output LC filter circuit including the inductor L1 and the output capacitor C _OUT . This output LC filter circuit produces a substantially constant magnitude DC output voltage _VOUT at the output voltage node 114. In an actual concrete circuit, the output voltage _VOUT is supplied to drive the load 116 as shown in FIG. The output capacitor C _OUT is accompanied by a specific value of ESR, as shown by the dotted series circuit in FIG. When an output capacitor having an ESR of zero is used, the resistance value of the ESR in FIG. 1 is zero, which is equivalent to a short circuit between both terminals of the resistor.

  The buck voltage regulator 100 embodies a fixed on-time / variable off-time reduction control loop. In this specification, the fixed on-time is also referred to as “constant on-time”. In the following description, the fixed on-time feedback control loop of voltage regulator 100 will be described first, and a ripple injection circuit for injecting a desired amount of ripple into the feedback control loop will now be described.

Referring to FIG. 1, the buck voltage regulator 100 receives an input voltage _VIN at a terminal 102. A pair of power switches M1 and M2 are connected in series between the terminal 102 and the ground potential terminal PGND106. In this circuit configuration, the voltage regulator 100 includes separate ground terminals PGND and SGND for noise separation between the power switch and other circuit portions. The use of a separate ground potential terminal connection for noise isolation is well known and not critical to the configuration of the present invention. In this embodiment, the power switch M1 is composed of a PMOS transistor, the power switch M2 is composed of an NMOS transistor, and these transistors are controlled by a drive signal from the drive circuit 134. The switch output voltage V _SW is obtained at the common connection node 122 of these power switches M1 and M2. The switch output voltage V _SW is supplied to an LC filter circuit composed of an inductor L1 and an output capacitor C _OUT via the SW terminal 104, and is filtered by this LC filter to produce a substantially constant amplitude DC output voltage V _OUT as an output voltage node. 114 occurs. This DC output voltage _VOUT is used for driving the load 116.

The DC output voltage V _OUT is fed back to the voltage regulator 100 so as to constitute a feedback control loop for adjusting the switch output voltage V _SW . More specifically, the output voltage _VOUT is fed back to the voltage dividing circuit composed of resistors R1 and R2 via the FB terminal 108. A feedback voltage V _FB (node 124), which is a divided output of the output voltage _VOUT , is added to the first input terminal (negative input terminal) of the comparator 126, and the second input terminal (positive input terminal) of the comparator 126. ) Is applied with a reference voltage V _REF (node 138). The reference voltage V _REF is generated by a reference voltage generation circuit 136 that receives the supply of the input voltage _VIN . The reference voltage generation circuit 136 is well known and can be constituted by any circuit that receives the input voltage _VIN and generates a voltage having a desired magnitude.

Comparator 126 produces an error voltage signal V _ERR representing the difference between feedback voltage V _FB and reference voltage V _REF . The output voltage signal V _ERR is supplied to the start input terminal of the on-timer 128 and to the logic circuit 132 so as to form a fixed on-time control loop. The on-timer 128 produces a predetermined on-duration duration when the start input signal is asserted, and produces an end output indicating the end of the predetermined on-time duration. When the feedback voltage V _FB falls below the reference voltage V _REF , the error signal V _{COMP_OUT} is asserted, and the on-time length programmed in the on-timer 128 is started. At the start of the on-time, the on-timer 128 supplies a control signal to the bus 129 to the logic circuit 132, causing the logic circuit 132 to switch the high-side switch M1 to the on state. As a result, the current through the inductor L1 can be built up. The high-side switch M1 remains on for a fixed time length. When the on-time length expires, the on-timer 128 instructs the logic circuit 132 to turn off the high-side switch M1 and turn on the low-side switch M2.

In order to realize the minimum off-time control, the end output signal from the on-timer 128 is supplied to the start input terminal of the off-timer 130. Therefore, when the on-time expires, the off-time length programmed in the off-timer 130 is started. The off timer 130 supplies an end output signal to the logic circuit 132 to indicate the end of the off time length, and at that time, the power transistor M1 can return to the on state if the feedback voltage V _FB is equal to or lower than the reference voltage. . In this way, the minimum on-time is realized in the feedback loop.

Through the operations of the comparator 126, the on-timer 128, and the off-timer 130, the logic circuit 132 generates a control signal to the driving circuit 134 so that the power switches M1 and M2 are alternately turned on and off to generate the switch output voltage _VSW. To do. In this embodiment, the feedback control loop is formed such that the ON time of the voltage regulator 100 can be adapted to different input voltages and different output voltages in order to keep the operating frequency constant.

FIG. 2 is a flow diagram illustrating the constant on-time / minimum off-time reduction control loop operation implemented in the switching voltage regulator system 10 of FIG. Referring to FIG. 2, the feedback voltage V _FB is compared with the reference voltage V _REF at the start of the operation of the feedback control loop (step 204). If the feedback voltage V _FB is less than or equal to the reference voltage V _REF , the control loop switches on the high side switch M1 and switches off the low side switch M2 for a fixed on time (step 206). After this fixed on-time, the high-side switch M1 is turned off for the minimum off-time, and the low-side switch M2 is turned on (step 208). Thereafter, the control loop returns to comparison step 204. If the feedback voltage V _FB is equal to or higher than the reference voltage V _REF , no switching is performed, the high-side switch M1 remains in the off state, and the low-side switch M2 remains in the on state. However, when the feedback voltage V _FB becomes equal to or lower than the reference voltage V _REF , the high-side switch M1 is turned on again for a fixed on-time (step 206). The control loop continues to operate to keep the feedback voltage V _FB above the reference voltage V _REF .

で与えられる。ここでConstTonは一定オン時間を表し、Contr.Toffはオフ時間を表す。上記一定オン時間が次式、すなわち
ConstTon ≒ 1/Vin （式２）
で与えられるとすると、スイッチ出力電圧の周波数はＶ_ＩＮの関数としてほぼ一定になる。用途によっては、スイッチ出力電圧の一定周波数が望ましい。 As shown in the flowchart of FIG. 2, the buck switching voltage regulator system 10 of FIG. 1 increases the off time from the minimum off time (min off) to the rated off time when the feedback voltage is equal to or higher than the reference voltage V _REF . Adjust the off-time. In continuous current mode, the operating frequency of this buck voltage regulator is stable and the duty cycle is:

Given in. Here, ConstTon represents a constant on-time, and Contr.Toff represents an off-time. The constant on-time is
ConstTon ≒ 1 / Vin (Formula 2)
, The frequency of the switch output voltage is approximately constant as a function of _VIN . Depending on the application, a constant frequency of the switch output voltage is desirable.

Returning to FIG. 1, back switching regulator 100 produces a ripple with a predetermined amount from the switching output voltage by cooperative operation of the feedforward capacitor C _FF, ripple feedback control loop of the switching regulator system 10 A ripple injection circuit 120 for injecting a voltage signal is included. By providing this ripple injection circuit and feedforward capacitor _CFF , the buck voltage regulator 100 of the present invention can be connected to the output capacitor _COUT regardless of the value of EST. That is, since a capacitor having zero ESR such as a ceramic capacitor can also be used as the output capacitor C _OUT , the ripple component of the output voltage _VOUT can be minimized. On the other hand, the ripple injection circuit and feedforward capacitor of the present invention operate to provide the necessary ripple in the feedback control loop. When a capacitor with a large ESR is used, the ripple injection circuit of the present invention does not require the generation of ripples and can be deactivated with a feedforward capacitor.

The ripple injection circuit 120 includes a first capacitor C _INJ and a resistor R _INJ inserted between the node 122 and the node 124 in series connection with each other. In one embodiment, one terminal of the first capacitor _{C INJ} connected to the switching output voltage node SW, connected to another terminal to the resistor _{R INJ,} and the resistor _{R INJ} capacitor _{C INJ}饋Connected to the feedback voltage V _FB (node 124). In another embodiment, the connection order of capacitor C _INJ and resistor R _INJ is reversed. The ripple injection circuit 120 cooperates with a voltage divider consisting of resistors R1 and R2 to produce a feedback voltage _VFB with a desired voltage level and a desired amount of ripple. In this voltage regulator, the ripple injection circuit 120 is connected to the switch voltage output node 122 so that a ripple voltage signal is generated from the switching output voltage V _SW . That is, the ripple voltage signal is a divided output signal of the switch output voltage V _SW, comprises a frequency of the voltage V _SW. The magnitude of the ripple voltage signal obtained at the feedback voltage V _FB node 124 is determined by the capacitance value of the feed forward capacitor C _FF . The feed forward capacitor C _FF is connected between the output voltage _VOUT node 114 and the feed forward (FFWD) terminal 110 of the voltage regulator 100. The FFWD terminal 110 is directly connected to the feedback voltage V _FB node 124. That is, the feedforward capacitor C _FF is connected between the output voltage V _OUT node 114 and the feedback voltage V _FB node 124.

This ripple voltage is divided by the capacitor C _INJ and the feed forward capacitor C _FF . The addition of the switch output voltage _{V SW} to the capacitor _{C INJ,} the capacitor _{C INJ} acts as a differentiating circuit. When the switching speed of the switch voltage V _SW is sufficiently high, the capacitor C _INJ acts as a short circuit. In this way, produce a ripple voltage signal switches the output voltage V _SW divides. In one embodiment, the peak value of the ripple voltage is about 20 mV.

The feed-forward capacitor C _FF is connected in parallel with the series-connected resistors R1 and R2, and forms a capacitive voltage dividing circuit in cooperation with the capacitor C _INJ . Therefore, the peak peak voltage of the ripple voltage signal is a function of the capacitance value of the feedforward capacitor _CFF . That is, the capacitance value of the feed forward capacitor C _FF is used to program the ripple injection circuit so that the voltage regulator 100 can operate with the output capacitor C _OUT having an arbitrary ESR value.

More specifically, the feedforward capacitor C _FF AC couples the output voltage _VOUT and the feedback voltage _VFB . When the capacitance of capacitor C _FF is very large, capacitor C _FF acts as a short circuit for the AC signal appearing at output voltage _VOUT node 114. That is, the ripple injection circuit is shorted by the large C _FF, ripple voltage signal to be injected into the feedback voltage V _FB node does not occur. Instead, the output voltage _VOUT including the ripple voltage component is applied to the voltage divider of the feedback control loop via the FB terminal 108. That is, the feedback voltage V _FB is generated from the output voltage signal _VOUT including the required ripple.

On the other hand, when the capacitance of the capacitor C _FF is very small or zero, the capacitor C _FF becomes an open circuit with respect to the AC signal appearing at the output voltage _VOUT node 114. In that case, the ripple signal generated in the ripple injection circuit including capacitor C _INJ and resistor R _INJ passes to feedback voltage V _FB node 124 and supplies the ripple maximum value to the feedback control loop.

In an actual concrete circuit, when the output capacitor C _OUT having a sufficiently large ESR is used, the ripple injection circuit 120 for generating the ripple voltage signal to the feedback control loop is not necessary. When the ripple voltage signal from the ripple injection circuit is not required, a feedforward capacitor _CFF having a large capacitance value is used, the capacitor C _INJ of the ripple injection circuit is substantially short-circuited, and the ripple voltage signal from the ripple injection circuit is The capacitor C _FF cancels out.

On the other hand, if an output capacitor C _OUT with very low or zero ESR is used, the ripple injection circuit 120 is used to generate the required ripple voltage signal to the feedback control loop. That is, a small feedforward capacitor C _FF capacity value, the ripple signal generated from the switching output voltage V _SW by the ripple injection circuit 120 is used in order to allow passage to the feedback voltage node 124.

As described above, the feedforward capacitor C _FF operates to adjust the magnitude of the ripple voltage to be supplied from the ripple injection circuit 120. In one embodiment, the capacitance value of the feedforward capacitor _{C FF} is in the range of 220pF to 2.2uF. Then, the voltage regulator 100 can operate with an output capacitor having an arbitrary ESR value simply by selecting a corresponding capacitance value of the feedforward capacitor. In addition to configuring a ripple injection circuit and a capacitive voltage divider circuit, the feedforward capacitor improves the stability of the transient response characteristic by introducing zero in the feedback control loop.

Furthermore, since the ripple voltage signal generated by the ripple injection circuit is an AC version of the switch output voltage V _SW to the inductor L1, the ripple voltage signal is proportional to the input voltage _VIN . From the viewpoint of control loop stability, a larger ripple is desirable, but from the viewpoint of accuracy (load adjustment, output voltage ripple), the input voltage needs to be minimized so as to minimize the effect of fluctuations. There is.

In this embodiment, so that use mutual adjustment of the ESR characteristics of the output capacitor C _OUT mutually different capacitance value of the externally connecting to feedforward capacitor feedforward capacitor C _FF in IC back regulator. That is, the magnitude of the injected ripple voltage can be finely adjusted by the capacitance of the feedforward capacitor _CFF . However, in other embodiments, both the ripple injection circuit and the feed forward capacitor C _FF can be incorporated into the voltage regulator IC to reduce the external components of the system 10. When incorporated in such an IC, the feedforward capacitor _CFF has a capacitance value suitable for a predetermined range of the ESR value of the output capacitor.

The buck voltage regulator of this invention including a ripple injection circuit and a feed forward capacitor has a number of advantages over conventional ones. For example, in one conventional technique, a residual value having a very small ripple voltage is amplified in order to generate a ripple voltage from the output voltage _VOUT . If the ripple voltage signal is actually very small, it is very difficult to duplicate the ripple or discriminate the ripple signal from the noise signal. In contrast, the ripple injection circuit of the present invention generates a ripple signal from the switch output voltage. Therefore, a simple circuit can be used to divide the switch output voltage, and this ripple signal can be generated without the influence of noise.

[Improvement of output voltage accuracy]
In the buck voltage regulator of FIG. 1, the DC output voltage _VOUT is a voltage having almost a constant magnitude and almost no voltage ripple. The ripple voltage signal from the ripple injection circuit 120 is injected at the negative feedback voltage V _FB node 124. Since the control loop formed by this ripple injection circuit has a small gain, its accuracy is limited. In operation, the average DC voltage (intermediate value) of the ripple voltage signal must be equal to the comparator reference voltage V _REF . However, when a ripple voltage is injected into the feedback voltage V _FB , the average DC voltage of the ripple signal deviates from the reference voltage V _REF due to various factors such as a delay in switching on the high-side switch. As a result, the output voltage _VOUT includes a DC offset voltage component, which affects the operation accuracy of the buck voltage regulator.

で与えられる。 FIG. 3 is a waveform diagram of the feedback voltage V _FB of the constant on-time voltage regulator of FIG. Referring to FIG. 3, the waveform 190 of the feedback voltage V _FB including the injection ripple is shown. The waveform diagram of FIG. 3 is shown assuming that the “on” resistance of the power switch is zero. At the time zero, the high-side switch M1 is turned on through the constant on-time t _ON. The peak-to-peak value ΔV ₁ of ripple is:

Given in.

で与えられる。 When the high-side switch is turned off after the fixed on-time has elapsed, the feedback voltage _VFB decreases. When the feedback voltage V _FB decreases to the level of the reference voltage V _REF (line 194), the high-side switch M1 is turned on again after the propagation delay t _delay . The magnitude ΔV ₂ at which the feedback voltage V _FB drops below the reference voltage V _REF is expressed by the following equation:

Given in.

Due to the delay in switching on the high-side switch, the average feedback voltage AVG_V _FB (line 192) deviates from the reference voltage V _REF (line 194). The average feedback voltage AVG_V _FB and the reference voltage difference between the error voltage _{V ERR2} between _{V REF,} that is, the error voltage _{V ERR2} given by ₁ / 2ΔV 1 -ΔV _2. The error voltage V _ERR2 is multiplied by the feedback voltage division ratio to calculate the error of the output voltage _VOUT . Therefore, the residual DC voltage error that appears in the output voltage V _OUT is (V _OUT / V _REF ) times the error that appears as a voltage error at the feedback terminal. As a result, the output voltage _VOUT has an enlarged voltage error, and the accuracy is lowered. For example, when the error voltage V _ERR2 is 10 mV, the output voltage _VOUT is 1.8 V, and the reference voltage V _REF is 0.9 V, the residual DC voltage error appearing in the output voltage is 10 mV × (1.8 / 0.9 ) = 20 mV, and an offset of 20 mV is generated in the output voltage _VOUT .

Furthermore, since the time lengths Δt _ON and t _delay are mutually independent parameters, the accuracy of the DC output voltage _VOUT decreases. Further, the voltages ΔV ₁ and ΔV ₂ fluctuate according to the input voltage _VIN and the output voltage _VOUT , and adversely affect the voltage adjustment function. Also, in an actual specific configuration, the “on” resistance is not zero. Therefore, the output voltage V _OUT varies depending on the size of the load. These factors reduce the accuracy of the adjusted output voltage _VOUT , leading to undesirable results.

  According to another aspect of the present invention, a buck switching type voltage regulator using a constant on-time / variable off-time control loop has a ripple injection circuit with high accuracy, that is, a feedback control loop of a voltage regulator. A ripple injection circuit for injecting a ripple voltage signal at a point different from the feedback voltage node is incorporated. FIG. 4 is a schematic diagram of a constant on-time voltage regulator incorporating a ripple injection control scheme with increased output voltage accuracy according to one embodiment of the present invention. Among the components shown in FIG. 4, those common to the components shown in FIG. 1 are shown in the same drawing with common reference numerals for the sake of simplicity of explanation.

Referring to FIG. 4, the buck switching voltage regulator system 40 includes a buck switching voltage regulator (buck voltage regulator) 400 connected to the output LC filter circuit. The buck voltage regulator 400 receives the input voltage _VIN and supplies the switching voltage V _SW (terminal 404) to the output LC filter circuit including the inductor L1 and the output capacitor C _OUT . The output LC filter circuit produces a substantially constant magnitude DC output voltage _VOUT at the output voltage node 414. In an actual implementation circuit, the output voltage _VOUT is supplied to drive the load 416 as shown in FIG. The output capacitor C _OUT is accompanied by a value of ESR, ie, the resistance ESR shown in dotted lines as being inserted in series with this capacitor. When an output capacitor with ESR set to zero is used, the ESR resistance value becomes zero, which is equivalent to a short circuit.

  The buck voltage regulator 400 embodies a constant on-time / variable off-time reduction control loop. The operation of the constant on-time feedback control loop of the buck voltage regulator 400 is the same as that of the buck voltage regulator 100 of FIG. The buck voltage regulator 400 includes a ripple injection circuit 420 that increases output voltage accuracy. The configuration and operation of the ripple injection circuit 420 that injects a desired amount of ripple into the feedback control loop to increase output voltage accuracy will now be described.

The back-switching voltage regulator 400 cooperates with the feedforward capacitor C _FF to produce a certain amount of ripple from the switching output voltage and inject the ripple voltage signal into the feedback control loop of the buck-switching voltage regulator system 40. A moving ripple injection circuit 420 is included. More specifically, the ripple injection circuit 420 injects the ripple voltage signal at a point different from the point where the feedback voltage V _FB occurs in the feedback control loop. As a result, as described later, the influence of the voltage error on the output voltage _VOUT due to the ripple voltage signal is greatly reduced.

The ripple injection circuit 420 includes an amplifier 450 inserted between the feedback voltage node 424 of the buck voltage regulator 400 and the error comparator 426. The amplifier 450 is connected so that the feedback voltage _VFB is received at the non-inverting input terminal and the reference voltage _VREF is received at the inverting input. Amplifier 450 produces an output voltage V _X at output terminal 452 that represents the difference between feedback voltage V _FB and reference voltage V _REF . More specifically, the output voltage V _OUT at node 414 is generated at the output node 424 of the voltage divider comprising resistors R1 and R2 via feedback terminal (FB) 408. The feedback voltage V _FB , which is a divided output of the output voltage _VOUT , is compared with the reference voltage V _REF by the amplifier 450 to generate the output voltage V _X.

This output voltage V _X is supplied to the inverting input terminal of the error comparator 426 and compared with the second reference voltage V _REF2 to the non-inverting input terminal of the comparator 426. Reference voltage generator 436 generates reference voltages V _REF and V _REF2 . The second reference voltage V _REF2 is a DC voltage selected to bias error comparator 426 and amplifier 450 to the appropriate common mode level. The error comparator 426 evaluates the difference between the output voltage V _X and the second reference voltage V _REF2 and generates an output voltage signal V _{COMP_OUT} representing the difference between the two. The output voltage V _{COMP_OUT} is supplied to the control circuit 432 to complete the constant on-time / variable off-time control loop of the buck voltage regulator 400. The control circuit 432 includes a control logic circuit as well as a timer for realizing a constant on-time / variable off-time reduction control loop.

  In this embodiment, amplifier 450 is an amplifier with a high output impedance, such as a transconductance (Gm) amplifier. The amplifier 450 is an amplifier having a high DC gain but an AC gain of 1. In one embodiment, amplifier 450 comprises an operational transconductance amplifier (OTA) with high output impedance and low Gm. When the output impedance of the amplifier 450 is high, the amplifier enables feed forward transmission of the injected ripple voltage signal from its amplifier output terminal to the error comparator. If the amplifier 450 is embodied as OTA, the buck switching voltage regulator system 40 adds the good transient response characteristics obtained with the switching voltage regulator system 10 and the stability of the feedback control loop. Can be maintained without the need for an amplifier. The low Gm OTA operates to increase only the gain at a very low frequency, and has a gain of 1 at a high frequency without impairing phase preservation.

The ripple injection circuit 420 includes a resistor R _INJ and a first capacitor C _INJ inserted in series connection between the switching output voltage V _SW (node 422) and the output terminal 452 of the amplifier 450. The feedforward FFWD terminal 410 of the buck voltage regulator 400 is also connected to the output terminal 452 of the amplifier 450. The output terminal 452 of the amplifier 450 becomes a ripple injection node of the feedback control loop, and the ripple injection node 452 is independent of the feedback voltage node 424. The output impedance of the amplifier 450 is high, thereby allowing the ripple voltage signal to be injected into the input terminal 452 of the ripple voltage signal. When the feed forward capacitor C _FF is connected between the output voltage V _OUT (node 414) of the back voltage adjustment 100 and the feed forward FFWD terminal 410, the feed forward capacitor C _FF is connected to the output voltage V _OUT (node 414). And the ripple injection node 452. If the ripple signal occurs in the ripple injection node 452, the amount of the ripple signal is determined by the capacitance value of the feedforward capacitor C _FF.

The ripple injection circuit 420 is connected to the switching output voltage node 422 so that a ripple voltage signal is generated from the switching output voltage _VSW . That is, the ripple voltage signal is a divided output of the switching output voltage V _SW, having a switching frequency of the switching output voltage. By including the ripple injection circuit and the feedforward capacitor C _FF, back voltage regulator 400 of the invention can be connected to the output capacitor C _OUT with any ESR. That is, a zero ESR capacitor such as a ceramic capacitor can be used as the output capacitor C _OUT to minimize the ripple voltage at the output voltage _VOUT . On the other hand, the ripple injection circuit and feedforward capacitor of the present invention operate to supply the necessary ripple to the feedback control loop. When a capacitor having a large ESR is used, the ripple injection circuit of the present invention does not require the generation of ripple, and can be deactivated by the feedforward capacitor _CFF .

The ripple voltage signal generated by the ripple injection circuit 420 depends on the resistance value of the resistor R _INJ , the capacitance value of the capacitor C _INJ , and the capacitance value of the feedforward capacitor C _FF . Resistor R _INJ and capacitor C _INJ act as a low pass filter, _producing a ripple voltage at node 452 capacitively _divided by capacitor C _INJ and capacitor C _FF . More specifically, the magnitude of the ripple voltage signal is given by the formula (ON time) * (V _IN −V _OUT ) / R _INJ / (C _INJ + C _FF ). In this way, the switching output voltage _VSW is divided to generate a ripple voltage signal. In one embodiment, the peak value of this ripple voltage is about 20 mV.

The feedforward capacitor C _FF forms a capacitive voltage divider together with the capacitor C _INJ . That is, the peak peak voltage value of the ripple voltage signal is a function of the capacitance value of the feedforward capacitor _CFF . Therefore, the capacitance value of the feedforward capacitor C _FF is used to program the ripple injection circuit so that the buck voltage regulator 400 can cooperate with the output capacitor C _OUT with any ESR value. More particularly, inserted in an AC coupling between the output voltage _{V OUT} and the voltage _{V X} feedforward capacitor _{C FF.} If the capacitance of capacitor C _FF is very large, capacitor C _FF becomes a short circuit for the AC signal to output voltage _VOUT node 414. Therefore, the ripple injection circuit is short-circuited by the large-capacity feedforward capacitor _CFF , and the ripple signal generated by the ripple injection circuit is not injected into the ripple injection node 452. Instead, the output voltage _VOUT including the ripple voltage component is supplied to the voltage divider of the feedback control loop via the FB terminal 408. Accordingly, the feedback voltage V _FB is generated from the output voltage signal _VOUT containing the required ripple.

On the other hand, when the capacitance value of the capacitor C _FF is very small or zero, the capacitor C _FF becomes an open circuit for the AC signal appearing at the output voltage _VOUT node 114. In this case, the ripple signal generated by the ripple injection circuit of capacitor C _INJ and resistor R _INJ goes to ripple injection node 452 and supplies the maximum value of ripple to the feedback control loop.

Therefore, in an actual implementation circuit, if an output capacitor C _OUT having a sufficiently large ESR value is used, the ripple injection circuit 420 for an arbitrary ripple voltage signal to the feedback control loop becomes unnecessary. When the ripple voltage signal from the ripple injection circuit becomes unnecessary, a feedforward capacitor C _FF having a large capacitance value is used, the effect of the capacitor C _INJ of the ripple injection circuit is short-circuited by the capacitor C _FF , and the ripple generated by the ripple injection circuit is generated. to cancel the signal in the feedforward capacitor _{C FF.}

On the other hand, when using the output capacitor C _OUT whose ESR is very small or zero, the supply of the ripple voltage signal necessary for the feedback control loop depends on the ripple injection circuit 420. In this case, the ripple injection circuit 420 transmits the ripple signal generated from the switching output voltage V _SW to the ripple injection node 452 using the feedforward capacitor C _FF having a small capacitance value. In this way, the feedforward capacitor C _FF acts to adjust the magnitude of the ripple voltage supplied from the ripple injection circuit 420. In one embodiment, the capacitance value of the feed forward capacitor C _FF is in the range of 220 pF to 2.2 u F.

  As described above, the buck voltage regulator 400 can cooperate with an output capacitor having an arbitrary ESR value simply by selecting a capacitance value corresponding to the feedforward capacitor. The ripple injection circuit 420 in the buck voltage regulator 400 brings about the same advantages as the above-mentioned advantages of the ripple injection circuit 420 in the buck voltage regulator 100, so that further explanation of the advantages is omitted.

As shown in the above configuration, the ripple injection circuit 420 is a modification of the feedback control loop of the buck voltage regulator 400. In operation, when the voltage V _X drops below the reference voltage V _REF2 , the high side switch M1 is turned on for a certain on time t _ON . After the fixed on-time t _ON has elapsed, the high-side switch M1 is turned off and the low-side switch M2 is turned on for at least the minimum off time. When the voltage _{V X} drops below the reference voltage _{V REF2,} the high-side switch M1 is switched on again. A ripple injection circuit 420 injects a ripple voltage signal into the output voltage V _X of the amplifier 450. That is, this ripple voltage is injected at a stage after the gain stage of the amplifier 450.

As with the back voltage regulator, the voltage waveform of voltage V _{X at} the input of error comparator 426 is subject to voltage V _REF2 and varies with input voltage V _IN , output voltage _VOUT and load current. However, the less accurate comparator input is moved to the ripple injection node 452 rather than the feedback voltage node 424. The resulting voltage error at the feedback voltage node 424 is equal to the voltage error at the ripple injection node divided by the gain of the amplifier 450. By inserting the gain stage of the amplifier 450, the DC error in the output voltage _VOUT is greatly suppressed. More specifically, the offset error at the feedback voltage node is 1 / A times the offset error of the average DC voltage of voltage V _X (where A is the DC gain of amplifier 450). The DC error associated with the output voltage C _OUT becomes a value greatly reduced by the DC gain of the amplifier 450, and as a result, the output voltage can be adjusted for high accuracy. In one embodiment, amplifier 450 has a DC gain A of 600 or greater. Therefore, when the error voltage V _ERR2 is 10 mV, the residual DC voltage error appearing in the output voltage _VOUT is only 16 μV, achieving a significant reduction in error and a significant improvement in accuracy.

[Alternative example]
Depending on the application, the buck-switching voltage regulator system 40 may be applicable for operation in discontinuous conduction mode (DCM). In DCM, the low-side switch M2 is not allowed to conduct current in the reverse direction. If the current is in the opposite direction, by switching off the low-side switch M2, supplied to a voltage V _X of the load current in the output capacitor falls below the reference voltage V _REF2, the high-side switch M1 at the time again Try to switch it on.

However, when the load is very light, the feedback voltage V _FB can be higher than the reference voltage V _REF for a long time. During that period the amplifier 450 pulls the voltage _{V X} to a much higher level than the voltage _{V REF.} Next, the abrupt change in the load occurs, the voltage V _X, before feedback control loop is switched on again the high-side switch, it is necessary to decrease significantly. According to an alternative embodiment of the present invention, the transient response characteristic of a buck voltage regulator operating with DCM during load condition variations by adding a clamp circuit to the ripple injection circuit to limit variations in voltage V _X To improve.

FIG. 5 is a schematic diagram of a constant on-time voltage regulator incorporating an improved output voltage accuracy ripple injection control scheme according to an alternative embodiment of the present invention. For simplicity of explanation, the components in FIG. 5 that are the same as those in FIG. 4 are shown with common reference numerals. Referring to FIG. 5, the buck voltage regulator 500 in the buck switching voltage regulator system 50 has the same configuration as the buck voltage regulator 400 of FIG. 4 except that a clamp circuit 560 is added. Therefore, the operation of the buck voltage regulator 500 is the same as that of the buck voltage regulator 400 except for the clamping operation, and will not be described in detail. The clamp circuit 560 is connected to the ripple injection node 552 and limits the voltage V _{X of the} node 552 to a value higher than the reference voltage V _REF2 by ΔV _X. Therefore, the voltage V _X does not exceed V _REF2 + ΔV _X even in the light load operation state. When the load fluctuates, the voltage V _X drops by ΔV _X before the feedback control loop operates to turn on the high side switch. In one embodiment, this ΔV _X value is about 15 mV.

In the embodiment shown in FIGS. 4 and 5, the feedforward capacitor C _FF is externally attached to the integrated circuit of the buck voltage regulators 400 and 500, so that the ESR characteristic of the output capacitor C _OUT can be matched. Capacitor _CFF capacity value can be selected. The size of the injection ripple voltage can be finely adjusted by the feed-forward capacitor C _FF in the configuration described above. However, in other embodiments, to reduce the number of external components back switching regulator system 40 and 50, the incorporation of both the ripple injection circuit and the feedforward capacitor C _FF to back voltage regulator integrated circuit You can also. If incorporated, the capacitance value of the capacitor C _FF is a value matching the value of a range of ESR values of the output capacitor.

Also, in the embodiment shown in FIGS. 4 and 5, a ripple injection circuit including amplifiers 450 and 550 and a voltage divider consisting of resistors R1 and R2 is integrated into the integrated circuit of the buck voltage regulators 400 and 500. It is shown by. Further, the clamp circuit 560 is shown in an integrated form with the integrated circuit of the buck voltage regulator 500. In these embodiments, one or more components of the ripple injection circuit may be external to the buck voltage regulator integrated circuit. The amount of circuit elements to be incorporated into a single integrated circuit is a design choice. The implementation of the ripple injection circuit of the present invention is not limited to a particular degree of integration. In one embodiment, the voltage divider R1 / R2 and the OTA are externally attached to the integrated circuit of the buck voltage regulator. Any one of these voltage dividers R1 / R2, feedforward capacitor C _FF , operational transconductance amplifier, injection capacitor C _INJ , injection resistor R _INJ, and clamp circuit is externally or internally attached to the buck voltage regulator integrated circuit. Can be connected with The degree of circuit integration is not critical to the practice of this invention.

FIG. 6 is a circuit diagram of an operational transconductance amplifier and clamp circuit that can be incorporated into the constant on-time voltage regulator of FIGS. 4 (no clamp circuit) and FIG. 5 according to one embodiment of the present invention. Referring to FIG. 6, the transistors M1, M2, M3 and M4 constitute the operational transconductance amplifier (OTA) 600 which receives the output voltage _{V X} receives a feedback voltage _{V FB} and the reference voltage _{V REF.} OTA600 comprises a high output impedance at the output node 602 to allow the injection of ripple voltage signal to the output voltage V _X.

In FIG. 6, the OTA 600 is shown with a clamp circuit 620 incorporated therein. The clamp circuit 620 is optional and is not used in the specific circuit of the OTA of FIG. Clamp circuit 620, when the clamping of the output voltage V _X as shown in the embodiment of FIG. 5 are required, incorporate the OTA. The clamp circuit 620 includes an amplifier 622 that compares the output voltage V _X with the clamp voltage V _clamp . The output signal from the amplifier 622 is supplied to the base terminal of the NPN bipolar transistor Q1. Transistor Q1 is connected between a ground potential point and the node 602 of the output voltage _{V X,} to maintain the output voltage _{V X} in clamp voltage _{V clamp.} In one embodiment, the clamp voltage V _clamp is set to V _REF + ΔV _X. FIG. 7 is a circuit diagram of a clamp circuit that can be used to implement the clamp circuit 620 of FIG.

[Multi-mode on / off time control]
In the above-described buck voltage regulator, the constant on-time control / variable off-time control scheme is applied to the switching operation control of the high-side switch and the low-side switch. More specifically, the constant on-time given by equation (2) above is a function of the input voltage _VIN . The operating frequency of the buck voltage regulator is stable while the duty cycle varies as the off time is adjusted to increase from the minimum off time. In this operating state, even if the feedback voltage V _FB becomes equal to or lower than the reference voltage V _{REF at} the end of the constant on-time, the high-side switch is turned off, and the low-side switch is turned on again. Switch on for the previous minimum off time. The minimum off-time is necessary to sufficiently secure the setup time of the control circuit, particularly the time required for setup of the error comparator. In some cases, it may be desirable to keep the high side switch on until the feedback voltage reaches the reference voltage.

Also, although the buck voltage regulator reaches a duty cycle of 100% under ideal conditions, the need for the minimum on-time places a limit on the duty cycle of the buck voltage regulator duty cycle. In addition, the delay associated with switching the switch on and switching off also limits the duty cycle. Further, when current detection is required for the low-side switch as in the current limiting mode or the discontinuous conduction mode, sufficient time must be given to ensure the current detection function. The maximum duty cycle value D _max achievable in that case is given by:
_{D max = t on / (t} on + t off, min)
Limited to

While it is possible to increase the duty cycle by increasing the on-time t _on, it is possible that results in increased on-time t _on is undesirable. First, increasing on time results in increased inductor current ripple and is not always practical. Second, the on-time cannot be too long. Although the on-time can be extended until the feedback voltage V _FB becomes equal to or higher than the reference voltage V _REF , such a state can directly lead to an inconvenient result, particularly when there is a short circuit. In the short-circuit state, the feedback voltage cannot rise above the reference voltage, the high-side switch cannot be switched off, and the inductor current becomes extremely large. Finally, if the on-time is extended too much, the transient response characteristics deteriorate. Assume that the load current increases rapidly from a small value to a large value. Since the sudden increase in current reduces the feedback voltage V _FB to a value below the reference voltage V _REF , the voltage regulator loop tries to make the on time t _on as long as possible. If the on-time t _on is extended too much, the inductor current will be much larger than the load current, due to the energy stored in the inductor when the high-side switch is turned off and the low-side switch is turned on. As a result, the output voltage exceeds the target value.

  According to one aspect of the present invention, the buck switching voltage regulator embodies a multi-mode on-time / off-time control scheme for realizing a constant on-time / variable off-time control loop. This multi-mode on-time / off-time control scheme can be incorporated into the buck switching voltage regulator of FIGS. 1, 4 and 5 to allow high duty cycle operation of the buck switching voltage regulator. . FIG. 8 is a logic diagram of an on-time / off-time control circuit that embodies a multi-mode on-time / off-time control scheme in a buck switching voltage regulator according to one embodiment of the present invention. In one embodiment, the on-time control circuit 800 is configured to include the logic circuit 132 of the buck voltage regulator 100 or the buck voltage regulators 400 and 500 to implement the multi-mode on-time / off-time control scheme according to the present invention. The control circuits 432 and 532 are embodied. FIG. 8 merely illustrates the logical relationship between the different operation signals and the timer of the on-time control circuit, and is not intended to illustrate the literal realization of the on-time control circuit. Those skilled in the art who have touched the above description will appreciate that the on-time control circuit can be implemented in a variety of ways through the use of a variety of circuit elements.

Referring to FIG. 8, an on-time control circuit 800 includes a first logic circuit 810 that generates a Top_Switch_On signal that switches a high-side switch on, and a second logic circuit 820 that generates a Top_Switch_Off signal that switches a high-side switch off. including. The operation of this multi-mode on-time / off-time control scheme is as follows. The first logic circuit 810 asserts the Top_Switch_On signal when the feedback voltage V _FB is equal to or lower than the reference voltage V _REF and reaches the minimum off time. If the Normal_Off signal is asserted or the Force_Off signal is asserted with the high-side switch turned on, the Top_Switch_Off signal is asserted. When the minimum on time t _{on_min} is reached or the feedback voltage V _FB becomes equal to or higher than the reference voltage V _REF , the Normal_Off signal is asserted. In this way, the high-side switch is turned on for at least the minimum on time t _{on_min} and remains on until the feedback voltage V _FB is greater than or equal to the reference voltage V _REF . However, the on-time control circuit 800 imposes two maximum on-time limits on the high side switch. When the maximum on time t _{on_max1} or the maximum on time t _{on_max2} is reached, the Force_Off signal is asserted. When the Force_Off signal is asserted, the Top_Switch_Off signal is asserted, and the high-side switch is turned off regardless of the value of the feedback voltage _VFB . That is, when the Force_Off signal is asserted, the high-side switch is turned off even if the feedback voltage V _FB is equal to or lower than the reference voltage.

The two maximum on-time limits act to set a first maximum on-time t _{on_max1} and a second extended maximum on-time t _{on_max2} . The second maximum on-time t _{on_max2} is longer than the first maximum on-time t _{on_max1} . In operation, the first maximum on-time t _{on_max1} is applied, but under certain conditions it is allowed to extend the on-time to the second on-time t _{on_max2} . As further described below, the first maximum on-time t _{on_max1} is selected when the off-time in the preceding switching cycle is not the minimum off-time, and the second extended maximum on-time t _{on_max2} is selected in the preceding switching cycle. Select when the off time is the minimum off time.

The operation of the multimode on-time / off-time control scheme is as follows. When the duty cycle is low or medium, the on-time control circuit embodies a constant on-time and controls the off-time of the high-side switch so as to realize the voltage adjustment operation. When the duty cycle is high, the off time is fixed to the minimum off time, and the on time is controlled by the on time control circuit so as to realize the voltage adjustment operation. With the above limit value, the maximum duty cycle t _{on, max} / (t _{on, max} + t _{off, min} ) is realized. This maximum duty cycle is close to 100% when t _{on, max} is selectively allowed to be extended to a large value under specific conditions. The maximum on-time extension is realized using two maximum on-times including a large second maximum on-time.

FIG. 9 is a schematic diagram of a maximum on-time control circuit according to one embodiment of the present invention. Referring to FIG. 9, the maximum on-time control circuit 900 generates a Force_Off signal when the first maximum on-time t _{on_max1} or the second maximum on-time t _{on_max2} has elapsed. In the maximum on-time control circuit 900, a first maximum on-time t _{on_max1} is set by a first timer circuit including a capacitor C _X , a current source 960, and an NMOS transistor M11. In operation, when the high-side switch is switched off (Top_Switch_Off signal is asserted), the transistor M11 is switched on and discharges the capacitor _CX . At that time, the voltage V _TMAX of the node 962 is at or near the ground potential. The comparator 940 compares the voltage V _TMAX of the capacitor C _X (node 962) with the DC voltage V _DC . When the voltage V _TMAX is lower than the DC voltage V _{DC, the} comparator 940 generates a logic low Force_Off signal.

When the Top_Switch_Off signal is deasserted and the high side switch is turned on, the transistor M11 is turned off, allowing the current source 960 to charge the capacitor _CX . When the voltage V _{TMAX at} the upper terminal (node 962) of the capacitor _CX reaches the voltage _VDC , the state of the comparator 940 switches and produces a Force_Off signal at a logic high level. A logic high level of the Force_Off signal indicates that the Force_Off signal is asserted, and thus the Top_Switch_Off signal is asserted. In this way, the capacitance of the capacitor _{C X,} that is, sets the maximum on-time _{t on, max1} time is first to charge the capacitor _{C X} to the voltage _{V DC.}

According to one embodiment of the present invention, the maximum on-time control circuit 900 sets a second or extended maximum on-time t _{on, max2} under certain conditions. Under these conditions, the maximum on-time is allowed to extend beyond the first maximum on-time t _{on, max1} if the minimum off-time was used in the previous switching cycle. To enable it, the maximum on-time control circuit 900 operates to add a capacitor _CY to the capacitor C _X in parallel when the minimum off-time has been used in the preceding switching cycle. Includes a timer circuit. The sum of the capacitances of capacitor C _Y and capacitor C _X increases the time to charge the capacitor voltage V _TMAX to DC voltage V _DC , thereby extending the maximum on-time to t _on, max 2. If the off time is longer than the minimum off time in the preceding switching cycle, the maximum on time is not extended and the maximum on time determined by the capacitor _CX is maintained.

The configuration and operation of this second timer circuit will now be described with reference to FIG. 9 and FIG. 10 which is a related timing diagram. The second timer circuit includes a monostable circuit 970 that receives a signal t _{off, min_reached} that is asserted when the minimum off-time is reached. The monostable circuit 970 generates a pulse t _{off, min_reached} (waveform 1004). An AND gate 972 takes the logical product of this pulse t _{off, min_reached} and the Top_Switch_On signal indicating the switching of the high-side switch to ON. Therefore, when the high side switch is turned on simultaneously with the pulse t _{off, min_reach} , the switch represents that the minimum off time has been used in the preceding switching cycle. Therefore, the output of AND gate 972 is asserted. If the high side switch does not turn on at the end of the minimum off time, the output of the AND gate 972 is not asserted.

The output of the AND gate 972 is applied to the set input terminal S of the flip-flop circuit 974. On the other hand, the Top_Switch_Off signal is applied to the reset input terminal R of the circuit 974. The Increase_ton _{, max} signal _, which is the output Q of the circuit 974, is applied to the gate terminal of the NMOS transistor M12. Drain terminal of the NMOS transistor M12 is connected to node 962, a source terminal is connected to the capacitor _{C Y.} When Increase_t _{on, max} signal is asserted, transistor M12 is switched on to connect in parallel a capacitor _{C Y} to the capacitor _{C X.} When the Increase_ton _{, max} signal is not asserted, the transistor M12 is turned off.

The Increase_ton _{, max} signal is asserted when the output of the AND gate 972 is asserted and the output Q of the flip-flop circuit 974 becomes a logic high level. When the Top_Switch_Off signal is asserted, the output Q of the flip-flop circuit 974 is reset to a logic low level. If neither the set input nor the reset input of circuit 974 is asserted, output Q remains in its previous logic state.

The operation of the second timer circuit is as follows. When the minimum off-time is reached (time A), the t _{off, min_reached} signal is asserted and the monostable circuit 970 produces a pulse t _{off, min_reached} (waveform 1004). Next, when the Top_Switch_On signal is asserted and the high-side switch is simultaneously turned on (time point A), the output of the AND gate 972 is asserted. Therefore, the flip-flop circuit 974 is set and the Increase_ton _{, max} signal (waveform 1006) is asserted. As a result, transistor M12 is switched ON, the capacitor C _Y is a longer maximum on-time is connected in parallel to the capacitor C _X. Due to the pulse t _{off, min_reached} , the output of the AND gate 972 is applied to the set input S of the circuit 974 for the duration of the pulse. However, the Increase_ton _{, max} signal remains asserted until the Top_Switch_Off signal is asserted (time point B) until the Increase_ton _{, max} signal is reset.

On the other hand, in the next switching cycle, when the Top_Switch_On signal is not asserted (time point C) although the minimum off-time is reached, the AND gate 972 has no output, and the Increase_ton _{, max} signal remains in the reset state. . That is, if the minimum off-time has been reached but the high-side switch has not been turned on, the maximum on-time control circuit 900 determines that there was no minimum off-time in the preceding switching cycle. In that case, it is not necessary to extend the maximum on-time.

The maximum on-time control circuit 900, when embodied in a buck voltage regulator, provides various advantages for improving the operation of the voltage regulator. First, the maximum on-time control circuit 900 provides two maximum on-times, namely a first maximum on-time t _{on_max1} and a second, ie extended maximum on-time t _{on_max2} . The extended maximum on-time is provided only for conditions requiring a higher duty cycle. That is, the extended maximum on-time is provided only if the preceding switching cycle uses the minimum off-time. When the duty cycle is low or moderate, the buck voltage regulator is not affected by the two maximum on-times. That is, this control loop controls an off time longer than the minimum off time t _{off, min} . If the duty cycle is higher, the buck voltage regulator starts the voltage regulation operation by controlling the on time t _on using the minimum off time t _{off, min} . In that region, the on-time t _on is normally extended until the feedback voltage V _FB reaches the reference voltage V _REF before reaching the maximum on-time t _{on, max1} . However, as the duty cycle continues to increase, the required on-time becomes greater than the first maximum on-time t _{on, max1} . In order to allow a higher duty cycle, a second or extended maximum on-time t _{on, max2} is used under certain conditions. Since the maximum on time t _{on, max} is extended only when the preceding switching cycle uses the minimum off time, transient overshoot is avoided. During the transient state, the maximum on-time is not extended because the off-time is usually longer than the minimum off-time.

FIG. 11 is a schematic diagram of a maximum on-time control circuit according to an alternative embodiment of the present invention. Referring to FIG. 11, the maximum on-time control circuit 1100 has the same configuration as the above-described maximum on-time control circuit 900, but a protection circuit against a short-circuit state is added. More specifically, the maximum on-time control circuit 1100 is configured to disable the maximum on-time extension operation when a short circuit condition occurs. That is, when a short circuit condition occurs, the output current reaches the current limit value. In the maximum on-time control circuit 1100, a Not_In_Current_Limit signal is sent to the AND gate 1172, and a logical product between the pulse t _{off, min_reached} and the pulse Top_Switch_On is obtained. Therefore, in addition to the above two states (when the minimum off time is reached and when the high-side switch is turned on), the AND gate 1172 outputs its output only when the output current is not subject to current limitation. 1174 can be sent to the set input terminal to indicate that there is no short circuit at the output of the buck switching voltage regulator. In this way, the extension of the maximum on-time is avoided when the short-circuit state is detected in the switching voltage regulator.

  The detailed description set forth above is intended to be illustrative of particular embodiments of the invention and is not intended to be limiting. Many variations and modifications are possible within the scope of the invention. In other words, the present invention is defined only by the claims of the appended claims.

  It can be used to manufacture switching voltage regulators with improved performance at low cost.

1 is a schematic diagram of a fixed (constant) on-time voltage regulator incorporating a ripple injection control scheme according to one embodiment of the present invention. FIG. FIG. 3 is an explanatory diagram of a constant on-time / minimum off-time control loop used in the voltage regulator of FIG. 1. FIG. 2 is a voltage waveform diagram showing a feedback voltage V _FB of the constant on-time voltage regulator of FIG. 1. 1 is a schematic diagram of a constant on-time voltage regulator with a ripple injection control scheme with improved output voltage accuracy according to one embodiment of the present invention. FIG. 6 is a schematic diagram of a constant on-time voltage regulator with a ripple injection control scheme with increased output voltage accuracy according to an alternative embodiment of the present invention. 6 is a circuit diagram of an operational transconductance amplifier and clamp circuit that can be incorporated into the constant on-time voltage regulator of FIG. 4 (without a clamp circuit) and FIG. FIG. 6 is a circuit diagram of a clamp circuit that can be incorporated into the constant on-time voltage regulator of FIG. 5. 1 is a logic circuit diagram of an on-time / off-time control circuit for realizing a multi-mode on-time / off-time control scheme in a buck switching type voltage regulator according to one embodiment of the present invention. 1 is a schematic diagram of a maximum on-time control circuit according to one embodiment of the present invention. FIG. FIG. 10 is a timing chart showing the operation of the maximum on-time control circuit of FIG. 9. 3 is a schematic diagram of a maximum on-time control circuit according to another embodiment of the present invention. FIG.

Explanation of symbols

10, 40, 50 buck switching voltage regulator system 100, 400, 500 back switching voltage regulator 102, 104, 106, 108, 110, 112;
402, 404, 406, 408, 410, 412;
502, 504, 506, 508, 510, 512 Terminal 114, 414, 514 Output voltage V _OUT node 116, 416, 516 Load 120, 420, 520 Ripple injection circuit 126, 426, 526 Error comparison circuit 128 On timer 130 Off timer 132 logic circuit 134 drive circuit 432, 532 control circuit M1, M2 transistor power switch 136, 436, 536 reference voltage V _REF generation circuit 206 turn on switch M1 for a certain on time 208 turn off switch M1 for a minimum off time

Claims (23)

The first switch and the second switch are controlled using a constant on-time / variable off-time feedback control loop configured to receive an input voltage and to generate a switching output voltage at the switch output node configured in an integrated circuit. A back-switching type voltage regulator, wherein the switch output node is connected to an LC filter circuit externally attached to the integrated circuit, and an adjusted voltage having a substantially constant magnitude, that is, a feedback voltage node is connected to the output node. In a buck switching voltage regulator that generates a regulated voltage that is fed back to a voltage divider inside the buck switching voltage regulator that generates a return voltage,
A first input terminal connected to receive the feedback voltage, a second input terminal connected to receive the first reference voltage, the feedback voltage and the first reference voltage A high output impedance amplifier having an output terminal producing a first output voltage representative of the difference between
A first input terminal connected to receive a second reference voltage; a second input terminal connected to receive the first output voltage of the amplifier; and the buck switching voltage regulator. An error comparator that produces an output voltage that controls a constant on-time / variable off-time control loop of the detector;
A first capacitor and a first resistor formed in the integrated circuit and inserted in series between the switch output node and the output terminal of the amplifier;
A second capacitor connected between the output node and the output terminal of the amplifier, wherein the first capacitor and the first resistor are associated with the switching output voltage and of the second capacitor. Buck switching that generates a ripple voltage signal having a magnitude that is a function of a capacitance value and supplies the ripple voltage signal to the output terminal of the amplifier for use in the constant on-time / variable off-time feedback control loop. Type voltage regulator.   2. The buck switching voltage regulator according to claim 1, wherein the amplifier includes an operational transconductance amplifier having a small transconductance value.   3. The buck switching voltage regulator according to claim 2, wherein the amplifier has a high DC gain and an AC gain of 1.   2. The buck switching voltage regulator according to claim 1, wherein the amplifier is formed in the integrated circuit.   2. The buck switching type voltage regulator according to claim 1, wherein the amplifier is formed outside the integrated circuit.   The buck switching voltage regulator according to claim 1, wherein the second capacitor is formed outside the integrated circuit.   2. The buck switching voltage regulator according to claim 1, wherein the second capacitor is formed in the integrated circuit. 7. The buck switching voltage regulator according to claim 6, wherein the LC filter circuit includes a first inductor and an output capacitor, and the second capacitor has a capacitance value proportional to an equivalent series resistance (ESR) value of the output capacitor. .   9. The buck switching voltage according to claim 8, wherein the second capacitor has a large capacitance value when the ESR value of the output capacitor is large, and has a small capacitance value when the ESR value of the output capacitor is small or zero. Adjuster. The buck switching voltage regulator according to claim 9, wherein the second capacitor has a capacitance value in a range of 220 pF to 2 u F.   The buck switching voltage regulator according to claim 9, wherein the magnitude of the ripple voltage signal is small when the capacitance value of the second capacitor is large and large when the capacitance value is small.   8. The buck switching voltage regulator of claim 7, wherein the LC filter circuit includes a first inductor and an output capacitor, and the second capacitor has a capacitance value associated with a range of equivalent series resistance (ESR) of the output capacitor. vessel.   2. The buck switching voltage regulator according to claim 1, wherein the ripple voltage signal is a divided output voltage of the switching output voltage. A back-switching voltage regulator that controls a first switch and a second switch using a constant on-time / variable off-time feedback control loop so as to receive an input voltage and generate a switching output voltage at a switch output node. The switch output node is connected to an LC filter circuit, and a regulated voltage having a substantially constant magnitude is generated at the output node, that is, an internal voltage of the buck switching voltage regulator that generates a feedback voltage at the feedback voltage node. In a method in a back-switching voltage regulator that is adapted to produce a regulated voltage that is fed back to the voltage regulator,
Supplying the feedback voltage to a first input terminal of a high output impedance amplifier;
Supplying a first reference voltage to a second input terminal of the amplifier;
Generating a first output voltage representative of a difference between the feedback voltage and the first reference voltage at an output terminal of the amplifier;
Generating a ripple voltage signal from the switching output voltage;
Injecting the ripple voltage signal into the output terminal of the amplifier for use in a constant on-time / variable off-time feedback control loop;
Supplying the first output signal of the amplifier including the injected ripple voltage signal to a first input terminal of a comparator;
Supplying a second reference voltage to a second input terminal of the comparator;
Adjusting the magnitude of the ripple voltage signal at the output terminal of the amplifier using a capacitive voltage divider. Supplying the feedback voltage to the first input terminal of the high output impedance amplifier includes supplying the feedback voltage to the first input terminal of the operational transconductance amplifier having a low transconductance value;
The step of supplying the first reference voltage to the second input terminal of the amplifier includes supplying the first reference voltage to the second input terminal of an operational transconductance amplifier having a low transconductance value. Item 15. The method according to Item 14.   The method of claim 15, wherein the amplifier comprises a high DC gain and an AC gain of 1. A first capacitor and a first resistor, that is, the ripple voltage is generated from the switching output voltage between the switch output node and the output terminal of the amplifier, and the ripple voltage signal is output from the output of the amplifier. 15. The method of claim 14, further comprising the step of inserting a first capacitor and a first resistor to be injected into the terminal in series connection.   The method of claim 17, wherein the ripple voltage signal is a divided output of the switching output voltage. Adjusting the magnitude of the ripple voltage signal at the feedback voltage node with a capacitive voltage divider includes:
18. The method according to claim 17, further comprising providing a second capacitor between the output voltage node and the output terminal of the amplifier, that is, a second capacitor whose capacitance value determines the magnitude of the ripple voltage signal. . The method of claim 19, wherein the LC filter circuit includes a first inductor and an output capacitor, and the second capacitor has a capacitance value proportional to an equivalent series resistance (ESR) value of the output capacitor.   The step of providing the second capacitor provides a second capacitor having a large capacitance value when the ESR value of the output capacitor is large, and a capacitance value when the ESR value of the output capacitor is small or zero. 21. The method of claim 20, comprising providing a small second capacitor. The method of claim 21, wherein the second capacitor has a capacitance value in the range of 2.2 u F from 220pF.   20. The method of claim 19, wherein the magnitude of the ripple voltage signal is small when the capacitance value of the second capacitor is large and large when it is small.

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